CN1078026C - 接收数据信号大小的确定方法、确定装置及数据提取装置 - Google Patents

接收数据信号大小的确定方法、确定装置及数据提取装置 Download PDF

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CN1078026C
CN1078026C CN93114837A CN93114837A CN1078026C CN 1078026 C CN1078026 C CN 1078026C CN 93114837 A CN93114837 A CN 93114837A CN 93114837 A CN93114837 A CN 93114837A CN 1078026 C CN1078026 C CN 1078026C
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林赛A·韦费，Jr
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Abstract

一种接收数据信号大小的确定方法、确定装置及数据提取装置。确定装置包含：接收数据信号产生第一乘积抽样和第二乘积抽样的乘法器：和根据两抽样产生数据信号大小的值的加法器。确定方法包含：第一乘积抽样步骤；第二乘积抽样步骤；和数据信号大小的合成值的步骤。数据提取装置包含接收机和一个或多个解调器。每个解调器包含：两种提取I和Q分量的装置和一个或多个点积装置。每个点积装置包含：乘积装置和两种加法装置。

Description

接收数据信号大小的确定方法、确定装置及数据提取装置
本发明涉及扩谱通信系统，尤其涉及通过测定与通信系统的基准信号同相位的那部分数据信号的大小来解调通信信号中所用的方法和装置。本发明进一步涉及产生包含在通信信号中的导频信号和数据信号间的点积。
在发送数字信号的通信系统中，为从所接收的信号中取出数据提出了各种解调方案。特别是，应用四相移相键控(QPSK)调制技术的系统，当解调接收信号时，不是立即容许取出为多径信号组合完成信号加权所必须的信息。
因此，本发明的目的是在解调已调信号的过程中规定一种相对于所接收的基准的信号加权方法。
本发明是一种方法和装置，在以数字方式调制数字数据的通信系统中，用于解调发送信号以便提取发送的数字数据。更准确地说，本发明是用于数字通信系统，在该系统中，数据信号及导频信号两者都以双相移相键控调制在载频上并且以四相移相键控(QPSK)方式加以扩展。在接收机端，通过产生导频和数据信号相位矢量之间的点积从所接收的信号中提取数据。与导频信号相位矢量(数据的相位基准)同相的数据信号相位矢量分量的大小由这些信号矢量的点积或相位投影确定。尤其是，这些信号矢量的点积为同相导频分量(PI)乘以同相数据分量(DI)的积加上正交相位导频分量(PQ)乘以正交相位数据分量(DQ)的积。
在典型现实中本发明体现在通信系统的接收机中该接收机接收各自定义相应的相位矢量的导频信号和数据信号。每个接收信号矢量用它的I和Q分量来表示。本发明的电路从信号矢量分量确定与导频信号矢量同相的数据信号矢量的大小。
确定电路包含一乘法器电路，它用来接收数据信号I分量的抽样和导频信号I分量的抽样，将所接收的数据信号I分量的抽样与导频信号I分量的抽样相乘，并提供第一乘积抽样。该乘法器电路也用来接收数据信号Q分量的抽样和导频信号Q分量的抽样，将所接收的数据信号Q分量的抽样与导频信号Q分量的抽样相乘，并提供第二乘积抽样。该确定电路也包含一加法器电路，它用来接收第一和第二乘积抽样，将两者相加，并提供一个代表与导频信号矢量同相的数据信号矢量幅度的数值的合成抽样。
该确定电路也可包括存贮电路和选择电路。该存贮电路用于存贮数据信号I分量抽样、数据信号Q分量抽样、导频信号I分量抽样和导频信号Q分量抽样。选择电路用于接收所存贮的数据信号I和Q分量抽样，导频信号的I和Q分量的抽样和选择信号。该选择电路响应选择信号的第一状态向乘法器电路提供数据信号，和导频信号的I分量的抽样的输出，并响应选择信号的第二状态向乘法器电路提供数据信号Q和导频信号Q分量的抽样的输出。
从所接收的信号提取数据的提取装置，该提取装置包含：接收信号的接收机，所述信号包含一个或多个基站发出的同样发射信号的一个或多个多径传播，发射信号包含数据信号和基准信号；并联耦连于接收机的一个或多个解调器，每个解调器工作于多径传播中的一特定传播上，解调器的每一个包含：从特定传播提取数据信号的同相(I)和正交相位(Q)分量的装置，和从特定传播提取基准信号的同相(I)和正交相位(Q)分量的装置；每个耦连于对应的一解调器的一个或多个点积装置，为每个特定传播确定与所述基准信号同相的所述数据信号的相应大小，每个点积装置包含：产生数据和基准信号的I分量的积提供第一中间值、和产生数据和基准信号的Q分量的积提供第二中间值的乘积装置，和将第一和第二中间值相加以提供第一数据输出的第一加法装置；和对第一数据输出进行相加的第二加法装置。
下面结合附图进行详细描述将会更清楚地认识到本发明的特征、目的和优点，其中同样的标号前后标识一致。
图1为实现本发明的点积处理方法的接收机的典型方框图；
图2为所接收的导频和数据信号的典型矢量表示；
图3为从所接收的I和Q信号分量提取导频和信息数据的数字接收机和相关电路的典型方框图；
图4为QPSK信号空间的典型图；
图5为图3接收机中使用的点积电路的功能框图；和
图6表示实现图3的点积电路的示例框图。
在已转让给这里的受让人的美国专利第5,103,459号题为“码分多址联接蜂窝电话系统中形成信号波形的方法和装置”中，揭示了一种发送数字已调信号的调制方案，这里将其说明书作为参考收编。这种调制方案在网孔至移动站的线路中使用一种与数据信号一起发送的导频信号，它用作接收解调器的相位基准。导频信号的这种用途是众所周知的，并在题为“使用卫星或地面转发器的扩展频谱多址联接通信系统”的美国专利第4,901,307号中进一步加以揭示，该专利也转让给这里的受让人，这里将其说明书作为参考收编。
在上述美国专利第5,103,459号中揭示了一种用于解调被发送的QPSK扩展导频和数据信号的接收机。该接收机如美国专利第5,109,390号题为“码分多址联接蜂窝电话系统中的分集式接收机”所进一步揭示的那样具有多径接收能力，该专利也转让给这里的受让人，这里的其说明书作为参考收编。
图1以框图形式表示了如美国专利第5,103,459号中所揭示的用于接收和解调基站发送波形的接收机的基本构成。在图1中，基站发送信号由天线10接收并供给包含模拟接收机12和数字接收机14的分集式RAKE接收机。由天线10所接收并供给模拟接收机12的信号可以包含同一基站发送信号的多径传播、包含供单个或多个远程接收机用的导频信号和数据信号。模拟接收机12，在典型实施例中构成QPSK调制解调器和降频变频器，并把所接收的信号数字化成复合的I和Q分量。把该合成的I和Q分量供给数字接收器14以便解调。然后把解调数据供给数字电路16以便组合、去交错和解码。控制器12使用某些数据在数字接收机14中设定某些解调参数，这些将在下面加以详细讨论。
从模拟接收机12输出的每个I和Q分量可包含同一导频和相应数据信号的多径传播。在数字接收机14中，某些多径传播的发送信号，按照搜索接收机14a与控制器18给合所进行的选择，每一个由称为“手指”(finger)的不同的多数据接收机或解调器14b—14d所处理。虽然在该例子中仅描述三个数据解调手指(解调器14b—14d)，但应当理解，使用更多或更少的手指也是可以的。通过去扩展，每个手指从复合的I和Q分量中为所选路径提取每个导频信号和数据信号的I和Q分量。
每个手指的导频信号的I和Q分量形成一个导频信号矢量(PI、PQ)。同样，每个手指的数据信号的I和Q分量形成一个数据信号矢量(DI、DQ)。由路径的每个导频信号和数据信号的这些I和Q分量可计算出与导频信号矢量同相的数据信号矢量分量的大小。
图2显示导频信号和一数据信号的典型矢量表示。在图2中，用于分集式RAKE接收机的一个手指的导频信号和数据信号的去扩展(despread)的I和Q分量分别定义IQ构象中的导频信号矢量20和数据信号矢量22。通常导频信号以比数据信号更强的信号强度进行发送，就这一点而论导频信号矢量20的大小比所接收的数据信号矢量22更大。而且，由于导频信号矢量比数据信号矢量强得多，所以它可用作精确的相位基准供信号处理之用。
在发送过程中，发送的导频和数据信号通过同样路径到达接收机。在没有噪声情况下，导频和数据信号矢量方向一致且处于相互相关的相位角π/4、-π/4、3π/4或-3π/4当中的一个相位角上。然而由于信道噪声，所接收的信号可能偏离发送相位角。在本发明的典型实施例中，进一步把导频信号低通滤波以除掉噪声和数据，而数据信号则依然没有被滤波，于是当存在噪声时，则在导频和数据信号矢量之间形成一个以导频作为精确的相位基准的相位差θ。应当注意，如图2所示的信号矢量，在导频和数据矢量之间存在一相位差。
列出的点积，也称为导频信号矢量20和数据信号矢量22的标积，在多解调器或多手指分集式接收机中特别有利于从所接收的信号中提取数据。在这类接收机中，把几个手指进行分配以便解调来自几个不同路径或信号源的信号。在每个手指中，通过将数据矢量投影到导频矢量上用点积求出与导频信号矢量同相的数据信号矢量的分量大小。在形成导频和数据矢量之间的点积的过程中，数据上的正交噪声被除掉。
在多手指分集式接收机中，有效的组合，由每个手指产生的数据点积也用来加权于该数据。于是，借助于组合前的导频信号的幅度，可用点积来估测该数据。如果输入信号没有与数据正交，且总输入功率保持在某个设定点上，导频信号的幅度正比于手指的信噪比(SNR)的平方根。于是按照“微波移动通信”一书(1974年，纽约John Wiley&Sons书局出版)中的第313—319页上的“最大比率组合”一文所述，可获得最佳组合。
导频信号矢量P和数据信号矢量D之间在IQ座标空间中的点积可用等式(1)表示：
P·D＝|P||D| cos θ    ……(1)
其中θ为P和D矢量之间的夹角。
如图2所示，矢量20和22之间的点积，按等式(1)计算产生叠加在矢量20上的矢量分量24。
应当理解，等式(1)按矢量分量形式可表达为等式：
P·D＝PIDI＋PQDQ       ……(2)
其中PI和PQ分别为导频矢量P的I和Q分量；而DI和DQ分别为数据矢量D的I和Q分量。
在处理导频和数据I和Q分量的过程中，研究由等式(1)表达的点积，不但能得到投影而且得到换算。通过研究等式(2)的表达式，很容易在数字应用中实现点积。单一的乘法和累加单元就能三步完成这种操作以便减少硬件的复杂性。
图3进一步详细显示图1的数字接收机14部分和数字电路16。在图3中，来自模拟接收机12的复合I和Q信号抽样加到每个数据解调手指14b—14d。为讨论起见，仅详细说明数字解调手指之一(手指14b)，其它手指具有同样结构和功能。指定每个手指14b—14c对通过不同路径到达用户接收机的发送信号进行解调，因而在解调过程中使用至少相隔一个PN时隙稍有差别的定时。
复合I和Q分量信号抽样(每个为多位值)输入给QPSK去扩展器30。QPSK去扩展器30也从导频PN序列发生器32接收导频PN序列PNI和PNQ。导频PN序列发生器32按照序列定时和由控制器(图1)18所提供的状态输入(未图示)所产生的PN序列PNI和PNQ与在发射机中所使用的PNI和PNQ相同。控制器18一般由微处理器构成并包括适当的存贮器和程序指令。
在典型的实施例中，以抽样的速率把I和Q分量信号抽样供给QPSK去扩展器30，该速率相当于八倍PN序列的时隙速率(chiprate)。然而应当理解，也可以以任何大于PN序列时隙速率提供抽样。在典型实施例中，PN时隙速率为1.2288Mcps，它比数据符号速率19.2Ksps大得多。
QPSK去扩展器30除掉复合I和Q分量信号抽样上的PN扩展以便由此提取复合I和Q分量抽样。为了理解去扩展器30的工作，有必要理解典型发送调制方案、BPSK调制和QPSK扩展对导频和数据信号具有的作用。图4表示了I和Q扩展信号的调制构象。通常在载频中使用无相移或相移180°代表两个数据状态(即“0”或“1”)来发送BPSK信号。在为BPSK调制方案的QPSK扩展规定同一数据位的两个型式时(其中没有I或Q扩展信号输入)，I/Q输出信号具有信号空间坐标(0，0)或(1，1)。由于QPSK扩展工程中，I和QPN序列的作用，如图4所示，合成信号具有四个相位中的一个。下面的表I表明作为I和Q扩展的结果在坐标(0，0)或(1，1)出现的数据之间的对应关系和反时针旋转。
            表I
   IPN    QPN 旋转角度
    0011     0101     0°270°90°180°
应当进一步理解，在典型的调制方案中，发送调制方案采用FIR滤波信号。为了FIR滤波，I和QPN扩展导频和数据的数值“0”和“1”分别被转换成数值“+1”和“-1”。滤波后，抽样从数字形式变换成模拟形式用于载波调制。
在接收和解调已调载波的时候，把复合I和Q信号抽样加到去扩展器30。虽然从为去扩展器30而设的导频PN序列发生器32引出的PN时隙为“0”和“1”值，但这些数值被去扩展器30理解为“+1”和“-1”值。由于这样理解的结果，I和Q分量信号抽样的符号必须根据如表II中表明的PN值而改变。为了正确地改变I和Q值的符号，需要考虑QPSK波形的相位角。下面的表II表明了由PN位引起的接收信号坐标的相应顺时针(CW)或反时针(CCW)旋转。因此相对于I和Q输入的I和Q输出依据表II决定。
                 表II
  IPN   QPN 旋转角 IouT  QouT
   0011    0101   0°90CCW90CW180°  IIN-QINQIN-IIN  QINIIN-IIN-QIN
作为例子，人们可研究输入数据的全零(“0”)序列。于是未扩展的数据具有如图4所示的信号坐标(0，0)。应用表I的关系，数据被扩展为图4所示的四个IQ矢量之一。把表II所示旋转应用于去扩展数据序列的过程中，每个IQ信号矢量回转到对应于一个零的第一象限，即坐标(0，0)。
I和Q分量抽样分别从QPSK去扩展器30输出到数字滤波器34和36，在那里信号被数字滤波。滤波器34和36通常构成一个简单的具有反馈系数为(N－1)/N的一阶滤波器，在典型实施例中N＝64。从波滤器34和36输出的已滤波的I和Q信号抽样为导频信号的I和Q分量的抽样并称为导频I(PI)和导频Q(PQ)抽样。导频I和导频Q抽样被加到点积电路38，它是数字电路16(图1)的一部分。
应当理解，在为这例子所研究的调制方案中，所发送的导频信号使用全零Walsh码作为导频信号，它是用I和QPN扩展序列加以PN扩展。就使用全零Walsh码而论，PN扩展导频信号与I和QPN扩展序列自身是相同的。因此，通过除掉复合I和Q分量信号上的PN扩展和滤波，就能再现全零导频。应当理解，其它任何一种Walsh码都可用作导频信号。应当进一步理解，对于导频信号的应用，一个预定的输入可用一个Walsh序列复盖以供发送之用。当接收时，用下面所描述的与数据再现有关的方法从去扩展信号中除掉Walsh复盖，以便再现原来的输入。
为了再现数据，I和Q分量也分别从QPSK去扩展器30输出到数字混合器40和42，它们可构成模2加法器或异门。数字混合器40和42也从Walsh序列发生器44接收一个Walsh序列。该Walsh序列与指定给发射机中的该信道的Walsh序列是相同的，并且按照由控制器18输入的序列分配(未图示)加以选择。在典型实施例中，该Walsh序列的时隙速率(chip rate)也是1.2288Mcps。数字混合器40和42完成Walsh时隙序列和相应各输入I和Q分量抽样之间的模2相加。已去扩展而且此刻没有被复盖的I和Q分量抽样从数字混合器40和42输出去，在那里分别把它们供给累加器46和48。累加器46和48分别累加I和Q分量抽样，直到一个码元时间过完，在典型实施例中，该码元时间相当于64个抽样或1/19200秒。累加器46、48的输出是以19200码元/秒的码元速率进行，并且是相应的码元数据I和Q，在本文中称其为数据I(DI)和数据Q(DQ)抽样。数据I和数据Q抽样也加到点积电路38。其次在数据输出之后把累加器46、48清零或置位，以便累加下一批抽样。
每个其它解调手指14c—14d也提供各自路径的导频I和Q、及数据I和Q抽样给各自的点积电路50和52。点积电路38、50和52每个都完成关于所接收的导频I和Q及数据I和Q抽样的点积运算，以便提供反映出与该路径的导频同相的码元期间的数据信号幅度的相应标量值。码元抽样数据是从每个点积电路38、50和52输出到码元组合器54。每个点积电路38、50和52的输出可用舍位器(a bit truncator)(未图示)截掉码元抽样值的较低位以便减少处理的技术要求。组合器54将输入的码元抽样相加并提供一个输出码元抽样。组合器54的输出也可用舍位器(未图示)舍掉码元抽样值的较低位以便减少位处理的技术要求。
组合器54的输出加到数字混合器56。当需要时，用户PN序列也作为输入加到数字混合器例如当用户PN用于对所发送的码元流进行扰码时。用户PN发生器58，在控制器18的控制下(输入未图示)，产生用于对所发送的码元流进行扰码的相同的用户PN序列，数字混合器56可以如前面所讨论的那样简单地使之形成为一组逻辑异门。通常用户PN序列是以码元速率传送或计时。
把用户PN已解扰的码元抽样供给去交错器(deinterleaver)60，在那里使已被交错的码元的帧除去交错。然后，把已解错的码元供给解码器62，用于对代表前向纠错(FEC)编码数据的码元进行解码。通常使解码器62构成一个维特比解码器。
图5以功能框图形式图示包含图3的点积电路38、50和52的部件。在图5中，数据I抽样和对应的导频I抽样作为输入加到数字乘法器70，而数据Q抽样和对应的导频Q抽样作为输入加到数字乘法器72。在乘法器70中数据I抽样和导频I抽样之间相乘的积作为输入加到数字加法器74。同样，在乘法器72中数据Q抽样和导频Q抽样之间相乘的积作为另一个输入加到数字加法器74。加法器74将两个输入值相加以便提供一个输出码元抽样，用于与来自其它路径的已解调码元相结合。该码元抽样值代表由导频信号强度换算的与导频矢量同相的数据矢量值。
图6提供了图3的点积电路38的典型实现，包括点积电路50和52在内都具有相同的结构。图6的电路以数字电路形式实现上面提出的等式(1)和(2)。在图6中，数据I和数据Q抽样和相应的导频I和导频Q抽样分别加到锁存器80、82、84和86，在那里为响应以码元速率提供的锁存起动信号而把它们贮存在其中，由于这些抽样当中的每一个都是多位抽样，所以锁存器80—86每一个都由一连串锁存元件(未图示)构成，每个元件贮存一个抽样的不同位。
贮存在每个锁存器(80和82)中的I、Q值分别加到2∶1多位输入多路调制器88的I和Q输入端。同样，每个锁存器(84和86)的输出分别加到2∶1多位输入多路调制器90的I和Q输入端。一个I/Q选择信号也加到多路调制器88和90。多路调制器88和90响应I/Q选择信号以便在半个码元周期中提供一个来自其中一个输入(例如I输入)的输出，而在另外半个码元周期中提供一个来自另外的其中一个输入(例如Q输入)的输出。
从多路调制器88和90输出的选择数据和导频抽样加到串联的相乘和累加元件92，它包含数字乘法器94和累加器96。元件92在每个码元周期中依次用乘法器94将数据I抽样乘以导频I抽样，用乘法器94将数据Q抽样与导频Q抽样相乘，并在累加器96中使这些乘积相加以提供代表与导频同相的码元的幅度的码元抽样值。根据码元时钟输入，每一码元周期一次把在元件92中产生的数值从那里除掉。
应当看到，可以设计出点积电路的种种其它数字结构。例如，不用多路复用那些要乘在一起的数值，而是将数据I与导频I和数据Q与导频Q用于分立式乘法器中的个别乘法器中。
上面描述的较佳实施例使擅长技术的任何人能够制造或使用本发明。对这些实施例作种种修改对擅长技术的那些人来说是显而易见的，在本文中确定的一般原则可应用于其它实施例而不需创造性的劳动。因此，本发明并不规定限于在本文中所显示的实施例，但规定限于与本文所揭示的新颖特征和原则一致的最宽的范围。

Claims (14)

1.一种确定扩谱通信系统接收机中与导频信号同相的数据信号大小的确定装置，所述接收机在公共信号传输通道上接收该导频信号和数据信号，每个信号具有同相(I)和正交相位(Q)的分量，其特征在于，所述确定装置包含：
连接接收数据信号I、Q分量抽样和导频信号I、Q分量抽样并将所述数据信号I分量抽样和导频信号I分量抽样相乘产生第一乘积抽样、和将所述数据信号Q分量抽样和导频信号Q分量抽样相乘产生第二乘积抽样的乘法器；和
连接接收和相加所述第一和第二乘积抽样以产生代表与所述导频信号同相位的所述数据信号大小的值的加法器。
2.如权利要求1所述的确定装置，其特征在于，可进一步包含：
存贮所述数据信号I、数据信号Q、导频信号I、和导频信号Q分量抽样的存贮装置；和
接收所述被存贮的数据信号I和Q分量抽样、所述导频信号I和Q分量抽样、和一选择信号的选择装置，该选择装置响应所述选择信号的第一状态将所述数据信号和导频信号的I分量抽样加给所述乘法器，和响应所述选择信号的第二状态将所述数据信号和导频信号的Q分量抽样加给所述乘法器。
3.如权利要求1所述的确定装置，其特征在于，其中所述数据和导频信号相互同步地在所述公共信号传输通道上发送。
4.在一通信系统接收机中，一种确定和基准信号相位相关的预定相位空间中与导频信号同相的数据信号大小的方法，所述接收机接收作为所述基准信号的所述导频信号和所述数据信号，其每个信号具有同相位(I)和正交相位(Q)的分量，其特征在于，所述方法包含步骤为：
产生所接收的数据信号I分量抽样和导频信号I分量抽样的积以提供合成的第一乘积抽样；
产生所接收的数据信号Q分量抽样和导频信号Q分量抽样的积以提供合成的第二乘积抽样；和
将所述第一和第二乘积抽样相加，以提供代表与所述导频信号同相的所述数据信号大小的合成值。
5.如权利要求4所述的方法，其特征在于，可进一步包含步骤为：
存贮所述数据信号和导频信号的I、Q分量的各个抽样；
提供所述被存贮的数据信号和导频信号的I分量抽样，用以相互同步相乘；和
提供所述被存贮的数据信号和导频信号的Q分量抽样，用以相互同步相乘。
6.如权利要求4所述的方法，其特征在于，所述通信系统包含无线电话/数据通信系统，其中远端用户位于众多蜂窝区中，并用码分多址(CDMA)扩谱型通信信号至少与一个基站进行信息信号通信。
7.一种通信系统中从所接收的信号提取数据的提取装置，其特征在于，该提取装置包含：
接收信号的接收机，所述信号包含一个或多个基站发出的同样发射信号的一个或多个多径传播，所述发射信号包含数据信号和基准信号；
并联耦连于所述接收机的一个或多个解调器，每个解调器工作于所述多径传播中的一特定传播上，所述解调器的每一个包含：
从所述特定传播提取数据信号的同相(I)和正交相位(Q)分量的装置，和
从所述特定传播提取基准信号的同相(I)和正交相位(Q)分量的装置；
每个耦连于对应的一解调器的一个或多个点积装置，为每个特定传播确定与所述基准信号同相的所述数据信号的相应大小，所述每个点积装置包含：
产生所述数据和基准信号的所述I分量的积提供第一中间值、和产生所述数据和基准信号的所述Q分量的积提供第二中间值的乘积装置，和
将所述第一和第二中间值相加以提供第一数据输出的第一加法装置；和
对所述第一数据输出进行相加的第二加法装置。
8.如权利要求7所述的提取装置，其特征在于，可进一步包含：
存贮所述数据信号的所述I和Q分量的第一装置；
存贮所述基准信号的所述I和Q分量的第二装置；
耦连于所述第一装置和所述乘积装置之间的第三装置，它响应一选择信号，并当所述选择信号为第一状态时将所述数据信号的I分量加给所述乘积装置，和当所述选择信号为第二状态时将所述数据信号的Q分量加给所述乘积装置；和
耦连于所述第二装置和所述乘积装置之间的第四装置，它响应一选择信号，并当所述选择信号为第一状态时将所述基准信号的I分量加给所述乘积装置，和当所述选择信号为第二状态时将所述基准信号的Q分量加给所述乘积装置。
9.如权利要求8所述的提取装置，其特征在于，所述第一装置包含：
第一对锁存器，每一个连接接收所述数据信号的所述I和Q分量之一，且有一输出端；和
所述第二装置包含：
第二对锁存器，每一个连接接收所述基准信号的所述I和Q分量之一，且有一输出端。
10.如权利要求9所述的提取装置，其特征在于，所述第三装置包含：
第一多路复用器，它具有一选择信号输入端，各耦连于所述第一对锁存器的输出端的一对输入端，和耦连于所述乘积装置一输入端的第一输出端；和
所述第四装置包含：
第二多路复用器，它具有一选择信号输入端，各耦连于所述第二对锁存器的输出端的一对输入端，和耦连于所述乘积装置第二输入端的第二输出端。
11.如权利要求7所述的提取装置，其特征在于，所述乘积装置可包含：
连接接收所述数据和基准信号的I分量的第一乘法器，它具有一耦连于所述第一加法装置的乘积输出端；和
连接接收所述数据和基准信号的Q分量的第二乘法器，它具有一耦连于所述第一加法置的乘积输出端。
12.如权利要求2所述的提取装置，其特征在于，所述第一加法装置包含具有一对输入端的加法器，所述输入端的每一个耦连于所述第一和第二乘法器的所述乘积输出端之一。
13.如权利要求7所述的提取装置，其特征在于，所述通信系统包含无线电话/数据通信系统，该系统中，远端用户位于众多蜂窝区中并用码分多址(CDMA)扩谱型通信信号与至少一个基站进行信息信号的通信。
14.如权利要求7所述的提取装置，其特征在于，所述数据和基准信号相互同步被发送。
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EP0671082B1 (en) 1999-05-26
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