CN107465398B - Series-connection dual-port negative impedance converter for signal envelope distortion compensation - Google Patents
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Abstract
The invention discloses a series two-port negative impedance converter for signal envelope distortion compensation. The improved negative impedance converter based on the floating type differential structure is characterized in that a three-port network structure is improved into a two-port network structure, namely, a differential input positive electrode is improved into an input port, a differential input negative electrode is improved into an output port, the original differential output port is removed, the two-port negative impedance converter with the series characteristic is formed, the non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter is adjusted through resistors connected with the positive and negative input ports of an operational amplifier and impedance connected with the operational amplifier, and accordingly envelope dispersion compensation is conducted on square wave signals after being distorted by a high-pass filter. The invention overcomes the defect that the traditional negative impedance converter can only be connected in parallel, has the characteristics of small size, simple structure and high-precision adjustment, and realizes the adjustment of the transmission coefficient of the circuit. The method has application prospect in the dispersion compensation of circuits such as radio frequency transceivers and the like.
Description
Technical Field
The invention relates to a negative impedance converter, in particular to a series two-port negative impedance converter for signal envelope distortion compensation.
Background
Distortion is inevitably generated during signal transmission. Whether in electronic circuits, radio frequency microwave circuits, optical fiber communication, or in spatial signal transmission, the signal will be distorted to different degrees as long as it has a bandwidth. The distortion is a main reason for suppressing the transmission distance, transmission accuracy and transmission quality in the signal transmission process. Among the many variants, the most common and most important is group delay distortion. In signal transmission, group delay refers to a phase response that exhibits a negative slope for a given frequency, thereby producing a delay relative to the original signal waveform envelope. When different frequency components in the signal are subjected to nonlinear response (dispersion), the envelope of the signal is distorted, which is called group delay distortion. The group delay distortion causes the signal bandwidth to be widened, the error rate to be increased, the channel noise to be increased, the synchronism to be poor, the transmission distance to be shortened and the like, and the serious distortion even causes the signal to be incapable of being demodulated. In an electronic circuit, the dispersion of a signal is mainly caused by the nonlinear impedance characteristic of a Foster device, and how to counteract the nonlinear response of the Foster device is the core of suppressing group delay distortion.
The research on the negative impedance converter in the scientific community has a long history, since the conception of the non-Foster device is proposed by Rodolph Sanon in 1920, various forms of non-Foster devices have been provided, and a great deal of research on the working stability of the non-Foster devices has been carried out, at present, the realization of the non-Foster devices is realized on the basis of the principle of the negative impedance converter, a circuit is constructed by using a transistor active device, and equivalent circuit parameters are realized at an output port, for example, L inwil firstly realizes a grounding type negative impedance changer by using a transistor in 1953, Antoniou realizes a floating type differential structure negative impedance converter by using a differential input circuit structure in 1972, and the circuit structure of the floating type differential structure negative impedance converter is shown in figure 1 and comprises two operational amplifiers, four independent resistors R connected with positive and negative input ports of the two operational amplifiers and an impedance ZLAnd the two ends of the circuit structure are respectively connected with the negative input port and the positive input port of the two operational amplifiers. The positive pole of the differential input is led out from the positive input port of the first operational amplifier and the connected resistor, the negative pole of the differential input is led out from the negative input port of the second operational amplifier and the connected resistor, and the impedance Z isLThe two ends are differential output ports.
Zuiwei a. xu implements 2012 the use of feedback theory to adjust the stability of the negative impedance transformer. Also, much research has been focused on compensating for Foster devices using their non-Foster characteristics (i.e., the slope of the dispersion characteristic curve of the impedance with frequency is negative). As in 2009, the successful application of negative capacitance to a small antenna by Sussman Fort cancels its reactance, expanding the bandwidth and improving the signal-to-noise ratio of the antenna reception; fei Gao realized compensation of the reflection coefficient of artificial dielectric materials using non-Foster devices in 2014.
Up to now, in the field of microwave communications, there have been various methods for compensating impedance values to cancel out the reactance characteristics of circuits, such as compensating for the input impedance of electrically small antennas and artificial dielectric materials using negative impedance transformers. However, the negative impedance converter is limited by the circuit structure of the negative impedance converter, and the negative impedance converter in the work is connected in parallel to the circuit, and then compensates the impedance in the circuit. The negative impedance converter with the floating-ground type differential structure has a complex structure, so that the negative impedance converter is limited to be used in the fields of antennas and artificial materials. The above causes the compensation circuit using the negative impedance converter to stay in compensation for the reflection coefficient at all times.
Disclosure of Invention
In order to solve the problems existing in the background art, the invention aims to provide a series double-port negative impedance converter for signal envelope distortion compensation, so that the series double-port negative impedance converter becomes a double-port negative impedance converter with series characteristics, overcomes the defect that the traditional negative impedance converter can only be connected in parallel, has the characteristics of small size, simple structure and high-precision adjustment, and widens the application range of the negative impedance converter.
The technical scheme adopted by the invention for solving the technical problems is as follows:
the invention is based on the improvement of a floating-earth differential structure negative impedance converter, and improves a three-port network structure into a double-port network structure, namely, the original differential input positive electrode is improved into an input port, the differential input negative electrode is improved into an output port, the original differential output port is removed, so that the double-port negative impedance converter with the series characteristic is formed, and the non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter is adjusted through the resistors connected with the positive and negative input ports of the two operational amplifiers and the impedance connected between the two operational amplifiers, so that the envelope dispersion compensation is carried out on the square wave signal distorted by a high-pass filter.
The dual-port negative impedance converter with the series characteristic comprises a loop circuit structure formed by two operational amplifiers, wherein a positive input port and a negative input port of a first operational amplifier are respectively connected with a first resistor and a second resistor, and the other ends of the first resistor and the second resistor are connected with an output port of a second operational amplifier; meanwhile, the positive and negative input ports of the second operational amplifier are respectively connected with a third resistor and a fourth resistor, and the other ends of the third resistor and the fourth resistor are connected with the output port of the first operational amplifier; one end of the impedance is connected to a first operation amplified negative input port and a second resistor connected with the first operation amplified negative input port, and the other end of the impedance is connected to a second operation amplified positive input port and a third resistor connected with the second operation amplified positive input port;
the input port is led out from a positive input port of the first operational amplifier and a first resistor connected with the positive input port, and forms an input port of a dual-port network with a ground wire; and the output port is led out from the fourth resistor connected with the negative input port of the second operational amplifier and forms an output port of the dual-port network with the ground wire.
The non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter is adjusted through the resistors connected with the positive and negative input ports of the two operational amplifiers and the impedance connected between the two operational amplifiers, the two operational amplifiers are enabled to be in a normal working condition by adjusting the resistance values of the respective resistors connected with the positive and negative input ports of the two operational amplifiers, and the transmission coefficient of the whole circuit is changed by adjusting the impedance value connected between the two operational amplifiers.
The non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter is adjusted through the resistor connected with the positive and negative electrode input ports of the two operational amplifiers and the impedance connected between the two operational amplifiers, and the calculation formula of the transmission coefficient is as follows:
wherein B is the transmission coefficient of the circuit, R is the resistance values of four independent resistors connected with the positive and negative input ports of the operational amplifier, and ZLIs the resistance value of the impedance connected with the operational amplifier, AoIs the gain of the operational amplifier.
The dispersion compensation of the envelope of the square wave signal distorted by the high-pass filter is realized by adjusting the non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter through the resistor connected with the positive and negative input ports of the two operational amplifiers and the impedance connected between the two operational amplifiers, and then cascading the non-Foster characteristic with the high-pass filter with the Foster characteristic to offset the dispersion characteristic of a Foster device, and performing the dispersion compensation of the envelope of the square wave signal distorted by the high-pass filter.
Compared with the background technology, the invention has the following beneficial effects:
the double-port negative impedance converter with the series characteristic overcomes the defect that the traditional negative impedance converter can only be connected in parallel, has the characteristics of small size, simple structure and high-precision adjustment, and realizes the adjustment of the transmission coefficient of a circuit. Meanwhile, the method has an engineering application foundation, and particularly has a wide application prospect in dispersion compensation of circuits such as radio frequency transceivers and the like.
Drawings
Fig. 1 is a circuit configuration diagram of a negative impedance converter of a conventional floating-ground type differential structure.
Fig. 2(a) is a circuit configuration diagram of a two-port negative impedance converter of the series characteristic of the present invention.
FIG. 2(b) is a diagram of the low frequency equivalent circuit of two operational amplifiers of the present invention.
Fig. 3 is a numerical calculation diagram for adjusting the reactance value of the transmission coefficient of the output port by changing the resistance values of four independent resistors R connected to two operational amplifiers according to the transmission coefficient calculation formula of the present invention.
FIG. 4 is a diagram illustrating a method for changing impedance Z connected between two operational amplifiers by a transmission coefficient calculation formula according to the present inventionLThe impedance value of the output port is used for adjusting the numerical calculation graph of the reactance value of the transmission coefficient of the output port.
FIG. 5 shows the present invention using circuit simulation software to change the impedance Z connected between two operational amplifiersLThe impedance value of the output port is used for adjusting a simulation result diagram of the reactance value of the transmission coefficient of the output port.
Fig. 6 is a circuit configuration diagram of the transmission characteristic of the actually measured negative impedance converter according to the present invention.
Fig. 7 is a reactance diagram of the transmission characteristic of the measured negative impedance converter of the present invention.
Fig. 8 is a circuit diagram of a high pass filter in accordance with the present invention.
Fig. 9 is a circuit diagram of a high pass filter of the present invention.
FIG. 10 is a time domain voltage signal diagram collected by the present invention using circuit simulation software after passing 75MHz square waves through a high pass filter and a high pass filter of a cascaded negative impedance converter, respectively.
FIG. 11 is a time domain voltage signal diagram collected after the square wave with the actual measurement frequency of 75MHz passes through a high pass filter and a high pass filter of a cascaded negative impedance converter respectively.
Detailed Description
The invention is further illustrated by the following figures and examples.
The embodiment of the invention and the implementation working process thereof are as follows:
according to the theoretical knowledge of microwave engineering, an S parameter matrix and a transmission coefficient matrix ABCD of the dual-port network can be converted with each other, and the specific calculation formula is as follows:
wherein A represents the application of a voltage V across the 1 port (i.e., input port)1And measuring the open-circuit voltage V on the 2-port (i.e. output port)2B represents the voltage V applied to the 1 port1With measurement of short-circuiting at 2 portsCurrent I2C represents the application of a current I on the 1 port2And measuring the open-circuit voltage V on the 2-port2D represents the application of the current I on the 1 port1And measuring the short-circuit current I on the 2-port2The ratio of (A) to (B); s12Representing the excitation of the 1 port and measuring the ratio of the transmitted wave voltages, S, out of the 2 ports21Exciting the 2-port and measuring the ratio of the transmitted wave voltage, S, coming out of the 1-port11Representing excitation of the 1 port and measuring the ratio of the reflected wave voltages, S, coming out of the 1 port22Indicating that the 2 port is excited and measuring the reflected wave voltage ratio out of the 2 port.
In the field of microwave engineering, the S-parameter matrix of a dual-port network can often be directly obtained by a vector network analyzer. Therefore, the transmission coefficient matrix ABCD of the dual-port network can be obtained by the formulas (1) - (4) only by obtaining the corresponding S parameter matrix.
The circuit structure of the series-characteristic dual-port negative impedance converter of the present invention is shown in FIG. 2(a), and includes a loop circuit structure formed by two operational amplifiers and an impedance ZLAnd the two ends of the circuit structure are respectively connected with the negative input port and the positive input port of the two operational amplifiers. Wherein fig. 2(b) is a low frequency equivalent circuit structure of two operational amplifiers. According to kirchhoff's voltage-current law, the transmission coefficient matrix ABCD of the two-port network can be obtained by the following formula:
N＝(R+2ro)[Uout+Uin+2Ao(Uout-Uin)]+(R+2ro)2(Iout-Iin) (10)
wherein, R is the resistance value of four independent resistors connected with the positive and negative input ports of the operational amplifier, and ZLIs the resistance value of the impedance connected with the operational amplifier, AoFor gain of operational amplifier, Uin，Iin，Uout，IoutThe input voltage, the input current, the output voltage and the output current value of the dual-port network are respectively. U shapeA1And iA1Is the voltage and current value, U, of the output port of the first operational amplifierA2And iA2The voltage and current values of the output port of the second operational amplifier. U shapeZN，UZPIs impedance ZLAnd connecting the voltage value of the negative input port of the first operational amplifier and the voltage value of the positive input port of the second operational amplifier. In the low frequency equivalent circuit structure of the operational amplifier, ridIs the input impedance of the operational amplifier, roIs the output impedance of the operational amplifier, UiFor the voltages of the positive and negative input ports of the operational amplifier, UoIs the output port voltage of the operational amplifier, AodIs transconductance between an input port and an output port of the operational amplifier, iAIs the current at the output port of the operational amplifier.
And (5) obtaining the relationship between the input port voltage and the input port current and the output port voltage and the output port current by simultaneous formulas (5) to (10), thus obtaining a transmission coefficient matrix ABCD matrix. When the input impedance of the operational amplifier is infinite and the output impedance is zero, the parameter B in the transmission coefficient matrix is Uin/IoutCan be expressed as:
by changing the positive and negative input ends of two operational amplifiersResistance R of four independent resistors connected with ports and impedance Z connected between two operational amplifiersLThe non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter can be adjusted, and then the impedance converter is cascaded with a high-pass filter with the Foster characteristic, so that the dispersion characteristic of a Foster device is offset, and the dispersion compensation of the envelope of the square wave signal after being distorted by the high-pass filter is carried out.
The numerical calculation of the reactance value of the transmission coefficient of the output port by changing the resistance values of four independent resistors R connected with the positive and negative input ports of the two operational amplifiers through the transmission coefficient calculation formula (11) is shown in fig. 3. Wherein the impedance ZLThe resistance of (1) is fixed at 10pF, while the resistance of all four independent resistors R varies from 3 Ω to 60 Ω, and all four independent resistors are identical. The reactance value of the transmission coefficient can be continuously adjusted by changing the resistance value R, and the dispersion characteristic curve of the reactance exhibits non-Foster characteristics between 15MHz and 100 MHz.
The invention calculates formula (11) by transmission coefficient, and changes impedance Z connected between two operational amplifiersLThe value of the reactance value for adjusting the transmission coefficient of the output port is calculated as shown in fig. 4. Wherein the four independent resistors R have a fixed resistance of 100 omega and the impedance ZLTo a value of 3pF to 60 pF. By varying the resistance value ZLThe reactance value of the transmission coefficient can be continuously adjusted, and the dispersion characteristic curve of the reactance exhibits non-Foster characteristics between 10MHz and 100 MHz.
The invention utilizes circuit simulation software MultismTMChanging the impedance Z connected between the two operational amplifiersLThe results of the simulation of the reactance value to adjust the transmission coefficient of the output port are shown in fig. 5. The operational amplifier adopts a double-channel OPA2695 operational amplifier of TI company, and simulation software directly provides SPICE model parameters of the chip. Wherein the four independent resistors R have a fixed resistance of 100 omega and the impedance ZLTo a value of 3pF to 60 pF. By varying the resistance value ZLThe reactance value of the transmission coefficient can be continuously adjusted and the dispersion characteristic curve of the reactance exhibits a non-foster characteristic between 1MHz and 100 MHz.
By comparing different reactance values in fig. 4 and fig. 5, the change trend of the reactance values can be found out to be corresponding to specific numerical values, and the numerical calculation result and the simulation result are corresponding to each other, so that the correctness of theoretical derivation is verified.
The implementation working process of the invention is as follows:
fig. 6 shows a circuit configuration of the present invention in which the transmission characteristic of the negative impedance converter is actually measured. A capacitor C is connected in series with the input port of the negative impedance converter0And measuring S parameter matrixes of the input port and the output port, and performing inverse calculation by formulas (1) to (4) to obtain a transmission coefficient matrix ABCD.
The reactance value of the transmission characteristic of the negative impedance converter measured in the present invention is shown in fig. 7. The operational amplifier adopts a double-channel OPA2695 operational amplifier of Texas Instruments (TI), four independent resistors R have fixed resistance value of 100 omega, and impedance ZLResistance of 3 pF. A capacitor with the impedance value of 2.7pF is connected in series with an input port of the negative impedance converter, an S parameter matrix of the input port and an S parameter matrix of the output port are measured, and a transmission coefficient matrix ABCD matrix is obtained through inverse calculation of the formulas (1) - (4). Since the initial operating band of the vector network (Agilent 8722ES) is in the range of 50MHz, a dispersion characteristic curve with a transmission coefficient B between 50MHz and 100MHz is obtained. The integral equivalent curve represents a dispersion characteristic curve between an input port and an output port of the circuit structure in fig. 7, and it can be seen that the curve is basically a horizontal straight line between 50MHz and 100MHz, which represents that the dispersion is basically zero. Furthermore, the Foster characteristic curve represents the capacitance C0The non-foster characteristic curve represents a dispersion curve of the transmission coefficient B of the negative impedance converter. The slope of the non-Foster characteristic compensates for the slope of the Foster characteristic such that the capacitance C0The characteristic curve of the circuit (overall equivalent) after the cascade connection with the negative impedance converter is substantially free of dispersion.
In fig. 4, 5, and 7, when the resistance values of the four independent resistors R are fixed to 100 Ω, the impedance Z is setLThe variation trend of the reactance value in the non-Foster characteristic curve at the resistance value of 3pF is corresponding to the specific value, and the correctness of the theory should be characterized again.
Height actually measured by the inventionThe pass filter circuit configuration is shown in fig. 8. The high-pass filter shown in the figure adopts a symmetrical structure in which a capacitor C is arranged1Is 100pF, resistance R1Is 100 omega. The signal generator transmits an input signal, and the oscilloscope collects an output signal.
The circuit structure of the high-pass filter of the actual measurement cascaded negative impedance converter is shown in fig. 9. The negative impedance converter shown in the figure is cascaded between two mutually symmetrical high-pass filters, in which a capacitor C is present1Is 100pF, resistance R1Is 100 omega. The operational amplifier of the negative impedance converter adopts a double-channel OPA2695 operational amplifier of Texas Instruments (TI), the resistance values of four independent resistors R are fixed to be 100 omega, and the impedance Z isLA resistance of 180 pF. The signal generator transmits an input signal, and the oscilloscope collects an output signal.
The time domain voltage signals acquired by the invention through the high pass filter of the high pass filter and the high pass filter of the cascade negative impedance converter with the frequency of 75MHz by using circuit simulation software are shown in figure 10. The signal envelope of the uncompensated curve is typical of the attenuation response of a high pass filter, corresponding to the case where the input signal passes through the high pass filter, while the signal envelope of the compensated curve corresponds to the case of the high pass filter of the cascaded negative impedance converter. The compensation curve is no longer a filter decay response and the shape of the signal envelope is more nearly a square wave relative to the signal envelope of the uncompensated curve. This shows that the signal is compensated by the cascaded negative impedance converter, and the non-foster characteristic of the negative impedance converter is used to offset the dispersion characteristic of the foster device, i.e. the dispersion compensation is performed on the square wave envelope signal distorted by the high pass filter.
The time domain voltage signals collected after the square wave with the actual measurement frequency of 75MHz respectively passes through the high-pass filter and the high-pass filter of the cascaded negative impedance converter are shown in fig. 11. The signal envelope of the uncompensated curve is typical of the attenuation response of a high pass filter, corresponding to the case where the input signal passes through the high pass filter, while the signal envelope of the compensated curve corresponds to the case of the high pass filter of the cascaded negative impedance converter. The compensation curve is no longer a filter decay response and the shape of the signal envelope is more nearly a square wave relative to the signal envelope of the uncompensated curve. This shows that the signal is compensated by the cascaded negative impedance converter, and the non-foster characteristic of the negative impedance converter is used to offset the dispersion characteristic of the foster device, i.e. the dispersion compensation is performed on the square wave envelope signal distorted by the high pass filter. The result corresponds to a simulation conclusion, and theoretical correctness is further verified.
Claims (4)
1. A series two-port negative impedance transformer for signal envelope distortion compensation, characterized by: the improved negative impedance converter based on the floating type differential structure is characterized in that a three-port network structure is improved into a double-port network structure, namely, an original differential input positive electrode is improved into an input port, a differential input negative electrode is improved into an output port, the original differential output port is removed, so that the double-port negative impedance converter with the series characteristic is formed, the non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter is adjusted through resistors connected with the positive and negative input ports of two operational amplifiers and impedance connected between the two operational amplifiers, and accordingly envelope dispersion compensation is performed on square wave signals distorted by a high-pass filter;
the dual-port negative impedance converter with the series characteristic comprises a loop circuit structure formed by two operational amplifiers, wherein a positive input port and a negative input port of a first operational amplifier are respectively connected with a first resistor and a second resistor, and the other ends of the first resistor and the second resistor are connected with an output port of a second operational amplifier; meanwhile, the positive and negative input ports of the second operational amplifier are respectively connected with a third resistor and a fourth resistor, and the other ends of the third resistor and the fourth resistor are connected with the output port of the first operational amplifier; one end of the impedance is connected to a first operation amplified negative input port and a second resistor connected with the first operation amplified negative input port, and the other end of the impedance is connected to a second operation amplified positive input port and a third resistor connected with the second operation amplified positive input port;
the input port is led out from a positive input port of the first operational amplifier and a first resistor connected with the positive input port, and forms an input port of a dual-port network with a ground wire; and the output port is led out from the fourth resistor connected with the negative input port of the second operational amplifier and forms an output port of the dual-port network with the ground wire.
2. A series two-port negative impedance transformer for signal envelope distortion compensation as claimed in claim 1 wherein: the non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter is adjusted through the resistors connected with the positive and negative input ports of the two operational amplifiers and the impedance connected between the two operational amplifiers, the two operational amplifiers are enabled to be in a normal working condition by adjusting the resistance values of the respective resistors connected with the positive and negative input ports of the two operational amplifiers, and the transmission coefficient of the whole circuit is changed by adjusting the impedance value connected between the two operational amplifiers.
3. A series two-port negative impedance transformer for signal envelope distortion compensation as claimed in claim 2, wherein: the non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter is adjusted through the resistor connected with the positive and negative electrode input ports of the two operational amplifiers and the impedance connected between the two operational amplifiers, and the calculation formula of the transmission coefficient is as follows:
wherein B is the transmission coefficient of the circuit, R is the resistance values of four independent resistors connected with the positive and negative input ports of the operational amplifier, and ZLIs the resistance value of the impedance connected with the operational amplifier, AoIs the gain of the operational amplifier.
4. A series two-port negative impedance transformer for signal envelope distortion compensation as claimed in claim 1 wherein: the dispersion compensation of the envelope of the square wave signal distorted by the high-pass filter is realized by adjusting the non-Foster characteristic of the transmission coefficient of the whole circuit of the impedance converter through the resistor connected with the positive and negative input ports of the two operational amplifiers and the impedance connected between the two operational amplifiers, and then cascading the non-Foster characteristic with the high-pass filter with the Foster characteristic to offset the dispersion characteristic of a Foster device, and performing the dispersion compensation of the envelope of the square wave signal distorted by the high-pass filter.
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| CN103636122A (en) * | 2011-04-07 | 2014-03-12 | Hrl实验室有限责任公司 | Non-foster circuit |
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| CN107465398A (en) | 2017-12-12 |
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