CN107395041B - High-conversion-efficiency isolated micro grid-connected inverter and control method thereof - Google Patents
High-conversion-efficiency isolated micro grid-connected inverter and control method thereof Download PDFInfo
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- 238000010586 diagram Methods 0.000 description 19
- 238000009434 installation Methods 0.000 description 4
- 238000010248 power generation Methods 0.000 description 4
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
-
- H02J3/385—
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E10/00—Energy generation through renewable energy sources
- Y02E10/50—Photovoltaic [PV] energy
- Y02E10/56—Power conversion systems, e.g. maximum power point trackers
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Inverter Devices (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses an isolated micro grid-connected inverter with high conversion efficiency and a control method thereof, belonging to the technical field of micro inverters. The purpose is to provide an isolated micro grid-connected inverter with high conversion efficiency, and the functions of maximum power tracking and boosting are realized. The high-conversion-efficiency isolated micro grid-connected inverter comprises an input end, a DC-DC part and a DC-AC part, wherein the DC-DC part comprises a main switching tube, an auxiliary switching tube, a boosting inductor, an isolation transformer, a resonant inductor, a resonant capacitor, a first rectifying diode, a second rectifying diode, a first secondary capacitor, a second secondary capacitor, a clamping capacitor, a parasitic diode and an anti-parallel diode. The inverter and the method thereof provided by the invention improve the conversion efficiency, realize the functions of maximum power tracking and boosting and ensure that each component operates at the maximum power point.
Description
Technical Field
The invention discloses an isolated micro grid-connected inverter with high conversion efficiency and a control method thereof, belonging to the technical field of micro inverters.
Background
With the advantages of high efficiency, flexible expansion, simple and convenient installation and the like of the distributed photovoltaic grid-connected system, medium and small power photovoltaic grid-connected power generation becomes a research hotspot.
Common photovoltaic grid-connected power generation system structures include a centralized system structure, a distributed system structure and the like. When in use, the photovoltaic modules are connected in series or in parallel. Because the photovoltaic module has the influence of factors such as manufacturing error, different installation inclination angles, different orientation, different aging degrees, local shadows and the like, the characteristics of each photovoltaic cell are different from each other. The maximum power point tracking of the system is performed for the whole group string, and each component cannot be guaranteed to operate at the maximum power point.
Compared with the traditional photovoltaic grid connection, the micro-inverter can ensure that each solar component operates at the maximum power point, and the whole power generation system can obtain better power generation efficiency; and the installation is convenient, the service life is long, hot plugging is supported, and the installation space is not occupied independently basically. With the development of the distributed photovoltaic industry, the proportion of civil and small commercial photovoltaic devices is gradually increased, and the market demand for micro inverters is continuously increased.
Disclosure of Invention
In view of the above disadvantages in the prior art, an object of the present invention is to provide an isolated micro grid-connected inverter with high conversion efficiency, which realizes Maximum Power Point Tracking (MPPT) and boosting functions.
The high-conversion-efficiency isolated micro grid-connected inverter comprises an input end, a DC-DC part and a DC-AC part, wherein the DC-DC part comprises a main switching tube, an auxiliary switching tube, a boosting inductor, an isolation transformer, a resonant inductor, a resonant capacitor, a first rectifying diode, a second rectifying diode, a first secondary capacitor, a second secondary capacitor, a clamping capacitor, a parasitic diode and an anti-parallel diode;
the main switch tube and the auxiliary switch tube are connected between the input end and the primary side of the isolation transformer, the boosting inductor is connected between the collector electrode of the main switch tube and the input end, the resonant capacitor is connected in series with the resonant inductor, the resonant capacitor is respectively connected with the resonant inductor and the emitter electrode of the auxiliary switch tube, the resonant inductor is connected with the primary side of the isolation transformer, the first secondary capacitor is connected with the secondary side of the isolation transformer through a first rectifier diode, the second secondary capacitor is connected with the secondary side of the isolation transformer through a second rectifier diode, the first rectifier diode is connected in series with a second rectifier diode, the clamping capacitor is connected between the collector electrode of the auxiliary switch tube and the primary side of the isolation transformer, the parasitic capacitor is connected in parallel to the main switch tube, and.
Further, the maximum output power of the isolated micro grid-connected inverter with high conversion efficiency is 310W.
Further, the working voltage range of the isolated micro grid-connected inverter with high conversion efficiency is 15-60V.
The invention also provides a control method of the high-conversion-efficiency isolated micro grid-connected inverter, which is realized by the high-conversion-efficiency isolated micro grid-connected inverter, and the control period comprises six stages:
the first stage is as follows:
the main switch tube is conducted, the auxiliary switch tube is turned off, the input inductance current is linearly increased, the resonance inductance current is reduced and the direction is positive, the resonance capacitance voltage is increased, the first rectifier diode is conducted, the first secondary side capacitance voltage is increased, the second secondary side capacitance voltage is reduced, the parasitic diode is not conducted until the resonance inductance current is reduced to zero;
and a second stage:
the main switch tube is conducted, the auxiliary switch tube is turned off, the input inductance current is linearly increased, the resonance inductance current is changed from positive to negative, the voltage of the resonance capacitor begins to be reduced, the second rectifier diode is conducted, the voltage of the second secondary side capacitor is increased, and the voltage of the first secondary side capacitor is reduced;
and a third stage:
the main switch tube is turned off, the auxiliary switch tube is turned off, the input inductive current starts to linearly decrease, the resonant inductive current starts to increase but still is a negative value, the parasitic capacitor starts to charge until the voltage of the parasitic capacitor is equal to that of the clamping capacitor, the second rectifier diode is always conducted, the voltage of the second secondary side capacitor rises, the voltage of the first secondary side capacitor decreases, and the resonant inductive current starts to slowly increase until the resonant inductive current becomes zero;
a fourth stage:
the main switch tube is turned off, the auxiliary switch tube is turned off, and the input inductive current begins to linearly decrease; the resonant inductor current starts to increase from zero, the first rectifier diode starts to be conducted, the voltage of the second secondary side capacitor starts to decrease, the first rectifier voltage increases, the parasitic diode of the auxiliary switch tube starts to be conducted, and the clamping capacitor starts to be charged until the auxiliary switch tube starts to be conducted;
the fifth stage:
the auxiliary switching tube is conducted, and because the parasitic diode is conducted, the auxiliary switching tube is in a zero-voltage conducting state, the resonant inductor current continues to increase, the first rectifier diode is conducted, the first secondary side capacitor voltage is increased, the second secondary side capacitor voltage is reduced, and the input inductor current keeps linearly reduced;
the sixth stage:
the auxiliary switch tube is turned off, the resonant inductor current starts to decrease, the first rectifier diode is kept to be conducted, the first secondary capacitor voltage is increased, the second secondary capacitor voltage is reduced, the input inductor current keeps to be linearly reduced, the energy stored in the resonant inductor is larger than the energy stored in the parasitic capacitor, the parasitic capacitor voltage is discharged to zero, the anti-parallel diode of the main switch tube is conducted at the moment, the main switch tube is turned on, the main switch tube is in a zero-voltage turning-on state, and the next period starts.
The invention has the beneficial effects that: according to the isolated micro grid-connected inverter with high conversion efficiency and the control method thereof, the conversion efficiency is improved, the maximum power tracking and boosting functions are realized, and each component is ensured to operate at the maximum power point.
Drawings
FIG. 1 is a main circuit diagram of an inverter of the present invention;
FIG. 2 is a schematic diagram of six stages in the example;
FIG. 3 is an equivalent circuit diagram of the first stage in the embodiment;
FIG. 4 is an equivalent circuit diagram of the second stage in the embodiment;
FIG. 5 is an equivalent circuit diagram of the third stage in the embodiment;
FIG. 6 is an equivalent circuit diagram of the fourth stage in the embodiment;
FIG. 7 is an equivalent circuit diagram of the fifth stage in the embodiment;
FIG. 8 is an equivalent circuit diagram of the sixth stage in the embodiment;
FIG. 9 is a schematic diagram of the operation state of the DC-AC part in the embodiment;
FIG. 10 is a waveform diagram of the DC-AC partial switch tube driving;
FIG. 11 is a waveform diagram of grid voltage and grid-connected current;
FIG. 12 is a graph of main switching tube drive and voltage stress waveforms;
FIG. 13 is a graph of auxiliary switching tube drive and voltage stress waveforms;
FIG. 14 is a graph of the conversion efficiency of a micro-inverter;
fig. 15 is a grid-connection current distortion rate diagram.
Detailed Description
The invention will be further described with reference to the accompanying drawings and the detailed description below:
in the embodiment, an isolated micro inverter topology with high conversion efficiency is provided, as shown in fig. 1. The topology adopts a two-stage topology, the front-stage DC-DC part is used for realizing Maximum Power Point Tracking (MPPT) and boosting functions, and the rear-stage DC-AC part inverts direct current into alternating current and transmits the alternating current to a power grid. The maximum power of the whole polar plate is generally less than 310W, and the maximum output power proposed by the patent is also 310W. The open circuit voltage is typically below 60V depending on the parameters of the plate. The working voltage range U of the inverterPVBetween 15-60V. DC-DC part will UPVThe voltage rises to Uout(approximately 400V). The operation principle of the DC-DC part will be described below. The DC-DC part adopts a scheme based on a resonant isolation type boost soft switch. The main switch tube Q5Auxiliary switch tube Q6Boost inductor L and isolation transformer T1Resonant inductor LrResonant capacitor CpRectifier diode D1And D2Capacitor C1And C2And (4) forming. The main pipe and the auxiliary pipe are conducted according to a certain opening mode, a certain dead driving time is left between the opening and the closing of the two switch pipes, and ZVS zero voltage conduction of the two switch pipes can be achieved.
The control process is divided into six stages as shown in fig. 2.
First stage (t)0-t1)：
t0Time, main switch tube Q5Conducting auxiliary switch tube Q6Turn off, input of inductor current iLLinearly increasing, resonant inductor current iLrDecreasing, but positive, resonant capacitor voltage UCpAnd (4) increasing. Secondary side diode D of transformer1On, the capacitor voltage UC1Step-up, capacitor voltage UC2And decreases. Due to clamping capacitor voltage UCAuxiliary switch tube Q with higher voltage6The parallel diode is non-conductive. The equivalent circuit diagram is shown in fig. 3. This state continues until t1Time of day, resonant inductor current iLrReducing to zero.
Second stage (t)1-t2)：
t1Time, main switch tube Q5Is still conducted, the auxiliary switch tube keeps Q6Turn off, input of inductor current iLLinearly increasing, resonant inductor current iLrFrom positive to negative, the resonant capacitor voltage UCpThe decrease is started. Secondary side diode D2On, the capacitor voltage UC2Step-up, capacitor voltage UC1And decreases. The equivalent circuit diagram is shown in fig. 4.
Third stage (t)2-t3)：
t2Time, main switch tube Q5Turn-off, auxiliary switch tube Q6Turn off, input of inductor current iLThe initial linearity decreases and the resonant inductor current begins to increase but remains negative. Main switch tube Q5Parasitic capacitance CrStarting charging until t3Time of day, parasitic capacitance voltage UCrEqual to the clamp capacitor voltage Uc, i.e. UCr= Uc. Secondary side diode D2Always on, capacitor voltage UC2Step-up, voltage UC1And decreases. The resonant inductor current begins to slowly increase until t3The time instant becomes zero. The charging process is short in time, and the inductive current i is input in the processLThe size remains substantially constant. The equivalent circuit diagram is shown in fig. 5.
The fourth stage (t)3-t4)：
t3Time, main switch tube Q5Turn-off, auxiliary switch tube Q6And turning off and keeping turning off. Input of inductor current iLThe linear reduction continues. The resonant inductor current starts to increase from zero. Secondary side diode D1Begins to conduct, capacitor voltage UC2Initially decreased, voltage UC1And (4) increasing. Auxiliary switch tube Q6The parasitic diode starts to conduct and starts to supply to the clamping capacitor CcAnd (6) charging. Until t4Time-of-day auxiliary switch tube Q6Conduction is started. The equivalent circuit diagram is shown in fig. 6.
The fifth stage (t)4-t5)：
t4Time-of-day auxiliary switch tube Q6Conducting due to the anti-parallel diode of the auxiliary switch tubeAfter the switch-on, the auxiliary switch tube is in a zero voltage switching-on state. Resonant inductor current iLrThe increase continues. Diode D1On, the capacitor voltage UC1Step-up, capacitor voltage UC2And decreases. Input of inductor current iLThe linearity is kept down. The equivalent circuit diagram is shown in fig. 7.
The sixth stage (t)5-t6)：
t5Time-of-day auxiliary switch tube Q6And (6) turning off. Resonant inductor current iLrThe decrease is started. Diode D1Keep on, capacitor voltage UC1Step-up, capacitor voltage UC2And decreases. Input of inductor current iLThe linearity is kept down. Suppose resonant inductance LrThe energy stored in the capacitor is larger than the parasitic capacitance CrThe stored energy, the parasitic capacitance voltage will be discharged to zero, at which time the anti-parallel diode of the main switch tube is turned on. If the main switch tube is turned on at the moment, the main tube is in a zero-voltage turning-on state. t is t6Turn on Q5And another cycle begins. The equivalent circuit diagram is shown in fig. 8.
The later stage DC-AC part inverts the direct current into alternating current and transmits the alternating current to a power grid. To reduce switching losses, the power device Q1-Q4One part works in a power frequency state, and the other part works in a high-frequency state. As shown in fig. 9.
FIG. 10 shows a switching tube driving waveform, Q1And Q2Operating at power frequency, Q3And Q4And working in a high-frequency state. Fig. 11 shows a grid voltage and grid-connected current waveform, which has a good sine degree and a low distortion rate. Fig. 12 and 13 show the driving of the main switching tube and the auxiliary switching tube of the DC-DC part and the voltage stress waveforms thereof, and it can be seen from the diagrams that the main switching tube and the auxiliary switching tube belong to zero voltage switching.
Fig. 14 shows the conversion efficiency of the micro-inverter when the output power is from no load to full load (310W) and the input voltage is 25V, 30V and 40V, respectively, and it can be seen that the maximum efficiency reaches 94.7%.
Fig. 15 shows the grid-connected current distortion rate when the output power is from no load to full load (310W) when the input voltage is 25V, 30V and 40V, respectively, and it can be seen from the figure that the minimum grid-connected current distortion rate is 2.9%.
Various other modifications and changes may be made by those skilled in the art based on the above-described technical solutions and concepts, and all such modifications and changes should fall within the scope of the claims of the present invention.
Claims (1)
1. A control method of an isolated micro grid-connected inverter with high conversion efficiency is realized based on the isolated micro grid-connected inverter with high conversion efficiency, and the isolated micro grid-connected inverter with high conversion efficiency comprises an input end, a DC-DC part and a DC-AC part, and is characterized in that the DC-DC part comprises a main switching tube, an auxiliary switching tube, a boosting inductor, an isolation transformer, a resonant inductor, a resonant capacitor, a first rectifying diode, a second rectifying diode, a first secondary capacitor, a second secondary capacitor, a clamping capacitor, a parasitic diode and an anti-parallel diode;
the control method is characterized in that a control cycle of the control method comprises six stages:
the first stage is as follows:
the main switch tube is conducted, the auxiliary switch tube is turned off, the boosting inductance current is linearly increased, the resonance inductance current is reduced and the direction is positive, the resonance capacitance voltage is increased, the first rectifier diode is conducted, the first secondary side capacitance voltage is increased, the second secondary side capacitance voltage is reduced, the parasitic diode is not conducted until the resonance inductance current is reduced to zero;
and a second stage:
the main switching tube is conducted, the auxiliary switching tube is turned off, the boosting inductance current is linearly increased, the resonance inductance current is changed from positive to negative, the resonance capacitor voltage begins to be reduced, the second rectifier diode is conducted, the second secondary side capacitor voltage is increased, and the first secondary side capacitor voltage is reduced;
and a third stage:
the main switch tube is turned off, the auxiliary switch tube is turned off, the boost inductive current starts to linearly decrease, the resonant inductive current starts to increase but still has a negative value, the parasitic capacitor starts to charge until the voltage of the parasitic capacitor is equal to that of the clamping capacitor, the second rectifier diode is always conducted, the voltage of the second secondary side capacitor rises, the voltage of the first secondary side capacitor decreases, and the resonant inductive current starts to slowly increase until the resonant inductive current becomes zero;
a fourth stage:
the main switch tube is turned off, the auxiliary switch tube is turned off, and the boost inductive current starts to linearly decrease; the resonant inductor current starts to increase from zero, the first rectifier diode starts to be conducted, the voltage of the second secondary capacitor starts to decrease, the voltage of the first secondary capacitor increases, the parasitic diode of the auxiliary switch tube starts to be conducted, and the clamping capacitor starts to be charged until the auxiliary switch tube starts to be conducted;
the fifth stage:
the auxiliary switching tube is conducted, and as the parasitic diode is conducted and the auxiliary switching tube is in a zero-voltage conduction state, the resonant inductor current continues to increase, the first rectifier diode is conducted, the first secondary side capacitor voltage is increased, the second secondary side capacitor voltage is reduced, and the boost inductor current keeps linearly reduced;
the sixth stage:
the auxiliary switch tube is turned off, the resonant inductor current starts to decrease, the first rectifier diode is kept to be conducted, the first secondary capacitor voltage is increased, the second secondary capacitor voltage is reduced, the boost inductor current keeps to be linearly reduced, the energy stored in the resonant inductor is larger than the energy stored in the parasitic capacitor, the parasitic capacitor voltage is discharged to zero, the anti-parallel diode of the main switch tube is conducted at the moment, the main switch tube is turned on, the main switch tube is in a zero-voltage turning-on state, and the next period starts.
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| CN110649802B (en) * | 2019-08-22 | 2021-02-05 | 东莞理工学院 | Correction method of single-stage resonant AC-DC power factor correction conversion device |
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|---|---|---|---|---|
| CN1929276A (en) * | 2006-08-09 | 2007-03-14 | 哈尔滨工业大学 | Soft switch back exciting converter used for solar energy photovoltaic generation incorporate in power network |
| CN101951011A (en) * | 2010-08-25 | 2011-01-19 | 南京航空航天大学 | Solar photovoltaic and commercial power combined power supply system and control method thereof |
| CN203911800U (en) * | 2014-06-26 | 2014-10-29 | 陕西光伏产业有限公司 | High-frequency isolated photovoltaic inverter |
| CN105790576A (en) * | 2016-05-19 | 2016-07-20 | 上海电机学院 | Isolated-type CUK soft switching converter |
| CN106887945A (en) * | 2017-04-10 | 2017-06-23 | 东莞理工学院 | Single-stage resonant mode isolates Sofe Switch boosting power factor correction circuit and bearing calibration |
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Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1929276A (en) * | 2006-08-09 | 2007-03-14 | 哈尔滨工业大学 | Soft switch back exciting converter used for solar energy photovoltaic generation incorporate in power network |
| CN101951011A (en) * | 2010-08-25 | 2011-01-19 | 南京航空航天大学 | Solar photovoltaic and commercial power combined power supply system and control method thereof |
| CN203911800U (en) * | 2014-06-26 | 2014-10-29 | 陕西光伏产业有限公司 | High-frequency isolated photovoltaic inverter |
| CN105790576A (en) * | 2016-05-19 | 2016-07-20 | 上海电机学院 | Isolated-type CUK soft switching converter |
| CN106887945A (en) * | 2017-04-10 | 2017-06-23 | 东莞理工学院 | Single-stage resonant mode isolates Sofe Switch boosting power factor correction circuit and bearing calibration |
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