CN107124102A - There is one kind self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters - Google Patents
There is one kind self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters Download PDFInfo
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- CN107124102A CN107124102A CN201710253583.2A CN201710253583A CN107124102A CN 107124102 A CN107124102 A CN 107124102A CN 201710253583 A CN201710253583 A CN 201710253583A CN 107124102 A CN107124102 A CN 107124102A
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
Abstract
The invention discloses one kind there is self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, belong to converters technical field.Wherein, power supply UinPositive pole and coupling inductance T1 primary side winding inductance L1aThe primary side winding inductance L of Same Name of Ends and coupling inductance T22aSame Name of Ends is connected, UinNegative pole ground connection, wherein, coupling inductance T1 primary side winding inductance L1aNon-same polarity and electric capacity C1One end, switching tube S1Drain electrode and diode D1Anode connection, switching tube S1Source ground, diode D1Negative electrode and electric capacity C2One end, coupling inductance T1 vice-side winding inductance L1cSame Name of Ends connection, for prior art DC converter adjust gain when there is the problem of dutycycle controlled range is small, it gain can be adjusted in wider duty cycle range, and possess self-balancing ability.
Description
Technical field
There is self-balancing ability, wide dutycycle the present invention relates to converters technical field, more particularly to one kind
Control the high-gain DC/DC converters that interlock.
Background technology
Global disposable fossil energy is petered out, and can produce greenhouse gases, air pollution etc. one in use
Serial environmental problem, for alleviation problem above, the green energy resource such as photovoltaic, fuel cell, which generates electricity by way of merging two or more grid systems, receives extensive attention.So
And the output voltage of these energy is generally relatively low, therefore needed in low pressure regenerative resource grid-connected system with high boosting
The DC power converter of function.And traditional Boost is easily limited by circuit parasitic parameter, gain characteristic of boosting by
Limit.
In the prior art, the alternation parallel DC/DC converters realized using three winding coupling inductance can obtain high voltage
Gain, while the features such as being also equipped with low input current ripple, low switch device voltage stress, high conversion efficiency, just as in recent years
Come one of focus for studying.Wherein, will during existing non-isolation type three winding coupling inductance alternation parallel DC/DC converters are per phase
The one of secondary of coupling inductance and a secondary of another coupling inductance are joined directly together and connect, then with electric capacity, diode, switching tube
Multiplication of voltage loop is constituted, voltage gain is improved, reduces input, output current ripple, also with good automatic current equalizing ability,
But the converter working condition of this type is by duty-cycle limit, the on off state that dutycycle is more than 0.5 need to be operated in, it is real
Influenceed in the application of border by factors, the scope of application of dutycycle is further restricted, it is impossible to generally applicable；And if
The synchronous operation of two switching tubes is reduced inrush current using independent startup control circuit, not only increase converter control
The complexity of system, and the flexibility ratio of voltage gain regulation is limited, reduce the dynamic property of converter.
Chinese invention patent, publication No.：103618446A, publication date：On March 5th, 2014, a kind of band of the disclosure of the invention
The passive-clamp parallel connection type booster converter of coupling inductance and switching capacity, including two power switch pipes, two poles of afterflow two
Pipe, two switching capacities, two output diodes, an output capacitance, two clamp diodes, two clamping capacitances and two
Three winding coupling inductance.The zero current turning-on of power switch pipe is realized using the leakage inductance of two three winding coupling inductances, and is controlled
Current fall rate in diode processed, so as to solve the reverse-recovery problems of diode when off.Using clamp diode and
Clamping capacitance composition passive circuit realizes the lossless transfer of the soft switching and leakage inductance energy of power switch pipe, wherein clamping two poles
Pipe is not connected in loop of power circuit, can reduce the conduction loss of diode, clamping capacitance is staggeredly placed, and realizes two staggeredly branch
The current balance on road.The high-gain output of converter is realized using second and third winding of two three winding coupling inductances, entirely
Inverter power loss is small, simple for structure.Its weak point is that dutycycle adjustable extent is small, is controlled according to independent startup
Circuit adds circuit control cost, and application is narrow.
The content of the invention
1. the invention technical problem to be solved
For prior art DC converter adjust gain when there is the problem of dutycycle controlled range is small, the present invention is carried
Supply a kind of there is self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters.It can be in wider dutycycle model
Enclose it is interior gain is adjusted, and possess self-balancing ability.
2. technical scheme
To solve the above problems, the technical scheme that the present invention is provided is：
There is one kind self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, power supply UinPositive pole and coupling
Close inductance T1 primary side winding inductance L1aThe primary side winding inductance L of Same Name of Ends and coupling inductance T22aSame Name of Ends is connected, UinIt is negative
Pole is grounded, wherein, coupling inductance T1 primary side winding inductance L1aNon-same polarity and electric capacity C1One end, switching tube S1Drain electrode and
Diode D1Anode connection, switching tube S1Source ground, diode D1Negative electrode and electric capacity C2One end, coupling inductance T1
Vice-side winding inductance L1cSame Name of Ends connection, electric capacity C2The other end ground connection, coupling inductance T1 vice-side winding inductance L1cIt is non-
Same Name of Ends and diode D2Anode connection, diode D2Negative electrode and diode Do2Anode and coupling inductance T2 secondary around
Group inductance L2bNon-same polarity is all connected with；
Electric capacity C1The other end and coupling inductance T1 vice-side winding inductance L1bSame Name of Ends connection, coupling inductance T1 pair
Side winding inductance L1bThe other end and diode Do1Anode and diode D4Negative electrode connection, diode Do1Negative electrode and two
Pole pipe Do2Negative electrode, output capacitance CoOne end and resistance R one end connection, output capacitance CoThe other end and resistance R it is another
One end is grounded；
Coupling inductance T2 primary side winding inductance L2aNon-same polarity and switching tube S2Drain electrode, electric capacity C3One end and two poles
Pipe D3Anode be all connected with, switching tube S2Source ground, electric capacity C3The other end and coupling inductance T2 vice-side winding inductance L2b
Same Name of Ends connection, diode D3Negative electrode and electric capacity C4One end and coupling inductance T2 vice-side winding inductance L2cSame Name of Ends
Connection, electric capacity C4The other end ground connection, coupling inductance T2 vice-side winding L2cNon-same polarity and diode D4Anode connection.
Preferably, switching tube S1With switching tube S2The input signal dutycycle of grid is 0-1.
3. beneficial effect
The technical scheme provided using the present invention, compared with prior art, is had the advantages that：
(1) there is one kind of the invention self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, realization
Voltage high-gain conversion, voltage gain regulation is more flexible；
(2) there is one kind of the invention self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, account for
Sky is than in whole excursion (0<D<1) possesses consistent voltage gain, so that realizing for control circuit is simpler；
(3) there is one kind of the invention self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, pass through
The secondary of two groups of coupling inductances intersects bridging, and branch voltage and electric current can realize autobalance；
(4) there is one kind of the invention self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, switch
Tube voltage stress is substantially reduced, can using low stress levels and low on-resistance high performance switch device, reduce hardware into
This；
(5) there is one kind of the invention self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, defeated
Enter the structure that side employs crisscross parallel, input current ripple has obtained effective suppression；
(6) there is one kind of the invention self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, in pincers
In the presence of the circuit of position, leakage inductance energy is fully utilized, and reduces switch tube voltage spike, based on above feature, the converter
There is good application value in field of new energy generation such as photovoltaic, fuel cells.
Brief description of the drawings
Fig. 1 is circuit structure diagram of the invention；
Fig. 2 is circuit structure diagram of the invention；
Fig. 3 key operation waveforms when dutycycle is more than 0.5 for the present invention；
Fig. 4 is the equivalent circuit of present invention mode 1 when dutycycle is more than 0.5；
Fig. 5 is the equivalent circuit of present invention mode 2 when dutycycle is more than 0.5；
Fig. 6 is the equivalent circuit of present invention mode 3 when dutycycle is more than 0.5；
Fig. 7 is the equivalent circuit of present invention mode 4 when dutycycle is more than 0.5；
Fig. 8 is the equivalent circuit of present invention mode 5 when dutycycle is more than 0.5；
Fig. 9 is the equivalent circuit of present invention mode 6 when dutycycle is more than 0.5；
Figure 10 is the equivalent circuit of present invention mode 7 when dutycycle is more than 0.5；
Figure 11 is the equivalent circuit of present invention mode 8 when dutycycle is more than 0.5；
Figure 12 key operation waveforms when dutycycle is less than 0.5 for the present invention；
Figure 13 is the equivalent circuit of present invention mode 1 when dutycycle is less than 0.5；
Figure 14 is the equivalent circuit of present invention mode 2 when dutycycle is less than 0.5；
Figure 15 is the equivalent circuit of present invention mode 3 when dutycycle is less than 0.5；
Figure 16 is the equivalent circuit of present invention mode 4 when dutycycle is less than 0.5；
Figure 17 is the equivalent circuit of present invention mode 5 when dutycycle is less than 0.5；
Figure 18 is the equivalent circuit of present invention mode 6 when dutycycle is less than 0.5；
Figure 19 is the switch drive voltage Ugs of 200W experimental prototype1With leakage inductance electric current iLk1、iLk2Waveform；
Figure 20 is the switch drive voltage Ugs of 200W experimental prototype1, leakage inductance electric current iLk1With input current iinWaveform；
Figure 21 is the switch drive voltage Ugs of 200W experimental prototype1, switching tube S1Voltage stress UDS1With clamp capacitor C2
Voltage UC2Waveform；
Figure 22 is the diode D of 200W experimental prototype1、D2Voltage stress UD1、UD2Waveform；
Figure 23 is the power device voltage stress analogous diagram of converter of the present invention.
Embodiment
To further appreciate that present disclosure, with reference to drawings and Examples, the present invention is described in detail.
Embodiment 1
As shown in figure 1, there is one kind of the present embodiment self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC changes
Parallel operation, power supply UinPositive pole and coupling inductance T1 primary side winding inductance L1aSame Name of Ends and coupling inductance T2 primary side winding electricity
Feel L2aSame Name of Ends is connected, UinNegative pole ground connection, wherein, coupling inductance T1 primary side winding inductance L1aNon-same polarity and electric capacity
C1One end, switching tube S1Drain electrode and diode D1Anode connection, switching tube S1Source ground, diode D1Negative electrode and electric capacity
C2One end, coupling inductance T1 vice-side winding inductance L1cSame Name of Ends connection, electric capacity C2The other end ground connection, coupling inductance T1
Vice-side winding inductance L1cNon-same polarity and diode D2Anode connection, diode D2Negative electrode and diode Do2Anode
With coupling inductance T2 vice-side winding inductance L2bNon-same polarity is all connected with；
Electric capacity C1The other end and coupling inductance T1 vice-side winding inductance L1bSame Name of Ends connection, coupling inductance T1 pair
Side winding inductance L1bThe other end and diode Do1Anode and diode D4Negative electrode connection, diode Do1Negative electrode and two
Pole pipe Do2Negative electrode, output capacitance CoOne end and resistance R one end connection, output capacitance CoThe other end and resistance R it is another
One end is grounded；
Coupling inductance T2 primary side winding inductance L2aNon-same polarity and switching tube S2Drain electrode, electric capacity C3One end and two poles
Pipe D3Anode be all connected with, switching tube S2Source ground, electric capacity C3The other end and coupling inductance T2 vice-side winding inductance L2b
Same Name of Ends connection, diode D3Negative electrode and electric capacity C4One end and coupling inductance T2 vice-side winding inductance L2cSame Name of Ends
Connection, electric capacity C4The other end ground connection, coupling inductance T2 vice-side winding L2cNon-same polarity and diode D4Anode connection,
Switching tube S1With switching tube S2The input signal dutycycle of grid is 0-1.
The present invention is using two three winding coupling inductances T1 and T2, it is proposed that one kind has self-balancing ability, wide dutycycle
Control the high-gain DC/DC converters that interlock.The converter is in input side using traditional crisscross parallel Boost connection side
Formula, reduces input current ripple.The tertiary winding of each coupling inductance jump to another inductance that is coupled the second winding and
Between output diode, circulating pathway is provided for the quasi- voltage doubling unit charging that its second winding and electric capacity are constituted, while two couplings
The secondary of inductance has carried out the coupling that intersects.The passive absorption circuit unit being made up of diode and electric capacity is turned off in switching tube
Afterwards, circulating pathway is provided for leakage inductance, the leakage inductance energy discharged in electric capacity is shifted by fly-wheel diode to storage capacitor again, is filled
Divide and make use of leakage inductance energy and reduce switch tube voltage spike, improve conversion efficiency；The converter can be operated in duty
(0 in the whole excursion of ratio<D<1), while voltage gain is consistent in the whole transformation range of dutycycle, be conducive to
Realization to controlling circuit.
The equivalent circuit structure of embodiment 2
There is one kind of the present embodiment self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, its structure
Same as Example 1, its equivalent circuit structure is as shown in Figure 2.
Fig. 2 is that there is one kind that the present embodiment is proposed self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC conversion
Device, secondary leakage inductance conversion to the equivalent structure after primary side；Two coupling inductances of T1, T2, each coupling inductance are had in the structure
There are three windings, coupling inductance T1 Same Name of Ends represents that coupling inductance T2 Same Name of Ends is represented with " " with " * ".Wherein, L1a、
L2aRespectively coupling inductance T1, T2 primary side winding inductance, L1b、L1cAnd L2b、L2cRespectively coupling inductance T1, T2 vice-side winding is electric
Sense, L1a、L2aThe number of turn be n1, L1b、L2bThe number of turn be n2, L1c、L2cThe number of turn be n3, the turn ratio of coupling inductance T1, T2
For N1=n2/n1, N2=n3/n1；Lm1And Lk1Respectively coupling inductance T1 magnetizing inductance, coupling inductance T1 primary side leakage inductance with
Total leakage inductance of the secondary conversion to primary side；Lm2And Lk2Respectively coupling inductance T2 magnetizing inductance, coupling inductance T2 primary side leakage inductance
Total leakage inductance to primary side is converted with secondary；C1、C3For storage capacitor, by clamp diode D1、D3With clamp capacitor C2、C4Constitute
Two groups of passive absorption circuit units, D2、D4For fly-wheel diode, Do1、Do2For output diode；Voltage doubling unit 1 is by electric capacity C1With
Coupling inductance T1 vice-side winding inductance L1bQuasi- voltage doubling unit 1 and switching tube that (the second winding for referring to coupling inductance T1) is constituted
S1、S2Clamp capacitor C4With coupling inductance T2 vice-side winding L2c(tertiary winding for referring to coupling inductance T2) formation；Multiplication of voltage list
Member 2 is by electric capacity C3With coupling inductance T2 vice-side winding inductance L2bThe quasi- multiplication of voltage that (the second winding for referring to coupling inductance T2) is constituted
Unit 2 and switching tube S1、S2Clamp capacitor C2With coupling inductance T1 vice-side winding L1c(refer to the 3rd of coupling inductance T1 around
Group) formed；UC1、UC2、UC3、UC4Respectively electric capacity C1、C2、C3、C4Both end voltage, iD1、iD2、iD3、iD4Respectively flow through diode
D1、D2、D3、D4Electric current, iC2、iC4Respectively electric capacity C2、C4The electric current flowed through；UDS1And iS1Respectively switching tube S1Two ends electricity
Press, flow through switching tube S1Electric current；iLk1、iLk2Respectively the first phase, the input current of the second phase, iDo1、iDo2Respectively flow through
Diode Do1、Do2Electric current, UinFor input voltage, UoFor the voltage at load R two ends, i.e. output voltage.
Operation principle (the D of embodiment 3>0.5)
There is one kind in the present embodiment self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, switch
Pipe S1With switching tube S2The input signal dutycycle D of grid>0.5, the converter in the present embodiment is in D>Groundwork when 0.5
Waveform in a switch periods as shown in figure 3, have 8 operation modes, as shown in Fig. 4-11.
[the t of mode 10-t1]
In t0Moment, switching tube S1Begin to turn on, S2Maintain conducting, diode D1、D3、D4And Do2Shut-off, D2And Do1Conducting,
Corresponding equivalent circuit is as shown in Figure 4.In this working stage, the clamp capacitor C of the first phase2With coupling inductance T1Tertiary winding string
Join to quasi- (the electric capacity C of voltage doubling unit 23With coupling inductance T2 vice-side winding inductance L2bConstitute) charging, charging current and the second phase
Input current is co-flowed into switching tube S2.(coupling inductance T1 primary side leakage inductance converts total leakage inductance L to primary side with secondary to leakage inductancek1,
Coupling inductance T2 primary side leakage inductance converts total leakage inductance L to primary side with secondaryk2) control vice-side winding (the of coupling inductance T1
Second winding of two windings, the coupling inductance T1 tertiary winding and coupling inductance T2) electric current rate of change, so as to also control two
Pole pipe D2、Do1The rate of descent of cut-off current, and then alleviate diode D2、Do1Reverse-recovery problems.
[the t of mode 21-t2]
As shown in figure 5, in this stage, switching tube S1、S2Simultaneously in opening state, all diodes are in reversely
Cut-off state, current flow paths are as shown in Figure 5.In input power UinIn the presence of, magnetizing inductance Lm1、Lm2With leakage inductance Lk1、
Lk2Charging energy-storing, until switching tube S2Shut-off, the mode terminates.
[the t of mode 32-t3]
With reference to Fig. 3 and Fig. 6, in t2Moment, switching tube S2Shut-off, switching tube S1Maintain conducting, diode D1、D2And Do1Still
In reverse blocking state.Due in t2Moment switching tube S2Shut-off, leakage inductance Lk2The energy of middle storage passes through clamp diode D3To
Electric capacity C4Charging.Meanwhile, magnetizing inductance Lm2With storage capacitor C3In energy through output diode Do2Transmitted to load-side.At this
In one stage, storage capacitor C1Charging energy-storing.Corresponding equivalent circuit is as shown in Figure 6.
[the t of mode 43-t4]
With reference to Fig. 3 and Fig. 7, in this mode, switching tube S2Continue to turn off, switching tube S1Continue to turn on, diode D1、D2
And Do1Shut-off, diode D3Zero-current switching, D4And Do2Still turn on, current flow paths are as shown in Figure 7.It is stored in magnetizing inductance
Lm2With electric capacity C3In energy continue on through output diode Do2Transmitted to load-side.While electric capacity C4In energy pass through diode
D4To storage capacitor C1Transfer.
[the t of mode 54-t5]
As shown in figure 8, switching tube S2In t4Moment begins to turn on, the switching tube S in this mode1Continue to turn on.Diode
D1、D2、D3And Do1Shut-off, D4And Do2Conducting, quasi- voltage doubling unit 1 is in the second phase clamp capacitor C4With the coupling inductance T2 tertiary windings
Collective effect under charging energy-storing, charging current and the first phase input current (leakage inductance Lk1On the electric current i that flows throughLk1) be co-flowed into
Switching tube S1.Until t5At the moment, flow through diode D4、Do2Electric current be reduced to zero, this mode terminates.
[the t of mode 65-t6]
In the mode, switching tube S1、S2Conducting state is in, all diodes are in off state, as shown in Figure 9.
Magnetizing inductance Lm1、Lm2With leakage inductance Lk1、Lk2Electric current iLk1、iLk2In input voltage UinIn the presence of it is linearly increasing.
[the t of mode 76-t7]
As seen from Figure 10, in t=t6Moment, switching tube S1Shut-off, switching tube S2Continue to turn on, diode D3、D4With
Do2Shut-off, D1、D2And Do1Conducting, is stored in magnetizing inductance Lm1With electric capacity C1In energy through output diode Do1Carried to load-side
For.Meanwhile, it is stored in leakage inductance Lk1In energy pass through clamp diode D1It is transferred to electric capacity C2In.Diode D2Conducting, is defined again
Unit 2 is pressed (by electric capacity C3With coupling inductance T2 vice-side winding inductance L2bConstitute) in storage capacitor C3Charging provides logical circulation road
Footpath.Until t7Moment, this mode terminates, into next mode.
[the t of mode 87-t0']
In this stage, switching tube S1Shut-off, S2Conducting, equivalent circuit as shown in figure 11, flows through diode D1Electric current drop
It is to turn off naturally after zero, diode D3、D4And Do2Shut-off, D2And Do1Conducting, electric capacity C3Charging energy-storing, magnetizing inductance Lm1And electric capacity
C1Continue through output diode Do1Energy is transmitted to load-side, quasi- voltage doubling unit 2 is (by electric capacity C3With coupling inductance T2 secondary
Winding inductance L2bConstitute) to storage capacitor C3Charging provides circulation path.
Operation principle (the D of embodiment 4<0.5)
There is one kind in the present embodiment self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters in D<
Key operation waveforms when 0.5 are as shown in figure 12, switching tube S1And S2Interleaved operation, its drive signal differs 180 ° of phase angles,
There are 6 operation modes in one switch periods, as shown in figures 13-18.
[the t of mode 10-t1]
As shown in figure 13.In the mode, switching tube S1Conducting, S2Still in off-state, diode D1、D2And Do1Shut-off, D3、D4
And Do2Conducting.Input power UinTo coupling inductance T1 magnetizing inductance Lm1With leakage inductance Lk1Charging, coupling inductance T2 leakage inductance Lk2
The energy of middle storage passes through clamp diode D3Continue to electric capacity C4Transfer, coupling inductance T1 magnetizing inductance Lm2And storage capacitor
C3In energy through output diode Do2Transmitted to load-side.Meanwhile, diode D4Conducting, electric capacity C1Charging energy-storing.
[the t of mode 21-t2]
With reference to Figure 12 and Figure 14, in t1Moment, switching tube S1Maintain conducting, switching tube S2Continue to turn off.In this mode,
D4And Do2Conducting, diode D3Zero-current switching, diode D1、D2And Do1It is still within reverse blocking state.Corresponding equivalent electric
Road is as shown in figure 14.
[the t of mode 32-t3]
With reference to Figure 12 and Figure 15, switching tube S1And S2It is in off state, diode D2、D3And D4It is in reversely cut-off
State, diode Do1And Do2Conducting, as shown in figure 15.Leakage inductance Lk1The energy of middle storage passes through clamp diode D1To electric capacity C2Fill
Electricity.In the mode, output diode Do1And Do2Conducting, magnetizing inductance Lm1With electric capacity C1In energy pass through Do1To load-side
Transfer, magnetizing inductance Lm2With electric capacity C3In energy pass through Do2Shifted to load-side.
[the t of mode 43-t4]
With reference to Figure 12 and Figure 16, switching tube S2In t3Moment begins to turn on, Do2、D3And D4Shut-off, the switching tube in this mode
S1Continue to turn off.Leakage inductance Lk1The energy of middle storage continues through clamp diode D1To electric capacity C2Charging, magnetizing inductance Lm1And storage
Can electric capacity C1In energy continue on through output diode Do1Charged to load-side.Meanwhile, diode D2Conducting, electric capacity C3Charging storage
Energy.Corresponding equivalent circuit is as shown in figure 16.
[the t of mode 54-t5]
The corresponding equivalent circuit of this mode is as shown in figure 17.In t4Moment switching tube S1Still in off state, switching tube S2
Maintain conducting.Diode D1Zero current is turned off naturally, diode Do2、D3And D4It is still within reverse blocking state, diode D2Lead
It is logical, electric capacity C3Charging energy-storing.
[the t of mode 65-t6]
With reference to Figure 12 and Figure 18, in the mode, switching tube S1And S2It is off state, diode D simultaneously1、D2And D4
In reverse blocking state, diode Do1、Do2And D3Conducting.Leakage inductance Lk2The energy of middle storage passes through clamp diode D3To electric capacity
C4Charging, is stored in magnetizing inductance Lm2With electric capacity C3In energy through output diode Do2Shifted to load-side.
The voltage gain of embodiment 5 is calculated
For simplifying the analysis, there is one kind in the present embodiment self-balancing ability, wide Duty ratio control to interlock high-gain DC/
DC converters, structure is same as Example 1, and equivalent structure is identical with Fig. 2, and operation principle is identical with embodiment 3 and 4, following
Loss is disregarded in analysis and ignores the influence of coupling inductance leakage inductance.
Voltage gain (D ＞ 0.5)
During mode 6 shown in mode 2 and the Fig. 9 being operated in when converter shown in Fig. 5, input power UinRespectively to excitation electricity
Feel Lm1、Lm2Charging：
ULm1=ULm2=Uin (1)
During the mode 7 being operated in shown in mode 3 and Figure 10 shown in Fig. 6, electric capacity C1、C2、C3、C4Voltage expression be：
It can be obtained by (1), (2) and (3), the expression formula of the converter output voltage：
The voltage gain of converter：
Voltage gain (D<0.5)
According to Figure 15 and Figure 18, electric capacity C can be obtained2、C4The voltage at two ends：
In fig. 13, switching tube S1Conducting, coupling inductance T1 is in the energy storage stage, and below equation can be listed according to Figure 13：
ULm1=Uin (7)
It can be obtained according to (6), (7) and (8)：
The expression formula of the converter output voltage：
The step-up ratio that converter can be obtained is：
To sum up analyze, it can be seen that the converter is (0 in the whole period of change of dutycycle<D<1), its voltage gain is expressed
Formula is identical, therefore is conducive to controlling the realization of circuit.In addition, the voltage gain expression formula of the converter has three degree of freedom, point
Not Wei dutycycle D and coupling inductance T1 and T2 turn ratio N1And N2, add the flexibility ratio of gain-adjusted.
The voltage stress of the switching device of embodiment 6
There is one kind in the present embodiment self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, according to
Embodiment 3-5 analysis, can derive switching tube S1、S2Voltage stress：
Clamp diode D1、D3Voltage stress：
Sustained diode2、D4Voltage stress：
Output diode Do1、Do2Voltage stress：
In turn ratio N1=N2In the case of=1, the ratio between voltage stress and output voltage of each power device are with switching tube duty
The change curve of ratio is as shown in figure 23.As can be seen that with the increase of dutycycle, the voltage stress of each power device reduce and
Always it is less than output voltage.Particularly, the maximum voltage stress of switching tube is less than 1/3rd of output voltage, is conducive to selection small
The high performance switching device of power.
The self-balancing ability of embodiment 7 is analyzed
There is one kind in the present embodiment self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, structure
It is same as Example 1, on the basis of embodiment 2-5, it is assumed that switching tube S1Dutycycle be D1, switching tube S2Dutycycle be
D2, turn ratio N1=N2=N, as D1 ≠ D2, storage capacitor C1、C3Both end voltage is respectively：
In switching tube S1Shut-off, S2During conducting, the first phase output voltage is：
Wherein, ULm1_dischargeRepresent coupling inductance T1 magnetizing inductances Lm1Discharge voltage.
In switching tube S1Shut-off, S2During conducting, the second phase output voltage is：
Wherein, ULm2_dischargeRepresent coupling inductance T2 magnetizing inductances Lm2Discharge voltage.
Automatic current equalizing capability analysis when the switching tube dutycycle of table 1 is asymmetric
Analyzed more than, when dutycycle is asymmetric, storage capacitor C1、C3The voltage at two ends can be with dutycycle
Change is automatically adjusted, and is kept per phase output voltage under input voltage and coupling inductance primary side and the collective effect of quasi- voltage doubling unit
Unanimously so that two-phase input current can keep autobalance.
Can be seen that the converter of the present embodiment when dutycycle is asymmetric from the simulation analysis of table 1, with preferably from
It is dynamic to flow ability.Each coupling inductance tertiary winding, which intersects, to be jumped in another group of coupling inductance, and secondary is intersected
Coupling so that branch current can realize autobalance.
The performance verification of embodiment 8
In order to verify that embodiment 1-6 puies forward the service behaviour of converter, the present embodiment has built 200W experiment sample
Machine is verified.Model machine major parameter is as shown in table 2.
The type selecting of each device of table 2
Abscissa represents time t (10us/ lattice) in Figure 19-22, and 10us is represented per lattice；Ordinate represent voltage or electric current with
The sign of parameters is corresponding, from Figure 19 and 20, because the current waveform of two coupling inductances has carried out interleaved operation,
So that total input current iinRipple greatly reduce.Figure 21 is switching tube S1On drive signal Ugs1With its voltage stress UDS1Ripple
Shape and clamp capacitor C2Voltage UC2Waveform, switching tube S1Voltage stress UDS1It is approximately output voltage Uo1/4, realize low
Voltage stress function, switching tube S1Both end voltage be no better than clamp capacitor C2Voltage, it is more consistent with theory analysis.Figure 22
For clamp diode D1And sustained diode2Voltage stress UD1、UD2Waveform, it can be seen that clamp diode D1Voltage should
Power UD1About the 1/4 of output voltage Uo, diode D2Voltage stress UD2Also below output voltage Uo, experimental result preferably tests
The operation principle and its steady-state characteristic of the converter are demonstrate,proved.
Schematical above that the present invention and embodiments thereof are described, the description does not have restricted, institute in accompanying drawing
What is shown is also one of embodiments of the present invention, and actual structure is not limited thereto.So, if the common skill of this area
Art personnel are enlightened by it, without departing from the spirit of the invention, are designed and the technical scheme without creative
Similar frame mode and embodiment, all should belong to protection scope of the present invention.
Claims (2)
1. there is one kind self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC converters, it is characterised in that power supply Uin
Positive pole and coupling inductance T1 primary side winding inductance L1aThe primary side winding inductance L of Same Name of Ends and coupling inductance T22aSame Name of Ends connects
Connect, UinNegative pole ground connection, wherein, coupling inductance T1 primary side winding inductance L1aNon-same polarity and electric capacity C1One end, switch
Pipe S1Drain electrode and diode D1Anode connection, switching tube S1Source ground, diode D1Negative electrode and electric capacity C2One end, coupling
Inductance T1 vice-side winding inductance L1cSame Name of Ends connection, electric capacity C2The other end ground connection, coupling inductance T1 vice-side winding electricity
Feel L1cNon-same polarity and diode D2Anode connection, diode D2Negative electrode and diode Do2Anode and coupling inductance T2
Vice-side winding inductance L2bNon-same polarity is all connected with；
Electric capacity C1The other end and coupling inductance T1 vice-side winding inductance L1bSame Name of Ends connection, coupling inductance T1 secondary around
Group inductance L1bThe other end and diode Do1Anode and diode D4Negative electrode connection, diode Do1Negative electrode and diode
Do2Negative electrode, output capacitance CoOne end and resistance R one end connection, output capacitance CoThe other end and resistance R the other end
It is grounded；
Coupling inductance T2 primary side winding inductance L2aNon-same polarity and switching tube S2Drain electrode, electric capacity C3One end and diode D3
Anode be all connected with, switching tube S2Source ground, electric capacity C3The other end and coupling inductance T2 vice-side winding inductance L2b's
Same Name of Ends is connected, diode D3Negative electrode and electric capacity C4One end and coupling inductance T2 vice-side winding inductance L2cSame Name of Ends connect
Connect, electric capacity C4The other end ground connection, coupling inductance T2 vice-side winding L2cNon-same polarity and diode D4Anode connection.
A kind of there is self-balancing ability, wide Duty ratio control to interlock high-gain DC/DC conversion 2. according to claim 1
Device, it is characterised in that switching tube S1With switching tube S2The input signal dutycycle of grid is 0-1.
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