CN107733221B - Multi-unit coupling inductance switch capacitor network high-gain direct current converter - Google Patents

Multi-unit coupling inductance switch capacitor network high-gain direct current converter Download PDF

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CN107733221B
CN107733221B CN201711036069.XA CN201711036069A CN107733221B CN 107733221 B CN107733221 B CN 107733221B CN 201711036069 A CN201711036069 A CN 201711036069A CN 107733221 B CN107733221 B CN 107733221B
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diode
capacitor
current
boosting unit
port
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CN107733221A (en
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张岩
李新颖
丁恺诚
刘进军
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Xian Jiaotong University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention discloses a multi-unit coupling inductance switch capacitor network high-gain direct current converter, which comprises an input end power supply VinA controllable switch tube S, a coupling inductor of a secondary multi-winding, a plurality of two-port diode capacitor boosting units, a diode D, an output capacitor C andoutput end load RL(ii) a The main circuit topology fully combines the characteristics of the multi-winding coupling inductor and the diode capacitor boosting unit, overcomes the inherent defect of the impulse current of the diode capacitor network, obviously improves the voltage gain, reduces the voltage stress of the switching tube, realizes the natural turn-off of all diodes, reduces the switching loss, improves the electric energy conversion efficiency, and has wide application prospect in a new energy distributed power generation system.

Description

Multi-unit coupling inductance switch capacitor network high-gain direct current converter
Technical Field
The invention belongs to the field of grid-connected micro-grids of new energy photovoltaic, fuel cells and the like, relates to a high-gain non-isolated direct current conversion technology, and particularly relates to a multi-unit coupling inductance switch capacitor network high-gain direct current converter.
Background
Solar energy and fuel cells are two new energy forms which are developed most rapidly in recent years and become one of the most promising energy sources in the future. However, the photovoltaic panels can generally be connected in series to increase the output voltage level, but are subject to cloud cover and bad weather, and the output voltage is low and fluctuates in a wide range. The above problems also exist with fuel cells. Therefore, the converter of the grid-tied interface must have a wide input and high boost capability. The traditional voltage source type inverter is based on a voltage reduction principle that the direct current side voltage must be larger than a grid-connected voltage peak value, the range of the new energy power generation direct current voltage is 30-50V and is far lower than a power grid voltage peak value, in order to achieve the grid-connected purpose, the grid-connected topology commonly used at present is a two-stage structure of direct current boosting and inversion, the former stage achieves a voltage wide input boosting function and provides direct current bus voltage (DC-DC) required by inversion, and the later stage achieves grid-connected conversion (DC-AC) from direct current to alternating current. Compared with a single-pole structure inversion topology, the two-stage structure can realize hierarchical optimization design and control, and has wide application prospect.
When the duty ratio of a traditional direct current converter with a boosting function works at a limit value of 1, the theoretical voltage gain tends to be infinite. However, in an actual circuit, due to the influence of parasitic parameters of devices, the circuit cannot work at a limit duty ratio and has limited boosting capacity. The current and voltage stress of the diode is large, and meanwhile, the reverse recovery problem exists due to hard turn-off, so that the problems of serious switching loss and EMI are caused, and the efficiency of the system is reduced. Furthermore, the dynamic performance of the converter is significantly degraded due to the strong non-linearity and non-minimum phase system characteristics of the system. Therefore, the wide-input high-gain direct current conversion technology is an important theoretical basis for realizing wide-input-range voltage regulation, efficient electric energy conversion and high power density of the power electronic converter, and is one of the key scientific and technical problems to be solved urgently in a new energy distributed power generation system.
The high-gain direct current converter is divided into an isolated type and a non-isolated type. The non-isolated converter has the functions of wide input and high gain conversion by adjusting the turn ratio of the primary side and the secondary side of the transformer. But the cost and volume of the circuit increases and the efficiency decreases due to the presence of the magnetic element. To obtain high gain requires an increase in the turn ratio, but the transformer linearity is deteriorated and the problems of magnetic leakage and magnetic bias are serious. The non-isolated converter mainly has a coupling inductance boosting unit technology, a switch capacitor network technology or a boosting unit technology formed by combining the coupling inductance boosting unit technology and the switch capacitor network technology, the coupling inductance magnetic element also has the problems of a transformer, and the switch capacitor network has a serious current peak problem due to instantaneous charging and discharging of capacitors through diodes, so that the circuit loss and the system cost are increased. The boosting unit combined with the boosting unit has the advantages of the boosting unit and the boosting unit, and the natural turn-off of the diode is realized while the high-gain boosting effect is achieved.
Document 1, "Yan Zhang, Zhuo Dong, Jinjun L iu, Xiaolong Ma, Xinying L i and jiuqiong Han," Modeling and controller design of high voltage generator DC-DC converter with multi-cell diode-capacitor network, "2016IEEE 8th International Power Electronics and Motion Control reference (IPEMC-ECCE Asia), hefeei, 2016, pp.3066-3072" mentions a multi-cell diode-capacitor network high-gain DC converter as shown in fig. 1 (a). the circuit of fig. 1(a) introduces a cross capacitor network into the diode-capacitor boost circuit to realize the turn-on and turn-off of S, C and C of the cross capacitor network, and has significant advantages in high gain applications of high gain and Power densityi1、Ci2And (i is more than or equal to 1 and less than or equal to N) in parallel charging and in series discharging, so that higher voltage gain is obtained. Document 2 "m.s.bharstar, p.sanjeevikumar, f.blaabjerg, v.fed a k, m.cernat and r.m.kulkani," Non-isolated and Non-inverting Cockcroft-Walton multiplexed hybrid 2Nx interleaved boost converter for recycled diode application, "International Power Electronics and Motion control switch (PEMC), Varna,2016, pp.146-151" refers to a single cell circuit of the same cross-type diode capacitance network, as shown in fig. 1(b), and the operation principle is completely the same as that of the circuit of fig. 1 (a). When S is ON, the main circuit shown in fig. 1(a) appears that two capacitors with voltage source characteristics are directly subjected to short-circuit charging and discharging processes of the power semiconductor device, so that an extremely large inrush current is generated, the device loss is increased, and the efficiency of the circuit is reduced.
Disclosure of Invention
Aiming at the defects of the prior art, the invention aims to provide a multi-unit coupling inductance switch capacitor network high-gain direct current converter, wherein a coupling inductance secondary winding is added between two-port diode capacitor networks, so that the short-circuit charging and discharging processes of power semiconductor devices between capacitors are avoided, the output voltage of each boosting unit is combined with the turn ratio of the coupling inductance, and the voltage gain range is remarkably improved.
In order to achieve the purpose, the invention adopts the following scheme:
a multi-unit coupling inductance switch capacitance network high gain DC converter is characterized in that: comprising an input terminal power supply VinA controllable switch tube S, a coupling inductor of a secondary multi-winding, a plurality of two-port diode capacitor boosting units, a diode D, an output capacitor C and an output end load RL；
The coupling inductor is equivalent to a multi-winding ideal transformer and excitation inductor LmParallel connected with leakage inductor LkAre connected in series; input end power supply VinThe positive pole of the controllable switch tube is connected with the positive pole of the primary side of the coupling inductor, and the controllable switch tube S is connected with the negative pole of the primary side of the coupling inductor and the input end power supply VinThe two ends of the negative electrode of the capacitor boosting unit are simultaneously connected in parallel at the input end of the first diode and the second diodeThe boost unit of the port diode capacitor is composed of a diode D1,D2And a capacitor C1,C2The other two-port diode capacitor boosting unit has the same structure as the first two-port diode capacitor boosting unit; a coupling inductor secondary side first winding is connected in series between the first two-port diode capacitor boosting unit and the second two-port diode capacitor boosting unit, the end with the same name is positioned at the input end of the second two-port diode capacitor boosting unit, a coupling inductor secondary side second winding is connected in series between the second two-port diode capacitor boosting unit and the third two-port diode capacitor boosting unit, the end with the same name is positioned at the output end of the second two-port diode capacitor boosting unit, and so on, the Nth winding of the coupling inductor secondary sideiThe winding is connected between the ith two-port diode capacitor boosting unit and the (i +1) th two-port diode capacitor boosting unit, if i is an even number, the dotted terminal is positioned at the side connected with the ith two-port diode capacitor boosting unit, if (i +1) is an even number, the dotted terminal is positioned at the side connected with the (i +1) th two-port diode capacitor boosting unit, the output end of the direct current converter is connected with a rectifier diode D and an output capacitor C in parallel, and an output end load R is connected with the output end of the rectifier diode D and the output capacitor C in parallelL。
2. The multi-cell coupled inductor-switched capacitor network high-gain dc converter of claim 1, wherein: the two-port diode capacitor boosting unit comprises a first diode Di1A second diode Di2A first DC capacitor Ci1And a second DC capacitor Ci2；
The coupling inductor is connected in series with the anode of the input end of the two ports, and when i is an even number, the same-name end is connected with the first diode Di1When i is odd, the different name end is connected with the first diode Di1Anode of (2), first DC capacitor Ci1Anode of the first diode Di1Anode of (2), second DC capacitor Ci2Anode of the first diode Di1A cathode of (a); first direct current capacitor Ci1Negative pole of the first diode D is connected with the second diode Di2Anode of (2), second DC capacitor Ci2Negative pole of the first diode D is connected with the second diode Di2A cathode of (a); when i is even number, the different name end of the secondary winding and a second diode Di2The cathode of the voltage boosting unit is the input end of a two-port coupling inductance diode capacitance boosting unit; when i is odd number, the dotted terminal of the secondary winding and the second diode Di2The cathode of the voltage boosting unit is the input end of a two-port coupling inductance diode capacitance boosting unit; first diode Di1And a second diode Di2The anode of the capacitor boosting unit is the output end of a two-port coupling inductance diode capacitor boosting unit; wherein i is more than or equal to 1 and less than or equal to M +1, and M is the number of secondary windings of the coupling inductor.
Compared with the prior art, the invention has the following beneficial effects:
according to the multi-unit coupling inductance switch capacitor network high-gain direct current converter, the main circuit topology fully combines the characteristics of the multi-winding coupling inductance and the diode capacitor boosting network, and the converter has the following obvious advantages: 1) the voltage gain is obviously improved, and the voltage stress of the switching tube is reduced; 2) the single-switch working mode reduces the control complexity, and the driving circuit has a simple structure; 3) the turn ratio of the coupling inductor is reduced, the volume of the magnetic element is reduced, and the power density is improved; 4) the natural turn-off of all diodes is realized, the switching loss is reduced, and the electric energy conversion efficiency is improved. 5) When the number of the coupling inductance switch capacitor boosting units is even, the voltage stress of the semiconductor device is only related to the output voltage and is not related to the voltage gain. The multi-unit coupling inductance switch capacitor network high-gain direct current converter has a wide application prospect in a new energy distributed power generation system.
Drawings
FIG. 1 is a high gain DC converter with a multi-cell diode-capacitor network; the cascade connection method comprises the following steps that (a) diode capacitor network multi-unit cascade connection is performed, and (b) diode capacitor network single-unit cascade connection is performed;
FIG. 2 is a diagram of a multi-unit coupled inductor-switched capacitor network high-gain DC converter;
FIG. 3 is a basic two-port diode capacitor boosting unit;
fig. 4 shows a multi-unit coupled inductor-switched capacitor network high-gain dc converter (M ═ 1);
fig. 5 shows the main waveforms of a multi-unit coupled inductor-switched capacitor network high-gain dc converter (M is 1);
fig. 6 is a topology structure of a multi-unit coupled inductor-switched capacitor network high-gain dc converter (M is 1) in each operating mode according to the present invention; wherein (a) is the circulation path of the mode 1 current, (b) is the circulation path of the mode 2 current, (c) is the circulation path of the mode 3 current, (d) is the circulation path of the mode 4 current, and (e) is the circulation path of the mode 5 current;
fig. 7 is a simplified analysis waveform after ignoring modes 1 and 3 of the multi-unit coupled inductor-switched capacitor network high-gain dc converter of the present invention (M ═ 1);
fig. 8 shows the relationship between the voltage gain and the duty ratio and the coupling coefficient when N is 3 in the multi-unit coupled inductor-switched capacitor network high-gain dc converter of the present invention (M is 1);
fig. 9 is a relationship between voltage gain and duty ratio when N is 3, and the number of units of the coupling inductor diode capacitor network in the multi-unit coupling inductor switch capacitor network high-gain dc converter of the present invention (M is 1);
fig. 10 shows the relationship between the switching tube voltage stress and the rectifier diode voltage stress and the number of the coupling inductance diode capacitance network units when N is 3 in the multi-unit coupling inductance switching capacitance network high-gain dc converter (M is 1) of the present invention
FIG. 11 shows simulation waveforms (V) of the multi-unit coupled inductor-switched capacitor network high-gain DC converter of the present inventionin＝30V，vo＝540V，dson＝0.6，RL300 Ω); wherein (a) a capacitor C1And C3Voltage, output voltage Vo(b) Leakage inductance current and excitation current (c) diode current iD1、iD3、iD5(ii) a (d) Diode current iD1Partial amplification oscillogram
Detailed Description
The invention is further described below with reference to the accompanying drawings.
Referring to fig. 2, the present invention includes an input terminal power supply VinA controllable switch tube S, a coupling inductor of a secondary multi-winding, a plurality of two-port diode capacitor boosting units, an output rectifier diode, an output capacitor and an output end load RL(ii) a As shown in fig. 3The two-port diode capacitor boosting unit comprises a first diode D1A second diode D2A first DC capacitor C1And a second DC capacitor C2(ii) a First direct current capacitor C1Anode of the first diode D1Anode of (2), second DC capacitor C2Anode of the first diode D1A cathode of (a); first direct current capacitor C1Negative pole of the first diode D is connected with the second diode D2Anode of (2), second DC capacitor C2Negative pole of the first diode D is connected with the second diode D2A cathode of (a); first diode D1And a second diode D2The coupled inductor can be equivalent to a multi-winding ideal transformer with fixed transformation ratio and an excitation inductor LmParallel connected with equivalent primary side leakage inductor LkAre connected in series; input end power supply VinThe positive pole of the controllable switch tube is connected with the positive pole of the primary side of the coupling inductor, and the controllable switch tube S is connected with the negative pole of the primary side of the coupling inductor and the input end power supply VinAnd the two ends of the cathode are simultaneously connected in parallel with the input end of the first two-port diode capacitor boosting unit. The first two-port diode capacitor boosting unit consists of a diode D1,D2And a capacitor C1,C2The other two-port diode capacitor boosting units have the same structure. The coupling inductor secondary side first winding is connected in series between the first two-port diode capacitor boosting unit and the second two-port diode capacitor boosting unit, and the same-name end of the coupling inductor secondary side first winding is located at the input end of the second two-port diode capacitor boosting unit. A secondary side second winding of the coupling inductor is connected in series between the second two-port diode capacitor boosting unit and the third two-port diode capacitor boosting unit, the same-name end is positioned at the output end of the second two-port diode capacitor boosting unit, and so on, the Nth winding of the secondary side of the coupling inductoriThe winding is connected between the ith two-port diode capacitor boosting unit and the (i +1) th two-port diode capacitor boosting unit, the homonymy end is positioned at the connecting side (if i is an even number) of the ith two-port diode capacitor boosting unit, or the homonymy end is positioned at the connecting side (if (i +1) is an even number) of the (i +1) th two-port diode capacitor boosting unit, the output end of the direct-current converter is connected with a rectifier diode D and an output capacitor C in parallel, and the output end of the direct-current converter is connected with an output endL。
The principle of the invention is as follows:
to simplify the analysis, the following assumptions were made for the converter:
1) all power devices are ideal devices, parasitic capacitance and internal equivalent resistance are negligible, and the forward voltage drop is zero when the diode is turned on.
2) Capacitor C1、C2、C3、C4、C5The capacitance value is large enough, and the capacitance voltage is constant in the whole working process.
3) The exciting inductor L m has large inductance value, the exciting current is a constant DC quantity, the coupling coefficient k of the coupling inductor is equal to Lm/(Lm+Lk) And the transformation ratio N is equal to N2/N1The equivalent resistance and parasitic capacitance of the coupling inductance are negligible.
Fig. 4 shows an equivalent circuit of coupled inductor circuit analysis, and the basic operating principle of the multi-unit coupled inductor-switched capacitor network high-gain dc converter (M ═ 1) is as follows:
the key waveforms of the converter during operation are shown in fig. 5, and it can be seen from the waveforms that the circuit is divided into five operation modes in one period, as shown in fig. 6.
Mode 1 (t)0～t1):t0The switch tube S is closed at the moment, the switch current rises from zero due to the equal primary and secondary currents of the transformer, and the diode D1、D2、D3、D4The coupled inductor excitation voltage is still reversed to be negative left and positive right, the excitation current is reduced, the leakage inductance current is rapidly increased, the current flow path is shown in figure 6(a), and the excitation inductor LmEnergy is released to the load through the secondary coil. Diode current iD5Decrease rapidly when the leakage inductance current is equal to the excitation inductance current, i.e. t1Time of day, diode current iD5Dropping to zero and the mode ends.
Mode 2 (t)1～t2):t1Time D5Off, D3、D4Is immediately conducted and current iD3、iD4Slowly increasing from zeroAnd (4) adding. D1、D2Still disconnected, switch tube S continues to conduct. During this mode, the current flow path is as shown in fig. 6 (b). The power supply charges the exciting inductor and simultaneously passes through the secondary coil and the capacitor C1、C2Series capacitor C3、C4And charging in parallel. At this time, the capacitor C5The load is supplied with power separately. t is t2The switch tube is turned off at the moment, and the mode is ended.
Mode 3 (t)2～t3) Diode D at the moment of switching off the switch1、D2Immediately on, the leakage inductance current begins to decrease. The current flow path is shown in fig. 6 (c). D3、D4Remains on, D5And continuing to switch off. The exciting voltage is positive, the current continues to rise, simultaneously the leakage inductance current is sharply reduced, and the secondary coil current and the diode current iD3、iD4And thus decreases rapidly. The load being formed by a capacitor C5And supplying power separately. When the leakage current decreases to be equal to the exciting current, i.e. t3Time of day, diode current iD3、iD4Decreasing to zero, the mode ends.
Mode 4 (t)3～t4):t3Time D3、D4Opening, D5And conducting. The current flow path is shown in fig. 6 (d). The switching tube is continuously disconnected, diode D1、D2Remain on. The excitation voltage is negative in the reverse direction, the excitation current begins to decrease, the leakage inductance current continues to decrease but the decrease rate is greater than the excitation current. When the leakage inductance current is equal to iLmWhen v (N +1), i.e. t4Time of day, diode D1、D2The current drops to zero and the mode ends.
Mode 5 (t)4～t5):t4Time diode D1、D2The current flow path is broken as shown in fig. 6 (e). S, D3、D4Continued disconnection, D5Remain on. The exciting current continues to decrease, and the leakage inductance current is iLm/(N+1)。 t5And (4) switching on the switch tube at the moment, ending the period and entering the next period again.
Because mode i and mode iii times are extremely short,to simplify the analysis, these two modes are negligible. The simplified waveform diagram is shown in fig. 7. Since the average value of the capacitor current period is zero, the diode D1、 D2、D3、D4、D5Is equal to the load current average. The current flowing through the secondary coil is 1/N times of the difference between the leakage inductance current and the excitation inductance current. During mode II, the integral of the secondary coil current over time is the two capacitors C3、C4The amount of charge charged. The amount of charge is shown as the field current I in FIG. 7LmThe area of the above shaded area is 1/N times. During mode IV and mode V, the integral of the secondary current over time is the capacitance C, since the two capacitances are in series3And C4Half of the discharged charge amount, corresponding to the charge amount, is represented as the exciting current I of FIG. 7LmThe area of the shaded area below is 1/N times. Let t in the simplified graph be assumed3At this time, the difference between the leakage inductance current and the excitation current is h. From FIG. 7, it can be derived iD3、iD4At t3The current peak at the moment is equal to h/2N. From FIG. 7, t can also be derived3Time iD1、iD2Has a current peak value of ILmDuring mode V, the leakage current is equal to the secondary winding current, and the leakage current value is I from KC L because the primary-to-secondary current ratio is NLm/(N+1)。
D1、D2、D3、D4The average value of the current periods of (a) is equal and equal to the load current, we can obtain:
Figure RE-GDA0001542196120000091
from the foregoing analysis, the area of the shaded area on the inductor current is twice as large as the area of the shaded area on the inductor current, so that the formula (2) holds.
Figure RE-GDA0001542196120000092
From the above two formulae, Δ D is:
Figure RE-GDA0001542196120000093
during mode II, the excitation inductance voltage and the leakage inductance voltage are respectively expressed as
Figure RE-GDA0001542196120000094
And
Figure RE-GDA0001542196120000095
as shown in fig. 6(b), the following equation can be obtained:
Figure RE-GDA0001542196120000096
Figure RE-GDA0001542196120000097
2VC1+NkVin＝VC3(6)
during mode IV, the magnetizing inductance voltage and the leakage inductance voltage are respectively expressed as
Figure RE-GDA0001542196120000098
And
Figure RE-GDA0001542196120000099
as shown in fig. 6(d), from kirchhoff's voltage law:
Figure RE-GDA00015421961200000910
Figure RE-GDA00015421961200000911
during mode V, the leakage inductance current versus the excitation current relationship is:
Figure RE-GDA0001542196120000101
further, the relationship between the leakage inductance voltage and the excitation voltage during mode V can be obtained.
Figure RE-GDA0001542196120000102
The coupling coefficient k of the coupling inductor is equal to Lm/(Lm+Lk) Further, it can be obtained:
Figure RE-GDA0001542196120000103
meanwhile, the whole loop comprises:
Figure RE-GDA0001542196120000104
the applied volt-second balance for the exciting inductance and the coupling inductance is as follows:
Figure RE-GDA0001542196120000105
Figure RE-GDA0001542196120000106
from equations (3) to (14), the voltage gain expression can be obtained as follows:
Figure RE-GDA0001542196120000107
the voltage gain curves with duty cycle at different coupling coefficients are shown in fig. 8. As can be seen from the figure, the variation in the coupling coefficient has little effect on the gain and is negligible. Therefore, when k is 1, the voltage gain under ideal coupling conditions is expressed as:
Figure RE-GDA0001542196120000108
capacitor C1、C2、C3、C4The voltages are expressed as:
Figure RE-GDA0001542196120000109
Figure RE-GDA00015421961200001010
switch tube S, diode D1、D2、D3、D4、D5The voltage stress expressions are respectively:
Figure RE-GDA0001542196120000111
Figure RE-GDA0001542196120000112
under ideal conditions, the coupling coefficient k is 1, the number of turns of the secondary winding of the coupling electric tube is the same, namely N1:N0＝N2:N0＝···＝NM:N0The voltage gain and the switching tube stress expression of the multi-booster unit circuit are respectively shown in the following table by repeating the analysis process.
Figure RE-GDA0001542196120000113
TABLE 1
As can be seen from table 1, when M is an even number, the voltage stress of the main switching tube and the output diode is only related to the output voltage and not to the voltage gain. Fig. 9 shows the relationship between the voltage gain and the boost duty ratio of the multi-unit coupled inductor-switched capacitor network high-gain dc converter, the coupling inductor transformation ratio and the number of basic units. Fig. 10 shows the relationship between the voltage stress and the voltage gain of the high-gain dc converter power device of the multi-unit coupled inductor-switched capacitor network, the coupling inductance transformation ratio and the number of basic units. Therefore, the voltage gain of the multi-unit module is greatly improved, the voltage stress of the semiconductor device is reduced, and the cost and the conduction loss of the device are further reduced.
MAT L AB/Simulink-based simulation verification of the multi-layerThe working principle and the theoretical analysis of the unit coupling inductance switch capacitor network high-gain direct current converter are carried out. Main circuit parameters: vin＝30V,Lm＝400uH,Lk＝0.5uH, C5＝500uF,C1＝C2＝C3＝C4＝500uF,fsFig. 11 shows leakage inductance current, excitation current and capacitor voltage V of the coupling inductor when the single-unit coupling inductor-switched capacitor network high-gain dc converter operates in a steady state, where N is 3, D is 0.6, and R L is 300 ΩC1、VC3Output voltage VoDiode current iD1、iD3、iD5. Capacitance voltage V in FIG. 11 (a)C1、VC3And an output voltage VoThe simulation results are substantially in agreement with theoretical values of 75V, 240V and 540V. It can be seen from fig. 11(b) and (c) that the main switch is turned on with zero current, and the diodes used are naturally turned off, so that the switching losses are reduced and the converter efficiency is improved.
Obviously, the multi-unit coupling inductance switch capacitor network high-gain direct current converter improves the voltage gain, avoids the limit duty ratio, reduces the voltage stress of a power device, and can effectively improve the electric energy conversion efficiency and the power density. The method has wide application prospect in a new energy distributed power generation system.
While the invention has been described in further detail with reference to specific preferred embodiments thereof, it will be understood by those skilled in the art that various changes in form and details may be made therein without departing from the spirit and scope of the invention as defined by the appended claims.

Claims (1)

1. A multi-unit coupling inductance switch capacitance network high gain DC converter is characterized in that: comprising an input terminal power supply VinA controllable switch tube S, a coupling inductor of a secondary multi-winding, a plurality of two-port diode capacitor boosting units, a diode D, an output capacitor C and an output end load RL；
The coupling inductor is equivalent to a multi-winding ideal transformer and excitation inductor LmParallel connected with leakage inductor LkAre connected in series; input end power supply VinThe positive pole of the controllable switch tube is connected with the positive pole of the primary side of the coupling inductor, and the controllable switch tube S is connected with the negative pole of the primary side of the coupling inductor and the input end power supply VinThe two ends of the negative electrode of the capacitor boosting unit are simultaneously connected in parallel at the input end of the first diode capacitor boosting unit with two ports, and the first diode capacitor boosting unit with two ports is composed of a diode D1,D2And a capacitor C1,C2The other two-port diode capacitor boosting unit has the same structure as the first two-port diode capacitor boosting unit; a coupling inductor secondary side first winding is connected in series between the first two-port diode capacitor boosting unit and the second two-port diode capacitor boosting unit, the end with the same name is positioned at the input end of the second two-port diode capacitor boosting unit, a coupling inductor secondary side second winding is connected in series between the second two-port diode capacitor boosting unit and the third two-port diode capacitor boosting unit, the end with the same name is positioned at the output end of the second two-port diode capacitor boosting unit, and so on, the Nth winding of the coupling inductor secondary sideiThe winding is connected between the ith two-port diode capacitor boosting unit and the (i +1) th two-port diode capacitor boosting unit, if i is an even number, the dotted terminal is positioned at the side connected with the ith two-port diode capacitor boosting unit, if (i +1) is an even number, the dotted terminal is positioned at the side connected with the (i +1) th two-port diode capacitor boosting unit, the output end of the direct current converter is connected with a rectifier diode D and an output capacitor C in parallel, and an output end load R is connected with the output end of the rectifier diode D and the output capacitor C in parallelL(ii) a The two-port diode capacitor boosting unit comprises a first diode Di1A second diode Di2A first DC capacitor Ci1And a second DC capacitor Ci2；
The coupling inductor is connected in series with the anode of the input end of the two ports, and when i is an even number, the same-name end is connected with the first diode Di1When i is odd, the different name end is connected with the first diode Di1Anode of (2), first direct current capacitor Ci1Anode of the first diode Di1Anode of (2), second DC capacitor Ci2Anode of the first diode Di1A cathode of (a); first direct current capacitor Ci1Negative electrode ofSecond diode Di2Anode of (2), second DC capacitor Ci2Negative pole of the first diode D is connected with the second diode Di2A cathode of (a); when i is even number, the different name end of the secondary winding and a second diode Di2The cathode of the voltage boosting unit is the input end of a two-port coupling inductance diode capacitance boosting unit; when i is odd number, the dotted terminal of the secondary winding and the second diode Di2The cathode of the voltage boosting unit is the input end of a two-port coupling inductance diode capacitance boosting unit; first diode Di1And a second diode Di2The anode of the capacitor boosting unit is the output end of a two-port coupling inductance diode capacitor boosting unit; wherein i is more than or equal to 1 and less than or equal to M +1, and M is the number of secondary windings of the coupling inductor;
when the winding number M of the secondary winding of the coupling inductor is 1, the circuit in one period is divided into five working modes when the converter works:
mode 1 (t)0～t1):t0The switch tube S is closed at the moment, the switch current rises from zero due to the equal primary and secondary currents of the transformer, and the diode D1、D2、D3、D4The coupled inductor is turned off after bearing the back voltage, the exciting voltage of the coupled inductor is still reversed to be negative left and positive right, the exciting current is reduced, meanwhile, the leakage inductance current is rapidly increased, and the exciting inductor LmReleasing energy to the load through the secondary coil; diode current iD5Decrease rapidly when the leakage inductance current is equal to the excitation inductance current, i.e. t1Time of day, diode current iD5Drops to zero and the mode ends;
mode 2 (t)1～t2):t1Time D5Off, D3、D4Is immediately conducted and current iD3、iD4Slowly increasing from zero; d1、D2The switch tube S is still disconnected and is continuously conducted; during this mode, the power supply charges the magnetizing inductor while passing through the secondary winding and the capacitor C1、C2Series capacitor C3、C4Charging in parallel; at this time, the capacitor C5Independently supplying power to the load; t is t2The switch tube is disconnected at the moment, and the mode is ended;
mode 3 (t)2～t3) Switch tube is disconnected instantaneously and has two stagesPipe D1、D2Conducting immediately, and reducing leakage inductance current; d3、D4Remains on, D5Continuing to turn off; the exciting voltage is positive, the current continues to rise, simultaneously the leakage inductance current is sharply reduced, and the secondary coil current and the diode current iD3、iD4And thus rapidly decreases; the load being formed by a capacitor C5Independently supplying power; when the leakage current decreases to be equal to the exciting current, i.e. t3Time of day, diode current iD3、iD4When the value is reduced to zero, the mode is ended;
mode 4 (t)3～t4):t3Time D3、D4Opening, D5Conducting; the switching tube is continuously disconnected, diode D1、D2Keeping conduction; the reverse direction of the exciting voltage is negative, the exciting current begins to drop, the leakage inductance current continues to drop, but the dropping rate is greater than the exciting current; when the leakage inductance current is equal to iLmWhen v (N +1) is exceeded, LmFor exciting current, N is the primary-to-secondary current ratio, i.e. t4Time of day, diode D1、D2The current drops to zero and the mode ends;
mode 5 (t)4～t5):t4Time diode D1、D2Disconnecting; s, D3、D4Continued disconnection, D5Keeping conduction; the exciting current continues to decrease, and the leakage inductance current is iLm/(N+1)，LmIs exciting current, and N is primary and secondary current ratio; t is t5And (4) switching on the switch tube at the moment, ending the period and entering the next period again.
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