CN106961222A - A kind of DC DC controlled resonant converters - Google Patents

A kind of DC DC controlled resonant converters Download PDF

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Publication number
CN106961222A
CN106961222A CN201710245707.2A CN201710245707A CN106961222A CN 106961222 A CN106961222 A CN 106961222A CN 201710245707 A CN201710245707 A CN 201710245707A CN 106961222 A CN106961222 A CN 106961222A
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CN
China
Prior art keywords
frequency
resonant
full bridge
switching circuit
bridge switching
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Pending
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CN201710245707.2A
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Chinese (zh)
Inventor
张东华
李国栋
李小兵
杨奇
王媛
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WUHAN ZHONGYUAN ELECTRONICS GROUP Ltd
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WUHAN ZHONGYUAN ELECTRONICS GROUP Ltd
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Priority to CN201710245707.2A priority Critical patent/CN106961222A/en
Publication of CN106961222A publication Critical patent/CN106961222A/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
    • H02M3/3381—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement using a single commutation path
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a kind of DC DC controlled resonant converters, including full bridge switching circuit, electric capacity Crr and switch K1 tie points in series, transformer T and resonant capacitance Cr the second branch roads in series, tie point exports one end with full bridge switching circuit by resonant inductance Lr with one end after the second branch circuit parallel connection and is connected, tie point is connected with the other end after the second branch circuit parallel connection with the full bridge switching circuit output other end, transformer T secondary is connected with output rectifier and filter, also include controlling network B2, controlling network B2 measures the frequency of the PWM waveform for driving full bridge switching circuit and controlling switch K1 disconnects and closed.The present invention is accessed in underloading, is cut out when heavily loaded, it is ensured that underloading voltage stabilization does not lose efficiency.

Description

A kind of DC-DC controlled resonant converters
Technical field
The present invention relates to PFM power conversion technologies field, more particularly to a kind of DC-DC controlled resonant converters, it is adaptable to electronic It is automobile mounted charging and other require that efficient power apparatus is powered.
Background technology
Controlled resonant converter is a kind of DC/DC converters grown up using soft switch technique, by setting up resonance circuit, Switching tube is allowd to carry out break-make switching under no-voltage, with good, low, multiple-channel output direct current power supply of loss of isolation performance etc. Advantage.
Fig. 1 is the electrical block diagram of existing DC/DC controlled resonant converters, using the DC/DC controlled resonant converters as half-bridge LLC Exemplified by controlled resonant converter, the LLC half bridge resonant includes：Full bridge switching circuit, resonance circuit, resonance potential output electricity Road, transformer and output rectifier and filter, the circuit operation principle shown in Fig. 1 are as follows：When Q2 shut-offs, (now, Q1 is not led also It is logical), C1 electric discharges, the resonance current (electric current for flowing through L1, C1) formed by L1, C1 charges to the junction capacity at Q2 two ends, together When the junction capacity at Q1 two ends is discharged, Q1 both end voltages drop is gradually reduced, when Q1 both end voltages are reduced to zero, D1 conductings, Realize Q1 zero voltage switching；D1 is turned on, i.e. Q1 connects input voltage, and input voltage, Q1, L1, C1, L2 constitute current loop, Under input voltage effect, resonance current is raised in SIN function form, and C1 is charged, and flows through L2 exciting current line Property rise, resonance current is more than exciting current, and its difference between current passes through after being converted into transformer secondary winding through transformer primary side winding Exported after rectifying and wave-filtering；
Because Ql switching frequency is less than L1 and resonant capacitance C1 resonant frequency, thus, resonance current passes through half half After the resonance of harmonic period (a quarter harmonic period), Ql charges still in conducting state, continuation to C1, resonance current Be gradually reduced, exciting current is still linearly raised, when resonance current drops to it is equal with exciting current when, difference between current is zero, is made It is zero to obtain transformer primary side winding current, and the electric current for flowing through D3 in output rectifier and filter is zero, D3 shut-offs, i.e., D3 is in electricity Turned off naturally when flowing through zero, so as to realize zero-current switching；
Hereafter, Q1 continues to turn on, and the electric current for flowing through transformer primary side winding is approximately that zero, L2 is no longer clamped by output voltage Position is acted on and as free inductance, so, L1, C1 and L2 composition resonance circuit are carried out in resonance, practical application, L2 inductance value Inductance value much larger than L1, that is to say, that be much larger than by the harmonic period of L1, C1 and L2 resonance circuit constituted by L1, C1 group Into resonance circuit harmonic period, and Q1 turn-on cycle is shorter, thus, it is believed that resonance current is in Q1 turn-on cycle It is held essentially constant, and continues to charge to C1.
Hereafter, Q1 is turned off, and the resonance current deflecting formed by L1, C1 and L2, the junction capacity to Q1 two ends charges, together When the junction capacity at Q2 two ends is discharged, Q2 both end voltages drop is gradually reduced, when Q2 both end voltages are reduced to zero, D2 conductings, Q2 zero voltage switching is realized, now, C1 charge volume reaches maximum；
Q1 shut-offs, D2 conductings, C1 electric discharges, Q2, L1, C1, L2 composition continuous current circuit, resonance current subtract in SIN function form Small, flow through L2 exciting current reduces in linear form, and the amplitude that resonance current reduces is more than the amplitude that exciting current reduces, its Difference between current is exported after being converted into transformer secondary winding through transformer primary side winding after rectifying and wave-filtering；
Because Q2 switching frequency is less than L1 and resonant capacitance C1 resonant frequency, thus, resonance current passes through half half After the resonance of harmonic period, Q2 is still in conducting state, and C1 continues to discharge, and resonance current gradually increases, exciting current still line Property reduction, when resonance current is increased to it is equal with exciting current when, difference between current is zero so that transformer primary side winding current is Zero, the electric current for flowing through D4 in output rectifier and filter is zero, D4 shut-offs, i.e. D4 is turned off naturally in current over-zero, so that real Existing zero-current switching；
Hereafter, Q2 continues to turn on, and the electric current for flowing through transformer primary side winding is approximately that zero, L2 is no longer clamped by output voltage Position is acted on and as free inductance, so, L1, C1 and L2 composition resonance circuit carry out resonance, conducting week of the resonance current in Q2 It is held essentially constant in phase, C1 continues to discharge,
Hereafter, Q2 is turned off, and repeats foregoing schemes.
The functional relation of controlled resonant converter output voltage Vo and input voltage vin and circuit parameter shown in Fig. 1 are such as Shown in formula (1).
In formula (1), M is the ratio of output voltage and input voltage, QsFor quality factor (resonance coefficient), f is switch Frequency, n is transformer primary vice-side winding ratio, f1For resonant frequency, wherein,
In formula, ReIt is resistance of the load equivalent resistance value conversion to converter primary side winding, its computing formula is：
Po=Vo*IoFormula (5)
In formula (5), PoFor the bearing power of output,
Fig. 2 is the controlled resonant converter transfer curve schematic diagram of existing symmetrical half bridge structure, and the transmission function is switch Switching frequency and output voltage characteristic curve.
Referring to Fig. 2 and combination formula (1), in real work, switching frequency is typically chosen in the frequency after M acquirement maximums Rate section, from Figure 2 it can be seen that when switching frequency is raised, output voltage declines, and after switching frequency is increased to certain value, transmission Function characteristic becomes very flat, that is to say, that on the flat characteristic curve, it is desirable to the larger change of switching frequency Scope could meet output voltage small change scope, so, it is necessary to the change of switching frequency when output voltage range is wider Scope is very wide.
From the foregoing it will be appreciated that in the case where circuit structure parameter is determined, output voltage adjusting range is become by existing resonance The limitation of parallel operation transfer function characteristics curve, i.e., can only adjust output voltage by adjusting switching frequency, switching frequency compared with Gao Shi, controlled resonant converter regulating power drastically declines, and adjusting range is smaller, it is impossible to meet the wide model of output voltage in practical application Enclose adjustment.
Further, if extension output voltage adjusting range is, it is necessary to higher switching frequency range, and controlled resonant converter When switching frequency excursion is wide so that transformer and output rectifier and filter design are complicated, it is considered to magnetic member device in circuit The characteristic of part causes the electric capacity in transformer and filter circuit, it is necessary to the requirement according to circuit lowermost switch frequency is designed It is very big with inductance parameters, so that whole controlled resonant converter design is complicated, volume is big, high cost.
Moreover, when switching frequency is higher, switch conduction times are reduced, and the harmonic period of circuit keeps constant, with the Exemplified by during one switch conduction, resonance current after the resonance of half of harmonic period during reducing, due to resonance current Time of reduction not enough, does not have an intersection point with linear elevated exciting current, and the difference between current of resonance current and exciting current is not zero, Transformer primary side winding current is converted into after transformer secondary winding, flows through the electricity of commutation diode in output rectifier and filter Stream is not zero so that commutation diode is turned off in the case where there is electric current to flow through, it is impossible to realize zero-current switching, so as to add Circuit loss, further, because commutation diode can not realize zero-current switching characteristic, causes commutation diode two ends to export Due to voltage spikes is very high, in order to avoid commutation diode punctures, it is necessary to select the commutation diode of high withstand voltage, but the rectification of high withstand voltage The conduction voltage drop of diode is general higher, so as to also increase loss, causes transducer reliability to reduce, and efficiency declines.Equally Ground, when first switch is turned off, it is necessary to which the junction capacity to second switch two ends is discharged so that second switch both end voltage drops When being gradually decrease to zero, the zero voltage switching of second switch is realized, but if switching frequency is higher, then to second switch two ends The time that junction capacity is discharged is inadequate so that when second switch both end voltage drop is not reduced to zero, second switch conducting, this Sample, also increases circuit loss.
The content of the invention
The present invention seeks in view of the above-mentioned problems existing in the prior art there is provided a kind of DC/DC controlled resonant converters, in underloading When access, cut out when heavily loaded, it is ensured that underloading voltage stabilization does not lose efficiency.
The above-mentioned purpose of the present invention is achieved through the following technical solutions：
A kind of DC-DC controlled resonant converters, including full bridge switching circuit, electric capacity Crr and switch K1 tie points in series, Transformer T and resonant capacitance Cr the second branch roads in series, tie point pass through resonant inductance with one end after the second branch circuit parallel connection Lr exports one end with full bridge switching circuit and is connected, and tie point is exported with the other end after the second branch circuit parallel connection with full bridge switching circuit The other end is connected, and transformer T secondary is connected with output rectifier and filter, also including controlling network B2, and controlling network B2 is surveyed Measure the frequency increase of PWM waveform for driving full bridge switching circuit and during more than 2.5Fr, then controlling network B2 controlling switches K1 Closure；When the frequency that controlling network B2 measures the PWM waveform for driving full bridge switching circuit reduces and is less than 2Fr, then control The controlling switch K1 of network B 2 disconnects, and the set of frequency of the PWM waveform of full bridge switching circuit is in resonant frequency F1With resonant frequency F3It Between,
F3=3Fr formula (9)
Wherein, LmFor transformer T primary side inductance value, Cr is resonant capacitance Cr capacitance, and Crr is electric capacity Crr electricity Capacitance, Lr is resonant inductance Lr inductance value.
The present invention has advantages below relative to prior art：
1st, access, cut out when heavily loaded in underloading, it is ensured that underloading voltage stabilization does not lose efficiency；
2nd, while same effect is reached, the number of devices that the present invention is used is few, and technical difficulty is low.In traditional scheme In, it is general to use increase fictitious load or enter PWM mode of operations.The mode of switching at runtime is typically coordinated to carry using fictitious load High efficiency, but need to increase the judgement for accessing or exiting, it is more complicated；Needed using PWM mode of operations in PFM and PWM Switch under two states, two kinds of control models, equivalent to two sets controls are excessively complicated, and the addition of PWM mode can make conversion Device exits Sofe Switch, increase loss；
3rd, parallel network B1 is single electric capacity, and number of devices is few, the access of the network and exits and only needs to simple return difference Compare.
Brief description of the drawings
Fig. 1 is the principle schematic of prior art；
Fig. 2 is the controlled resonant converter transfer curve schematic diagram of existing symmetrical half bridge structure, and the transmission function is switch Switching frequency and output voltage characteristic curve；
Fig. 3 is principle schematic of the invention；
Fig. 4 is the normalized gain curve after addition parallel network.
Embodiment
Below by embodiment, and with reference to accompanying drawing, technical scheme is described in further detail.
Embodiment 1：
As shown in figure 3, a kind of DC-DC controlled resonant converters, including：Full bridge switching circuit (power tube Q1, power tube Q2, work( Rate pipe Q3, power tube Q4), resonance circuit (resonant inductance Lr, resonant capacitance Cr, parallel network B1), transformer (T) and output Current rectifying and wave filtering circuit (commutation diode D1, commutation diode D2, commutation diode D3, commutation diode D4, electric capacity Co).
Electric capacity Crr and switch K1 tie points in series, transformer T and resonant capacitance Cr the second branch roads in series, Tie point exports one end with full bridge switching circuit by resonant inductance Lr with one end after the second branch circuit parallel connection and is connected, tie point It is connected with the other end after the second branch circuit parallel connection with the full bridge switching circuit output other end, transformer T secondary and output rectification filter Wave circuit is connected, and also including controlling network B2, controlling network B2 measures the frequency of the PWM waveform for driving full bridge switching circuit When increasing and being more than 2.5Fr, then controlling network B2 controlling switches K1 is closed；Controlling network B2 is measured for driving full-bridge switch When the frequency of the PWM waveform of circuit reduces and is less than 2Fr, then controlling network B2 controlling switches K1 disconnects, full bridge switching circuit The set of frequency of PWM waveform is in resonant frequency F1With resonant frequency F3Between,
F3=3Fr formula (13)
Wherein, LmFor transformer T primary side inductance value, Cr is resonant capacitance Cr capacitance, and Crr is electric capacity Crr electricity Capacitance, Lr is resonant inductance Lr inductance value.
When its underloading works, parallel network B1 (electric capacity Crr) adds resonance, when resonator frequency is improved, electric capacity Crr's Impedance diminishes, and the voltage that electric capacity Crr and resonant inductance Lr partial pressures are obtained is added on the network that transformer T primary side is connected with Cr；
Transformer T, for entering after line translation to obtain exchange resonance output voltage simultaneously by the exchange resonance input voltage of input It is output to output rectifier and filter；
Output rectifier and filter (commutation diode D1, commutation diode D2, commutation diode D3, commutation diode D4, Electric capacity Co), the exchange resonance output voltage for transformer T to be exported forms direct voltage output after carrying out rectifying and wave-filtering, its The course of work is with described in technical background.
Controlling network B2, the frequency for measuring the PWM waveform for being used to drive full bridge switching circuit, and will measure The frequency and set of frequency value of PWM waveform are compared, and controlling switch K1.；
K1 is switched, for being switched in or out parallel network B1.
Parallel network B1 can select electric capacity Crr, as shown in Figure 3.
The present invention, which is achieved in that, measures PWM waveform for driving full bridge switching circuit by controlling network B2 Frequency, the set of frequency value that the frequency of PWM waveform is set with controlling network B2 is compared：
Controlling network B2 measures the frequency increase of the PWM waveform for driving full bridge switching circuit and more than 2.5Fr, then controls System switch K1 closures, make its gain curve be changed into shown in Fig. 4.Controlling network B2 measures the PWM for driving full bridge switching circuit The frequency of waveform reduces and less than 2Fr, then controlling switch K1 disconnections.
As shown in figure 4, after parallel network B1 (when being electric capacity Crr) access, whole circuit has three resonance points, point It is not that resonant frequency is resonant frequency F1Resonance point 1, the resonance point 2 that resonant frequency is resonant frequency Fr, resonant frequency be humorous Vibration frequency F3Resonance point 3, arranged from small to large according to the resonant frequency of resonance point, respectively resonant frequency F1, resonant frequency Fr and resonant frequency F3：
Wherein, resonant frequency F1For resonant capacitance Cr, transformer T primary sides inductance and resonant inductance Lr resonant frequency；
Resonant frequency Fr is resonant inductance Lr and resonant capacitance Cr resonant frequency；
Resonant frequency F3For resonant inductance Lr and electric capacity Crr resonant frequency.
PWM waveforms for driving full bridge switching circuit (power tube Q1, power tube Q2, power tube Q3, power tube Q4) Set of frequency is in F1And F3Between, when the input of full bridge switching circuit is rated voltage (such as civil power 220V), the frequency of PWM waveform Rate should be Fr.When the input voltage increase of full bridge switching circuit, the frequency increase of PWM waveform, due to adding for parallel network B1 Enter to introduce resonant frequency for resonant frequency F3Resonance point 3, the gain M of DC-DC controlled resonant converters crosses below equation calculating：
Wherein, LmFor transformer T primary side inductance value, VoFor the output voltage of output rectifier and filter, VinFor driving The input voltage of full bridge switching circuit, R is the load resistance of output rectifier and filter；Cr is resonant capacitance Cr capacitance, Crr is electric capacity Crr capacitance, and Lr is resonant inductance Lr inductance value, and S is complex plane parameter, and n is transformer T primary sides and pair The turn ratio of sideline circle.
It is equal to resonant frequency F in the frequency of PWM waveform3When gain M be 0, while the frequency of PWM waveform can also be obtained In resonant frequency F1To resonant frequency F3Between be monotone decreasing, the frequency of input voltage increase PWM waveform also increases, input electricity Pressure reduces, and the frequency of PWM waveform also reduces, when input voltage is rated voltage, efficiency highest.
Specific embodiment described herein is only to spirit explanation for example of the invention.Technology neck belonging to of the invention The technical staff in domain can be made various modifications or supplement to described specific embodiment or be replaced using similar mode Generation, but without departing from the spiritual of the present invention or surmount scope defined in appended claims.

Claims (1)

1. a kind of DC-DC controlled resonant converters, including full bridge switching circuit, it is characterised in that electric capacity Crr and switch K1 are in series Tie point, transformer T and resonant capacitance Cr the second branch roads in series, tie point pass through with one end after the second branch circuit parallel connection Resonant inductance Lr exports one end with full bridge switching circuit and is connected, tie point and the other end and full-bridge switch after the second branch circuit parallel connection The circuit output other end is connected, and transformer T secondary is connected with output rectifier and filter, also including controlling network B2, control When network B 2 measures the frequency increase of the PWM waveform for driving full bridge switching circuit and is more than 2.5Fr, then controlling network B2 is controlled System switch K1 closures；The frequency that controlling network B2 measures the PWM waveform for driving full bridge switching circuit reduces and less than 2Fr When, then controlling network B2 controlling switches K1 disconnects, and the set of frequency of the PWM waveform of full bridge switching circuit is in resonant frequency F1It is harmonious Vibration frequency F3Between,
F r = 1 2 π ( C r × L r )
F 1 = 1 2 π ( C r × ( L r + L m )
F 3 = 1 2 π ( C r r × L r )
F3=3Fr
Wherein, LmFor transformer T primary side inductance value, Cr is resonant capacitance Cr capacitance, and Crr is electric capacity Crr capacitance, Lr is resonant inductance Lr inductance value.
CN201710245707.2A 2017-04-14 2017-04-14 A kind of DC DC controlled resonant converters Pending CN106961222A (en)

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Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107204707A (en) * 2017-07-24 2017-09-26 中国西电电气股份有限公司 A kind of two-way isolation DC/DC converter and its control method for being used to suppress peak voltage
CN107818865A (en) * 2017-09-19 2018-03-20 东南大学 A kind of high frequency centre tap flat surface transformer in LLC half bridge resonant
CN109768711A (en) * 2019-02-28 2019-05-17 深圳市西林电气技术有限公司 A kind of synchronous commutating control circuit and method
CN110729901A (en) * 2019-09-03 2020-01-24 深圳市崧盛电子股份有限公司 Power supply and LED light source
CN113472094A (en) * 2021-08-13 2021-10-01 上海伏达半导体有限公司 Wireless charging transmitting device, resonant circuit, quality factor detection method and processor

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CN103475232A (en) * 2013-09-30 2013-12-25 刘闯 High-precision bidirectional converter for electric energy storage and circulation
US20150124487A1 (en) * 2013-11-04 2015-05-07 Futurewei Technologies, Inc. Adjustable Resonant Apparatus for Power Converters
CN105207483A (en) * 2014-05-30 2015-12-30 纬创资通股份有限公司 Llc resonant power converter
CN105896996A (en) * 2016-06-20 2016-08-24 杭州电子科技大学 Novel variable-structure bidirectional active full-bridge resonant converter

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CN101297465A (en) * 2005-10-25 2008-10-29 皇家飞利浦电子股份有限公司 Power converter
CN101488715A (en) * 2009-02-19 2009-07-22 普天信息技术研究院有限公司 DC/DC resonance converter
CN103475232A (en) * 2013-09-30 2013-12-25 刘闯 High-precision bidirectional converter for electric energy storage and circulation
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CN105896996A (en) * 2016-06-20 2016-08-24 杭州电子科技大学 Novel variable-structure bidirectional active full-bridge resonant converter

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107204707A (en) * 2017-07-24 2017-09-26 中国西电电气股份有限公司 A kind of two-way isolation DC/DC converter and its control method for being used to suppress peak voltage
CN107818865A (en) * 2017-09-19 2018-03-20 东南大学 A kind of high frequency centre tap flat surface transformer in LLC half bridge resonant
CN107818865B (en) * 2017-09-19 2019-05-31 东南大学 A kind of high frequency centre tap flat surface transformer in LLC half bridge resonant
CN109768711A (en) * 2019-02-28 2019-05-17 深圳市西林电气技术有限公司 A kind of synchronous commutating control circuit and method
CN110729901A (en) * 2019-09-03 2020-01-24 深圳市崧盛电子股份有限公司 Power supply and LED light source
CN113472094A (en) * 2021-08-13 2021-10-01 上海伏达半导体有限公司 Wireless charging transmitting device, resonant circuit, quality factor detection method and processor

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Application publication date: 20170718