CN106655793A - Common resonant inductor type wide-input-range LLC resonant converter - Google Patents
Common resonant inductor type wide-input-range LLC resonant converter Download PDFInfo
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- CN106655793A CN106655793A CN201710070060.4A CN201710070060A CN106655793A CN 106655793 A CN106655793 A CN 106655793A CN 201710070060 A CN201710070060 A CN 201710070060A CN 106655793 A CN106655793 A CN 106655793A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
- H02M3/3381—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement using a single commutation path
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
- H02M3/3385—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement with automatic control of output voltage or current
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a common resonant induction type wide-input-range LLC resonant converter and belongs to the technical field of power electronic converters. The common resonant induction type wide-input-range LLC resonant converter comprises an input source, a primary side switch network, a common resonant inductor, two resonant capacitors, two transformers, a secondary side rectifying circuit, an output filter capacitor and an output load; the input voltage range of the converter is widened by using the dynamically adjustable topological structure. The common resonant induction type wide-input-range LLC resonant converter has a special operating mode, and has voltage gain 0.75 times of that of a traditional full-bridge LLC resonant converter, the input voltage range in the single operating mode can be reduced significantly, resonant cavity parameters are optimized, availability of the transformers is improved, device cost is reduced, the power and power density of the converter are increased, and the demand for high efficiency and high power density in wide input range applications is met.
Description
Technical field
The present invention relates to a kind of common resonant inductive type wide input range LLC resonant converter, belongs to Technics of Power Electronic Conversion
Device technical field, especially belongs to isolated DC-direct current energy converter technique field.
Background technology
Increasingly serious with environmental pollution and energy shortage problem, regenerative resource is increasingly subject to people's attention.
Renewable energy power generation form mainly has photovoltaic generation, wind-power electricity generation, water generating and fuel cell-powered etc., and they all have
The characteristics of output voltage range width.Therefore, in order to efficiently utilize regenerative resource, energy waste is reduced, needs one kind
The DC/DC converters that can be worked in wide input voltage range.
In recent years, traditional LLC controlled resonant converter is widely used because of efficiency high, power density height, low cost.It
The Sofe Switch of all power semiconductors can be realized, electromagnetic interference is reduced, high frequency is realized.Tradition shown in accompanying drawing 1 is complete
Shown in the voltage gain expression formula such as formula (1) of bridge LLC resonant converter.It is in document test result indicate that, input voltage range
MrangeAt 1.5 times or so, the whole working range efficiency relative equilibrium of traditional LLC controlled resonant converter.Input voltage range is wider,
Magnetizing inductance (the L of converterm) less, the circulation for causing is bigger, and the efficiency of whole working range is also lower.Therefore, tradition
LLC resonant converter is not appropriate for the wide occasion of input voltage range.
In formula, inductance ratio k=Lm/Lr, switching frequency (fs) one change value f of markn=2 π fs(LrCr)0.5, load (Ro) mark
Change value Q=π2(Lr/Cr)0.5/(8n2Ro)。
In order to expand the input voltage range of traditional LLC controlled resonant converter, document " Z.Liang, R.Guo, G.Wang,
A.Huang.A new wide input range high efficiency photovoltaic inverter[C].IEEE
Energy Conversion Congr.and Expos., Atlanta, USA：IEEE, 2010：2937-2943 " is in accompanying drawing 1
On the basis of propose the mode of dynamic regulation topological structure.As the switching tube S of conventional full bridge LLC resonant converter in accompanying drawing 1P3Place
Yu Changguan, switching tube SP4In it is normally opened when, converter is by the conventional half-bridge LLC resonant converter being equivalent in Fig. 2.Half-bridge LLC
Controlled resonant converter is because of resonant capacitance CrThere is DC offset voltage 0.5Uin, voltage gain only has the one of full-bridge LLC resonant converter
Half, as shown in formula (2).Using both mode of operations (being designated as high-gain mode of operation and low gain mode of operation respectively herein)
After jointly controlling, the transducer gain after conventional full bridge LLC resonant converter is expanded in Fig. 1 is as shown in Figure 3.By formula (1), formula
(2) understand with accompanying drawing 3, input voltage range M of the converter under single mode of operationrange>=2 times, just can guarantee that two kinds of works
The gain linking of operation mode.Although total input voltage range of two mode of operations reaches more than 4 times (2Mrange), but single
Mode of operation input voltage range will be in the case of at least 2 times, efficiency and unbalanced, performance of the converter in whole working range
It is unoutstanding.
In order to further lift the efficiency of each operating point, document " Haibing Hu, Xiang Fang, Frank Chen,
Z.John Shen, Issa Batarseh.A Modified High-Efficiency LLC Converter With Two
Transformers for Wide Input-Voltage Range Applications[J].IEEE Trans.Power
Electron., Apr.2013,28 (4)：1946-1960 " proposes dual transformer molded breadth input range LLC as shown in Figure 4
Controlled resonant converter.On the basis of original high-gain or low gain mode of operation, by the second transformer (T2) incision with
It is no, a total of four kinds of mode of operations of dual transformer type LLC resonant converter.Every kind of mode of operation input voltage range is at 1.5 times
Left and right, hence it is evident that improve the efficiency in whole working range.But wherein under two kinds of mode of operations, transformer (T2) be shorted,
Transmission energy, does not reduce magnetic core utilization rate.On hardware is constituted, secondary rectifying tube number is more, many short-circuit transformations of former limit
Device (T2) two switching tube (SP5And SP6), corresponding drive circuit (as isolation optocoupler drives) and supervisor (SP1、SP2、SP3With
SP4) drive circuit (such as charge pump half-bridge driven chip) is inconsistent, increased the complexity of hardware.
In the occasion such as fuel cell-powered, the input voltage range of converter is at 2～3 times.Above two scheme
Total input voltage range design load reaches 4 times, it appears wide, the device cost of converter can be brought again and is increased and efficiency sacrifice.
The content of the invention
The purpose of the present invention is, for the deficiencies in the prior art, for wide input voltage range occasion a kind of common resonant to be provided
Inductive type wide input range LLC resonant converter.
The purpose of the present invention is achieved through the following technical solutions：
A kind of common resonant inductive type wide input range LLC resonant converter is by input source (Uin), primary side switch net
Network (10), common resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2), the first transformer (T1), second
Transformer (T2), secondary side rectification circuit (20), output filter capacitor (Co) and output loading (Ro) constitute, wherein the first transformer
(T1) former limit magnetizing inductance value be Lm1, the second transformer (T2) former limit magnetizing inductance value be Lm2；The primary side switch network
(10) input two ends respectively with input source (Uin) two ends be connected, output end b and the first resonance of primary side switch network (10)
Electric capacity (Cr1) one end be connected, the first resonant capacitance (Cr1) other end and the first transformer (T1) primary side winding different name end phase
Even, the first transformer (T1) primary side winding Same Name of Ends and the second transformer (T2) primary side winding Same Name of Ends, common resonant inductance
(Lr) one end be connected, common resonant inductance (Lr) the other end be connected with output end a of primary side switch network (10), second become
Depressor (T2) primary side winding different name end and the second resonant capacitance (Cr2) one end be connected, the second resonant capacitance (Cr2) the other end
It is connected with output end c of primary side switch network (10), the first transformer (T1) vice-side winding Same Name of Ends and secondary side rectification circuit
(20) input d is connected, the input e of secondary side rectification circuit (20) and the second transformer (T2) vice-side winding different name end phase
Even, the second transformer (T2) vice-side winding Same Name of Ends and the first transformer (T1) vice-side winding different name end be connected, secondary rectification
The output two ends of circuit (20) respectively with output filter capacitor (Co) two ends, output loading (Ro) two ends be connected.
Primary side switch network (10) the output positive pulse amplitude is Uin, negative pulse amplitude be-UinOr 0, positive negative pulse stuffing width
Spend the square-wave voltage u for 50%abAnd uac, and the phase place of the two square-wave voltages is consistent.
The primary side switch network (10) is two bridge arm switching networks, and it is by first switch pipe (SP1), second switch pipe
(SP2), the 3rd switching tube (SP3) and the 4th switching tube (SP4) constitute, first switch pipe (SP1) drain electrode and the 3rd switching tube
(SP3) drain electrode, input source (Uin) positive pole be connected, first switch pipe (SP1) source electrode and second switch pipe (SP2) drain electrode,
Primary side switch network (10) output end a is connected, second switch pipe (SP2) source electrode and the 4th switching tube (SP4) source electrode, input
Source (Uin) negative pole, primary side switch network (10) output end c be connected, the 4th switching tube (SP4) drain electrode and the 3rd switching tube
(SP3) source electrode, primary side switch network (10) output end b be connected.
The primary side switch network (10) is three bridge arm switching networks, and it is by first switch pipe (SP1), second switch pipe
(SP2), the 3rd switching tube (SP3), the 4th switching tube (SP4), the 5th switching tube (SP5) and the 6th switching tube (SP6) constitute, first
Switching tube (SP1) drain electrode and the 3rd switching tube (SP3) drain electrode, the 5th switching tube (SP5) drain electrode, input source (Uin) positive pole
It is connected, first switch pipe (SP1) source electrode and second switch pipe (SP2) drain electrode, primary side switch network (10) output end a be connected,
Second switch pipe (SP2) source electrode and the 4th switching tube (SP4) source electrode, the 6th switching tube (SP6) source electrode, input source (Uin)
Negative pole is connected, the 4th switching tube (SP4) drain electrode and the 3rd switching tube (SP3) source electrode, primary side switch network (10) output end b
It is connected, the 6th switching tube (SP6) drain electrode and the 5th switching tube (SP5) source electrode, primary side switch network (10) output end c be connected.
The secondary side rectification circuit (20) is full bridge rectifier, and it is by the first commutation diode (D1), the second rectification two
Pole pipe (D2), the 3rd commutation diode (D3) and the 4th commutation diode (D4) constitute, the first commutation diode (D1) anode and
The input d of secondary side rectification circuit (20), the second commutation diode (D2) negative electrode be connected, the second commutation diode (D2) sun
Pole and the 4th commutation diode (D4) anode, output filter capacitor (Co) negative pole, output loading (Ro) negative pole be connected, the
Four commutation diode (D4) negative electrode and secondary side rectification circuit (20) input e, the 3rd commutation diode (D3) anode phase
Even, the 3rd commutation diode (D3) negative electrode and the first commutation diode (D1) negative electrode, output filter capacitor (Co) positive pole,
Output loading (Ro) positive pole be connected.
The secondary side rectification circuit (20) is a kind of voltage doubling rectifing circuit, and it is by the first commutation diode (D1), it is second whole
Stream diode (D2), the first voltage multiplying rectifier electric capacity (Co1) and the second voltage multiplying rectifier electric capacity (Co2) constitute, the first commutation diode
(D1) anode and secondary side rectification circuit (20) input d, the second commutation diode (D2) negative electrode be connected, the second rectification two
Pole pipe (D2) anode and the second voltage multiplying rectifier electric capacity (Co2) negative pole, output filter capacitor (Co) negative pole, output loading (Ro)
Negative pole be connected, the second voltage multiplying rectifier electric capacity (Co2) positive pole and secondary side rectification circuit (20) input e, the first voltage multiplying rectifier
Electric capacity (Co1) negative pole be connected, the first voltage multiplying rectifier electric capacity (Co1) positive pole and the first commutation diode (D1) negative electrode, output
Filter capacitor (Co) positive pole, output loading (Ro) positive pole be connected.
The secondary side rectification circuit (20) is another kind of voltage doubling rectifing circuit, and it is by the first commutation diode (D1), second
Commutation diode (D2), auxiliary voltage multiplying rectifier electric capacity (Caux) constitute, aid in voltage multiplying rectifier electric capacity (Caux) negative pole and secondary it is whole
The input d of current circuit (20) is connected, and aids in voltage multiplying rectifier electric capacity (Caux) positive pole and the first commutation diode (D1) sun
Pole, the second commutation diode (D2) negative electrode be connected, the first commutation diode (D1) negative electrode and output filter capacitor (Co) just
Pole, output loading (Ro) positive pole be connected, the second commutation diode (D2) anode and secondary side rectification circuit (20) input e,
Output filter capacitor (Co) negative pole, output loading (Ro) negative pole be connected.
Technical solution of the present invention is that traditional LLC resonator is split into two with the essential distinction of existing technical scheme
Branch road, two branch road common resonant inductance, each containing a resonant capacitance and a transformer, the series connection of two transformer secondaries,
Two transformers work always simultaneously, when resonant capacitance DC offset voltage is 0 in wherein one branch road, and in another branch road
Resonant capacitance DC offset voltage is 0.5UinWhen, converter occurs in that mode of operation specific to the present invention, as shown in formula (3)
Voltage gain, be 0.75 times, 1.5 times of formula (2) conventional half-bridge LLC converters of formula (1) conventional full bridge LLC converter, this
The input voltage range of single mode of operation can be obviously reduced, optimal cavity parameter improves transformer utilization factor, reduces device
Part cost, the efficiency and power density of Lifting Transform device meet wide input voltage range occasion high efficiency and high power density
Demand.
The present invention has the advantages that：
(1) input voltage range under single mode of operation is obviously reduced, and LLC resonator parameters are optimized, and is lifted whole
The efficiency of individual working range；
(2) two transformers work always simultaneously, and utilization rate is improved, and reduces volume, hoisting power density；
(3) power semiconductor number is obviously reduced, reduces cost, hoisting power density；
(4) drive circuit of primary side switch pipe is consistent, reduces cost.
Description of the drawings
Accompanying drawing 1 is conventional full bridge LLC resonant converter schematic diagram；
Accompanying drawing 2 is conventional half-bridge LLC resonant converter schematic diagram；
Accompanying drawing 3 is after conventional full bridge LLC resonant converter is jointly controlled using two kinds of mode of operations of high-gain and low gain
Voltage gain schematic diagram；
Accompanying drawing 4 is traditional double transformer type wide input range LLC resonant converter schematic diagram；
Accompanying drawing 5 is a kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of the present invention；
Accompanying drawing 6 is that primary side switch network (10) of the present invention is adopted using two bridge arm switching networks, secondary side rectification circuit (20)
A kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of full bridge rectifier；
Accompanying drawing 7 is that primary side switch network (10) of the present invention is adopted using two bridge arm switching networks, secondary side rectification circuit (20)
A kind of a kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of voltage doubling rectifing circuit；
Accompanying drawing 8 is that primary side switch network (10) of the present invention is adopted using two bridge arm switching networks, secondary side rectification circuit (20)
A kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of another kind of voltage doubling rectifing circuit；
Accompanying drawing 9 is that primary side switch network (10) of the present invention is adopted using three bridge arm switching networks, secondary side rectification circuit (20)
A kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of full bridge rectifier；
Accompanying drawing 10 is that primary side switch network (10) of the present invention is adopted using three bridge arm switching networks, secondary side rectification circuit (20)
A kind of a kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of voltage doubling rectifing circuit；
Accompanying drawing 11 is that primary side switch network (10) of the present invention is adopted using three bridge arm switching networks, secondary side rectification circuit (20)
A kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of another kind of voltage doubling rectifing circuit；
Accompanying drawing 12 is the primary side switch pipe control strategy schematic diagram in low gain mode of operation of converter shown in accompanying drawing 6；
Accompanying drawing 13 is the exemplary operation waveform diagram in middle gain mode of operation of converter shown in accompanying drawing 6；
Accompanying drawing 14～16 is the t in accompanying drawing 13 of converter shown in accompanying drawing 60～t1、t1～t2、t2～t3Each mould in time period
State equivalent circuit (sense of current is labeled as positive direction in figure)；
Accompanying drawing 17 is Fundamental Wave Equivalent Circuit schematic diagram of the converter shown in accompanying drawing 6 in middle gain mode of operation；
Accompanying drawing 18 be converter shown in accompanying drawing 6 adopt in two kinds of mode of operations of gain and low gain jointly control after voltage
Gain schematic diagram；
Accompanying drawing 19 is the primary side switch pipe control strategy schematic diagram in high-gain mode of operation of converter shown in accompanying drawing 9；
Accompanying drawing 20 is that converter shown in accompanying drawing 9 is jointly controlled using high-gain, three kinds of mode of operations of middle gain and low gain
Voltage gain schematic diagram afterwards；
Designation in the figures above：UinFor input source；10 is primary side switch network；A, b, c are primary side switch network
(10) three output ports；20 is secondary side rectification circuit；D, e are two input ports of secondary side rectification circuit (20)；LrFor
Common resonant inductance；CrFor resonant capacitance；Cr1For the first resonant capacitance；Cr2For the second resonant capacitance；T1For the first transformer；T2
For the second transformer；LmFor the former limit magnetizing inductance of transformer；Lm1For the first transformer (T1) former limit magnetizing inductance；Lm2For
Two transformer (T2) former limit magnetizing inductance；N: 1 is transformer turns ratio；n1: 1 or n1: be first transformer (T at 1: 11) original it is secondary
The side turn ratio；n2: 1 or n2: be second transformer (T at 1: 12) the former secondary turn ratio；SP1、SP2、SP3、SP4、SP5And SP6Respectively former limit
First, second, third, fourthth, the 5th and the 6th switching tube；D1、D2、D3、D4、D5、D6、D7、D8Respectively first, second,
3rd, the four, the five, the six, the 7th and the 8th commutation diode；CoFor output filter capacitor；Co1And Co2For first, second multiplication of voltage
Commutation capacitor；CauxTo aid in voltage multiplying rectifier electric capacity；RoFor output loading；UoFor output voltage；IoFor output current；M is voltage
Gain；fnTo mark a Switching frequency；fnminFor the change value of mark one of lowermost switch frequency；fnmaxFor the mark one of highest switching frequency
Change value；iLr、iLr1、iLr2Respectively flow through Lr、Cr1、Cr2Electric current；im1、im2Respectively flow through Lm1、Lm2Electric current；isTo flow through
The electric current of two transformer secondaries；uLr、uCr1、uCr2Respectively Lr、Cr1、Cr2The voltage at two ends；uGSP1、uGSP2、uGSP3、uGSP4、
uGSP5And uGSP6Respectively switching tube SP1、SP2、SP3、SP4、SP5And SP6Driving voltage；uabFor (10) two, primary side switch network
Voltage between port a, b, uacFor the voltage between two ports a, c；UiacFor positive negative pulse stuffing amplitude ± Uin, pulse width
The fundametal compoment of 50% square-wave voltage；ILr、ILr1、ILr2、Im1、Im2、IsRespectively iLr、iLr1、iLr2、im1、im2、isFundamental wave
Component；ULr、UCr1、UCr2Respectively uLr、uCr1、uCr2Fundametal compoment；t0、t1、t2、t3And t4For the time.
Specific embodiment
Technical scheme is described in detail with reference to accompanying drawing.
As shown in Figure 5, a kind of common resonant inductive type wide input range LLC resonant converter is by input source
(Uin), primary side switch network (10), common resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2),
One transformer (T1), the second transformer (T2), secondary side rectification circuit (20), output filter capacitor (Co) and output loading (Ro) structure
Into wherein the first transformer (T1) former limit magnetizing inductance value be Lm1, the second transformer (T2) former limit magnetizing inductance value be Lm2；
The input two ends of the primary side switch network (10) respectively with input source (Uin) two ends be connected, primary side switch network (10) it is defeated
Go out to hold b and the first resonant capacitance (Cr1) one end be connected, the first resonant capacitance (Cr1) other end and the first transformer (T1) former limit
The different name end of winding is connected, the first transformer (T1) primary side winding Same Name of Ends and the second transformer (T2) primary side winding it is of the same name
End, common resonant inductance (Lr) one end be connected, common resonant inductance (Lr) the other end and primary side switch network (10) output
End a is connected, the second transformer (T2) primary side winding different name end and the second resonant capacitance (Cr2) one end be connected, the second resonance electricity
Hold (Cr2) the other end be connected with output end c of primary side switch network (10), the first transformer (T1) vice-side winding Same Name of Ends
It is connected with the input d of secondary side rectification circuit (20), the input e of secondary side rectification circuit (20) and the second transformer (T2) pair
Side winding different name end is connected, the second transformer (T2) vice-side winding Same Name of Ends and the first transformer (T1) vice-side winding different name
End is connected, the output two ends of secondary side rectification circuit (20) respectively with output filter capacitor (Co) two ends, output loading (Ro) two ends phase
Even.
In the present invention, primary side switch network (10) the output positive pulse amplitude is Uin, negative pulse amplitude be-UinOr
0th, positive negative pulse stuffing width is 50% square-wave voltage uabAnd uac, and the phase place of the two square-wave voltages is consistent.In order to realize
This purpose, the primary side switch network (10) can be two bridge arm switching networks or three bridge arm switching networks.
As shown in accompanying drawing 6, accompanying drawing 7 or accompanying drawing 8, the primary side switch network (10) is two bridge arm switching networks, and it is by
One switching tube (SP1), second switch pipe (SP2), the 3rd switching tube (SP3) and the 4th switching tube (SP4) constitute, first switch pipe
(SP1) drain electrode and the 3rd switching tube (SP3) drain electrode, input source (Uin) positive pole be connected, first switch pipe (SP1) source electrode and
Second switch pipe (SP2) drain electrode, primary side switch network (10) output end a be connected, second switch pipe (SP2) source electrode and the 4th
Switching tube (SP4) source electrode, input source (Uin) negative pole, primary side switch network (10) output end c be connected, the 4th switching tube (SP4)
Drain electrode and the 3rd switching tube (SP3) source electrode, primary side switch network (10) output end b be connected.
As shown in accompanying drawing 9, accompanying drawing 10 or accompanying drawing 11, the primary side switch network (10) is three bridge arm switching networks, it by
First switch pipe (SP1), second switch pipe (SP2), the 3rd switching tube (SP3), the 4th switching tube (SP4), the 5th switching tube (SP5)
With the 6th switching tube (SP6) constitute, first switch pipe (SP1) drain electrode and the 3rd switching tube (SP3) drain electrode, the 5th switching tube
(SP5) drain electrode, input source (Uin) positive pole be connected, first switch pipe (SP1) source electrode and second switch pipe (SP2) drain electrode,
Primary side switch network (10) output end a is connected, second switch pipe (SP2) source electrode and the 4th switching tube (SP4) source electrode, the 6th
Switching tube (SP6) source electrode, input source (Uin) negative pole be connected, the 4th switching tube (SP4) drain electrode and the 3rd switching tube (SP3)
Source electrode, primary side switch network (10) output end b are connected, the 6th switching tube (SP6) drain electrode and the 5th switching tube (SP5) source electrode,
Primary side switch network (10) output end c is connected.
As shown in accompanying drawing 6 or accompanying drawing 9, the secondary side rectification circuit (20) is full bridge rectifier, and it is by the first rectification two
Pole pipe (D1), the second commutation diode (D2), the 3rd commutation diode (D3) and the 4th commutation diode (D4) constitute, first is whole
Stream diode (D1) anode and secondary side rectification circuit (20) input d, the second commutation diode (D2) negative electrode be connected, the
Two commutation diode (D2) anode and the 4th commutation diode (D4) anode, output filter capacitor (Co) negative pole, output it is negative
Carry (Ro) negative pole be connected, the 4th commutation diode (D4) negative electrode and secondary side rectification circuit (20) input e, the 3rd rectification
Diode (D3) anode be connected, the 3rd commutation diode (D3) negative electrode and the first commutation diode (D1) negative electrode, output filter
Ripple electric capacity (Co) positive pole, output loading (Ro) positive pole be connected.
As shown in accompanying drawing 7 or accompanying drawing 10, the secondary side rectification circuit (20) is a kind of voltage doubling rectifing circuit, and it is whole by first
Stream diode (D1), the second commutation diode (D2), the first voltage multiplying rectifier electric capacity (Co1) and the second voltage multiplying rectifier electric capacity (Co2) structure
Into the first commutation diode (D1) anode and secondary side rectification circuit (20) input d, the second commutation diode (D2) the moon
Extremely it is connected, the second commutation diode (D2) anode and the second voltage multiplying rectifier electric capacity (Co2) negative pole, output filter capacitor (Co)
Negative pole, output loading (Ro) negative pole be connected, the second voltage multiplying rectifier electric capacity (Co2) positive pole and secondary side rectification circuit (20)
Input e, the first voltage multiplying rectifier electric capacity (Co1) negative pole be connected, the first voltage multiplying rectifier electric capacity (Co1) positive pole and the first rectification
Diode (D1) negative electrode, output filter capacitor (Co) positive pole, output loading (Ro) positive pole be connected.
As shown in accompanying drawing 8 or accompanying drawing 11, the secondary side rectification circuit (20) is another kind of voltage doubling rectifing circuit, and it is by first
Commutation diode (D1), the second commutation diode (D2), auxiliary voltage multiplying rectifier electric capacity (Caux) constitute, aid in voltage multiplying rectifier electric capacity
(Caux) negative pole be connected with the input d of secondary side rectification circuit (20), aid in voltage multiplying rectifier electric capacity (Caux) positive pole and first
Commutation diode (D1) anode, the second commutation diode (D2) negative electrode be connected, the first commutation diode (D1) negative electrode and defeated
Go out filter capacitor (Co) positive pole, output loading (Ro) positive pole be connected, the second commutation diode (D2) anode and secondary rectification
The input e of circuit (20), output filter capacitor (Co) negative pole, output loading (Ro) negative pole be connected.
The purpose of the present invention is that the isolated DC of high efficiency and high power density is realized for wide input voltage range occasion
Conversion, in order to realize the purpose, the present invention widens the input voltage range of converter by the way of dynamic regulation topological structure.
Traditional LLC resonator is split into two branch roads by the present invention, and two branch road common resonant inductance each contain a resonant capacitance
With a transformer, two transformer secondaries series connection, two transformers work always simultaneously, when resonant capacitance in wherein one branch road
DC offset voltage is 0, and resonant capacitance DC offset voltage is 0.5U in another branch roadinWhen, converter occurs in that this
Bright specific mode of operation, the voltage gain as shown in formula (3) is 0.75 times, formula of formula (1) conventional full bridge LLC converter
(2) 1.5 times of conventional half-bridge LLC converters, this can be obviously reduced the input voltage range of single mode of operation, optimize resonance
Chamber parameter, improves transformer utilization factor, reduces device cost, and the efficiency and power density of Lifting Transform device meet wide input electricity
The demand of pressure scope occasion high efficiency and high power density.
Below with the primary side switch network (10) shown in accompanying drawing 6 using two bridge arm switching networks, secondary side rectification circuit (20)
As a example by using a kind of common resonant inductive type wide input range LLC resonant converter of full bridge rectifier, illustrate the present invention's
Operation principle.In accompanying drawing 6, Lm1=Lm2=2Lm, Cr1=Cr2=0.5Cr, n1=n2=2n.In existing document, in order to meet work(
Rate demand, converter resonant capacitance CrOften need multiple thin-film capacitors in parallel.Therefore, compared with converter in existing document, accompanying drawing 6
In converter resonant capacitance volume will not increase.The converter adopts VFC, low gain mode of operation and middle gain work
Primary side switch pipe control strategy under operation mode is respectively as shown in accompanying drawing 12 and accompanying drawing 13.
In the low gain mode of operation of accompanying drawing 12, the switching tube (S of converter former limit the 3rd shown in accompanying drawing 6P3) drive uGSP3
Keep often closing, the 4th switching tube (SP4) drive uGSP4Maintain a normally open, first switch pipe (SP1) drive uGSP1With second switch pipe
(SP2) drive uGSP2For the complementary conducting of dutycycle 50%.The square-wave voltage u of switching network (10) outputab、uacPositive pulse width
Value is all Uin, negative pulse amplitude all for 0, positive negative pulse stuffing width be all 50%, both phase places are consistent.Under low gain mode of operation,
The converter can be equivalent to the conventional half-bridge LLC converters in Fig. 2, shown in voltage gain such as formula (2), not remake herein in detail
Description.
Accompanying drawing 13 gives primary side switch network (10) shown in accompanying drawing 6 using two bridge arm switching networks, secondary rectified current
Road (20) is worked using a kind of common resonant inductive type wide input range LLC resonant converter of full bridge rectifier in middle gain
Exemplary operation waveform during pattern.In accompanying drawing 13, converter former limit first switch pipe (SP1) drive uGSP1With the 4th switch
Pipe (SP4) drive uGSP4It is consistent, second switch pipe (SP2) drive uGSP2With the 3rd switching tube (SP3) drive uGSP3Keep one
Cause, uGSP1And uGSP2For the complementary conducting of dutycycle 50%.The square-wave voltage u of switching network (10) outputabPositive negative pulse stuffing amplitude
For ± Uin, square-wave voltage uacPositive pulse amplitude is Uin, negative pulse amplitude be 0, uab、uacPositive negative pulse stuffing width is all 50%,
Both phase places are consistent.
t0Moment, former limit first switch pipe (SP1) and the switching tube (S of former limit the 4thP4) simultaneously turn off, four switching tubes of former limit
(SP1、SP2、SP3And SP4) all in off state, secondary current isFor 0, four rectifying tube (D of secondary1、D2、D3And D4) do not lead
It is logical, the magnetizing inductance (L of the first transformerm1), the magnetizing inductance (L of the second transformerm2) with shared resonant inductance (Lr), it is first humorous
Shake electric capacity (Cr1), the second resonant capacitance (Cr2) common resonance, in the process, former limit second switch pipe (SP2) and the 3rd switch
Pipe (SP3) drain-source voltage is reduced to 0, is that no-voltage is opened and got ready, output filter capacitor (Co) to output loading (Ro) supply
Electricity, t0～t1Mode equivalent circuit in time period is as shown in Figure 14.
t1Moment, former limit second switch pipe (SP2) and the 3rd switching tube (SP3) realize that no-voltage is open-minded, the first transformer
Magnetizing inductance (Lm1), the magnetizing inductance (L of the second transformerm2) it is output (Uo) it is refracted to the voltage reversal clamp of former limit, im1、
im2Electric current linear decline, common resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2) common resonance, it is defeated
Enter source (Uin) provide energy, i to resonator and loadLr1With im1Difference and secondary refraction electric current is/n1It is equal, iLr2With im2
Difference and secondary refraction electric current is/n2It is equal, secondary the second commutation diode (D2) and the 3rd commutation diode (D3) middle stream
Overcurrent is, with output filter capacitor (Co) common to output loading (Ro) power supply, t1～t2Mode equivalent circuit in time period
As shown in Figure 15.
t2Moment, resonance current (i equal with exciting curentLr1=im1, iLr2=im2), the second commutation diode (D2) and the
Three commutation diode (D3) realize zero-current switching, the magnetizing inductance (L of the first transformerm1), the magnetizing inductance of the second transformer
(Lm2) and secondary disengagement, with shared resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2) common resonance,
Input source (Uin) to resonator storage energy, output filter capacitor (Co) to output loading (Ro) power supply, t2～t3In time period
Mode equivalent circuit is as shown in Figure 16.
t3Moment, former limit second switch pipe (SP2) and the 3rd switching tube (SP3) simultaneously turn off, lower half switch periods start,
The course of work is similar to, and narration is not repeated.
In the whole work process of accompanying drawing 13, the first resonant capacitance (Cr1) DC offset voltage be 0, the second resonance electricity
Hold (Cr2) DC offset voltage be 0.5Uin.Accompanying drawing 17 is Fundamental Wave Equivalent Circuit of the converter under middle gain mode of operation,
Using fundamental Wave Analysis derivation converter voltage gain now, as shown in formula (3).Voltage gain under middle gain mode of operation
It is 0.75 times, 1.5 times of formula (2) conventional half-bridge LLC converters of formula (1) conventional full bridge LLC converter.Middle gain mode of operation
It is mode of operation specific to the present invention.
After being jointly controlled using two kinds of mode of operations of low gain and middle gain, the voltage gain model of converter shown in accompanying drawing 6
Enclose and obtained obvious extension, as shown in Figure 18.From formula (2), formula (3) and accompanying drawing 21, the converter is in single work
Input voltage range M under patternrangeWhen >=1.5 times, it is ensured that mode of operation low gain mode of operation and middle gain work
The gain linking of pattern.Therefore, the total input voltage range under two mode of operations can reach more than 2.25 times
(1.5Mrange).Compared with the converter in existing document, total input voltage range of converter shown in accompanying drawing 6 is attached at 2.25 times
When near (such as 2.5 times of input voltage ranges of some fuel cell-powered occasions), because of the input voltage model under single mode of operation
Enclose and substantially narrow, efficiency performance is preferable.
Below with the primary side switch network (10) shown in accompanying drawing 9 using three bridge arm switching networks, secondary side rectification circuit (20)
As a example by using a kind of common resonant inductive type wide input range LLC resonant converter of full bridge rectifier, this is further illustrated
The operation principle of invention.In accompanying drawing 9, Lm1=Lm2=2Lm, Cr1=Cr2=0.5Cr, n1=n2=2n.The converter adopts frequency conversion
Control.Compared with converter shown in accompanying drawing 6, converter shown in accompanying drawing 9 has three kinds of mode of operations, more a kind of high-gain Working mould
Formula, its primary side switch pipe control strategy is as shown in Figure 19.In figure, converter former limit first switch pipe (SP1) drive uGSP1With
4th switching tube (SP4) drive uGSP4, the 6th switching tube (SP6) drive uGSP6It is consistent, second switch pipe (SP2) drive uGSP2
With the 3rd switching tube (SP3) drive uGSP3, the 5th switching tube (SP5) drive uGSP5It is consistent, uGSP1And uGSP2For dutycycle 50%
Complementation conducting.The square-wave voltage u of switching network (10) outputab、uacPositive negative pulse stuffing amplitude all be ± Uin, positive negative pulse stuffing width
Degree is all 50%, and both phase places are consistent.Under high-gain mode of operation, the converter can be equivalent to conventional full bridge LLC in Fig. 1
Converter, shown in voltage gain such as formula (1), is no longer described in detail herein.
In middle gain mode of operation, the converter former limit the 5th switching tube (SP5) drive uGSP5Keep often closing, the 6th opens
Close pipe (SP6) drive uGSP6Maintain a normally open, first switch pipe (SP1) drive uGSP1With the 4th switching tube (SP4) drive uGSP4Keep one
Cause, second switch pipe (SP2) drive uGSP2With the 3rd switching tube (SP3) drive uGSP3It is consistent, uGSP1And uGSP2For dutycycle
50% complementary conducting.The square-wave voltage u of switching network (10) outputabPositive negative pulse stuffing amplitude is ± Uin, square-wave voltage uacJust
Pulse amplitude is Uin, negative pulse amplitude be 0, uab、uacPositive negative pulse stuffing width is all 50%, and both phase places are consistent.In middle gain work
Under operation mode, the converter can be equivalent to the converter shown in accompanying drawing 6, shown in voltage gain such as formula (3), not remake herein in detail
Thin description.
In low gain mode of operation, the converter former limit the 3rd switching tube (SP3) drive uGSP3With the 5th switching tube (SP5)
Drive uGSP5Keep often closing, the 4th switching tube (SP4) drive uGSP4With the 6th switching tube (SP6) drive uGSP6Maintain a normally open, first
Switching tube (SP1) drive uGSP1With second switch pipe (SP2) drive uGSP2For the complementary conducting of dutycycle 50%.Switching network (10) is defeated
The square-wave voltage u for going outab、uacPositive pulse amplitude all be Uin, negative pulse amplitude all for 0, positive negative pulse stuffing width be all 50%,
Both phase places are consistent.Under low gain mode of operation, the converter can be equivalent to the conventional half-bridge LLC converters in Fig. 2, voltage
Shown in gain such as formula (2), no longer it is described in detail herein.
After being jointly controlled using three kinds of mode of operations, the voltage gain scope of converter shown in accompanying drawing 9 has been obtained significantly
Extension, as shown in Figure 20.From formula (1), formula (2), formula (3) and accompanying drawing 20, the converter is under single mode of operation
Input voltage range Mrange>=1.5 times, it is ensured that the gain linking of low gain mode of operation and middle gain mode of operation.Cause
This, the input voltage range under three mode of operations can reach more than 3 times (2Mrange).With the converter phase in existing document
Than, total input voltage range of the converter shown in accompanying drawing 9 at 3 times, because the input voltage range under single mode of operation it is bright
Aobvious to narrow, efficiency performance is preferable.
It can be seen from the description of above-mentioned two embodiment, compared with the converter in existing document, power of the present invention is partly led
Body device count is less, and the drive circuit of primary side switch pipe is consistent, and reduces cost；Single Working mould can be obviously reduced
Input voltage range under formula, optimal cavity parameter, improves efficiency；Two transformers work always simultaneously, improve device
Part utilization rate, reduces volume, improves power density, meets wide input voltage range occasion high efficiency and high power density
Demand.
Above content described in this specification is only illustration made for the present invention.Technology belonging to of the invention
The technical staff in field can be made various modifications to described specific embodiment or supplement or substituted using similar mode, only
Without departing from the content of description of the invention or to surmount scope defined in the claims, the guarantor of the present invention all should be belonged to
Shield scope.
Claims (7)
1. a kind of common resonant inductive type wide input range LLC resonant converter, it is characterised in that：
A kind of common resonant inductive type wide input range LLC resonant converter is by input source (Uin), primary side switch network
(10), common resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2), the first transformer (T1), second become
Depressor (T2), secondary side rectification circuit (20), output filter capacitor (Co) and output loading (Ro) constitute, wherein the first transformer
(T1) former limit magnetizing inductance value be Lm1, the second transformer (T2) former limit magnetizing inductance value be Lm2；The primary side switch network
(10) input two ends respectively with input source (Uin) two ends be connected, output end b and the first resonance of primary side switch network (10)
Electric capacity (Cr1) one end be connected, the first resonant capacitance (Cr1) other end and the first transformer (T1) primary side winding different name end phase
Even, the first transformer (T1) primary side winding Same Name of Ends and the second transformer (T2) primary side winding Same Name of Ends, common resonant inductance
(Lr) one end be connected, common resonant inductance (Lr) the other end be connected with output end a of primary side switch network (10), second become
Depressor (T2) primary side winding different name end and the second resonant capacitance (Cr2) one end be connected, the second resonant capacitance (Cr2) the other end
It is connected with output end c of primary side switch network (10), the first transformer (T1) vice-side winding Same Name of Ends and secondary side rectification circuit
(20) input d is connected, the input e of secondary side rectification circuit (20) and the second transformer (T2) vice-side winding different name end phase
Even, the second transformer (T2) vice-side winding Same Name of Ends and the first transformer (T1) vice-side winding different name end be connected, secondary rectification
The output two ends of circuit (20) respectively with output filter capacitor (Co) two ends, output loading (Ro) two ends be connected.
2. a kind of common resonant inductive type wide input range LLC resonant converter according to claims 1, its feature exists
In：Primary side switch network (10) the output positive pulse amplitude is Uin, negative pulse amplitude be-UinOr 0, positive negative pulse stuffing width is
50% square-wave voltage uabAnd uac, and the phase place of the two square-wave voltages is consistent.
3. a kind of common resonant inductive type wide input range LLC resonant converter according to claims 1, its feature exists
In：The primary side switch network (10) is two bridge arm switching networks, and it is by first switch pipe (SP1), second switch pipe (SP2),
Three switching tube (SP3) and the 4th switching tube (SP4) constitute, first switch pipe (SP1) drain electrode and the 3rd switching tube (SP3) drain electrode,
Input source (Uin) positive pole be connected, first switch pipe (SP1) source electrode and second switch pipe (SP2) drain electrode, primary side switch network
(10) output end a is connected, second switch pipe (SP2) source electrode and the 4th switching tube (SP4) source electrode, input source (Uin) negative pole,
Primary side switch network (10) output end c is connected, the 4th switching tube (SP4) drain electrode and the 3rd switching tube (SP3) source electrode, former limit
Switching network (10) output end b is connected.
4. a kind of common resonant inductive type wide input range LLC resonant converter according to claims 1, its feature exists
In：The primary side switch network (10) is three bridge arm switching networks, and it is by first switch pipe (SP1), second switch pipe (SP2),
Three switching tube (SP3), the 4th switching tube (SP4), the 5th switching tube (SP5) and the 6th switching tube (SP6) constitute, first switch pipe
(SP1) drain electrode and the 3rd switching tube (SP3) drain electrode, the 5th switching tube (SP5) drain electrode, input source (Uin) positive pole be connected,
First switch pipe (SP1) source electrode and second switch pipe (SP2) drain electrode, primary side switch network (10) output end a be connected, second
Switching tube (SP2) source electrode and the 4th switching tube (SP4) source electrode, the 6th switching tube (SP6) source electrode, input source (Uin) negative pole
It is connected, the 4th switching tube (SP4) drain electrode and the 3rd switching tube (SP3) source electrode, primary side switch network (10) output end b be connected,
6th switching tube (SP6) drain electrode and the 5th switching tube (SP5) source electrode, primary side switch network (10) output end c be connected.
5. a kind of common resonant inductive type wide input range LLC resonant converter according to claims 1, its feature exists
In：The secondary side rectification circuit (20) is full bridge rectifier, and it is by the first commutation diode (D1), the second commutation diode
(D2), the 3rd commutation diode (D3) and the 4th commutation diode (D4) constitute, the first commutation diode (D1) anode and secondary
The input d of rectification circuit (20), the second commutation diode (D2) negative electrode be connected, the second commutation diode (D2) anode and
4th commutation diode (D4) anode, output filter capacitor (Co) negative pole, output loading (Ro) negative pole be connected, the 4th is whole
Stream diode (D4) negative electrode and secondary side rectification circuit (20) input e, the 3rd commutation diode (D3) anode be connected, the
Three commutation diode (D3) negative electrode and the first commutation diode (D1) negative electrode, output filter capacitor (Co) positive pole, output it is negative
Carry (Ro) positive pole be connected.
6. a kind of common resonant inductive type wide input range LLC resonant converter according to claims 1, its feature exists
In：The secondary side rectification circuit (20) is a kind of voltage doubling rectifing circuit, and it is by the first commutation diode (D1), the pole of the second rectification two
Pipe (D2), the first voltage multiplying rectifier electric capacity (Co1) and the second voltage multiplying rectifier electric capacity (Co2) constitute, the first commutation diode (D1) sun
The input d of pole and secondary side rectification circuit (20), the second commutation diode (D2) negative electrode be connected, the second commutation diode (D2)
Anode and the second voltage multiplying rectifier electric capacity (Co2) negative pole, output filter capacitor (Co) negative pole, output loading (Ro) negative pole
It is connected, the second voltage multiplying rectifier electric capacity (Co2) positive pole and secondary side rectification circuit (20) input e, the first voltage multiplying rectifier electric capacity
(Co1) negative pole be connected, the first voltage multiplying rectifier electric capacity (Co1) positive pole and the first commutation diode (D1) negative electrode, output filtering
Electric capacity (Co) positive pole, output loading (Ro) positive pole be connected.
7. a kind of common resonant inductive type wide input range LLC resonant converter according to claims 1, its feature exists
In：The secondary side rectification circuit (20) is another kind of voltage doubling rectifing circuit, and it is by the first commutation diode (D1), the second rectification two
Pole pipe (D2), auxiliary voltage multiplying rectifier electric capacity (Caux) constitute, aid in voltage multiplying rectifier electric capacity (Caux) negative pole and secondary side rectification circuit
(20) input d is connected, and aids in voltage multiplying rectifier electric capacity (Caux) positive pole and the first commutation diode (D1) anode, second
Commutation diode (D2) negative electrode be connected, the first commutation diode (D1) negative electrode and output filter capacitor (Co) positive pole, output
Load (Ro) positive pole be connected, the second commutation diode (D2) anode and secondary side rectification circuit (20) input e, output filter
Ripple electric capacity (Co) negative pole, output loading (Ro) negative pole be connected.
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