CN106559006A - Two-way AC-DC converter - Google Patents
Two-way AC-DC converter Download PDFInfo
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- CN106559006A CN106559006A CN201510641469.8A CN201510641469A CN106559006A CN 106559006 A CN106559006 A CN 106559006A CN 201510641469 A CN201510641469 A CN 201510641469A CN 106559006 A CN106559006 A CN 106559006A
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Abstract
The present invention provides a kind of two-way AC DC transducers, which is connected between electrical network and battery, possess wave filter, bridge-type AC DC converter sections, double active bridge type DC DC converter sections and control unit, bus capacitor is configured between AC DC converter sections and DC DC converter sections, wave filter possesses at least one input inductance, in AC DC levels, control unit, it is consistent with the phase place of the electric current of the electrical network with the phase place of the electric current of the input of AC DC converter sections, and the voltage at bus capacitor two ends becomes the mode of assigned voltage, AC DC converter sections are controlled；In DC DC levels, control unit, in the way of the electric current of the outfan of DC DC converter sections becomes the first reference current that compensate for by the phase shift of input inductance generation, is controlled to DC DC converter sections.Two-way AC DC transducers of the invention, can reduce the ripple on bus capacitor.
Description
Technical field
The present invention relates to a kind of two-way AC-DC converter, on more particularly to a kind of bus capacitor
The little two-way AC-DC converter of ripple voltage.
Background technology
Electric automobile is connected with power system, the power supply from automobile to power system is carried out
Technology be referred to as V2G (Vehicle to Grid).According to V2G technologies, do not make in electric automobile
When using for mobile instrument, can store the jumbo battery being equipped on car as electric power
Equipment and use.
With the interest of the V2G technologies of the transmission for the energy between different power supplys it is continuous
Improve, two-way inversion charging system necessitates.
In non-patent literature 1, even if disclosing the ripple current using two frequencys multiplication with electrical network
Lithium ion battery is charged, its battery performance will not also occur big deterioration.
In addition, in non-patent literature 2 in form, using the sine electricity of two frequencys multiplication with electrical network
Stream is charged.As shown in figure 8, the transducer of non-patent literature 2 possesses following two-way open up
Structure is flutterred, non-bridge PFC and bidirectional active bridge (DAB) module is included during charging, during electric discharge
Comprising full-bridge boost formula transducer and inverter.Two-way inversion charging system can provide right
The AC-DC that set of cells etc. is charged is changed and for battery is connected to electrical network
Both DC-AC conversions.Thereby, it is possible to utilize force device in the two directions, as a result,
Higher energy transmission efficiency can be realized by less element.
Fig. 9 is the circuit block diagram of non-patent literature 2.In fig .9, battery charge power is by formula
(1) representing.
If the energy is all transmitted to battery, then the charging current of battery is by following formula (2)
To represent.
io=pin/Vb=2VacIacsin2(ωt)/Vb=Iosin2(ωt)……(2)
Figure 10 is the control block diagram of non-patent literature 2.The control unit is with charging current as Iosin2(ωt)
Mode bidirectional active bridge (DAB) module of DC-DC levels is controlled.According to the structure,
The capacity of bus capacitor can be reduced.For example, output is 3kW, the two ends of bus capacitor
Ripple voltage be 2% in the case of, the capacity of bus capacitor can be reduced to 400 μ F.
Prior art literature
Non-patent literature 1：Bala S,Tengner T,Rosenfeld P,et al.The effect of low
frenquency curent ripple on the performance of a Lithium Iron
Phosphate(LFP)battery energy storage system[c].IEEE Energy Conversion
Cpngress and Exposition,ECCE 2012,2012:3485-3492.
Non-patent literature 2：Xue,L.,et al.,Dual active bridge based battery charger
for plug-in hybrid electric vehicle with charging current containing low
frequency ripple.2013,IEEE.p.1920-1925.
The content of the invention
Invention technical problem to be solved
But, in non-patent literature 2, consider in AC-DC levels for filtering high frequency
The inductance L of noiseacIn energy storage.Due to inductance LacIn energy, bus capacitor
The ripple voltage at two ends can become big.
Inductance LacEnergy, represented by formula (3).
Its inductance LacPower represented by following formula (4).
The electric power being sent in battery is represented by following formula (5)
Wherein,
Then, in VinIin10 (ω L of ＞1I2 in) in the case of, the electric current of outlet side carrys out table by following formula (6)
Show,
As described above, if be necessary the energy absorption in inductance to output current
(charging current) carries out phase shift.It is 3kW in output, input voltage is 110V, input
In the case that the inductance of side AC-DC levels is 3mH, phase offset angleFor 15.78 °.Cause
This, it has to consider phase offset angleDiscounting for the phase offset angleIt is then female
The ripple voltage at line voltage two ends becomes big.
Solve the means of technical problem
The present invention is completed to solve such problem, and its object is to offer one kind makes
The less capacitance so as to more reduce bus capacitor of the ripple voltage at busbar voltage two ends
Two-way AC-DC converter.
The present invention is made to solve above-mentioned technical problem, and the present invention's is a kind of two-way
AC-DC converter, which is connected between electrical network and battery, it is characterised in that possess wave filter,
Bridge-type AC-DC converter sections, double active bridge type DC-DC converter sections and control unit, it is described
Bus capacitor, the filtering are configured between AC-DC converter sections and the DC-DC converter sections
Device possesses at least one input inductance, in AC-DC levels, the control unit, with the AC-DC
The phase place of the electric current of the input of converter section is consistent with the phase place of the electric current of the electrical network, and institute
The voltage for stating bus capacitor two ends becomes the mode of assigned voltage, and the AC-DC converter sections are entered
Row control；In DC-DC levels, the control unit, with the output of the DC-DC converter sections
The electric current at end becomes the side of the first reference current of the phase shift that compensate for being produced by the input inductance
Formula, is controlled to the DC-DC converter sections.
Two-way AC-DC converter of the invention, improves power factor in AC-DC levels
And the voltage at bus capacitor two ends is maintained into desired value, in DC-DC levels, realize mending
The sinusoidal charging of two frequencys multiplication of the phase shift of input inductance is repaid, such that it is able to make busbar voltage two ends
The capacitance less, thus, it is possible to more reduce bus capacitor of ripple voltage.
In addition, in the two-way AC-DC converter of the present invention, it is preferable that described first with reference to electricity
Stream according to from the input voltage and input current of the electrical network, the voltage at the battery two ends,
And the phase shifting angle produced by the input inductance is calculating.
In addition, in the two-way AC-DC converter of the present invention, it is preferable that the phase shifting angle origin
Input voltage and input current, the value of the input inductance and the electricity from the electrical network
The frequency of net is calculating.
In addition, in the two-way AC-DC converter of the present invention, it is preferable that the control unit possesses：
Sampling unit, samples to the input voltage and input current from the electrical network；Second ginseng
Current calculation unit is examined, according to the input voltage and the input current and the battery two
The voltage at end is calculating second reference current；Phase shifting angle computing unit, according to the input
Voltage and the input current, the value of the input inductance and the mains frequency are calculating
Phase shifting angle；Phase locking unit, enters horizontal lock to the line voltage, so as to obtain the electrical network electricity
The phase place of pressure；Phase-shifting unit, the phase place to being obtained by the phase locking unit carry out phase shift, make this
/ 2nd of phase shifting angle described in phase offset；Squaring cell, to being exported by the phase-shifting unit
The cosine of phase place carry out square operation；And multiplication unit, by second reference current with
The result of the squaring cell is multiplied, so as to obtain first reference current.
The effect of invention
Two-way AC-DC converter of the invention, can compensate for be input into inductance and producing
Phase shift, can reduce the ripple voltage at bus capacitor two ends, therefore, it is possible to reduce bus capacitor
Capacitance.
Description of the drawings
Fig. 1 is the figure of the two-way AC-DC converter for representing embodiments of the present invention.
Fig. 2 is the charge mode of the two-way AC-DC converter for representing embodiments of the present invention
Control block diagram.
Fig. 3 is the discharge mode of the two-way AC-DC converter for representing embodiments of the present invention
Control block diagram.
Fig. 4 is the charge mode of the two-way AC-DC converter for representing embodiments of the present invention
Detailed control block diagram.
Fig. 5 is the double active bridge of the two-way AC-DC converter for representing embodiments of the present invention
(DAB) the control strategy figure of type DC-DC converter section.
Fig. 6 be compare under charge mode it is existing without decoupling mode, non-patent literature 2, and this
The figure of the bus capacitor and its ripple voltage of embodiment.
Fig. 7 be compare under discharge mode it is existing without decoupling mode, non-patent literature 2, and this
The figure of the bus capacitor and its ripple voltage of embodiment.
Fig. 8 is the figure of the two-way AC-DC converter for representing prior art.
Fig. 9 is the circuit block diagram of the two-way AC-DC converter for representing prior art.
Figure 10 is the control block diagram of the two-way AC-DC converter for representing prior art.
Specific embodiment
Hereinafter, referring to the drawings, explain for implementing mode of the invention.
Fig. 1 is the figure of the two-way AC-DC converter for representing embodiments of the present invention.First,
The circuit structure of the two-way AC-DC converter of present embodiment is illustrated using Fig. 1.Fig. 1's is double
To in AC-DC converter, possess input filter, bridge-type AC-DC converter sections, double have
Source bridge (DAB) type DC-DC converter section and control unit.Bridge-type AC-DC converter sections have
Standby switch element T5～T8.DAB type DC-DC converter sections possess switch element T1～T4, T1 '～
T4’.Between bridge-type AC-DC converter sections and DAB type DC-DC converter sections, it is configured with
Bus capacitor Cbus。
<Input filter>
As described above, in non-patent literature 2, not accounting for the inductance L in AC-DC levelsac
In energy storage.In non-patent literature 2, in electrical network and bridge-type AC-DC converter sections
Between be connected with inductance Lac, its high-frequency noise produced in being used to filter switch element.At this
In bright, it is also possible to adopt single inductance to be filtered as non-patent literature 2.Single inductance is
First-order system, will not produce the problem of resonance.But, if being filtered using single inductance,
Need the inducer that inductance value is larger.This can cause the increase of component size, and inductive energy storage
Also increase.
It is therefore preferred that in the present embodiment of the present invention, using LCL filter as input
Wave filter.LCL filter is by inducer Lg1, Lg2, capacitor Cin, inducer L1, L2.
LCL filter is widely used in being connected with electrical network, by just can using small electric inductance value
The high-frequency noise produced in filtering switching voltage.Have an advantage in that, with stronger stability,
Single electric current loop, control parameter design is simple, and relatively low cost.
In present embodiment, it is assumed that the cut-off frequency of wave filter is set as the switch frequency of switch element
The 1/10 of rate, and L=L1+L2。
Then, cut-off frequency fnRepresented by following formula (7).
If it is desired to reduce electric capacity Cin, then need to increase inductance value L.In 10% converter inductance
Under the demand of current ripples, and set L1=L2=3mH, then capacitor CinSize such as following formula (8)
It is shown.
Assume Lg=Lg1+Lg2, α=L/ (L+Lg), then the output current of transducer and output voltage
Transmission function is as shown in following formula (9).
When α=0.5, the size of transmission function is minimum, now can preferably suppress radio-frequency component.
I.e., in the present embodiment, Lg1=Lg2=3mH.
Additionally, the example of the value of each element in Fig. 1 is as shown in table 1.
[table 1]
According to analog result, the having stable behavior of the two-way AC-DC converter of each value with table 1.
<The circuit structure of charge mode>
Fig. 2 is the control block diagram of the charge mode of the two-way AC-DC converter for representing the present invention.
Under charge mode, electric power is supplied to battery from electrical network.In this mode, bridge-type AC-DC
Converter section as non-bridge PFC circuits, double active bridge (DAB) type DC-DC converter section conducts
Phase shift full-bridge circuit and work.Line voltage Jing non-bridge PFC circuits are adjusted to bus capacitor
The voltage at two ends, and battery is charged by phase shift full-bridge circuit.In the electricity of the present invention
In line structure, bridge-type AC-DC converter sections realize power-factor improvement and Voltage Cortrol, DAB
Type DC-DC converter section is realized charging the sine of battery.
The operating principle of the non-bridge PFC circuits of present embodiment and common boost PFC circuit phase
Seemingly.Compared to common voltage lifting PFC, this pair of boosting is obtained in that lower common mode without bridge rectification
The efficiency of noise and Geng Gao.For suppression common mode noise, two are connected with the outfan of electrical network
Diode D9, D10.In the positive half cycle of the line voltage of Fig. 2, only switch element T8 work,
When switch element T8 is turned on, the electric current of inducer L1 rises, and electric current is through switch element T8
Electrical network is returned to diode D9；When switch element T8 is turned off, electric current is via switch element T5
Body diode, bus capacitor CbusElectrical network is returned to diode D9, now electrical network and inducer
L1 transfers energy to load-side together.In the negative half period of the line voltage of Fig. 2, unit is only switched
Part T7 works, and when switch element T7 is turned on, the electric current of inducer L2 rises, and electric current is passed through
Switch element T7 and diode D10 return to electrical network；When switch element T7 is turned off, electric current Jing
By the body diode of T6, bus capacitor CbusElectrical network is returned to diode D10, now electrical network and
Inducer L2 transfers energy to load-side together.The non-bridge PFC circuits of present embodiment
Concrete control mode will be described later.
As shown in Fig. 2 the circuit structure of the phase shift full-bridge circuit of present embodiment with commonly use
Phase shift full-bridge circuit it is identical.Using the phase shift full-bridge circuit of double active full bridge structures, it is because
Which has, and switch element voltage x current stress is relatively small, circuit structure is symmetrical and easily realizes switch
The advantages of ZVT (Zero-Voltage-Switching, ZVS) of element.As which is big
It still is able to realize that Sofe Switch switches under power such that it is able to reduce switching loss.As shown in Fig. 2
The dutycycle of switch element T1～T4 is 50%, and switch element T1 and switch element T4
Ripple formed 180 ° it is anti-phase, and the ripple of switch element T2 and switch element T3 formed 180 ° it is anti-
Phase.And there is phase contrast between switch element T1, T4 and switch element T2, T3.This reality
The phase shift full-bridge circuit of mode is applied by changing the phase contrast such that it is able to controlled output electric current.
Its specific control mode is described further below.
<The circuit structure of discharge mode>
Fig. 3 is the control block diagram of the discharge mode of the two-way AC-DC converter for representing the present invention.
In discharge mode, electric power is supplied to electrical network from battery.In this mode, double active bridges (DAB)
, used as full-bridge boost circuit, bridge-type AC-DC converter sections are used as single-phase for type DC-DC converter section
Inverter circuit and work.Via full-bridge boost circuit, the output voltage of battery is boosted up to
The voltage at bus capacitor two ends, the voltage at the bus capacitor two ends is via above-mentioned single-phase inversion afterwards
Device circuit and be connected to electrical network, so as to energy is returned to electrical network.As shown in figure 3, as full-bridge
The control mode of booster circuit, the monocyclic control of voltage loop are used, so as to ensure its work
In full-bridge boost pattern.It is of course also possible to use the control model of electric current loop and Voltage loop.And
In single-phase inverter circuit, reference current is obtained by the phase-locked loop pll of line voltage,
And PWM drive signal is obtained by the PI compensation of current loop.
Below with regard to the bridge-type AC-DC converter sections in charge mode, double active bridge (DAB) types
The control mode of DC-DC converter sections is illustrated.Full-bridge boost circuit and list in discharge mode
The control mode of phase inverter circuit is by the voltage and current signal in charge mode reverse control
Mode processed, the description thereof will be omitted for here.
<The control mode of non-bridge PFC circuits under charge mode>
In the non-bridge PFC circuits of charge mode, control unit obtains electrical network by phase-locked loop pll
The phase place of voltage (electric current), and with the phase place of the input current of above-mentioned non-bridge PFC circuits with
The mode that the phase place of line voltage (electric current) is consistent is controlled.That is, AC-DC turns
The phase place for changing the electric current of the input in portion is consistent with the phase place of line voltage (electric current).Additionally,
By the dutycycle for changing switch element, so as to by the output voltage control of non-bridge PFC circuits be
The value of regulation.That is, with bus capacitor CbusThe voltage at two ends becomes the side of assigned voltage
Formula controls AC-DC converter sections.By make non-bridge PFC circuits input current phase place with electricity
The phase place of net voltage (electric current) is consistent, so as to reach the effect for improving power factor.By control
The output voltage of non-bridge PFC circuits processed, so as to provide electric power for rear class battery.
As shown in Fig. 2 the difference of the output voltage and la tension de reference Uref est 2 to non-bridge PFC circuits
PI controls are carried out, and to the phase place in the phase place and phaselocked loop of the input current of non-bridge PFC circuits
PI controls are carried out, so as to the dutycycle of controlling switch element T5～T8, desired output is obtained.
Fig. 4 is bridge-type AC-DC converter sections, double active bridge (DAB) type DC-DC conversions
The detailed control block diagram of the control unit in portion.As shown in figure 4, sampled to line voltage by AD,
Inductance L1, L2Electric current sampled, and seek its virtual value, and while power network current entered
Horizontal lock；When line voltage be timing, inductance L1Conducting；When line voltage is to bear, inductance
L2Conducting.Voltage loop filters the 100Hz voltage stricture of vaginas on dc bus first by digital filter
Ripple, is then compared with voltage reference afterwards by pi regulator, afterwards by with PLL phase locking unit phases
Take advantage of to be divided by with voltage effective value and generate the current reference benchmark of electric current loop, in electric current loop, nothing of sampling
The value of the input current of bridge PFC circuits, and by its compared with above-mentioned current reference benchmark after lead to
Pi regulator is crossed, so as to controlling switch element T7, T8.
<The control mode of phase shift full-bridge circuit under charge mode>
Fig. 5 is the control strategy figure of the phase shift full-bridge circuit under the charge mode of present embodiment.
As shown in above-mentioned formula (6), the 1st reference currentIt is by input voltage
VsWith input current Is, battery two ends voltage VbattAnd the phase shift produced by inductance L1, L2
AngleCome what is calculated.In addition, the phase in order to compensate inductance L1, L2 in input filter generation
Move, it is necessary to which the output current of phase shift full-bridge circuit is controlled toThat is, have
Necessity becomes the inductance that compensate for input filter with the electric current of the outfan of DC-DC converter sections
1st reference current of the phase place that L1, L2 are producedMode controlling DC-DC
Converter section.Wherein, angle of phase displacementIt is by the input voltage from electrical network
VsWith input current Is, input inductance L1 value and electrical network frequencies omega calculating.Now,
The reference current of the phase shift that reference current has been arranged to compensate for being produced by input inductance L1, L2.
As shown in Fig. 2, Fig. 4, Fig. 5, by the calculating of the virtual value to above-mentioned line voltage,
With to inductance L1, the calculating of the upper electric currents of L2 calculates phase shift angleWith reference current Iref。
According to phase shift angleMake reference current IrefThe phase shift on the basis of the voltage of above-mentioned sampling electrical network
So as to be controlled to phase shift full-bridge circuit.
Specifically, control unit can possess：Sampling unit, to the input electricity from the electrical network
Pressure VsWith input current IsSampled；Second reference current computing unit, according to input voltage
VsWith input current IsAnd the voltage V at battery two endsbattTo calculate the second reference current；Phase shift
Angle computing unit, according to input voltage VsWith input current Is, input inductance L1 value and
Mains frequency ω is calculating phase shifting anglePhase locking unit PLL, to the line voltage VsCarry out
Lock phase, so as to obtain the phase place of line voltage；Phase-shifting unit, to being obtained by the phase locking unit
Phase place carry out phase shift, make phase shifting angle described in the phase offset1/2nd；Squaring cell,
The cosine of the phase place to being exported by the phase-shifting unit carries out square operation；And multiplication unit,
Second reference current is multiplied with the result of the squaring cell, so as to obtain described first
Reference current
In the switch element T1～T4 to phase shift full-bridge circuit, when T1 '～T4 ' is controlled, fill
Under power mode, switch element T1 '～T4 ' is controlled as Close All.Switch element T1～T4
Dutycycle be 50%, and switch element T1 and switch element T4 is anti-phase into 180 °,
And switch element T2 is anti-phase into 180 ° with switch element T3.By controlling switch element T1,
Phase contrast between T4 and switch element T2, T3 such that it is able to by the defeated of phase shift full-bridge circuit
The charging current for going out electric current, i.e. battery is controlled to
<The capacitance of bus capacitor>
The control mode of present embodiment is compared with 2 control mode of non-patent literature, this reality
The decrement for applying the bus capacitor storage energy of mode is identical with the energy stored on input inductance.
The energy is represented by following formula (10).
Due toAnd
So the capacitance of bus capacitor is represented by following formula (11).
According to formula (11), in the control mode of the present invention, in order that the ripple voltage of bus capacitor
Become 2%, the capacitance of bus capacitor can be made to reduce by 193.3 μ F.
<Without decoupling mode, non-patent literature 2, and present embodiment bus capacitor and its ripple
The comparison of voltage>
Fig. 6 is compared under charge mode without decoupling mode, non-patent literature 2, and this embodiment party
The form of the ripple voltage at the bus capacitor two ends of formula.Fig. 7 is compared under discharge mode without solution
Coupling mode, non-patent literature 2, and present embodiment bus capacitor two ends ripple voltage table
Lattice.From fig. 6 it can be seen that in the charge state, when bus capacitor is 200 μ F, this
The ripple voltage at the bus capacitor two ends of embodiment can be reduced to 6.8V.Can be with from Figure 10
Find out, in the discharged condition, when bus capacitor is 200 μ F, the bus electricity of present embodiment
The ripple voltage for holding two ends can be reduced to 4.8V.According to the invention it is thus possible to reduce mother
The ripple voltage at line capacitance two ends, and then the capacitance of bus capacitor can be reduced.
Although being illustrated to the present invention above in association with drawings and Examples, can be
Understand, the invention is not limited in any way for described above.Those skilled in the art without departing from
The present invention connotation and scope in the case of can as needed to the present invention carry out deformation and
Change, these deformations and change are within the scope of the present invention.For example, although explanation above
Using LCL filter as wave filter situation, but using single inductance as input filter
The situation of device is equally applicable to the present invention.Now, so that the charging current of battery becomes compensate for
The mode of the reference current of the phase shift produced by single inductance, is carried out to the DC-DC converter sections
Control.
Symbol description
PinCharge power
VacLine voltage
IacPower network current
ioBattery charge
VbBattery charging voltage
ω mains frequencies
LacFilter inductance
is(t) filter inductance LacElectric current
PL(t) filter inductance LacPower
VsThe input voltage of AC-DC converter sections
IsThe input current of AC-DC converter sections
T1～T4, T1 '～T4 ', T5～T8 switch elements
Fs switching frequencies
CinCapacitor
Lg1,Lg2,L1,L2Inducer
CbusBus capacitor
VbattBattery charging voltage
Claims (4)
1. a kind of two-way AC-DC converter, which is connected between electrical network and battery, its feature
It is,
Possess wave filter, bridge-type AC-DC converter sections, double active bridge type DC-DC converter sections
And control unit,
Bus capacitor is configured between the AC-DC converter sections and the DC-DC converter sections,
The wave filter possesses at least one input inductance,
In AC-DC levels, the control unit, with the input of the AC-DC converter sections
The phase place of electric current is consistent with the phase place of the electric current of the electrical network, and the bus capacitor two ends
Voltage becomes the mode of assigned voltage, and the AC-DC converter sections are controlled；
In DC-DC levels, the control unit, with the outfan of the DC-DC converter sections
Electric current becomes the mode of the first reference current of the phase shift that compensate for being produced by the input inductance,
The DC-DC converter sections are controlled.
2. two-way AC-DC converter as claimed in claim 1, it is characterised in that
First reference current is according to the input voltage and input current from the electrical network, institute
The voltage for stating battery two ends and the phase shifting angle that produced by the input inductance are calculating.
3. two-way AC-DC converter as claimed in claim 2, it is characterised in that
The phase shifting angle is by the input voltage and input current from the electrical network, input electricity
The frequency of the value of sense and the electrical network is calculating.
4. two-way AC-DC converter as claimed in claim 1 or 2, it is characterised in that
The control unit possesses：
Sampling unit, samples to the input voltage and input current from the electrical network；
Second reference current computing unit, according to the input voltage and the input current and
The voltage at the battery two ends is calculating the second reference current；
Phase shifting angle computing unit, according to the input voltage and the input current, the input
The frequency of the value of inductance and the electrical network is calculating phase shifting angle；
Phase locking unit, enters horizontal lock to the voltage of the electrical network, so as to obtain the electricity of the electrical network
The phase place of pressure；
Phase-shifting unit, the phase place to being obtained by the phase locking unit carry out phase shift, make the phase place inclined
Move 1/2nd of the phase shifting angle；
Squaring cell, the cosine of the phase place to being exported by the phase-shifting unit carry out square operation；
And
Multiplication unit, second reference current is multiplied with the result of the squaring cell, from
And obtain first reference current.
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510641469.8A CN106559006B (en) | 2015-09-30 | 2015-09-30 | Two-way AC-DC converter |
| JP2016188057A JP6710615B2 (en) | 2015-09-30 | 2016-09-27 | Bidirectional AC-DC converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510641469.8A CN106559006B (en) | 2015-09-30 | 2015-09-30 | Two-way AC-DC converter |
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| CN106559006A true CN106559006A (en) | 2017-04-05 |
| CN106559006B CN106559006B (en) | 2019-02-05 |
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| CN201510641469.8A Active CN106559006B (en) | 2015-09-30 | 2015-09-30 | Two-way AC-DC converter |
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| CN109687702A (en) * | 2017-10-18 | 2019-04-26 | 现代自动车株式会社 | DC-DC converter |
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| WO2020056659A1 (en) | 2018-09-20 | 2020-03-26 | Abb Schweiz Ag | Power converter |
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| CN113315391A (en) * | 2021-04-29 | 2021-08-27 | 武汉华海通用电气有限公司 | Digital PFC circuit |
Also Published As
| Publication number | Publication date |
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| CN106559006B (en) | 2019-02-05 |
| JP6710615B2 (en) | 2020-06-17 |
| JP2017070193A (en) | 2017-04-06 |
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