CN106104995A - 频率变换器 - Google Patents

频率变换器 Download PDF

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CN106104995A
CN106104995A CN201580013285.5A CN201580013285A CN106104995A CN 106104995 A CN106104995 A CN 106104995A CN 201580013285 A CN201580013285 A CN 201580013285A CN 106104995 A CN106104995 A CN 106104995A
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voltage
frequency component
frequency changer
interstage exchange
changer
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C·迈耶
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Vensys Elektrotechnik GmbH
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Abstract

本发明涉及一种用于产生网络交流电压的频率变换器，其具有预定电源频率分量，包括用于将恒定电压变换为中间交流电压的至少一个变换器模块，中间交流电压具有预定电源频率分量以及干扰频率分量。本发明的目的是减少干扰频率分量相对于频率变换器的预定电源频率分量的比例。为了这个目的，以相移来互连至少一个变换器模块所属类型的多个变换器模块，使得通过叠加多个中间交流电压来产生网络交流电压，网络交流电压的最终干扰频率分量比每个单个中间交流电压的干扰频率分量少。

Description

频率变换器
技术领域
本发明涉及一种使用将恒定电压变换为中间交流电压的至少一个变换器模块来产生具有预定主频率分量的电源交流电压的频率变换器，其中中间交流电压具有预定主频率分量以及干扰频率分量。
背景技术
电力供应电网可以基于不同的电源频率。然而，为了将这些电网相互连结，有必要使用所谓的频率变换器。在例如将要从50Hz电网供电来提供16 2/3Hz铁路电网时存在此问题。
类似地，在用于生产电能的工厂(诸如风力涡轮机或太阳能系统)需要频率变换器，以便将所产生的交流电压或DC电压变换为具有由电网供应点施加的主频率分量的电压。
如果电网供应点是家庭电网的一部分，则默认的主频率分量为50Hz。
反之，如果电网供应点是铁路电网的一部分，则预定主频率分量也可以是16 2/3Hz。
通过例如DE 94 08 504 U1、DE 44 43 747 C1、EP 2 088 688 A2或EP 2 282 399B1，已经了解用于铁路电网的频率变换器。
根据应用，所描述的变换器的类型可以具有从几千瓦到数兆瓦的电力传输。当今，这种变换器的操作通常基于快速切换功率半导体，例如，具有绝缘栅电极的双极晶体管(绝缘栅双极型晶体管，简称IGBT)。由于功率半导体的切换操作，除了规定的主频率分量，也不可避免地出现干扰频率分量。参照低干扰频率分量，利用已知的频率变换器来符合电网供应点施加的规格有时是困难的甚至是不可能的。
发明内容
因此，本发明的目的是减少在频率变换器中的相对于预定主频率分量的干扰频率分量的量。
由权利要求1的特征来实现这个目的。
根据本发明的用于产生具有预定主频率分量的交流电源电压的频率变换器包括用于将恒定电压变换为中间交流电压的至少一个变换器模块，其中中间交流电压具有预定主频率分量以及干扰频率分量，特征在于至少一个变换器模块所属类型的多个变换器模块被按照下述方式异相地彼此互连，通过叠加多个中间交流电压来产生电源交流电压，其最终的干扰频率分量低于每个中间交流电压的干扰频率分量。
在传统变换器中，通常仅仅时钟频率、斜率和电感的参数可用于减小干扰频率分量，以及为了实现主频率分量中最小的可能纹波。然而，这些参数的最优化与同时对最高可能效率和低电磁干扰的需求形成对比。
相反地，本发明的特别优点是用于设计根据本发明的频率变换器的另外设计参数是可得的，使得可以更好地整体符合上述需求。
根据优选实施例，提供包括至少一个功率组件和平滑组件的变换器模块。至少一个功率组件优选地是具有绝缘栅电极的双极型晶体管(绝缘栅双极型晶体管，简称IGBT)。优选地使用电感器或线圈作为平滑组件。
频率变换器的输入功率通常被提供为DC电压的形式。然后通过对功率组件或多个功率组件进行时钟控制(clock)来完成中间电路交流电压的产生。通过快速导通/关断功率组件，电流流过电感器，其平均值依赖于导通时间和关断时间的比例(脉冲宽度调制或PWM)。为了产生脉冲宽度调制，用于各种应用的各种微控制器在市场上是可得的。
根据本发明，产生多个中间交流电压，其中可以通过在节点处加和这种最简单的方式来实现它们的叠加。单个中间交流电压相对于特定基本周期的相位偏移优选地(但不必需)是等距的。优选地，作为基波周期，脉冲宽度调制的相应时钟被用作基础。
附图说明
由以下附图来示出本发明的另外细节和优点，特别地，
图1是根据本发明的频率变换器的示意图，
图2是基于脉冲宽度调制的典型中间交流电压的轮廓，
图3是根据本发明由于几个中间交流电压重叠得到的电源交流电压的轮廓，
图4是基于多个脉冲宽度调制的典型的中间交流电压的轮廓，以及
图5是根据本发明实施例正弦半波的产生。
具体实施方式
图1示出根据本发明的频率变换器的基本电路图。在本示例实施例中，恒定输入电压Ue需要被变换为16 2/3Hz的电源交流电压Ua，以供应铁路电网。恒定输入电压Ue可以是例如由风力涡轮机的发电机101在本地产生并且然后由整流器102整流的电压。
电容器103和104提供具有接地点并且具有限定对称点的第一中间电路。随后是组件105，其包括总共6个变换器模块，用于恒定电压Ue将变换为中间交流电压。进而，每个变换器模块包括具有续流二极管的两个IGBT和电感器。经脉冲宽度调制电压后的电压L1a、L1b、L1c、L2a、L2b和L2c被施加在电感器上。每个电感器使得各个脉冲宽度调制后的电压平滑，并且在输出处产生中间交流电压(其包含预定主频率分量和干扰频率分量)。
中间交流电压在节点106和107处汇聚并且通过叠加形成初级电压L1-L2，其被供应到变压器108的初级绕组。变压器108被设计为使得利用中间电路接地通过对称电压L1-L2来产生用于馈送到铁路电网的单侧电源交流电压Ua。交流电源电压Ua的预定主频率分量是16 2/3Hz的铁路电网的电网频率。同时，得到的交流电网电压Ua的干扰频率分量低于6个电感器的输出处的每个中间交流电压的干扰频率分量。参照图2和图3进一步说明这种效应。
图2示出基于脉冲宽度调制的典型中间交流电压的轮廓。图2的上轮廓对应于变换器模块内脉冲宽度调制后的电压轮廓，例如，电压轮廓L1a。通过对变换器模块的上IGBT进行时钟控制来产生正矩形半波，同时通过相应地对变换器模块的下IGBT进行时钟控制来产生负矩形半波。如果将脉冲宽度调制后的电压轮廓L1a馈送至电感器，则在电感器的输出处得到图2中下方的正弦曲线。下方的轮廓中示出了预定主频率分量的基波分量，其中预定主频率分量除了包括基波分量还包含由正弦基波振荡的锯齿状轮廓表示的干扰频率分量(具有谐波和/或失真的正弦基波分量)。
图3示出基于几个中间交流电压的创造性叠加，交流电网电压的轮廓。从图3的三个上方曲线中可以看出，虽然时钟是彼此异相的，但是脉冲宽度调制后的电压轮廓L1a、L1b和L1c具有基本相同的时钟控制。如果此时例如时钟L1a在随后的电感器中减弱，则下一时钟L1b已经恰好异相地发生，以便通过产生进一步增加来对抗L1a的衰减，从而减小干扰频率分量。这同样适用于L1c的相位偏移。因此，在节点106处产生下方的预定主频率波的正弦基波分量的轮廓，其相对于图2包含有明显减少的干扰频率分量。以相同的方式(因此未示出)产生负电压分量L2，使得在节点106与107之间，由于几个中间交流电压的叠加呈现出最终的电压L1-L2。
在图2和图3中，假设由仅具有正电平与负电平的脉冲宽度调制产生中间交流电压。基本上，当然也可以想到通过提供若干个IGBT的串联连接，提供了若干个电压电平并且因此提供了若干个脉冲宽度调制来产生中间交流电压。图4示出基于具有2个正电压电平和2个负电压电平的多个脉冲宽度调制的这种中间交流电压的轮廓。在这种情况下，中间交流电压已经包括相对于图2大幅减少的干扰频率分量。如果根据图3的创造性方法被应用到图4的几个中间交流电压，则可以实现干扰频率分量相对于图3的下方的轮廓的进一步减少。
图5示出根据本发明的实施例正弦半波的产生。在解释各个脉冲及其效果之前，对所谓的降压变换器的工作原理进行说明：
在图1中，可以看出每个IGBT具有续流二极管。在关断IGBT之后，电流由电感器驱动而换向至相应的续流二极管。如果将电感考虑为RL元件，则当IGBT导通时，电流遵循上升指数函数(e-函数)，并且如果IGBT被关断，电流遵循衰减e-函数。由比例L/R来确定e-函数的时间常数τ，从而使τ＝L/R。根据这些考虑，直接根据脉冲宽度调制的时钟周期T与时间常数τ的比例确定主频率分量的纹波。如果比例Τ/τ是大的，则主频率分量具有大的纹波。比例Τ/τ越小，主频率分量越接近期望的理想形状。
这些考虑还意味着在传统频率变换器中，可以通过以下三种措施来实现具有较少干扰频率分量的小纹波，尽管这三种措施中的每一个具有某些缺点：
·脉冲宽度调制的时钟频率f(其中f＝1/T)按照恒定的斜率增大。本文中的恒定的斜率是指各个时钟的恒定的导通/关断次数。
缺点：由于每秒切换次数的总和增大，所以开关损耗也增大。
·时钟频率f和斜率一起增加，使得每秒切换次数总和保持不变。
缺点：更快的切换导致更多的EMC干扰。此外，控制损耗增大。
·时间常数τ通过增大电感L。
缺点：大电感器是昂贵的、大型的和重的。
通过一个示例来最终阐明这些考虑：
用于产生脉冲宽度调制的商用微控制器通常产生几千赫兹数量级(例如f＝2.4kHz)的时钟频率。在2.4kHz下，因而基波周期T大约为0.42ms。如果使用具有L＝0.3mH和R＝0.1Ω的商用电感器，则该时间常数τ具有在τ≈3ms范围内的值。这导致比例Τ/τ具有显著小于1的数值，但是通常不足以符合电源的剩余纹波方面的电流需求。
参照图5，现在再次清楚地示出这个剩余纹波是如何根据本发明被进一步降低的。首先，假设三相L1a、L1b和L1c具有相对于基波周期T相同的相位偏移，即，相位偏移相当于基波周期T的三分之一。传统频率变换器仅利用一相工作，例如利用相L1a。在相L1a的关断时钟过程中，电流如所述地指数衰减，从而产生所述残留纹波。由此，相L1b和L1c的随后时钟有效地对抗该纹波。
当然，可以留给本领域技术人员来决定选择位置和相数，使得通过叠加各个中间交流电压来产生电源交流电压，从而其最终干扰频率分量低于每个中间交流电压的干扰频率分量。因此，例如，相数不一定必须被设置为三个。也可以提供两相或三个以上的相。另外，相同的相位偏移也不实现本发明的优点所必需的。根据应用，各相也可以在基波周期T上不规则地分布。最后，显然还可以设想，各相的单个脉冲重叠。图5只是可能的示例性实施例，其中脉冲长度被精确地选择，使得在下一阶段的时钟开始之前该时钟结束。

Claims (8)

1.一种用于产生具有预定主频率分量的电源交流电压的频率变换器，
具有用于将恒定电压变换为中间交流电压的至少一个变换器模块，其中所述中间交流电压具有预定主频率分量和干扰频率分量，
特征在于
所述至少一个变换器模块的类型的多个变换器模块被具有相位偏移地彼此互连，从而通过叠加若干个中间交流电压来产生电源交流电压，最终的干扰频率分量低于每个中间交流电压的所述干扰频率分量。
2.根据权利要求1所述的频率变换器，
特征在于所述变换器模块包括至少一个功率组件和平滑组件。
3.根据权利要求2所述的频率变换器，
特征在于所述至少一个功率组件是具有绝缘栅电极的双极型晶体管(绝缘栅双极型晶体管，IGBT)。
4.根据权利要求2或3所述的频率变换器，特征在于所述平滑组件是电感器或线圈。
5.根据权利要求2-4中任一项所述的频率变换器，特征在于通过对功率组件进行时钟控制来产生中间电路交流电压。
6.根据权利要求5所述的频率变换器，
特征在于所述时钟控制是基于脉冲宽度调制的。
7.根据权利要求1至6中任一项所述的频率变换器，特征在于通过在一个节点处加和来提供单个中间交流电压的叠加。
8.根据权利要求1至7中任一项所述的频率变换器，特征在于单个中间交流电压的相位偏移相对于各个基波周期是等距的。
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