CN105897207A - Continuous variable gain amplifier - Google Patents
Continuous variable gain amplifier Download PDFInfo
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- CN105897207A CN105897207A CN201610182628.7A CN201610182628A CN105897207A CN 105897207 A CN105897207 A CN 105897207A CN 201610182628 A CN201610182628 A CN 201610182628A CN 105897207 A CN105897207 A CN 105897207A
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- comparator
- amplifier
- gain control
- current switch
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03G—CONTROL OF AMPLIFICATION
- H03G1/00—Details of arrangements for controlling amplification
- H03G1/0005—Circuits characterised by the type of controlling devices operated by a controlling current or voltage signal
- H03G1/0088—Circuits characterised by the type of controlling devices operated by a controlling current or voltage signal using discontinuously variable devices, e.g. switch-operated
Abstract
Disclosed in the invention is a continuous variable gain amplifier comprising a gain control circuit, a resistance network and a trans-impedance amplifier. The gain control circuit is used for generating gain control levels to control turning on or off of current switches in the resistance network and controlling a continuous split ratio change corresponding to each current switch; the resistance network is used for converting input voltage signals into continuously changing current signals under control of the gain control levels and outputting the current signals; and the trans-impedance amplifier is used for converting the current signals outputted by the resistance network into output voltage signals. Therefore, continuous gain control of a current domain is realized by using multiple current switches; and thus the amplifier can work in a current mode, so that high bandwidth and high linearity are realized with low power consumption and thus the ultra wide band application is met. In addition, because realization of the continuous variable gain amplifier does not rely on the high-performance amplifier and the circuit structure is simple, the amplifier is easy to realize with low costs.
Description
Technical field
The present invention relates to electronic technology field, particularly relate to a kind of continuous variable gain amplifier.
Background technology
In various Radio Transmission Technologys, due to practical communication environment, such as communication distance, obstacle, the difference of interference, wireless
Receiving-transmitting chain gain in communication equipment often has large range of change, therefore, generally individually can arrange in receiving-transmitting chain
There is corresponding VGA (Variable Gain Amplifier, variable gain amplifier), such as the VGA of continuous, also cry continuously
VGA, provides variable gain to realize constant output signal power.
Specifically, as it is shown in figure 1, the typical structural representation of the continuous VGA that it is existing X Amplifier type.By
Fig. 1 understands, and described X amplifier can include resistor network 11, transconductance stage circuit 12, gain control circuit 13, output-stage circuit 14
And feedback resistance 15, wherein: described resistor network 11, can be used for that input voltage signal is converted to one group and there is fixed attenuation
The voltage signal of stepping, the corresponding transconductance stage that each voltage signal after conversion can be input in transconductance stage circuit 12
Input anode；Transconductance stage circuit 12, can be used under the control of gain control circuit 13, the voltage inputted by resistor network 11
Signal is converted to current signal and exports to output-stage circuit 14；Output-stage circuit 14, can be used for the current signal that will receive
Be converted to voltage signal and export, it addition, output-stage circuit 14 is also with feedback resistance 15, and output signal is fed back to mutual conductance
The input negative terminal of each transconductance stage in level circuit 12.
It is to say, in X amplifier, transconductance stage circuit 12 and output-stage circuit 14 may make up a voltage amplifier,
Utilizing resistive degeneration to promote the linearity, therefore, X amplifier can obtain the higher linearity.But, due to X amplifier
Using voltage-type mode of operation, open-loop gain bandwidth is amassed limited, and under the conditions of ultra broadband, loop gain deficiency, the linearity are disliked
Change notable, thus there is the problem being difficult to realize high linearity under ultra broadband.Further, since the Continual Gain Actuator control of X amplifier
System is by regulating current source distribution in transconductance stage and then gating different signal voltage realizations, thus so that control
Circuit is complex, and chip area is bigger.Further, owing to the performance of X amplifier depends on high performance amplifier, thus, also deposit
Being difficult at CMOS (Complementary Metal Oxide Semiconductor, complementary metal oxide semiconductors (CMOS)) or
BICMOS (Bipolar Complementary Metal Oxide Semiconductor, partly lead by bipolar complementary metal oxidation
Body) etc. realize under technique, need to rely on high-performance technique and cause relatively costly etc. problem.
In sum, the VGA existence continuously such as existing X amplifier is difficult to realize high linearity and gain under ultra broadband
The problem that control circuit is more complicated, relatively costly etc..Therefore, a kind of new continuous VGA of offer is needed badly to solve the problems referred to above.
Summary of the invention
Embodiments provide a kind of continuous variable gain amplifier, be difficult in order to solve existing continuous VGA
High linearity and more complicated, relatively costly etc. the problem of circuit is realized under ultra broadband.
First aspect, it is provided that a kind of continuous variable gain amplifier, including gain control circuit, resistor network and across
Impedance amplifier, wherein, described resistor network includes that L resistance sub-network, each resistance sub-network include from signal input part coupling
Being bonded to N bar the first parallel branch and second parallel branch of signal output part, each first parallel branch includes the one of series connection
First resistance and a current switch, described second parallel branch includes one second resistance, and, the first parallel connection that each two is adjacent
Being serially connected with one the 3rd resistance between branch road, wherein, the value of described L is 1 or 2, and described N is the positive integer not less than 2 and described N
It is 1 with the difference of the exponent number of described resistor network:
Described gain control circuit, for according to controlling voltage signal, generates gain control level, described gain control electricity
Equal the on and off of N number of current switch in N bar the first parallel branch for controlling each resistance sub-network, and control institute
State the split ratio consecutive variations that each current switch in N number of current switch is corresponding；
Described resistor network, under the control of the described gain control level of described gain control circuit, will input
Voltage signal is converted into the current signal of continuous variable and exports to described trans-impedance amplifier；
Described trans-impedance amplifier, the described current signal for being exported by described resistor network is converted to output voltage letter
Number.
Wherein, the split ratio that current switch is corresponding typically refers to the output electric current of current switch and the input electricity of current switch
The ratio of stream.
In conjunction with first aspect, in the first possible implementation of first aspect, described gain control circuit includes
Datum generative circuit and N number of comparator, described N number of comparator is in parallel with the N bar first of each resistance sub-network respectively
N number of current switch one_to_one corresponding in branch road；
Described datum generative circuit, for generating and the described the most N number of datum of N number of comparator, and
By the output of each datum to corresponding comparator；Wherein, described N number of datum according to set order raise successively or
Reduce successively；
Each comparator, for comparing the datum of described control voltage signal and input extremely described comparator
Relatively, generate one group of gain control level and export to corresponding current switch；Wherein, described N number of comparator is generated and is exported
Often group gain control level to the N group gain control level of corresponding current switch is provided with the common mode electrical level fixed.
In conjunction with first aspect, in the implementation that the second of first aspect is possible, described gain control circuit includes
Datum generative circuit and M comparator, described M is more than described N；And, each comparator in described M comparator and
Another comparator combination of two being separated by Z comparator with described comparator can obtain N group comparator, described N group comparator
Respectively with the N number of current switch one_to_one corresponding in N bar first parallel branch of each resistance sub-network, described Z is the most natural
Number；
Described datum generative circuit, for generating and described M comparator M datum one to one, and
By the output of each datum to corresponding comparator；Wherein, described M datum according to set order raise successively or
Reduce successively；
Often the first comparator in group comparator, for described control voltage signal and input extremely described first comparator
Datum compare, generate a pair gain control level, and by generate this in gain control level along with institute
The gain control level in rising trend that increases stating control voltage signal exports to the current switch corresponding to this group comparator；
Often the second comparator in group comparator, for described control voltage signal and input extremely described second comparator
Datum compare, generate a pair gain control level, and by generate this in gain control level along with institute
The gain control level on a declining curve that increases stating control voltage signal exports to the current switch corresponding to this group comparator；
Wherein, the datum that described first comparator is corresponding is less than the datum that described second comparator is corresponding, and,
Described N group comparator exported to corresponding current switch, by the first comparator output along with described control voltage signal
Increase gain control level in rising trend and the second comparator output along with described control voltage signal increase in
The often group gain control level that the gain control level of downward trend is formed is provided with the common mode electrical level fixed.
In conjunction with the implementation that the second of first aspect is possible, in the third possible implementation of first aspect
In, if the difference of described M and described N is 1, each comparator in the most described M comparator and adjacent with described comparator another
One comparator combination of two obtains N group comparator.
In conjunction with the first of first aspect to any one the possible implementation in the third possible implementation,
In 4th kind of possible implementation of first aspect, described comparator is difference amplifier.
In conjunction with any one the possible implementation in the 4th kind of possible implementation of first aspect to first aspect,
In the 5th kind of possible implementation of first aspect, each current switch includes two MOS (Metal-Oxide-
Semiconductor, metal-oxide semiconductor (MOS)) pipe；
First end and the resistance being in series with described current switch of said two metal-oxide-semiconductor are connected, and the second end is with described
The signal output part of gain control circuit is connected；3rd termination one fixed level of the metal-oxide-semiconductor in said two metal-oxide-semiconductor, separately
3rd end of one metal-oxide-semiconductor is connected with the signal input part of described trans-impedance amplifier；Described second end is the gate terminal of metal-oxide-semiconductor.
In conjunction with the 5th kind of possible implementation of first aspect, in the 6th kind of possible implementation of first aspect
In, described metal-oxide-semiconductor is N-type metal-oxide-semiconductor or p-type metal-oxide-semiconductor.
In conjunction with any one the possible implementation in the 6th kind of possible implementation of first aspect to first aspect,
In the 7th kind of possible implementation of first aspect, described trans-impedance amplifier is based on current amplifier across resistance amplification
Amplifying across resistance of device, trans-impedance amplifier based on operational amplifier, the trans-impedance amplifier of cobasis scale-up version or common grid scale-up version
Device.
In conjunction with any one the possible implementation in the 7th kind of possible implementation of first aspect to first aspect,
In the 8th kind of possible implementation of first aspect, if the value of described L is 1, the most described trans-impedance amplifier is single-ended defeated
Enter trans-impedance amplifier.
In conjunction with any one the possible implementation in the 7th kind of possible implementation of first aspect to first aspect,
In the 9th kind of possible implementation of first aspect, if the value of described L is 2, the most described trans-impedance amplifier is that difference is defeated
Enter trans-impedance amplifier.
As shown in the above, the continuous variable gain amplifier that the embodiment of the present invention provides can use multiple current switch
The Continual Gain Actuator realizing current field controls, i.e. be operable with under current-mode, such that it is able to realize high-band under relatively low power consumption
Width and high linearity, meet ultra wideband applications, solve existing continuous VGA and be difficult to realize asking of high linearity under ultra broadband
Topic.Further, since the realization of continuous variable gain amplifier that the embodiment of the present invention is provided does not relies on high performance amplifier,
Can realize based on non-high-performance techniques such as CMOS or BICMOS, thus, cost can be substantially reduced；Further, owing to the present invention implements
The gain control of the continuous variable gain amplifier that example is provided uses current switch and resistor network to realize, thus so that its
Circuit structure is relatively simple, is easier to realize.
Accompanying drawing explanation
For the technical scheme being illustrated more clearly that in the embodiment of the present invention, in embodiment being described below required for make
Accompanying drawing briefly introduce, it should be apparent that, below describe in accompanying drawing be only some embodiments of the present invention, for this
From the point of view of the those of ordinary skill in field, on the premise of not paying creative work, it is also possible to obtain other according to these accompanying drawings
Accompanying drawing.
Fig. 1 show the typical structural representation of the continuous VGA of existing X Amplifier type；
What Fig. 2 showed in the embodiment of the present invention possesses the one of the continuous variable gain amplifier of a resistance sub-network
Possible structural representation；
What Fig. 3 showed in the embodiment of the present invention possesses the one of the continuous variable gain amplifier of two resistance sub-networks
Possible structural representation；
A kind of possible structural representation of the current switch that Fig. 4 show in the embodiment of the present invention；
A kind of possible structural representation of the gain control circuit that Fig. 5 show in the embodiment of the present invention；
A kind of possible structural representation of the 7 rank resistor networks that Fig. 6 show in the embodiment of the present invention；
A kind of possible gain control curve synoptic diagram of the 7 rank resistor networks that Fig. 7 show in the embodiment of the present invention；
A kind of possible schematic diagram of one group of gain control curve that Fig. 8 show in the embodiment of the present invention；
A kind of possible structural representation of the difference amplifier that the comparator that Fig. 9 show in the embodiment of the present invention is used
Figure；
A kind of possible control schematic diagram of the gain control circuit that Figure 10 show in the embodiment of the present invention；
The alternatively possible schematic diagram of one group of gain control curve that Figure 11 show in the embodiment of the present invention；
A kind of possible structure of the trans-impedance amplifier based on current amplifier that Figure 12 show in the embodiment of the present invention
Schematic diagram；
A kind of possible structure of the trans-impedance amplifier based on operational amplifier that Figure 13 show in the embodiment of the present invention
Schematic diagram；
A kind of possible structural representation of the cobasis scale-up version trans-impedance amplifier that Figure 14 show in the embodiment of the present invention.
Detailed description of the invention
In order to make the object, technical solutions and advantages of the present invention clearer, below in conjunction with accompanying drawing the present invention made into
One step ground describes in detail, it is clear that described embodiment is only a part of embodiment of the present invention rather than whole enforcement
Example.Based on the embodiment in the present invention, those of ordinary skill in the art are obtained under not making creative work premise
All other embodiments, broadly fall into the scope of protection of the invention.
It is difficult under ultra broadband, realize high linearity and circuit is more complicated, relatively costly to solve existing continuous VGA
Deng problem, embodiments provide a kind of continuous variable gain amplifier, as in figure 2 it is shown, described continuous variable gain
Amplifier can include gain control circuit 21, resistor network 22 and trans-impedance amplifier 23, and wherein, described resistor network includes L
Individual resistance sub-network, each resistance sub-network includes N bar the first parallel branch coupleding to signal output part from signal input part
And second parallel branch, each first parallel branch includes one first resistance and a current switch of series connection, described second
Parallel branch includes one second resistance, and, it is serially connected with one the 3rd resistance between the first parallel branch that each two is adjacent, wherein,
The value of described L is determined by the input number of the trans-impedance amplifier 23 of rear end, and concretely 1 or 2 (as a example by Fig. 2, described L
Value be 1, i.e. include a resistance sub-network), described N is the positive integer not less than 2 and described N and described resistor network
The difference of the exponent number of 22 is that 1 (wherein, the exponent number of resistor network refers to the dividing potential drop number of times that resistor network is capable of, every dividing potential drop one
Secondary for single order；And, the most identical with the quantity of the 3rd resistance that the resistance sub-network of resistor network is comprised):
Described gain control circuit 21, can be used for according to controlling voltage signal, and (level also can be named to generate gain control level
Voltage), the described gain control level N number of current switch in N bar the first parallel branch controlling each resistance sub-network
On and off, and control split ratio consecutive variations corresponding to each current switch in described N number of current switch (wherein,
The split ratio that current switch is corresponding typically refers to the output electric current of current switch and the ratio of the input current of current switch)；
Described resistor network 22, can be used under the control of the described gain control level of described gain control circuit 21,
Input voltage signal is converted into the current signal of continuous variable and exports to described trans-impedance amplifier 23；
Described trans-impedance amplifier 23, can be used for the described current signal that described resistor network 22 exports is converted to output electricity
Pressure signal.
It is to say, the continuous variable gain amplifier that the embodiment of the present invention is provided can use multiple current switch to realize
The Continual Gain Actuator of current field controls, i.e. be operable with under current-mode, such that it is able to realize under relatively low power consumption high bandwidth and
High linearity, meets ultra wideband applications, solves the problem that existing continuous VGA is difficult to realize high linearity under ultra broadband.
Further, since the realization of continuous variable gain amplifier that the embodiment of the present invention is provided does not relies on high performance amplifier, can
Realize based on non-high-performance techniques such as CMOS or BICMOS, thus, cost can be substantially reduced；Further, due to the embodiment of the present invention
The gain control of the continuous variable gain amplifier provided uses current switch and resistor network to realize, thus so that its electricity
Line structure is relatively simple, is easier to realize.
It should be noted that with the input impedance of resistance sub-network, as R, (value of this R can set flexibly according to practical situation
Fixed) as a example by, then as in figure 2 it is shown, the value of the second resistance in resistance sub-network can be (1+1/P) R, the value of the first resistance can
For (P+1) R, the value of the 3rd resistance can be R/P.Wherein, P be set resistor network parameter (its value can be according to actual feelings
Condition combines the design experiences of those skilled in the art and sets flexibly, and the numerical value of typically greater than 0), this is not repeated.
Further, as it is shown on figure 3, the resistor network 22 of described continuous variable gain amplifier may also include two resistance
Sub-network, in such cases, the input voltage signal of resistor network 22 can be two paths of differential signals, and i.e. a pair equal in magnitude and pole
The symmetric signal (Vip and Vin as shown in Figure 3) that property is contrary.
It addition, from the figure 3, it may be seen that in such cases, each resistance sub-network of described resistor network may each comprise from signal
Input coupled to N bar the first parallel branch and second parallel branch of signal output part, and each first parallel branch includes
One first resistance of series connection and a current switch, described second parallel branch includes one second resistance, and, each two is adjacent
One the 3rd resistance it is serially connected with between first parallel branch.
It is to say, in the present embodiment, described continuous variable gain amplifier can use fully differential structure to realize.That is, its
Resistor network can include and two paths of differential signals two resistance sub-networks one to one, the knot that each resistance sub-network is possessed
The structure that structure is possessed with the resistor network in Fig. 2 is identical.In addition, it is necessary to explanation, now, the electricity that resistor network is exported
Stream signal is also corresponding two-way, Ioutp and Ioutn as shown in Figure 3, the voltage signal that trans-impedance amplifier is exported also is
Corresponding two-way, Von and Vop etc. as shown in Figure 3.If further, the input impedance of each resistance sub-network is R, then resistance
The differential input impedance of network can be 2R, does not repeats this.
Alternatively, as shown in Figure 4, each current switch in described resistor network 22 can use two metal-oxide-semiconductors (to be not limited to
Shown in Fig. 4 two NMOS tube M1 and M2, it is possible to be two PMOS etc.) realize, wherein:
First end and the resistance being in series with described current switch of said two metal-oxide-semiconductor are connected, and the second end is with described
The signal output part of gain control circuit 21 is connected；Of a metal-oxide-semiconductor (the metal-oxide-semiconductor M2 as in Fig. 4) in said two metal-oxide-semiconductor
Three termination one fixed levels (specifically, when this metal-oxide-semiconductor is NMOS tube, its 3rd end can ground connection or low level, specifically can as figure
Shown in 4；When this metal-oxide-semiconductor is PMOS, its 3rd end can connect a fixing high level, and this high level can be higher than described low electricity
Flat), the 3rd end of another metal-oxide-semiconductor (the metal-oxide-semiconductor M1 in Fig. 4) with as described in the corresponding signal input phase of trans-impedance amplifier 23
Even；Described second end is the gate terminal of metal-oxide-semiconductor, and described first end, the 3rd end are the non-gate terminal of metal-oxide-semiconductor, e.g., as described MOS
When pipe is for NMOS tube, described first end can be drain electrode, and the 3rd end can be source electrode.
Wherein it is desired to explanation, in the present embodiment, two metal-oxide-semiconductor M1 Yu M2 all work in deep linear zone, are equivalent to two
Individual variable resistance R1 (corresponding metal-oxide-semiconductor M1) and the parallel connection of R2 (corresponding metal-oxide-semiconductor M2).Correspondingly, by two metal-oxide-semiconductor grids of regulation
Control voltage Vctrl1 and Vctrl2, split ratio C (the output electric current of metal-oxide-semiconductor M1 and the institute of output current signal can be changed
State the ratio of the input current of current switch):
It is to say, as a example by the current switch described in Fig. 4, when M2 pipe complete switches off, during the conducting of M1 pipe, current signal is only
Flow through M1, corresponding to current switch fully on state；When M1 pipe complete switches off, during the conducting of M2 pipe, current signal flows only through M2,
State is complete switched off corresponding to current switch；And when M2 Yu M1 all presents certain impedance, when not turning off, open corresponding to electric current
Close complete switch off～fully on intermediateness, now, current switch output current signal can consecutive variations, with realize
Any split ratio between 0 to 1.
Alternatively, described gain control circuit 21, it is particularly used according to controlling voltage signal (i.e. Vctrl) generation N group
Gain control level, described N group gain control level N number of with N bar first parallel branch of each resistance sub-network respectively
Current switch one_to_one corresponding, and by often organizing the gain control level output grid to corresponding current switch, to control each electricity
N number of current switch in N bar first parallel branch of resistance sub-network sequentially turns on, and controls N article of each resistance sub-network the
The split ratio consecutive variations that each current switch in N number of current switch in one parallel branch is corresponding.
Specifically, due to during Continual Gain Actuator control, working properly in order to ensure resistor network 22, have fixing
Decay stepping, it should make current switch have constant impedance.And, due to as a example by the current switch shown in Fig. 4, M1's and M2
Parallel impedance is as follows:
Where it is assumed that metal-oxide-semiconductor M1 and M2 is identical transistor, μ refers to the carrier density of arbitrary metal-oxide-semiconductor, coxRefer to
Unit are gate oxide capacitance, W refers to the width of arbitrary metal-oxide-semiconductor, and L refers to the length of arbitrary metal-oxide-semiconductor, VGS1Refer to the grid of metal-oxide-semiconductor M1
Pole tension, VGS2Refer to the grid voltage of metal-oxide-semiconductor M2, VTHRefer to the threshold voltage of arbitrary metal-oxide-semiconductor.
That is, V is worked asGS1+VGS2-2VTHTime fixing, can ensure that current switch impedance is fixed.Thus, in the present embodiment, gain
Control circuit 21 generates and exports the often group gain control level of the current switch to correspondence and is required to have fixing common mode electricity
Flat, with during Continual Gain Actuator control so that the constant impedance of current switch；It addition, gain control circuit 21 generates and defeated
The N group gain control level gone out to corresponding current switch needs to control in N bar first parallel branch of each resistance sub-network
N number of current switch sequentially turn on, high linearity could be kept during Continual Gain Actuator control, this is not repeated.
Wherein it is desired to explanation, when described resistor network 22 is working properly, the decay stepping of described resistor network 22
AstepCan be expressed as follows, i.e. can be arranged by parameter P adjusting resistor network 22:
Such as, as a example by the continuous variable gain amplifier shown in Fig. 3, under the excitation of 200 ohm differential source impedances, for
The input coupling that realization is good, R may be configured as 100 ohm.If requiring, decay stepping is-2.5dB, then P may be configured as 3.Need
It is noted that decay stepping is the least, then the gain control curve often organizing gain control level that gain control circuit 21 generates
Closer to linearly, and, the resistor network exponent number of needs is the highest, does not repeats this.
Alternatively, as it is shown in figure 5, described gain control circuit 21 specifically can include datum generative circuit and N number of
Comparator, such as comparator 1～comparator N；Described N number of comparator respectively with N bar first parallel branch of each resistance sub-network
In N number of current switch one_to_one corresponding；
Described datum generative circuit, can be used for generating and the described the most N number of datum of N number of comparator,
And by the output of each datum to corresponding comparator；Wherein, described N number of datum raises successively according to the order set
Or reduce successively；Such as, as it is shown in figure 5, described datum generative circuit can generate Vref_1, Vref_2 ..., Vref_N
N number of datum raised successively, does not repeats this altogether；
Each comparator, can be used for controlling voltage signal (Vctrl as shown in Figure 5) and input to described comparator
Datum compares, and generates one group of gain control level and exports to corresponding current switch；Wherein, described N number of comparison
The often group gain control level that device is generated and exports to the N group gain control level of corresponding current switch is provided with fixing
Common mode electrical level.
It is to say, in the implementing of gain control circuit 21, N number of ginseng can be generated based on datum generative circuit
Examine level and send into N number of comparator, and based on described N number of comparator, control voltage signal and each datum are compared,
Generate N group gain control level (i.e. obtaining N group gain control curve), in parallel to control the N bar first of each resistance sub-network
N number of current switch in branch road sequentially turns on.
Such as, as shown in Figure 6, it is assumed that the exponent number of resistor network 22 is 7, i.e. each resistance sub-network possesses 8 electric currents and opens
Close (such as sw1～sw8), then gain control circuit 21 specifically can generate 8 groups of gain control curves as shown in Figure 7.Can by Fig. 7
Knowing, often group gain control curve all can have fixing common mode electrical level, and, raise along with controlling the continuous of voltage signal Vctrl,
Current switch sw1, sw2 ..., sw8 will be successively from turning off to fully on；In addition, it is necessary to explanation, the gain shown in Fig. 7
What the longitudinal axis of controlling curve represented is the size of the gain control level generated, and its value generally can be at the source electrode electricity of current switch
Change between flat (such as 1.25V)～the supply voltage (such as 2.5V) of gain control circuit 21；Further, each comparator generates
One group of gain control level may each comprise one and increase gain control in rising trend electricity along with described control voltage signal
Flat and, one increase gain control level on a declining curve along with described control voltage signal, this is not repeated.
Further, in the present embodiment, each comparator specifically can use difference amplifier, and (difference amplifier refers to handle
The circuit that the difference of two input voltages is amplified) realize, with to controlling voltage signal Vctrl and corresponding datum
Vref carries out differential amplification, generates a pair gain control level Vctrl_p and Vctrl_n, to obtain shown in Fig. 8 group gain
Controlling curve.Specifically, as shown in Figure 8, when Vctrl is equal to Vref, the gain control level of output is equal, is exactly equal to altogether
Mould level, does not repeats this.
In addition, it is necessary to explanation, in the present embodiment, each comparator can use the difference amplifier shown in Fig. 9 to realize.
As shown in Figure 9, described difference amplifier can include a pair symmetrically arranged PMOS, two to be respectively symmetrically the NMOS tube of setting with
And two resistance, constant-current sources.Certainly, it should be noted that comparator also can use the structure being different from shown in Fig. 9, only
Want can according to control voltage signal Vctrl and corresponding reference level Vref generate a pair gain control level Vctrl_p and
Vctrl_n, is not limited in any way this.
Alternatively, so that gain control is more flexible, in the present embodiment, also can being separated by Z, individual (described Z is any
Natural number, as 0,1 or 2 etc.) two comparators of comparator, the gain control level such as two adjacent comparators combines
Get up to work, to reach the spacing by regulating datum, adjust the common mode of the gain control curve ultimately generated neatly
The effect of level.
Specifically, in such cases, described gain control circuit 21 can include that datum generative circuit and M is compared
Device, described M is more than described N；And, each comparator in described M comparator and be separated by Z comparator with described comparator
Another comparator combination of two can obtain N group comparator, described N group comparator respectively with N article of each resistance sub-network
N number of current switch one_to_one corresponding in one parallel branch, described Z is random natural number；
Described datum generative circuit, can be used for generating and described M comparator M datum one to one,
And by the output of each datum to corresponding comparator；Wherein, described M datum raises successively according to the order set
Or reduce successively；
Often the first comparator in group comparator, can be used for controlling voltage signal and input to described first comparator
Datum compares, and generates a pair gain control level, and by generate this in gain control level along with described
The gain control level in rising trend that increases controlling voltage signal exports to the current switch corresponding to this group comparator；
Often the second comparator in group comparator, can be used for controlling voltage signal and input to described second comparator
Datum compares, and generates a pair gain control level, and by generate this in gain control level along with described
The gain control level on a declining curve that increases controlling voltage signal exports to the current switch corresponding to this group comparator；
Wherein, the datum that described first comparator is corresponding is less than the datum that described second comparator is corresponding, and,
Described N group comparator exported to corresponding current switch, by the first comparator output along with described control voltage signal
Increase gain control level in rising trend and the second comparator output along with described control voltage signal increase in
The often group gain control level that the gain control level of downward trend is formed is provided with the common mode electrical level fixed.
For example, it is assumed that each resistance sub-network possesses sw1～N altogether N number of current switch, gain control circuit 21 possesses and compares
Device 1～M M comparator altogether, and M deducts N equal to 1, and, comparator 1 and 2 corresponding current switch sw1, comparator 2 and 3 is corresponding electric
Stream switch sw2 ..., comparator M-1 and comparator M corresponding current switch swN, i.e. each comparison in described M comparator
Device and another comparator combination of two adjacent with described comparator obtain N group comparator, the most as shown in Figure 10:
When current switch is controlled, the Vctrl_ that the Vctrl_1p that can be generated by comparator 1 and comparator 2 generate
2n is combined as the gain control level of current switch sw1, is connected to the grid of current switch sw1, e.g., is connected to by Vctrl_1p
The grid of the M1 of current switch sw1, Vctrl_2n is connected to the grid of the M2 of current switch sw1；And, comparator 2 is generated
Vctrl_2p and the Vctrl_3n that generates of comparator 3 be combined as the gain control level of current switch sw2, be connected to electric current and open
Closing the grid of sw2, e.g., Vctrl_2p is connected to the grid of the M1 of current switch sw2, Vctrl_3n is connected to current switch
The grid etc. of the M2 of sw2.
Correspondingly, in such cases, as a example by current switch sw1, corresponding one group that gain control circuit 21 is generated
Compared by the gain control level in rising trend and second that increases along with described control voltage signal of the first comparator output
The gain control formed compared with the increase gain control level on a declining curve along with described control voltage signal of device output
Curve can be as shown in figure 11.As shown in Figure 11, if the difference of datum corresponding to two comparators is △ Vref, then common mode electricity
Putting down and can improve △ Vref*K/2, wherein, K is the absolute value of gain control slope of a curve.It is to say, in this way,
The spacing by regulating datum can be reached, adjust the gain control curve that gain control circuit 21 ultimately generates neatly
The effect of common mode electrical level.
In addition, it is necessary to explanation, include as a example by two NMOS tube by each current switch, this current switch corresponding one
In group gain control level along with described control voltage signal to increase gain control level in rising trend the most corresponding
The NMOS tube in described current switch, impedance is on a declining curve；In one group of gain control level that this current switch is corresponding
Along with increasing of described control voltage signal is in the most corresponding described current switch of gain control level on a declining curve,
The NMOS tube that impedance is in rising trend, does not repeats this.
Further, it should be noted that in the present embodiment, be all to include that a datum generates with gain control circuit 21
Illustrate as a example by circuit, but, it practice, the number of the datum generative circuit included by gain control circuit 21
Do not limit, as being N number of etc., as long as N number of datum raising successively according to the order set or reducing successively can be generated
And export to corresponding comparator, this is not repeated.
Further, in the present embodiment, described trans-impedance amplifier 23 can possess multiple implementation, e.g., can be based on
The trans-impedance amplifier of current amplifier, trans-impedance amplifier based on operational amplifier, cobasis scale-up version or altogether grid scale-up version across
Impedance amplifier etc., as long as the current signal that described resistor network 22 exports can be converted to voltage signal and export by it,
This is not limited in any way.
In addition, it is necessary to explanation, if the value of described L is 1, the most described trans-impedance amplifier 23 usually single ended input across
Impedance amplifier (specifically can be as shown in Figure 2)；If the value of described L is 2, the most described trans-impedance amplifier 23 usually Differential Input across
Impedance amplifier (specifically can be as shown in Figure 3).
Specifically, with trans-impedance amplifier 23 for Differential Input trans-impedance amplifier (being the trans-impedance amplifier shown in Fig. 3),
And as a example by being trans-impedance amplifier based on current amplifier, now, the structural representation of described trans-impedance amplifier 23 can be such as Figure 12
Shown in.
As shown in Figure 12, described trans-impedance amplifier 23 can include two input pipe Q1, two second level PMOS M2, two
Source follower M3, multiple current source and two feedback resistance Rf.The operation principle of described trans-impedance amplifier 23 is: electric current is believed
Number inflow input pipe Q1 (input pipe is not limited to audion, it is possible to for metal-oxide-semiconductor), and at current source load, be converted to voltage letter
Number, and amplify through second level M2 pipe common source, export finally by source follower M3.Source follower exports current input terminal and adds
Upper described feedback resistance, improves the trans-impedance amplifier linearity by resistive degeneration, now, trans-impedance amplifier 23 across resistance
Transimpedance can be expressed as:
Wherein, ro1For the output impedance of the Q1 in Figure 12, ro2For the output impedance of the M2 in Figure 12, RfAnti-in Figure 12
Feed resistance, gm2For the mutual conductance of the M2 in Figure 12, ASFGain for the M3 in Figure 12.From above formula, when open-loop gain is sufficiently high
Time, trans-impedance amplifier 23 approximate feedback resistance R across resistancef。
Further, with trans-impedance amplifier 23 for Differential Input trans-impedance amplifier, and it is based on operational amplifier across resistance
As a example by amplifier, now, the structural representation of described trans-impedance amplifier 23 can be as shown in figure 13.
As shown in Figure 13, described trans-impedance amplifier 23 can include an operational amplifier and two feedback resistance Rf.Logical
The high open-loop gain crossing operational amplifier can realize low input impedance, and according to the short characteristic of the void of operational amplifier, this structure realizes
Be actually the size of feedback resistance across resistance, can be expressed as follows:
Further, with trans-impedance amplifier 23 for Differential Input trans-impedance amplifier, and it it is cobasis scale-up version trans-impedance amplifier
As a example by, now, the structural representation of described trans-impedance amplifier 23 can be as shown in figure 14.
As shown in Figure 14, described trans-impedance amplifier 23 can include that four audions, two sign-changing amplifiers and four are negative
Carry resistance RL, with input stage circuit, mutual conductance intensifier circuit realizes higher equivalent transconductance, thus realizes low input impedance.Defeated
Enter electric current directly through load resistance, this structure realize across resistance the most i.e. equal to load resistance RL, it may be assumed that
Further, it should be noted that in the present embodiment, it is assumed that control voltage signal is Vctrl, trans-impedance amplifier 23
Realize is equal to R across resistancef, then, as a example by Fig. 2, when current switch is all in off state, least gain Gain is obtainedmin, this
Time control voltage signal be Vctrlmin, it may be assumed that
When current switch is all in fully on state, obtain maximum gain Gainmax, now controlling voltage signal is
Vctrlmax:
It is to say, the gain of continuous variable gain amplifier in the present embodiment and controlling between voltage signal Vctrl
Relation be represented by:
In addition, it is necessary to explanation, technical scheme described in the present embodiment goes for any needing Continual Gain Actuator control
Circuit engineering field, as being applicable to frequency mixer etc..The voltage conversion to electric current, electric current typically can be included due to optical mixing process
Territory is mixed with local oscillator, and voltage changes the processes such as output, thus, it is adaptable to during frequency mixer, technical scheme described in the present embodiment
Can be used for voltage to electric current change after, it is achieved the consecutive variations of current signal, to realize the continuous variable of mixer gain, right
This does not repeats.
As shown in the above, the continuous variable gain amplifier that the embodiment of the present invention provides can use multiple current switch
The Continual Gain Actuator realizing current field controls, i.e. be operable with under current-mode, such that it is able to realize high-band under relatively low power consumption
Width and high linearity, meet ultra wideband applications, solve existing continuous VGA and be difficult to realize asking of high linearity under ultra broadband
Topic.Further, since the realization of continuous variable gain amplifier that the embodiment of the present invention is provided does not relies on high performance amplifier,
Can realize based on non-high-performance techniques such as CMOS or BICMOS, thus, cost can be substantially reduced；Further, owing to the present invention implements
The gain control of the continuous variable gain amplifier that example is provided uses current switch and resistor network to realize, thus so that electricity
Line structure is relatively simple, is easier to realize.
In addition, it is necessary to explanation, " first ", " second " and " the 3rd " mentioned in the present embodiment etc. is not used in qualifier
The order of body or quantity.Such as, any one in the first resistance, the second resistance or the 3rd resistance can essentially include multiple string
The resistance etc. that connection resistance, parallel resistance or any-mode connect.
Although preferred embodiments of the present invention have been described, but those skilled in the art once know basic creation
Property concept, then can make other change and amendment to these embodiments.So, claims are intended to be construed to include excellent
Select embodiment and fall into all changes and the amendment of the scope of the invention.
Obviously, those skilled in the art can carry out various change and the modification essence without deviating from the present invention to the present invention
God and scope.So, if these amendments of the present invention and modification belong to the scope of the claims in the present invention and equivalent technologies thereof
Within, then the present invention is also intended to comprise these change and modification.
Claims (10)
1. a continuous variable gain amplifier, it is characterised in that include gain control circuit, resistor network and amplify across resistance
Device, wherein, described resistor network includes that L resistance sub-network, each resistance sub-network include coupleding to letter from signal input part
N bar first parallel branch of number outfan and the second parallel branch, each first parallel branch includes one first electricity of series connection
Resistance and a current switch, described second parallel branch includes one second resistance, and, adjacent the first parallel branch of each two it
Between be serially connected with one the 3rd resistance, wherein, the value of described L is 1 or 2, and described N is that the positive integer not less than 2 and described N are with described
The difference of the exponent number of resistor network is 1；
Described gain control circuit, for according to controlling voltage signal, generating gain control level, described gain control level is used
The on and off of the N number of current switch in N bar the first parallel branch controlling each resistance sub-network, and control described N
The split ratio consecutive variations that each current switch in individual current switch is corresponding；
Described resistor network, under the control of the described gain control level of described gain control circuit, by input voltage
Signal is converted into the current signal of continuous variable and exports to described trans-impedance amplifier；
Described trans-impedance amplifier, is converted to output voltage signal for the described current signal exported by described resistor network.
2. continuous variable gain amplifier as claimed in claim 1, it is characterised in that described gain control circuit includes reference
Level generating circuitry and N number of comparator, described N number of comparator respectively with N bar first parallel branch of each resistance sub-network
In N number of current switch one_to_one corresponding；
Described datum generative circuit, for generating and the described the most N number of datum of N number of comparator, and will be every
One datum output is to corresponding comparator；Wherein, described N number of datum raises or successively successively according to the order set
Reduce；
Each comparator, for the datum of described control voltage signal and input extremely described comparator is compared, raw
Become one group of gain control level and export to corresponding current switch；Wherein, described N number of comparator is generated and is exported to correspondence
Current switch N group gain control level in often group gain control level be provided with the common mode electrical level fixed.
3. continuous variable gain amplifier as claimed in claim 1, it is characterised in that described gain control circuit includes reference
Level generating circuitry and M comparator, described M is more than described N；And, each comparator in described M comparator and with institute
Stating comparator to be separated by another comparator combination of two of Z comparator and can obtain N group comparator, described N group comparator is respectively
With the N number of current switch one_to_one corresponding in N bar first parallel branch of each resistance sub-network, described Z is random natural number；
Described datum generative circuit, for generating and described M comparator M datum one to one, and will be every
One datum output is to corresponding comparator；Wherein, described M datum raises or successively successively according to the order set
Reduce；
Often the first comparator in group comparator, for described control voltage signal and the ginseng of input extremely described first comparator
Examine level to compare, generate a pair gain control level, and by generate this in gain control level along with described control
The gain control level in rising trend that increases of voltage signal processed exports to the current switch corresponding to this group comparator；
Often the second comparator in group comparator, for described control voltage signal and the ginseng of input extremely described second comparator
Examine level to compare, generate a pair gain control level, and by generate this in gain control level along with described control
The gain control level on a declining curve that increases of voltage signal processed exports to the current switch corresponding to this group comparator；
Wherein, the datum that described first comparator is corresponding is less than the datum that described second comparator is corresponding, and, described
N group comparator exported to corresponding current switch, by the first comparator output along with the increasing of described control voltage signal
The increase along with described control voltage signal of gain control level the most in rising trend and the output of the second comparator is decline
The often group gain control level that the gain control level of trend is formed is provided with the common mode electrical level fixed.
4. continuous variable gain amplifier as claimed in claim 3, it is characterised in that if the difference of described M and described N is 1, then
Each comparator and another comparator combination of two adjacent with described comparator in described M comparator obtain N group and compare
Device.
5. the continuous variable gain amplifier as described in as arbitrary in claim 2～4, it is characterised in that described comparator is difference
Amplifier.
6. the continuous variable gain amplifier as described in Claims 1 to 5 is arbitrary, it is characterised in that each current switch includes
Two metal-oxide semiconductor (MOS) metal-oxide-semiconductors；
First end and the resistance being in series with described current switch of said two metal-oxide-semiconductor are connected, the second end and described gain
The signal output part of control circuit is connected；3rd termination one fixed level of the metal-oxide-semiconductor in said two metal-oxide-semiconductor, another MOS
3rd end of pipe is connected with the signal input part of described trans-impedance amplifier；Described second end is the gate terminal of metal-oxide-semiconductor.
7. continuous variable gain amplifier as claimed in claim 6, it is characterised in that described metal-oxide-semiconductor is N-type metal-oxide-semiconductor or p-type
Metal-oxide-semiconductor.
8. the continuous variable gain amplifier as described in as arbitrary in claim 1～7, it is characterised in that described trans-impedance amplifier is
Trans-impedance amplifier based on current amplifier, trans-impedance amplifier based on operational amplifier, the trans-impedance amplifier of cobasis scale-up version,
Or it is total to the trans-impedance amplifier of grid scale-up version.
9. the continuous variable gain amplifier as described in as arbitrary in claim 1～8, it is characterised in that if the value of described L is 1,
The most described trans-impedance amplifier is single ended input trans-impedance amplifier.
10. the continuous variable gain amplifier as described in as arbitrary in claim 1～8, it is characterised in that if the value of described L is
2, the most described trans-impedance amplifier is Differential Input trans-impedance amplifier.
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| CN108206680A (en) * | 2016-12-16 | 2018-06-26 | 江苏安其威微电子科技有限公司 | Variable gain amplifier |
| WO2018137155A1 (en) * | 2017-01-24 | 2018-08-02 | 华为技术有限公司 | Optical receiver |
| CN109120232A (en) * | 2017-06-25 | 2019-01-01 | 深圳市前海方成微电子有限公司 | Suitable for low noise, the high bandwidth trans-impedance amplifier of wide dynamic range |
| CN109212259A (en) * | 2017-07-03 | 2019-01-15 | 无锡华润上华科技有限公司 | The front-end circuit of accelerometer |
| CN113824414A (en) * | 2021-11-22 | 2021-12-21 | 中晟微电子(南京)有限公司 | Gain control circuit applied to transimpedance amplifier and control method thereof |
| CN113868170A (en) * | 2021-09-08 | 2021-12-31 | 维沃移动通信有限公司 | Processor, impedance adjusting method and electronic equipment |
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| CN109212259B (en) * | 2017-07-03 | 2021-06-01 | 无锡华润上华科技有限公司 | Front-end circuit of accelerometer |
| CN109212259A (en) * | 2017-07-03 | 2019-01-15 | 无锡华润上华科技有限公司 | The front-end circuit of accelerometer |
| CN113868170A (en) * | 2021-09-08 | 2021-12-31 | 维沃移动通信有限公司 | Processor, impedance adjusting method and electronic equipment |
| CN113868170B (en) * | 2021-09-08 | 2024-04-26 | 维沃移动通信有限公司 | Processor, impedance adjusting method and electronic equipment |
| CN113824414A (en) * | 2021-11-22 | 2021-12-21 | 中晟微电子(南京)有限公司 | Gain control circuit applied to transimpedance amplifier and control method thereof |
Also Published As
| Publication number | Publication date |
|---|---|
| CN109347454A (en) | 2019-02-15 |
| CN105897207B (en) | 2019-01-08 |
| CN109347454B (en) | 2022-02-15 |
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