CN105896986A - Resonant converter and control method thereof - Google Patents
Resonant converter and control method thereof Download PDFInfo
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- CN105896986A CN105896986A CN201410777221.XA CN201410777221A CN105896986A CN 105896986 A CN105896986 A CN 105896986A CN 201410777221 A CN201410777221 A CN 201410777221A CN 105896986 A CN105896986 A CN 105896986A
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Abstract
The present invention discloses a resonant converter and a control method thereof, belonging to the field of the power electronic converter technology. The resonant converter and control method thereof are composed of an input source, an original edge LLC resonance circuit, a transformer, a secondary active Boost rectification circuit and an output load. Based on the traditional LLC resonance converter, the secondary active Boost rectification circuit is substituted for the active Boost rectification circuit so as to realize the fixed frequency phase-shifting control of a converter, the frequency conversion control of the converter and the frequency conversion and fixed frequency phase-shifting combined control to facilitate the design of magnetic elements, reduce the voltage stress of the original edge switch tube and the secondary rectifier tube so as to realize the soft switch of each power semiconductor device, improve the voltage gain range, the efficiency and the power density of the converter and satisfy the requirement of a wide voltage gain margin conversion occasion.
Description
Technical field
The present invention relates to a kind of controlled resonant converter and control method thereof, belong to converters technical field, especially belong to every
Release DC-to-dc transformation of electrical energy technical field.
Background technology
Isolated DC Width funtion gain ranging changer is applicable to requirement input and output electrical isolation and input voltage or output voltage
The occasion of wider range, this quasi-converter has widely in every field such as generation of electricity by new energy, industry, civilian, Aero-Space
Application.The voltage gain scope, efficiency and the power density that how to improve this quasi-converter are always the weight that this technical field is paid close attention to
Point problem.
LLC resonant converter is to obtain the Width funtion gain ranging isolated converter of extensive concern in recent years, as shown in Figure 1.It
Voltage gain is more than 1 when, it is possible to realize the Sofe Switch of all switching tubes, be particularly suitable for high frequency, high power density occasion
Application.But, traditional LLC resonant converter needs to realize the regulation of output voltage by changing switching frequency, works as load
Or during input voltage fluctuation, switching frequency needs to change in wide range, and this gives the design and analysis of changer, control and reality
The most all bring extreme difficulties.Therefore, when voltage gain wider range, traditional LLC controlled resonant converter efficiency is decreased obviously.
In Width funtion gain ranging occasion, LLC changer and three level or multilevel converter are often combined by scholars, this
Quasi-converter generally uses fixed-frequency control, but needs a lot of power semiconductor, adds cost and complexity, and reducing can
By property.Document " Haibing Hu, Xiang Fang, Frank Chen, Z.John Shen, Issa Batarseh.A Modified
High-Efficiency LLC Converter With Two Transformers for Wide Input-Voltage Range
Applications [J] .IEEE Transactions on Power Electronics, 2013,28 (4): 1946-1960. " propose a kind of pair
Transformer device structure, this changer can substantially increase voltage gain scope, but need also exist for a lot of power semiconductor.
Summary of the invention
It is an object of the invention to, for the deficiencies in the prior art, provide a kind of controlled resonant converter for Width funtion gain ranging conversion occasion
And control method.
It is an object of the invention to be achieved through the following technical solutions:
Described a kind of controlled resonant converter is by input source (Uin), former limit LLC resonance circuit (10), transformator (T), auxiliary edge active Boost
Rectification circuit (20) and output loading (Ro) constitute, its limit, Central Plains LLC resonance circuit (10) is by former limit the first switching tube (S1), former limit
Second switch pipe (S2), former limit the 3rd switching tube (S3), former limit the 4th switching tube (S4), resonant capacitance (Cr), resonant inductance (Lr) and swash
Magnetoelectricity sense (Lm) composition, auxiliary edge active Boost rectification circuit (20) is by secondary the 5th switching tube (S5), secondary the 6th switching tube (S6)、
Secondary the first commutation diode (D1), secondary the second commutation diode (D2), secondary the first output filter capacitor (Co1) and secondary second
Output filter capacitor (Co2) composition；Former limit the first switching tube (S of described primary circuit (10)1) drain electrode be connected in former limit the 3rd switching tube
(S3) drain electrode and input source (Uin) anode, former limit the first switching tube (S1) source electrode be connected in former limit second switch pipe (S2) drain electrode and
Resonant capacitance (Cr) one end, resonant capacitance (Cr) the other end be connected in resonant inductance (Lr) one end, resonant inductance (Lr) the other end
It is connected in magnetizing inductance (Lm) one end and transformator (T) primary side winding (NP) Same Name of Ends, transformator (T) primary side winding (NP) non-of the same name
End is connected in magnetizing inductance (Lm) the other end, former limit the 3rd switching tube (S3) source electrode and former limit the 4th switching tube (S4) drain electrode, former
Limit the 4th switching tube (S4) source electrode be connected in former limit second switch pipe (S2) source electrode and input source (Uin) negative terminal；Described transformator (T)
Vice-side winding (NS) Same Name of Ends be connected in secondary the 5th switching tube (S of auxiliary edge active Boost rectification circuit (20)5) drain electrode, secondary
First commutation diode (D1) anode and secondary the second commutation diode (D2) negative electrode, secondary the first commutation diode (D1) the moon
Pole is connected in secondary the first output filter capacitor (Co1) one end and output loading (Ro) one end, output loading (Ro) the other end be connected in
Secondary the second output filter capacitor (Co2) one end and secondary the second commutation diode (D2) anode, secondary second exports filtered electrical
Hold (Co2) the other end be connected in secondary the first output filter capacitor (Co1) the other end, transformator (T) vice-side winding (NS) non-of the same name
End and secondary the 6th switching tube (S6) drain electrode, secondary the 6th switching tube (S6) source electrode be connected in secondary the 5th switching tube (S5) source electrode.
Described a kind of controlled resonant converter can be taked to determine frequency displacement phase control method as follows: described first to the 6th switching tube (S1～S6)
Switching frequency is equal and fixing, the first switching tube (S1) and second switch pipe (S2) complementary conducting, the 3rd switching tube (S3) switch with the 4th
Pipe (S4) complementary conducting, the 5th switching tube (S5) and the 6th switching tube (S6) complementary conducting, the first switching tube (S1), second switch pipe (S2)、
3rd switching tube (S3), the 4th switching tube (S4), the 5th switching tube (S5) and the 6th switching tube (S6) dutycycle equal, first switch
Pipe (S1) and the 4th switching tube (S4) simultaneously turn on, simultaneously turn off, second switch pipe (S2) and the 3rd switching tube (S3) simultaneously turn on, together
Time turn off, the first switching tube (S1) moment of opening be not later than the 6th switching tube (S6) open the moment, the 3rd switching tube (S3) open-minded
Moment is not later than the 5th switching tube (S5) open the moment, by regulating the first switching tube (S1) and the 6th switching tube (S6) turn-on instant it
Between phase shifting angle realize the control of output voltage, phase shifting angle is the biggest, and output voltage gain is the biggest.
Described a kind of controlled resonant converter can take the following method for controlling frequency conversion similar with traditional LLC: described first to fourth opens
Close pipe (S1～S4) switching frequency equal, the 5th to the 6th switching tube (S5～S6) the whole cycle complete switches off, the first switching tube (S1) with
Second switch pipe (S2) complementary conducting, the 3rd switching tube (S3) and the 4th switching tube (S4) complementary conducting, the first switching tube (S1), second
Switching tube (S2), the 3rd switching tube (S3), the 4th switching tube (S4) dutycycle is equal, the first switching tube (S1) and the 4th switching tube (S4)
Simultaneously turn on, simultaneously turn off, second switch pipe (S2) and the 3rd switching tube (S3) simultaneously turn on, simultaneously turn off, by regulation first
To the 4th switching tube (S1～S4) switching frequency realize the control of output voltage, switching frequency more low output voltage gain is the biggest,
When low switching frequency is defeated, output voltage gain is the highest.
Described a kind of controlled resonant converter can be taked in the specific implementation such as down coversion and determine frequency displacement and be combined control method: as described in humorous
Shake changer switching frequency higher than lowermost switch frequency time, the 5th switching tube (S5) and the 6th switching tube (S6) be held off, conversion
Device uses the method for controlling frequency conversion described in claim 2；And described controlled resonant converter is when switching frequency is equal to lowermost switch frequency,
5th switching tube (S5) and the 6th switching tube (S6) start working, changer uses determines frequency displacement phase control method described in claim 3.
Technical solution of the present invention essential difference is in that with existing technical scheme, and control program both can use determines frequency displacement phase control side
Method, it would however also be possible to employ method for controlling frequency conversion, it is also possible to use frequency conversion and determine frequency displacement and be combined control method, it is possible to achieve to output
Buck regulation, this scheme is easy to the design of magnetics, can also be reduced primary side switch pipe and the electricity of secondary rectifier tube simultaneously
Compressive stress, it is achieved the Sofe Switch of each power semiconductor, voltage gain scope, efficiency and the power density of Lifting Transform device,
Meet the demand of Width funtion gain ranging conversion occasion.
There is advantages that
(1) control mode both can use and determine frequency displacement phase control method, it would however also be possible to employ method for controlling frequency conversion, it is also possible to use frequency conversion
It is combined control method with determining frequency displacement；
(2) full operating range or part working range use and determine frequency displacement phase control, can optimize the design of changer；
(3) voltage gain wide ranges, is suitable for Width funtion gain ranging conversion occasion；
(4) voltage of all switching devices can realize voltage clamp naturally, and switching device voltage stress is low；
(5) all switching devices can realize Sofe Switch in full-load range, and conversion efficiency is high；
(6) this changer can work with HF switch, thus effectively reduces the volume weight of inductance and transformator, it is achieved high power is close
Degree；
Accompanying drawing explanation
Accompanying drawing 1 is traditional LLC resonant converter schematic diagram；
Accompanying drawing 2 is a kind of controlled resonant converter schematic diagram of the present invention；
Accompanying drawing 3 is that a kind of controlled resonant converter of the present invention uses key operation waveforms when determining frequency displacement phase control；
Accompanying drawing 4～8 is the equivalent circuit diagram that a kind of controlled resonant converter of the present invention uses when determining frequency displacement phase control in each switch mode；
Designation in the figures above: 10 is former limit LLC resonance circuit；20 is auxiliary edge active Boost rectification circuit；T is
Transformator；NPAnd NSIt is respectively primary side winding and the vice-side winding of transformator (T)；S1、S2、S3And S4Be respectively former limit first,
Second, third and the 4th switching tube；S5And S6For secondary the five, the 6th switching tube；D1And D2Whole for secondary first and second
Stream diode；LrFor resonant inductance；LmFor transformator (T) magnetizing inductance；CrFor resonant capacitance；Co1And Co2For output filtering
Electric capacity；RoFor output loading；UinFor input source；UoFor output voltage；iinOutput electric current for input source；IoFor load current；
iLrFor flowing through resonant inductance (Lr) electric current；iLmFor flowing through magnetizing inductance (Lm) electric current；uCrFor resonant capacitance (Cr) voltage at two ends；
iS1、iS2、iS3And iS4It is respectively and flows into primary side switch pipe S1、S2、S3And S4Drain current；iS5S6For flowing into secondary-side switch pipe
S5Drain current and S6Source current；isecFor flowing out transformator (T) vice-side winding NSThe electric current of Same Name of Ends；iDP1And iDP2
Respectively flow into former limit sustained diodeP1And DP2The electric current of anode；iD1And iD2It is respectively and flows into secondary commutation diode D1
And D2The electric current of anode；uGS1、uGS2、uGS3And uGS4、uGS5And uGS6It is respectively switching tube S1、S2、S3、S4、S5With
S6Driving voltage；uDS1、uDS4And uDS6It is respectively switching tube S1、S4, and S6Drain-source voltage；t0、t1、t2、t3、
t4And t5For the time；TSIt it is switch periods；D is secondary-side switch pipe S5And S6Relative to primary side switch pipe S1～S4Phase shift duty
Ratio.
Detailed description of the invention
In conjunction with accompanying drawing, technical scheme is described in detail.
As shown in Figure 2, described a kind of controlled resonant converter is by input source (Uin), former limit LLC resonance circuit (10), transformator (T),
Auxiliary edge active Boost rectification circuit (20) and output loading (Ro) constitute, its limit, Central Plains LLC resonance circuit (10) is opened by former limit first
Close pipe (S1), former limit second switch pipe (S2), former limit the 3rd switching tube (S3), former limit the 4th switching tube (S4), resonant capacitance (Cr), humorous
Shake inductance (Lr) and magnetizing inductance (Lm) composition, auxiliary edge active Boost rectification circuit (20) is by secondary the 5th switching tube (S5), secondary
Six switching tube (S6), secondary the first commutation diode (D1), secondary the second commutation diode (D2), secondary the first output filter capacitor
(Co1) and secondary the second output filter capacitor (Co2) composition；Former limit the first switching tube (S of described primary circuit (10)1) drain electrode be connected in
Former limit the 3rd switching tube (S3) drain electrode and input source (Uin) anode, former limit the first switching tube (S1) source electrode be connected in former limit second and open
Close pipe (S2) drain electrode and resonant capacitance (Cr) one end, resonant capacitance (Cr) the other end be connected in resonant inductance (Lr) one end, resonance
Inductance (Lr) the other end be connected in magnetizing inductance (Lm) one end and transformator (T) primary side winding (NP) Same Name of Ends, transformator (T) former limit
Winding (NP) non-same polarity be connected in magnetizing inductance (Lm) the other end, former limit the 3rd switching tube (S3) source electrode and former limit the 4th switch
Pipe (S4) drain electrode, former limit the 4th switching tube (S4) source electrode be connected in former limit second switch pipe (S2) source electrode and input source (Uin) negative
End；Described transformator (T) vice-side winding (NS) Same Name of Ends be connected in secondary the 5th switching tube of auxiliary edge active Boost rectification circuit (20)
(S5) drain electrode, secondary the first commutation diode (D1) anode and secondary the second commutation diode (D2) negative electrode, secondary first is whole
Stream diode (D1) negative electrode be connected in secondary the first output filter capacitor (Co1) one end and output loading (Ro) one end, output loading
(Ro) the other end be connected in secondary the second output filter capacitor (Co2) one end and secondary the second commutation diode (D2) anode, secondary
Second output filter capacitor (Co2) the other end be connected in secondary the first output filter capacitor (Co1) the other end, transformator (T) secondary around
Group (NS) non-same polarity and secondary the 6th switching tube (S6) drain electrode, secondary the 6th switching tube (S6) source electrode be connected in secondary the 5th and open
Close pipe (S5) source electrode.
A kind of controlled resonant converter of the present invention is taked to determine frequency displacement phase control method as follows in the specific implementation, and described first to the 6th
Switching tube (S1～S6) switching frequency equal and fixing, the first switching tube (S1) and second switch pipe (S2) complementary conducting, the 3rd switch
Pipe (S3) and the 4th switching tube (S4) complementary conducting, the 5th switching tube (S5) and the 6th switching tube (S6) complementary conducting, the first switching tube (S1)、
Second switch pipe (S2), the 3rd switching tube (S3), the 4th switching tube (S4), the 5th switching tube (S5) and the 6th switching tube (S6) dutycycle
Equal, the first switching tube (S1) and the 4th switching tube (S4) simultaneously turn on, simultaneously turn off, second switch pipe (S2) and the 3rd switching tube (S3)
Simultaneously turn on, simultaneously turn off, the first switching tube (S1) moment of opening be not later than the 6th switching tube (S6) open the moment, the 3rd opens
Close pipe (S3) moment of opening be not later than the 5th switching tube (S5) open the moment, by regulating the first switching tube (S1) and the 6th switching tube
(S6) phase shifting angle between turn-on instant realizes the control of output voltage, phase shifting angle is the biggest, and output voltage gain is the biggest.
A kind of controlled resonant converter of the present invention can take the following VFC side similar with traditional LLC in the specific implementation
Method, described first to fourth switching tube (S1～S4) switching frequency equal, the 5th to the 6th switching tube (S5～S6) the whole cycle is complete
Turn off, the first switching tube (S1) and second switch pipe (S2) complementary conducting, the 3rd switching tube (S3) and the 4th switching tube (S4) complementary conducting,
First switching tube (S1), second switch pipe (S2), the 3rd switching tube (S3), the 4th switching tube (S4) dutycycle is equal, the first switching tube
(S1) and the 4th switching tube (S4) simultaneously turn on, simultaneously turn off, second switch pipe (S2) and the 3rd switching tube (S3) simultaneously turn on, simultaneously
Turn off, by regulating first to fourth switching tube (S1～S4) switching frequency realize the control of output voltage, switching frequency is the lowest defeated
Going out voltage gain the biggest, when lowermost switch frequency is defeated, output voltage gain is the highest.
A kind of controlled resonant converter of the present invention can be taked in the specific implementation such as down coversion and determine frequency displacement and be combined control method,
Described controlled resonant converter switching frequency higher than lowermost switch frequency time, the 5th switching tube (S5) and the 6th switching tube (S6) be held off,
Changer uses the method for controlling frequency conversion described in claim 2；And described controlled resonant converter at switching frequency equal to lowermost switch frequency
During rate, the 5th switching tube (S5) and the 6th switching tube (S6) start working, changer use described in claim 3 to determine frequency displacement phased
Method processed.
In the specific implementation, the first switching tube (S1) and second switch pipe (S2) switching signal between when must be provided with rational dead band
Between to realize the first switching tube (S1) and second switch pipe (S2) Sofe Switch, the 3rd switching tube (S3) and the 4th switching tube (S4) switch
Rational Dead Time is must be provided with to realize the 3rd switching tube (S between signal3) and the 4th switching tube (S4) Sofe Switch；Described
In method for controlling frequency conversion, the 5th switching tube (S5) and the 6th switching tube (S6) complete switch off in the whole cycle；To determine frequency displacement phased described
In method processed, the 5th switching tube (S5) and the 6th switching tube (S6) switching signal between then need not arrange any Dead Time.
In the specific implementation, all of switching tube should select the semiconductor switch device with parasitic body diode, such as metal oxygen
Compound semiconductor field effect transistor etc..If selected switching tube is without parasitic body diode, then should its drain electrode and
Source electrode two ends anti-paralleled diode.
It is an object of the invention to realize the isolated DC conversion of Width funtion gain ranging, in order to realize this purpose, the present invention is in tradition
Its secondary side rectification circuit replaces on the basis of LLC changer active Boost rectification circuit, and control program both can use fixed
Frequency displacement phase control method, it would however also be possible to employ method for controlling frequency conversion, it is also possible to use frequency conversion and determine frequency displacement and be combined control method, can
To realize the buck regulation to output, this scheme is easy to the design of magnetics, can also be reduced primary side switch pipe and pair simultaneously
The voltage stress of limit rectifier tube, it is achieved the Sofe Switch of each device for power switching, the voltage gain scope of Lifting Transform device, efficiency and
Power density, meets the demand of Width funtion gain ranging conversion occasion.
Can visually see from the circuit structure of a kind of controlled resonant converter of the present invention shown in accompanying drawing 2, opening of the former limit of this changer
Pass device is all input directly into voltage clamp, i.e. its voltage stress and is equal to input voltage, and the switching device of changer secondary is all
Directly it is output filter capacitor voltage clamp, namely its voltage stress is no more than the half of output voltage, the institute of primary and secondary side
There is switching device the most to there is not due to voltage spikes problem, there is the advantage that switching device voltage stress is low.
Assume that all inductance, electric capacity, switching tube and diode are all ideal component, ignore the first output filter capacitor Co1With second
Output filter capacitor Co2On voltage ripple, then the first output filter capacitor Co1With the second output filter capacitor Co2On voltage
Equal to output voltage 0.5Uo。
Below as a example by a kind of controlled resonant converter shown in accompanying drawing 2, illustrate that the present invention uses operation principle when determining frequency displacement phase control.
Accompanying drawing 3 gives this controlled resonant converter and uses key operation waveforms when determining frequency displacement phase control.One controlled resonant converter of the present invention
(hereinafter referred to as changer) has five kinds of switch mode in half switch periods.
Switch mode 1 [t0, t1]: t0Before moment, former limit second switch pipe (S2), former limit the 3rd switching tube (S3) and secondary the 5th open
Close pipe (S5) conducting, resonance current is negative value, secondary the 6th switching tube (S6) body diode conducting, secondary the 5th switching tube (S5) and secondary
Limit the 6th switching tube (S6) branch road that constitutes flows through forward current, resonant capacitance (Cr) and resonant inductance (Lr) resonance, input source is formed instead
Voltage is added in resonant capacitance (Cr), resonant inductance (Lr) and magnetizing inductance (Lm) the resonator cavity input that constitutes, transformator (T) secondary around
Group (NS) both end voltage is zero, magnetizing inductance (Lm) size of current keep constant；t0In the moment, turn off former limit second switch pipe (S2) and
Former limit the 3rd switching tube (S3), resonance current is from former limit the first switching tube (S1) body diode and former limit the 4th switching tube (S4) body diode
Afterflow, former limit the first switching tube (S1) and former limit the 4th switching tube (S4) drain-source voltage is 0, equivalent circuit corresponding to this mode is such as
Shown in Fig. 4.
Switch mode 2 [t1, t2]: t1In the moment, open former limit the first switching tube (S1) and former limit the 4th switching tube (S4) zero electricity can be realized
Press off logical, secondary the 6th switching tube (S6) body diode conducting, secondary the 5th switching tube (S5) and secondary the 6th switching tube (S6) constitute
Branch road flows through forward current, secondary the first commutation diode (D1) and secondary the second commutation diode (D2) it is off state, resonance
Electric capacity (Cr) and resonant inductance (Lr) resonance, input source forms positive voltage and is added in resonant capacitance (Cr), resonant inductance (Lr) and magnetizing inductance
(Lm) the resonator cavity input that constitutes, transformator (T) vice-side winding (NS) both end voltage is zero, magnetizing inductance (Lm) size of current guarantor
Holding constant, equivalent circuit corresponding to this mode is as shown in Figure 5.
Switch mode 3 [t2, t3]: t2Moment, secondary the 5th switching tube (S5) turn off, secondary the 6th switching tube (S6) realize no-voltage and open
Logical, secondary the 5th switching tube (S5) and secondary the 6th switching tube (S6) branch current that constitutes drops to 0, secondary the first rectification two pole
Pipe (D1) conducting, resonant capacitance (Cr) and resonant inductance (Lr) resonance, magnetizing inductance (Lm) it is output refraction voltage (nP/nS*Uo) clamp,
Electric current linear rise, input source passes through resonator cavity to output loading (Ro) transmission energy, equivalent circuit such as Fig. 6 that this mode is corresponding
Shown in.
Switch mode 4 [t3, t4]: t3Moment, resonant inductance (Lr) electric current and magnetizing inductance (Lm) electric current is equal, resonant capacitance (Cr)、
Resonant inductance (Lr) and magnetizing inductance (Lm) three's common resonance, secondary the first commutation diode (D1) electric current drops to zero, it is achieved zero
Switch off current, equivalent circuit corresponding to this mode is as shown in Figure 7.
Switch mode 5 [t4, t5]: t4Moment, transformator (T) vice-side winding (NS) both end voltage drops to zero, secondary the 5th switching tube
(S5) body diode conducting, secondary the 5th switching tube (S5) and secondary the 6th switching tube (S6) branch road that constitutes flows through reverse current, resonance
Electric capacity (Cr) and resonant inductance (Lr) resonance, magnetizing inductance (Lm) size of current keeps constant, equivalent circuit such as Fig. 8 that this mode is corresponding
Shown in.
t5After moment, lower half switch periods starts, and work process is similar to, and narration is not repeated.
According to the description of above-mentioned work process, it is open-minded that each switching device of this changer all can realize no-voltage, two rectifications
Diode can realize zero-current switching, there is not diode reverse recovery problem, and therefore, all of switching device is all soft
Switch working state.Additionally, the present invention uses when determining frequency displacement phase control, it is simple to the design of magnetics, can be with Lifting Transform device
Output voltage gain scope, efficiency and power density, meet Width funtion gain ranging conversion occasion demand.
Claims (4)
1. a controlled resonant converter, it is characterised in that:
Described a kind of controlled resonant converter is by input source (Uin), former limit LLC resonance circuit (10), transformator (T), auxiliary edge active Boost
Rectification circuit (20) and output loading (Ro) constitute, its limit, Central Plains LLC resonance circuit (10) is by former limit the first switching tube (S1), former limit
Second switch pipe (S2), former limit the 3rd switching tube (S3), former limit the 4th switching tube (S4), resonant capacitance (Cr), resonant inductance (Lr) and swash
Magnetoelectricity sense (Lm) composition, auxiliary edge active Boost rectification circuit (20) is by secondary the 5th switching tube (S5), secondary the 6th switching tube (S6)、
Secondary the first commutation diode (D1), secondary the second commutation diode (D2), secondary the first output filter capacitor (Co1) and secondary second
Output filter capacitor (Co2) composition；
Former limit the first switching tube (S of described primary circuit (10)1) drain electrode be connected in former limit the 3rd switching tube (S3) drain electrode and input source
(Uin) anode, former limit the first switching tube (S1) source electrode be connected in former limit second switch pipe (S2) drain electrode and resonant capacitance (Cr) one
End, resonant capacitance (Cr) the other end be connected in resonant inductance (Lr) one end, resonant inductance (Lr) the other end be connected in magnetizing inductance (Lm)
One end and transformator (T) primary side winding (NP) Same Name of Ends, transformator (T) primary side winding (NP) non-same polarity be connected in magnetizing inductance
(Lm) the other end, former limit the 3rd switching tube (S3) source electrode and former limit the 4th switching tube (S4) drain electrode, former limit the 4th switching tube (S4)
Source electrode be connected in former limit second switch pipe (S2) source electrode and input source (Uin) negative terminal；
Described transformator (T) vice-side winding (NS) Same Name of Ends be connected in auxiliary edge active Boost rectification circuit (20) secondary the 5th switch
Pipe (S5) drain electrode, secondary the first commutation diode (D1) anode and secondary the second commutation diode (D2) negative electrode, secondary first
Commutation diode (D1) negative electrode be connected in secondary the first output filter capacitor (Co1) one end and output loading (Ro) one end, output is negative
Carry (Ro) the other end be connected in secondary the second output filter capacitor (Co2) one end and secondary the second commutation diode (D2) anode, secondary
Limit the second output filter capacitor (Co2) the other end be connected in secondary the first output filter capacitor (Co1) the other end, transformator (T) secondary
Winding (NS) non-same polarity and secondary the 6th switching tube (S6) drain electrode, secondary the 6th switching tube (S6) source electrode be connected in secondary the 5th
Switching tube (S5) source electrode.
2. based on a kind of controlled resonant converter described in claim 1 determine frequency displacement phase control method for one kind, it is characterised in that:
Described first to the 6th switching tube (S1～S6) switching frequency equal and fixing, the first switching tube (S1) and second switch pipe (S2)
Complementary conducting, the 3rd switching tube (S3) and the 4th switching tube (S4) complementary conducting, the 5th switching tube (S5) and the 6th switching tube (S6) complementary
Conducting, the first switching tube (S1), second switch pipe (S2), the 3rd switching tube (S3), the 4th switching tube (S4), the 5th switching tube (S5)
With the 6th switching tube (S6) dutycycle equal, the first switching tube (S1) and the 4th switching tube (S4) simultaneously turn on, simultaneously turn off, second
Switching tube (S2) and the 3rd switching tube (S3) simultaneously turn on, simultaneously turn off, the first switching tube (S1) moment of opening be not later than the 6th switch
Pipe (S6) open the moment, the 3rd switching tube (S3) moment of opening be not later than the 5th switching tube (S5) open the moment, by regulation the
One switching tube (S1) and the 6th switching tube (S6) phase shifting angle between turn-on instant realizes the control of output voltage, phase shifting angle is the biggest, defeated
Go out voltage gain the biggest.
3. a method for controlling frequency conversion based on a kind of controlled resonant converter described in claim 1, it is characterised in that:
Described first to fourth switching tube (S1～S4) switching frequency equal, the 5th to the 6th switching tube (S5～S6) the whole cycle is complete
Turn off, the first switching tube (S1) and second switch pipe (S2) complementary conducting, the 3rd switching tube (S3) and the 4th switching tube (S4) complementary conducting,
First switching tube (S1), second switch pipe (S2), the 3rd switching tube (S3), the 4th switching tube (S4) dutycycle is equal, the first switching tube
(S1) and the 4th switching tube (S4) simultaneously turn on, simultaneously turn off, second switch pipe (S2) and the 3rd switching tube (S3) simultaneously turn on, simultaneously
Turn off, by regulating first to fourth switching tube (S1～S4) switching frequency realize the control of output voltage, switching frequency is the lowest defeated
Going out voltage gain the biggest, when lowermost switch frequency is defeated, output voltage gain is the highest.
4. frequency conversion based on a kind of controlled resonant converter described in claim 1,2 and 3 and determine frequency displacement and be combined a control method,
It is characterized in that:
Described controlled resonant converter switching frequency higher than lowermost switch frequency time, the 5th switching tube (S5) and the 6th switching tube (S6) keep
Turning off, changer uses the method for controlling frequency conversion described in claim 2；And described controlled resonant converter at switching frequency equal to minimum
During switching frequency, the 5th switching tube (S5) and the 6th switching tube (S6) start working, changer uses determines frequency described in claim 3
Phase-shifting control method.
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| CN111064368A (en) * | 2019-12-17 | 2020-04-24 | 珠海格力电器股份有限公司 | Frequency conversion control method and device, storage medium and semi-double bridge type resonant converter |
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