CN105119856B - Single carrier frequency domain equalization method based on sub-block analysis - Google Patents
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Abstract
The invention discloses a kind of single carrier frequency domain equalization method based on sub-block analysis, mainly solves the hardware complexity height of prior art, and the problem of implementation process complexity.Implementation step is：1st, for N Fast Fourier Transform (FFT)s fft block and fft block is divided into multiple sub-blocks from receiving terminal intercepted length；2nd, N points FFT is to the channel response among the period residing for i-th of sub-block；3rd, the coefficient of balanced device is calculated, obtains the frequency domain equalization data of whole fft block；4th, the time domain equalization data of whole fft block are obtained by frequency domain equalization data；5th, the time domain equalization data of i-th of sub-block are obtained；6th, the time domain equalization data of each sub-block are spliced, obtains final equilibrium result.The present invention does frequency domain equalization in fft block, it is not necessary to and inter-block-interference is eliminated, greatly reduces hardware complexity, simplifies balanced realization process, and bit error rate performance is better than prior art, suitable for more severe channel circumstance.
Description
Technical field
The invention belongs to New Technology Of Shortwave Communication field, more particularly to a kind of single carrier frequency domain equalization method, believe for eliminating
The intersymbol interference that road introduces, improve the performance of receiver.
Background technology
Short wave communication is also known as high frequency HF radio communications, is communicated by 1.5MHz~30MHz electromagnetic wave.Due to
Short wave communication can realize non-relay telecommunication, and with equipment is simple, maneuverability, survivability is strong and network reconfiguration is fast
The advantages that prompt, it is widely used in government, diplomacy, military affairs, business, meteorological departments, especially military service.
Short wave communication is mainly carried out by ground wave transmission and sky-wave transmission two ways.Ground wave transmission passes through terrestrial relay station
Increase communication distance, transmission path is not easy to be influenceed by Changes in weather without ionosphere, but its transmission range is by ground
The limitation of face relay station quantity.Sky-wave transmission is communicated by ionospheric reflection, and electromagnetic wave can be in ionosphere and ground
Between carry out multiple reflections, be appropriate for long-distance transmissions.But ionosphere has unstable hierarchy, channel circumstance complexity
And it is unstable, the unfavorable factors such as multi-path jamming, signal fadeout and Doppler frequency shift be present, it is difficult to ensure that reliable communication.
In short wave communication, multipath effect can be produced by more transmission paths of ionospheric reflection, so that in band
Intersymbol interference ISI can be produced in the limited channel of width, this interference is also embodied by causing signal to produce Rayleigh fading in time domain,
Frequency domain produces frequency dispersal and frequency selective fading.Balancing technique is exactly to improve receiver error performance to eliminate ISI
A kind of key technology.
The realization principle of balanced device is that a kind of adjustable or nonadjustable wave filter is inserted in baseband system, whole by compensating
The amplitude-frequency and phase-frequency characteristic of individual system to meet the requirement without intersymbol interference comprising the whole system characteristic including the balanced device,
Its essence is the inverse filtering of time-varying transmission channel.Data processing form is distinguished, balanced device is grown up in time domain earliest
's.But being continuously increased with wireless system bandwidth demand, time domain equalization shown in terms of real-time processing it is very big not
Foot.The complexity of time domain equalization is exponentially increased trend with the increase of equalizer length, and this governs it in Practical Project
In application.Therefore need to consider the method such as orthogonal frequency division multiplex OFDM and single carrier frequency domain equalization of other anti-multipath jammings
SC-FDE。
OFDM is a kind of multicarrier transmission mode of anti-ISI, has good antinoise and anti-multipath jamming energy
Power, suitable for frequency selective fading channels.But OFDM technology peak-to-average force ratio is high and to phase noise and carrier frequency error
It is sensitive.SC-FDE peak-to-average force ratios are lower than OFDM, it is not necessary to the Linear Power Amplifier of high-precision Frequency Synchronization technology and high cost, Ke Yi great
It is big to reduce equipment cost.SC-FDE complexity and performance is suitable with OFDM, and is easier and traditional single carrier short-pass
Believe system compatible.SC-FDE is converted the signal into frequency domain and is carried out balanced place using convolution and the corresponding relation of frequency domain multiplication product
Reason, reduces complexity, suitable for short wave bandwidth serial modem compared with time domain equalization.
Single carrier frequency domain equalization be Fast Fourier Transform (FFT) and inverse transformation FFT/IFFT by way of frequency domain number multiplies
Realize, its complexity linearly increases with the maximum delay extension of channel, and complexity is much lower compared with time domain equalization algorithm.Transmission
Process such as Fig. 1, wherein UW are unique word.
Under slow fading environment, channel is constant when can regard as, and least mean-square error is being carried out to reception signal
During MMSE frequency domain equalizations, the channel matrix in fft block is a circular matrix.But under rapid fading environment, the time-varying of channel
It is constant that characteristic can cause the channel in a fft block to be not construed as, so that the frequency domain equalization based on FFT and IFFT
Performance deteriorate.For this problem, a rational solution is exactly to reduce the length of fft block, i.e., in receiving terminal
One fft block is divided into multiple sub-blocks, and approximately regards the channel in each sub-block as constant.
At present, the SC-FDE technologies for one fft block being divided into multiple sub-blocks in receiving terminal are by whole FFT in receiving terminal
Block is divided into several sub-blocks, carries out MMSE equilibriums, the technical scheme that such as following two documents propose respectively in each sub-block
It is exactly to carry out MMSE equilibriums respectively in each sub-block.
Prior art 1：K.Kambara,H.Nishimoto,T.Nishimura,T.Ohgane,and Y.Ogawa,
“Subblock processing in MMSE-FDE unde r fast fading environments,”IEEE
J.Sel.Areas Commun.,vol.26,no.2,pp.359–365,Feb.2008.
Prior art 2：Seok-Ki Ahn,and Kyeongcheol Yang,“A Novel Subblock-Based
Frequency-Domain Equalizer over Doubly-Selective Channels,”IEEE
Communications letters,vol.17,no.8,August.2013.
Due to the presence of intersymbol interference, previous symbol can produce interference, thus above two method to the latter symbol
When dividing sub-block, the inter-block-interference from previous sub-block can be produced in each sub-block.In order to eliminate inter-block-interference, need
MMSE equilibriums are first done to whole fft block, then the processing such as are deinterleaved, decode, encoding, interweaving, modulate, obtain transmission signal
Initialization estimation, interference of the previous sub-block to the sub-block is then subtracted from each sub-block using estimated result.Again every
MMSE equilibriums are carried out in individual sub-block respectively.These processes for eliminating inter-block-interference not only significantly increase hardware complexity, and
And implement more complicated.
The content of the invention
It is an object of the invention to the deficiency for above-mentioned prior art, it is proposed that a kind of single carrier based on sub-block analysis
Frequency-domain equilibrium method, to reduce hardware complexity, simplify balanced realization process.
To achieve the above object, technical scheme comprises the following steps：
(1) a length of N Fast Fourier Transform (FFT) fft block is intercepted in the receiving terminal of communication system
Y=[y0,…,ym,…,yN-1], the fft block includes a length of NDData block and a length of NUUnique word, wherein ymTable
Show m-th of symbol in reception signal, m=0 ..., N-1, N=ND+NU, N ＞ 0；
(2) a length of N fft block is divided into M sub-block, each a length of N of sub-blocks=N/M, wherein, the data of i-th of sub-block
ForWhereinRepresent the nth data in i-th of sub-block, n
=0 ..., Ns- 1, i=0 ..., M-1, according to the data of each sub-block, the expression for obtaining reception signal is：Y=[Y0,…,
Yi,…,YM-1]。
(3) i-th of sub-block Y is selectediChannel response h (i) among the residing period rings as the channel of whole fft block
Should, N point FFT are to h (i), obtain domain channel response D=[d0,…,dk,…,dN-1], wherein dkFor the frequency of k-th of Frequency point
Domain channel response, k=0 ..., N-1.
(4) according to the domain channel response d of k-th of Frequency pointk, calculate k-th of frequency dot factor of balanced device：
Wherein,Represent dkConjugation, | dk|2Represent to dkModulus square,Represent equivalent noise；
(5) frequency domain equalization processing is done in fft block using the coefficient of balanced device, obtains the frequency domain equalization in whole fft block
Data R=[R0,…,Rk,…,RN-1],RkRepresent the frequency domain equalization data of k-th of Frequency point；
(6) inverse fast Fourier transform IFFT is carried out to the frequency domain equalization data R of whole fft block, obtain the fft block when
Domain equalization data r=[r0,…,rk,…,rN-1], wherein rkRepresent the time domain equalization data of k-th of symbol.
(7) i-th of sub-block Y is taken outiCorresponding time domain equalization data：
WhereinRepresent the nth data in i-th of sub-block of time domain equalization data, n=0 ..., Ns-1。
(8) by M sub-block respectively according to step (3) to step (7) processing, and the equalization data of each sub-block is spelled
Connect, obtain final equilibrium result S=[S0,…,Si,…,SM-1]。
The present invention has advantages below：
1. for the present invention when dividing sub-block, sub-block number is unrestricted, suitable for more severe channel circumstance；
2. influence of the present invention due to considering equivalent noise when calculating equalizer coefficients, therefore bit error rate performance is better than
Prior art, so as to improve receiver performance；
3. the present invention in fft block due to doing MMSE frequency domain equalizations, it is not necessary to which iterative process eliminates inter-block-interference, significantly
Hardware complexity is reduced, and balanced realization process can be simplified.
Brief description of the drawings
Fig. 1 is existing single carrier frequency domain equalization SC-FDE system block diagram；
Frame structure used in Fig. 2 present invention；
Fig. 3 is single carrier frequency domain equalization method implementation process figure of the present invention based on sub-block analysis；
Fig. 4 is the partition schematic diagram in the present invention；
Fig. 5 be the present invention when dividing different sub-block numbers, simulation result figure that the bit error rate of system changes with signal to noise ratio.
Embodiment
The embodiment of the present invention is further described below in conjunction with the accompanying drawings.
The system of single carrier frequency domain equalization SC-FDE shown in Fig. 1, its operation principle are：In transmitting terminal elder generation data portion
Encoded, interweaved and modulated, according to shown in Fig. 2 frame structure insert unique word UW, wherein DATA is data division, by into
Shape filtering, then by channel, matched filtering is first passed through in receiving terminal, channel estimation is done according to reception signal, obtains letter
Road matrix, reception signal is done into Fast Fourier Transform (FFT) FFT, does equilibrium treatment, obtains frequency domain equalization data, by frequency domain equalization number
According to inverse fast Fourier transform IFFT is passed through, time domain equalization data are obtained, then by processing such as deinterleaving, decodings, sent
Signal.The present invention carries out equilibrium treatment for reception signal.
Reference picture 3, step is as follows for of the invention realizing：
Step 1, Fast Fourier Transform (FFT) fft block is intercepted.
In the receiving terminal of communication system, a length of N Fast Fourier Transform (FFT) fft block is intercepted from reception signal
Y=[y0,…,ym,…,yN-1], the fft block includes a length of NDData block and a length of NUUnique word, wherein ymTable
Show m-th of symbol in reception signal, m=0 ..., N-1, N=ND+NU, N ＞ 0；
Step 2, a length of N fft block is divided into M sub-block.
According to accompanying drawing 4, a length of N fft block is divided into M sub-block, each a length of N of sub-blocks=N/M, wherein, i-th of son
The data of block areWhereinRepresent n-th in i-th of sub-block
Individual data, n=0 ..., Ns- 1, i=0 ..., M-1, if N/M is not integer, it is rounded downwards, M-1 block lengths before making
It is equal, when processing, as long as special consideration final stage；
According to the data of each sub-block, the expression for obtaining reception signal is：Y=[Y0,…,Yi,…,YM-1]。
Step 3, N points FFT is to the channel response among the period residing for i-th of sub-block.
In rapid fading environment, channel matrix is no longer a circular matrix, if according further to the equilibrium in slow fading environment
Device coefficient carries out equilibrium, then equalization performance can be deteriorated.Therefore in the present invention, it is two by channel matrix decomposition
Point, circular matrix and acyclic matrix, the channel response among circular matrix part period residing for i-th of sub-block therein
To form, acyclic matrix part is due to the introduced distracter of the time-varying characteristics of channel；
Select i-th of sub-block YiChannel responses of the channel response h (i) as whole fft block among the residing period, it is right
H (i) is N point FFT, obtains domain channel response D=[d0,…,dk,…,dN-1], wherein dkFor the frequency domain letter of k-th of Frequency point
Road responds, k=0 ..., N-1.
Step 4, the coefficient of balanced device is calculated.
(4a) is handled the acyclic matrix part in step 3 as a part for equivalent noise, and its is equivalent to make an uproar
SoundCalculated according to the following equation：
Wherein, σ2For noise power, i.e., the variance of added white Gaussian noise, P in channelsTo send signal in each frequency
The mean power of rate point, hN-1Represent the channel response during the N-1 symbol, h0Channel during representing the 0th symbol rings
Should, fkFor the row k vector of leaf transformation matrix F in N point discrete Fouriers, F=[f0,…,fk,…,fN-1]T, []TRepresenting matrix
Transposition；
(4b) is according to the domain channel response d of k-th of Frequency pointkAnd equivalent noiseCalculate k-th of frequency of balanced device
Rate dot factor：
Wherein,Represent dkConjugation, | dk|2Represent to dkModulus square,Represent equivalent noise.
Step 5, the frequency domain equalization data of whole fft block are obtained.
Frequency domain equalization processing is done in fft block using the coefficient of balanced device, its step is as follows：
(5a) is N point quick Fouriers conversion FFT to the data Y in fft block, and obtaining its data in frequency domain is：Z=
[Z0,…,Zk,…,ZN-1], wherein ZkFor the data at k-th of Frequency point, k=0 ..., N-1；
(5b) utilizes the coefficient w of balanced devicekWith the data Z at k-th of Frequency pointk, the balanced number of k-th of Frequency point of calculating
According to：
Rk=wk*Zk
(5c) calculates the equalization data of all Frequency points according to (5b), you can the frequency domain obtained in whole fft block is equal
Weigh data R=[R0,…,Rk,…,RN-1]。
Step 6, the time domain equalization data of whole fft block are obtained.
Inverse fast Fourier transform IFFT is carried out to the frequency domain equalization data R of whole fft block, obtains the time domain of the fft block
Equalization data r=[r0,…,rk,…,rN-1], wherein rkRepresent the time domain equalization data of k-th of symbol.
Step 7, the time domain equalization data of i-th of sub-block are obtained.
Because channel is change in whole data block, channel when balanced among the period residing for i-th of sub-block rings
When should replace the channel response of whole fft block, the coefficient of balanced device is inaccurate for other sub-blocks, and corresponding equalization data is not yet
Accurately, therefore given up, only retain the equalization data of i-th of sub-block, that is, take out i-th of sub-block YiCorresponding time domain equalization number
According to：WhereinIn i-th of sub-block for representing time domain equalization data
Nth data, n=0 ..., Ns-1。
Step 8, the time domain equalization data of each sub-block are spliced, obtains final equilibrium result.
By M sub-block respectively according to step (3) to step (7) processing, and the equalization data of each sub-block is spliced,
Obtain final equilibrium result S=[S0,…,Si,…,SM-1]。
The impact of performance of the present invention can be further illustrated by following emulation：
A, simulation parameter
The relevant parameter of frequency domain equalization system is set using the parameter list shown in table 1.
The frequency domain equalization system parameter of table 1
B, emulation content
The fft block that length is 256 is divided into 2,4,8 and 16 sub-blocks, with the present invention respectively to different partitions
In the case of data carry out BER Simulation, and the situation with not dividing sub-block compares, as a result such as Fig. 5.
From fig. 5, it can be seen that the bit error rate performance of division sub-block is substantially better than the bit error rate performance for not dividing sub-block, and
With the increase of block count, the bit error rate reduces, but the increase of group block number to a certain extent when, bit error rate performance does not have substantially
Lifting.So first being emulated in practical application, suitable sub-block number is selected, then uses it for actual frequency domain equalization system
In system.
Claims (2)
1. based on the single carrier frequency domain equalization method of sub-block analysis, comprise the following steps：
(1) a length of N Fast Fourier Transform (FFT) fft block Y=[y are intercepted in the receiving terminal of communication system0,…,ym,…,yN-1], should
Fft block includes a length of NDData block and a length of NUUnique word, wherein ymM-th of symbol in expression reception signal, m=0 ...,
N-1, N=ND+NU, N ＞ 0；
(2) a length of N fft block is divided into M sub-block, each a length of N of sub-blocks=N/M, if N/M is not integer, by its to
Under round, M-1 block lengths are equal before making；Wherein, the data of i-th of sub-block areIts
InRepresent the nth data in i-th of sub-block, n=0 ..., Ns- 1, i=0 ..., M-1, according to the number of each sub-block
According to the expression for obtaining reception signal is：Y=[Y0,…,Yi,…,YM-1]；
(3) i-th of sub-block Y is selectediChannel responses of the channel response h (i) as whole fft block among the residing period, to h
(i) N point FFT are, obtain domain channel response D=[d0,…,dk,…,dN-1], wherein dkFor the frequency domain channel of k-th of Frequency point
Response, k=0 ..., N-1；
(4) according to the domain channel response d of k-th of Frequency pointk, calculate k-th of frequency dot factor of balanced device：
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Wherein,Represent dkConjugation, | dk|2Represent to dkModulus square；Equivalent noise is represented, it enters according to the following equation
Row calculates：
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Wherein, σ2For noise power, i.e., the variance of added white Gaussian noise, P in channelsTo send signal in each Frequency point
Mean power, hN-1Represent the channel response during the N-1 symbol, h0Represent the channel response during the 0th symbol, fkFor
The row k vector of leaf transformation matrix F, F=[f in N point discrete Fouriers0,…,fk,…,fN-1]T, []TThe transposition of representing matrix；
(5) frequency domain equalization processing is done in fft block using the coefficient of balanced device, obtains the frequency domain equalization data R in whole fft block
=[R0,…,Rk,…,RN-1],RkRepresent the frequency domain equalization data of k-th of Frequency point；
(6) inverse fast Fourier transform IFFT is carried out to the frequency domain equalization data R of whole fft block, the time domain for obtaining the fft block is equal
Weigh data r=[r0,…,rk,…,rN-1], wherein rkRepresent the time domain equalization data of k-th of symbol；
(7) i-th of sub-block Y is taken outiCorresponding time domain equalization data：WhereinRepresent the nth data in i-th of sub-block of time domain equalization data, n=0 ..., Ns-1；
(8) by M sub-block respectively according to step (3) to step (7) processing, and the equalization data of each sub-block is spliced,
Obtain final equilibrium result S=[S0,…,Si,…,SM-1]。
2. according to the method for claim 1, wherein the coefficient using balanced device in the step (5) is done in fft block
Frequency domain equalization processing, is carried out as follows：
(5.1) N point quick Fouriers conversion FFT is to the data Y in fft block, obtaining its data in frequency domain is：Z=
[Z0,…,Zk,…,ZN-1], wherein ZkFor the data at k-th of Frequency point, k=0 ..., N-1；
(5.2) the coefficient w of balanced device is utilizedkWith the data Z at k-th of Frequency pointk, the equalization data of k-th of Frequency point of calculating：
Rk=wk*Zk
(5.3) equalization data of all Frequency points is calculated according to (5.2), you can obtain the frequency domain equalization in whole fft block
Data R=[R0,…,Rk,…,RN-1]。
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Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101778062A (en) * | 2009-12-24 | 2010-07-14 | 北京韦加航通科技有限责任公司 | Single carrier frequency domain equalization frame structure aiming at short-wave communication channel |
| CN102752244A (en) * | 2012-07-25 | 2012-10-24 | 浙江大学 | Single carrier frequency domain equalization method without cyclic prefix |
| CN103973619A (en) * | 2014-05-07 | 2014-08-06 | 清华大学 | Signal transmission method for single-carrier modulation with time-frequency domain combination |
| CN103986676A (en) * | 2014-05-29 | 2014-08-13 | 电子科技大学 | Single carrier frequency domain equalization method for shortwave communication channel |
| JP5642613B2 (en) * | 2011-04-05 | 2014-12-17 | 日本電信電話株式会社 | Wireless communication system and wireless communication method |
-
2015
- 2015-07-14 CN CN201510412966.0A patent/CN105119856B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101778062A (en) * | 2009-12-24 | 2010-07-14 | 北京韦加航通科技有限责任公司 | Single carrier frequency domain equalization frame structure aiming at short-wave communication channel |
| JP5642613B2 (en) * | 2011-04-05 | 2014-12-17 | 日本電信電話株式会社 | Wireless communication system and wireless communication method |
| CN102752244A (en) * | 2012-07-25 | 2012-10-24 | 浙江大学 | Single carrier frequency domain equalization method without cyclic prefix |
| CN103973619A (en) * | 2014-05-07 | 2014-08-06 | 清华大学 | Signal transmission method for single-carrier modulation with time-frequency domain combination |
| CN103986676A (en) * | 2014-05-29 | 2014-08-13 | 电子科技大学 | Single carrier frequency domain equalization method for shortwave communication channel |
Non-Patent Citations (1)
| Title |
|---|
| 用于短波高速数据传输的迭代合并均衡算法;高美等;《系统工程与电子技术》;20130930;第35卷(第9期);全文 * |
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