CN105024548A - Improved split inductance zero-current-transition boost chopper circuit and modulation method thereof - Google Patents

Improved split inductance zero-current-transition boost chopper circuit and modulation method thereof Download PDF

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Publication number
CN105024548A
CN105024548A CN201510448046.4A CN201510448046A CN105024548A CN 105024548 A CN105024548 A CN 105024548A CN 201510448046 A CN201510448046 A CN 201510448046A CN 105024548 A CN105024548 A CN 105024548A
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current
resonant
inductance
main switch
zero
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廖志凌
熊颖杰
刘康
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Jiangsu University
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Jiangsu University
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    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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Abstract

The invention discloses an improved split inductance zero-current-transition boost chopper circuit and a modulation method thereof, and belongs to the field of power electronics. On the basis of an original improved split inductance zero-current-transition boost chopper circuit, the positive electrode of a boost circuit input end voltage source Vg is connected in series with a smoothing reactor L, thereby forming a branch I; a circuit branch including a main switching tube S1 and a resonant inductor Lr1 forms a branch II which is connected in parallel with the branch I; an auxiliary switching tube S2, a resonant inductor Lr2 and a resonant capacitor Cr form a branch III which is connected in parallel with a main path II; moreover, the anode of a diode D is connected with the resonant inductor Lr2; the cathode of the diode D is connected with an output voltage-stabilized capacitor C0 at an output end; and the output capacitor is connected in parallel with an output load. The situation of unstable input current at a circuit input end is analyzed and improved, so that the aims of improving the network access electric energy quality and increasing the circuit working efficiency are fulfilled.

Description

A kind of modified model division inductance zero-current switching boost chopper circuit and modulator approach thereof
Technical field
The invention belongs to parallel network power generation technology electric and electronic technical field, be specifically related to divide the improvement of inductance zero-current switching boost chopper circuit and model analysis and modulator approach.
Background technology
Igbt (IGBT) under high-frequency work is more in high-voltage great-current applications, but it belongs to minority carrier devices exists serious " conditions of streaking ", this not only can make switch under hard switching state, produce certain turn-off power loss, and then circuit efficiency is reduced, this will limit switch high frequency operation, the thermal stability of equipment reduces, the use of Sofe Switch can reduce switching loss to a certain extent, mainly eliminate device loss in switching process by introducing resonant process before and after opening at switch, therefore, the introducing of soft switch technique can solve above problem well.
The Sofe Switch mode that zero conversion pwm circuit (Zero Transition PWM Converter) compares to other types can obtain little current stress, voltage stress, obtain the favor of many researchers, specifically comprise Zero voltage transition pwm circuit ZVT-PWM (Zero-Voltage-Transition PWM Converter) and zero-current switching pwm circuit ZCT-PWM (Zero-Current-Transition PWM Converter), and the frequency on-off mode of determining that zero-current switching pwm circuit does not change main switch because of it is applied in this boost circuit, this zero current PWM unit can realize the zero current turning-on of main switch, the zero-current switching of main switch, the zero current turning-on of auxiliary switch and the zero-current switching of auxiliary switch.In this unit, select resonant inductance to be converted into division inductance, ensure that zero loss of two HF switch turns on and off, and improve the withstand voltage level on diode D.
Summary of the invention
The present invention is directed to division inductance zero-current switching boost chopper circuit Problems existing, namely DC side input inductance L causes certain influence that circuit can not be changed according to predetermined direction under different modalities to the branch road including main switch and the electric current of the branch road including auxiliary switch respectively, improvement has been done to this inductance inductance L, in addition, detailed supplementing describes modulation strategy and control method.
The technical scheme of circuit of the present invention is: a kind of modified model division inductance zero-current switching boost chopper circuit, comprises 2 IGBT main switch S with anti-paralleled diode 1, auxiliary switch S 2, 2 resonant inductance L r1, L r2, 1 resonant capacitance C r, 1 DC side input inductance L, 1 diode D, 1 output capacitance C 0outlet side load in parallel with it;
Described main switch S 1, the first resonant inductance L r1, DC side input inductance L and DC voltage source V gbe in series, and auxiliary switch S 2, the second resonant inductance L r2, resonant capacitance C rbe in series the branch road and main switch S that are formed 1, the first resonant inductance L r1the branch road formed is in parallel, the anode of diode D and the second resonant inductance L r2one end be connected, the negative electrode of diode D and the output electric capacity of voltage regulation C of output 0be connected, this output capacitance is in parallel with output loading;
Described main switch S 1with auxiliary switch S 2all be operated in high frequency state; Auxiliary switch S 2for realizing the zero-current switching of main switch, auxiliary switch S 2at main switch S 1conducting before turning off.
The technical scheme of modulator approach of the present invention is:
A modulator approach for modified model division inductance zero-current switching boost chopper circuit, comprises the following steps:
[t 0, t 1): t 0moment, main switch S 1, the first resonant inductance L r1, DC side input inductance L and DC voltage source V gform a continuous current circuit, the electric current flowing through this loop is a stable value I within this time period l, and with main switch S 1, the first resonant inductance L r1what the branch road formed was in parallel includes auxiliary switch S 2, the second resonant inductance L r2with resonant capacitance C rbranch road in, i s2=0, v cr=-U ca, v d=-V 0, this time period is similar to energy storage stage of boost under traditional hard switching operating state;
[t 1, t 2): t 1moment, auxiliary switch S 2conducting, the basis of original conducting branches has increased newly by auxiliary switch S 2, the second resonant inductance L r2with resonant capacitance C rthe branch road of composition, this period works as analysis is divided into three minor time slices, within first minor time slice, the first resonant inductance L r1on current i lr1non-linear decline, auxiliary switch S 2on current i s2non-linear increase, the voltage reversal on resonant capacitance reduces, until main switch S 1on current i s1be reduced to 0, main switch S 1realize zero-current switching, first minor time slice terminates, and enters second minor time slice, auxiliary switch S in this time period 2on current i s2continue non-linear increasing to maximum forward peak value, resonant capacitance C ron resonance potential v crnon-linear reduction always, until reduce to 0, main switch S 1on current i s1oppositely increase to maximum resonance peak value, this time period terminates, and enters the 3rd minor time slice, main switch S in this time period 1on current i s1reverse reduction, resonant capacitance C ron resonance potential v crstart to increase from 0 forward, auxiliary switch S 2on current i s2forward reduces until t 2moment i s2=I l, i s1=0 main switch S 1realize the whole circuit variation process of zero-current switching to terminate;
[t 2, t 3): t 2after moment, i s2=I l, i s1=0, resonant capacitance C ron resonance potential v crlinear rising is until t 3moment v cr=V 0, this process terminates;
[t 3, t 4): in this time period, the second resonant inductance L r2, resonant capacitance C r, DC side input voltage source V g, output loading formed equivalent circuit, the second resonant inductance L r2with resonant capacitance C rthere is resonance;
[t 4, t 5): auxiliary switch S 2on current i s2maintain 0, resonant capacitance C ron resonance potential v cralso maintain a definite value, this time period circuitry processes is exactly the boost chopper circuit of PWM under traditional hard switching;
[t 5, t 6): t 5moment, main switch S 1zero current turning-on, main switch S 1on current i s1linear rising is until t 6moment i s1=I lthis process terminates;
[t 6, t 0): t 6after moment, the second resonant inductance L r2, resonant capacitance C r, DC side input voltage source V gwith the first resonant inductance L r1there is resonance.
Further, also comprise and adopt SPWM modulation strategy, in modulation strategy, select triangular wave as carrier wave.
Further, described main switch S 1, auxiliary switch S 2under being operated in high frequency 65KHz.
Further, selection output current I is also comprised lwith load voltage V oas new control variables, adopt closed loop PI to regulate and realize.
Beneficial effect of the present invention is: on original division inductance zero-current switching boost chopper circuit basis, main switch S 1, the first resonant inductance L r1, DC side input inductance L and DC voltage source V gbe in series, and auxiliary switch S 2, resonant inductance L r2, resonant capacitance C rbe in series the branch road and main switch S that are formed 1, the first resonant inductance L r1the branch road formed is in parallel, the anode of diode D and the second resonant inductance L r2be connected, and the output electric capacity of voltage regulation C of the negative electrode of diode D and output 0be connected, this output capacitance is in parallel with output loading.And original input side inductance L=5.7e-4H, because this inductance can make main switch and the distortion of auxiliary switch current waveform, now be adjusted to L=5.7e-2H, to reach the effect of plateau current value, perfect again in conjunction with modulation strategy and control mode, circuit working efficiency is further enhanced.Steadily do not carry out analysis and modification with regard to circuit input end input current herein, and with the addition of control method, to reach the object improved the network access quality of power supply and improve circuit working efficiency.
Accompanying drawing explanation
The circuit topological structure that Fig. 1 improves;
Fig. 2 control system block diagram;
Fig. 3 divides inductance zero-current switching boost chopper circuit each stage operation mode equivalent circuit diagram, wherein:
(a) t 0~ t 1stage equivalent circuit diagram;
(b) t 1~ t 2stage equivalent circuit diagram;
(c) t 2~ t 3stage equivalent circuit diagram;
(d) t 3~ t 4stage equivalent circuit diagram;
(e) t 4~ t 5stage equivalent circuit diagram;
(f) t 5~ t 6stage equivalent circuit diagram;
(g) t 6~ t 0stage equivalent circuit diagram.
Embodiment
Below in conjunction with the accompanying drawing in the embodiment of the present invention, the technical scheme in the embodiment of the present invention is clearly and completely described.
As shown in Figure 1, circuit of the present invention comprises 2 IGBT main switch S with anti-paralleled diode 1, auxiliary switch S 2, 2 resonant inductance L r1, L r2, 1 resonant capacitance C r, 1 DC side input inductance L, 1 diode D, 1 output capacitance C 0outlet side load in parallel with it; Described main switch S 1, the first resonant inductance L r1, DC side input inductance L and DC voltage source V gbe in series, and auxiliary switch S 2, the second resonant inductance L r2, resonant capacitance C rbe in series the branch road and main switch S that are formed 1, the first resonant inductance L r1the branch road formed is in parallel, the anode of diode D and the second resonant inductance L r2one end be connected, the negative electrode of diode D and the output electric capacity of voltage regulation C of output 0be connected, this output capacitance is in parallel with output loading; Described main switch S 1with auxiliary switch S 2all be operated in high frequency state; Auxiliary switch S 2for realizing the zero-current switching of main switch, auxiliary switch S 2it is open-minded before main switch turns off.
The present invention will set about improving from the following aspects, and particular content comprises:
(1) on topological structure optimum configurations, input side inductance L=5.7e-4H originally can cause main switch and the auxiliary distortion flow through switching tube electric current and flow through auxiliary switch current waveform, and can not be stable at I flowing through good fortune main switch electric current at the 3rd operation mode l, be now adjusted to L=5.7e-2H, to reach the effect of plateau current value, as shown in Figure 1.
(2) in control method, select grid current and output voltage to be new control variables, adopt two close cycles PI to regulate and realize realizing correcting to grid current, as shown in Figure 2.
(3) in modulator approach, adopt SPWM modulation strategy, in modulation strategy, select triangular wave as carrier wave.Two main switches are operated in high frequency, main switch S 1be operated in high frequency 65KHz, and auxiliary switch S 2main to realize the zero-current switching of main switch for target, with the time conducting of delayed main switch t=0.00001088 and and main switch S 1under being equally operated in high frequency 65KHz.
As shown in Figure 3, according to improving analysis above, the positive half cycle of one-period comprises 7 operation mode processes for control principle of the present invention and method:
First job mode: t 0moment, main switch S 1, resonant inductance L r1, DC side input inductance L and DC voltage source V gform a continuous current circuit, the electric current flowing through this loop is a stable value I within this time period l, and with main switch S 1, the first resonant inductance L r1what the branch road formed was in parallel includes auxiliary switch S 2, the second resonant inductance L r2with resonant capacitance C rbranch road in, i s2=0, v cr=-U ca, v d=-V 0, this time period is similar to energy storage stage of boost under traditional hard switching operating state;
Second operation mode: t 1moment, auxiliary switch S 2conducting, the basis of original conducting branches has increased newly by auxiliary switch S 2, the second resonant inductance L r2with resonant capacitance C rthe branch road of composition, this period works as analysis is divided into three minor time slices, within first minor time slice, the first resonant inductance L r1on current i lr1non-linear decline, auxiliary switch S 2on current i s2non-linear increase, the voltage reversal on resonant capacitance reduces, until main switch S 1on current i s1be reduced to 0, main switch S 1realize zero-current switching, first minor time slice terminates, and enters second minor time slice, auxiliary switch S in this time period 2on current i s2continue non-linear increasing to maximum forward peak value, resonant capacitance C ron resonance potential v crnon-linear reduction always, until reduce to 0, main switch S 1on current i s1oppositely increase to maximum resonance peak value, this time period terminates, and enters the 3rd minor time slice, main switch S in this time period 1on current i s1reverse reduction, resonant capacitance C ron resonance potential v crstart to increase from 0 forward, auxiliary switch S 2on current i s2forward reduces until t 2moment i s2=I l, i s1=0 main switch S 1realize the whole circuit variation process of zero-current switching to terminate;
3rd operation mode: t 2after moment, i s2=I l, I s1=0, resonant capacitance C ron resonance potential v crlinear rising is until t 3moment v cr=V 0, this process terminates;
4th operation mode: in this time period, the second resonant inductance L r2, resonant capacitance C r, DC side input voltage source V g, output loading formed equivalent circuit, the second resonant inductance L r2with resonant capacitance C rthere is resonance;
5th operation mode: auxiliary switch S 2on current i s2maintain 0, resonant capacitance C ron resonance potential v cralso maintain a definite value, this time period circuitry processes is exactly the boost chopper circuit of PWM under traditional hard switching;
6th operation mode: t 5moment, main switch S 1zero current turning-on, main switch S 1on current i s1linear rising is until t 6moment i s1=I lthis process terminates;
7th operation mode: t 6after moment, the second resonant inductance L r2, resonant capacitance C r, DC side input voltage source V gwith the first resonant inductance L r1there is resonance.
This circuit described work of next work period is identical with above-mentioned steps.
Finally it should be noted that, above embodiment is only in order to illustrate technical scheme of the present invention and unrestricted, with reference to preferred embodiment to invention has been detailed description, those of ordinary skill in the art is to be understood that, can modify to technical scheme of the present invention and be equal to replacement, and not departing from the spirit and scope of technical solution of the present invention, it all should be encompassed in right of the present invention.

Claims (5)

1. a modified model division inductance zero-current switching boost chopper circuit, is characterized in that: comprise 2 IGBT main switch S with anti-paralleled diode 1, auxiliary switch S 2, 2 resonant inductance L r1, L r2, 1 resonant capacitance C r, 1 DC side input inductance L, 1 diode D, 1 output capacitance C 0outlet side load in parallel with it;
Described main switch S 1, the first resonant inductance L r1, DC side input inductance L and DC voltage source V gbe in series, and auxiliary switch S 2, the second resonant inductance L r2, resonant capacitance C rbe in series the branch road and main switch S that are formed 1, the first resonant inductance L r1the branch road formed is in parallel, the anode of diode D and the second resonant inductance L r2one end be connected, the negative electrode of diode D and the output electric capacity of voltage regulation C of output 0be connected, this output capacitance is in parallel with output loading;
Described main switch S 1with auxiliary switch S 2all be operated in high frequency state; Auxiliary switch S 2for realizing the zero-current switching of main switch, auxiliary switch S 2it is open-minded before main switch turns off.
2. the modulator approach of modified model division inductance zero-current switching boost chopper circuit according to claim 1, is characterized in that: comprise the following steps:
[t 0, t 1): t 0moment, main switch S 1, the first resonant inductance L r1, DC side input inductance L and DC voltage source V gform a continuous current circuit, the electric current flowing through this loop is a stable value I within this time period l, and with main switch S 1, the first resonant inductance L r1what the branch road formed was in parallel includes auxiliary switch S 2, the second resonant inductance L r2with resonant capacitance C rbranch road in, i s2=0, v cr=-U ca, v d=-V 0, this time period is similar to energy storage stage of boost under traditional hard switching operating state;
[t 1, t 2): t 1moment, auxiliary switch S 2conducting, the basis of original conducting branches has increased newly by auxiliary switch S 2, the second resonant inductance L r2with resonant capacitance C rthe branch road of composition, this period works as analysis is divided into three minor time slices, within first minor time slice, the first resonant inductance L r1on current i lr1non-linear decline, auxiliary switch S 2on current i s2non-linear increase, the voltage reversal on resonant capacitance reduces, until main switch S 1on current i s1be reduced to 0, main switch S 1realize zero-current switching, first minor time slice terminates, and enters second minor time slice, auxiliary switch S in this time period 2on current i s2continue non-linear increasing to maximum forward peak value, resonant capacitance C ron resonance potential v crnon-linear reduction always, until reduce to 0, main switch S 1on current i s1oppositely increase to maximum resonance peak value, this time period terminates, and enters the 3rd minor time slice, main switch S in this time period 1on current i s1reverse reduction, resonant capacitance C ron resonance potential v crstart to increase from 0 forward, auxiliary switch S 2on current i s2forward reduces until t 2moment i s2=I l, i s1=0 main switch S 1realize the whole circuit variation process of zero-current switching to terminate;
[t 2, t 3): t 2after moment, i s2=I l, i s1=0, resonant capacitance C ron resonance potential v crlinear rising is until t 3moment v cr=V 0, this process terminates;
[t 3, t 4): in this time period, the second resonant inductance L r2, resonant capacitance C r, DC side input voltage source V g, output loading formed equivalent circuit, the second resonant inductance L r2with resonant capacitance C rthere is resonance;
[t 4, t 5): auxiliary switch S 2on current i s2maintain 0, resonant capacitance C ron resonance potential v cralso maintain a definite value, this time period circuitry processes is exactly the boost chopper circuit of PWM under traditional hard switching;
[t 5, t 6): t 5moment, main switch S 1zero current turning-on, main switch S 1on current i s1linear rising is until t 6moment i s1=I lthis process terminates;
[t 6, t 0): t 6after moment, the second resonant inductance L r2, resonant capacitance C r, DC side input voltage source V gwith the first resonant inductance L r1there is resonance.
3. the modulator approach of modified model division inductance zero-current switching boost chopper circuit according to claim 2, is characterized in that: also comprise and adopt SPWM modulation strategy, select triangular wave as carrier wave in modulation strategy.
4. the modulator approach of modified model division inductance zero-current switching boost chopper circuit according to claim 2, is characterized in that: described main switch S 1, auxiliary switch S 2under being operated in high frequency 65KHz.
5. the modulator approach of modified model division inductance zero-current switching boost chopper circuit according to claim 2, is characterized in that, also comprise and select output current I lwith load voltage V 0as new control variables, adopt closed loop PI to regulate and realize.
CN201510448046.4A 2015-07-27 2015-07-27 Improved split inductance zero-current-transition boost chopper circuit and modulation method thereof Pending CN105024548A (en)

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CN105871202A (en) * 2016-06-17 2016-08-17 扬州大学 Single-tube buck-boost soft switching device
CN105896977A (en) * 2016-04-07 2016-08-24 厦门大学 Soft switch of interlaced parallel DC-DC converter
CN109417352A (en) * 2017-09-18 2019-03-01 深圳欣锐科技股份有限公司 A kind of soft switch circuit
CN111865076A (en) * 2020-06-24 2020-10-30 国网山东省电力公司淄博供电公司 Direct-current voltage reduction circuit applied to energy supply of relay protection device of transformer substation
CN116488456A (en) * 2023-06-21 2023-07-25 深圳市恒运昌真空技术有限公司 Voltage conversion circuit and voltage converter
WO2023245743A1 (en) * 2022-06-21 2023-12-28 国网江苏省电力有限公司电力科学研究院 Zero-switching-loss non-isolated direct-current boost topology circuit and control method therefor

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Cited By (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN105896977A (en) * 2016-04-07 2016-08-24 厦门大学 Soft switch of interlaced parallel DC-DC converter
CN105896977B (en) * 2016-04-07 2018-09-11 厦门大学 A kind of Sofe Switch of crisscross parallel type DC-DC converter
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CN109417352A (en) * 2017-09-18 2019-03-01 深圳欣锐科技股份有限公司 A kind of soft switch circuit
CN111865076A (en) * 2020-06-24 2020-10-30 国网山东省电力公司淄博供电公司 Direct-current voltage reduction circuit applied to energy supply of relay protection device of transformer substation
WO2023245743A1 (en) * 2022-06-21 2023-12-28 国网江苏省电力有限公司电力科学研究院 Zero-switching-loss non-isolated direct-current boost topology circuit and control method therefor
CN116488456A (en) * 2023-06-21 2023-07-25 深圳市恒运昌真空技术有限公司 Voltage conversion circuit and voltage converter
CN116488456B (en) * 2023-06-21 2024-08-02 深圳市恒运昌真空技术股份有限公司 Voltage conversion circuit and voltage converter

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Application publication date: 20151104