CN104821731A - Multi-stage series matrix converter and motor drive device - Google Patents

Abstract

The invention provides a plural-series-stage matrix converter and a motor drive device which can suppress electric power loss in a stipulated condition. The plural-series-stage matrix converter of the implemented mode has a voltage transformer, a power converting part and a control part. The power converting part is provided with a single-phase power converting unit part in each output phase. The single-phase power converting unit part is in multi-stage series connection and is connected via a second winding of the voltage converted, and is provided with single-phase power converting units of a plurality of bidirectional switches. The control part selectively executes a first control mode and a second control mode. The first control mode carries out switching control on the plurality of bidirectional switches. The second control mode continuously carries out connecting control on a part of the bidirectional switches of the plurality of bidirectional switches. When the difference between the frequency of the voltage output from the power converting part to a load and the frequency of a three-phase power supply is in a prescribed scope, the control part is to be used for control switching of the mode of the plurality of bidirectional switches from the first control mode to the second control mode.

Description

Plural serial stage matrix converter and motor drive

Technical field

The present invention relates to a kind of plural serial stage matrix converter and motor drive.

Background technology

Higher harmonic current can be suppressed due to matrix converter and effectively utilize regenerated electric power, being therefore concerned as new power inverter.

As described matrix converter, known following a kind of plural serial stage matrix converter, its each output is provided with Monophase electric power converting unit portion mutually, and described Monophase electric power converting unit portion is carried out electric power by multiple bidirectional switch to three-phase alternating current and is converted to the Monophase electric power converting unit of single-phase alternating current by multistage being connected in series and forms.

Prior art document

Patent documentation

Patent documentation 1: Japanese Unexamined Patent Publication 2006-174559 publication

Summary of the invention

The technical problem to be solved in the present invention

In plural serial stage matrix converter in the past, produce power consumption because of the switching loss of bidirectional switch.

The present invention completes in view of the above problems, its objective is and provides a kind of plural serial stage matrix converter and the motor drive that can suppress power consumption under prescribed conditions.

For the method for technical solution problem

In a technical scheme of the present invention, plural serial stage matrix converter has transformer, power conversion unit and switch driving part.Described transformer has a winding and multiple secondary winding, and the three-phase alternating current from the described winding of three-phase alternating-current supply supply is distributed to described multiple secondary winding.Described power conversion unit has Monophase electric power converting unit portion mutually in each output, and described Monophase electric power converting unit portion to be connected with described secondary winding by multistage being connected in series and being had the Monophase electric power converting unit of multiple bidirectional switch and form.Described switch driving part optionally performs the first control model and the second control model, wherein the first control model carries out switch control rule to described multiple bidirectional switch, and the second control model continues to carry out connection to a part of bidirectional switch in described multiple bidirectional switch and controls.In addition, when from described power conversion unit to when the difference of the frequency of the frequency of the output voltage of load and described three-phase alternating-current supply is in prescribed limit, the pattern being used for controlling described multiple bidirectional switch is converted to the second control model from the first control model by described switch driving part.

Invention effect

Adopt a technical scheme of the present invention, a kind of plural serial stage matrix converter and the motor drive that can suppress power consumption under prescribed conditions can be provided.

Accompanying drawing explanation

Fig. 1 is the figure of the structure example of the motor drive representing the first execution mode.

Fig. 2 is the figure of an example of the concrete structure of the Monophase electric power converting unit representing the plural serial stage matrix converter shown in Fig. 1.

Fig. 3 is the figure of another structure example representing the bidirectional switch shown in Fig. 2.

Fig. 4 be to export export mutually pulse voltage schematically illustrate figure.

Fig. 5 is the figure of the state of the drive singal of each Monophase electric power converting unit represented the second control model.

Fig. 6 is the key diagram of the switching about the first control model and the second control model.

Fig. 7 is the figure of the structure example representing the control part shown in Fig. 1.

Fig. 8 is the figure of the structure example of the motor drive representing the second execution mode.

Fig. 9 is the figure representing one time of the transformer shown in Fig. 8 voltage phase difference between winding and secondary winding.

Figure 10 is the figure of the example representing the voltage vector exported respectively from the Monophase electric power converting unit of same output phase.

Figure 11 is the figure of another example representing one time of the transformer shown in Fig. 8 voltage phase difference between winding and secondary winding.

Figure 12 represents under the second control model of the second execution mode, for the figure of the state of the drive singal of each Monophase electric power converting unit.

Figure 13 is the figure of the structure example of the motor drive representing the 3rd execution mode.

Figure 14 is the figure of the example representing one time of the transformer shown in Figure 13 voltage phase difference between winding and secondary winding.

Figure 15 represents under the second control model of the 3rd execution mode, for the figure of the state of the drive singal of each Monophase electric power converting unit.

Figure 16 is the figure of the example representing the voltage vector exported respectively from the Monophase electric power converting unit of same output phase.

Figure 17 is the figure of another example representing one time of the transformer shown in Figure 13 voltage phase difference between winding and secondary winding.

Figure 18 represents under the second control model of the 3rd execution mode, for the figure of the state of the drive singal of each Monophase electric power converting unit.

Description of reference numerals

1,1A, 1B: plural serial stage matrix converter

2: three-phase alternating-current supply

3: electric rotating machine (load)

10,10A, 10B: transformer

11: windings

12,12a ~ 12i, 13,13a ~ 13i, 14,14a ~ 14r: secondary winding

20: voltage detection department

30,30B: power conversion unit

31,31a ~ 31c, 31B, 31Ba ~ 31Bc: Monophase electric power converting unit portion

32,32a ~ 32r, 32A, 32B, 32C: Monophase electric power converting unit

40,40A, 40B: control part

61, the 61A, 61B: first switch driver

62,62A, 62B: second switch driver

100,100A: motor drive

SW, Sw1 ~ Sw6: bidirectional switch

Embodiment

Below, the execution mode of plural serial stage matrix converter disclosed in the present application and motor drive is described in detail with reference to accompanying drawing.In the following embodiments, explanation conversion is supplied to load plural serial stage matrix converter and motor drive from the three-phase alternating current of AC power is exemplified.In addition, the invention is not restricted to below shown in execution mode.

[1. the first execution mode]

[structure of 1.1. matrix converter]

Fig. 1 is the figure of the structure example of the motor drive representing the first execution mode.As shown in Figure 1, the motor drive 100 of the first execution mode has plural serial stage matrix converter 1, three-phase alternating-current supply 2 (following, to be designated as AC power 2) and electric rotating machine 3.

Plural serial stage matrix converter 1 is located between AC power 2 and electric rotating machine 3, and the electric power carried out between AC power 2 and electric rotating machine 3 is changed.AC power 2 is such as electric power system (Grid), but AC power 2 is not limited to electric power system.

Electric rotating machine 3 is such as synchronous generator/motor, induction generator/motor etc., repeatedly carries out operating by exporting and stop the three-phase alternating current from plural serial stage matrix converter 1 and stops with the frequency being same as AC power 2.In addition, as load an example and describe electric rotating machine 3, but load is not limited to electric rotating machine 3.

Plural serial stage matrix converter 1 has: input terminal T _r, T _s, T _t; Lead-out terminal T _u, T _v, T _w; Transformer 10; Voltage detection department 20; Power conversion unit 30; With control part 40.

The R phase of AC power 2, S-phase and T-phase respectively with input terminal T _r, T _s, T _tconnect, the three-phase alternating current of AC power 2 is via described input terminal T _r, T _s, T _tinput to the transformer 10 of plural serial stage matrix converter 1.The U phase of electric rotating machine 3, V phase and W phase respectively with lead-out terminal T _u, T _v, T _wconnect, from the three-phase alternating current of power conversion unit 30 via described lead-out terminal T _u, T _v, T _wexport electric rotating machine 3 to.Below, sometimes U phase, V phase are designated as output phase with W phase.

Plural serial stage matrix converter 1 has the first control model and the second control model.Under the first control model, the three-phase alternating current supplied from AC power 2 is converted to the three-phase alternating current of optional frequency and voltage via power conversion unit 30 and is supplied to electric rotating machine 3 by plural serial stage matrix converter 1.In addition, under the second control model, the electric power conversion that plural serial stage matrix converter 1 does not carry out being realized by power conversion unit 30 and from power conversion unit 30 output voltage.Explain described control model later.

Transformer 10 has a winding 11 and nine secondary winding 12a ~ 12i (following, to be sometimes generically and collectively referred to as secondary winding 12).The three-phase alternating current supplied from AC power 2 to winding 11 is dispensed to nine secondary winding 12a ~ 12i via transformer 10.

At this, winding 11 and the voltage phase difference of secondary winding 12a ~ 12i is made to be that the transformation ratio (being such as, 1) of zero, secondary winding 12a ~ 12i is identical.In addition, secondary winding 12 corresponding with R phase, S-phase and T-phase is respectively set to r phase, s phase and t phase mutually, r phase, s phase is set to the voltage of t phase and inputs phase voltage Vr, Vs, Vt.

Voltage detection department 20 is located between AC power 2 and transformer 10, for detecting the instantaneous voltage value V of the R phase of AC power 2, S-phase, each phase of T-phase _r, V _s, V _t(following, be designated as input phase voltage V _r, V _s, V _t).In addition, below sometimes general name AC power 2 each phase voltage and be designated as input voltage Vi.In addition, each voltage V that mutually export of general name from power conversion unit 30 to electric rotating machine 3 sometimes _u, V _v, V _w, and be designated as output voltage V _o.

Power conversion unit 30 has the Monophase electric power converting unit portion 31a ~ 31c (following, be sometimes generically and collectively referred to as Monophase electric power converting unit portion 31) corresponding with the U phase of electric rotating machine 3, V phase and W, and exports three-phase alternating current to electric rotating machine 3.One end of Monophase electric power converting unit portion 31a ~ 31c is interconnected in neutral point N, and the other end is connected to the U phase of electric rotating machine 3, V phase and W phase.

Monophase electric power converting unit portion 31 has three Monophase electric power converting units three-phase alternating current being converted to single-phase alternating current.Specifically, Monophase electric power converting unit portion 31a has Monophase electric power converting unit 32a, 32d, 32g, Monophase electric power converting unit portion 31b has Monophase electric power converting unit 32b, 32e, 32h, and Monophase electric power converting unit portion 31c has Monophase electric power converting unit 32c, 32f, 32i.In addition, sometimes Monophase electric power converting unit 32a ~ 32i is generically and collectively referred to as Monophase electric power converting unit 32 below.

Each Monophase electric power converting unit 32 has input terminal T3 (input terminal Tr, Ts, Tt described later) and lead-out terminal T1, T2, the three-phase alternating current inputing to input terminal T3 is converted to single-phase alternating current and exports from lead-out terminal T1, T2 via secondary winding 12.

Specifically, in Monophase electric power converting unit portion 31a, be connected in series the output of Monophase electric power converting unit 32a, 32d, 32g, be added Monophase electric power converting unit 32a, 32d, 32g output voltage and export the U phase of electric rotating machine 3 to.In Monophase electric power converting unit portion 31b, be connected in series the output of Monophase electric power converting unit 32b, 32e, 32h, be added Monophase electric power converting unit 32b, 32e, 32h output voltage and export the V phase of electric rotating machine 3 to.In Monophase electric power converting unit portion 31c, be connected in series the output of Monophase electric power converting unit 32c, 32f, 32i, be added Monophase electric power converting unit 32c, 32f, 32i output voltage and export the W phase of electric rotating machine 3 to.

Fig. 2 is the figure of an example of the concrete structure representing Monophase electric power converting unit 32.As shown in Figure 2, Monophase electric power converting unit 32 has switching circuit 33 and filter 34.Described Monophase electric power converting unit 32 is also referred to as single-phase matrix convertor.In addition, Monophase electric power converting unit 32 is such as provided with not shown buffer circuit.

Switching circuit 33 has bidirectional switch Sw1 ~ Sw6 (following, to be sometimes designated as bidirectional switch Sw).Described bidirectional switch Sw1 ~ Sw6 is connected to each terminal Tr, Ts, Tt and each between terminal T1, T2.

Bidirectional switch Sw1 is configured to: the circuit that will be connected in antiparallel unidirectional switch elements 15 and diode 18, and is connected in antiparallel unidirectional switch elements 16 and carries out differential concatenation with the circuit of diode 17 and be connected.Bidirectional switch Sw2 ~ Sw6 and bidirectional switch Sw1 is same structure.

Unidirectional switch elements 15,16 is such as the thyristors such as MOSFET (Metal-Oxide-SemiconductorField-Effect Transistor: mos field effect transistor) or IGBT (Insulated GateBipolar Transistor: insulated gate bipolar transistor).In addition, unidirectional switch elements 15,16 also can be generation semiconductor switch element SiC, GaN.By turning on/off separately the unidirectional switch elements 15,16 for forming bidirectional switch Sw1 ~ Sw6, the direction that is energized can be controlled.

In addition, bidirectional switch Sw1 ~ Sw6 is not limited to the structure shown in Fig. 2.Such as, as shown in Figure 3, each bidirectional switch Sw1 ~ Sw6 also can be configured to be connected in antiparallel by unidirectional switch elements 15 and diode 17 form be connected in series body be made up of unidirectional switch elements 16 and diode 18 be connected in series body.Fig. 3 is the figure of another structure example representing bidirectional switch Sw1 ~ Sw6.

In addition, also unidirectional switch elements 15,16 can be set to respectively the switch element of reverse block-type, and bidirectional switch Sw1 ~ Sw6 is configured to mutually be connected in antiparallel these switch elements.

Filter 34 is located at switching circuit 33 and between terminal Tr, Ts, Tt, for suppressing radio-frequency component (PWM composition) impact on AC power 2 because switching circuit 33 produces.Described filter 34 is made up of three reactors L1r, L1s, L1t and three capacitors C1rs, C1st, C1rt.

One end of reactor L1r, L1s, L1t is connected to terminal Tr, Ts, Tt, and the other end is connected to switching circuit 33 side.In addition, capacitor C1rs, C1st, C1rt is connected between the other end of reactors different in reactor L1r, L1s, L1t.In addition, filter 34 is not limited to the structure shown in Fig. 2, such as, also can be configured to not be provided with reactor L1r, L1s, L1t.

[1.2. control part 40]

Control part 40 shown in Fig. 1 has the switch driver 47 (example of switch driving part) generating the drive singal for driving each Monophase electric power converting unit 32 according to control model.

Switch driver 47 is to each Monophase electric power converting unit 32 output drive signal Gr1, Gs1, Gt1, Gr2, Gs2, Gt2, G1r, G1s, G1t, G2r, G2s, G2t (following, to be sometimes generically and collectively referred to as drive singal G).Via described drive singal G, on/off control is carried out to the unidirectional switch elements 15,16 forming bidirectional switch Sw1 ~ Sw6.

As shown in Figure 2, to grid input drive signal Gr1, Gs1, Gt1, Gr2, Gs2, Gt2 of the unidirectional switch elements 15 of formation bidirectional switch Sw1 ~ Sw6.As shown in Figure 2, to grid input drive signal G1r, G1s, G1t, G2r, G2s, G2t of the unidirectional switch elements 16 of formation bidirectional switch Sw1 ~ Sw6.

Switch driver 47 has the first control model and the second control model.First control model is the control model of carrying out electric power conversion via power conversion unit 30, is performed by the first switch driver 61.Second control model is the control model of not carrying out electric power conversion via power conversion unit 30, is performed by second switch driver 62.

Plural serial stage matrix converter 1 switches the first control model and the second control model and performs.Thus, owing to not needing following switching device shifter: the device namely, to the device of the electric power and Direct driver electric rotating machine 3 that utilize AC power 2 switched to drive the device of electric rotating machine 3 with the electric power of conversion AC power 2, therefore can realize the miniaturization of hardware.Below, each control model is illustrated.

[1.2.1. first control model]

First switch driver 61 is based on input phase voltage V _r, V _s, V _tand output frequency instruction ω ^*, generate the drive singal G for driving each Monophase electric power converting unit 32.

Specifically, the first switch driver 61 is based on output frequency instruction ω ^*, generate the output phase voltage directive V corresponding respectively with U phase, V phase and W phase _u ^*, V _v ^*, V _w ^*.Export phase voltage directive V _u ^*, V _v ^*, V _w ^*there is the voltage instruction of fundamental frequency omega b respectively and there is the voltage instruction sum of treble frequency ω t (=3 × ω b).Thus, each output mutually from power conversion unit 30 to electric rotating machine 3 the voltage V of fundamental frequency omega b and treble frequency ω t can be had _u, V _v, V _w.In addition, fundamental frequency omega b is by output frequency instruction ω ^*specified frequency.

Such as, the first switch driver 61 is based on input phase voltage V _r, V _s, V _tmagnitude relationship with export phase voltage directive V _u ^*, V _v ^*, V _w ^*, the methods such as usage space vector method or triangle wave, generate the drive singal G as PWM (Pulse Width Modulation) signal for each Monophase electric power converting unit 32.Generated drive singal G is exported to corresponding Monophase electric power converting unit 32 by the first switch driver 61 respectively.

Fig. 4 be to export export mutually pulse voltage schematically illustrate figure.As shown in Figure 4, based on the drive singal G exported from the first switch driver 61, switch to export export mutually input phase voltage Vr, Vs, Vt to electric rotating machine 3 voltage pulse output.Such as, the first switch driver 61 generates the drive singal G to the U phase of electric rotating machine 3, V phase and W phase voltage pulse output and exports power conversion unit 30 to, thus carries out PWM control to power conversion unit 30.

Utilize the drive singal G exported from the first switch driver 61, export respectively corresponding to the phase voltage directive with fundamental frequency omega b and the phase voltage of phase voltage directive sum with treble frequency ω t to U phase, V phase and W phase.

When all outputing to U phase, V phase and W phase corresponding to the phase voltage directive with fundamental frequency omega b with when having the phase voltage of phase voltage directive sum of treble frequency ω t, the phase voltage corresponding to the phase voltage directive with treble frequency ω t in these two phase voltage directives is always identical value in U phase, V phase and W phase.Therefore, the phase voltage corresponding with the phase voltage directive with treble frequency ω t can not be there is offset exporting voltage between lines (voltage that the U phase voltage alternate with V, V phase are alternate with W and the W phase voltage alternate with U).That is, export phase voltage and comprise the voltage component corresponding with the phase voltage directive with fundamental frequency omega b and treble frequency ω t, and to export voltage between lines be the voltage determined by means of only the phase voltage directive with fundamental frequency omega b.

There is the phase voltage directive of fundamental frequency omega b by being added and there is the phase voltage directive of treble frequency ω t, comparing with before addition, exporting phase voltage directive V _u ^*, V _v ^*, V _w ^*peak value diminish.Therefore, with output phase voltage directive V _u ^*, V _v ^*, V _w ^*the √ 3 of peak value doubly compare, the peak value exporting voltage between lines can be increased.Export phase voltage directive V _u ^*, V _v ^*, V _w ^*peak-peak be limited to input 0.866 times of voltage between lines, but now, compared with not being added the situation of the phase voltage directive with treble frequency ω t, by being added the phase voltage directive with treble frequency ω t, output voltage between lines can be increased.

[1.2.2. second control model]

Second switch driver 62 generates drive singal G for each Monophase electric power converting unit 32, the voltage between lines that described drive singal G is used for not carrying out electric power switching motion and exports the three-phase voltage inputted from secondary winding 12.Specifically, second switch driver 62 generates and exports the drive singal G of different voltages between lines for (between U phase from V phase, between V phase and W phase and between W phase and U phase) between each phase to U phase, V phase and W phase.

Fig. 5 represents the figure for the state of the drive singal G of each Monophase electric power converting unit 32 in the second control model.In addition, the Monophase electric power converting unit 32 of position U1 ~ U3, the V1 ~ V3 shown in the U1 ~ U3 shown in Fig. 5, V1 ~ V3, W1 ~ W3 and Fig. 1, W1 ~ W3 is corresponding.At this, the situation being active high signal for drive singal G, but drive singal G also can be active low signal.

As shown in Figure 5, second switch driver 62 generates for each Monophase electric power converting unit 32 and is used for continuing to carry out connecting the drive singal G controlled to a part of bidirectional switch Sw in multiple bidirectional switch Sw, and exports each Monophase electric power converting unit 32 to.Thus, can continue to export a voltage between lines from three voltages between lines of the three-phase alternating voltage of secondary winding 12 output from each Monophase electric power converting unit 32.

Specifically, second switch driver 62 is to Monophase electric power converting unit 32a, 32d, 32g output drive signal G of U phase, and in drive singal G, drive singal Gr1, G1r, G2s, Gs2 are high level, and other are low level.Thus, connect bidirectional switch Sw1 and bidirectional switch Sw5, disconnect bidirectional switch Sw in addition.Therefore, voltage between lines between r phase with s phase can be exported from the Monophase electric power converting unit 32a of U phase, 32d, 32g.

In addition, second switch driver 62 is to Monophase electric power converting unit 32b, 32e, 32h output drive signal G of V phase, and in drive singal G, drive singal Gs1, G1s, G2t, Gt2 are high level, and other are low level.Thus, connect bidirectional switch Sw2 and bidirectional switch Sw6, disconnect bidirectional switch Sw in addition, can from the Monophase electric power converting unit 32b of V phase, voltage between lines between 32e, 32h output s phase with t phase.

In addition, second switch driver 62 is to Monophase electric power converting unit 32c, 32f, 32i output drive signal G of W phase, and in drive singal G, drive singal Gr2, G2r, G1t, Gt1 are high level, and other are low level.Thus, connect bidirectional switch Sw3 and bidirectional switch Sw4, disconnect bidirectional switch Sw in addition, can from the Monophase electric power converting unit 32c of W phase, voltage between lines between 32f, 32i output t phase with r phase.

Like this, under the second control model, second switch driver 62 controls bidirectional switch Sw1 ~ Sw6 in the mode that each output is mutually different to make the voltage between lines exported from each Monophase electric power converting unit 32.Like this, the voltage of each output phase can be exported from each Monophase electric power converting unit portion 31 owing to not carrying out the switch motion of power conversion unit 30, the power consumption because switch motion produces can be suppressed thus.

[switching of 1.2.3. control model]

Fig. 6 is the key diagram of the switching about the first control model and the second control model.In the example shown in Fig. 6, represent as output frequency instruction ω ^*after slowly rising to incoming frequency ω i from zero, output frequency instruction ω ^*switching between control model when slowly dropping to zero from incoming frequency ω i.Incoming frequency ω i is the frequency of input voltage Vi.

Control part 40 is such as according to the setpoint frequency ω inputted from epigyny device (not shown) _tG(output voltage V _othe desired value of frequency) generate output frequency instruction ω ^*.In addition, at this, to ω _tGthe situation of=ω i is described.In addition, control part 40 carries out the driving of each Monophase electric power converting unit 32 from usual operation mode.

Under usual operation mode, the first switch driver 61 exports and corresponds to output frequency instruction ω ^*drive singal G and PWM control is carried out to switching circuit 33.Thus, output voltage V _ofrequencies omega _o(following, be designated as output frequency ω _o) rise (moment t0 ~ t1).If output frequency instruction ω ^*close to incoming frequency ω i and output frequency ω _owith the difference (moment t1) in prescribed limit of incoming frequency ω i, control part 40 is judged to be output frequency ω _oconsistent with incoming frequency ω i, usual operation mode is converted to the first translative mode.

Under this first translative mode, in the same manner as usual operation mode, control part 40 carries out PWM control by the first switch driver 61 couples of bidirectional switch Sw and the electric power carried out between AC power 2 and electric rotating machine 3 is changed.In addition, incoming frequency ω i is such as commercial frequency 50Hz or 60Hz.In addition, prescribed limit is such as 1Hz or 2Hz.

When being converted to the first translative mode, control part 40 performs and makes output voltage V _ophase theta _o(following, be designated as output phase theta _o) the phase place servo antrol servo-actuated with the phase theta i of input voltage Vi (following, to be designated as input phase θ i).When making output phase theta by described phase place servo antrol _owith when the difference of input phase θ i is in prescribed limit, control part 40 is judged to export phase theta _oconsistent with input phase θ i, terminate phase place servo antrol.

When control part 40 is judged to export phase theta _oafter consistent with input phase θ i, control model is converted to the second control model from the first control model, carrys out control switch circuit 33 (moment t2) based on the drive singal G exported from second switch driver 62.

As mentioned above, start electric rotating machine 3 under the first control model after, make output frequency ω _owhen rising to the frequency equal with incoming frequency ω i and be converted to the second control model, control part 40 carries out phase place servo antrol.This is because, even if frequency is consistent, if there is phase difference between input voltage Vi and output voltage Vo, when being converted to the second control model from the first control model, also likely can producing impact to output current Io and cause overcurrent condition.

In addition, due to control part 40, carry out phase place when being judged to be that frequency is consistent servo-actuated, therefore can the amplitude of variation of rejection of acceleration, thus can suppress the variation of the output current Io of the first translative mode.

Frequencies omega is set under the state under the second control model, bidirectional switch Sw controlled _tGvalue when being changed, when control part 40 is judged to be that frequency is inconsistent, be then converted to second translative mode (moment t4) of the first control model from the second control model.Such as, as setpoint frequency ω _tGwith the difference of incoming frequency ω i when prescribed limit is outer, control part 40 is judged to be that frequency is inconsistent.

When being converted to the second translative mode, control part 40 performs to remove gradually and exports the servo-actuated stopping control of the servo-actuated phase place of phase theta o to input phase θ i.When terminating the servo-actuated stopping of phase place and controlling (moment t5), control part 40 is by changing output frequency instruction ω ^*and change output frequency ω o, to make output frequency instruction ω ^*close to setpoint frequency ω _tG.If setpoint frequency ω _tGwhen being zero and having halt instruction, as output frequency instruction ω ^*when becoming assigned frequency (moment t6), control part 40 stops usual operation mode.

Like this, when being judged to be that frequency is inconsistent, the servo-actuated stopping of plural serial stage matrix converter 1 excute phase controls and is converted to the first control model from the second control model.Therefore, can suppress to produce output current Io to impact.

In addition, the first switch driver 61 can generate the output phase voltage directive V of the composition of the frequencies omega t not comprising fundamental frequency omega b tri-times _u ^*, V _v ^*, V _w ^*, but now, each Monophase electric power converting unit 32 only can export the sine voltage without distortion of about 0.866 times that reaches input voltage.

To this, now, when making the benchmark of output phase theta o be U phase voltage to be the phase place of positive maximum after being judged to export phase theta o and being consistent with input phase θ i, control part 40 judges whether output phase theta o is arranged in π/6+n π/3 (n as 1 ~ 5 arbitrary integer)-θ _{zE_Bandnd}to π/6+n π/3+ θ _{zE_Band}scope in.

When output phase theta o is positioned at π/6+n π/3-θ _{zE_Bandnd}to π/6+n π/3+ θ _{zE_Band}scope in time, control part 40 drives the pattern of bidirectional switch Sw to be converted to the second control model from the first control model by being used for.Thereby, it is possible to output phase theta when making pattern switch _ooptimization, and reduce output current I _ovariation.In addition, when input phase θ i is positioned at π/6+n π/3-θ _{zE_Bandnd}to π/6+n π/3+ θ _{zE _ Band}scope in time, control part 40 also can make the first control model be converted to the second control model.

[concrete example of 1.3. control part 40]

Fig. 7 is the figure of the structure example representing control part 40.As shown in Figure 7, control part 40 has frequency instruction maker 41, V/f controller 42, d shaft voltage instruction generator 43, instruction amplitude arithmetic unit 44, instructing phase arithmetic unit 45, exports phase operator 46 (example of phase calculation section) and switch driver 47.

In addition, control part 40 also has incoming frequency detector 48, integrator 49, output frequency determinant 50 (example of frequency detection unit), output phase determination device 51 (example in phase determination portion), pattern switching determination device 52 (example of pattern switch judgement part) and mode decision device 53.

Described control part 40 such as comprises the microcomputer and various circuit with CPU (Central Processing Unit: central processing unit), ROM (Read Only Memory: read-only memory), RAM (Random Access Memory: random access memory), input/output port etc.The CPU of described microcomputer is by reading and performing the program that is stored in ROM and play the function in each portion 41 ~ 53.In addition, each portion 41 ~ 53 also can not service routine and being only made up of hardware.

Frequency instruction maker 41 generates and corresponds to setpoint frequency ω _tGoutput frequency instruction ω ^*and export V/f controller 42 to.Such as, because setting is changed, setpoint frequency ω is made _tGvalue change to when being greater than current value, frequency instruction maker 41 generates and makes output frequency ω _osetpoint frequency ω is arrived within specified time limit _tGoutput frequency instruction ω ^*.

Such as, if the moment t0 input shown in Fig. 6 is greater than the setpoint frequency ω of currency _tG, frequency instruction maker 41 generates output frequency instruction ω ^*, its along with the time process with constant increment rate be in line increase and at moment t1 and setpoint frequency ω _tGunanimously.

In addition, such as, at ω _tG=ω ^*state under, because of setting change, setpoint frequency ω _tGvalue change to when being less than current value, then frequency instruction maker 41 generates and makes output frequency instruction ω ^*setpoint frequency ω is arrived within specified time limit _tGoutput frequency instruction ω ^*.

V/f controller 42 exports to instruction amplitude arithmetic unit 44 and instructing phase arithmetic unit 45 and corresponds to output frequency instruction ω ^*q axle output voltage instruction Vq ^*.In addition, dq coordinate system is according to output frequency instruction ω ^*the diaxon orthogonal coordinate system rotated, the anglec of rotation of d axle is consistent with output phase theta o.

D shaft voltage instruction generator 43 exports d axle output voltage instruction Vd to instruction amplitude arithmetic unit 44 and instructing phase arithmetic unit 45 ^*.D axle output voltage instruction Vd ^*be the voltage instruction corresponding to d axle composition, such as, be set as zero.In addition, under the first control model, d shaft voltage instruction generator 43 also can export to instruction amplitude arithmetic unit 44 and instructing phase arithmetic unit 45 the d axle output voltage instruction Vd that its value corresponds to output frequency ω o ^*.

Instruction amplitude arithmetic unit 44 is according to d axle output voltage instruction Vd ^*with q axle output voltage instruction Vq ^*, computing is carried out to output voltage instruction amplitude v1.Such as, instruction amplitude arithmetic unit 44 carries out computing according to formula (1) below to output voltage instruction amplitude v1.Output voltage instruction amplitude v1 exports to switch driver 47 by instruction amplitude arithmetic unit 44.

[formula 1]

$v1=\sqrt{{\mathrm{Vd}}^{*2}+{V_q}^{*2}}...\left(1\right)$

Instructing phase arithmetic unit 45 is according to d axle output voltage instruction Vd ^*with q axle output voltage instruction Vq ^*carry out computing output voltage instructing phase θ _v.Such as, instructing phase arithmetic unit 45 carrys out computing output voltage instructing phase θ according to formula (2) below _v.Described output voltage instructing phase θ is exported to output phase operator 46 from instructing phase arithmetic unit 45 _v.In addition, as Vd=0, do not carry out the Vq of formula (2) ^*/ Vd ^*computing, if q axle output voltage instruction Vq ^*for just, make θ v=pi/2, if q axle output voltage instruction Vq ^*be negative, make θ v=3 pi/2.

[formula 2]

θv＝tan-1(Vq ^*/Vd ^*) …(2)

Export phase operator 46 and export the control phase θ corresponding to the mode select signal Sm1 ~ Sm4 exported from mode decision device 53 _pWM.Export phase operator 46 according to mode select signal Sm1 ~ Sm4 select correspond respectively to usual operation mode, the first translative mode, the second control model and the second translative mode phase place and as control phase θ _pWMexport.

Under usual operation mode, export phase operator 46 and such as correspond to output frequency instruction ω by being added ^*phase theta and output voltage instructing phase θ v and obtain control phase θ _pWM, under the second control model, using input phase θ i as control phase θ _pWMexport.

In addition, export phase operator 46 and under the first translative mode, carry out phase place servo antrol, in the mode making output phase theta o servo-actuated gradually relative to input phase θ i to obtain control phase θ _pWM.Output phase operator 46 generates and exports phase theta 1 for reducing input phase θ i and the conversion of the difference exporting phase theta o.Export phase operator 46 to increase to make the ratio of incoming frequency ω i process in time, limit changes and incoming frequency ω i and output frequency instruction ω ^*the ratio be multiplied respectively, while make incoming frequency ω i and output frequency instruction ω ^*phase Calais obtains inversion frequency instruction ω _trans, by inversion frequency instruction ω _transcarry out time integral, calculate conversion and export phase theta 1.Such as, output frequency instruction ω is made ^*be multiplied by and be reduced to the ratio of 0 in certain time from 1, make incoming frequency ω i be multiplied by the ratio increasing to 1 at one time from 0, thus make both ratio sums be always 1.In addition, such as export phase operator 46 to pass through input phase θ i and control phase θ _pWMdifference carry out PI amplification and generate phase compensation value θ aj.Then, export phase operator 46 conversion output phase theta 1 is added with phase compensation value θ aj and obtains control phase θ _pWM.

In addition, export phase operator 46 under the second translative mode, carry out the servo-actuated stopping control of phase place, obtain and export the servo-actuated control phase θ of phase theta o relative to input phase θ i for removing gradually _pWM.In order to make the ratio of incoming frequency ω i process in time reduce, exporting phase operator 46 limit and changing incoming frequency ω i and output frequency instruction ω ^*ratio, Shi Qixiang Calais, limit obtains inversion frequency instruction ω _trans, by inversion frequency instruction ω _transcarry out time integral to calculate conversion and export phase theta 1.In addition, export phase operator 46 and also carry out: when utilizing PI amplifier to generate phase compensation value θ ai, its proportionality coefficient vanishing is reset by integration and makes phase compensation value θ ai be zero.Now, in order to prevent control phase θ _pWMbecome stepped, also can in time in carrying out proportionality coefficient vanishing and integration replacement gradually skewedly.Then, export phase operator 46 conversion output phase theta 1 is added with phase compensation value θ aj and obtains control phase θ _pWM.When terminating the servo-actuated stopping of phase place and controlling, export phase operator 46 and notify the servo-actuated stopping ending message of phase place to mode decision device 53.

As mentioned above, switch driver 47 have the first switch driver 61 for performing the first control model with for performing the second switch driver 62 of the second control model.Switch driver 47 is selected control model based on the mode select signal Sm1 ~ Sm4 exported from mode decision device 53.

Specifically, when mode select signal Sm1, Sm2, Sm4 are high level, switch driver 47 selects the first control model, and when mode select signal Sm3 is high level, switch driver 47 selects the second control model.

First switch driver 61 generates and output voltage instruction amplitude v1 and control phase θ _pWM2the output phase voltage directive V of corresponding amplitude and phase place _u ^*, V _v ^*, V _w ^*.First switch driver 61 such as utilizes V _u ^*=v1 × { cos (θ _pWM)+Acos (3 θ _pWM), V _v ^*=v1 × { cos (θ _pWM-2/3 π)+Acos (3 θ _pWM-2/3 π) }, V _w ^*=v1 × { cos (θ _pWM+ 2/3 π)+Acos (3 θ _pWM+ 2/3 π) } etc. formula generate and export phase voltage directive V _u ^*, V _v ^*, V _w ^*.In addition, A is coefficient, is usually set to 1/3.

Incoming frequency detector 48 is according to the input phase voltage V detected by voltage detection department 20 _r, V _s, V _t, computing is carried out to incoming frequency ω i.Incoming frequency ω i exports to output phase operator 46, integrator 49 and output frequency determinant 50 by incoming frequency detector 48.Incoming frequency detector 48 is such as made up of PLL (Phase Locked Loop: phase-locked loop) etc.

Integrator 49, by carrying out integration to the incoming frequency ω i exported from incoming frequency detector 48, carries out computing to input phase θ i.Input phase θ i exports to output phase operator 46 by integrator 49.When being made up of incoming frequency detector 48 PLL, can input phase θ i being exported from PLL and remove integrator 49.

As output frequency instruction ω ^*with the difference of incoming frequency ω i in prescribed limit, and incoming frequency ω i and setpoint frequency ω _tGdifference in prescribed limit time, output frequency determinant 50 will represent that the frequency decision signal Sf (example of the consistent signal of frequency) of the consistent high level of frequency exports mode decision device 53 to.

In addition, in the example shown in Fig. 6, as the output frequency compared with incoming frequency ω i, utilize the output frequency instruction ω corresponding to output frequency ω o ^*, but the output frequency test section of direct-detection output frequency ω o also can be set in control part 40.Now, when the difference of output frequency ω o and incoming frequency ω i is in prescribed limit, output frequency determinant 50 exports the consistent frequency decision signal Sf of expression frequency to replace output frequency instruction ω ^*.

Under the first translative mode, if input phase θ i and control phase θ _pWMdifference at phase threshold Δ θ _{zE_cmp}time following, export phase determination device 51 and export with mode decision device 53 the phase determination signal Sp representing the high level that phase place is consistent to pattern switching determination device 52.

When exporting from exporting phase determination device 51 the phase determination signal Sp representing that phase place is consistent, and control phase θ _pWMat π/6+n π/3-θ _{zE_Band}to π/6+n π/3+ θ _{zE_Band}scope in time, pattern is switched and determined device 52 and exports the mode switching signal Ssw of high level representing and switch instruction to mode decision device 53.

Mode decision device 53 judges control model according to frequency decision signal Sf and phase determination signal Sp.Mode decision device 53 exports the mode select signal Sm1 ~ Sm4 corresponding to judged control model.

Under usual operation mode, mode decision device 53 makes mode select signal Sm1 be high level, makes other mode select signals Sm2 ~ Sm4 be low level.Under usual operation mode, when frequency decision signal Sf becomes high level from low level, switching is used for making control model be converted to the status signal Sm1 ~ Sm4 of the first translative mode by mode decision device 53.

Conversion to the first translative mode is by making mode select signal Sm1 become low level from high level, makes mode select signal Sm2 become high level to carry out from low level.Thus, when the difference of output frequency ω o and incoming frequency ω i is in prescribed limit, control model switches to the first translative mode from usual operation mode.

Under the state of the first translative mode, when phase determination signal Sp is high level, switching is used for making control model be converted to the status signal Sm1 ~ Sm4 of the second control model by mode decision device 53.Conversion to the second control model is by making mode select signal Sm2 become low level from high level, makes mode select signal Sm3 become high level to carry out from low level.

Under the second control model, when making frequency decision signal Sf become low level from high level, switching is used for making control model be converted to the status signal Sm1 ~ Sm4 of the second translative mode by mode decision device 53.Conversion to the second translative mode is by making mode select signal Sm3 become low level from high level, makes mode select signal Sm4 become high level to carry out from low level.Like this, as setpoint frequency ω _tGwith the difference of incoming frequency ω i when prescribed limit is outer, be the second translative mode from the second control mode switch.

Under the second translative mode, when notifying the servo-actuated stopping ending message of phase place by output phase operator 46, switching is used for making control model be converted to the status signal Sm1 ~ Sm4 of usual operation mode by mode decision device 53.Conversion to usual operation mode is by making mode select signal Sm4 become low level from high level, makes mode select signal Sm1 become high level to carry out from low level.Thus, at the end of the servo-actuated stopping process of phase place, usual operation mode is switched to from the second translative mode.

In addition, output phase voltage directive V is generated by the first switch driver 61 _u ^*, V _v ^*, V _w ^*, during to make the composition of the frequencies omega t wherein not comprising fundamental frequency omega b tri-times, mode decision device 53 can carry out transform mode control based on the state of mode switching signal Ssw.

Such as, under the state of the first translative mode, when phase determination signal Sp and mode switching signal Ssw becomes high level, control model is converted to the second control model by mode decision device 53.Thus, terminate phase place servo antrol, when output phase theta o or input phase θ i is at π/6+n π/3-θ _{zE_Band}to π/6+n π/3+ θ _{zE_Band}scope in time, switch to the second control model from the first translative mode.

In addition, under the second control model, when frequency decision signal Sf becomes low level from high level, and when mode switching signal Ssw becomes high level, control model can be converted to the second translative mode by mode decision device 53.

[2. the second execution mode]

Then, the plural serial stage matrix converter of the motor drive of the second execution mode is described.The secondary winding of the transformer of the plural serial stage matrix converter of the second execution mode has voltage phase difference.In addition, in the following, same Reference numeral is marked to the structural element had with the same function of plural serial stage matrix converter 1 of the first execution mode, and the repetitive description thereof will be omitted.

Fig. 8 is the figure of the structure example of the motor drive representing the second execution mode.As shown in Figure 8, the motor drive 100A of the second execution mode has plural serial stage matrix converter 1A, AC power 2 and electric rotating machine 3.

Plural serial stage matrix converter 1A has: input terminal T _r, T _s, T _t; Lead-out terminal T _u, T _v, T _w; Transformer 10A; Voltage detection department 20; Power conversion unit 30; With control part 40A.

Transformer 10A has a winding 11 and nine secondary winding 13a ~ 13i (following, to be sometimes generically and collectively referred to as secondary winding 13).The three-phase alternating current supplied from AC power 2 to winding 11 is dispensed to nine secondary winding 13a ~ 13i via transformer 10A.Described transformer 10A is the phase shifting transformer making to produce between the secondary winding 13 corresponding to same output phase voltage phase difference.

Fig. 9 is the figure of an example of the voltage phase difference represented between a winding 11 of the transformer 10A shown in Fig. 8 and secondary winding 13.As shown in Figure 9, in transformer 10A, the voltage-phase being connected to three secondary winding 13 in each Monophase electric power converting unit portion 31 is staggered 20 degree respectively.

Specifically, in U phase, for the secondary winding 13a corresponding to position U1, with the secondary winding 13d corresponding to position U2, there is the voltage phase difference of 20 degree, with the secondary winding 13g corresponding to position U3, there is the voltage phase difference of 40 degree.Similarly, in V phase, for the secondary winding 13b corresponding to position V1, with the secondary winding 13e corresponding to position V2, there is the voltage phase difference of 20 degree, with the secondary winding 13h corresponding to position V3, there is the voltage phase difference of 40 degree.

In addition, in W phase, for the secondary winding 13c corresponding to position W1, with the secondary winding 13f corresponding to position W2, there is the voltage phase difference of 20 degree, with the secondary winding 13i corresponding to position W3, there is the voltage phase difference of 40 degree.In addition, in this as an example, secondary winding 13a ~ 13c is made to be zero relative to the voltage phase difference of a winding 11.

That is, the voltage-phase of the voltage-phase of the r1 phase of secondary winding 13a ~ 13c, s1 phase and t1 phase and the R phase of AC power 2, S-phase and T-phase is identical.In addition, r2 phase, the s2 phase of secondary winding 13d ~ 13f stagger 20 degree with the voltage-phase of t2 phase relative to the R phase of AC power 2, the voltage-phase of S-phase and T-phase.In addition, r3 phase, the s3 phase of secondary winding 13g ~ 13i stagger 40 degree with the voltage-phase of t3 phase relative to the R phase of AC power 2, the voltage-phase of S-phase and T-phase.Thus, by setting voltage phase difference between secondary winding 13, the higher harmonic current that winding 11 effluent is dynamic can be reduced in.

When the voltage inputted to three the Monophase electric power converting units 32 forming Monophase electric power converting unit portion 31 has phase difference, under the second control model, the voltage exported from three Monophase electric power converting units 32 also will produce phase difference.Figure 10 is the figure of the example representing the voltage vector exported respectively from the Monophase electric power converting unit 32a of position U1, U2, U3,32d, 32g.

As shown in Figure 10, the voltage exported from the Monophase electric power converting unit portion 31 of U phase is determined by the synthesized voltage vector of Monophase electric power converting unit 32a, 32d, 32g.Therefore, compared with the total value of the size of the voltage exported respectively from Monophase electric power converting unit 32a, 32d, 32g, the size of the voltage exported from the Monophase electric power converting unit portion 31 of U phase is less.That is, if the transformation ratio of transformer 10A is identical with the transformation ratio of transformer 10, compared with plural serial stage matrix converter 1, under the second control model, the voltage that plural serial stage matrix converter 1A exports from the Monophase electric power converting unit portion 31 of U phase diminishes.In addition, in the same manner as the Monophase electric power converting unit portion 31 of U phase, the voltage exported from V phase and the Monophase electric power converting unit portion 31 of W phase also diminishes.

To this, in the transformer 10A of present embodiment, according to the voltage-phase of multiple secondary winding 13a ~ 13i, the difference with the mean value of these voltage-phases, the transformation ratio K between a winding 11 and secondary winding 13a ~ 13i is set.

Such as, make (between R phase with S-phase, between S-phase and T-phase, between T-phase and R phase) voltage between R phase, S-phase and T-phase line separately be 3300V, make each Monophase electric power converting unit portion 31 export the voltage of 3300V.Now, each Monophase electric power converting unit 32 exports the value i.e. voltage of 3300/3 √ 3V of 3300V divided by 3 × √ 3, and transformation ratio K is 1/3 √ 3.Described transformation ratio K (=1/3 √ 3) is made to be benchmark transformation ratio Ka.

In the example shown in Fig. 9, the multiple secondary winding 13 corresponding to each Monophase electric power converting unit portion 31 are made to be (0 degree of+20 degree+40 degree)/3=20 degree relative to the mean value (following, to be designated as mean value Δ θ av) of the voltage phase difference of a winding 11.In addition, the difference of the voltage-phase of mean value Δ θ av and secondary winding 13a ~ 13c is 20 degree.In addition, the difference of the voltage-phase of mean value Δ θ av and secondary winding 13d ~ 13f is 0 degree.In addition, the difference of the voltage-phase of mean value Δ θ av and secondary winding 13g ~ 13i is 20 degree.

Therefore, each secondary winding 13 is set as the 3/{1+2cos (20 °) of benchmark transformation ratio Ka relative to the transformation ratio of a winding 11 } doubly.Thus, the voltage exported from each Monophase electric power converting unit portion 31 can be suppressed to reduce because of the voltage phase difference between secondary winding 13.

Control part 40A has switch driver 47A, and described switch driver 47A has the first switch driver 61A and second switch driver 62A.Second switch driver 62 shown in second switch driver 62A and Fig. 1 carries out same action.

First switch driver 61A is based on input phase voltage V _r, V _s, V _twith output frequency instruction ω ^*, the position of the Monophase electric power converting unit 32 of corresponding each phase, generates the drive singal G for driving each Monophase electric power converting unit 32.Such as, Monophase electric power converting unit 32, the first switch driver 61A for position U1, V1, W1 generates and input phase θ i and the mutually corresponding drive singal G of corresponding output.

In addition, for the Monophase electric power converting unit 32 of position U2, V2, W2, generate the drive singal G mutually corresponding to the phase place and corresponding output that add 20 degree at input phase θ i.In addition, Monophase electric power converting unit 32, the first switch driver 61A for position U3, V3, W3 generates the drive singal G mutually corresponding to the phase place and corresponding output that add 40 degree at input phase θ i.

In addition, as mentioned above, as shown in Figure 10, under the second control model, the voltage exported from the Monophase electric power converting unit portion 31 of U phase is determined by the synthesized voltage vector of Monophase electric power converting unit 32a, 32d, 32g.Therefore, under the second control model, relative to the input phase voltage V applied to a winding 11 _r, the voltage exported from the Monophase electric power converting unit portion 31 of U phase only staggers the phase place of mean value Δ θ av.

Thus, when being converted to the first translative mode, different from the first execution mode, control part 40A performs and output phase theta o only to be staggered the servo-actuated phase place servo antrol of the phase place of mean value Δ θ av from input phase θ i.By described phase place servo antrol, when the difference of phase place exporting phase theta o and the mean value Δ θ av that only staggers from input phase θ i is in prescribed limit, control part 40A is judged to terminate to export servo-actuated to input phase θ i of phase theta o, and terminates phase place servo antrol.

Like this, the voltage phase difference between the plural serial stage matrix converter 1A of the second execution mode is provided with corresponding to the secondary winding 13 of same output phase, thus, can reduce the higher harmonic current being flowing in winding 11 side.In addition, in plural serial stage matrix converter 1A, voltage phase difference due to corresponding secondary winding 13 sets the transformation ratio K of transformer 10A, and the output phase voltage as voltage aggregate value exported from each Monophase electric power converting unit portion 31 therefore can be suppressed to reduce because of the voltage phase difference between secondary winding 13.

In addition, the voltage phase difference between secondary winding 13 is not limited to the example shown in Fig. 9.Figure 11 is the figure of another example of the voltage phase difference represented between a winding 11 of the transformer 10A shown in Fig. 8 and secondary winding 13.As shown in figure 11, using a winding 11 as benchmark, the voltage-phase being connected to three secondary winding 13 in Monophase electric power converting unit portion 31 is 0 degree, 20 degree, 160 degree.

Because t phase is staggered 120 degree relative to r, therefore in the Monophase electric power converting unit 32 be connected with the secondary winding 13 of the voltage-phase with 160 degree, because the first switch driver 61A is using T-phase as benchmark, therefore voltage phase difference is 40 degree.

Such as, the drive singal G of Monophase electric power converting unit 32 that R phase is changed to T-phase by second switch driver 62A, S-phase is changed to R phase and T-phase is changed to S-phase and generate for being connected to secondary winding 13c, 13f, 13i.

Figure 12 represents under the second control model, for the figure of the state of the drive singal G of each Monophase electric power converting unit 32.As shown in figure 12, compared with the state shown in Fig. 5, the state for the drive singal of the Monophase electric power converting unit 32g ~ 32i corresponding from position U3, V3, W3 is different, and the state for the drive singal G of other Monophase electric power converting unit 32 is identical.

Because second switch driver 62A generates drive singal G like this, each Monophase electric power converting unit portion 31 therefore can be made to stagger respectively in the secondary winding 13 corresponding respectively to three Monophase electric power converting units 32 state of 20 degree.

In addition, by the transformation ratio K with the transformer 10A of voltage phase difference shown in transformation ratio K and the Fig. 9 with the transformer 10A of voltage phase difference shown in Figure 11 is set as identical transformation ratio, the voltage exported from each Monophase electric power converting unit portion 31 therefore can be suppressed to reduce because of the voltage phase difference between secondary winding 13.

As mentioned above, in the plural serial stage matrix converter 1A of the second execution mode, the higher harmonic current being flowing in winding 11 side is reduced by the voltage phase difference between a winding 11 and secondary winding 13, and corresponded to the transformation ratio K of voltage phase difference by setting, the reduction of the output voltage of power conversion unit 30 can be suppressed.

[3. the 3rd execution mode]

Then, the plural serial stage matrix converter of the motor drive of the 3rd execution mode is described.Each Monophase electric power converting unit portion of the plural serial stage matrix converter of the 3rd execution mode have six Monophase electric power converting units.In addition, in the following, mark same Reference numeral to having with the first execution mode and the plural serial stage matrix converter 1 of the second execution mode, the structural element of the same function of 1A, and the repetitive description thereof will be omitted.

Figure 13 is the figure of the structure example of the motor drive representing the 3rd execution mode.As shown in figure 13, the plural serial stage matrix converter 1B of the 3rd execution mode has: input terminal T _r, T _s, T _t; Lead-out terminal T _u, T _v, T _w; Transformer 10B; Power conversion unit 30B; With control part 40B.

In addition, plural serial stage matrix converter 1B also has voltage detection department 20, but in fig. 13, eliminates voltage detection department 20.In addition, in the same manner as plural serial stage matrix converter 1,1A, plural serial stage matrix converter 1B is connected with AC power 2 and electric rotating machine 3, but in fig. 13, eliminates AC power 2 and electric rotating machine 3.

Transformer 10B has a winding 11 and 18 secondary winding 14a ~ 14r (following, to be sometimes generically and collectively referred to as secondary winding 14).The three-phase alternating current supplied from AC power 2 to winding 11 is dispensed to 18 secondary winding 14a ~ 14r via transformer 10B.Described transformer 10B is the phase shifting transformer making to produce between the secondary winding 14 corresponding to same output phase voltage phase difference.

Power conversion unit 30B has the Monophase electric power converting unit portion 31Ba ~ 31Bc (following, to be sometimes generically and collectively referred to as Monophase electric power converting unit portion 31B) corresponding to the U phase of electric rotating machine 3, V phase and W phase, and exports three-phase alternating current to electric rotating machine 3.One end of Monophase electric power converting unit portion 31Ba ~ 31Bc is interconnected in neutral point N, and the other end is connected to the U phase of electric rotating machine 3, V phase and W phase.

Monophase electric power converting unit portion 31B has six Monophase electric power converting units three-phase alternating current being converted to single-phase alternating current, and phase adduction exports the output of these six Monophase electric power converting units.

Specifically, Monophase electric power converting unit portion 31Ba has and is connected to secondary winding 14a, the Monophase electric power converting unit 32a of 14d, 14g, 14j, 14m, 14p, 32d, 32g, 32j, 32m, 32p (following, to be sometimes designated as Monophase electric power converting unit 32A).Be connected in series the output of these six Monophase electric power converting unit 32A, be added the output voltage of these six Monophase electric power converting unit 32A and export the U phase of electric rotating machine 3 to.

Similarly, Monophase electric power converting unit portion 31Bb has and is connected to secondary winding 14b, the Monophase electric power converting unit 32b of 14e, 14h, 14k, 14n, 14q, 32e, 32h, 32k, 32n, 32q (following, to be sometimes designated as Monophase electric power converting unit 32B).Be connected in series the output of these six Monophase electric power converting unit 32B, be added the output voltage of these six Monophase electric power converting unit 32B and export the V phase of electric rotating machine 3 to.

Monophase electric power converting unit portion 31Bc has and is connected to secondary winding 14c, the Monophase electric power converting unit 32c of 14f, 14i, 14l, 14o, 14r, 32f, 32i, 32l, 32o, 32r (following, to be sometimes designated as Monophase electric power converting unit 32C).Be connected in series the output of these six Monophase electric power converting unit 32C, be added the output voltage of these six Monophase electric power converting unit 32C and export the W phase of electric rotating machine 3 to.

In addition, in the following, sometimes Monophase electric power converting unit 32a ~ 32r is generically and collectively referred to as Monophase electric power converting unit 32.Monophase electric power converting unit 32 shown in Figure 13 is same structure with the Monophase electric power converting unit 32 shown in Fig. 1 and Fig. 2.

Control part 40B has switch driver 47B, and described switch driver 47B has the first switch driver 61B and second switch driver 62B.The first switch driver 61A shown in first switch driver 61B and Fig. 8 carries out same action.Specifically, the first switch driver 61B is based on input phase voltage V _r, V _s, V _twith output frequency instruction ω ^*, the position of the Monophase electric power converting unit 32 of corresponding each phase, generates drive singal G for each Monophase electric power converting unit 32.

Figure 14 is the figure of an example of the voltage phase difference represented between a winding 11 of the transformer 10B shown in Figure 13 and secondary winding 14.As shown in figure 14, using a winding 11 as benchmark, in U phase, there is relative to winding 11 corresponding to the secondary winding 14a of position U1 ~ U6,14d, 14g, 14j, 14m, 14p the voltage phase difference of 0 degree, 10 degree, 20 degree, 30 degree, 40 degree, 50 degree respectively.

Similarly, in V phase, there is relative to winding 11 corresponding to the secondary winding 14b of position V1 ~ V6,14e, 14h, 14k, 14n, 14q the voltage phase difference of 0 degree, 10 degree, 20 degree, 30 degree, 40 degree, 50 degree respectively.In addition, in W phase, there is relative to winding 11 corresponding to the secondary winding 14c of position W1 ~ W6,14f, 14i, 14l, 14o, 14r the voltage phase difference of 0 degree, 10 degree, 20 degree, 30 degree, 40 degree, 50 degree respectively.

First switch driver 61B generates the drive singal G corresponding to the position of the Monophase electric power converting unit 32 of each phase and input phase θ i for each Monophase electric power converting unit 32.Such as, relative to the Monophase electric power converting unit 32 of position U2, V2, W2, generate and add to input phase θ i the drive singal G that the corresponding output of the phase place of 10 degree is mutually corresponding.In addition, relative to the Monophase electric power converting unit 32 of position U4, V4, W4, generate and add to input phase θ i the drive singal G that the corresponding output of the phase place of 30 degree is mutually corresponding.

In the same manner as the second switch driver 62 shown in Fig. 1, second switch driver 62B generates for each Monophase electric power converting unit 32 and continues to carry out connecting the drive singal G controlled to a part of bidirectional switch Sw in multiple bidirectional switch Sw, and exports each Monophase electric power converting unit 32 to.

Figure 15 represents under the second control model, for the figure of the state of the drive singal G of each Monophase electric power converting unit 32.In addition, the Monophase electric power converting unit 32 of position U1 ~ U6, the V1 ~ V6 shown in the U1 ~ U6 shown in Figure 15, V1 ~ V6, W1 ~ W6 and Figure 13, W1 ~ W6 is corresponding.

As shown in figure 15, second switch driver 62B is for the Monophase electric power converting unit 32A output drive signal G of U phase, and in this drive singal G, drive singal Gr1, G1r, G2s, Gs2 are high level, and other drive singal are low level.Thus, the voltage between lines between r phase with s phase is exported from the Monophase electric power converting unit 32A of U phase.

In addition, second switch driver 62B is for the Monophase electric power converting unit 32B output drive signal G of V phase, and in this drive singal G, drive singal Gs1, G1s, G2t, Gt2 are high level, and other drive singal are low level.Thus, the voltage between lines between s phase with t phase is exported from the Monophase electric power converting unit 32B of V phase.In addition, second switch driver 62B is for the Monophase electric power converting unit 32C output drive signal G of W phase, and in this drive singal G, drive singal Gr2, G2r, G1t, Gt1 are high level, and other drive singal are low level.Thus, the voltage between lines between t phase with r phase is exported from the Monophase electric power converting unit 32C of W phase.

But under the second control model, when the voltage inputted to six the Monophase electric power converting units 32 forming Monophase electric power converting unit portion 31B exists phase difference, the voltage exported from six Monophase electric power converting units 32 is inconsistent.The synthesis of this to be the voltage owing to exporting from Monophase electric power converting unit portion 31B be voltage vector of six Monophase electric power converting units.

Figure 16 is the figure of the example representing the voltage vector exported respectively from the Monophase electric power converting unit 32a of position U1 ~ U6,32d, 32g, 32i, 32m, 32p.As shown in figure 16, the voltage exported from the Monophase electric power converting unit portion 31Ba of U phase is determined by the synthesized voltage vector of Monophase electric power converting unit 32a, 32d, 32g, 32i, 32m, 32p.

Therefore, compared with the total value of the size of the voltage exported respectively from Monophase electric power converting unit 32a, 32d, 32g, 32i, 32m, 32p, the size of the voltage exported from the Monophase electric power converting unit portion 31 of U phase is less.

To this, transformer 10B, according to the voltage-phase of multiple secondary winding 14a ~ 14r, the difference with the mean value of these voltage-phases, sets the transformation ratio K1 between a winding 11 and secondary winding 14a ~ 14r.

Such as, make R phase, S-phase and T-phase voltage between lines separately be 6600V, make each Monophase electric power converting unit portion 31 export the voltage of 6600V.Now, each Monophase electric power converting unit 32 exports the value i.e. voltage of 6600/6 √ 3V of 6600V divided by 6 × √ 3, and transformation ratio K is 1/6 √ 3.Described transformation ratio K (=1/6 √ 3) is made to be benchmark transformation ratio Kb.

In the example shown in Figure 14, make the mean value of the voltage phase difference of six secondary winding 14 corresponding to each Monophase electric power converting unit portion 31B (following, to be designated as mean value Δ θ av1) for (0 degree of+10 degree+20 degree+30 degree+40 degree+50 degree)/6=25 degree.In addition, the voltage-phase of secondary winding 14a ~ 14r and the difference of mean value Δ θ av1 are respectively 5 degree, 15 degree and 25 degree.

Therefore, each secondary winding 14 is set as 6/{2cos (5 °)+2cos (15 °)+2cos (25 °) of benchmark transformation ratio Kb relative to the transformation ratio K of a winding 11 } doubly.Thus, the voltage exported from each Monophase electric power converting unit portion 31B can be suppressed to reduce because of the voltage phase difference between secondary winding 14.

In addition, the voltage phase difference of secondary winding 14 is not limited to the example shown in Figure 14.Figure 17 is the figure of another example of the voltage phase difference represented between a winding 11 of the transformer 10B shown in Figure 13 and secondary winding 14.As shown in figure 17, using a winding 11 as benchmark, the voltage phase difference being connected to six secondary winding 14 of Monophase electric power converting unit portion 31B is 0 degree, 10 degree, 20 degree, 150 degree, 160 degree, 170 degree.

In the Monophase electric power converting unit 32 be connected with the secondary winding 14 of the voltage phase difference with 150 degree, 160 degree and 170 degree, because the first switch driver 61B is using T-phase as benchmark, therefore voltage phase difference is respectively 30 degree, 40 degree and 50 degree.Such as, second switch driver 62B to R phase is changed to T-phase, S-phase is changed to R phase and T-phase is changed to S-phase and the drive singal G generated for the Monophase electric power converting unit 32 corresponding with secondary winding 14c, 14f, 14i.

In addition, identical with the second execution mode, when being converted to the first translative mode, control part 40B performs and output phase theta o only to be staggered the servo-actuated phase place servo antrol of the phase place of mean value Δ θ av1 from input phase θ i.By described phase place servo antrol, when the difference of phase place exporting phase theta o and the mean value Δ θ av1 that only staggers from input phase θ i is in prescribed limit, control part 40B is judged to terminate to export servo-actuated to input phase θ i of phase theta o, and terminates phase place servo antrol.

Figure 18 represents under the second control model, for the figure of the state of the drive singal G of each Monophase electric power converting unit 32.As shown in figure 18, compared with the state shown in Figure 15, state for the drive singal G of the Monophase electric power converting unit 32j ~ 32r corresponding from position U4, V4, W4, U5, V5, W5, U6, V6, W6 is different, and the state for the drive singal G of other Monophase electric power converting unit 32 is identical.

Because second switch driver 62B generates drive singal G like this, each Monophase electric power converting unit portion 31B therefore can be made to stagger respectively in the secondary winding 14 corresponding respectively to three Monophase electric power converting units 32 state of 10 degree.

In addition, by the transformation ratio K with the transformer 10B of voltage phase difference shown in transformation ratio K and the Figure 14 with the transformer 10B of voltage phase difference shown in Figure 17 is set as identical transformation ratio, the voltage exported from each Monophase electric power converting unit portion 31B therefore can be suppressed to reduce because of the voltage phase difference between secondary winding 14.

[4. variation]

In the above-described embodiment, in each output phase, each secondary winding 13,14 is identical relative to the transformation ratio K of a winding 11, but transformation ratio K also can change according to the voltage phase difference of multiple secondary winding 13,14 corresponding with same output.

Such as, also can be different according to the difference of the mean value Δ θ av of voltage-phase, Δ θ av1 in each secondary winding 13,14, transformation ratio K.Such as, when the transformer 10A shown in Fig. 9, transformation ratio K corresponding to the secondary winding 13d ~ 13f of position U2, V2, W2 is set as the value identical with benchmark transformation ratio Ka, the transformation ratio K corresponding to secondary winding 13a ~ 13c, 13g ~ 13i of position U1, V1, W1, U3, V3, W3 be set as be benchmark transformation ratio Ka 1/cos (20 °) doubly.Thus, the voltage exported from each Monophase electric power converting unit portion 31 also can be suppressed to reduce because of the voltage phase difference between secondary winding 13.

In addition, when transformer 10B as shown in fig. 13 that, the mean value Δ θ av1 of voltage-phase is 25 degree.Therefore, corresponding to the transformation ratio K of secondary winding 14a ~ 14c, 14p ~ 14r of position U1, V1, W1, U6, V6, W6 be set as be benchmark transformation ratio Kb 1/cos (25 °) doubly.In addition, corresponding to the transformation ratio K of secondary winding 14d ~ 14f, 14m ~ 14o of position U2, V2, W2, U5, V5, W5 be set as be benchmark transformation ratio Kb 1/cos (15 °) doubly.In addition, corresponding to the transformation ratio K of the secondary winding 14g ~ 14l of position U3, V3, W3, U4, V4, W4 be set as be benchmark transformation ratio Kb 1/cos (5 °) doubly.Thus, the voltage exported from each Monophase electric power converting unit portion 31B also can be suppressed to reduce because of the voltage phase difference between secondary winding 14.

In addition, in transformer 10A, 10B, the corresponding secondary winding 13,14 of the Monophase electric power converting unit 32 making to be in same position relation between output mutually for same phase poor, but in the Monophase electric power converting unit 32 that also can make to correspond to same output phase, the secondary winding 13,14 of connection has mutually different voltage-phases.Such as, also the voltage-phase of the secondary winding 13 being connected to Monophase electric power converting unit 32 can be made to be respectively 0 degree, 20 degree, 40 degree relative to position U1, U2, U3, be respectively 20 degree, 40 degree, 0 degree relative to position V1, V2, V3, be respectively 20 degree, 40 degree, 0 degree relative to position W1, W2, W3.

In addition, in the transformer 10 of the first execution mode, the voltage phase difference between a winding 11 and secondary winding 12 is made to be zero, as long as but voltage phase difference between secondary winding 12 is that zero, voltage phase difference between winding 11 and secondary winding 12 also can be non-vanishing.

In addition, in transformer 10A, 10B of the second execution mode and the 3rd execution mode, make the voltage phase difference between a winding 11 and secondary winding 12a ~ 12c, 14a ~ 14c be zero, but described voltage phase difference also can be non-vanishing.

For a person skilled in the art, further effect and other variation can also be drawn.Thus, scope of the present invention is not limited to specific, the representative execution mode that describes in detail above.So in the master spirit not departing from the invention that claims and equivalent thereof define or scope, can various change be carried out.

Claims (13)

1. a plural serial stage matrix converter, is characterized in that, has:

Transformer, it has a winding and multiple secondary winding, and the three-phase alternating current from the described winding of three-phase alternating-current supply supply is distributed to described multiple secondary winding;

Power conversion unit, it has Monophase electric power converting unit portion mutually in each output, and described Monophase electric power converting unit portion to be connected with described secondary winding by multistage being connected in series and being had the Monophase electric power converting unit of multiple bidirectional switch and form; And

Switch driving part, it optionally performs the first control model and the second control model, wherein said first control model carries out switch control rule to described multiple bidirectional switch, and described second control model continues to carry out connection to a part of bidirectional switch in described multiple bidirectional switch and controls

When from described power conversion unit to when the difference of the frequency of the frequency of the output voltage of load and described three-phase alternating-current supply is in prescribed limit, the pattern being used for controlling described multiple bidirectional switch is converted to the second control model from the first control model by described switch driving part.

2. plural serial stage matrix converter according to claim 1, is characterized in that,

Under described second control model, described switch driving part controls described bidirectional switch, a voltage between lines three voltages between lines of the three-phase alternating voltage exported to make to continue to export from each described Monophase electric power converting unit, from the described secondary winding being connected to described Monophase electric power converting unit.

3. plural serial stage matrix converter according to claim 2, is characterized in that,

Under described second control model, described switch driving part controls described bidirectional switch, and to make in each described output phase, the described voltage between lines exported from each described Monophase electric power converting unit is different.

4. the plural serial stage matrix converter according to claim 1,2 or 3, is characterized in that,

Under described first control model, described switch driving part controls described bidirectional switch, with make from described power conversion unit to each described output mutually respectively output packet containing the voltage of the frequency of fundamental frequency and this fundamental frequency three times.

5. the plural serial stage matrix converter according to claim 1,2 or 3, is characterized in that,

The voltage-phase of the described multiple secondary winding connected respectively from the described multiple Monophase electric power converting units being located at same output phase of described transformer is mutually different.

6. plural serial stage matrix converter according to claim 5, is characterized in that,

When the difference of the frequency of described output voltage and the frequency of described three-phase alternating-current supply is in prescribed limit, and the difference of value and described output voltage phase place that described multiple two windings are added the voltage-phase of described three-phase alternating-current supply relative to the mean value of the voltage phase difference of a described winding in prescribed limit time, described switch driving part is converted to described second control model from described first control model.

7. plural serial stage matrix converter according to claim 5, is characterized in that,

Described transformer, according to the difference of described multiple secondary winding relative to the described voltage phase difference of a winding and the mean value of this voltage phase difference, sets the transformation ratio between a described winding and described secondary winding.

8. plural serial stage matrix converter according to claim 7, is characterized in that,

In each described output phase, the described transformation ratio being connected to the described secondary winding of described Monophase electric power converting unit is identical.

9. plural serial stage matrix converter according to claim 7, is characterized in that,

According to the difference of the mean value with described voltage phase difference, the described transformation ratio of each described secondary winding is different.

10. the plural serial stage matrix converter according to claim 1,2 or 3, is characterized in that,

Also have frequency detection unit, when the difference of the frequency of described output voltage and the frequency of described three-phase alternating-current supply is in prescribed limit, described frequency detection unit carries out the consistent judgement of frequency,

When having been carried out the consistent judgement of frequency by described frequency detection unit, described switch driving part has driven the pattern of described bidirectional switch to be converted to described second control model from described first control model by being used for.

11. plural serial stage matrix converters according to claim 10, is characterized in that also having:

Phase calculation section, when having been carried out the consistent judgement of described frequency by described frequency detection unit, described phase calculation section has carried out the servo antrol making the voltage-phase of the phase place of described output voltage and described three-phase alternating-current supply servo-actuated; And

Phase determination portion, when the difference of the phase place of described output voltage and the voltage-phase of described three-phase alternating-current supply is in prescribed limit, described phase determination portion carries out the consistent judgement of phase place,

When having carried out the consistent judgement of described frequency by described frequency detection unit, and when having carried out the consistent judgement of described phase place by described phase determination portion, the pattern being used for controlling described bidirectional switch has been converted to described second control model from described first control model by described switch driving part.

12. plural serial stage matrix converters according to claim 11, is characterized in that,

Also there is pattern switch judgement part, the consistent judgement of described frequency has been carried out by described frequency detection unit, and under the state of having carried out the consistent judgement of described phase place by described phase determination portion, when the phase place of described output voltage and the difference of π/6+n π/3 are in prescribed limit, described pattern switch judgement part is judged to be it is pattern switching instant, wherein: n is arbitrary integer in 1 ~ 5

At described pattern switching instant, the pattern being used for controlling described bidirectional switch is converted to described second control model from described first control model by described switch driving part.

13. 1 kinds of motor drives, is characterized in that having:

Plural serial stage matrix converter according to any one of claim 1 ~ 12; And

Motor, it repeatedly carries out operating with the frequency being same as described three-phase alternating-current supply by exporting and stop the three-phase alternating current from described plural serial stage matrix converter and stops,

Described plural serial stage matrix converter after starting described motor with described first control model, the frequency frequency of described output voltage being risen to be same as described three-phase alternating-current supply and be converted to described second control model.