CN104601027A - Tandem double flyback quasi resonant converter suitable for neutral point clamped direct current bus - Google Patents
Tandem double flyback quasi resonant converter suitable for neutral point clamped direct current bus Download PDFInfo
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- CN104601027A CN104601027A CN201510013564.3A CN201510013564A CN104601027A CN 104601027 A CN104601027 A CN 104601027A CN 201510013564 A CN201510013564 A CN 201510013564A CN 104601027 A CN104601027 A CN 104601027A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33538—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type
- H02M3/33546—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type with automatic control of the output voltage or current
- H02M3/33553—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type with automatic control of the output voltage or current with galvanic isolation between input and output of both the power stage and the feedback loop
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Testing Electric Properties And Detecting Electric Faults (AREA)
Abstract
The invention discloses a tandem double flyback quasi resonant converter suitable for a neutral point clamped direct current bus. The tandem double flyback quasi resonant converter suitable for the neutral point clamped direct current bus comprises a main power circuit, a logic control circuit 10, a drive circuit 20 and a detection circuit 30. The tandem double flyback quasi resonant converter suitable for the neutral point clamped direct current bus has the advantages of using characteristics of the neutral point clamped direct current bus, reducing voltage born by two ends of a switch tube to a half of that of single end flyback through a mode of connecting primary sides of two flyback circuits in series, effectively reducing stress of power devices, improving conversion efficiency and reliability of a convertor and reducing design cost of the convertor. The tandem double flyback quasi resonant converter suitable for the neutral point clamped direct current bus switches on the switch tube at the valley bottom of low voltage through a quasi resonant conversion technology, substantially reduces switch-on consumption of the switch tube, and further improves efficiency of the converter, reduces the size and the weight of the converter, and improves power density of the converter.
Description
Technical field
The present invention relates to utility power quality control field, especially a kind of two flyback quasi resonant convertor of series connection being applicable to neutral-point-clamped DC bus.
Background technology
Flourish along with national economy and science and technology, the development of the modernization large scale industry such as metallurgical, chemical and electric railway, the nonlinear-load in electric power system produces a large amount of harmonic wave and reactive power, and waveform distortion of the power supply network and load increase are on the rise.The decline of the quality of power supply seriously have impact on safety, the economical operation of electricity supply and use equipment, reduces the quality of life of the people.
Active Power Filter-APF (APF) and reactive power compensator (SVG) are the important quality of power supply devices reducing mains by harmonics and compensating power.Usually in these devices, DC bus-bar voltage, up to 900V, needs employing two alminium electrolytic condenser series connection to realize voltage stabilizing.For ensureing all pressures of two electric capacity, the general method of parallel resistance or closed-loop control that adopts carries out clamper to the mid-point voltage of DC bus.
The internal control circuit of quality of power supply device needs multiple voltage to power, and this is obtained from DC bus by converter usually.Because DC bus is up to 900V, if adopt existing topological structure, as single end flyback converter, single-ended forward converter, double-transistor flyback converter, two-transistor forward converter, full-bridge converter etc., need to use 1200V and above power device.But it is a lot of compared with the power device poor performance of below 900V more than the high tension apparatus performance of 1000V, adopt these device layout can reduce the efficiency of converter, produce more heat, need more large-area radiator, increase the volume and weight of converter, and reduce the reliability of converter.And these high tension apparatus are often expensive, significantly add the design cost of converter.
Adopt quasi-resonance technology can reduce the switching loss of power device, generally adopt special integrated chip to realize quasi-resonance conversion, but existing quasi-resonance chip all only has that below 700V's is withstand voltage, is not suitable for the high voltage dc bus of 900V.
Summary of the invention
The invention provides a kind of two flyback quasi resonant convertor of series connection being applicable to neutral-point-clamped DC bus, the switch tube voltage stress of converter can be reduced, so that can selectivity and the better low voltage power devices of price, thus improve efficiency and the reliability of converter, reduce the design cost of converter.A kind of two flyback quasi resonant convertor of series connection being applicable to neutral-point-clamped DC bus provided by the invention simultaneously, can directly adopt the integrated chip with quasi-resonance controlling functions to realize quasi-resonance conversion, thus improve the efficiency of converter further, reduce the volume and weight of converter.
Be applicable to the two flyback quasi resonant convertor of series connection of neutral-point-clamped DC bus, comprise main power circuit, logic control circuit 10, drive circuit 20 and testing circuit 30, wherein: main power circuit comprises former limit circuit, high frequency transformer T
1and secondary circuit, former limit circuit comprises DC bus, the first input capacitance C of neutral-point-clamped
i1with the second input capacitance C
i2and the first power switch pipe Q
1with the second power switch pipe Q
2, high frequency transformer T
1by former limit winding N
p1and N
p2, vice-side winding N
sand auxiliary winding N
aform, secondary circuit is by output diode D
owith output capacitance C
oform; The anode of DC bus and the first input capacitance C
i1one end electrical connection, connect high frequency transformer T simultaneously
1former limit winding N
p1one end, the first input capacitance C
i1the other end and the second input capacitance C
i2one end be connected in series, be electrically connected with the mid point end of DC bus, the second input capacitance C simultaneously
i2the other end connect the negative terminal of DC bus, high frequency transformer T
1former limit winding N
p1the other end connect the first power switch pipe Q
1one end, the first power switch pipe Q
1the other end and high frequency transformer T
1former limit winding N
p2one end electrical connection, be connected to the mid point end of DC bus, high frequency transformer T simultaneously
1former limit winding N
p2the other end and the second power switch pipe Q
2one end electrical connection, the second power switch pipe Q
2the other end connect the negative terminal of DC bus, high frequency transformer T
1vice-side winding N
sone end and output diode D
oone end electrical connection, output diode D
othe other end connect with output capacitance C
obe electrically connected with one end of load, output capacitance C
obe connected in parallel with the other end of load, simultaneously with high frequency transformer T
1vice-side winding N
sthe other end electrical connection.
Preferably, logic control circuit 10 comprises kernel control module 12, other control modules 11, pulse generating circuit 13 and the 3rd triode Q
3with the 4th triode Q
4the input of logic control circuit 10 is connected to the output of testing circuit 30, the input of logic control circuit 10 is also connected to one end of other control modules 11 and kernel control module 12 simultaneously, the other end and the kernel control module 11 of other control modules 12 are electrically connected, the output of kernel control module 11 is connected to the input of pulse generating circuit 13, and the output of pulse generating circuit 13 is connected to the 3rd triode Q
3with the 4th triode Q
4gate pole control end, the 3rd triode Q
3emitter and the 4th triode Q
4collector electrode connect, simultaneously as the output of logic control circuit 10.
Preferably, drive circuit 20 comprises totem-pote circuit 21 and driving transformer T
2, wherein totem-pote circuit 21 is by the 5th triode Q
5with the 6th triode Q
6form, driving transformer T
2by former limit winding N
dpwith vice-side winding N
dsform, the input of totem-pote circuit 21 connects and the 5th triode Q respectively
5with the 6th triode Q
6gate pole control end, the simultaneously output electrical connection of andlogic control circuit 10, the output of totem-pote circuit 21 connects the 5th triode Q
5emitter, the 6th triode Q
6collector electrode and driving transformer T
2former limit winding N
dpone end, driving transformer T
2former limit winding N
dpthe other end and the 6th triode Q
6emitter electrical connection, driving transformer T
2vice-side winding N
dsthe output of two ports as drive circuit 20 and the first power switch pipe Q of initiatively rate circuit
1with the second power switch pipe Q
2grid control end electrical connection.
Preferably, testing circuit 30 comprises detection resistance R1, comparator U1 and blanking circuit 31, the input of testing circuit 30 and high frequency transformer T
1auxiliary winding N
atwo ends electrical connection, an input of testing circuit 30 is connected to and detects resistance R
1one end, resistance R
1the other end be connected to comparator U
1an input, another input of testing circuit 30 is connected to reference level V
thone end, reference level V
ththe other end be connected to comparator U
1another input, comparator U
1output be connected to the input of blanking circuit 31, the output of blanking circuit 31 is connected to the input of logic control circuit 10.
First power switch pipe Q
1with the second power switch pipe Q
2when opening, high frequency transformer T
1former limit winding N
p1and N
p2inductance storage power, former limit winding N
p1and N
p2voltage is respectively the half of DC bus-bar voltage, the output diode D in secondary circuit
ocut-off, now, by output capacitance C
oenergy is provided to load.
As the first power switch pipe Q
1with the second power switch pipe Q
2during shutoff, the output diode D in secondary circuit
oconducting, is stored in energy in inductance through output diode D
o, output capacitance C
oto load release, give output capacitance C simultaneously
ocharging.Now, high frequency transformer T
1former limit winding N
p1and N
p2bear the magnitude of voltage that secondary output voltage reflexes to former limit, the first power switch pipe Q
1with the second power switch pipe Q
2both end voltage is half and the reflected voltage value sum of input voltage, and because former limit winding is divided into two groups, therefore reflected voltage also reduces to half compared with single-ended reverse exciting, the first power switch pipe Q
1with the second power switch pipe Q
2the voltage stress born also reduces to the half of single-ended reverse exciting.
When secondary current is about to drop to zero, the voltage that testing circuit 30 detects is lower than reference level V
th, comparator U
1output provide a signal, through blanking circuit 31 time delay, to prevent from disturbing the false triggering caused, then process through logic control circuit 10, at the first power switch pipe Q
1with the second power switch pipe Q
2both end voltage just in time provides drive singal at " trough " place, makes the first power switch pipe Q
1with the second power switch pipe Q
2" trough " can be realized open-minded, thus realize a kind of quasi-resonance control method, reduce the turn-on consumption of power switch pipe.
Beneficial effect of the present invention is: the feature utilizing neutral-point-clamped DC bus, by the form of two circuit of reversed excitation former limit series connection, the voltage that switching tube two ends are born is reduced to the half of single-ended reverse exciting, the stress effectively reducing power device, the conversion efficiency that improve converter and reliability, reduces the design cost of converter.By quasi-resonance converter technique, make switching tube at the Valley-Switching of low voltage, the turn-on consumption of switching tube is significantly reduced, the efficiency further increasing converter, the volume and weight reducing converter, improve the power density of converter.
Accompanying drawing explanation
Fig. 1 is circuit theory diagrams of the present invention.
Fig. 2 is the schematic diagram of logic control circuit of the present invention.
Fig. 3 is the schematic diagram of drive circuit of the present invention.
Fig. 4 is the schematic diagram of testing circuit of the present invention.
Embodiment
As shown in Figure 1, a kind of two flyback quasi resonant convertor of series connection being applicable to neutral-point-clamped DC bus, comprises main power circuit, logic control circuit 10, drive circuit 20 and testing circuit 30, wherein: main power circuit comprises former limit circuit, high frequency transformer T
1and secondary circuit, former limit circuit comprises DC bus, the first input capacitance C of neutral-point-clamped
i1with the second input capacitance C
i2and the first power switch pipe Q
1with the second power switch pipe Q
2, high frequency transformer T
1by former limit winding N
p1and N
p2, vice-side winding N
sand auxiliary winding N
aform, secondary circuit is by output diode D
owith output capacitance C
oform; The anode of DC bus and the first input capacitance C
i1one end electrical connection, connect high frequency transformer T simultaneously
1former limit winding N
p1one end, the first input capacitance C
i1the other end and the second input capacitance C
i2one end be connected in series, be electrically connected with the mid point end of DC bus, the second input capacitance C simultaneously
i2the other end connect the negative terminal of DC bus, high frequency transformer T
1former limit winding N
p1the other end connect the first power switch pipe Q
1one end, the first power switch pipe Q
1the other end and high frequency transformer T
1former limit winding N
p2one end electrical connection, be connected to the mid point end of DC bus, high frequency transformer T simultaneously
1former limit winding N
p2the other end and the second power switch pipe Q
2one end electrical connection, the second power switch pipe Q
2the other end connect the negative terminal of DC bus, high frequency transformer T
1vice-side winding N
sone end and output diode D
oone end electrical connection, output diode D
othe other end connect with output capacitance C
obe electrically connected with one end of load, output capacitance C
obe connected in parallel with the other end of load, simultaneously with high frequency transformer T
1vice-side winding N
sthe other end electrical connection.
As shown in Figure 2, logic control circuit 10 comprises kernel control module 12, other control modules 11, pulse generating circuit 13 and the 3rd triode Q
3with the 4th triode Q
4the input of logic control circuit 10 is connected to the output of testing circuit 30, the input of logic control circuit 10 is also connected to one end of other control modules 11 and kernel control module 12 simultaneously, the other end and the kernel control module 11 of other control modules 12 are electrically connected, the output of kernel control module 11 is connected to the input of pulse generating circuit 13, and the output of pulse generating circuit 13 is connected to the 3rd triode Q
3with the 4th triode Q
4gate pole control end, the 3rd triode Q
3emitter and the 4th triode Q
4collector electrode connect, simultaneously as the output of logic control circuit 10.
As shown in Figure 3, drive circuit 20 comprises totem-pote circuit 21 and driving transformer T
2, wherein totem-pote circuit 21 is by the 5th triode Q
5with the 6th triode Q
6form, driving transformer T
2by former limit winding N
dpwith vice-side winding N
dsform, the input of totem-pote circuit 21 connects and the 5th triode Q respectively
5with the 6th triode Q
6gate pole control end, the simultaneously output electrical connection of andlogic control circuit 10, the output of totem-pote circuit 21 connects the 5th triode Q
5emitter, the 6th triode Q
6collector electrode and driving transformer T
2former limit winding N
dpone end, driving transformer T
2former limit winding N
dpthe other end and the 6th triode Q
6emitter electrical connection, driving transformer T
2vice-side winding N
dsthe output of two ports as drive circuit 20 and the first power switch pipe Q of initiatively rate circuit
1with the second power switch pipe Q
2grid control end electrical connection.
As shown in Figure 4, testing circuit 30 comprises detection resistance R1, comparator U1 and blanking circuit 31, the input of testing circuit 30 and high frequency transformer T
1auxiliary winding N
atwo ends electrical connection, an input of testing circuit 30 is connected to and detects resistance R
1one end, resistance R
1the other end be connected to comparator U
1an input, another input of testing circuit 30 is connected to reference level V
thone end, reference level V
ththe other end be connected to comparator U
1another input, comparator U
1output be connected to the input of blanking circuit 31, the output of blanking circuit 31 is connected to the input of logic control circuit 10.
Major control principle of the present invention is: the first power switch pipe Q
1with the second power switch pipe Q
2when opening, high frequency transformer T
1former limit winding N
p1and N
p2inductance storage power, former limit winding N
p1and N
p2voltage is respectively the half of DC bus-bar voltage, the output diode D in secondary circuit
ocut-off, now, by output capacitance C
oenergy is provided to load.
As the first power switch pipe Q
1with the second power switch pipe Q
2during shutoff, the output diode D in secondary circuit
oconducting, is stored in energy in inductance through output diode D
o, output capacitance C
oto load release, give output capacitance C simultaneously
ocharging.Now, high frequency transformer T
1former limit winding N
p1and N
p2bear the magnitude of voltage that secondary output voltage reflexes to former limit, the first power switch pipe Q
1with the second power switch pipe Q
2both end voltage is half and the reflected voltage value sum of input voltage, and because former limit winding is divided into two groups, therefore reflected voltage also reduces to half compared with single-ended reverse exciting, the first power switch pipe Q
1with the second power switch pipe Q
2the voltage stress born also reduces to the half of single-ended reverse exciting.
When secondary current is about to drop to zero, the voltage that testing circuit 30 detects is lower than reference level V
th, comparator U
1output provide a signal, through blanking circuit 31 time delay, to prevent from disturbing the false triggering caused, then process through logic control circuit 10, at the first power switch pipe Q
1with the second power switch pipe Q
2both end voltage just in time provides drive singal at " trough " place, makes the first power switch pipe Q
1with the second power switch pipe Q
2" trough " can be realized open-minded, thus realize a kind of quasi-resonance control method, reduce the turn-on consumption of power switch pipe.
Although the present invention illustrates with regard to preferred implementation and describes, only it will be understood by those of skill in the art that otherwise exceed claim limited range of the present invention, variations and modifications can be carried out to the present invention.
Claims (7)
1. one kind is applicable to the two flyback quasi resonant convertor of series connection of neutral-point-clamped DC bus, it is characterized in that, comprise: main power circuit, logic control circuit 10, drive circuit 20 and testing circuit 30, wherein: main power circuit comprises former limit circuit, high frequency transformer T
1and secondary circuit, former limit circuit comprises DC bus, the first input capacitance C of neutral-point-clamped
i1with the second input capacitance C
i2and the first power switch pipe Q
1with the second power switch pipe Q
2, high frequency transformer T
1by former limit winding N
p1and N
p2, vice-side winding N
sand auxiliary winding N
aform, secondary circuit is by output diode D
owith output capacitance C
oform; The anode of DC bus and the first input capacitance C
i1one end electrical connection, connect high frequency transformer T simultaneously
1former limit winding N
p1one end, the first input capacitance C
i1the other end and the second input capacitance C
i2one end be connected in series, be electrically connected with the mid point end of DC bus, the second input capacitance C simultaneously
i2the other end connect the negative terminal of DC bus, high frequency transformer T
1former limit winding N
p1the other end connect the first power switch pipe Q
1one end, the first power switch pipe Q
1the other end and high frequency transformer T
1former limit winding N
p2one end electrical connection, be connected to the mid point end of DC bus, high frequency transformer T simultaneously
1former limit winding N
p2the other end and the second power switch pipe Q
2one end electrical connection, the second power switch pipe Q
2the other end connect the negative terminal of DC bus, high frequency transformer T
1vice-side winding N
sone end and output diode D
oone end electrical connection, output diode D
othe other end connect with output capacitance C
obe electrically connected with one end of load, output capacitance C
obe connected in parallel with the other end of load, simultaneously with high frequency transformer T
1vice-side winding N
sthe other end electrical connection.
2. converter as claimed in claim 1, it is characterized in that, described logic control circuit 10 comprises kernel control module 12, other control modules 11, pulse generating circuit 13 and the 3rd triode Q
3with the 4th triode Q
4the input of logic control circuit 10 is connected to the output of testing circuit 30, the input of logic control circuit 10 is also connected to one end of other control modules 11 and kernel control module 12 simultaneously, the other end and the kernel control module 11 of other control modules 12 are electrically connected, the output of kernel control module 11 is connected to the input of pulse generating circuit 13, and the output of pulse generating circuit 13 is connected to the 3rd triode Q
3with the 4th triode Q
4gate pole control end, the 3rd triode Q
3emitter and the 4th triode Q
4collector electrode connect, simultaneously as the output of logic control circuit 10.
3. converter as claimed in claim 1, it is characterized in that, described drive circuit 20 comprises totem-pote circuit 21 and driving transformer T
2, wherein totem-pote circuit 21 is by the 5th triode Q
5with the 6th triode Q
6form, driving transformer T
2by former limit winding N
dpwith vice-side winding N
dsform, the input of totem-pote circuit 21 connects and the 5th triode Q respectively
5with the 6th triode Q
6gate pole control end, the simultaneously output electrical connection of andlogic control circuit 10, the output of totem-pote circuit 21 connects the 5th triode Q
5emitter, the 6th triode Q
6collector electrode and driving transformer T
2former limit winding N
dpone end, driving transformer T
2former limit winding N
dpthe other end and the 6th triode Q
6emitter electrical connection, driving transformer T
2vice-side winding N
dsthe output of two ports as drive circuit 20 and the first power switch pipe Q of initiatively rate circuit
1with the second power switch pipe Q
2grid control end electrical connection.
4. converter as claimed in claim 1, is characterized in that, described testing circuit 30 comprises detection resistance R1, comparator U1 and blanking circuit 31, the input of testing circuit 30 and high frequency transformer T
1auxiliary winding N
atwo ends electrical connection, an input of testing circuit 30 is connected to and detects resistance R
1one end, resistance R
1the other end be connected to comparator U
1an input, another input of testing circuit 30 is connected to reference level V
thone end, reference level V
ththe other end be connected to comparator U
1another input, comparator U
1output be connected to the input of blanking circuit 31, the output of blanking circuit 31 is connected to the input of logic control circuit 10.
5. converter as claimed in claim 1, is characterized in that, the first power switch pipe Q
1with the second power switch pipe Q
2when opening, high frequency transformer T
1former limit winding N
p1and N
p2inductance storage power, former limit winding N
p1and N
p2voltage is respectively the half of DC bus-bar voltage, the output diode D in secondary circuit
ocut-off, now, by output capacitance C
oenergy is provided to load.
6. converter as claimed in claim 1, is characterized in that, as the first power switch pipe Q
1with the second power switch pipe Q
2during shutoff, the output diode D in secondary circuit
oconducting, is stored in energy in inductance through output diode D
o, output capacitance C
oto load release, give output capacitance C simultaneously
ocharging; Now, high frequency transformer T
1former limit winding N
p1and N
p2bear the magnitude of voltage that secondary output voltage reflexes to former limit, the first power switch pipe Q
1with the second power switch pipe Q
2both end voltage is half and the reflected voltage value sum of input voltage, and because former limit winding is divided into two groups, therefore reflected voltage also reduces to half compared with single-ended reverse exciting, the first power switch pipe Q
1with the second power switch pipe Q
2the voltage stress born also reduces to the half of single-ended reverse exciting.
7. converter as claimed in claim 1, it is characterized in that, when secondary current is about to drop to zero, the voltage that testing circuit 30 detects is lower than reference level V
th, comparator U
1output provide a signal, through blanking circuit 31 time delay, to prevent from disturbing the false triggering caused, then process through logic control circuit 10, at the first power switch pipe Q
1with the second power switch pipe Q
2both end voltage just in time provides drive singal at " trough " place, makes the first power switch pipe Q
1with the second power switch pipe Q
2realize " trough " open-minded.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510013564.3A CN104601027A (en) | 2015-01-12 | 2015-01-12 | Tandem double flyback quasi resonant converter suitable for neutral point clamped direct current bus |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510013564.3A CN104601027A (en) | 2015-01-12 | 2015-01-12 | Tandem double flyback quasi resonant converter suitable for neutral point clamped direct current bus |
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|---|---|
| CN104601027A true CN104601027A (en) | 2015-05-06 |
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|---|---|---|---|
| CN201510013564.3A Pending CN104601027A (en) | 2015-01-12 | 2015-01-12 | Tandem double flyback quasi resonant converter suitable for neutral point clamped direct current bus |
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| CN108233723A (en) * | 2018-03-26 | 2018-06-29 | 珠海格力电器股份有限公司 | Flyback circuit and flyback converter |
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| CN109889046A (en) * | 2019-01-16 | 2019-06-14 | 深圳市凌康技术有限公司 | A kind of flyback sourse input series connection voltage-equalizing control circuit and its control method |
| CN110073585A (en) * | 2016-12-22 | 2019-07-30 | 斯兰纳亚洲有限公司 | Accessory power supply for switched-mode power supply |
| CN110212777A (en) * | 2019-06-19 | 2019-09-06 | 杰华特微电子（杭州）有限公司 | The control circuit and control method for cascading circuit of reversed excitation, cascading circuit of reversed excitation |
| CN112838771A (en) * | 2020-04-08 | 2021-05-25 | 青岛经济技术开发区海尔热水器有限公司 | Instant electric water heater and power circuit thereof |
| CN113300611A (en) * | 2021-07-28 | 2021-08-24 | 佛山市联动科技股份有限公司 | Isolation power consumption adjusting circuit |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101925237A (en) * | 2010-08-20 | 2010-12-22 | 杭州电子科技大学 | Primary constant-current control device of isolated type flyback converter |
| EP2339727A1 (en) * | 2009-12-23 | 2011-06-29 | Comarco Wireless Technologies, Inc. | Single-stage single switch power factor correction circuit having isolated output and boost inductor between AC source and bridge rectifier |
| CN103414354A (en) * | 2013-07-16 | 2013-11-27 | 燕山大学 | Power switch device pulse transformer isolation driving circuit |
| CN104218807A (en) * | 2014-08-22 | 2014-12-17 | 国家电网公司 | High-voltage-resistant switching power supply |
| CN204517693U (en) * | 2015-01-12 | 2015-07-29 | 南京亚派科技股份有限公司 | A kind of two flyback quasi resonant convertor of series connection being applicable to neutral-point-clamped DC bus |
-
2015
- 2015-01-12 CN CN201510013564.3A patent/CN104601027A/en active Pending
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP2339727A1 (en) * | 2009-12-23 | 2011-06-29 | Comarco Wireless Technologies, Inc. | Single-stage single switch power factor correction circuit having isolated output and boost inductor between AC source and bridge rectifier |
| CN101925237A (en) * | 2010-08-20 | 2010-12-22 | 杭州电子科技大学 | Primary constant-current control device of isolated type flyback converter |
| CN103414354A (en) * | 2013-07-16 | 2013-11-27 | 燕山大学 | Power switch device pulse transformer isolation driving circuit |
| CN104218807A (en) * | 2014-08-22 | 2014-12-17 | 国家电网公司 | High-voltage-resistant switching power supply |
| CN204517693U (en) * | 2015-01-12 | 2015-07-29 | 南京亚派科技股份有限公司 | A kind of two flyback quasi resonant convertor of series connection being applicable to neutral-point-clamped DC bus |
Cited By (15)
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|---|---|---|---|---|
| CN112271929A (en) * | 2016-03-12 | 2021-01-26 | 快捷韩国半导体有限公司 | Active clamp flyback converter |
| CN112271929B (en) * | 2016-03-12 | 2024-05-28 | 快捷韩国半导体有限公司 | Active Clamp Flyback Converter |
| CN107181410A (en) * | 2016-03-12 | 2017-09-19 | 快捷韩国半导体有限公司 | Active clamp flyback converter |
| CN107181410B (en) * | 2016-03-12 | 2020-12-08 | 快捷韩国半导体有限公司 | Active clamp flyback converter |
| CN110073585B (en) * | 2016-12-22 | 2021-08-10 | 阿帕尔斯电力股份有限公司 | Auxiliary power supply for a switched mode power supply |
| CN110073585A (en) * | 2016-12-22 | 2019-07-30 | 斯兰纳亚洲有限公司 | Accessory power supply for switched-mode power supply |
| CN107834858A (en) * | 2017-11-07 | 2018-03-23 | 合肥东胜汽车电子有限公司 | Width funtion inputs the DCDC Switching Power Supplies of two-stage multiple-channel output |
| CN108233723A (en) * | 2018-03-26 | 2018-06-29 | 珠海格力电器股份有限公司 | Flyback circuit and flyback converter |
| CN109149988B (en) * | 2018-08-10 | 2021-04-20 | 爱士惟新能源技术(江苏)有限公司 | Auxiliary power supply |
| CN109149988A (en) * | 2018-08-10 | 2019-01-04 | 艾思玛新能源技术（江苏）有限公司 | A kind of accessory power supply |
| CN109889046A (en) * | 2019-01-16 | 2019-06-14 | 深圳市凌康技术有限公司 | A kind of flyback sourse input series connection voltage-equalizing control circuit and its control method |
| CN110212777A (en) * | 2019-06-19 | 2019-09-06 | 杰华特微电子（杭州）有限公司 | The control circuit and control method for cascading circuit of reversed excitation, cascading circuit of reversed excitation |
| CN112838771A (en) * | 2020-04-08 | 2021-05-25 | 青岛经济技术开发区海尔热水器有限公司 | Instant electric water heater and power circuit thereof |
| CN113300611A (en) * | 2021-07-28 | 2021-08-24 | 佛山市联动科技股份有限公司 | Isolation power consumption adjusting circuit |
| CN113300611B (en) * | 2021-07-28 | 2022-04-19 | 佛山市联动科技股份有限公司 | Isolation power consumption adjusting circuit |
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