CN103840652B - A kind of hybrid power factor correcting circuit - Google Patents
A kind of hybrid power factor correcting circuit Download PDFInfo
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- CN103840652B CN103840652B CN201210472357.0A CN201210472357A CN103840652B CN 103840652 B CN103840652 B CN 103840652B CN 201210472357 A CN201210472357 A CN 201210472357A CN 103840652 B CN103840652 B CN 103840652B
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The present invention provides a kind of hybrid power factor correcting circuit, including: power circuit be connected with described power circuit, be used for producing the drive pulse signal of M × N road phase shift and be input to the control circuit in described power circuit；Described power circuit includes: rectifier bridge；M boost inductance, the outfan of each boost inductance is connected with N number of power device respectively；Electrochemical capacitor, the positive terminal of described electrochemical capacitor is connected with the common port of the cathode end of M reverse fast recovery diode, forming the second cathode output end, the negative pole end of described electrochemical capacitor is connected with the emitter stage common port of M × N number of power device, forms the second cathode output end；Described control circuit includes: outer voltage controller；M current inner loop controller, current inner loop controller described in each of which connects has N number of phase shift to compare driver；Carrier generator.The present invention can be effectively improved power grade, simplifies boost inductance design, it is simple to power device type selecting and installation, reduces overall cost.
Description
Technical field
The present invention relates to power electronic devices technical field, particularly relate to a kind of circuit of power factor correction, specifically a kind of multiple
Close circuit of power factor correction.
Background technology
Single-phase active power factor corrector (APFC) has been widely applied in the frequency-conversion domestic electric appliances such as convertible frequency air-conditioner, is used as to hand over directly
The front stage circuits of AC-AC converter, gets final product AC-DC converter.Along with the trend of some application scenario convertible frequency air-conditioner high-power, need
The high-power single-phase APFC of corresponding power grade to be developed.Till up to now, following alternative circuit occurs altogether: (1)
Multistage staggered APFC；(2) single-stage APFC, it is considered to power device is in parallel；(3) single-stage APFC, selects high-power component.
The first scheme: advantage is to share power between APFC at different levels, and boost inductance can be installed at plate, deficiency is to rise
The ripple frequency of voltage inductance is equal to carrier frequency, need to consider at different levels between equal flow problems, boost inductor current detection difficult,
Control program is complex.
First scheme: advantage is just can be with hoisting power grade, and deficiency is that the ripple frequency of boost inductance is equal to carrier frequency,
Boost inductance can not be installed at plate, needs to consider equal flow problem between power device.For the APFC of more than 5.0kW, the party
Though feasible in case principle, the most unreasonable, it is difficult to use.
The third scheme: advantage is just can be with hoisting power grade, and deficiency is that the ripple frequency of boost inductance is equal to carrier frequency,
Boost inductance can not be extremely difficult in plate installing device type selecting, and indices is all difficult to improve.Similar first scheme, for
The APFC of more than 5.0kW, though feasible in program principle, the most unreasonable, it is difficult to adopt
With.
To this end, for high-power APFC application scenario, feasible on the first protocol population, but when using parallel power device
Time, it is also desirable to prior art especially actuation techniques is improved, in order to solve boost inductance design, power device type selecting etc. and ask
Topic, it is intended to improve overall performance.
Through the retrieval of prior art discovery following documents also having been encircleed high-power APFC:
【1】Michael O'Loughlin.UCC28070 300-W Interleaved PFC Pre-Regulator Design Review.Application
Report.SLUA479B-August 2008-Revised July 2010；【2】RENESAS Electronics Corporation,R2A20104/114
APN Rev.1.5 2010.07.23.http://www.renesas.com；【3】Fairchild Semiconductor Corporation,FANxxxx-Three
Channels Interleaved CCM PFC Controller.2011, Rev.0.2.Preliminary Version.www.fairchildsemi.com；
【4】Thomas Nussbaumer,Johann W.Kolar.Design Guidelines for Interleaved Single-Phase
BOOST PFC Circuits[J].IEEE Trans,power electron,vol.56,no.7,pp.2559–2573,July 200。
Document above the most all also exists such as problems such as boost inductance design and installation question, power device type selecting and installations.
Summary of the invention
The shortcoming of prior art in view of the above, it is an object of the invention to provide a kind of hybrid power factor correcting circuit, uses
In solving power device type selecting and installation difficulty and the relatively costly problem that existing circuit of power factor correction exists.
For achieving the above object and other relevant purposes, the present invention provides a kind of hybrid power factor correcting circuit, including: power
Circuit and be connected with described power circuit, be used for producing the drive pulse signal of M × N road phase shift and be input to described power circuit
In control circuit；Rectifier bridge, is electrically connected with single phase ac, and the output of described rectifier bridge forms the first cathode output end and first negative
Pole outfan；M boost inductance, the input of each boost inductance is connected with described first cathode output end, and each rises
The outfan of voltage inductance is connected with N number of power device respectively, the other end of each described power device and described first negative pole
Outfan is connected；M reverse fast recovery diode, each reverse fast recovery diode anode is corresponding and a boost inductance
Outfan is connected；Electrochemical capacitor, the public affairs of the positive terminal of the described electrochemical capacitor reversely cathode end of fast recovery diode individual with M
End is connected altogether, forms the second cathode output end, and the negative pole end of described electrochemical capacitor is public with the emitter stage of M × N number of power device
End is connected, and forms the second cathode output end；Described control circuit includes: outer voltage controller, defeated with described power circuit
Go out end to be connected, be used for obtaining voltage control quantity；M current inner loop controller, with described outer voltage controller and described power
Circuit is connected, and is used for obtaining electric current controlled quentity controlled variable；Carrier generator, is used for producing carrier signal；Driver is compared in M × N number of phase shift,
It is connected with the power device in described current inner loop controller, carrier generator and described power circuit respectively, is used for producing
The drive pulse signal of M × N road phase shift gives described power circuit；Current inner loop controller described in each of which connects N number of shifting
Compare driver；Wherein M, N are the positive integer more than 2.
Alternatively, described power device is insulated gate bipolar transistor, the colelctor electrode of described insulated gate bipolar transistor and send out
Connect inverse parallel between emitter-base bandgap grading and have fly-wheel diode；The colelctor electrode of described insulated gate bipolar transistor and the anode phase of fly-wheel diode
Even, emitter stage is connected with the negative electrode of electrochemical capacitor.
Alternatively, described power circuit also includes examining leakage resistance, and one end of described inspection leakage resistance is connected with the first cathode output end,
The other end is connected with the emitter stage of insulated gate bipolar transistor each described respectively.
Alternatively, the gate pole of outfan and described insulated gate bipolar transistor that driver is compared in described phase shift is connected.
Alternatively, described outer voltage controller according to the DC voltage of the output in power circuit and obtains electricity with reference to DC voltage
Pressure controlled quentity controlled variable.
Alternatively, described current controller according to the voltage control quantity in described outer voltage controller, the first cathode output end and
Current signal in the input voltage measurement signal of the first cathode output end formation and boost inductance obtains electric current controlled quentity controlled variable.
Alternatively, electric current controlled quentity controlled variable and the carrier wave generation that driver exports is compared in each phase shift according to described current inner loop controller
The carrier signal that device produces produces driving pulse, and is input in the power device in described power circuit by described driving pulse.
Alternatively, described rectifier bridge is both arms diode rectifier bridge；The live wire of described single-phase alternating current and zero line connect ac capacitor
Rear it is connected with two brachium pontis midpoints of described both arms diode rectifier bridge respectively.
Alternatively, be connected with between described first cathode output end and the first cathode output end the first resistance of series connection, the second resistance,
And the 3rd resistance.
As it has been described above, a kind of hybrid power factor correcting circuit of the present invention, have the advantages that
1, the present invention is by using M level cross structure, every grade of cross structure to include the N weight power device of parallel connection at power circuit,
Control circuit produces the driving signal of MN road phase shift, is used for driving power device in power circuit, can effectively reach to improve merit
Rate grade, simplifies boost inductance design, it is simple to power device type selecting and installation, reduces overall cost, can be widely used in
In single phase power factor correcting circuit.
2, circuit structure of the present invention is simple, and control algolithm is easy, reduces the design time.
3, the present invention uses the phase-shifting trigger principle of multiple power device to realize unity power factor correction, and doubled boost inductance
The Miniaturization Design of ripple frequency, beneficially boost inductance, reduces switching loss and the conduction loss of power device simultaneously.
Accompanying drawing explanation
Fig. 1 is shown as the structural representation of power circuit in a kind of hybrid power factor correcting circuit of the present invention.
Fig. 2 is shown as the structural representation of control circuit in a kind of hybrid power factor correcting circuit of the present invention.
Element numbers explanation
1 power circuit
2 control circuits
Detailed description of the invention
By particular specific embodiment, embodiments of the present invention being described below, those skilled in the art can be taken off by this specification
The content of dew understands other advantages and effect of the present invention easily.
Refer to Fig. 1.It should be clear that structure depicted in this specification institute accompanying drawings, ratio, size etc., the most only in order to coordinate
Content disclosed in bright book, understands for those skilled in the art and reads, being not limited to the enforceable restriction of the present invention
Condition, therefore do not have technical essential meaning, the modification of any structure, the change of proportionate relationship or the adjustment of size, at not shadow
Ring under the effect that can be generated by of the present invention and the purpose that can reach, all should still fall and obtain can contain at disclosed technology contents
In the range of lid.Meanwhile, in this specification cited as " on ", D score, "left", "right", the term of " middle " and " " etc.,
It is merely convenient to understanding of narration, and is not used to limit the enforceable scope of the present invention, being altered or modified of its relativeness,
Without under essence change technology contents, when being also considered as the enforceable category of the present invention.
Current power factor correcting circuit the most generally also exists such as boost inductance design and installation question, power device type selecting and installation
Etc. problem.In view of this, it is an object of the invention to provide a kind of hybrid power factor correcting circuit, be used for solving existing power
Power device type selecting that factor correcting circuit exists and installation difficulty and relatively costly problem.The present invention described in detail below
The principle of a kind of hybrid power factor correcting circuit and embodiment, make those skilled in the art need not creative work
Understand a kind of hybrid power factor correcting circuit of the present invention.
Refer to Fig. 1 and Fig. 2, be shown as the structural representation of a kind of hybrid power factor correcting circuit of the present invention.Such as Fig. 1
Shown in Fig. 2, the present invention provides a kind of hybrid power factor correcting circuit, including: power circuit 1 and control circuit 2.
Described power circuit 1 and single phase alternating current power supply uinIt is connected, it is provided that DC voltage output end, and is connected with control circuit 2,
There is signal contact each other.
Refer to Fig. 1, be shown as the structural representation of power circuit in a kind of hybrid power factor correcting circuit of the present invention.As
Shown in Fig. 1, described power circuit 1 at least includes rectifier bridge B1, M boost inductance, M × N number of power device, an electricity
Solve an electric capacity E1 and inspection leakage resistance R8.
Rectifier bridge B1, with single phase ac source uinBeing connected, described rectifier bridge B1 output forms the first cathode output end DCP1 and the
One cathode output end DCN1.Specifically, in the present embodiment, described rectifier bridge B1 is both arms diode rectifier bridge；Described list
Live wire ACL and the zero line ACN of cross streams electricity is connected with two brachium pontis midpoints of described both arms diode rectifier bridge respectively.More enter
One step ground, described both arms diode rectifier bridge is by four diodes (the diode Di1 shown in figure, diode Di2, diode
Di3 and diode Di4) constitute.
Meanwhile, two inputs of described both arms diode rectifier bridge, the live wire ACL of the most described single-phase alternating current and zero line
Connecting between ACN has ac capacitor C1, one end of described ac capacitor C1 to be connected with the live wire ACL of described single-phase alternating current,
The other end is connected with the zero line ACN of described single-phase alternating current.
It is connected with string between the first cathode output end DCP1 and the first cathode output end DCN1 that described rectifier bridge B1 output is formed
First resistance R1, the second resistance R2 and the 3rd resistance R3 of connection.First cathode output end DCP1 and the output of the first negative pole
Input voltage measurement signal is formed between end DCN1 | uin|。
M boost inductance, the input of each boost inductance is connected with described first cathode output end DCP1, and each rises
The outfan of voltage inductance is connected with N number of power device respectively, and one has M × N number of power device, each described power device
The other end be all connected with described first cathode output end DCN1, wherein M, N are the positive integer more than 2.
The input and the first cathode output end DCP1 that specifically refer to Fig. 1, the first boost inductance L1 are connected, first liter of piezoelectricity
The outfan of sense L1 is connected with the colelctor electrode of power device S11 ~ power device S1N；The input of the second boost inductance L2 with
First cathode output end DCP1 is connected, the outfan of the second boost inductance L2 and power device S21 ~ power device S2N current collection
The most connected；By that analogy, (M-1) boost inductance L(M-1)Input and the first cathode output end DCP1 be connected, (M-1)
Boost inductance L(M-1)Outfan be connected with power device S (M-1) 1 ~ power device S1 (M-1) N colelctor electrode；M rises piezoelectricity
Sense LMInput and the first cathode output end DCP1 be connected, M boost inductance LMOutfan and power device SM1～
Power device SMN colelctor electrode is connected.
First boost inductance L1, the second boost inductance L2 are until (M-1) boost inductance L(M-1), M boost inductance LMPoint
The not electric current i of corresponding output the first boost inductanceL1, the electric current i of the second boost inductanceL2Until the electric current of (M-1) boost inductance
iL(M-1), the electric current i of M boost inductanceLM。
In the present embodiment, described power device is insulated gate bipolar transistor, the current collection of described insulated gate bipolar transistor
Fly-wheel diode it is connected with between pole and emitter stage；The colelctor electrode of described insulated gate bipolar transistor and the negative electrode phase of fly-wheel diode
Even, emitter stage is connected with the anode of fly-wheel diode.
Specifically, as it is shown in figure 1,
The outfan of the first boost inductance L1 respectively with colelctor electrode and the sustained diode 11 of insulated gate bipolar transistor P11
Negative electrode be connected to the colelctor electrode of insulated gate bipolar transistor P1N and the anode of sustained diode 1N, insulated gate bipolar
The emitter stage of transistor P11 and the anode of sustained diode 11 are to the emitter stage of insulated gate bipolar transistor P1N and afterflow two
The anode of pole pipe D1N is connected with described first cathode output end DCN1 by inspection leakage resistance R8.
The outfan of the second boost inductance L2 respectively with colelctor electrode and the sustained diode 21 of insulated gate bipolar transistor P21
Negative electrode be connected to the colelctor electrode of insulated gate bipolar transistor P2N and the anode of sustained diode 2N, insulated gate bipolar
The emitter stage of transistor P21 and the anode of sustained diode 21 are to the emitter stage of insulated gate bipolar transistor P2N and afterflow two
The anode of pole pipe D2N is connected with described first cathode output end DCN1 by inspection leakage resistance R8.
The like, the annexation of the 3rd boost inductance to (M-2) boost inductance with power device repeats the most one by one at this.
(M-1) boost inductance L(M-1)Outfan respectively with colelctor electrode and the afterflow two of insulated gate bipolar transistor P (M-1) 1
The negative electrode of pole pipe D (M-1) 1 is to the colelctor electrode of insulated gate bipolar transistor P (M-1) N and the anode of sustained diode (M-1) N
Being connected, the emitter stage of insulated gate bipolar transistor P (M-1) 1 and the anode of sustained diode (M-1) 1 are to insulated gate bipolar
The emitter stage of transistor P (M-1) N and the anode of sustained diode (M-1) N are defeated with described first negative pole by inspection leakage resistance R8
Go out to hold DCN1 to be connected.
M boost inductance LMOutfan respectively with colelctor electrode and sustained diode M1 of insulated gate bipolar transistor PM1
Anode be connected to the colelctor electrode of insulated gate bipolar transistor PMN and the negative electrode of sustained diode MN, insulated gate bipolar
The emitter stage of transistor PM1 and the anode of sustained diode M1 are to the emitter stage of insulated gate bipolar transistor PMN and continuous
The anode of stream diode DMN is connected with described first cathode output end DCN1 by inspection leakage resistance R8.
The outfan of each described boost inductance is also connected with a reverse fast recovery diode, and one has M recovery two the fastest
Pole is managed, and each reverse fast recovery diode anode correspondence is connected with the outfan of a boost inductance.It will be noted from fig. 1 that
The outfan of the first boost inductance L1 is connected with reverse fast recovery diode D1, and the outfan of the second boost inductance L2 is connected with reversely
Fast recovery diode D2, (M-1) boost inductance L(M-1)Outfan be connected with reverse fast recovery diode D (M-1), M liter
Voltage inductance LMOutfan be connected with reverse fast recovery diode DM.
After the outfan of each described boost inductance connects a reverse fast recovery diode, M reverse fast recovery diode
Cathode end pools a common output end, and this common output end is connected with the positive terminal of described electrochemical capacitor E1.
The positive terminal of described electrochemical capacitor E1 is connected with the common port of the cathode end of M reverse fast recovery diode, is formed
Second cathode output end DCP2, the negative pole end of described electrochemical capacitor E1 is connected with the emitter stage common port of M × N number of power device,
Form the second cathode output end DCN2.Between second cathode output end DCP2 and the second cathode output end DCN2, output is straight
Stream voltage Udc。
Described electrochemical capacitor E1 is parallel with the resistance R4 of series connection, resistance R5 and resistance R6, and described electrochemical capacitor E1 is the most also
It is associated with resistance R7.
One end of described steady resistance R8 is connected with the first cathode output end DCN1, the other end respectively with insulation each described
The emitter stage of grid bipolar transistor (could also say that the emitter stage of insulated gate bipolar transistor and the anode of fly-wheel diode
Common end) it is connected.
Described control circuit 2 is connected with described power circuit 1, is used for producing the drive pulse signal of M × N road phase shift and inputting
In described power circuit 1.
Described control circuit 2 includes: an outer voltage controller, M current inner loop controller, a carrier generator and
Driver is compared in M × N number of phase shift.
Described outer voltage controller, is connected with the outfan of described power circuit 1, is used for obtaining voltage control quantity.Specifically,
Described outer voltage controller has two inputs, receives the DC voltage U of output in power circuit 1 respectivelydcStraight with reference
Stream voltage Uref, described with reference to DC voltage UrefSetting according to actual needs, general analog control circuit is 5.0V, numeral control
Circuit processed is 3.0V.Described outer voltage controller obtains the DC voltage U of the output in power circuit 1dcWith reference unidirectional current
Pressure Uref, control computing through PI and obtain voltage control quantity.Meanwhile, described outer voltage controller output voltage control amount.
The quantity of described current inner loop controller is equal, due to described boost inductance with the quantity of boost inductance in power circuit 1
Quantity is M, so the quantity of shown current inner loop controller is also M.
Described M current inner loop controller, is connected with described outer voltage controller and described power circuit 1 respectively, is used for obtaining
Obtain electric current controlled quentity controlled variable.Specifically, each described current controller has three inputs, and voltage control quantity, the first positive pole are defeated
Go out to hold the input voltage measurement signal formed between DCP1 and the first cathode output end DCN1 | uin| and in M boost inductance
Current signal (the electric current i of the first boost inductanceL1, the electric current i of the second boost inductanceL2Until the electric current of (M-1) boost inductance
iL(M-1), the electric current i of M boost inductanceLM) respectively with ring controller in ring controller, the 2nd stream in the 1st stream until the
In M-1 stream, three inputs of ring controller and m-th current inner loop controller are respectively connected with, and each current inner loop controls
Device output electric current controlled quentity controlled variable.
Accordingly, the electric current i of the first boost inductanceL1Input in the 1st current inner loop controller, the electric current i of the second boost inductanceL2
Input in the 1st current inner loop controller until the electric current i of (M-1) boost inductanceL(M-1)Input the M-1 current inner loop to control
In device, in input m-th current inner loop controller.
Further, described current controller is through in the voltage control quantity in described outer voltage controller, power circuit 1
The input voltage measurement signal formed between first cathode output end DCP1 and the first cathode output end DCN1 | uin| and M
The computing of the current signal of boost inductance obtains electric current controlled quentity controlled variable.
Described carrier generator, is used for producing carrier signal；Described carrier signal can be triangle carrier signal or sawtooth carrier wave
Signal.
The quantity that driver is compared in described phase shift is equal with the quantity of power device in power circuit 1, due to merit in power circuit 1
The quantity of rate device is M × N number of, so described phase shift compares the quantity of driver also for M × N number of.
Driver is compared in described M × N number of phase shift, respectively with described current inner loop controller, carrier generator and described power
Power device in circuit 1 is connected, and is used for producing the drive pulse signal of M × N road phase shift to described power circuit 1, the most often
One described current inner loop controller connects has N number of phase shift to compare driver.Described phase shift compares the outfan of driver with described
The gate pole of insulated gate bipolar transistor is connected.
Specifically, as in figure 2 it is shown, the 1st current inner loop controller compare with the 11st phase shift respectively driver P11, the 12nd
Driver P12 is compared in phase shift, until 1(N-1) phase shift compares driver P1(N-1) and 1N phase shift compare driver
The input of P1N is connected, and driver P11 is compared in the 11st phase shift simultaneously, driver P12 is compared in the 12nd phase shift, until 1(N-1)
Driver P1(N-1 is compared in phase shift) the outfan respectively corresponding and insulated gate bipolar of driver P1N is compared with 1N phase shift
The gate pole of transistor P11, insulated gate bipolar transistor P12 gate pole until insulated gate bipolar transistor P1(N-1)
Gate pole is connected with the gate pole of insulated gate bipolar transistor P1N.
Similarly, the 2nd current inner loop controller compares driver P21 with the 21st phase shift respectively, driving is compared in the 22nd phase shift
Device P22, until 2(N-1) phase shift compares driver P2(N-1) and 2N phase shift compare the input of driver P1N
Being connected, driver P21 is compared in the 21st phase shift simultaneously, driver P22 is compared in the 22nd phase shift, until 2(N-1) phase shift ratio
Relatively driver P2(N-1) the outfan respectively corresponding and insulated gate bipolar transistor of driver P2N is compared with 2N phase shift
The gate pole of P21, insulated gate bipolar transistor P22 gate pole until insulated gate bipolar transistor P2(N-1) gate pole and
The gate pole of insulated gate bipolar transistor P2N is connected.
The like, the 3rd current inner loop controller to (M-2) individual current inner loop controller compares the company of driver with phase shift
Connect pass to tie up to this and repeat the most one by one.
The M-1 current inner loop controller compares driver P (M-1) 1 with (M-1) 1 phase shift respectively, (M-1) 2 phase shift is compared
Driver P (M-1) 2, until driver P (M-1) (N-1) is compared in (M-1) (N-1) phase shift and (M-1) N phase shift is compared
The input of driver P (M-1) N is connected, and driver P (M-1) 1 is compared in (M-1) 1 phase shift simultaneously, (M-1) 2 phase shift is compared
Driver P (M-1) 2, until driver P (M-1) (N-1) is compared in (M-1) (N-1) phase shift and (M-1) N phase shift is compared
The outfan of driver P (M-1) N correspondence respectively and the gate pole of insulated gate bipolar transistor P (M-1) 1, insulated gate bipolar crystalline substance
The gate pole of body pipe P (M-1) 2 is until the gate pole of insulated gate bipolar transistor P (M-1) (N-1) and insulated gate bipolar transistor
The gate pole of P (M-1) N is connected.
M-th current inner loop controller compares driver PM1 with M1 phase shift respectively, driver PM2 is compared in M2 phase shift,
Until M(N-1) phase shift compares driver PM(N-1) input that compares driver PMN with MN phase shift is connected,
Driver PM1 is compared in M1 phase shift simultaneously, driver PM2 is compared in M2 phase shift, until M(N-1) phase shift compares
Driver PM(N-1) the outfan respectively corresponding and insulated gate bipolar transistor of driver PMN is compared with MN phase shift
The gate pole of PM1, insulated gate bipolar transistor PM2 gate pole until insulated gate bipolar transistor PM(N-1) gate pole
It is connected with the gate pole of insulated gate bipolar transistor PMN.
The input that described carrier generator compares driver with each phase shift is connected.
Electric current controlled quentity controlled variable that driver exports is compared in each phase shift according to described current inner loop controller and carrier generator produces
Carrier signal produces driving pulse, and is input to by described driving pulse in the power device in described power circuit 1.
From the foregoing, it will be observed that each current inner loop controller compares driver with N number of phase shift and is connected, M current inner loop controller is even
Being connected to M × N number of phase shift and compare driver, produce the drive pulse signal of M × N road phase shift altogether, its phase shift is 360 °/MN,
It is distributed regularly.
In summary it can be seen, the invention belongs to the circuit of power factor correction that M level is staggered, every grade of circuit of power factor correction is responsible for
Driving N phase shift 360 °/MN driving pulse, every grade of circuit of power factor correction only undertakes the 1/M of general power, total current.Often
The dutycycle of power device only has 1/M during original single-stage power factor correcting circuit, and the conduction loss of every power device is only
There is original 1/MN.In the case of switching frequency is constant, the on-off times of every power device is constant, but switching loss becomes
Declining again, the ripple frequency of boost inductance increases to original N times, and the design of boost inductance can be greatly simplified, synthesis
M × N times that total current ripple frequency is carrier frequency, the beneficially filtering of ac capacitor C1.If reduction switching frequency,
Then on-off times and the switching loss of every power device can decline, and the ripple frequency of boost inductance can keep constant.Power
The power consumption of device is disperseed, and its type selecting can be simplified.
Being analyzed by above, the power factor correcting method that the present invention drives by using two-stage phase shift, except being capable of power
Outside factor correcting, it is also possible to being suitable for relatively high power application scenario, concrete methods of realizing has two kinds:
(1) maintaining carrier frequency constant, the switching frequency i.e. maintaining power device is constant, simplifies the design of boost inductance, but
The conduction loss of total power device is constant, and total switching loss doubles, and the switching loss that every power device undertakes is substantially reduced.
(2) reduce carrier frequency at double, reduce the switching frequency of power device the most at double, maintain the design of original boost inductance,
But the conduction loss of total power device is constant, total switching loss is constant, and the switching loss that every power device undertakes is significantly
The type selecting of reduction, beneficially device and installation.
In use, according to practical situation, M Yu N can be the relatively small integer more than 2.
In sum, a kind of hybrid power factor correcting circuit of the present invention, have the advantages that
1, the present invention is by using M level cross structure, every grade of cross structure to include the N weight power device of parallel connection at power circuit,
Control circuit 2 produces the driving signal of MN road phase shift, is used for driving power device in power circuit, can effectively reach to improve
Power grade, simplifies boost inductance design, it is simple to power device type selecting and installation, reduces overall cost, can apply widely
In single phase power factor correcting circuit.
2, circuit structure of the present invention is simple, and control algolithm is easy, reduces the design time.
3, the present invention uses the phase-shifting trigger principle of multiple power device to realize unity power factor correction, and doubled boost inductance
The Miniaturization Design of ripple frequency, beneficially boost inductance, reduces switching loss and the conduction loss of power device simultaneously.
So, the present invention effectively overcomes various shortcoming of the prior art and has high industrial utilization.
The principle of above-described embodiment only illustrative present invention and effect thereof, not for limiting the present invention.Any it is familiar with this skill
Above-described embodiment all can be modified under the spirit and the scope of the present invention or change by the personage of art.Therefore, such as
All that in art, tool usually intellectual is completed under without departing from disclosed spirit and technological thought etc.
Effect is modified or changes, and must be contained by the claim of the present invention.
Claims (9)
1. a hybrid power factor correcting circuit, it is characterised in that including: power circuit and be connected with described power circuit, be used for
Produce the drive pulse signal of M × N road phase shift and be input to the control circuit in described power circuit；
Described power circuit includes:
Rectifier bridge, is electrically connected with single phase ac, and the output of described rectifier bridge forms the first cathode output end and the first negative pole is defeated
Go out end；
M boost inductance, the input of each boost inductance is connected with described first cathode output end, and each rises
The outfan of voltage inductance is connected with the colelctor electrode of N number of power device, the emitter stage of each described power device with
Described first cathode output end is connected；
M reverse fast recovery diode, each reverse fast recovery diode anode correspondence is defeated with a boost inductance
Go out end to be connected；
Electrochemical capacitor, the public affairs of the positive terminal of the described electrochemical capacitor reversely cathode end of fast recovery diode individual with M
End is connected altogether, forms the transmitting of the second cathode output end, the negative pole end of described electrochemical capacitor and M × N number of power device
Pole common port is connected, and forms the second cathode output end；
Described control circuit includes:
Outer voltage controller, is connected with the outfan of described power circuit, is used for obtaining voltage control quantity；
M current inner loop controller, is connected with described outer voltage controller and described power circuit, is used for obtaining electricity
Flow control amount；
Carrier generator, is used for producing carrier signal；
Driver is compared in M × N number of phase shift, respectively with described current inner loop controller, carrier generator and described merit
Power device in rate circuit is connected, and is used for producing the drive pulse signal of M × N road phase shift to described power circuit；
Current inner loop controller described in each of which connects has N number of phase shift to compare driver；
Each current inner loop controller compares driver with N number of phase shift and is connected, and M current inner loop controller connects
Having M × N number of phase shift to compare driver, produce the drive pulse signal of M × N road phase shift altogether, its phase shift is
360°/MN；
Wherein M, N are the positive integer more than 2.
Hybrid power factor correcting circuit the most according to claim 1, it is characterised in that described power device is insulated gate bipolar
Transistor npn npn, between the collector and emitter of described insulated gate bipolar transistor, inverse parallel has fly-wheel diode；Described absolutely
The colelctor electrode of edge grid bipolar transistor is connected with the negative electrode of fly-wheel diode, and emitter stage is connected with the anode of fly-wheel diode.
Hybrid power factor correcting circuit the most according to claim 2, it is characterised in that described power circuit also includes inspection stream electricity
Resistance, one end of described inspection leakage resistance is connected with the first cathode output end, the other end respectively with insulated gate bipolar each described
The emitter stage of transistor is connected.
Hybrid power factor correcting circuit the most according to claim 2, it is characterised in that the output of driver is compared in described phase shift
End is connected with the gate pole of described insulated gate bipolar transistor.
Hybrid power factor correcting circuit the most according to claim 1, it is characterised in that described outer voltage controller is according to merit
DC voltage and the reference DC voltage of the output in rate circuit obtain voltage control quantity.
Hybrid power factor correcting circuit the most according to claim 1, it is characterised in that described current inner loop controller is according to institute
State the input voltage inspection that the voltage control quantity in outer voltage controller, the first cathode output end and the first cathode output end are formed
Survey the current signal in signal and boost inductance and obtain electric current controlled quentity controlled variable.
Hybrid power factor correcting circuit the most according to claim 1, it is characterised in that each phase shift compare driver according to
The carrier signal that the electric current controlled quentity controlled variable of described current inner loop controller output and carrier generator produce produces drive pulse signal,
And described drive pulse signal is input in the power device in described power circuit.
Hybrid power factor correcting circuit the most according to claim 1, it is characterised in that described rectifier bridge is that both arms diode is whole
Stream bridge；The live wire of described single-phase alternating current and zero line connect after ac capacitor respectively with two of described both arms diode rectifier bridge
Brachium pontis midpoint is connected.
Hybrid power factor correcting circuit the most according to claim 1, it is characterised in that described first cathode output end and first
The first resistance of series connection, the second resistance and the 3rd resistance it is connected with between cathode output end.
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| Publication number | Priority date | Publication date | Assignee | Title |
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| US9966841B2 (en) * | 2015-05-18 | 2018-05-08 | Texas Instruments Incorporated | Power factor correction |
| CN105939102A (en) * | 2016-06-29 | 2016-09-14 | 儒竞艾默生环境优化技术（上海）有限公司 | Equal duty ratio power factor correction method and system and electronic equipment |
| CN106411116B (en) * | 2016-06-29 | 2018-10-19 | 儒竞艾默生环境优化技术（上海）有限公司 | A kind of Multi- Switch power factor correcting method, system and electronic equipment |
| DE102016221379A1 (en) * | 2016-10-31 | 2018-05-03 | Robert Bosch Gmbh | Suppressor and power supply |
| CN108599550A (en) * | 2018-06-22 | 2018-09-28 | 广东志高暖通设备股份有限公司 | A kind of active alternating expression power factor correction circuit |
| CN116683768A (en) * | 2023-06-15 | 2023-09-01 | 广州市锐丰数字科技有限公司 | Single-phase staggered parallel voltage-stabilizing power supply |
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| CN101217255A (en) * | 2008-01-16 | 2008-07-09 | 艾默生网络能源有限公司 | A PFC circuit with current sharing control module and the corresponding current sharing control method |
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