CN103825478B - Control method based on power frequency fixed switching frequency modular multi-level converter - Google Patents
Control method based on power frequency fixed switching frequency modular multi-level converter Download PDFInfo
- Publication number
- CN103825478B CN103825478B CN201410067306.9A CN201410067306A CN103825478B CN 103825478 B CN103825478 B CN 103825478B CN 201410067306 A CN201410067306 A CN 201410067306A CN 103825478 B CN103825478 B CN 103825478B
- Authority
- CN
- China
- Prior art keywords
- submodule
- group
- impulse waveform
- parameter
- level converter
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
Landscapes
- Inverter Devices (AREA)
Abstract
The invention discloses a kind of control method based on power frequency fixed switching frequency modular multi-level converter, by the modulation strategy periodically impulse waveform shifted, so that it is determined that often organize the feature of four impulse waveform parameters, and then the occurrence of impulse waveform parameter is determined with reference to nearest level modulation strategy, and use impulse waveform parameter vector form, impulse waveform parameter is finely adjusted by the principle according to the meritorious equipartition of energy, it is compiled into impulse waveform parameter list, under conditions of ensureing total harmonic distortion, it is achieved module absorbed power autobalance.Modulation ratio is determined by detection line voltage and current actual value, impulse waveform parameter is obtained than tabling look-up according to modulation, and then by corresponding principle and sub module cascade number size, impulse waveform carried out submodule switching signal when periodic shift obtains controlling without capacitance voltage, achieve control based on power frequency fixed switching frequency modular multi-level converter, provide good reference value for engineer applied.
Description
Technical field
The present invention relates to modular multilevel topological structure mesohigh electric energy quality controller and D.C. high voltage transmission neck
Territory, particularly relates to a kind of control method based on power frequency fixed switching frequency modular multi-level converter.
Background technology
Along with social progress and industrial development, there is two major features in modern power systems: electrical power trans mission/distribution system is huge, power train
System voltage and the continuous lifting of power grade.First, the demand of electric power is got more and more, in order to meet user to electricity by modern society
The demand that power is growing, power system becomes more and more huger, and coverage is more and more wide.This gives the steady of power system
Qualitative bring challenges.Simultaneously as China is vast in territory, but uneven geographical distribution of resources, in order to improve the effect of long term distance transmission of electricity
Rate, the application of D.C. high voltage transmission (HVDC, high-voltage direct current) technology is more and more extensive.Secondly, modern
The load of power system also has new feature: power electronic equipment has superior performance, by consumption industries such as industrial or agricultural
A large amount of employings.But, power electronic equipment, as nonlinear load, can inject idle and harmonic wave to electrical network, along with non-linear negative
Carrying the increase of capacity, it is the most increasing on the impact of distribution system, makes system exist dangerous, unstable hidden danger.Centering is high
Pressure electrical power trans mission/distribution system carries out reactive-load compensation, can be effectively improved the stability of power system.By height between different electric power systems
Pressure DC transmission system (HVDC) interconnection, can solve the asynchronous problem of system, it is also possible to stop fault to spread between the systems,
It it is the feasible method improving system stability with reliability.
Modular multi-level converter (MMC, Modular Multilevel Converter) must after proposing
Research widely and the strong interest of engineer to scholar.Modular multi-level converter has plurality of advantages: modularity sets
Meter, low switching frequency, low-power consumption, high-quality spectral characteristic etc..These advantages are to the manufacture of modular multi-level converter, peace
Dress, safeguards and brings huge convenience, also make it directly be linked into mesohigh electrical network without net side transformer.How electric modularity is now
Flat current transformer has been applied to HVDC transmission system and mesohigh utility power quality control system, becomes that to improve power transmission and distribution system steady
The qualitative effective ways with reliability.
Along with the development of high-power, engineer applied always being wished, modular multi-level converter has higher
Efficiency.One method of most effective of which is exactly to reduce the switching frequency of semiconductor switch device.But, in actual applications,
The reduction of switching frequency can control to bring extreme difficulties to modulation strategy and capacitor voltage balance.Become for modular multilevel
Many modulation strategies that stream device is proposed are the most applicable with capacitor voltage balance control method.Accordingly, it would be desirable to it is a kind of novel
It is solid that modulation strategy and corresponding capacitor voltage balance control method make modular multi-level converter operate effectively in
Determine under power frequency switching frequency.
For the control method problem under modular multi-level converter low switching frequency, many research work are with achievement
It is suggested.A kind of modulation strategy based on fixing power frequency switching frequency, and the uniform distribution that energy is between submodule be by
Periodically shift pulse waveform realizes, but the method is not owing to considering problem that each submodule energy loss is different and nothing
Method ensures that DC capacitor voltage meansigma methods is constant.As the most perfect, also scholar proposes a kind of fine setting pulse width
Control method carry out holding capacitor voltage constant, but this method can increase the harmonic content of output voltage.A class is also had to put down
The method of weighing apparatus capacitance voltage is by being ranked up capacitance voltage and being judged whether to enter electric capacity by the polarity of bridge arm current
Row discharge and recharge.But to be switching frequency higher and does not fixes for the problem of this kind of method.Author not yet sees for based on work
Frequently the good control strategy of fixed switching frequency modular multi-level converter.To this end, also need to based on power frequency switch lock
The control strategy problem of rate modular multi-level converter carries out systematic research.
Summary of the invention
For drawbacks described above or deficiency, it is an object of the invention to provide a kind of at power frequency fixed switching frequency lower mold massing
The modulation strategy of Multilevel Inverters and corresponding capacitor voltage balance control method.
For reaching object above, the technical solution used in the present invention is:
Comprise the following steps:
1), establishment impulse waveform initial parameter table:
1.1, according to the feature of impulse waveform in a power frequency period, set represent this impulse waveform one group of parameter as
(rk,wk), wherein, rkFor impulse waveform center position, wkIt it is half impulse waveform width;
1.2, the submodule of each for modular multi-level converter brachium pontis is divided into some groups, often containing four submodules in group
Block, and the impulse waveform set in every group includes sk1, sk2, sk3, sk4, its parameter is respectively (rk,wk), (-rk,π-wk), (-rk,
wk), (rk,π-wk);
1.3, set modulation ratio m, set modulation is substituted into following relationship than m, obtains set modulation ratio under m
Impulse waveform initial parameter rk'、wk':
Wherein i=1,2 ..., (N/2), N is each brachium pontis submodule number, k=1,2 ..., N/4, swiFor pulse
Waveform initial time value;
1.4, according to formula in step 1.3 (1) (2) (3), order modulation take different values than m, modulated accordingly than lower often
Initial parameter (the r of group pulse waveformk',wk'), by modulation than m and the corresponding initial parameter modulated than lower every group pulse waveform
(rk',wk') it is compiled into impulse waveform initial parameter table;
2), impulse waveform initial parameter table fine setting:
2.1, two-dimensional coordinate plane graph is set up, by the initial parameter of group pulse waveform every in impulse waveform initial parameter table
(rk',wk') be mapped in two-dimensional coordinate plane with the form of vector;
2.2, according to modular multi-level converter cascade submodule number, to impulse waveform initial parameter (rk',wk')
It is finely adjusted, obtains impulse waveform parameter (rk,wk);
2.3, by impulse waveform parameter (r obtained after step 2.2 is finely tunedk,wk), it is compiled into impulse waveform parameter
Table;
3) determination of submodule switching signal when, controlling without capacitance voltage:
3.1, the three-phase current i of detection module Multilevel Inverters ACa,ib,ic, by three-phase current ia,ib,icEnter
Row three-phase static coordinate system, to the computing of biphase rotating coordinate system, obtains watt current actual value i after computingdReal with reactive current
Actual value iq;
3.2, by watt current command value id *With watt current actual value idAnd referenced reactive current value iq *With idle electricity
Stream actual value iqIt is separately input on d axle and the q axle of current inner loop based on dq uneoupled control;3.3, obtain based on dq decoupling control
Active voltage command value v of the current inner loop output of systemid *With reactive voltage command value viq *, and according to active voltage command value
vid *With reactive voltage command value viq *Obtain modulating the phase contrast δ than m and line voltage and current transformer ac output voltage;
3.4, according to the modulation generated in step 3.3 than m, by inquiry impulse waveform parameter list obtain this modulation than under
Set of pulses waveform parameter (rk,wk);
3.5, phaselocked loop is utilized to detect current time electric network voltage phase θPLL, the phase obtained with step 3.3 by it
Potential difference δ is added, and obtains current time current transformer output AC voltage phase thetaph,x;
3.6, according to step 3.4 and step 3.5 gained impulse waveform parameter and current transformer output AC voltage phase thetaph,x,
Obtain the submodule pulse waveform signal before shifting
In formula (4), ph=a, b, c;X=u, l;I=1,2 ..., N, a phase, b phase, c phase is modular multilevel unsteady flow
The three-phase of device AC, u is the upper brachium pontis of modular multi-level converter, and l is the lower brachium pontis of modular multi-level converter;
3.7, the pulse waveform signal generated in step 3.6 is carried out periodic shift, when generation controls without capacitance voltage
Each submodule switching signal.
When setting up two-dimensional coordinate plane graph in described step 2.1, its x-axis, y-axis coordinate be: x=Lcos (rk'), y=
Lsin(rk'), wherein, L=sin (wk')。
In described step 2.2, according to the number of modular multi-level converter cascade submodule, ginseng initial to impulse waveform
Number (rk',wk') it is finely adjusted and specifically includes:
(1), when modular multi-level converter cascade submodule number is less than or equal to 12, then keep impulse waveform initial
Parameter (rk',wk') representated by the vertical coordinate of vector constant, abscissa is displaced toPlace, obtains impulse waveform parameter
(rk,wk);
(2), when modular multi-level converter cascade submodule number is less than 60 more than 12, two group pulse waveforms ginsengs are selected
Number is finely adjusted, and the principle of fine setting is to make the meansigma methods of the abscissa of vector represented by two group pulse waveform parameters beObtain impulse waveform parameter (rk,wk);
(3), when modular multi-level converter cascade submodule number is more than 60, three group pulse waveform parameters are selected to enter
Row fine setting, the principle of fine setting is to make the meansigma methods of the abscissa of vector represented by three group pulse waveform parameters be?
To impulse waveform parameter (rk,wk)。
By three-phase current i in described step 3.1a,ib,icCarry out the three-phase static coordinate system fortune to biphase rotating coordinate system
The transformation matrix calculated is:
Wherein, ω is the angular frequency of modular multi-level converter.
Watt current command value i in described step 3.2d *With referenced reactive current value iq *Particularly as follows:
When modular multi-level converter is operated under rectification mode, watt current command value id *By three-phase dc bus
The result that average voltage is exported through single channel subtractor and single channel proportional and integral controller with DC voltage set-point is true
Fixed;Referenced reactive current value iq *Determine according to the actual reactive requirement of AC network.
The modulation in described step 3.3 calculating than the phase contrast δ of m and line voltage and current transformer ac output voltage
Formula is:
The pulse waveform signal generated in step 3.6 is carried out periodic shift by described step 3.7, generates without electric capacity electricity
Voltage-controlled processed time each submodule switching signal specifically include:
(1), when modular multi-level converter cascade submodule number is less than or equal to 12, by shared set of pulses waveform
Parameter (rk,wk) four submodules be divided into a group, in each group, the pulse waveform signal corresponding to the first two submodule is carried out
Periodic shift, the pulse waveform signal corresponding to latter two submodule is also carried out same displacement, thus produces corresponding to phase
Answer the switching signal that submodule is new;
(2) when modular multi-level converter cascade submodule number is less than 60 more than 12, by two group pulse waveform parameters
The meansigma methods of representative vector abscissa isEight submodules be divided into one big group, wherein parameter (rka,wka) institute
Four corresponding submodules are a group, parameter (rkb,wkbFour submodules corresponding to) are b group;By a group the first two submodule institute
Corresponding pulse waveform signal carries out periodic shift with the pulse waveform signal corresponding to b group the first two submodule;By a, b two
The pulse waveform signal that in group, latter two submodule is corresponding shifts;
(3) when modular multi-level converter cascade submodule number is more than 60, by three group pulse waveform parameter institute's generations
The meansigma methods of table vector abscissa is12 submodules be divided into one big group, wherein parameter (rka,wka) institute right
Four submodules answered are a group, parameter (rkb,wkbFour submodules corresponding to) are b group, parameter (rkc,wkcCorresponding to) four
Individual submodule is c group;Impulse waveform corresponding to the first two submodule in a group, b group and c group is shifted, latter two submodule
Impulse waveform corresponding to block shifts.
Described step 3) after also include capacitor voltage balance control, particularly as follows:
4.1, half power frequency period every to submodule DC capacitor voltage is sampled once, is input to by sampling gained signal
Moving average low pass filter obtains capacitance voltage flip-flop after processing;
4.2, each for step 4.1 gained brachium pontis N number of capacitance voltage value is carried out descending sort, and according to ranking results antithetical phrase
Module is numbered;
4.3, the submodule capacitor voltage value of numbered i and numbered N+1-i is subtracted each other, obtains difference, wherein i=1,
2 ..., N/2, then, by difference compared with marginal value Δ V, if difference is more than or equal to Δ V, then turn to step 4.4;If difference
Less than Δ V, then continue after adding 1 by i value to implement step 4.3;
4.4, at the initial time of each power frequency period, the bridge arm current signal that previous periodic sampling obtains is utilized, to this
Current calculation its from LEiMoment is to LEN+1-iThe integration in moment, obtains rising edge transfer charge amount QL, and, to the previous cycle
Bridge arm current calculates it from FEiMoment is to FEN+1-iThe integration in moment, obtains trailing edge transfer charge amount QF;Wherein, LEiFor numbering
The rising edge time of the submodule switching pulse signal of i, LEN+1-iRising for the submodule switching pulse signal of numbering N+1-i
Along the moment,
FEiFor the trailing edge moment of the submodule switching pulse signal of numbering i, FEN+1-iSubmodule for numbering N+1-i is opened
Close the trailing edge moment of pulse signal;
4.5, rising edge transfer charge amount Q obtained by step 4.4 is judgedL:
If rising edge transfer charge amount QLMore than 0, then exchange the submodule of numbered i and the submodule of numbered N+1-i
The rising edge of switching pulse signal, and make i value add 1;Otherwise, the operation that i value is added 1 is carried out;
Judge trailing edge transfer charge amount QF:
If trailing edge transfer charge amount QFLess than 0, then exchange the submodule of numbered i and the submodule of numbered N+1-i
The trailing edge of switching pulse signal, and make i value add 1;
Otherwise carry out the operation that i value is added 1, i with N/2 is compared, if more than N/2, then illustrate that all submodules switch arteries and veins
Rush signal all to have determined that;Otherwise, forward step 4.3 to continue to implement above-mentioned steps.
Compared with the prior art, the invention have the benefit that
The invention provides a kind of control method based on power frequency fixed switching frequency modular multi-level converter, pass through
The modulation strategy periodically shifted impulse waveform, according to requirement such as direct current and meritorious first-harmonic to modulation strategy under power frequency
The balance of component, the symmetry of waveform, so that it is determined that often organize the feature of four impulse waveform parameters, and then adjust with reference to nearest level
System strategy determines the occurrence of impulse waveform parameter and is compiled into impulse waveform initial parameter table, and uses impulse waveform parameter to vow
Amount form, is finely adjusted impulse waveform parameter list according to the principle of the meritorious equipartition of energy, reduces voltage harmonic further the most abnormal
Variability.Further, the present invention determines modulation ratio m by detection line voltage and current actual value, obtains than tabling look-up according to modulation
Corresponding impulse waveform parameter, and then by the size of certain principle and sub module cascade number, impulse waveform is carried out periodically
Submodule switching signal when displacement obtains controlling without capacitance voltage, it is achieved that to how electric based on power frequency fixed switching frequency modularity
The control of flat current transformer, provides good reference value for engineer applied.
Further, sorted by antithetical phrase module capacitance voltage sample and bridge arm current zero passage detection judges whether full
Foot give-and-take conditions, if meeting, exchanging rising edge or the trailing edge of corresponding two sub-module switch pulse signals, thus obtaining
Whole submodule switching pulse signal.
Accompanying drawing illustrates:
Fig. 1 is modular multi-level converter main circuit topological structure of the present invention;
Fig. 2 is capacitor voltage balance control method flow chart of the present invention;
Fig. 3 is power frequency switching frequency modular multi-level converter system total closed loop control block diagram of the present invention;
Fig. 4 is closed loop capacitor voltage balance control system block diagram of the present invention;
Fig. 5 is two-dimensional coordinate plane graph of the present invention;Wherein, (a) is that a parameter maps two-dimensional coordinate plane graph, and (b) is
Multiple parameters map two-dimensional coordinate plane graph;
Fig. 6 is the submodule number of the present invention switching signal displacement policy map less than 12;
Fig. 7 is the submodule number of the present invention switching signal displacement policy map more than 12 less than 60;
Fig. 8 is the submodule number of the present invention switching signal displacement policy map more than 60;
Fig. 9 is the emulation experiment figure of power frequency modulation strategy;
Figure 10 is the l-G simulation test figure of capacitor voltage balance control method;
Figure 11 is the l-G simulation test figure being operated in dynamic response under rectification mode;
Figure 12 is the l-G simulation test figure being operated in dynamic response under inverter mode.
Detailed description of the invention:
Below in conjunction with the accompanying drawings the present invention is described in detail.
With reference to Fig. 1,2,3,4, the control based on power frequency fixed switching frequency modular multi-level converter in the present invention
Method, including the modulation strategy periodically shifted impulse waveform and exchange impulse waveform rising edge or the electric capacity of trailing edge
Voltage balancing control method.Specifically comprise the following steps that
The invention provides a kind of control method based on power frequency fixed switching frequency modular multi-level converter, including
Following steps:
1), establishment impulse waveform initial parameter table:
1.1, according to the feature of impulse waveform in a power frequency period, set represent this impulse waveform one group of parameter as
(rk,wk), wherein, rkFor impulse waveform center position, wkIt it is half impulse waveform width;
1.2, the submodule of each for modular multi-level converter brachium pontis is divided into some groups, often containing four submodules in group
Block, and the impulse waveform set in every group includes sk1, sk2, sk3, sk4, it is often organized parameter and is respectively (rk,wk), (-rk,π-wk), (-
rk,wk), (rk,π-wk);
1.3, set modulation ratio m, set modulation is substituted into following relationship than m, obtains set modulation ratio under m
Impulse waveform initial parameter rk'、wk':
Wherein i=1,2 ..., (N/2-1), N is each brachium pontis submodule number, k=1,2 ..., N/4, swiFor arteries and veins
Rush waveform initial time value;
1.4, according to the relational expression in step 1.3, order modulation takes different values than m, is modulated accordingly and often organizes arteries and veins than lower
Rush the initial parameter (r of waveformk',wk'), by modulation than m and the corresponding initial parameter (r modulated than lower every group pulse waveformk',
wk') it is compiled into impulse waveform initial parameter table;
2) impulse waveform initial parameter table fine setting:
2.1, set up two-dimensional coordinate plane graph, see Fig. 5, at the beginning of group pulse waveform every in impulse waveform initial parameter table
Beginning parameter (rk',wk') be mapped in two-dimensional coordinate plane with the form of vector, when setting up two-dimensional coordinate plane graph, its x-axis, y-axis
Coordinate is: x=Lcos (rk'), y=Lsin (rk'), wherein, L=sin (wk')。
2.2, according to the number of modular multi-level converter cascade submodule, to impulse waveform initial parameter (rk',wk')
It is finely adjusted, obtains impulse waveform parameter (rk,wk);
To impulse waveform initial parameter (rk',wk') it is finely adjusted and specifically includes:
(1), when modular multi-level converter cascade submodule number is less than or equal to 12, then keep impulse waveform initial
Parameter (rk',wk') representated by the vertical coordinate of vector constant, force to be displaced to abscissaPlace, obtains impulse waveform
Parameter (rk,wk);
(2), when modular multi-level converter cascade submodule number is less than 60 more than 12, two group pulse waveforms ginsengs are selected
Number is finely adjusted, and the principle of fine setting is to make the meansigma methods of the abscissa of vector represented by two group pulse waveform parameters beAgain vertical coordinate is finely adjusted in unit circle, makes the total harmonic distortion of current transformer output voltage reduce, obtain
Impulse waveform parameter (rk,wk);
(3), when modular multi-level converter cascade submodule number is more than 60, three group pulse waveform parameters are selected to enter
Row fine setting, the principle of fine setting is to make the meansigma methods of the abscissa of vector represented by three group pulse waveform parameters be?
To impulse waveform parameter (rk,wk)。
2.3, by impulse waveform parameter (r obtained after step 2.2 is finely tunedk,wk), it is compiled into impulse waveform parameter
Table;
3) determination of submodule switching signal when, controlling without capacitance voltage:
3.1, the three-phase current i of detection module Multilevel Inverters ACa,ib,ic, by three-phase current ia,ib,icEnter
Row three-phase static coordinate system, to the computing of biphase rotating coordinate system, obtains watt current actual value i after computingdReal with reactive current
Actual value iq;
By three-phase current ia,ib,icCarry out the three-phase static coordinate system transformation matrix to the computing of biphase rotating coordinate system
For:
Wherein, ω is the angular frequency of modular multi-level converter, and t is the time.
3.2, by watt current command value id *With watt current actual value idAnd referenced reactive current value iq *With idle electricity
Stream actual value iqIt is separately input on d axle and the q axle of current inner loop based on dq uneoupled control;
3.3, active voltage command value v of current inner loop based on dq uneoupled control output is obtainedid *Instruct with reactive voltage
Value viq *, and according to active voltage command value vid *With reactive voltage command value viq *Obtain modulating than m and line voltage and unsteady flow
The phase contrast δ of device ac output voltage;
Wherein, merit current instruction value id *With referenced reactive current value iq *Particularly as follows:
When modular multi-level converter is operated under rectification mode, watt current command value id *By three-phase dc bus
The result that average voltage is exported through single channel subtractor and single channel proportional and integral controller with DC voltage set-point is true
Fixed;Referenced reactive current value iq *Determine according to the actual reactive requirement of AC network.
3.4, according to the modulation generated in step 3.3 than m, by inquiry impulse waveform parameter list obtain this modulation than under
Set of pulses waveform parameter (rk,wk);The modulation calculating than the phase contrast δ of m and line voltage and current transformer ac output voltage
Formula is:
3.5, phaselocked loop is utilized to detect current time electric network voltage phase θPLL, the phase obtained with step 3.3 by it
Potential difference δ is added, and obtains current time current transformer output AC voltage phase thetaph,x;
3.6, according to step 3.4 and step 3.5 gained impulse waveform parameter and current transformer output AC voltage phase thetaph,x,
Obtain the submodule pulse waveform signal before shifting
Wherein, ph=a, b, c;X=u, l;I=1,2 ..., N, a phase, b phase, c phase is detection moduleization many level unsteady flow
The three-phase of device AC, u is the upper brachium pontis of modular multi-level converter, and l is the lower brachium pontis of modular multi-level converter;
3.7, the pulse waveform signal generated in step 3.6 is carried out periodic shift, when generation controls without capacitance voltage
Each submodule switching signal.
See Fig. 6, specifically include:
(1), when modular multi-level converter cascade submodule number is less than or equal to 12, by shared set of pulses waveform
Parameter (rk,wk) four submodules be divided into a group, in each group, the pulse waveform signal corresponding to the first two submodule enters
Line period shifts, and the pulse waveform signal corresponding to latter two submodule is also carried out same displacement, thus produce corresponding to
The switching signal that corresponding submodule is new;
(2) when modular multi-level converter cascade submodule number is less than 60 more than 12, Fig. 7 is seen, by two group pulses
Representated by waveform parameter, the meansigma methods of vector abscissa isEight submodules be divided into one big group, wherein parameter
(rka,wkaFour submodules corresponding to) are a group, parameter (rkb,wkbFour submodules corresponding to) are b group;By front for a group two
Pulse waveform signal corresponding to individual submodule and the pulse waveform signal corresponding to b group the first two submodule carry out periodically moving
Position;Pulse waveform signal corresponding for latter two submodule in a, b two groups is shifted;
(3) when modular multi-level converter cascade submodule number is more than 60, by three group pulse waveform parameter institute's generations
The meansigma methods of table vector abscissa is12 submodules be divided into one big group, wherein parameter (rka,wka) institute right
Four submodules answered are a group, parameter (rkb,wkbFour submodules corresponding to) are b group, parameter (rkc,wkcCorresponding to) four
Individual submodule is c group;Impulse waveform corresponding to the first two submodule in a group, b group and c group is shifted, latter two submodule
Impulse waveform corresponding to block shifts.
4), capacitor voltage balance controls:
4.1, half power frequency period every to submodule DC capacitor voltage is sampled once, is input to by sampling gained signal
Moving average low pass filter obtains capacitance voltage flip-flop after processing;
4.2, each for step 4.1 gained brachium pontis N number of capacitance voltage value is carried out descending sort, and according to ranking results antithetical phrase
Module is numbered;
4.3, the submodule capacitor voltage value of numbered i and numbered N+1-i is subtracted each other, obtains difference, wherein i=1,
2 ..., N/2, then, by difference compared with marginal value Δ V, if difference is more than or equal to Δ V, then turn to step 4.4;If difference
Less than Δ V, then continue after adding 1 by i value to implement step 4.3;
4.4, see Fig. 6,7, at the initial time of each power frequency period, utilize the bridge arm current that previous periodic sampling obtains
Signal, to this Current calculation its from LEiMoment is to LEN+1-iThe integration in moment, obtains rising edge transfer charge amount QL, and, right
The bridge arm current in previous cycle calculates it from FEiMoment is to FEN+1-iThe integration in moment, obtains trailing edge transfer charge amount QF;Its
In, LEiFor the rising edge time of the submodule switching pulse signal of numbering i, LEN+1-iSubmodule for numbering N+1-i switchs arteries and veins
Rush the rising edge time of signal, FEiFor the trailing edge moment of the submodule switching pulse signal of numbering i, FEN+1-iFor numbering N+1-
The trailing edge moment of the submodule switching pulse signal of i;
4.5, rising edge transfer charge amount Q obtained by step 4.4 is judgedL:
If rising edge transfer charge amount QLMore than 0, then exchange the submodule of numbered i and the submodule of numbered N+1-i
The rising edge of switching pulse signal, and make i value add 1;Otherwise, the operation that i value is added 1 is carried out;
Judge trailing edge transfer charge amount QF:
If trailing edge transfer charge amount QFLess than 0, then exchange the submodule of numbered i and the submodule of numbered N+1-i
The trailing edge of switching pulse signal, and make i value add 1;
Otherwise carry out the operation that i value is added 1, i with N/2 is compared, if more than N/2, then illustrate that all submodules switch arteries and veins
Rush signal all to have determined that;Otherwise, forward step 4.3 to continue to implement above-mentioned steps.
Seeing Fig. 9,10,11,12 and give the simulation waveform using control method of the present invention, wherein, Fig. 9 is power frequency modulation
The simulating, verifying of strategy, five simulation waveform figures are followed successively by from top to bottom: brachium pontis output voltage in A phase;Current transformer output lead electricity
Pressure;A cross streams side exports electric current and upper brachium pontis and lower bridge arm current;In A phase first submodule capacitor voltage of brachium pontis and
Flip-flop;The output voltage of first submodule of brachium pontis in A phase.
Figure 10 is the checking of capacitor voltage balance control method, and three simulation waveform figures are followed successively by from top to bottom: current transformer
AC three-phase phase voltage;AC side of converter three-phase phase current;24 submodule capacitor voltage of brachium pontis in A phase.
Figure 11 is the checking being operated in the dynamic response under rectification mode, and five simulation waveform figures are followed successively by from top to bottom:
Watt current command value and actual value and referenced reactive current value and actual value;AC side of converter three-phase phase voltage;Unsteady flow
Device AC three-phase phase current;24 submodule capacitor voltage of brachium pontis in A phase;DC side busbar voltage.
Figure 12 is the checking being operated in the dynamic response under inverter mode, and four simulation waveforms are followed successively by from top to bottom: have
Merit current instruction value and actual value and referenced reactive current value and actual value;AC side of converter three-phase phase voltage;Current transformer
AC three-phase phase current;24 submodule capacitor voltage of brachium pontis in A phase.
From simulation waveform it can be seen that this control method can make modular multi-level converter be operated in power frequency effectively
Under fixed switching frequency, and the dynamic characteristic that system work is in different modes also has well performance.
With reference to Fig. 1, constructing modular Multilevel Inverters in simulation software.The main circuit of modular multi-level converter
Structure, by respectively with six the linked reactor series connection of six brachium pontis, then constitutes double star and connects.Each brachium pontis has 24 copped waves
Block coupled in series forms, and module DC side parallel has electrolysis condenser, and switching device uses the large power all-controlled devices such as IGBT or GTO
Part.
In each brachium pontis, serial module structure number does not has the upper limit, value to be decided by electric power system electric pressure.In order to describe conveniently,
In the present invention, it is described in detail as a example by 24 block coupled in series.Again because the symmetry of A, B, C three-phase and upper and lower bridge arm
Symmetry, the most only needs the situation of brachium pontis in A phase of analyzing.Electrical network three-phase voltage is designated as us, it may be assumed that usa、usb、usc;Power supply three
Phase current is designated as is, it may be assumed that isa、isb、isc;In A phase, brachium pontis series connection 24 unit DC voltages of copped wave module are designated as v respectivelyap1、
vap2、vap3……vap24。
The present invention is given the control method of a kind of modular multi-level converter based on power frequency fixed switching frequency.Need
It is noted that the present invention is applicable to the integral multiple that number is 4 of the submodule on each brachium pontis of modular multi-level converter
Situation.For the feasibility of authentication control method, it is 100MVA that author has built capacity in simulation software, each brachium pontis by
The phantom of 24 copped wave block coupled in series.Modulator approach based on power frequency switching frequency in the present invention and capacitor voltage balance
Control method is verified in simulation software, and simulation results show modulation strategy effectively ensures fixing power frequency switch
Frequency and several power frequency period self-energy can be divided equally in submodule.Capacitance voltage control strategy realizes the most well simultaneously
The balance of submodule capacitor voltage controls in the case of do not affect AC output voltage waveforms.The method is correct, reliable,
Good reference value is provided for engineer applied.
Claims (4)
1. a control method based on power frequency fixed switching frequency modular multi-level converter, it is characterised in that include with
Lower step:
1), establishment impulse waveform initial parameter table:
1.1, according to the feature of impulse waveform in a power frequency period, the one group of parameter representing this impulse waveform is set as (rk,
wk), wherein, rkFor impulse waveform center position, wkIt it is half impulse waveform width;
1.2, the submodule of each for modular multi-level converter brachium pontis is divided into some groups, often containing four submodules in group,
And the impulse waveform set in every group includes sk1, sk2, sk3, sk4, its parameter is respectively (rk,wk), (-rk,π-wk), (-rk,wk),
(rk,π-wk);
1.3, set modulation ratio m, set modulation is substituted into following relationship than m, obtain set modulation than the arteries and veins under m
Rush waveform initial parameter rk'、wk':
Wherein i=1,2 ..., (N/2), N is each brachium pontis submodule number, k=1,2 ..., N/4, swiFor impulse waveform
Initial time value;
1.4, according to formula in step 1.3 (1) (2) (3), order modulation takes different values than m, is modulated accordingly and often organizes arteries and veins than lower
Rush the initial parameter (r of waveformk',wk'), by modulation than m and the corresponding initial parameter (r modulated than lower every group pulse waveformk',
wk') it is compiled into impulse waveform initial parameter table;
2), impulse waveform initial parameter table fine setting:
2.1, two-dimensional coordinate plane graph is set up, by the initial parameter (r of group pulse waveform every in impulse waveform initial parameter tablek',
wk') be mapped in two-dimensional coordinate plane with the form of vector;
2.2, according to the number of modular multi-level converter cascade submodule, to impulse waveform initial parameter (rk',wk') carry out
Fine setting, obtains impulse waveform parameter (rk,wk);
2.3, by impulse waveform parameter (r obtained after step 2.2 is finely tunedk,wk), it is compiled into impulse waveform parameter list;
3) determination of submodule switching signal when, controlling without capacitance voltage:
3.1, the three-phase current i of detection module Multilevel Inverters ACa,ib,ic, by three-phase current ia,ib,icCarry out three
Phase static coordinate is tied to the computing of biphase rotating coordinate system, obtains watt current actual value i after computingdWith reactive current actual value
iq;
3.2, by watt current command value id *With watt current actual value idAnd referenced reactive current value iq *Real with reactive current
Actual value iqIt is separately input on d axle and the q axle of current inner loop based on dq uneoupled control;
3.3, active voltage command value v of current inner loop based on dq uneoupled control output is obtainedid *With reactive voltage command value
viq *, and according to active voltage command value vid *With reactive voltage command value viq *Obtain modulating than m and line voltage and current transformer
The phase contrast δ of ac output voltage;
3.4, according to the modulation generated in step 3.3 than m, by inquiry impulse waveform parameter list obtain this modulation than under one group
Impulse waveform parameter (rk,wk);
3.5, phaselocked loop is utilized to detect current time electric network voltage phase θPLL, the phase contrast obtained with step 3.3 by it
δ is added, and obtains current time current transformer output AC voltage phase thetaph,x;
3.6, according to step 3.4 and step 3.5 gained impulse waveform parameter and current transformer output AC voltage phase thetaph,x, obtain
Submodule pulse waveform signal before shifting
In formula (4), ph=a, b, c;X=u, l;I=1,2 ..., N;A phase, b phase, c phase is handed over for modular multi-level converter
The three-phase of stream side, u is the upper brachium pontis of modular multi-level converter, and l is the lower brachium pontis of modular multi-level converter;
3.7, the pulse waveform signal generated in step 3.6 is carried out periodic shift, generate each son when controlling without capacitance voltage
Module switch signal;
When setting up two-dimensional coordinate plane graph in described step 2.1, its x-axis, y-axis coordinate be: x=Lcos (rk'), y=Lsin
(rk'), wherein, L=sin (wk');
In described step 2.2, according to the number of modular multi-level converter cascade submodule, to impulse waveform initial parameter
(rk',wk') it is finely adjusted and specifically includes:
(1), when modular multi-level converter cascade submodule number is less than or equal to 12, then impulse waveform initial parameter is kept
(rk',wk') representated by the vertical coordinate of vector constant, abscissa is displaced toPlace, obtains impulse waveform parameter (rk,
wk);
(2), when modular multi-level converter cascade submodule number is less than 60 more than 12, two group pulse waveform parameters are selected to enter
Row fine setting, the principle of fine setting is to make the meansigma methods of the abscissa of vector represented by two group pulse waveform parameters be?
To impulse waveform parameter (rk,wk);
(3), when modular multi-level converter cascade submodule number is more than 60, three group pulse waveform parameters are selected to carry out micro-
Adjusting, the principle of fine setting is to make the meansigma methods of the abscissa of vector represented by three group pulse waveform parameters beObtain arteries and veins
Rush waveform parameter (rk,wk);
The pulse waveform signal generated in step 3.6 is carried out periodic shift by described step 3.7, generates without capacitance voltage control
Time processed, each submodule switching signal specifically includes:
(1), when modular multi-level converter cascade submodule number is less than or equal to 12, by shared set of pulses waveform parameter
(rk,wk) four submodules be divided into a group, in each group, the pulse waveform signal corresponding to the first two submodule carries out the cycle
Property displacement, the pulse waveform signal corresponding to latter two submodule is also carried out same displacement, thus produces corresponding to corresponding son
The switching signal that module is new;
(2) when modular multi-level converter cascade submodule number is less than 60 more than 12, by two group pulse waveform parameter institute's generations
The meansigma methods of table vector abscissa isEight submodules be divided into one big group, wherein parameter (rka,wka) institute right
Four submodules answered are a group, parameter (rkb,wkbFour submodules corresponding to) are b group;By right for a group the first two submodule institute
The pulse waveform signal answered carries out periodic shift with the pulse waveform signal corresponding to b group the first two submodule;By a, b two groups
In pulse waveform signal corresponding to latter two submodule shift;
(3) when modular multi-level converter cascade submodule number is more than 60, will vow representated by three group pulse waveform parameters
The meansigma methods of amount abscissa is12 submodules be divided into one big group, wherein parameter (rka,wka) corresponding
Four submodules be a group, parameter (rkb,wkbFour submodules corresponding to) are b group, parameter (rkc,wkcCorresponding to) four
Submodule is c group;Impulse waveform corresponding to the first two submodule in a group, b group and c group is shifted, latter two submodule
Corresponding impulse waveform shifts;
Described step 3) after also include capacitor voltage balance control, particularly as follows:
4.1, half power frequency period every to submodule DC capacitor voltage is sampled once, is input to sampling gained signal slide
Average low pass filter obtains capacitance voltage flip-flop after processing;
4.2, each for step 4.1 gained brachium pontis N number of capacitance voltage value is carried out descending sort, and according to ranking results to submodule
It is numbered;
4.3, the submodule capacitor voltage value of numbered i and numbered N+1-i is subtracted each other, obtains difference, wherein i=1,
2 ..., N/2, then, by difference compared with marginal value Δ V, if difference is more than or equal to Δ V, then turn to step 4.4;If difference
Less than Δ V, then continue after adding 1 by i value to implement step 4.3;
4.4, at the initial time of each power frequency period, the bridge arm current signal that previous periodic sampling obtains is utilized, to this electric current
Calculate it from LEiMoment is to LEN+1-iThe integration in moment, obtains rising edge transfer charge amount QL, and, the brachium pontis to the previous cycle
Current calculation its from FEiMoment is to FEN+1-iThe integration in moment, obtains trailing edge transfer charge amount QF;Wherein, LEiFor numbering i
The rising edge time of submodule switching pulse signal, LEN+1-iDuring for the rising edge of the submodule switching pulse signal of numbering N+1-i
Carve, FEiFor the trailing edge moment of the submodule switching pulse signal of numbering i, FEN+1-iSubmodule for numbering N+1-i switchs arteries and veins
Rush the trailing edge moment of signal;
4.5, rising edge transfer charge amount Q obtained by step 4.4 is judgedL:
If rising edge transfer charge amount QLMore than 0, then exchange the submodule of numbered i and the submodule switch arteries and veins of numbered N+1-i
Rush the rising edge of signal, and make i value add 1;Otherwise, the operation that i value is added 1 is carried out;
Judge trailing edge transfer charge amount QF:
If trailing edge transfer charge amount QFLess than 0, then exchange the submodule of numbered i and the submodule switch arteries and veins of numbered N+1-i
Rush the trailing edge of signal, and make i value add 1;
Otherwise carry out the operation that i value is added 1, i with N/2 is compared, if more than N/2, then illustrating that all submodule switching pulses are believed
Number all have determined that;Otherwise, forward step 4.3 to continue to implement above-mentioned steps.
Control method based on power frequency fixed switching frequency modular multi-level converter the most according to claim 1, its
It is characterised by, by three-phase current i in described step 3.1a,ib,icCarry out the three-phase static coordinate system fortune to biphase rotating coordinate system
The transformation matrix calculated is:
Wherein, ω is the angular frequency of modular multi-level converter.
Control method based on power frequency fixed switching frequency modular multi-level converter the most according to claim 1, its
It is characterised by, watt current command value i in described step 3.2d *With referenced reactive current value iq *Particularly as follows:
When modular multi-level converter is operated under rectification mode, watt current command value id *By three-phase dc busbar voltage
The result that meansigma methods is exported through single channel subtractor and single channel proportional and integral controller with DC voltage set-point determines;Nothing
Merit current instruction value iq *Determine according to the actual reactive requirement of AC network.
Control method based on power frequency fixed switching frequency modular multi-level converter the most according to claim 1, its
It is characterised by, the meter than the phase contrast δ of m and line voltage and current transformer ac output voltage of the modulation in described step 3.3
Calculation formula is:
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
CN201410067306.9A CN103825478B (en) | 2014-02-26 | 2014-02-26 | Control method based on power frequency fixed switching frequency modular multi-level converter |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
CN201410067306.9A CN103825478B (en) | 2014-02-26 | 2014-02-26 | Control method based on power frequency fixed switching frequency modular multi-level converter |
Publications (2)
Publication Number | Publication Date |
---|---|
CN103825478A CN103825478A (en) | 2014-05-28 |
CN103825478B true CN103825478B (en) | 2016-08-17 |
Family
ID=50760372
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
CN201410067306.9A Expired - Fee Related CN103825478B (en) | 2014-02-26 | 2014-02-26 | Control method based on power frequency fixed switching frequency modular multi-level converter |
Country Status (1)
Country | Link |
---|---|
CN (1) | CN103825478B (en) |
Families Citing this family (12)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN104065057B (en) * | 2014-05-29 | 2016-03-02 | 浙江大学 | A kind of filtering method of cascade Distribution Static Compensator DC voltage |
WO2017005906A1 (en) * | 2015-07-09 | 2017-01-12 | Abb Schweiz Ag | Control of electrical converter based on optimized pulse patterns |
US10218285B2 (en) | 2015-10-19 | 2019-02-26 | Siemens Aktiengesellschaft | Medium voltage hybrid multilevel converter and method for controlling a medium voltage hybrid multilevel converter |
CN105915089B (en) * | 2016-05-06 | 2018-04-27 | 浙江大学 | A kind of balance control method of the MMC capacitance voltages based on drive signal logical process |
TWI702782B (en) * | 2017-10-26 | 2020-08-21 | 財團法人工業技術研究院 | Voltage balance control method and device for three-phase dc-ac inverter |
CN109067393B (en) * | 2018-08-28 | 2021-12-28 | 南方电网科学研究院有限责任公司 | Phase locking method, device and equipment of power system |
CN109254268B (en) * | 2018-10-17 | 2023-07-07 | 北京无线电测量研究所 | Radar waveform parameterization control method and system |
CN109728731A (en) * | 2019-01-07 | 2019-05-07 | 浙江大学 | A kind of controlled resonant converter with modular rectifier structure |
CN112350596B (en) * | 2020-11-19 | 2023-08-08 | 中国南方电网有限责任公司超高压输电公司 | Closed-loop control method for switching frequency of power module of flexible direct-current transmission system |
CN112636619B (en) * | 2020-11-24 | 2022-04-05 | 联合汽车电子有限公司 | Inverter bus current calculation method |
CN112564538B (en) * | 2020-12-16 | 2022-03-15 | 国网北京市电力公司 | Method and device for determining converter parameters |
CN114362202B (en) * | 2021-03-02 | 2023-06-20 | 天津大学 | Double-stage reverse thrust control method for multi-level converter |
Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN102739071A (en) * | 2012-06-20 | 2012-10-17 | 西安交通大学 | Method for controlling direct current capacitor voltage of modular multi-level converter based on circulating current decoupling |
Family Cites Families (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2011098100A1 (en) * | 2010-02-11 | 2011-08-18 | Siemens Aktiengesellschaft | Control of a modular converter having distributed energy stores by means of an observer for the currents and by means of an estimating unit for the intermediate circuit energy |
CN103001519B (en) * | 2012-12-01 | 2014-11-26 | 中国科学院电工研究所 | Method for controlling low-frequency operation of modular multilevel converter |
-
2014
- 2014-02-26 CN CN201410067306.9A patent/CN103825478B/en not_active Expired - Fee Related
Patent Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN102739071A (en) * | 2012-06-20 | 2012-10-17 | 西安交通大学 | Method for controlling direct current capacitor voltage of modular multi-level converter based on circulating current decoupling |
Also Published As
Publication number | Publication date |
---|---|
CN103825478A (en) | 2014-05-28 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
CN103825478B (en) | Control method based on power frequency fixed switching frequency modular multi-level converter | |
Shu et al. | Predictive harmonic control and its optimal digital implementation for MMC-based active power filter | |
CN104393779B (en) | A kind of modular multi-level converter control method based on carrier wave stacking modulation | |
CN108280271B (en) | Unified power flow controller equivalent modeling method based on switching period average principle | |
CN105811793B (en) | Modularization multi-level converter method for equalizing voltage based on self-energizing power supply frequency hopping control | |
CN104917406B (en) | Common-mode-injection-based nearest level modulation method for MMC | |
CN102739071A (en) | Method for controlling direct current capacitor voltage of modular multi-level converter based on circulating current decoupling | |
CN103401459B (en) | Triangularly connected chain H bridge suspended type inverter interphase DC side voltage balancing control method | |
CN101615853A (en) | The voltage vector pulse duration modulation method in three-level PWM rectifier symmetry three districts | |
CN111654052B (en) | Flexible direct current converter modeling device and method based on dynamic phasor method | |
CN103475250A (en) | General loop current control method for modular multi-level converter considering low frequency oscillation | |
CN106533233A (en) | Modularized multi-level converter optimization control method actively using second harmonic generation loop current | |
CN109347351A (en) | A kind of model predictive control method of modularization multi-level converter | |
CN107979106A (en) | MMC passive control methods under a kind of unbalanced electric grid voltage | |
CN105186898A (en) | Simplified multi-level space vector pulse width modulation method for any-level single-phase cascaded H-bridge type converter and modulation soft core thereof | |
CN102761284A (en) | Accuracy control method for single-phase diode clamping three level midpoint potential imbalance | |
CN107181259A (en) | The electrical-magnetic model and emulation mode of a kind of Distributed Power Flow controller | |
CN105099221A (en) | Simplified multilevel space vector pulse width modulation method for single-phase cascaded three-level bridge type converter of any number of level and modulation soft core thereof | |
CN104993494B (en) | Motor simulator based on four-quadrant power electronic converter and method | |
CN107947237A (en) | A kind of polymorphic type inverter isolated island microgrid method for analyzing stability | |
CN105024574B (en) | The MMC submodule capacitor voltage balance control methods modulated suitable for phase-shifting carrier wave | |
CN114070115A (en) | Multi-alternating-current-port high-voltage direct-hanging energy storage power conversion system and control method thereof | |
CN104410083A (en) | Capacitance midpoint potential balancing device on SVG (Static VAR Generator) direct current side and control method of capacitance midpoint potential balancing device | |
Moeini et al. | A hybrid phase shift-pulsewidth modulation and asymmetric selective harmonic current mitigation-pulsewidth modulation technique to reduce harmonics and inductance of single-phase grid-tied cascaded multilevel converters | |
CN104377721B (en) | VSC-HVDC optimal control method during a kind of unbalanced source voltage |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
C06 | Publication | ||
PB01 | Publication | ||
C10 | Entry into substantive examination | ||
SE01 | Entry into force of request for substantive examination | ||
C14 | Grant of patent or utility model | ||
GR01 | Patent grant | ||
CF01 | Termination of patent right due to non-payment of annual fee | ||
CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20160817 Termination date: 20190226 |