CN103594770B

CN103594770B - Passive double-frequency six-port device

Info

Publication number: CN103594770B
Application number: CN201310606618.8A
Authority: CN
Inventors: 吴永乐; 张伟伟; 刘元安; 高锦春; 黎淑兰; 于翠屏; 苏明
Original assignee: Beijing University of Posts and Telecommunications
Current assignee: Beijing University of Posts and Telecommunications
Filing date: 2013-11-25
Publication date: 2016-11-30
Anticipated expiration: 2033-11-25

Abstract

The invention discloses a passive dual-frequency six-port device, including a dual-frequency Wilkinson power splitter (A), the first port (a1) of which serves as the first port (Port1) of the passive dual-frequency six-port device; The first dual-frequency branch line coupler (B), its first port (b1) serves as the second port (Port2) of the passive dual-frequency six-port device; the second dual-frequency branch line coupler (C), the second port The first port (c1) and the fourth port (c4) serve as the fourth port (Port4) and the sixth port (Port6) of the passive dual-frequency six-port device respectively; and the third dual-frequency branch line coupler (D) , the first port (d1) and the fourth port (d4) serve as the fifth port (Port5) and the third port (Port3) of the passive dual-frequency six-port device respectively; the first port (Port1) and the The second port (Port2) is an input port, and the third port (Port3), the fourth port (Port4), the fifth port (Port5) and the sixth port (Port6) are output ports. The invention realizes that the two operating frequencies (f ₁ , f ₂ ) of the passive dual-frequency six-port device can be freely determined, and the phase differences between the four output ports are the same at the two operating frequencies.

Description

Passive Dual-Band Six-Port Device

技术领域technical field

本发明属于微波无源器件领域，特别的，涉及一种无源双频六端口器件。The invention belongs to the field of microwave passive devices, and in particular relates to a passive dual-frequency six-port device.

背景技术Background technique

六端口器件广泛应用于雷达，直接数字接收机，微波毫米波测量以及网络分析仪等领域中。1972年，美国国家标准局Hoer等人提出六端口电路的概念并将它用于微波网络分析，他们利用定向耦合器和功率分配器等具有特殊性能的微波分支元件组成六端口电路，并将信号源和负载接入6个端口中的两个端口，结果发现通过测量4个输出端口上的功率，便可以得到反射系数的幅度和相位信息。这种电路结构简单，造价低，同时还具有多功能、宽频段、高精度和高速度等优点。Six-port devices are widely used in radar, direct digital receiver, microwave and millimeter wave measurement and network analyzer and other fields. In 1972, the American National Bureau of Standards Hoer and others proposed the concept of a six-port circuit and used it for microwave network analysis. They used microwave branch components with special properties such as directional couplers and power dividers to form a six-port circuit, and the signal The source and load were connected to two of the six ports, and it was found that by measuring the power on the four output ports, the magnitude and phase information of the reflection coefficient could be obtained. This kind of circuit has simple structure and low cost, and also has the advantages of multi-function, wide frequency band, high precision and high speed.

随着无线通信的不断发展，双频器件的应用越来越广泛，许多无线通信标准基于两个或者更多的频段，比如全球移动通信系统(GSM)应用在0.9GHz，1.8GHz和1.9GHz等，双频特性可以极大的减小电路元件的数目从而减小成本，因此研究双频六端口电路具有重大的意义。With the continuous development of wireless communication, the application of dual-frequency devices is becoming more and more extensive. Many wireless communication standards are based on two or more frequency bands. For example, the Global System for Mobile Communications (GSM) is used in 0.9GHz, 1.8GHz and 1.9GHz. , the dual-frequency feature can greatly reduce the number of circuit components and reduce the cost, so it is of great significance to study the dual-frequency six-port circuit.

传统的六端口电路主要由3dB定向耦合器，魔T类混合接头和同向等分功分器等特殊的微波元件组成。而目前存在的双频六端口电路主要采用复合左右传输线的方法进行设计，但是这种基于左右手传输线的六端口电路应用于双频环境时，会导致四个输出端口之间的相位差在两个工作频率不同，进而影响了该六端口电路在双频环境下的应用，且左右手传输线制作复杂，不易实现。The traditional six-port circuit is mainly composed of special microwave components such as 3dB directional coupler, magic T type hybrid joint and co-directional equal power divider. However, the current dual-frequency six-port circuit is mainly designed by combining the left and right transmission lines. However, when the six-port circuit based on the left-hand transmission line is used in a dual-frequency environment, the phase difference between the four output ports will be between two The working frequency is different, which affects the application of the six-port circuit in a dual-frequency environment, and the production of the left and right hand transmission lines is complicated and difficult to implement.

发明内容Contents of the invention

(一)要解决的技术问题(1) Technical problems to be solved

鉴于上述技术问题，本发明提供了一种采用一个双频威尔金森功分器和三个双频分支线耦合器组成的无源双频六端口器件，以实现在两个工作频率输出端口的相位差相同，结构紧凑，易于集成。In view of the above-mentioned technical problems, the present invention provides a passive dual-frequency six-port device composed of a dual-frequency Wilkinson power divider and three dual-frequency branch line couplers, so as to realize the output ports at two operating frequencies The phase difference is the same, the structure is compact, and it is easy to integrate.

(二)技术方案(2) Technical solutions

根据本发明的一个方面，提供了一种无源双频六端口器件，其特征在于，包括：双频威尔金森功分器A，其第一端口a1作为无源双频六端口器件的第一端口Port1；第一双频分支线耦合器B，其第一端口b1作为所述无源双频六端口器件的第二端口Port2，第四端口b4通过50Ω负载连接到地；第二双频分支线耦合器C，其第二端口c2连接至所述双频威尔金森功分器A的第二端口a2，第三端口c3连接至所述第一双频分支线耦合器B的第二端口b2，第一端口c1和第四端口c4分别作为所述无源双频六端口器件的第四端口Port4和第六端口Port6；第三双频分支线耦合器D，其第二端口d2连接至所述双频威尔金森功分器A的第三端口a3，第三端口d3连接至所述第一双频分支线耦合器B的第三端口b3，第一端口d1和第四端口d4分别作为所述无源双频六端口器件的第五端口Port5和第三端口Port3；所述无源双频六端口器件中，所述第一端口Port1和第二端口Port2为输入端口，所述第三端口Port3、第四端口Port4、第五端口Port5和第六端口Port6为输出端口。According to one aspect of the present invention, a passive dual-frequency six-port device is provided, which is characterized in that it includes: a dual-frequency Wilkinson power divider A, the first port a1 of which is used as the first port of the passive dual-frequency six-port device One port Port1; the first dual-frequency branch line coupler B, its first port b1 is used as the second port Port2 of the passive dual-frequency six-port device, and the fourth port b4 is connected to the ground through a 50Ω load; the second dual-frequency Branch line coupler C, its second port c2 is connected to the second port a2 of the dual-frequency Wilkinson power divider A, and the third port c3 is connected to the second port of the first dual-frequency branch line coupler B Port b2, the first port c1 and the fourth port c4 are respectively used as the fourth port Port4 and the sixth port Port6 of the passive dual-frequency six-port device; the third dual-frequency branch line coupler D is connected to the second port d2 To the third port a3 of the dual-frequency Wilkinson power divider A, the third port d3 is connected to the third port b3 of the first dual-frequency branch line coupler B, the first port d1 and the fourth port d4 As the fifth port Port5 and the third port Port3 of the passive dual-frequency six-port device respectively; in the passive dual-frequency six-port device, the first port Port1 and the second port Port2 are input ports, and the The third port Port3, the fourth port Port4, the fifth port Port5 and the sixth port Port6 are output ports.

其中，所述双频威尔金森功分器A包括：彼此平行设置的第一对耦合线cl₁，其左端彼此连接作为双频威尔金森功分器A的第一端口a1；第一隔离电阻R₁，连接于所述第一对耦合线的右端口之间；彼此平行设置的第二对耦合线cl₂，其左端级联于第一对耦合线的右端，其右端分别作为双频威尔金森功分器A的第二端口a2和第三端口a3；以及第二隔离电阻R₂，连接于所述第二对耦合线的右端口之间。Wherein, the dual-frequency Wilkinson power divider A includes: a first pair of coupling lines cl ₁ arranged parallel to each other, the left ends of which are connected to each other as the first port a1 of the dual-frequency Wilkinson power divider A; the first isolation Resistor R ₁ is connected between the right ports of the first pair of coupling lines; the second pair of coupling lines cl ₂ arranged parallel to each other, the left end of which is cascaded to the right end of the first pair of coupling lines, and the right ends are respectively used as dual frequency The second port a2 and the third port a3 of the Wilkinson power divider A; and the second isolation resistor R ₂ are connected between the right ports of the second pair of coupled lines.

其中，所述第一对耦合线cl₁的左端连接到一引线l₀，以形成双频威尔金森功分器A的第一端口a1；以及所述第二对耦合线cl₂的右端分别连接到另一引线l₀，以分别形成双频威尔金森功分器A的第二端口a2和第三端口a3。Wherein, the left end of the first pair of coupled lines cl ₁ is connected to a lead line l ₀ to form the first port a1 of the dual-frequency Wilkinson power divider A; and the right ends of the second pair of coupled lines cl ₂ are respectively connected to another lead l ₀ to form the second port a2 and the third port a3 of the dual-frequency Wilkinson power splitter A respectively.

进一步，所述双频威尔金森功分器A中的参数满足以下条件：Further, the parameters in the dual-frequency Wilkinson power divider A meet the following conditions:

${Z Z}_{e e 11} = = {Z Z}_{o o} \sqrt{\frac{\sqrt{11 + + 88 {tan the tan}^{44} {θ θ}_{11}} - - 11}{{tan the tan}^{22} {θ θ}_{11}}},,$

${Z Z}_{e e 22} = = {Z Z}_{o o} \sqrt{\frac{\sqrt{11 + + 88 {tan the tan}^{44} {θ θ}_{11}} + + 11}{22 {tan the tan}^{22} {θ θ}_{11}}},,$

${R R}_{11} = = \frac{22 {Z Z}_{o o 11} {Z Z}_{o o 22} {tan the tan}^{22} {θ θ}_{11}}{\sqrt{(({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} (({Z Z}_{o o 11} {tan the tan}^{22} {θ θ}_{11} - - {Z Z}_{o o 22}))}},,$

${R R}_{22} = = \frac{22 {Z Z}_{o o} {Z Z}_{o o 22}^{22} (({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} + + 22 {Z Z}_{o o}^{22} {Z Z}_{o o 22} \sqrt{(({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} (({Z Z}_{o o 11} {tan the tan}^{22} {θ θ}_{11} - - {Z Z}_{o o 22}))}}{{Z Z}_{o o}^{22} {Z Z}_{o o 22} + + (({Z Z}_{o o 11} {Z Z}_{o o 22}^{22} - - {Z Z}_{o o}^{22} {Z Z}_{o o 11} + + {Z Z}_{o o 22}^{33})) {tan the tan}^{22} {θ θ}_{11}},,$

其中，f₁和f₂分别为两个工作频率，Z_e1为所述第一对耦合线的偶模特征阻抗，Z_e2为所述第二对耦合线的偶模特征阻抗，R₁,R₂为所述第一隔离电阻和第二隔离电阻的阻值，Z_o为引线l₀的特征阻抗，θ₁为第一对耦合线和第二对耦合线的电长度，Z_o1,Z_o2分别为第一对耦合线和第二对耦合线的奇模特征阻抗。Wherein, f ₁ and f ₂ are two operating frequencies respectively, Z _e1 is the even-mode characteristic impedance of the first pair of coupled lines, Z _e2 is the even-mode characteristic impedance of the second pair of coupled lines, R ₁ , R ₂ is the resistance value of the first isolation resistor and the second isolation resistor, Z _o is the characteristic impedance of the lead wire _l0 , θ ₁ is the electrical length of the first pair of coupled lines and the second pair of coupled lines, Z _o1 , Z _o2 are the odd-mode characteristic impedances of the first pair of coupled lines and the second pair of coupled lines, respectively.

优选的，所述双频威尔金森功分器A中的参数进一步满足以下条件：Z_o1＜Z_e1＜1.5Z_o1，Z_o2＜Z_e2＜1.5Z_o2；Preferably, the parameters in the dual-frequency Wilkinson power divider A further satisfy the following conditions: Z _o1 <Z _e1 <1.5Z _o1 , Z _o2 <Z _e2 <1.5Z _o2 ;

20Ω＜Z_e1，Z_e2＜150Ω，20Ω＜Z_o1，Z_o2＜120Ω；且20Ω<Z _e1 , Z _e2 <150Ω, 20Ω<Z _o1 , Z _o2 <120Ω; and

Z_o＝50Ω。Z _o =50Ω.

其中，所述第一双频分支线耦合器B、第二双频分支线耦合器C和第三双频分支线耦合器D为具有相同结构的双频分支线耦合器，每个所述双频分支线耦合器包括：分支线耦合器l₂，l₃，在该分支线耦合器的4个端口分别级联连接的第一双频阻抗匹配微带线l_a、第二双频阻抗匹配微带线l_b以及引线l₀。Wherein, the first dual-frequency branch line coupler B, the second dual-frequency branch line coupler C and the third dual-frequency branch line coupler D are dual-frequency branch line couplers with the same structure, each of the dual-frequency branch line couplers The frequency branch line coupler includes: branch line couplers l ₂ , l ₃ , the first dual-frequency impedance matching microstrip line l _a and the second dual-frequency impedance matching Microstrip line l _b and lead l ₀ .

其中，所述分支线耦合器包括沿第一方向平行设置的第一对微带线l₂，沿与第一方向垂直的第二方向平行设置的第二对微带线l₃；所述引线l₀连接到每个端口的第二双频阻抗匹配微带线l_b上，形成每个双频分支线耦合器的4个端口。Wherein, the branch line coupler includes a first pair of microstrip lines l ₂ arranged in parallel along a first direction, a second pair of microstrip lines l ₃ arranged in parallel along a second direction perpendicular to the first direction; the leads l ₀ is connected to the second dual frequency impedance matching microstrip line l _b of each port to form 4 ports of each dual frequency branch line coupler.

进一步，每个所述双频分支线耦合器的参数满足以下条件：Further, the parameters of each of the dual-frequency branch line couplers meet the following conditions:

${Z Z}_{22} = = \sqrt{22} {Z Z}_{33},,$

${Z Z}_{a a} = = \frac{- - H h &PlusMinus; &PlusMinus; \sqrt{{H h}^{22} - - 44 F f K K}}{22 F f},,$

${Z Z}_{b b} = = - - \frac{B B}{44 A A} + + \frac{11}{22} \sqrt{((\frac{{B B}^{22}}{44 {A A}^{22}} - - \frac{22 C C}{33 A A} + + {Δ Δ}_{11} + + {Δ Δ}_{22}))} + + \frac{11}{22} \sqrt{((\frac{{B B}^{22}}{22 {A A}^{22}} - - \frac{44 C C}{33 A A} - - {Δ Δ}_{11} - - {Δ Δ}_{22} + + \frac{44 A A B B C C - - {B B}^{33} - - 88 {A A}^{22} D D.}{44 {A A}^{33} \sqrt{((\frac{{B B}^{22}}{44 {A A}^{22}} - - \frac{22 C C}{33 A A} + + {Δ Δ}_{11} + + {Δ Δ}_{22}))}}))},,$

${R R}_{i i n no} = = \frac{\sqrt{(({Z Z}_{22}^{22} - - {Z Z}_{33}^{22})) {Z Z}_{22}^{22} {Z Z}_{33}^{22} {sin sin}^{22} ((θ θ))}}{(({Z Z}_{22} + + {Z Z}_{33})) [[{Z Z}_{22} - - {Z Z}_{33} + + (({Z Z}_{22} + + {Z Z}_{33})) {cos cos}^{22} ((θ θ))]]},,$

${X x}_{i i n no} = = \frac{(({Z Z}_{22} + + {Z Z}_{33})) {Z Z}_{22} {Z Z}_{33} c c o o s the s ((θ θ)) s the s i i n no ((θ θ))}{(({Z Z}_{22} + + {Z Z}_{33})) [[{Z Z}_{22} - - {Z Z}_{33} + + (({Z Z}_{22} + + {Z Z}_{33})) {cos cos}^{22} ((θ θ))]]},,$

A＝R_in(Z_o-R_in)tan²(θ)，A＝R _in (Z _o -R _in )tan ² (θ),

B＝2Z_oR_inX_in tan³(θ)，B＝2Z _o R _in X _in tan ³ (θ),

$C C = = (({R R}_{i i n no} - - {Z Z}_{o o})) (({Z Z}_{o o} {R R}_{i i n no}^{22} + + {Z Z}_{o o} {X x}_{i i n no}^{22} - - {Z Z}_{o o}^{22} {R R}_{i i n no})) - - [[22 + + {tan the tan}^{22} ((θ θ))]] {tan the tan}^{22} ((θ θ)) {Z Z}_{o o}^{22} {X x}_{i i n no}^{22},,$

$D D. = = - - 22 {Z Z}_{o o}^{33} {R R}_{i i n no} {X x}_{i i n no} {tan the tan}^{33} ((θ θ)),,$

$E E. = = {Z Z}_{o o}^{33} {R R}_{i i n no} (({R R}_{i i n no}^{22} + + {X x}_{i i n no}^{22} - - {Z Z}_{o o} {R R}_{i i n no})) {tan the tan}^{22} ((θ θ)),,$

F＝-Z_o tan²(θ)，F＝-Z _o tan ² (θ),

H＝(Z_o-R_in)Z_b-Z_oX_in tan(θ)，H＝(Z _o -R _in )Z _b -Z _o X _in tan(θ),

$K K = = {R R}_{i i n no} {Z Z}_{b b}^{22} {tan the tan}^{22} ((θ θ)) - - {Z Z}_{o o} {X x}_{i i n no} {Z Z}_{b b} t t a a n no ((θ θ)),,$

${Δ Δ}_{11} = = (\begin{matrix} \frac{\sqrt[33]{22} (({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}{33 A A [[22 {C C}^{33} - - 99 B B C C D D. + + 2727 {AD AD}^{22} + + 2727 {B B}^{22} E E. - - 7272 A A C C E E.} \\ + + \sqrt{- - 44 {(({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}^{33} + + {((22 {C C}^{33} - - 99 B B C C D D. + + 2727 {AD AD}^{22} + + 2727 {B B}^{22} E E. - - 7272 A A C C E E.))}^{22}} {]]}^{11 / / 33} \end{matrix}),,$

${Δ Δ}_{22} = = \frac{(({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}{{Δ Δ}_{11} {((A A B B))}^{22}},,$

其中，Z₂,Z₃分别为第一对微带线l₂和第二对微带线l₃的特征阻抗，Z_a,Z_b分别为每个端口的第一双频阻抗匹配微带线l_a和第二双频阻抗匹配微带线l_b的特征阻抗，Z_o为引线l₀的特征阻抗，θ为上述所有微带线的电长度。Among them, Z ₂ , Z ₃ are the characteristic impedances of the first pair of microstrip lines l ₂ and the second pair of microstrip lines 1 ₃ respectively, Z _a , Z _b are the first dual-frequency impedance matching microstrip lines of each port l _a and the second dual-frequency impedance match the characteristic impedance of the microstrip line l _b , Z _o is the characteristic impedance of the lead line l ₀ , and θ is the electrical length of all the above-mentioned microstrip lines.

优选的，上述所有微带线的特征阻抗Z_i满足：20Ω＜Z_i＜120Ω，其中i＝a,b,2,3。Preferably, the characteristic impedance Z _i of all the above-mentioned microstrip lines satisfies: 20Ω<Z _i <120Ω, where i=a, b, 2,3.

优选的，所述无源双频六端口器件的参数满足下述条件：Preferably, the parameters of the passive dual-frequency six-port device meet the following conditions:

Z_e1＝81.5769Ω，Z_o1＝43.3340Ω，Z_e2＝61.2918Ω，Z _e1 =81.5769Ω, Z _o1 =43.3340Ω, Z _e2 =61.2918Ω,

Z_o2＝40.1384Ω，R₁＝63.0738Ω，R₂＝565.1966Ω，Z _o2 =40.1384Ω, R ₁ =63.0738Ω, R ₂ =565.1966Ω,

Z_a＝41.5501Ω，Z_b＝74.7131Ω，Z₂＝42.4264Ω，Z _a =41.5501Ω, Z _b =74.7131Ω, Z ₂ =42.4264Ω,

Z₃＝30Ω，θ₁＝θ＝90°，Z ₃ =30Ω, θ ₁ =θ=90°,

无源双频六端口器件的两个工作频率分别为f₁＝3GHz，f₂＝5GHz。The two operating frequencies of the passive dual-frequency six-port device are respectively f ₁ =3 GHz and f ₂ =5 GHz.

(三)有益效果(3) Beneficial effects

从上述技术方案可以看出，本发明无源双频六端口器件具有以下有益效果：(1)通过一个双频威尔金森功分器以及三个双频分支线耦合器，实现了无源双频六端口器件两个工作频率(f₁、f₂)可以自由决定，且四个输出端口之间的相位差在两个工作频率相同；(2)采用耦合微带线结构的双频威尔金森功分器、微带线结构的双频分支线耦合器以及三个阻值不同的贴片电阻，实现了小型化、结构紧凑的无源双频六端口器件，易于单片微波集成技术(MMIC)进行集成。It can be seen from the above technical scheme that the passive dual-frequency six-port device of the present invention has the following beneficial effects: (1) through a dual-frequency Wilkinson power divider and three dual-frequency branch line couplers, the passive dual-frequency The two operating frequencies (f ₁ , f ₂ ) of the frequency six-port device can be freely determined, and the phase difference between the four output ports is the same at the two operating frequencies; (2) The dual-frequency Will with coupled microstrip line structure Jinsen power divider, dual-frequency branch line coupler with microstrip line structure and three chip resistors with different resistance values realize a miniaturized and compact passive dual-frequency six-port device, which is easy to monolithic microwave integration technology ( MMIC) for integration.

附图说明Description of drawings

图1显示了根据本发明示例性实施例的无源双频六端口器件的整体结构框图；Fig. 1 has shown the overall structural block diagram of passive dual-frequency six-port device according to an exemplary embodiment of the present invention;

图2为本发明的无源双频六端口器件中威尔金森功分器的等效电路原理图；Fig. 2 is the equivalent circuit schematic diagram of the Wilkinson power divider in the passive dual-frequency six-port device of the present invention;

图3为图2所示威尔金森功分器的平面结构示意图；Fig. 3 is the plane structure schematic diagram of Wilkinson power divider shown in Fig. 2;

图4为本发明的无源双频六端口器件中双频分支线耦合器的等效电路原理图；Fig. 4 is the equivalent circuit schematic diagram of the dual-frequency branch line coupler in the passive dual-frequency six-port device of the present invention;

图5为图4所示双频分支线耦合器的平面结构示意图；FIG. 5 is a schematic plan view of the dual-frequency branch line coupler shown in FIG. 4;

图6A～图6C为本发明无源双频六端口器件的理想模型仿真结果图；Fig. 6A～Fig. 6C are the ideal model simulation result diagrams of the passive dual-frequency six-port device of the present invention;

图7A～图7C为本发明优选实施例的无源双频六端口器件的物理模型仿真结果图。7A to 7C are diagrams showing simulation results of a physical model of a passive dual-frequency six-port device according to a preferred embodiment of the present invention.

具体实施方式detailed description

为使本发明的目的、技术方案和优点更加清楚明白，以下结合具体实施例，并参照附图，对本发明进一步详细说明。需要说明的是，在附图或说明书描述中，相似或相同的部分都使用相同的图号。附图中未绘示或描述的实现方式，为所属技术领域中普通技术人员所知的形式。另外，虽然本文可提供包含特定值的参数的示范，但应了解，参数无需确切等于相应的值，而是可在可接受的误差容限或设计约束内近似于相应的值。In order to make the object, technical solution and advantages of the present invention clearer, the present invention will be described in further detail below in conjunction with specific embodiments and with reference to the accompanying drawings. It should be noted that, in the drawings or descriptions of the specification, similar or identical parts all use the same figure numbers. Implementations not shown or described in the accompanying drawings are forms known to those of ordinary skill in the art. Additionally, while illustrations of parameters including particular values may be provided herein, it should be understood that the parameters need not be exactly equal to the corresponding values, but rather may approximate the corresponding values within acceptable error margins or design constraints.

本发明提供的无源双频六端口器件采用印刷电路板形成平面微带形式的平面六端口电路，由一个双频威尔金森功分器和三个双频分支线耦合器组合形成，进一步，采用奇偶模分析法解析出所述功分器和耦合器的解析解，使其可以工作在任意的两个频率点f₁和f₂。The passive dual-frequency six-port device provided by the present invention uses a printed circuit board to form a planar six-port circuit in the form of a planar microstrip, which is formed by combining a dual-frequency Wilkinson power divider and three dual-frequency branch line couplers. Further, Analytical solutions of the power divider and coupler are obtained by using the odd-even mode analysis method, so that they can work at any two frequency points f ₁ and f ₂ .

在本发明的一个示例性实施例中，提供了一种无源双频六端口器件。图1显示了根据本发明示例性实施例的无源双频六端口器件的整体结构框图。In an exemplary embodiment of the present invention, a passive dual-frequency six-port device is provided. Fig. 1 shows a block diagram of the overall structure of a passive dual-frequency six-port device according to an exemplary embodiment of the present invention.

参照图1，本实施例的无源双频六端口器件形成在介质板上，包括双频威尔金森功分器A、第一双频分支线耦合器B、第二双频分支线耦合器C以及第三双频分支线耦合器D。Referring to Fig. 1, the passive dual-frequency six-port device of the present embodiment is formed on a dielectric board, including a dual-frequency Wilkinson power divider A, a first dual-frequency branch line coupler B, and a second dual-frequency branch line coupler C and the third dual-frequency branch line coupler D.

双频威尔金森功分器A的第一端口a1为输入端口，并作为本发明实施例的无源双频六端口器件的第一端口Port1；双频威尔金森功分器A第二端口a2和第三端口a3为输出端口，分别连接到双频分支线耦合器C、D的第二端口c2和d2。The first port a1 of the dual-frequency Wilkinson power divider A is an input port, and is used as the first port Port1 of the passive dual-frequency six-port device of the embodiment of the present invention; the second port of the dual-frequency Wilkinson power divider A a2 and the third port a3 are output ports, which are respectively connected to the second ports c2 and d2 of the dual-frequency branch line couplers C and D.

第一双频分支线耦合器B的第一端口b1作为无源双频六端口器件的第二端口Port2，第四端口b4通过50Ω的电阻负载连接到地，第一双频分支线耦合器B的第二端口b2和第三端口b3分别连接到双频分支线耦合器C、D的第三端口c3和d3。The first port b1 of the first dual-frequency branch line coupler B is used as the second port Port2 of the passive dual-frequency six-port device, and the fourth port b4 is connected to the ground through a 50Ω resistive load. The first dual-frequency branch line coupler B The second port b2 and the third port b3 of are respectively connected to the third ports c3 and d3 of the dual-frequency branch line couplers C and D.

第二双频分支线耦合器C的第二端口c2连接至双频威尔金森功分器A的第二端口a2，其第三端口c3连接至第一双频分支线耦合器B的第二端口b2，其第一端口c1和第四端口c4分别作为无源双频六端口器件的第四端口Port4和第六端口Port6；The second port c2 of the second dual-frequency branch line coupler C is connected to the second port a2 of the dual-frequency Wilkinson power divider A, and its third port c3 is connected to the second port of the first dual-frequency branch line coupler B. Port b2, the first port c1 and the fourth port c4 of which are respectively used as the fourth port Port4 and the sixth port Port6 of the passive dual-frequency six-port device;

第三双频分支线耦合器D的第二端口d2连接至双频威尔金森功分器A的第三端口a3，第三端口d3连接至第一双频分支线耦合器B的第三端口b3，其第一端口d1和第四端口d4分别作为无源双频六端口器件的第五端口Port5和第三端口Port3。The second port d2 of the third dual-frequency branch line coupler D is connected to the third port a3 of the dual-frequency Wilkinson power divider A, and the third port d3 is connected to the third port of the first dual-frequency branch line coupler B b3, its first port d1 and fourth port d4 serve as the fifth port Port5 and the third port Port3 of the passive dual-frequency six-port device respectively.

上述无源双频六端口器件中，第一端口Port1和第二端口Port2为输入端口，第三端口Port3、第四端口Port4、第五端口Port5和第六端口Port6为输出端口。In the above passive dual-frequency six-port device, the first port Port1 and the second port Port2 are input ports, and the third port Port3, the fourth port Port4, the fifth port Port5 and the sixth port Port6 are output ports.

本实施例中，双频威尔金森功分器A采用耦合线结构(详见图2、图3)。第一双频分支线耦合器B、第二双频分支线耦合器C和第三双频分支线耦合器D电路结构相同，均采用微带线结构(详见图4、图5)，优选的采用3dB双频分支线耦合器。由此，由双频威尔金森功分器A和三个双频分支线耦合器B、C、D形成的无源双频六端口器件实现了小型化、结构紧凑的六端口平面电路，易于单片微波集成技术(MMIC)进行集成。In this embodiment, the dual-frequency Wilkinson power divider A adopts a coupled line structure (see FIG. 2 and FIG. 3 for details). The circuit structures of the first dual-frequency branch line coupler B, the second dual-frequency branch line coupler C and the third dual-frequency branch line coupler D are identical, and all adopt a microstrip line structure (see Fig. 4 and Fig. 5 for details), preferably The use of 3dB dual-frequency branch line coupler. Thus, the passive dual-frequency six-port device formed by the dual-frequency Wilkinson power divider A and three dual-frequency branch line couplers B, C, and D realizes a miniaturized and compact six-port planar circuit, which is easy to Monolithic microwave integration technology (MMIC) for integration.

下面，分别对本发明优选实施例的无源双频六端口器件中各个组成部分进行详细说明。In the following, each component of the passive dual-frequency six-port device according to the preferred embodiment of the present invention will be described in detail.

本实施例中，介质板采用普通射频微波板材即可，无需价格高昂的高介电常数板材，批量生产成本很低。In this embodiment, the common radio frequency microwave plate can be used as the dielectric plate, and there is no need for an expensive high dielectric constant plate, and the mass production cost is very low.

图2为本发明的无源双频六端口器件中威尔金森功分器的等效电路原理图。图3为图2所示威尔金森功分器的平面结构示意图。FIG. 2 is a schematic diagram of an equivalent circuit of a Wilkinson power divider in the passive dual-frequency six-port device of the present invention. FIG. 3 is a schematic plan view of the Wilkinson power divider shown in FIG. 2 .

参照图2和图3，本发明实施例的无源双频六端口器件中，双频威尔金森功分器A包括：第一对耦合线cl₁，第一隔离电阻R₁，第二对耦合线cl₂以及第二隔离电阻R₂，三个端口均为标准的特征阻抗50Ω。Referring to Fig. 2 and Fig. 3, in the passive dual-frequency six-port device of the embodiment of the present invention, the dual-frequency Wilkinson power divider A includes: a first pair of coupling lines cl ₁ , a first isolation resistor R ₁ , a second pair of The coupling line cl ₂ and the second isolation resistor R ₂ , the three ports all have a standard characteristic impedance of 50Ω.

更进一步，参见图3，第一对耦合线cl₁彼此平行，其左端相连接并端接引线l₀作为双频威尔金森功分器A的第一端口a1，也即无源双频六端口器件的第一端口Port1。引线l₀的长度为l₀，宽度为w₀。第一对耦合线cl₁的间距为cs₁，每根耦合线的宽度为cw₁，长度为cl₁。这里，端口引线l₀的作用是方便端口标准为50Ω的测量仪器测量，以及方便功分器和耦合器之间的连接，满足匹配条件。以下端口设置的端接引线l₀作用相同。Further, referring to Fig. 3, the first pair of coupling lines cl ₁ are parallel to each other, and the left ends thereof are connected and terminated with lead wire 1 ₀ as the first port a1 of the dual-frequency Wilkinson power divider A, that is, the passive dual-frequency six The first port Port1 of the port device. The length of lead l ₀ is l ₀ and the width is w ₀ . The distance between the first pair of coupled lines cl ₁ is cs ₁ , the width of each coupled line is cw ₁ , and the length is cl ₁ . Here, the role of the port lead _l0 is to facilitate the measurement of the measuring instrument whose port standard is 50Ω, and to facilitate the connection between the power divider and the coupler to meet the matching conditions. Termination leads l ₀ for the following port settings have the same effect.

第一隔离电阻R₁连接于第一对耦合线的右端之间。The _first isolation resistor R1 is connected between right ends of the first pair of coupled lines.

第二对耦合线cl₂彼此平行，其左端级联于第一对耦合线的右端(即第二对耦合线cl₂的每一根的左端连接到第一对耦合线的每一根的右端)。第二对耦合线cl₂的右端分别端接引线l₀作为双频威尔金森功分器A的第二端口a2和第三端口a3。引线l₀的长度为l₀，宽度为w₀。第二对耦合线cl₂的间距为cs₂，每根耦合线的宽度为cw₂，长度为cl₂。The _second pair of coupled lines cl2 are parallel to each other, and its left end is cascaded to the right end of the first pair of coupled lines (that is, the left end of each of the _second pair of coupled lines cl2 is connected to the right end of each of the first pair of coupled lines ). The right ends of the _second pair of coupled lines cl2 are respectively terminated with leads _l0 as the second port a2 and the third port a3 of the dual-frequency Wilkinson power splitter A. The length of lead l ₀ is l ₀ and the width is w ₀ . The distance between the second pair of coupled lines cl ₂ is cs ₂ , the width of each coupled line is cw ₂ , and the length is cl ₂ .

第二隔离电阻R₂连接在第二对耦合线cl₂的右端之间。The _second isolation resistor R2 is connected between the right ends of the _second pair of coupled lines cl2.

为了实现双频功率等分同向输出且两个工作频率可任意设置，图2和图3所示的双频威尔金森功分器中的各个参数满足下述条件：In order to achieve dual-frequency power equalization and output in the same direction and the two operating frequencies can be set arbitrarily, each parameter in the dual-frequency Wilkinson power divider shown in Figure 2 and Figure 3 meets the following conditions:

${Z Z}_{e e 11} = = {Z Z}_{o o} \sqrt{\frac{\sqrt{11 + + 88 {tan the tan}^{44} {θ θ}_{11}} - - 11}{{tan the tan}^{22} {θ θ}_{11}}} - - - - - - ((11))$

${Z Z}_{e e 22} = = {Z Z}_{o o} \sqrt{\frac{\sqrt{11 + + 88 {tan the tan}^{44} {θ θ}_{11}} + + 11}{22 {tan the tan}^{22} {θ θ}_{11}}} - - - - - - ((22))$

${R R}_{11} = = \frac{22 {Z Z}_{o o 11} {Z Z}_{o o 22} {tan the tan}^{22} {θ θ}_{11}}{\sqrt{(({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} (({Z Z}_{o o 11} {tan the tan}^{22} {θ θ}_{11} - - {Z Z}_{o o 22}))}} - - - - - - ((33))$

${R R}_{22} = = \frac{22 {Z Z}_{o o} {Z Z}_{o o 22}^{22} (({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} + + 22 {Z Z}_{o o}^{22} {Z Z}_{o o 22} \sqrt{(({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} (({Z Z}_{o o 11} {tan the tan}^{22} {θ θ}_{11} - - {Z Z}_{o o 22}))}}{{Z Z}_{o o}^{22} {Z Z}_{o o 22} + + (({Z Z}_{o o 11} {Z Z}_{o o 22}^{22} - - {Z Z}_{o o}^{22} {Z Z}_{o o 11} + + {Z Z}_{o o 22}^{33})) {tan the tan}^{22} {θ θ}_{11}} - - - - - - ((44))$

其中，f₁和f₂分别为两个工作频率，g＝f₂/f₁为频率比，Z_e1为第一对耦合线的偶模特征阻抗，Z_e2为第二对耦合线的偶模特征阻抗，R₁,R₂为第一隔离电阻和第二隔离电阻的阻值，Z_o为引线l₀的特征阻抗，优选为标准的50欧姆阻抗，θ₁为两对耦合线的电长度，Z_o1,Z_o2为独立变量，分别为第一对耦合线和第二对耦合线的奇模特征阻抗，通常满足Z_o1＜Z_e1＜1.5Z_o，₁Z_o2＜Z_e2＜1.5Z_o2的条件。在微带线可以实现的范围内，可以取20Ω＜Z_e1，Z_e2＜150Ω，20Ω＜Z_o1，Z_o2＜120Ω。Among them, f ₁ and f ₂ are two operating frequencies respectively, g=f ₂ /f ₁ is the frequency ratio, Z _e1 is the even mode characteristic impedance of the first pair of coupled lines, Z _e2 is the even mode of the second pair of coupled lines Characteristic impedance, R ₁ , R ₂ are the resistance values of the first isolation resistor and the second isolation resistor, Z _o is the characteristic impedance of the lead wire ₁₀ , preferably a standard 50 ohm impedance, and θ ₁ is the electrical length of the two pairs of coupled lines , Z _o1 , Z _o2 are independent variables, respectively the odd-mode characteristic impedance of the first pair of coupled lines and the second pair of coupled lines, usually satisfying Z _o1 <Z _e1 <1.5Z _o , ₁ Z _o2 <Z _e2 <1.5Z The condition of _o2 . Within the range that can be realized by the microstrip line, 20Ω<Z _e1 , Z _e2 <150Ω, 20Ω<Z _o1 , Z _o2 <120Ω can be set.

本发明的实施例中，第一对耦合线和第二对耦合线均采用耦合线结构，并且第一隔离电阻R₁和第二隔离电阻R₂采用贴片电阻的形式。采用耦合线结构和贴片电阻结构使该双频威尔金森功分器A的电路结构更加紧凑。In the embodiment of the present invention, both the first pair of coupled lines and the second pair of coupled lines adopt a coupled line structure, and the first isolation resistor R ₁ and the second isolation resistor R ₂ are in the form of chip resistors. The circuit structure of the dual-frequency Wilkinson power divider A is more compact by adopting the coupled line structure and the patch resistor structure.

本实施例中，第一双频分支线耦合器B、第二双频分支线耦合器C和第三双频分支线耦合器D为具有相同结构的双频分支线耦合器，所有端口均为标准的特征阻抗50Ω。In this embodiment, the first dual-frequency branch line coupler B, the second dual-frequency branch line coupler C and the third dual-frequency branch line coupler D are dual-frequency branch line couplers with the same structure, and all ports are The standard characteristic impedance is 50Ω.

图4为本发明的无源双频六端口器件中双频分支线耦合器的等效电路原理图。图5为图4所示双频分支线耦合器的平面结构示意图。FIG. 4 is a schematic diagram of an equivalent circuit of a dual-frequency branch line coupler in the passive dual-frequency six-port device of the present invention. FIG. 5 is a schematic plan view of the dual-frequency branch line coupler shown in FIG. 4 .

参照图4和图5，本发明的实施例中，双频分支线耦合器B、C、D具有相同的结构，下面以第一双频分支线耦合器B为例进行介绍，具体包括分支线耦合器、以及在分支线耦合器的4个端口的每一个级联连接的第一双频阻抗匹配微带线l_a、第二双频阻抗匹配微带线l_b以及引线l₀。Referring to Fig. 4 and Fig. 5, in the embodiment of the present invention, the dual-frequency branch line couplers B, C, and D have the same structure, and the first dual-frequency branch line coupler B is taken as an example for introduction below, specifically including the branch line The coupler, and the first dual-frequency impedance-matching microstrip line 1 _a , the second dual-frequency impedance-matching microstrip line 1 _b and the lead 1 ₀ cascadedly connected to each of the 4 ports of the branch line coupler.

分支线耦合器，包括沿第一方向平行设置的第一对微带线l₂，沿与第一方向垂直的第二方向平行设置的第二对微带线l₃。如图5所示，第一对微带线l₂的长度为l₂，宽度为w₂，第二对微带线l₃的长度为l₃，宽度为w₃。第一对微带线l₂与第二对微带线l₃彼此级联连接，形成方形结构的分支线耦合器。The branch line coupler includes a first pair of microstrip lines l ₂ arranged in parallel along a first direction, and a second pair of microstrip lines l ₃ arranged in parallel along a second direction perpendicular to the first direction. As shown in FIG. 5 , the length of the first pair of microstrip lines l ₂ is l ₂ and the width is w ₂ , and the length of the second pair of microstrip lines l ₃ is l ₃ and the width is w ₃ . The first pair of microstrip lines ₁₂ and the second pair of microstrip lines ₁₃ are connected in cascade to form a branch line coupler with a square structure.

进一步，如图4和图5所示，分支线耦合器的4个端口上分别连接有级联的第一双频阻抗匹配微带线l_a和第二双频阻抗匹配微带线l_b。微带线l_a的长度为l_a，宽度为w_a，微带线l_b的长度为l_b，宽度为w_b。Further, as shown in FIG. 4 and FIG. 5 , the four ports of the branch line coupler are respectively connected with the cascaded first dual-frequency impedance matching microstrip line 1 _a and the second dual-frequency impedance matching microstrip line 1 _b . The length of the microstrip line l _a is _la and the width is w _a , the length of the microstrip line l _b is l _b and the width is w _b .

更进一步，每个端口处的第二双频阻抗匹配微带线l_b均连接到一引线l₀，引线l₀也形成为微带线，其长度为l₀，宽度为w₀。引线l₀平行的连接到每个端口的第二双频阻抗匹配微带线l_b上，形成第一双频分支线耦合器B的4个端口b1、b2、b3、和b4。Furthermore, the second dual-frequency impedance matching microstrip line l _b at each port is connected to a lead line l ₀ , and the lead line l ₀ is also formed as a microstrip line with a length of l ₀ and a width of w ₀ . The leads _l0 are connected in parallel to the second dual-frequency impedance matching microstrip line lb of each port, forming four ports _b1 , b2, b3, and b4 of the first dual-frequency branch line coupler B.

参见图4，第一对微带线l₂的特征阻抗为Z₂，第二对微带线l₃的特征阻抗为Z₃，第一双频阻抗匹配微带线l_a的特征阻抗为Z_a，第二双频阻抗匹配微带线l_b的特征阻抗为Z_b，引线l₀的特征阻抗为Z₀，上述所有微带线的电长度均为θ。Referring to Fig. 4, the characteristic impedance of the first pair of microstrip lines l ₂ is Z ₂ , the characteristic impedance of the second pair of microstrip lines 1 ₃ is Z ₃ , and the characteristic impedance of the first dual-frequency impedance matching microstrip line 1 _a is Z _a , the characteristic impedance of the second dual-frequency impedance matching microstrip line _lb is _Zb , the characteristic impedance of the lead line _l0 is _Z0 , and the electrical length of all the above microstrip lines is θ.

分支线耦合器由彼此垂直的第一对微带线l₂和第二对微带线l₃组成传统的3dB分支线耦合器，其四个端口分别级联连接第一双频阻抗匹配微带线l_a和第二双频阻抗匹配微带线l_b。整体结构上下对称，左右对称，实现了双频功率等分、90度相位差输出且两个工作频率任意的分支线耦合器。采用耦合线结构和贴片电阻结构使该分支线耦合器的电路结构更加紧凑。The branch line coupler consists of the first pair of microstrip lines l ₂ and the second pair of microstrip lines l ₃ which are perpendicular to each other to form a traditional 3dB branch line coupler, and its four ports are cascaded to connect the first dual-frequency impedance matching microstrip Line l _a and the second dual-frequency impedance matching microstrip line l _b . The overall structure is symmetrical up and down and left and right, realizing dual-frequency power equalization, 90-degree phase difference output, and two branch line couplers with arbitrary operating frequencies. The circuit structure of the branch line coupler is more compact by adopting the coupling line structure and the patch resistor structure.

为了实现分支线耦合器的第二输出端口和第三输出端口(例如第一双频分支线耦合器B的端口b2和b3，其他双频分支线耦合器C、D类似)等幅，具有90度相位差且可以工作在两个任意频率，图4和图5所示的分支线耦合器中各个参数应当满足：In order to realize the equal amplitude of the second output port and the third output port of the branch line coupler (for example, the ports b2 and b3 of the first dual-frequency branch line coupler B, other dual-frequency branch line couplers C, D are similar), with 90 degree phase difference and can work at two arbitrary frequencies, each parameter in the branch line coupler shown in Figure 4 and Figure 5 should satisfy:

${Z Z}_{22} = = \sqrt{22} {Z Z}_{33} - - - - - - ((55))$

${Z Z}_{a a} = = \frac{- - H h &PlusMinus; &PlusMinus; \sqrt{{H h}^{22} - - 44 F f K K}}{22 F f} - - - - - - ((66))$

${Z Z}_{b b} = = - - \frac{B B}{44 A A} + + \frac{11}{22} \sqrt{((\frac{{B B}^{22}}{44 {A A}^{22}} - - \frac{22 C C}{33 A A} + + {Δ Δ}_{11} + + {Δ Δ}_{22}))} + + \frac{11}{22} \sqrt{((\frac{{B B}^{22}}{22 {A A}^{22}} - - \frac{44 C C}{33 A A} {Δ Δ}_{11} {Δ Δ}_{22} + + \frac{44 A A B B C C - - {B B}^{33} - - 88 {A A}^{22} D D.}{44 {A A}^{33} \sqrt{((\frac{{B B}^{22}}{44 {A A}^{22}} - - \frac{22 C C}{33 A A} + + {Δ Δ}_{11} + + {Δ Δ}_{22}))}}))} - - - - - - ((77))$

其中：in:

${R R}_{i i n no} = = \frac{\sqrt{(({Z Z}_{22}^{22} - - {Z Z}_{33}^{22})) {Z Z}_{22}^{22} {Z Z}_{33}^{22} {sin sin}^{22} ((θ θ))}}{(({Z Z}_{22} + + {Z Z}_{33})) [[{Z Z}_{22} - - {Z Z}_{33} + + (({Z Z}_{22} + + {Z Z}_{33})) {cos cos}^{22} ((θ θ))]]} - - - - - - ((88))$

${X x}_{i i n no} = = \frac{(({Z Z}_{22} + + {Z Z}_{33})) {Z Z}_{22} {Z Z}_{33} c c o o s the s ((θ θ)) s the s i i n no ((θ θ))}{(({Z Z}_{22} + + {Z Z}_{33})) [[{Z Z}_{22} - - {Z Z}_{33} + + (({Z Z}_{22} + + {Z Z}_{33})) {cos cos}^{22} ((θ θ))]]} - - - - - - ((99))$

A＝R_in(Z_o-R_in)tan²(θ) (10)A＝R _in (Z _o -R _in )tan ² (θ) (10)

B＝2Z_oR_inX_in tan³(θ) (11)B＝2Z _o R _in X _in tan ³ (θ) (11)

$C C = = (({R R}_{i i n no} - - {Z Z}_{o o})) (({Z Z}_{o o} {R R}_{i i n no}^{22} + + {Z Z}_{o o} {X x}_{i i n no}^{22} - - {Z Z}_{o o}^{22} {R R}_{i i n no})) - - [[22 + + {tan the tan}^{22} ((θ θ))]] {tan the tan}^{22} ((θ θ)) {Z Z}_{o o}^{22} {X x}_{i i n no}^{22} - - - - - - ((1212))$

$D D. = = - - 22 {Z Z}_{o o}^{33} {R R}_{i i n no} {X x}_{i i n no} {tan the tan}^{33} ((θ θ)) - - - - - - ((1313))$

$E E. = = {Z Z}_{o o}^{33} {R R}_{i i n no} (({R R}_{i i n no}^{22} + + {X x}_{i i n no}^{22} - - {Z Z}_{o o} {R R}_{i i n no})) {tan the tan}^{22} ((θ θ)) - - - - - - ((1414))$

F＝-Z_o tan²(θ) (15)F＝-Z _o tan ² (θ) (15)

H＝(Z_o-R_in)Z_b-Z_oX_in tan(θ) (16)H＝(Z _o -R _in )Z _b -Z _o X _in tan(θ) (16)

$K K = = {R R}_{i i n no} {Z Z}_{b b}^{22} {tan the tan}^{22} ((θ θ)) - - {Z Z}_{o o} {X x}_{i i n no} {Z Z}_{b b} t t a a n no ((θ θ)) - - - - - - ((1717))$

${Δ Δ}_{11} = = (\begin{matrix} \frac{\sqrt[33]{22} (({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}{33 A A [[22 {C C}^{33} - - 99 B B C C D D. + + 2727 {AD AD}^{22} + + 2727 {B B}^{22} E E. - - 7272 A A C C E E.} \\ + + \sqrt{- - 44 {(({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}^{33} + + {((22 {C C}^{33} - - 99 B B C C D D. + + 2727 {AD AD}^{22} + + 2727 {B B}^{22} E E. - - 7272 A A C C E E.))}^{22}} {]]}^{11 / / 33} \end{matrix}) - - - - - - ((1818))$

${Δ Δ}_{22} = = \frac{(({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}{{Δ Δ}_{11} {((33 A A))}^{22}} - - - - - - ((1919))$

其中，Z₂,Z₃分别为第一对微带线l₂和第二对微带线l₃的特征阻抗，Z_a,Z_b分别为每个端口的第一双频阻抗匹配微带线l_a和第二双频阻抗匹配微带线l_b的特征阻抗，Z_o为引线l₀的特征阻抗，通常为标准的50欧姆阻抗，θ为微带线l₂、l₃、l_a、l_b的电长度，Z₃为独立变量。在微带线可以实现的范围内，取20Ω＜Z_i＜120Ω(其中i＝a,b,2,3)。Among them, Z ₂ , Z ₃ are the characteristic impedances of the first pair of microstrip lines l ₂ and the second pair of microstrip lines 1 ₃ respectively, Z _a , Z _b are the first dual-frequency impedance matching microstrip lines of each port l _a and the second dual-frequency impedance match the characteristic impedance of the microstrip line l _b , Z _o is the characteristic impedance of the lead l ₀ , usually a standard 50 ohm impedance, θ is the microstrip line l ₂ , l ₃ , l _a , The electrical length of l _b , Z ₃ is an independent variable. Within the range that can be realized by the microstrip line, 20Ω<Z _i <120Ω (where i=a, b, 2, 3) is taken.

请参照图1，本实施例中，第一双频分支线耦合器B的第四端口b4接50欧姆负载。第二双频分支线耦合器C和第三双频分支线耦合器D的四个输出端口，即整个无源双频六端口器件的第三端口Port3、第四端口Port4、第五端口Port5和第六端口Port6均可以接二级管功率检测计从而测试其输出功率。Please refer to FIG. 1 , in this embodiment, the fourth port b4 of the first dual-frequency branch line coupler B is connected to a 50-ohm load. Four output ports of the second dual-frequency branch line coupler C and the third dual-frequency branch line coupler D, that is, the third port Port3, the fourth port Port4, the fifth port Port5 and the whole passive dual-frequency six-port device The sixth port, Port6, can be connected to a diode power detector to test its output power.

如上所述，根据本发明实施例的无源双频六端口器件，采用奇偶模分析法解析出功分器和耦合器的解析解，使其可以工作在任意的两个频率点(f₁、f₂)。进一步，采用平面微带线的形式实现该器件，从而克服了左右手传输线在两个工作频率上输出端口的相位差相反的缺点。As mentioned above, according to the passive dual-frequency six-port device of the embodiment of the present invention, the analytical solution of the power divider and the coupler is analyzed by using the odd-even mode analysis method, so that it can work at any two frequency points (f ₁ , f2 ₎ . Furthermore, the device is implemented in the form of a planar microstrip line, thereby overcoming the disadvantage that the phase difference between the output ports of the left and right hand transmission lines is opposite at two operating frequencies.

下面介绍本发明无源双频六端口器件的一个优选实施例。所述优选实施例是根据上述结构和理论计算式为基础，通过多次仿真测试，然后经过多次实际的测量和调试后得到，代表本发明的无源双频六端口器件的一个优选实施方案，但不能认为是对本发明的限制，凡是满足所述公式的实例都应在保护范围之列。A preferred embodiment of the passive dual-frequency six-port device of the present invention is introduced below. The preferred embodiment is based on the above-mentioned structure and theoretical calculation formula, obtained after multiple simulation tests, and then through multiple actual measurements and debugging, representing a preferred implementation of the passive dual-frequency six-port device of the present invention , but can not be considered as a limitation of the present invention, and all examples satisfying the formula should be included in the scope of protection.

本发明优选实施例的无源双频六端口器件的参数如下：Z_e1＝81.5769Ω，Z_o1＝43.3340Ω，Z_e2＝61.2918Ω，Z_o2＝40.1384Ω，R₁＝63.0738Ω,R₂＝565.1966Ω,Z_a＝41.5501Ω，Z_b＝74.7131Ω。Z₂＝42.4264Ω，Z₃＝30Ω，θ₁＝θ＝90°(f₀＝4GHz)。此时，无源双频六端口器件的两个工作频率分别为f₁＝3GHz，f₂＝5GHz。The parameters of the passive dual-frequency six-port device in the preferred embodiment of the present invention are as follows: Z _e1 =81.5769Ω, Z _o1 =43.3340Ω, Z _e2 =61.2918Ω, Z _o2 =40.1384Ω, R ₁ =63.0738Ω, R ₂ = 565.1966Ω, Z _a =41.5501Ω, Z _b =74.7131Ω. Z ₂ =42.4264Ω, Z ₃ =30Ω, θ ₁ =θ=90° (f ₀ =4GHz). At this time, the two operating frequencies of the passive dual-frequency six-port device are respectively f ₁ =3 GHz and f ₂ =5 GHz.

对于图3和图5所示的威尔金森功分器和分支线耦合器的器件结构，在基于相对介电常数为3.48，厚度为0.762mm的罗杰斯R04350B板材通过使用微带线计算工具，可以得到实际电路的参数：w₀＝2.73mm，l₀＝10mm，cw₁＝1.26mm，cs₁＝0.42mm，cl₁＝11.98mm，cw₂＝1.94mm，cs₂＝0.63mm，cl₂＝11.61mm，w_a＝3.01mm，l_a＝11.12mm w_b＝1.10mm，l_b＝11.58mm，w₂＝2.92mm，l₂＝11.13mm，w₃＝4.75mm，l₃＝10.89mm。For the device structure of the Wilkinson power divider and branch line coupler shown in Figure 3 and Figure 5, based on the Rogers R04350B plate with a relative permittivity of 3.48 and a thickness of 0.762mm, by using the microstrip line calculation tool, it can be The parameters of the actual circuit are obtained: w ₀ =2.73mm, l ₀ =10mm, cw ₁ =1.26mm, cs ₁ =0.42mm, cl ₁ =11.98mm, cw ₂ =1.94mm, cs ₂ =0.63mm, cl ₂ = 11.61 mm, w _a =3.01 mm, l _a =11.12 mm, w _b =1.10 mm, l _b =11.58 mm, w ₂ =2.92 mm, l ₂ =11.13 mm, w ₃ =4.75 mm, l ₃ =10.89 mm.

图6A～图6C为本发明无源双频六端口器件的理想模型仿真结果图。图7A～图7C为本发明优选实施例的无源双频六端口器件的物理模型仿真结果图。对比图6A和图7A可以看到，本发明优选实施例的无源双频六端口器件在两个工作频率处的输入端口具有很好地匹配和隔离，均已经达到-20dB以下。对比图6B和图7B可以看到，本发明优选实施例的无源双频六端口器件在两个工作频率处的输出端口的幅度相等，理想的幅度值为-6.021dB，物理模型仿真图接近理想的幅度值。从图6C和图7C中可以看到，本发明优选实施例的无源双频六端口器件在两个工作频率处的输出端口的相位差相同。6A to 6C are simulation results of an ideal model of the passive dual-frequency six-port device of the present invention. 7A to 7C are diagrams showing simulation results of a physical model of a passive dual-frequency six-port device according to a preferred embodiment of the present invention. Comparing Fig. 6A and Fig. 7A, it can be seen that the input ports of the passive dual-frequency six-port device in the preferred embodiment of the present invention have good matching and isolation at two operating frequencies, both of which have reached below -20dB. Comparing Fig. 6B and Fig. 7B, it can be seen that the amplitudes of the output ports at the two operating frequencies of the passive dual-frequency six-port device of the preferred embodiment of the present invention are equal, the ideal amplitude value is -6.021dB, and the physical model simulation diagram is close to Ideal amplitude value. It can be seen from FIG. 6C and FIG. 7C that the phase difference of the output ports at the two operating frequencies of the passive dual-frequency six-port device according to the preferred embodiment of the present invention is the same.

表Ⅰ和表Ⅱ显示了在两个不同工作频率的散射参数幅度和相位小结。Tables I and II show a summary of the magnitude and phase of the scattering parameters at two different operating frequencies.

表ⅠTable I

从表Ⅰ中可以看出对于理想仿真电路，对于两个工作频率具有相同的相位差，S₄₂与S₃₂之间的相位差为0°，S₅₂与S₃₂之间的相位差为-90°，S₆₂与S₃₂之间的相位差为90°。It can be seen from Table I that for an ideal simulation circuit, the two operating frequencies have the same phase difference, the phase difference between S ₄₂ and S ₃₂ is 0°, and the phase difference between S ₅₂ and S ₃₂ is -90 °, the phase difference between S ₆₂ and S ₃₂ is 90°.

表ⅡTable II

从表Ⅱ中可以看出，对于物理模型仿真电路，对两个工作频率具有相近的相位差，在f＝3GHz分别为0.001°、-90.232°、90.063°，在f＝5GHz分别为0.138°、-89.725°、89.34°。可见，本发明优选实施例的无源双频六端口器件充分接近理想模型的参数指标，实现了本发明的目的。It can be seen from Table II that for the physical model simulation circuit, the two operating frequencies have similar phase differences, which are 0.001°, -90.232°, and 90.063° at f=3GHz, and 0.138°, -90.063° at f=5GHz, respectively. -89.725°, 89.34°. It can be seen that the passive dual-frequency six-port device in the preferred embodiment of the present invention is sufficiently close to the parameter index of the ideal model, and achieves the purpose of the present invention.

至此，已经结合附图对本实施例进行了详细描述。依据以上描述，本领域技术人员应当对本发明的无源双频六端口器件有了清楚的认识。So far, the present embodiment has been described in detail with reference to the drawings. According to the above description, those skilled in the art should have a clear understanding of the passive dual-frequency six-port device of the present invention.

综上所述，本发明提供一种平面微带结构的无源双频六端口器件，克服了左右手传输线在两个工作频率上输出端口的相位差相反的缺点，实现四个输出端口幅度等分。同时，该无源双频六端口器件还具有结构简单、造价低、尺寸小、工作频率宽、在两个工作频率输出端口在两个频率内的相位差相同等优点，具有良好的推广应用前景。In summary, the present invention provides a passive dual-frequency six-port device with a planar microstrip structure, which overcomes the shortcoming that the output ports of the left and right hand transmission lines have opposite phase differences at two operating frequencies, and realizes four output ports with equal amplitudes. . At the same time, the passive dual-frequency six-port device also has the advantages of simple structure, low cost, small size, wide operating frequency, and the same phase difference between the two operating frequency output ports within two frequencies, etc., and has a good prospect for popularization and application .

以上所述的具体实施例，对本发明的目的、技术方案和有益效果进行了进一步详细说明，所应理解的是，以上所述仅为本发明的具体实施例而已，并不用于限制本发明，凡在本发明的精神和原则之内，所做的任何修改、等同替换、改进等，均应包含在本发明的保护范围之内。The specific embodiments described above have further described the purpose, technical solutions and beneficial effects of the present invention in detail. It should be understood that the above descriptions are only specific embodiments of the present invention and are not intended to limit the present invention. Any modifications, equivalent replacements, improvements, etc. made within the spirit and principles of the present invention shall be included within the protection scope of the present invention.

Claims

1. A passive dual-frequency six-port device, characterized in that, comprising:

A dual-frequency Wilkinson power splitter (A), the first port (a1) of which is used as the first port (Port1) of a passive dual-frequency six-port device;

The first dual-frequency branch line coupler (B), its first port (b1) is used as the second port (Port2) of the passive dual-frequency six-port device, and the fourth port (b4) is connected to the ground through a 50Ω load;

The second dual-frequency branch line coupler (C), its second port (c2) is connected to the second port (a2) of the dual-frequency Wilkinson power divider (A), and the third port (c3) is connected to The second port (b2) of the first dual-frequency branch line coupler (B), the first port (c1) and the fourth port (c4) are respectively used as the fourth port of the passive dual-frequency six-port device ( Port4) and the sixth port (Port6);

The third dual-frequency branch line coupler (D), its second port (d2) is connected to the third port (a3) of the dual-frequency Wilkinson power divider (A), and the third port (d3) is connected to The third port (b3) of the first dual-frequency branch line coupler (B), the first port (d1) and the fourth port (d4) are respectively used as the fifth port of the passive dual-frequency six-port device ( Port5) and the third port (Port3);

In the passive dual-frequency six-port device, the first port (Port1) and the second port (Port2) are input ports, and the third port (Port3), the fourth port (Port4), the fifth port ( Port5) and the sixth port (Port6) are output ports;

The first dual-frequency branch line coupler (B), the second dual-frequency branch line coupler (C), and the third dual-frequency branch line coupler (D) respectively include branch line couplers (l ₂ , l ₃ ), and the first dual-frequency impedance matching microstrip line (l _a ), the second dual-frequency impedance matching microstrip line (l _b ) and lead wires cascaded at each of the 4 ports of the branch line coupler (l ₀ );

The branch line coupler (l ₂ , l ₃ ) includes a first pair of microstrip lines (l ₂ ) arranged in parallel along a first direction, and a second pair of microstrip lines arranged in parallel along a second direction perpendicular to the first direction. stripline(l ₃ );

The characteristic impedance Z _i of all the above microstrip lines satisfies: 20Ω<Z _i <120Ω, where i=a, b, 2,3.

2. passive dual-frequency six-port device according to claim 1, is characterized in that, described dual-frequency Wilkinson power divider (A) comprises:

The first pair of coupling lines (cl ₁ ) arranged parallel to each other, the left ends of which are connected to each other as the first port (a1) of the dual-frequency Wilkinson power divider A;

A first isolation resistor (R ₁ ), connected between the right ports of the first pair of coupled lines;

The second pair of coupled lines (cl ₂ ) arranged in parallel to each other, the left end of which is cascaded to the right end of the first pair of coupled lines, and its right end serves as the second port (a2) and a third port (a3); and

The second isolation resistor (R ₂ ) is connected between the right ports of the second pair of coupled lines.

3. The passive dual-frequency six-port device according to claim 2, wherein,

The left end of the first pair of coupled lines (cl ₁ ) is connected to a lead wire (l ₀ ) to form a first port (a1) of a dual-frequency Wilkinson power divider (A); and

The two ports on the right end of the second pair of coupled lines (cl ₂ ) are respectively connected to two lead wires (l ₀ ) of the same length to respectively form the second port (a2) of the dual-frequency Wilkinson power splitter (A) ) and the third port (a3).

4. passive dual-frequency six-port device according to claim 3, is characterized in that, the parameter in described dual-frequency Wilkinson power splitter (A) satisfies the following conditions:

{Z Z}_{e e 11} = = {Z Z}_{o o} \sqrt{\frac{\sqrt{11 + + 88 {tan the tan}^{44} {θ θ}_{11}} - - 11}{{tan the tan}^{22} {θ θ}_{11}}},,

{Z Z}_{e e 22} = = {Z Z}_{o o} \sqrt{\frac{\sqrt{11 + + 88 {tan the tan}^{44} {θ θ}_{11}} + + 11}{22 {tan the tan}^{22} {θ θ}_{11}}},,

{R R}_{11} = = \frac{22 {Z Z}_{o o 11} {Z Z}_{o o 22} {tan the tan}^{22} {θ θ}_{11}}{\sqrt{(({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} (({Z Z}_{o o 11} {tan the tan}^{22} {θ θ}_{11} - - {Z Z}_{o o 22}))}},,

{R R}_{22} = = \frac{22 {Z Z}_{o o} {Z Z}_{o o 22}^{22} (({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} + + 22 {Z Z}_{o o}^{22} {Z Z}_{o o 22} \sqrt{(({Z Z}_{o o 11} + + {Z Z}_{o o 22})) {tan the tan}^{22} {θ θ}_{11} (({Z Z}_{o o 11} {tan the tan}^{22} {θ θ}_{11} - - {Z Z}_{o o 22}))}}{{Z Z}_{o o}^{22} {Z Z}_{o o 22} + + (({Z Z}_{o o 11} {Z Z}_{o o 22}^{22} - - {Z Z}_{o o}^{22} {Z Z}_{o o 11} + + {Z Z}_{o o 22}^{33})) {tan the tan}^{22} {θ θ}_{11}},,

Wherein, f ₁ and f ₂ are two operating frequencies respectively, Z _e1 is the even-mode characteristic impedance of the first pair of coupled lines, Z _e2 is the even-mode characteristic impedance of the second pair of coupled lines, R ₁ , R ₂ is the resistance value of the first isolation resistor and the second isolation resistor, Z _o is the characteristic impedance of the lead wire (l ₀ ), θ ₁ is the electrical length of the first pair of coupled lines and the second pair of coupled lines, Z _o1 , Z _o2 are the odd-mode characteristic impedances of the first pair of coupled lines and the second pair of coupled lines, respectively.

5. passive dual-frequency six-port device according to claim 4, the parameter in the described dual-frequency Wilkinson power divider (A) further satisfies the following conditions:

Z _o1 <Z _e1 <1.5Z _o1 , Z _o2 <Z _e2 <1.5Z _o2 ;

20Ω<Z _e1 , Z _e2 <150Ω, 20Ω<Z _o1 , Z _o2 <120Ω; and

Z _o =50Ω.

6. The passive dual-frequency six-port device according to claim 1, the first dual-frequency branch line coupler (B), the second dual-frequency branch line coupler (C) and the third dual-frequency branch line coupling Devices (D) are dual-frequency branch line couplers with the same structure, and each of the dual-frequency branch line couplers includes: branch line couplers (l ₂ , l ₃ ), at the 4 ports of the branch line couplers The first dual-frequency impedance matching microstrip line (l _a ), the second dual-frequency impedance matching microstrip line (l _b ) and the lead wire (l ₀ ) are connected in cascade respectively.

7. The passive dual-frequency six-port device according to claim 1 or 6, wherein,

The branch line coupler includes a first pair of microstrip lines (l ₂ ) arranged in parallel along a first direction, and a second pair of microstrip lines (l ₃ ) arranged in parallel along a second direction perpendicular to the first direction;

Each said lead wire (l ₀ ) is connected to a second dual frequency impedance matching microstrip line (l _b ) of each port, forming 4 ports of each dual frequency branch line coupler.

8. passive dual-frequency six-port device according to claim 7, is characterized in that, the parameter of each described dual-frequency branch line coupler satisfies the following conditions:

{Z Z}_{22} = = \sqrt{22} {Z Z}_{33},,

{Z Z}_{a a} = = \frac{- - H h &PlusMinus; &PlusMinus; \sqrt{{H h}^{22} - - 44 F f K K}}{22 F f},,

{Z Z}_{b b} = = - - \frac{B B}{44 A A} + + \frac{11}{22} \sqrt{((\frac{{B B}^{22}}{44 {A A}^{22}} - - \frac{22 C C}{33 A A} + + {Δ Δ}_{11} + + {Δ Δ}_{22}))} + + \frac{11}{22} \sqrt{((\frac{{B B}^{22}}{22 {A A}^{22}} - - \frac{44 C C}{33 A A} - - {Δ Δ}_{11} - - {Δ Δ}_{22} + + \frac{44 A A B B C C - - {B B}^{33} - - 88 {A A}^{22} D D.}{44 {A A}^{33} \sqrt{((\frac{{B B}^{22}}{44 {A A}^{22}} - - \frac{22 C C}{33 A A} + + {Δ Δ}_{11} + + {Δ Δ}_{22}))}}))},,

{R R}_{i i n no} = = \frac{\sqrt{(({Z Z}_{22}^{22} - - {Z Z}_{33}^{22})) {Z Z}_{22}^{22} {Z Z}_{33}^{22} {sin sin}^{22} ((θ θ))}}{(({Z Z}_{22} + + {Z Z}_{33})) [[{Z Z}_{22} - - {Z Z}_{33} + + (({Z Z}_{22} + + {Z Z}_{33})) {cos cos}^{22} ((θ θ))]]},,

{X x}_{i i n no} = = \frac{(({Z Z}_{22} + + {Z Z}_{33})) {Z Z}_{22} {Z Z}_{33} c c o o s the s ((θ θ)) s the s i i n no ((θ θ))}{(({Z Z}_{22} + + {Z Z}_{33})) [[{Z Z}_{22} - - {Z Z}_{33} + + (({Z Z}_{22} + + {Z Z}_{33})) {cos cos}^{22} ((θ θ))]]},,

A＝R _in (Z _o -R _in )tan ² (θ),

B＝2Z _o R _in X _in tan ³ (θ),

C C = = (({R R}_{i i n no} - - {Z Z}_{o o})) (({Z Z}_{o o} {R R}_{i i n no}^{22} + + {Z Z}_{o o} {X x}_{i i n no}^{22} - - {Z Z}_{o o}^{22} {R R}_{i i n no})) - - [[22 + + {tan the tan}^{22} ((θ θ))]] {tan the tan}^{22} ((θ θ)) {Z Z}_{o o}^{22} {X x}_{i i n no}^{22},,

D D. = = - - 22 {Z Z}_{o o}^{33} {R R}_{i i n no} {X x}_{i i n no} {tan the tan}^{33} ((θ θ)),,

E E. = = {Z Z}_{o o}^{33} {R R}_{i i n no} (({R R}_{i i n no}^{22} + + {X x}_{i i n no}^{22} - - {Z Z}_{o o} {R R}_{i i n no})) {tan the tan}^{22} ((θ θ)),,

F＝-Z _o tan ² (θ),

H＝(Z _o -R _in )Z _b -Z _o X _in tan(θ),

K K = = {R R}_{i i n no} {Z Z}_{b b}^{22} {tan the tan}^{22} ((θ θ)) - - {Z Z}_{o o} {X x}_{i i n no} {Z Z}_{b b} t t a a n no ((θ θ)),,

{Δ Δ}_{11} = = (\begin{matrix} \frac{\sqrt[33]{22} (({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}{33 A A [[22 {C C}^{33} - - 99 B B C C D D. + + 2727 {AD AD}^{22} + + 2727 {B B}^{22} E E. - - 7272 A A C C E E.} \\ + + \sqrt{- - 44 {(({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}^{33} + + {((22 {C C}^{33} - - 99 B B C C D D. + + 2727 {AD AD}^{22} + + 2727 {B B}^{22} E E. - - 7272 A A C C E E.))}^{22}} {]]}^{11 / / 33} \end{matrix}),,

{Δ Δ}_{22} = = \frac{(({C C}^{22} - - 33 B B D D. + + 1212 A A E E.))}{{Δ Δ}_{11} {((33 A A))}^{22}},,

Among them, Z ₂ , Z ₃ are the characteristic impedances of the first pair of microstrip lines (l ₂ ) and the second pair of microstrip lines (l ₃ ), respectively, Z _a , Z _b are the first dual-frequency impedance of each port The matching microstrip line (l _a ) and the characteristic impedance of the second dual-frequency impedance matching microstrip line (l _b ), Z _o is the characteristic impedance of the lead wire (l ₀ ), and θ is the electrical length of all the above microstrip lines.

9. The passive dual-frequency six-port device according to claim 4 or 8, the parameters of the passive dual-frequency six-port device meet the following conditions:

Z _e1 =81.5769Ω, Z _o1 =43.3340Ω, Z _e2 =61.2918Ω,

Z _o2 =40.1384Ω, R ₁ =63.0738Ω, R ₂ =565.1966Ω,

Z _a =41.5501Ω, Z _b =74.7131Ω, Z ₂ =42.4264Ω,

Z ₃ =30Ω, θ ₁ =θ=90°,

The two operating frequencies of the passive dual-frequency six-port device are respectively f ₁ =3 GHz and f ₂ =5 GHz;