CN103594770A - Passive double-frequency six-port device - Google Patents

Abstract

The invention discloses a passive double-frequency six-port device which comprises a double-frequency Wilkinson power divider (A), a first double-frequency branch line coupler (B), a second double-frequency branch line coupler (C) and a third double-frequency branch line coupler (D). A first port (a1) of the double-frequency Wilkinson power divider (A) is used as a first Port 1 of the passive double-frequency six-port device. A first port (b1) of the first double-frequency branch line coupler (B) is used as a second Port 2 of the passive double-frequency six-port device. A first port (c1) and a fourth port (c4) of the second double-frequency branch line coupler (C) are used as a fourth Port 4 and a sixth Port 6 of the passive double-frequency six-port device respectively. A first port (d1) and a fourth port (d4) of the third double-frequency branch line coupler (D) are used as a fifth Port 5 and a third Port 3 of the passive double-frequency six-port device respectively. The first Port 1 and the second Port 2 are used as input ports, and the third Port 3, the fourth Port4, the fifth Port 5 and the sixth Port 6 are used as output ports. Through the passive double-frequency six-port device, the work frequency (f1) and the work frequency (f2) of the passive double-frequency six-port device can be determined freely, and the phase differences of the four output ports at the two work frequency points are equal.

Description

Passive double frequency Six-port waveguide parts

Technical field

The invention belongs to microwave passive component field, special, relate to a kind of passive double frequency Six-port waveguide parts.

Background technology

Six-port waveguide parts is widely used in radar, and Direct Digital receiver, in the fields such as microwave and millimeter wave measurement and network analyzer.1972, the people such as the Hoer of NBS the concept of six-port circuit is proposed and by it for microwave network analysis, the microwave branch-off element that they utilize directional coupler and power divider etc. to have property forms six-port circuit, and by two ports in signal source and 6 ports of load access, found that by measuring 4 power on output port, just can obtain amplitude and the phase information of reflection coefficient.Sort circuit is simple in structure, and cost is low, also has multi-functional, wide-band, high accuracy and the advantage such as high-speed simultaneously.

Development along with radio communication, the application of double frequency device is more and more extensive, the frequency range of many wireless communication standards based on two or more, such as global system for mobile communications (GSM) is applied in 0.9GHz, 1.8GHz and 1.9GHz etc., thereby dual frequency characteristics can reduce greatly the number of circuit element and reduce cost, therefore study double frequency six-port circuit and be significant.

Traditional six-port circuit is mainly by 3dB directional coupler, and the special microwave component such as magic T class hybrid junction and in the same way decile power splitter forms.And the double frequency six-port circuit existing at present mainly adopts the method for compound left and right transmission line to design, when but this six-port circuit based on left-and-right-hand transmission line is applied to double frequency environment, can cause four phase differences between output port two operating frequency differences, and then affected the application of this six-port circuit under double frequency environment, and left-and-right-hand transmission line is made complicated, be difficult for realizing.

Summary of the invention

(1) technical problem that will solve

In view of above-mentioned technical problem, the invention provides an a kind of double-frequency Wilkinson power divider and three passive double frequency Six-port waveguide parts that double frequency branch line coupler forms of adopting, identical at the phase difference of two operating frequency output ports to realize, compact conformation, is easy to integrated.

(2) technical scheme

According to an aspect of the present invention, provide a kind of passive double frequency Six-port waveguide parts, it is characterized in that, having comprised: double-frequency Wilkinson power divider A, its first port a1 is as the first port Port1 of passive double frequency Six-port waveguide parts; The first double frequency branch line coupler B, its first port b1 is as the second port Port2 of described passive double frequency Six-port waveguide parts, and the 4th port b4 is connected to ground by 50 Ω loads; The second double frequency branch line coupler C, its second port c2 is connected to the second port a2 of described double-frequency Wilkinson power divider A, the 3rd port c3 is connected to the second port b2 of described the first double frequency branch line coupler B, and the first port c1 and the 4th port c4 are respectively as the 4th port Port4 and the 6th port Port6 of described passive double frequency Six-port waveguide parts; The 3rd double frequency branch line coupler D, its second port d2 is connected to the 3rd port a3 of described double-frequency Wilkinson power divider A, the 3rd port d3 is connected to the 3rd port b3 of described the first double frequency branch line coupler B, and the first port d1 and the 4th port d4 are respectively as five-port Port5 and the 3rd port Port3 of described passive double frequency Six-port waveguide parts; In described passive double frequency Six-port waveguide parts, described the first port Port1 and the second port Port2 are input port, and described the 3rd port Port3, the 4th port Port4, five-port Port5 and the 6th port Port6 are output port.

Wherein, described double-frequency Wilkinson power divider A comprises: the first couple of coupling line cl being set parallel to each other ₁, its left end is connected to each other as the first port a1 of double-frequency Wilkinson power divider A; The first isolation resistance R ₁, be connected between the right output port of described first pair of coupling line; The second couple of coupling line cl being set parallel to each other ₂, its left end level is coupled to the right-hand member of first pair of coupling line, and its right-hand member is respectively as the second port a2 and the 3rd port a3 of double-frequency Wilkinson power divider A; And the second isolation resistance R ₂, be connected between the right output port of described second pair of coupling line.

Wherein, described first couple of coupling line cl ₁left end be connected to a lead-in wire l ₀, to form the first port a1 of double-frequency Wilkinson power divider A; And described second couple of coupling line cl ₂right-hand member be connected respectively to another lead-in wire l ₀, to form respectively the second port a2 and the 3rd port a3 of double-frequency Wilkinson power divider A.

Further, the parameter in described double-frequency Wilkinson power divider A meets the following conditions:

$Z_{e1}=Z_o\sqrt{\frac{\sqrt{1+8{\tan }^4{\mathrm{\θ}}_1}-1}{{\tan }^2{\mathrm{\θ}}_1}},$

$Z_{e2}=Z_o\sqrt{\frac{\sqrt{1+8{\tan }^4{\mathrm{\θ}}_1}+1}{2{\tan }^2{\mathrm{\θ}}_1}},$

$R_1=\frac{2Z_{o1}{Z}_{o2}{\tan }^2{\mathrm{\θ}}_1}{\sqrt{(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\θ}}_1(Z_{o1}{\tan }^2{\mathrm{\θ}}_1-Z_{o2})}},$

$R_2=\frac{2Z_o{Z}_{o2}^2(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\θ}}_1+2Z_o^2{Z}_{o2}\sqrt{(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\θ}}_1(Z_{o1}{\tan }^2{\mathrm{\θ}}_1-Z_{o2})}}{Z_o^2{Z}_{o2}+(Z_{o1}{Z}_{o2}^2-Z_o^2{Z}_{o1}+Z_{o2}^3){\tan }^2{\mathrm{\θ}}_1},$

Wherein, f ₁and f ₂be respectively two operating frequencies, Z _e1for the even modular character impedance of described first pair of coupling line, Z _e2for the even modular character impedance of described second pair of coupling line, R ₁, R ₂for the resistance of described the first isolation resistance and the second isolation resistance, Z _ofor lead-in wire l ₀characteristic impedance, θ ₁be the electrical length of first pair of coupling line and second pair of coupling line, Z _o1, Z _o2be respectively the strange modular character impedance of first pair of coupling line and second pair of coupling line.

Preferably, the parameter in described double-frequency Wilkinson power divider A further meets the following conditions:

Z _o1＜Z _e1＜1.5Z _o1，Z _o2＜Z _e2＜1.5Z _o2；

20 Ω < Z _e1, Z _e2< 150 Ω, 20 Ω < Z _o1, Z _o2< 120 Ω; And

Z _o=50Ω。

Wherein, described the first double frequency branch line coupler B, the second double frequency branch line coupler C and the 3rd double frequency branch line coupler D are the double frequency branch line coupler with same structure, and described in each, double frequency branch line coupler comprises: branch line coupler l ₂, l ₃, at 4 ports, the first double frequency impedance matching microstrip line l that cascade connects respectively of this branch line coupler _a, the second double frequency impedance matching microstrip line l _band lead-in wire l ₀.

Wherein, described branch line coupler comprises the first couple of microstrip line l be arrangeding in parallel along first direction ₂, the second couple of microstrip line l be arrangeding in parallel along the second direction vertical with first direction ₃; Described lead-in wire l ₀be connected to the second double frequency impedance matching microstrip line l of each port _babove, form 4 ports of each double frequency branch line coupler.

Further, described in each, the parameter of double frequency branch line coupler meets the following conditions:

$Z_2=\sqrt{2}{Z}_3,$

$Z_a=\frac{-H\&PlusMinus;\sqrt{H^2-4\mathrm{FK}}}{2F},$

$Z_b=-\frac{B}{4A}+\frac{1}{2}\sqrt{(\frac{B^2}{{4A}^2}-\frac{2C}{3A}+{\mathrm{\&Delta;}}_1+{\mathrm{\&Delta;}}_2)}+\frac{1}{2}\sqrt{(\frac{B^2}{2A^2}-\frac{4C}{3A}-{\mathrm{\&Delta;}}_1-{\mathrm{\&Delta;}}_2+\frac{4\mathrm{ABC}-B^3-8A^{2}D}{4A^3\sqrt{(\frac{B^2}{4A^2}-\frac{2C}{3A}+{\mathrm{\&Delta;}}_1+{\mathrm{\&Delta;}}_2)}})},$

$R_{\mathrm{in}}=\frac{\sqrt{(Z_2^2-Z_3^2)Z_2^2{Z}_3^2{\sin }^2\left(\mathrm{\&theta;}\right)}}{(Z_2+Z_3)[Z_2-Z_3+(Z_2+Z_3){\cos }^2\left(\mathrm{\&theta;}\right)]},$

$X_{\mathrm{in}}=\frac{(Z_2+Z_3)Z_2{Z}_3\cos \left(\mathrm{\&theta;}\right)\sin \left(\mathrm{\&theta;}\right)}{(Z_2+Z_3)[Z_2-Z_3+(Z_2+Z_3){\cos }^2\left(\mathrm{\&theta;}\right)]},$

A＝R _in(Z _o-R _in)tan ²(θ)，

B＝2Z _oR _inX _intan ³(θ)，

$C=(R_{\mathrm{in}}-Z_o)(Z_o{R}_{\mathrm{in}}^2+Z_o{X}_{\mathrm{in}}^2-Z_o^2{R}_{\mathrm{in}})-[2+{\tan }^2\left(\mathrm{\&theta;}\right)]{\tan }^2\left(\mathrm{\&theta;}\right)Z_o^2{X}_{\mathrm{in}}^2,$

$D=-2Z_o^3{R}_{\mathrm{in}}{X}_{\mathrm{in}}{\tan }^3\left(\mathrm{\&theta;}\right),$

$E=Z_o^3{R}_{\mathrm{in}}(R_{\mathrm{in}}^2+X_{\mathrm{in}}^2-Z_o{R}_{\mathrm{in}}){\tan }^2\left(\mathrm{\&theta;}\right),$

F＝-Z _otan ²(θ)，

H＝(Z _o-R _in)Z _b-Z _oX _intan(θ)，

$K=R_{\mathrm{in}}{Z}_b^2{\tan }^2\left(\mathrm{\&theta;}\right)-Z_o{X}_{\mathrm{in}}{Z}_b\tan \left(\mathrm{\&theta;}\right),$

${\mathrm{\&Delta;}}_1=\left(\begin{array}{c}\frac{\sqrt[3]{2}(C^2-3\mathrm{BD}+12\mathrm{AE})}{3A[2C^3-9\mathrm{BCD}+27{\mathrm{AD}}^2+27B^{2}E-72\mathrm{ACE}}\\ +\sqrt{-4{(C^2-3\mathrm{BD}+12\mathrm{AE})}^3+{({2C}^3-9\mathrm{BCD}+27{\mathrm{AD}}^2+27B^{2}E-72\mathrm{ACE})}^2}{]}^{1/3}\end{array}\right),$

${\mathrm{\&Delta;}}_2=\frac{(C^2-3\mathrm{BD}+12\mathrm{AE})}{{\mathrm{\&Delta;}}_1{\left(3A\right)}^2},$

Wherein, Z ₂, Z ₃be respectively first couple of microstrip line l ₂with second couple of microstrip line l ₃characteristic impedance, Z _a, Z _bbe respectively the first double frequency impedance matching microstrip line l of each port _awith the second double frequency impedance matching microstrip line l _bcharacteristic impedance, Z _ofor lead-in wire l ₀characteristic impedance, the electrical length that θ is above-mentioned all microstrip lines.

Preferably, the characteristic impedance Z of above-mentioned all microstrip lines _imeet: 20 Ω < Z _i< 120 Ω, i=a wherein, b, 2,3.

Preferably, the parameter of described passive double frequency Six-port waveguide parts meets following condition:

Z _e1＝81.5769Ω，Z _o1＝43.3340Ω，Z _e2＝61.2918Ω，

Z _o2＝40.1384Ω，R ₁＝63.0738Ω，R ₂＝565.1966Ω，

Z _a＝41.5501Ω，Z _b＝74.7131Ω，Z ₂＝42.4264Ω，

Z ₃＝30Ω，θ ₁＝θ＝90°，

Two operating frequencies of passive double frequency Six-port waveguide parts are respectively f ₁=3GHz, f ₂=5GHz.

(3) beneficial effect

From technique scheme, can find out, the passive double frequency Six-port waveguide parts of the present invention has following beneficial effect: (1), by a double-frequency Wilkinson power divider and three double frequency branch line couplers, has realized two operating frequency (f of passive double frequency Six-port waveguide parts ₁, f ₂) can freely determine, and the phase difference between four output ports is identical two operating frequencies; (2) adopt the double-frequency Wilkinson power divider of coupling microstrip line structure, double frequency branch line coupler and three Chip-Rs that resistance is different of microstrip line construction, the passive double frequency Six-port waveguide parts of having realized miniaturization, compact conformation, is easy to monolithic microwave integrated technology (MMIC) and carries out integrated.

Accompanying drawing explanation

Fig. 1 has shown the overall structure block diagram of passive according to an exemplary embodiment of the present invention double frequency Six-port waveguide parts;

Fig. 2 is the equivalent circuit theory figure of Wilkinson power divider in passive double frequency Six-port waveguide parts of the present invention;

Fig. 3 is the planar structure schematic diagram of Wilkinson power divider shown in Fig. 2;

Fig. 4 is the equivalent circuit theory figure of double frequency branch line coupler in passive double frequency Six-port waveguide parts of the present invention;

Fig. 5 is the planar structure schematic diagram of double frequency branch line coupler shown in Fig. 4;

Fig. 6 A～Fig. 6 C is the ideal model simulation result figure of the passive double frequency Six-port waveguide parts of the present invention;

The physical model simulation result figure of the passive double frequency Six-port waveguide parts that Fig. 7 A～Fig. 7 C is the preferred embodiment of the present invention.

Embodiment

For making the object, technical solutions and advantages of the present invention clearer, below in conjunction with specific embodiment, and with reference to accompanying drawing, the present invention is described in more detail.It should be noted that, in accompanying drawing or specification description, similar or identical part is all used identical figure number.The implementation that does not illustrate in accompanying drawing or describe is form known to a person of ordinary skill in the art in affiliated technical field.In addition, although the demonstration of the parameter that comprises particular value can be provided herein, should be appreciated that, parameter is without definitely equaling corresponding value, but can in acceptable error margin or design constraint, be similar to corresponding value.

Passive double frequency Six-port waveguide parts provided by the invention adopts printed circuit board (PCB) to form the plane six-port circuit of planar microstrip form, by a double-frequency Wilkinson power divider and three double frequency branch line couplers, be combined to form, further, adopt odd-even mode analytical method to parse the analytic solutions of described power splitter and coupler, make it can be operated in two Frequency point f arbitrarily ₁and f ₂.

In one exemplary embodiment of the present invention, provide a kind of passive double frequency Six-port waveguide parts.Fig. 1 has shown the overall structure block diagram of passive according to an exemplary embodiment of the present invention double frequency Six-port waveguide parts.

With reference to Fig. 1, the passive double frequency Six-port waveguide parts of the present embodiment is formed on dielectric-slab, comprises double-frequency Wilkinson power divider A, the first double frequency branch line coupler B, the second double frequency branch line coupler C and the 3rd double frequency branch line coupler D.

The first port a1 of double-frequency Wilkinson power divider A is input port, and as the first port Port1 of the passive double frequency Six-port waveguide parts of the embodiment of the present invention; Double-frequency Wilkinson power divider A the second port a2 and the 3rd port a3 are output port, are connected respectively to the second port c2 and d2 of double frequency branch line coupler C, D.

The first port b1 of the first double frequency branch line coupler B is as the second port Port2 of passive double frequency Six-port waveguide parts, the 4th port b4 is connected to ground by the ohmic load of 50 Ω, and the second port b2 of the first double frequency branch line coupler B and the 3rd port b3 are connected respectively to the 3rd port c3 and the d3 of double frequency branch line coupler C, D.

The second port c2 of the second double frequency branch line coupler C is connected to the second port a2 of double-frequency Wilkinson power divider A, its the 3rd port c3 is connected to the second port b2 of the first double frequency branch line coupler B, and its first port c1 and the 4th port c4 are respectively as the 4th port Port4 and the 6th port Port6 of passive double frequency Six-port waveguide parts;

The second port d2 of the 3rd double frequency branch line coupler D is connected to the 3rd port a3 of double-frequency Wilkinson power divider A, the 3rd port d3 is connected to the 3rd port b3 of the first double frequency branch line coupler B, and its first port d1 and the 4th port d4 are respectively as five-port Port5 and the 3rd port Port3 of passive double frequency Six-port waveguide parts.

In above-mentioned passive double frequency Six-port waveguide parts, the first port Port1 and the second port Port2 are input port, and the 3rd port Port3, the 4th port Port4, five-port Port5 and the 6th port Port6 are output port.

In the present embodiment, double-frequency Wilkinson power divider A adopts coupled line structure (referring to Fig. 2, Fig. 3).The first double frequency branch line coupler B, the second double frequency branch line coupler C are identical with the 3rd double frequency branch line coupler D circuit structure, all adopt microstrip line construction (referring to Fig. 4, Fig. 5), preferably adopt 3dB double frequency branch line coupler.Thus, the passive double frequency Six-port waveguide parts that formed by double-frequency Wilkinson power divider A and three double frequency branch line coupler B, C, D has been realized six port planar circuits of miniaturization, compact conformation, is easy to monolithic microwave integrated technology (MMIC) and carries out integrated.

Below, respectively each part in the passive double frequency Six-port waveguide parts of the preferred embodiment of the present invention is elaborated.

In the present embodiment, dielectric-slab adopts common frequency microwave sheet material, and without the high high-k sheet material of price, batch production cost is very low.

Fig. 2 is the equivalent circuit theory figure of Wilkinson power divider in passive double frequency Six-port waveguide parts of the present invention.Fig. 3 is the planar structure schematic diagram of Wilkinson power divider shown in Fig. 2.

With reference to Fig. 2 and Fig. 3, in the passive double frequency Six-port waveguide parts of the embodiment of the present invention, double-frequency Wilkinson power divider A comprises: first couple of coupling line cl ₁, the first isolation resistance R ₁, second couple of coupling line cl ₂and the second isolation resistance R ₂, three ports are characteristic impedance 50 Ω of standard.

Further, referring to Fig. 3, first couple of coupling line cl ₁parallel to each other, its left end is connected and termination lead-in wire l ₀as the first port a1 of double-frequency Wilkinson power divider A, be also the first port Port1 of passive double frequency Six-port waveguide parts.Lead-in wire l ₀length be l ₀, width is w ₀.First couple of coupling line cl ₁spacing be cs ₁, the width of every coupling line is cw ₁, length is cl ₁.Here, port pins l ₀effect be that to facilitate port standard be that the measuring instrument of 50 Ω is measured, and facilitate the connection between power splitter and coupler, Satisfying Matching Conditions.The termination lead-in wire l arranging with lower port ₀act on identical.

The first isolation resistance R ₁be connected between the right-hand member of first pair of coupling line.

Second couple of coupling line cl ₂parallel to each other, its left end level is coupled to right-hand member (i.e. second couple of coupling line cl of first pair of coupling line ₂the left end of each root be connected to the right-hand member of each root of first pair of coupling line).Second couple of coupling line cl ₂right-hand member termination lead-in wire l respectively ₀the second port a2 and the 3rd port a3 as double-frequency Wilkinson power divider A.Lead-in wire l ₀length be l ₀, width is w ₀.Second couple of coupling line cl ₂spacing be cs ₂, the width of every coupling line is cw ₂, length is cl ₂.

The second isolation resistance R ₂be connected to second couple of coupling line cl ₂right-hand member between.

In order to realize, double frequency power decile is exported in the same way and two operating frequencies can arrange arbitrarily, and the parameters in the double-frequency Wilkinson power divider shown in Fig. 2 and Fig. 3 meets following condition:

$Z_{e1}=Z_o\sqrt{\frac{\sqrt{1+8{\tan }^4{\mathrm{\&theta;}}_1}-1}{{\tan }^2{\mathrm{\&theta;}}_1}}---\left(1\right)$

$Z_{e2}=Z_o\sqrt{\frac{\sqrt{1+8{\tan }^4{\mathrm{\&theta;}}_1}+1}{2{\tan }^2{\mathrm{\&theta;}}_1}}---\left(2\right)$

$R_1=\frac{2Z_{o1}{Z}_{o2}{\tan }^2{\mathrm{\&theta;}}_1}{\sqrt{(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\&theta;}}_1(Z_{o1}{\tan }^2{\mathrm{\&theta;}}_1-Z_{o2})}}---\left(3\right)$

$R_2=\frac{2Z_o{Z}_{o2}^2(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\&theta;}}_1+2Z_o^2{Z}_{o2}\sqrt{(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\&theta;}}_1(Z_{o1}{\tan }^2{\mathrm{\&theta;}}_1-Z_{o2})}}{Z_o^2{Z}_{o2}+(Z_{o1}{Z}_{o2}^2-Z_o^2{Z}_{o1}+Z_{o2}^3){\tan }^2{\mathrm{\&theta;}}_1}---\left(4\right)$

Wherein, f ₁and f ₂be respectively two operating frequencies, g=f ₂/ f ₁for frequency ratio, Z _e1be the even modular character impedance of first pair of coupling line, Z _e2be the even modular character impedance of second pair of coupling line, R ₁, R ₂be the resistance of the first isolation resistance and the second isolation resistance, Z _ofor lead-in wire l ₀characteristic impedance, be preferably 50 ohmages of standard, θ ₁be the electrical length of two pairs of coupling lines, Z _o1, Z _o2for independent variable, be respectively the strange modular character impedance of first pair of coupling line and second pair of coupling line, conventionally meet Z _o1< Z _e1< 1.5Z _o, Z _o2< Z _e2< 1.5Z _o2condition.In the scope that can realize at microstrip line, can get 20 Ω < Z _e1, Z _e2< 150 Ω, 20 Ω < Z _o1, Z _o2< 120 Ω.

In embodiments of the invention, first pair of coupling line and second pair of coupling line all adopt coupled line structure, and the first isolation resistance R ₁with the second isolation resistance R ₂adopt the form of Chip-R.Adopt coupled line structure and Chip-R structure to make the circuit structure of this double-frequency Wilkinson power divider A compacter.

In the present embodiment, the first double frequency branch line coupler B, the second double frequency branch line coupler C and the 3rd double frequency branch line coupler D are the double frequency branch line coupler with same structure, and all of the port is characteristic impedance 50 Ω of standard.

Fig. 4 is the equivalent circuit theory figure of double frequency branch line coupler in passive double frequency Six-port waveguide parts of the present invention.Fig. 5 is the planar structure schematic diagram of double frequency branch line coupler shown in Fig. 4.

With reference to Fig. 4 and Fig. 5, in embodiments of the invention, double frequency branch line coupler B, C, D have identical structure, the first double frequency branch line coupler B take below as example is introduced, specifically comprise branch line coupler and the first double frequency impedance matching microstrip line l connecting in each cascades of 4 ports of branch line coupler _a, the second double frequency impedance matching microstrip line l _band lead-in wire l _a.

Branch line coupler, comprises the first couple of microstrip line l be arrangeding in parallel along first direction ₂, the second couple of microstrip line l be arrangeding in parallel along the second direction vertical with first direction ₃.As shown in Figure 5, first couple of microstrip line l ₂length be l ₂, width is w ₂, second couple of microstrip line l ₃length be l ₃, width is w ₃.First couple of microstrip line l ₂with second couple of microstrip line l ₃cascade connects each other, forms the branch line coupler of square structure.

Further, as shown in Figure 4 and Figure 5, on 4 ports of branch line coupler, be connected with respectively the first double frequency impedance matching microstrip line l of cascade _awith the second double frequency impedance matching microstrip line l _b.Microstrip line l _alength be l _a, width is w _a, microstrip line l _blength be l _b, width is w _b.

Further, the second double frequency impedance matching microstrip line l of each port _ball be connected to a lead-in wire l ₀, lead-in wire l ₀also form microstrip line, its length is l ₀, width is w ₀.Lead-in wire l ₀parallel the second double frequency impedance matching microstrip line l that is connected to each port _babove, form 4 port b1, b2, b3 and the b4 of the first double frequency branch line coupler B.

Referring to Fig. 4, first couple of microstrip line l ₂characteristic impedance be Z ₂, second couple of microstrip line l ₃characteristic impedance be Z ₃, the first double frequency impedance matching microstrip line l _acharacteristic impedance be Z _a, the second double frequency impedance matching microstrip line l _bcharacteristic impedance be Z _b, lead-in wire l ₀characteristic impedance be Z ₀, the electrical length of above-mentioned all microstrip lines is θ.

Branch line coupler is by the first couple of microstrip line l being perpendicular to one another ₂with second couple of microstrip line l ₃form traditional 3dB branch line coupler, its four ports respectively cascade connect the first double frequency impedance matching microstrip line l _awith the second double frequency impedance matching microstrip line l _b.Overall structure is symmetrical up and down, symmetrical, has realized double frequency power decile, 90 degree phase differences outputs and two operating frequencies branch line coupler arbitrarily.Adopt coupled line structure and Chip-R structure to make the circuit structure of this branch line coupler compacter.

For example, in order to realize the second output port of branch line coupler and the 3rd output port (port b2 and the b3 of the first double frequency branch line coupler B, other double frequency branch line couplers C, D are similar) constant amplitude, have 90 degree phase differences and can be operated in two optional frequencies, in the branch line coupler shown in Fig. 4 and Fig. 5, parameters should meet:

$Z_2=\sqrt{2}{Z}_3---\left(5\right)$

$Z_a=\frac{-H\&PlusMinus;\sqrt{H^2-4\mathrm{FK}}}{2F}---\left(6\right)$

$Z_b=-\frac{B}{4A}+\frac{1}{2}\sqrt{(\frac{B^2}{{4A}^2}-\frac{2C}{3A}+{\mathrm{\&Delta;}}_1+{\mathrm{\&Delta;}}_2)}+\frac{1}{2}\sqrt{(\frac{B^2}{2A^2}-\frac{4C}{3A}-{\mathrm{\&Delta;}}_1-{\mathrm{\&Delta;}}_2+\frac{4\mathrm{ABC}-B^3-8A^{2}D}{4A^3\sqrt{(\frac{B^2}{4A^2}-\frac{2C}{3A}+{\mathrm{\&Delta;}}_1+{\mathrm{\&Delta;}}_2)}})}---\left(7\right)$

Wherein:

$R_{\mathrm{in}}=\frac{\sqrt{(Z_2^2-Z_3^2)Z_2^2{Z}_3^2{\sin }^2\left(\mathrm{\&theta;}\right)}}{(Z_2+Z_3)[Z_2-Z_3+(Z_2+Z_3){\cos }^2\left(\mathrm{\&theta;}\right)]}---\left(8\right)$

$X_{\mathrm{in}}=\frac{(Z_2+Z_3)Z_2{Z}_3\cos \left(\mathrm{\&theta;}\right)\sin \left(\mathrm{\&theta;}\right)}{(Z_2+Z_3)[Z_2-Z_3+(Z_2+Z_3){\cos }^2\left(\mathrm{\&theta;}\right)]}---\left(9\right)$

A＝R _in(Z _o-R _in)tan ²(θ) （10）

B＝2Z _oR _inX _intan ³(θ) （11）

$C=(R_{\mathrm{in}}-Z_o)(Z_o{R}_{\mathrm{in}}^2+Z_o{X}_{\mathrm{in}}^2-Z_o^2{R}_{\mathrm{in}})-[2+{\tan }^2\left(\mathrm{\&theta;}\right)]{\tan }^2\left(\mathrm{\&theta;}\right)Z_o^2{X}_{\mathrm{in}}^2---\left(12\right)$

$D=-2Z_o^3{R}_{\mathrm{in}}{X}_{\mathrm{in}}{\tan }^3\left(\mathrm{\&theta;}\right)---\left(13\right)$

$E=Z_o^3{R}_{\mathrm{in}}(R_{\mathrm{in}}^2+X_{\mathrm{in}}^2-Z_o{R}_{\mathrm{in}}){\tan }^2\left(\mathrm{\&theta;}\right)---\left(14\right)$

F＝-Z _otan ²(θ) （15）

H＝(Z _o-R _in)Z _b-Z _oX _intan(θ) （16）

$K=R_{\mathrm{in}}{Z}_b^2{\tan }^2\left(\mathrm{\&theta;}\right)-Z_o{X}_{\mathrm{in}}{Z}_b\tan \left(\mathrm{\&theta;}\right)---\left(17\right)$

${\mathrm{\&Delta;}}_1=\left(\begin{array}{c}\frac{\sqrt[3]{2}(C^2-3\mathrm{BD}+12\mathrm{AE})}{3A[2C^3-9\mathrm{BCD}+27{\mathrm{AD}}^2+27B^{2}E-72\mathrm{ACE}}\\ +\sqrt{-4{(C^2-3\mathrm{BD}+12\mathrm{AE})}^3+{({2C}^3-9\mathrm{BCD}+27{\mathrm{AD}}^2+27B^{2}E-72\mathrm{ACE})}^2}{]}^{1/3}\end{array}\right)---\left(18\right)$

${\mathrm{\&Delta;}}_2=\frac{(C^2-3\mathrm{BD}+12\mathrm{AE})}{{\mathrm{\&Delta;}}_1{\left(3A\right)}^2}---\left(19\right)$

Wherein, Z ₂, Z ₃be respectively first couple of microstrip line l ₂with second couple of microstrip line l ₃characteristic impedance, Z _a, Z _bbe respectively the first double frequency impedance matching microstrip line l of each port _awith the second double frequency impedance matching microstrip line l _bcharacteristic impedance, Z _ofor lead-in wire l ₀characteristic impedance, be generally 50 ohmages of standard, θ is microstrip line l ₂, l ₃, l _a, l _belectrical length, Z ₃for independent variable.In the scope that can realize at microstrip line, get 20 Ω < Z _i< 120 Ω (wherein i=a, b, 2,3).

Please refer to Fig. 1, in the present embodiment, the 4th port b4 of the first double frequency branch line coupler B connects 50 ohm load.Four output ports of the second double frequency branch line coupler C and the 3rd double frequency branch line coupler D, thus the 3rd port Port3 of whole passive double frequency Six-port waveguide parts, the 4th port Port4, five-port Port5 and the 6th port Port6 all can connect diode power detection meter and test its power output.

As mentioned above, according to the passive double frequency Six-port waveguide parts of the embodiment of the present invention, adopt odd-even mode analytical method to parse the analytic solutions of power splitter and coupler, make it can be operated in two Frequency point (f arbitrarily ₁, f ₂).Further, adopt the form of planar microstrip line to realize this device, thereby overcome the contrary shortcoming of phase difference of left-and-right-hand transmission line output port in two operating frequencies.

Introduce a preferred embodiment of the passive double frequency Six-port waveguide parts of the present invention below.Described preferred embodiment is to be basis according to said structure and theoretical calculation formula; by Multi simulation running, test; then after repeatedly actual measurement and debugging, obtain; represent a preferred embodiment of passive double frequency Six-port waveguide parts of the present invention; but can not think limitation of the present invention, every example that meets described formula all should be at the row of protection range.

The parameter of the passive double frequency Six-port waveguide parts of the preferred embodiment of the present invention is as follows:

Z _e1＝81.5769Ω，Z _o1＝43.3340Ω，Z _e2＝61.2918Ω，Z _o2＝40.1384Ω，

R ₁＝63.0738Ω,R ₂＝565.1966Ω,Z _a＝41.5501Ω，Z _b＝74.7131Ω。

Z ₂＝42.4264Ω，Z ₃＝30Ω，θ ₁＝θ＝90°(f ₀＝4GHz)。Now, two of passive double frequency Six-port waveguide parts operating frequencies are respectively f ₁=3GHz, f ₂=5GHz.

For the Wilkinson power divider shown in Fig. 3 and Fig. 5 and the device architecture of branch line coupler, based on relative dielectric constant, be 3.48, thickness is that the Rogers R04350B sheet material of 0.762mm passes through to use microstrip line computational tool, can obtain the parameter of side circuit: w ₀=2.73mm, l ₀=10mm, cw ₁=1.26mm, cs ₁=0.42mm, cl ₁=11.98mm, cw ₂=1.94mm, cs ₂=0.63mm, cl ₂=11.61mm, w _a=3.01mm, l _a=11.12mmw _b=1.10mm, l _b=11.58mm, w ₂=2.92mm, l ₂=11.13mm, w ₃=4.75mm, l ₃=10.89mm.

Fig. 6 A～Fig. 6 C is the ideal model simulation result figure of the passive double frequency Six-port waveguide parts of the present invention.

The physical model simulation result figure of the passive double frequency Six-port waveguide parts that Fig. 7 A～Fig. 7 C is the preferred embodiment of the present invention.Comparison diagram 6A and Fig. 7 A can see, the input port of the passive double frequency Six-port waveguide parts of the preferred embodiment of the present invention at two operating frequency places has and mate well and isolate, all reach-below 20dB.Comparison diagram 6B and Fig. 7 B can see, the passive double frequency Six-port waveguide parts of the preferred embodiment of the present invention equates in the amplitude of the output port at two operating frequency places, and desirable range value is-6.021dB that physical model analogous diagram approaches desirable range value.From Fig. 6 C and Fig. 7 C, can see, the passive double frequency Six-port waveguide parts of the preferred embodiment of the present invention is identical at the phase difference of the output port at two operating frequency places.

Table Ⅰ and Table Ⅱ have shown in the scattering parameter amplitude of two different operating frequencies and phase place brief summary.

Table I

From table I, can find out for desirable artificial circuit to there is identical phase difference, S for two operating frequencies ₄₂with S ₃₂between phase difference be 0 °, S ₅₂with S ₃₂between phase difference be-90 °, S ₆₂with S ₃₂between phase difference be 90 °.

Table II

From table II, can find out, for physical model artificial circuit, two operating frequencies to be had to close phase difference, at f=3GHz, be respectively 0.001 ° ,-90.232 °, 90.063 °,

be respectively 0.138 ° ,-89.725 °, 89.34 °.Visible, the passive double frequency Six-port waveguide parts of the preferred embodiment of the present invention fully approaches the parameter index of ideal model, has realized object of the present invention.

So far, by reference to the accompanying drawings the present embodiment be have been described in detail.According to above, describe, those skilled in the art should have clearly understanding to passive double frequency Six-port waveguide parts of the present invention.

In sum, the invention provides a kind of passive double frequency Six-port waveguide parts of planar microstrip structure, overcome the contrary shortcoming of phase difference of left-and-right-hand transmission line output port in two operating frequencies, realize four output port amplitude deciles.Meanwhile, that this passive double frequency Six-port waveguide parts also has is simple in structure, cost is low, size is little, operating frequency is wide, the equal advantage mutually of the phase difference at two operating frequency output ports in two frequencies, has good popularizing application prospect.

Above-described specific embodiment; object of the present invention, technical scheme and beneficial effect are further described; institute is understood that; the foregoing is only specific embodiments of the invention; be not limited to the present invention; within the spirit and principles in the present invention all, any modification of making, be equal to replacement, improvement etc., within all should being included in protection scope of the present invention.

Claims (10)

1. a passive double frequency Six-port waveguide parts, is characterized in that, comprising:

Double-frequency Wilkinson power divider (A), its first port (a1) is as first port (Port1) of passive double frequency Six-port waveguide parts;

The first double frequency branch line coupler (B), its first port (b1) is as second port (Port2) of described passive double frequency Six-port waveguide parts, and the 4th port (b4) is connected to ground by 50 Ω loads;

The second double frequency branch line coupler (C), its second port (c2) is connected to second port (a2) of described double-frequency Wilkinson power divider (A), the 3rd port (c3) is connected to second port (b2) of described the first double frequency branch line coupler (B), and the first port (c1) and the 4th port (c4) are respectively as the 4th port (Port4) and the 6th port (Port6) of described passive double frequency Six-port waveguide parts;

The 3rd double frequency branch line coupler (D), its second port (d2) is connected to the 3rd port (a3) of described double-frequency Wilkinson power divider (A), the 3rd port (d3) is connected to the 3rd port (b3) of described the first double frequency branch line coupler (B), and the first port (d1) and the 4th port (d4) are respectively as five-port (Port5) and the 3rd port (Port3) of described passive double frequency Six-port waveguide parts;

In described passive double frequency Six-port waveguide parts, described the first port (Port1) and the second port (Port2) are input port, and described the 3rd port (Port3), the 4th port (Port4), five-port (Port5) and the 6th port (Port6) are output port.

2. passive double frequency Six-port waveguide parts according to claim 1, is characterized in that, described double-frequency Wilkinson power divider (A) comprising:

The first couple of coupling line (cl being set parallel to each other ₁), its left end is connected to each other as the first port (a1) of double-frequency Wilkinson power divider A;

The first isolation resistance (R ₁), be connected between the right output port of described first pair of coupling line;

The second couple of coupling line (cl being set parallel to each other ₂), its left end level is coupled to the right-hand member of first pair of coupling line, and its right-hand member is respectively as the second port (a2) and the 3rd port (a3) of double-frequency Wilkinson power divider (A); And

The second isolation resistance (R ₂), be connected between the right output port of described second pair of coupling line.

3. passive double frequency Six-port waveguide parts according to claim 2, wherein,

Described first couple of coupling line (cl ₁) left end be connected to a lead-in wire (l ₀), to form first port (a1) of double-frequency Wilkinson power divider (A); And

Described second couple of coupling line (cl ₂) two ports of right-hand member are connected respectively to the identical two lead-in wire (l of length ₀), to form respectively the second port (a2) and the 3rd port (a3) of double-frequency Wilkinson power divider (A).

4. passive double frequency Six-port waveguide parts according to claim 3, is characterized in that, the parameter in described double-frequency Wilkinson power divider (A) meets the following conditions:

$Z_{e1}=Z_o\sqrt{\frac{\sqrt{1+8{\tan }^4{\mathrm{\&theta;}}_1}-1}{{\tan }^2{\mathrm{\&theta;}}_1}},$

$Z_{e2}=Z_o\sqrt{\frac{\sqrt{1+8{\tan }^4{\mathrm{\&theta;}}_1}+1}{2{\tan }^2{\mathrm{\&theta;}}_1}},$

$R_1=\frac{2Z_{o1}{Z}_{o2}{\tan }^2{\mathrm{\&theta;}}_1}{\sqrt{(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\&theta;}}_1(Z_{o1}{\tan }^2{\mathrm{\&theta;}}_1-Z_{o2})}},$

$R_2=\frac{2Z_o{Z}_{o2}^2(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\&theta;}}_1+2Z_o^2{Z}_{o2}\sqrt{(Z_{o1}+Z_{o2}){\tan }^2{\mathrm{\&theta;}}_1(Z_{o1}{\tan }^2{\mathrm{\&theta;}}_1-Z_{o2})}}{Z_o^2{Z}_{o2}+(Z_{o1}{Z}_{o2}^2-Z_o^2{Z}_{o1}+Z_{o2}^3){\tan }^2{\mathrm{\&theta;}}_1},$

Wherein, f ₁and f ₂be respectively two operating frequencies, Z _e1for the even modular character impedance of described first pair of coupling line, Z _e2for the even modular character impedance of described second pair of coupling line, R ₁, R ₂for the resistance of described the first isolation resistance and the second isolation resistance, Z _ofor lead-in wire (l ₀) characteristic impedance, θ ₁be the electrical length of first pair of coupling line and second pair of coupling line, Z _o1, Z _o2be respectively the strange modular character impedance of first pair of coupling line and second pair of coupling line.

5. passive double frequency Six-port waveguide parts according to claim 4, the parameter in described double-frequency Wilkinson power divider (A) further meets the following conditions:

Z _o1＜Z _e1＜1.5Z _o1，Z _o2＜Z _e2＜1.5Z _o2；

20 Ω < Z _e1, Z _e2< 150 Ω, 20 Ω < Z _o1, Z _o2< 120 Ω; And

Z _o=50Ω。

6. passive double frequency Six-port waveguide parts according to claim 1, described the first double frequency branch line coupler (B), the second double frequency branch line coupler (C) and the 3rd double frequency branch line coupler (D) are for having the double frequency branch line coupler of same structure, and described in each, double frequency branch line coupler comprises: branch line coupler (l ₂, l ₃), at 4 ports, the first double frequency impedance matching microstrip line (l that cascade connects respectively of this branch line coupler _a), the second double frequency impedance matching microstrip line (l _b) and lead-in wire (l ₀).

7. passive double frequency Six-port waveguide parts according to claim 6, wherein,

Described branch line coupler comprises the first couple of microstrip line (l be arrangeding in parallel along first direction ₂), along second couple of microstrip line (l with the setting of first direction vertical parallel ₃);

Described every lead-in wire (l ₀) be connected to the second double frequency impedance matching microstrip line (l of each port _b) above, form 4 ports of each double frequency branch line coupler.

8. passive double frequency Six-port waveguide parts according to claim 7, is characterized in that, described in each, the parameter of double frequency branch line coupler meets the following conditions:

$Z_2=\sqrt{2}{Z}_3,$

$Z_a=\frac{-H\&PlusMinus;\sqrt{H^2-4\mathrm{FK}}}{2F},$

$Z_b=-\frac{B}{4A}+\frac{1}{2}\sqrt{(\frac{B^2}{{4A}^2}-\frac{2C}{3A}+{\mathrm{\&Delta;}}_1+{\mathrm{\&Delta;}}_2)}+\frac{1}{2}\sqrt{(\frac{B^2}{2A^2}-\frac{4C}{3A}-{\mathrm{\&Delta;}}_1-{\mathrm{\&Delta;}}_2+\frac{4\mathrm{ABC}-B^3-8A^{2}D}{4A^3\sqrt{(\frac{B^2}{4A^2}-\frac{2C}{3A}+{\mathrm{\&Delta;}}_1+{\mathrm{\&Delta;}}_2)}})},$

$R_{\mathrm{in}}=\frac{\sqrt{(Z_2^2-Z_3^2)Z_2^2{Z}_3^2{\sin }^2\left(\mathrm{\&theta;}\right)}}{(Z_2+Z_3)[Z_2-Z_3+(Z_2+Z_3){\cos }^2\left(\mathrm{\&theta;}\right)]},$

$X_{\mathrm{in}}=\frac{(Z_2+Z_3)Z_2{Z}_3\cos \left(\mathrm{\&theta;}\right)\sin \left(\mathrm{\&theta;}\right)}{(Z_2+Z_3)[Z_2-Z_3+(Z_2+Z_3){\cos }^2\left(\mathrm{\&theta;}\right)]},$

A＝R _in(Z _o-R _in)tan ²(θ)，

B＝2Z _oR _inX _intan ³(θ)，

$C=(R_{\mathrm{in}}-Z_o)(Z_o{R}_{\mathrm{in}}^2+Z_o{X}_{\mathrm{in}}^2-Z_o^2{R}_{\mathrm{in}})-[2+{\tan }^2\left(\mathrm{\&theta;}\right)]{\tan }^2\left(\mathrm{\&theta;}\right)Z_o^2{X}_{\mathrm{in}}^2,$

$D=-2Z_o^3{R}_{\mathrm{in}}{X}_{\mathrm{in}}{\tan }^3\left(\mathrm{\&theta;}\right),$

$E=Z_o^3{R}_{\mathrm{in}}(R_{\mathrm{in}}^2+X_{\mathrm{in}}^2-Z_o{R}_{\mathrm{in}}){\tan }^2\left(\mathrm{\&theta;}\right),$

F＝-Z _otan ²(θ)，

H＝(Z _o-R _in)Z _b-Z _oX _intan(θ)，

$K=R_{\mathrm{in}}{Z}_b^2{\tan }^2\left(\mathrm{\&theta;}\right)-Z_o{X}_{\mathrm{in}}{Z}_b\tan \left(\mathrm{\&theta;}\right),$

${\mathrm{\&Delta;}}_1=\left(\begin{array}{c}\frac{\sqrt[3]{2}(C^2-3\mathrm{BD}+12\mathrm{AE})}{3A[2C^3-9\mathrm{BCD}+27{\mathrm{AD}}^2+27B^{2}E-72\mathrm{ACE}}\\ +\sqrt{-4{(C^2-3\mathrm{BD}+12\mathrm{AE})}^3+{({2C}^3-9\mathrm{BCD}+27{\mathrm{AD}}^2+27B^{2}E-72\mathrm{ACE})}^2}{]}^{1/3}\end{array}\right),$

${\mathrm{\&Delta;}}_2=\frac{(C^2-3\mathrm{BD}+12\mathrm{AE})}{{\mathrm{\&Delta;}}_1{\left(3A\right)}^2},$

Wherein, Z ₂, Z ₃be respectively first couple of microstrip line (l ₂) and second couple of microstrip line (l ₃) characteristic impedance, Z _a, Z _bbe respectively the first double frequency impedance matching microstrip line (l of each port _a) and the second double frequency impedance matching microstrip line (l _b) characteristic impedance, Z _ofor lead-in wire (l ₀) characteristic impedance, the electrical length that θ is above-mentioned all microstrip lines.

9. passive double frequency Six-port waveguide parts according to claim 8, is characterized in that, the characteristic impedance Z of above-mentioned all microstrip lines _imeet: 20 Ω < Z _i< 120 Ω, i=a wherein, b, 2,3.

10. according to the passive double frequency Six-port waveguide parts described in claim 4 or 8, the parameter of described passive double frequency Six-port waveguide parts meets following condition:

Z _e1＝81.5769Ω，Z _o1＝43.3340Ω，Z _e2＝61.2918Ω，

Z _o2＝40.1384Ω，R ₁＝63.0738Ω，R ₂＝565.1966Ω，

Z _a＝41.5501Ω，Z _b＝74.7131Ω，Z ₂＝42.4264Ω，

Z ₃＝30Ω，θ ₁＝θ＝90°，

Two operating frequencies of passive double frequency Six-port waveguide parts are respectively f ₁=3GHz, f ₂=5GHz.

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