CN103236790A - Method and device for controlling half-hysteresis ring pulse sequences of switching power supply in continuous working mode - Google Patents
Method and device for controlling half-hysteresis ring pulse sequences of switching power supply in continuous working mode Download PDFInfo
- Publication number
- CN103236790A CN103236790A CN2013101045541A CN201310104554A CN103236790A CN 103236790 A CN103236790 A CN 103236790A CN 2013101045541 A CN2013101045541 A CN 2013101045541A CN 201310104554 A CN201310104554 A CN 201310104554A CN 103236790 A CN103236790 A CN 103236790A
- Authority
- CN
- China
- Prior art keywords
- control
- pulse
- output
- converter
- timing device
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Landscapes
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a method and a device for controlling half-hysteresis ring pulse sequences of a switching power supply in a continuous working mode. The method includes that in each starting moment of a switching period, effective control pulses within the switching period are selected according to relationship between switching converter Vo (voltage output) and Vref (voltage reference). Selection rules include that a control pulse PH is adopted to control a switching tube S of a switching converter if the Vo is lower than the Vref; and if not, a control pulse PL is adopted to control the switching tube S. High-electrical level lasting time of each control pulse is a preset fixed value, and low-electrical level lasting time of each control pulse is acquired by comparison of inductive current IL and preset estimated current IV. The method for controlling the half-hysteresis ring sequences can be used for controlling a high-power switching converter in the continuous working mode; a control technology in the method is simple and practical; and the switching converter has strong stability and capacity of resisting disturbances and good dynamic performance, and is applicable to the switching converters with various topological structures.
Description
Technical field
The present invention relates to Switching Power Supply, especially a kind of control method of switch converters and device thereof.
Background technology
Switching Power Supply is a kind of conducting by control master power switch pipe, the power supply that the turn-off time is kept output voltage stabilization.It has advantages such as power consumption is little, energy conversion efficiency is high, and volume is little, voltage stabilized range is wide, all is widely used in each electronic product.Along with the development of power electronic technology and popularizing of battery powered portable electric appts, more and more higher to the performance requirement of Switching Power Supply.There are shortcomings such as transient response speed is slow, COMPENSATION NETWORK DESIGN difficulty for improving traditional pulse width modulation (PWM) technology, some novel control methods have been proposed in recent years, to improve the performance of Switching Power Supply, make it satisfy electronic equipment to the requirement of Switching Power Supply.
Pulse train (PT) control technology is a kind ofly to be operated in the novel fixed control method frequently that inductive current discontinuous mode (DCM) proposes at switch converters, and it realizes adjusting to output voltage by the compound mode of adjusting two groups of predefined control impuls.Circuit simply, not needing to realize compensating network, transient response speed is fast and the advantage of strong robustness because pulse train control switch converter has, and is highly suitable for the Switching Power Supply control system higher to reliability requirement.But when pulse train control switch converter is operated in inductive current continuous mode (CCM), because the pulse train controller is by regulating inductive current indirect regulation output voltage, make controller have hysteresis quality to the adjusting of output voltage, cause switch converters the low-frequency fluctuation phenomenon to occur, stable state and mapping variation.Present studies show that, equivalent series resistance (ESR) by increasing output filter capacitor but the low-frequency fluctuation phenomenon of suppressor pulse sequence control continuous operation mode switch converters, but the equivalent series resistance that increases output filter capacitor can make output voltage ripple increase.
Summary of the invention
The control method that the purpose of this invention is to provide a kind of Switching Power Supply, the technical disadvantages when making it to overcome existing pulse train control and being operated in the inductive current continuous mode.This method can be used for controlling the high power switch converter that works in continuous mode, and its control technology is simple, and stability and antijamming capability are strong, and dynamic property is good, is applicable to the switch converters of various topological structures.
The present invention realizes its goal of the invention, the technical scheme that adopts is: half of continuous operation mode Switching Power Supply stagnates and encircles pulse sequence control method, the half stagnant ring pulse train regulating system of being formed the continuous operation mode Switching Power Supply by converter TD and controller, its working method comprises: in the initial moment of each switch periods, select effective control impuls in this switch periods according to switch converters output voltage control impuls selective rule, thereby realize the control to the continuous operation mode switch converters; Its control impuls selective rule is: if V
oBe lower than V
Ref, adopt control impuls P
HSwitching tube S in the control switch converter; Otherwise, if V
oBe higher than V
Ref, adopt control impuls P
LControl switch pipe S.
Above-mentioned generation control impuls P
HMethod be: at the initial t of certain switch periods
0Constantly, single triggering timing device picks up counting control impuls P
HBecome high level by low level, the switching tube S among the converter TD is open-minded, inductive current I
LRise; At t
0+ τ
On_HConstantly, single triggering timing device finishes timing, control impuls P
HRemaining high level fix time τ
On_HAfter become low level, switching tube S turn-offs, diode D is open-minded, inductive current descends; Drop to default inductive current valley I at inductive current
vConstantly, control impuls P
HRemaining low level time τ
Off_HAfter become high level, single triggering timing device picks up counting again, switching tube S is open-minded again, converter enters next switch periods.
Above-mentioned generation control impuls P
LMethod and said process similar, the difference be at a switch periods inner control pulse P
LFor the low level duration is τ
On_L(τ
On_L＜τ
On_H).
Compared with prior art, the invention has the beneficial effects as follows:
One, the present invention provides a kind of simple and reliable control method for the continuous operation mode switch converters.This control method can be finished the control to main switch S in the converter by detecting an output voltage in the initial moment of each switch periods and simply judging its size and detect inductive current and simple its size of judgement.Overcome the detection that traditional continuous mode convertor controls method is difficult to avoid and handled shortcomings such as feedback quantity complexity, compensation tache design are loaded down with trivial details.
But two, the low-frequency fluctuation phenomenon of control method suppressor pulse sequence control continuous operation mode switch converters provided by the present invention, make the working range of controlled converter not be subjected to the restriction of pulse train control change device inductive current critical condition, widened range of application.
Another object of the present invention provides a kind of device of realizing the control method of above Switching Power Supply.
The present invention realizes that the technical scheme that this goal of the invention adopts is: a kind of device of realizing the control method of above Switching Power Supply, formed by converter and controller, controller comprises voltage detecting circuit, current detecting and comparison circuit, pulse selector, pulse generator, single triggering timing device 1, single triggering timing device 2, drive circuit, and its design feature is: current detecting links to each other with pulse selector, pulse generator, single triggering timing device 1, single triggering timing device 2 with comparison circuit; Voltage detecting circuit, pulse selector, pulse generator, drive circuit link to each other successively; Pulse generator links to each other with comparison circuit, single triggering timing device 1, single triggering timing device 2 with current detecting.
The course of work and the principle of this device are: current detecting and comparison circuit detect inductive current I
L, and with inductive current I
LWith default inductive current valley I
vRelatively, at inductive current I
LDrop to default inductive current valley I
vConstantly, produce clock pulse signal V
C1Arrive constantly when clock pulse, pulse selector is output voltage V relatively at this moment
oWith reference voltage V
RefMagnitude relationship, and the logical signal that will represent comparative result exports pulse generator to; Pulse generator clocks according to single triggering timing device and the comparative result of current detecting and comparison circuit, and generation frequency and duty ratio be different control impuls P all
H, P
L, and according to output voltage V
oWith reference voltage V
RefThe corresponding control impuls of magnitude relationship output realize control to converter switches pipe S.
As seen, adopt above device can realize the above method of the present invention easily and reliably.
Specifically consisting of of above-mentioned current detecting and comparison circuit: formed by current detection circuit ID and comparator AC1; The positive polarity termination of comparator AC1 is preset valley point current I
v, the inductive current I of negative polarity termination current detection circuit ID output
L
Like this, comparator AC1 is with inductive current I
LWith default valley point current I
vCompare, as inductive current I
LBe lower than default valley point current I
vThe time, the output signal V of comparator AC1
C1Be high level, otherwise, I worked as
LBe lower than I
vThe time, V
C1Be low level.
Specifically consisting of of above-mentioned pulse selector: formed by comparator AC2 and d type flip flop DFF; The converter output voltage V of the positive polarity termination voltage detecting circuit VD output of comparator AC2
o, negative polarity termination reference voltage V
Ref, the output of AC2 links to each other with the D end of d type flip flop DFF.
Like this, comparator AC2 is with output voltage V
oSame reference voltage V
RefCompare, work as output voltage V
oBe lower than reference voltage V
RefThe time, the output signal V of comparator AC2
C2Be low level, otherwise, V worked as
oBe lower than V
RefThe time, V
C2Be high level; Work as V
C1Rising edge comes interim, and d type flip flop DFF is the output signal V of comparator AC2 at this moment
C2Export the Q end to, produce pulse selecting signal V
Q, according to the operation principle of trigger: V
QAt V
C1Next rising edge remain unchanged before arriving, and
Level height all the time with V
QOn the contrary.
Specifically consisting of of above-mentioned pulse generator: by rest-set flip-flop RSFF1, RSFF2, with door AG1, AG2, and or door OG form; The S end of rest-set flip-flop RSFF1 and RSFF2 all meets the output signal V of current detecting and comparison circuit
C1, the output signal V of R end difference order triggering timing device OOT1 and OOT2
TLAnd V
THWith the Q end of the input termination rest-set flip-flop RSFF1 of door AG1 and the Q end of trigger DFF, hold with the Q of the input termination rest-set flip-flop RSFF2 of door AG2 and trigger DFF
End; Or the output of the input termination of door OG and door AG1 and AG2, the drive circuit DR of the output termination switching tube S of OG1.
Like this, at inductive current I
LDrop to default inductive current valley I
vConstantly, the S of rest-set flip-flop RSFF1 holds input high level, the control wave P of RSFF1 output
LBe high level, when single triggering timing device OOT1 clocks end, the R end input high level of rest-set flip-flop RSFF1, the control wave P of RSFF1 output
LBecome low level; The course of work of rest-set flip-flop RSFF2 and above-mentioned RSFF1 are similar, but because the single triggering timing device of the R termination of RSFF2 OOT2, and the duration that clocks of single triggering timing device OOT2 is greater than the duration that clocks of single triggering timing device OOT1, the control wave P of RSFF2 output
HHigh level lasting time greater than P
LAs pulse selecting signal V
QBe high level,
During for low level, AG1 is open-minded with door, and AG2 is blocked, or door OG output control pulse P
LTo drive circuit; Otherwise, as pulse selecting signal V
QBe low level,
During for high level, AG2 is open-minded with door, and AG1 is blocked, or door OG output control pulse P
HTo drive circuit.
Above pulse selector and pulse generator are simple in structure, and stable performance can realize the correlation function in the inventive method reliably.In the above-mentioned control device, the selection of control impuls and generation also can adopt the circuit of existing other structures to realize.
The present invention is further detailed explanation below in conjunction with the drawings and specific embodiments.
Description of drawings
Fig. 1 is the signal flow graph of the embodiment of the invention one method.
Fig. 2 is the circuit structure block diagram of the embodiment of the invention one.
Fig. 3 is the current detecting of the embodiment of the invention one and the circuit structure diagram of comparison circuit.
Fig. 4 is the circuit structure diagram of the pulse selector of the embodiment of the invention one.
Fig. 5 is the circuit structure diagram of the pulse generator of the embodiment of the invention one.
Fig. 6 a is the embodiment of the invention one a certain period inductive current I under limit
LThe time-domain-simulation oscillogram.
Fig. 6 b is the clock pulse signal V of switch periods zero hour of producing with the same period current detecting of Fig. 6 a and comparison circuit
C1The time-domain-simulation oscillogram.
Fig. 6 c is and Fig. 6 a control wave P of same period
HThe time-domain-simulation oscillogram.
Fig. 6 d is and Fig. 6 a control wave P of same period
LThe time-domain-simulation oscillogram.
Fig. 6 e is and effective control wave V of same period of Fig. 6 a
PThe time-domain-simulation oscillogram.
Fig. 6 f is and Fig. 6 a converter output voltage V of same period
oThe time-domain-simulation oscillogram.
Fig. 6 simulated conditions is as follows: input voltage V
In=50V, output reference voltage V
Ref=20V, inductance L=400 μ H, capacitor C=200 μ F, load resistance R=10 Ω, control impuls P
HDuration of high level be τ
On_H=8 μ s, control impuls P
LDuration of high level be τ
On_L=1 μ s, default valley point current I
v=1.8A.
Fig. 7 a is existing pulse train control change device a certain period under limit, effectively P in the control wave
HThe time-domain-simulation oscillogram of pulse.
Fig. 7 b be existing pulse train control change device with same period of Fig. 7 a, effectively P in the control wave
LThe time-domain-simulation oscillogram of pulse.
Fig. 7 c be existing pulse train control change device with same period of Fig. 7 a, converter output voltage V
oThe time-domain-simulation oscillogram.
Fig. 7 simulated conditions is as follows: input voltage V
In=50V, output reference voltage V
Ref=20V, inductance L=400 μ H, capacitor C=200 μ F, load resistance R=10 Ω, control impuls P
HDuty ratio be D
H=0.8, control impuls P
LDuty ratio be D
L=0.1, the switching frequency of converter is f=100kHz.
Fig. 8 is the circuit structure block diagram of the embodiment of the invention two.
Fig. 9 is the circuit structure block diagram of the embodiment of the invention three.
Embodiment
Embodiment one
Fig. 1 illustrates, and a kind of embodiment of the present invention is, a kind of control method of Switching Power Supply, and its concrete practice is:
In the initial moment of each switch periods, controller is according to the output voltage V of switch converters TD
oWith reference voltage V
RefBetween relation select effective control impuls in this switch periods, thereby realize the control to switch converters TD.Its control impuls selective rule is: if V
oBe lower than V
Ref, adopt control impuls P
HSwitching tube S in the control switch converter; Otherwise, if V
oBe higher than V
Ref, adopt control impuls P
LControl switch pipe S.
Controller produces control impuls P
HMethod be: at the initial t of certain switch periods
0Constantly, single triggering timing device picks up counting control impuls P
HBecome high level by low level, the switching tube S among the converter TD is open-minded, inductive current I
LRise; At t
0+ τ
On_HConstantly, single triggering timing device finishes timing, control impuls P
HRemaining high level fix time τ
On_HAfter become low level, switching tube S turn-offs, diode D is open-minded, inductive current descends; Drop to default valley point current I at inductive current
vConstantly, control impuls P
HRemaining low level time τ
Off_HAfter become high level, converter enters next switch periods.
Controller produces control impuls P
LMethod and said process similar, the difference be at a switch periods inner control pulse P
LFor the low level duration is respectively τ
On_L(τ
On_L＜τ
On_H).
This example adopts following device, and above-mentioned control method is realized quickly and easily.
Fig. 2 illustrates, the device of the control method of the Switching Power Supply that this is routine, formed by converter TD and controller, controller comprises voltage detecting circuit VD, current detecting and comparison circuit IDC, pulse selector PS, pulse generator PG, single triggering timing device OOT1, single triggering timing device OOT2, drive circuit DR, and its design feature is: current detecting links to each other with pulse selector PS, pulse generator PG, single triggering timing device OTT1, single triggering timing device OTT2 with comparison circuit IDC; Voltage detecting circuit VD, pulse selector PS, pulse generator PG, drive circuit be continuous DR successively; Pulse generator PG links to each other with comparison circuit IDC, single triggering timing device OOT1, single triggering timing device OOT2 with current detecting.
Fig. 3 illustrates, and the current detecting that this is routine and comparison circuit IDC specifically consist of: be made up of current detection circuit ID and comparator AC1; The positive polarity termination of comparator AC1 is preset valley point current I
v, the inductive current I of negative polarity termination current detection circuit ID output
LThe output of comparator AC1 links to each other with pulse selector PS, pulse generator PG, single triggering timing device OTT1, single triggering timing device OTT2.
Fig. 4 illustrates, and the pulse selector PS that this is routine specifically consists of: be made up of comparator AC2 and d type flip flop DFF; The converter output voltage V of the positive polarity termination voltage detecting circuit VD output of comparator AC2
o, negative polarity termination reference voltage V
Ref, the output of AC2 links to each other with the D end of d type flip flop DFF; The output Q of d type flip flop DFF and
PG links to each other with pulse generator.
Fig. 5 illustrates, and the pulse generator PG that this is routine specifically consists of: by rest-set flip-flop RSFF1, RSFF2, with door AG1, AG2, and or door OG form; The S end of rest-set flip-flop RSFF1 and RSFF2 all meets the output signal V of current detecting and comparison circuit
C1, the output signal V of R end difference order triggering timing device OOT1 and OOT2
TLAnd V
THWith the Q end of the input termination rest-set flip-flop RSFF1 of door AG1 and the Q end of trigger DFF, hold with the Q of the input termination rest-set flip-flop RSFF2 of door AG2 and trigger DFF
End; Or the output of the input termination of door OG and door AG1 and AG2, the drive circuit DR of the output termination switching tube S of OG1.
Its course of work of the device of this example and principle are:
Fig. 1-5 illustrates, and current detecting and comparison circuit IDC produce the clock pulse signal V that the switching tube cycle begins
C1As clock pulse signal V
C1Arrive constantly, pulse selector PS is output voltage V relatively at this moment
oWith reference voltage V
RefMagnitude relationship, and the logical signal that will represent comparative result exports pulse generator PG to; In this simultaneously, single triggering timing device OOT1 or OOT2 pick up counting; Pulse generator PG is according to the signal V that clocks of single triggering timing device OOT1 or OOT2
TLOr V
TH, clock pulse signal V
C1Produce all different control impuls P of frequency and duty ratio
H, P
LRealization is to the control of converter switches pipe S.
Current detecting and comparison circuit IDC finish inductive current and detect and relatively produce the switch periods clock pulse signal V of the zero hour
C1: Fig. 2,3 illustrates, and current detection circuit ID detects inductive current I
LComparator AC1 will preset valley point current I
vWith inductive current I
LCompare; As inductive current I
LBe lower than default valley point current I
vThe time, the output signal V of comparator AC1
C1Be high level, otherwise, I worked as
LBe lower than I
vThe time, V
C1Be low level; Because inductive current I
LBe lower than default valley point current I
vConstantly, S is open-minded for the converter switches pipe, I
LBegin to rise the output signal V of comparator AC1
C1Be a series of narrow pulse signals.
Pulse selector PS finishes the comparison of output voltage and the selection of control impuls: Fig. 2,4 illustrates, and comparator AC2 is with output voltage V
oSame reference voltage V
RefCompare, work as output voltage V
oBe lower than reference voltage V
RefThe time, the output signal V of comparator AC2
C2Be low level, otherwise, V worked as
oBe lower than V
RefThe time, V
C2Be high level; Work as V
C1Rising edge comes interim, and d type flip flop DFF is the output signal V of comparator AC2 at this moment
C2Export the Q end to, produce pulse selecting signal V
Q, according to the operation principle of trigger: V
QAt V
C1Next rising edge remain unchanged before arriving, and
Level height all the time with V
QOn the contrary.
Pulse generator PG finishes generation and the output of control impuls: Fig. 2,5 illustrates, and works as V
C1Rising edge comes interim, the S end input high level of rest-set flip-flop RSFF1, the control wave P of RSFF1 output
LBe high level, when single triggering timing device OOT1 clocks end, the R end input high level of rest-set flip-flop RSFF1, the control wave P of RSFF1 output
LBecome low level; The course of work of rest-set flip-flop RSFF2 and above-mentioned RSFF1 are similar, but because the single triggering timing device of the R termination of RSFF2 OOT2, and the duration that clocks of single triggering timing device OOT2 is greater than the duration that clocks of single triggering timing device OOT1, the control wave P of RSFF2 output
HHigh level lasting time greater than P
LAs pulse selecting signal V
QBe high level,
During for low level, AG1 is open-minded with door, and AG2 is blocked, or door OG output control pulse P
LTo drive circuit; Otherwise, as pulse selecting signal V
QBe low level,
During for high level, AG2 is open-minded with door, and AG1 is blocked, or door OG output control pulse P
HTo drive circuit.
This routine converter is the Buck converter.
With PSIM software this routine method is carried out the time-domain-simulation analysis, the result is as follows.
The above-mentioned control method of employing that Fig. 6 obtains for emulation and the work wave of converter under the nominal operation state of control device thereof.Fig. 6 a, Fig. 6 b, Fig. 6 c, Fig. 6 d, Fig. 6 e, Fig. 6 f are respectively converter inductive current I
L, switch periods zero hour clock pulse signal V
C1, control wave P
H, control wave P
L, imitate control wave V
P, the converter output voltage V
oAs can be seen from Figure 6,13 switch periods are formed cycle period, and the pulse train that the control impuls of switching tube S is formed is: 1P
H-5P
L-1P
H-6P
LThere is not the low-frequency fluctuation phenomenon in converter, the about 17mV of converter output voltage ripple.
Fig. 7 is the work wave of existing pulse train control change device under the nominal operation state.Fig. 7 a, Fig. 7 b, Fig. 7 c are respectively P in the effective control wave of converter
HP in pulse, the effective control wave
LPulse, converter output voltage V
oThe time-domain-simulation oscillogram.As can be seen from Figure 6, when converter is operated in continuous mode, control wave P
HWith control wave P
LContinuously as effective control impuls, the low-frequency fluctuation phenomenon appears in converter, the about 0.85V of converter output voltage ripple, converter output voltage ripple 17mV in the embodiment of the invention one.But so adopt the low-frequency fluctuation phenomenon of converter suppressor pulse sequence of the present invention control continuous operation mode switch converters, make the working range of controlled converter not be subjected to the restriction of pulse train control change device inductive current critical condition.
Embodiment two
Fig. 8 illustrates, and this example is basic identical with embodiment one, and difference is: the converter TD of the Switching Power Supply of this example control is the Boost converter.
Embodiment three
Fig. 9 illustrates, and this example is basic identical with embodiment one, and difference is: the converter TD of the Switching Power Supply of this example control is the Buck-Boost converter.
The inventive method can realize with analogue device or digital device easily; The Switching Power Supply that converter in can be used for above embodiment is formed, also can be used for multiple power circuit such as Cuk converter, BIFRED converter, anti exciting converter, half-bridge converter, full-bridge converter and form Switching Power Supply.
Claims (8)
1. partly stagnating of continuous operation mode Switching Power Supply encircled pulse sequence control method, the half stagnant ring pulse train regulating system of being formed the continuous operation mode Switching Power Supply by converter TD and controller, its working method comprises: in the initial moment of each switch periods, select effective control impuls in this switch periods according to switch converters output voltage control impuls selective rule, thereby realize the control to the continuous operation mode switch converters; Its control impuls selective rule is: if V
oBe lower than V
Ref, adopt control impuls P
HSwitching tube S in the control switch converter; Otherwise, if V
oBe higher than V
Ref, adopt control impuls P
LControl switch pipe S.
2. half of continuous operation mode Switching Power Supply as claimed in claim 1 stagnant ring pulse sequence control method is characterized in that: described generation control impuls P
HMethod be:
At the initial t of certain switch periods
0Constantly, single triggering timing device picks up counting control impuls P
HBecome high level by low level, the switching tube S among the converter TD is open-minded, inductive current I
LRise; At t
0+ τ
On_HConstantly, single triggering timing device finishes timing, control impuls P
HKeeping high level fix time τ
On_HAfter become low level, switching tube S turn-offs, diode D is open-minded, inductive current descends; Drop to default inductive current valley I at inductive current
vConstantly, control impuls P
HKeeping low level time τ
Off_HAfter become high level, single triggering timing device picks up counting again, switching tube S is open-minded again, converter enters next switch periods;
Produce control impuls P
LMethod and said process similar, the difference be at a switch periods inner control pulse P
LFor the low level duration is τ
On_L, τ
On_L＜τ
On_H
3. half of continuous operation mode Switching Power Supply as claimed in claim 1 stagnant ring pulse sequence control method is characterized in that described default inductive current valley I
vProduce the inductive current valley relevant with input variable or output variable for the inductive current valley of directly setting or by input, output feedback quantity.
4. half of the continuous operation mode Switching Power Supply as claimed in claim 2 ring pulse sequence control method that stagnates is characterized in that, the duration τ of described default high level
On_HWith low level duration τ
On_LBe the constant ON time of directly setting, or produce the constant ON time relevant with input variable or output variable by input, output feedback quantity.
5. realize the stagnate device of ring pulse train of half of claim 1 or 2 or 3 or 4 described realization continuous operation mode Switching Power Supplies for one kind, formed by converter TD and controller, controller comprises voltage detecting circuit VD, current detecting and comparison circuit IDC, pulse selector PS, pulse generator PG, single triggering timing device OOT1, single triggering timing device OOT2, drive circuit DR, it is characterized in that: current detecting links to each other with pulse selector PS, pulse generator PG, single triggering timing device OTT1, single triggering timing device OTT2 with comparison circuit IDC; Voltage detecting circuit VD, pulse selector PS, pulse generator PG, drive circuit are connected to DR successively; Pulse generator PG links to each other with comparison circuit IDC, single triggering timing device OOT1, single triggering timing device OOT2 with current detecting.
6. device according to claim 5, it is characterized in that: described current detecting and comparison circuit IDC specifically consist of: the positive polarity termination of comparator AC1 is preset valley point current I
v, the inductive current I of negative polarity termination current detection circuit ID output
L
7. device according to claim 5 is characterized in that: specifically the consisting of of described pulse selector: be made up of comparator AC2 and d type flip flop DFF; The converter output voltage V of the positive polarity termination voltage detecting circuit VD output of comparator AC2
o, negative polarity termination reference voltage V
Ref, the output of AC2 links to each other with the D end of d type flip flop DFF.
8. device according to claim 5 is characterized in that: specifically the consisting of of described pulse generator: by rest-set flip-flop RSFF1 and rest-set flip-flop RSFF2, with door AG1 and with door AG2, and or door OG form; The S end of rest-set flip-flop RSFF1 and RSFF2 all meets the output signal V of current detecting and comparison circuit
C1, the output signal V of R end difference order triggering timing device OOT1 and OOT2
TLAnd V
THWith the Q end of the input termination rest-set flip-flop RSFF1 of door AG1 and the Q end of trigger DFF, hold with the Q of the input termination rest-set flip-flop RSFF2 of door AG2 and trigger DFF
End; Or the output of the input termination of door OG and door AG1 and AG2, the drive circuit DR of the output termination switching tube S of OG1.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201310104554.1A CN103236790B (en) | 2013-03-28 | 2013-03-28 | Method and device for controlling half-hysteresis ring pulse sequences of switching power supply in continuous working mode |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201310104554.1A CN103236790B (en) | 2013-03-28 | 2013-03-28 | Method and device for controlling half-hysteresis ring pulse sequences of switching power supply in continuous working mode |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN103236790A true CN103236790A (en) | 2013-08-07 |
| CN103236790B CN103236790B (en) | 2015-03-25 |
Family
ID=48884813
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201310104554.1A Expired - Fee Related CN103236790B (en) | 2013-03-28 | 2013-03-28 | Method and device for controlling half-hysteresis ring pulse sequences of switching power supply in continuous working mode |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN103236790B (en) |
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104052280A (en) * | 2014-06-15 | 2014-09-17 | 西南交通大学 | Multi-valley point current type impulse sequence control method and device for continuous operating mode switching power supply |
| CN106208687A (en) * | 2016-09-26 | 2016-12-07 | 中国矿业大学 | Self adaptation valley point current type pulse sequence control method and device thereof |
| CN107769606A (en) * | 2017-12-05 | 2018-03-06 | 西南交通大学 | Capacitance current bifrequency pulse sequence control method and its device |
| CN111313703A (en) * | 2020-03-18 | 2020-06-19 | 广州大学 | Pulse sequence controlled PCCM Buck converter |
| CN113315374A (en) * | 2021-05-28 | 2021-08-27 | 电子科技大学 | Duty ratio modulation pulse sequence control method and device based on Buck converter |
| WO2023036220A1 (en) * | 2021-09-09 | 2023-03-16 | 广州金升阳科技有限公司 | Peak and valley turn-on control method and controller |
| CN114257140B (en) * | 2020-09-25 | 2024-05-31 | 苏州福瑞思信息科技有限公司 | Brushless DC motor starting device and starting method |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20020057080A1 (en) * | 2000-06-02 | 2002-05-16 | Iwatt | Optimized digital regulation of switching power supply |
| CN101814832A (en) * | 2010-04-12 | 2010-08-25 | 西南交通大学 | Improved pulse sequence control method of switch power supply and device thereof |
-
2013
- 2013-03-28 CN CN201310104554.1A patent/CN103236790B/en not_active Expired - Fee Related
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20020057080A1 (en) * | 2000-06-02 | 2002-05-16 | Iwatt | Optimized digital regulation of switching power supply |
| CN101814832A (en) * | 2010-04-12 | 2010-08-25 | 西南交通大学 | Improved pulse sequence control method of switch power supply and device thereof |
Non-Patent Citations (1)
| Title |
|---|
| 高玉: "脉冲序列控制CCM Buck变换器研究", 《中国优秀硕士学位论文全文数据库工程科技II辑》, no. 10, 15 October 2012 (2012-10-15), pages 6 - 20 * |
Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104052280A (en) * | 2014-06-15 | 2014-09-17 | 西南交通大学 | Multi-valley point current type impulse sequence control method and device for continuous operating mode switching power supply |
| CN106208687A (en) * | 2016-09-26 | 2016-12-07 | 中国矿业大学 | Self adaptation valley point current type pulse sequence control method and device thereof |
| CN107769606A (en) * | 2017-12-05 | 2018-03-06 | 西南交通大学 | Capacitance current bifrequency pulse sequence control method and its device |
| CN107769606B (en) * | 2017-12-05 | 2023-10-20 | 西南交通大学 | Capacitive current double-frequency pulse sequence control method and device thereof |
| CN111313703A (en) * | 2020-03-18 | 2020-06-19 | 广州大学 | Pulse sequence controlled PCCM Buck converter |
| CN114257140B (en) * | 2020-09-25 | 2024-05-31 | 苏州福瑞思信息科技有限公司 | Brushless DC motor starting device and starting method |
| CN113315374A (en) * | 2021-05-28 | 2021-08-27 | 电子科技大学 | Duty ratio modulation pulse sequence control method and device based on Buck converter |
| WO2023036220A1 (en) * | 2021-09-09 | 2023-03-16 | 广州金升阳科技有限公司 | Peak and valley turn-on control method and controller |
Also Published As
| Publication number | Publication date |
|---|---|
| CN103236790B (en) | 2015-03-25 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN103236790B (en) | Method and device for controlling half-hysteresis ring pulse sequences of switching power supply in continuous working mode | |
| CN101242134B (en) | Switch power control method and its device | |
| CN101505098A (en) | Multi-stage pulse sequence control method of pseudo-continuous working mode and apparatus thereof | |
| CN102223067B (en) | Device and method for driving constant-current source load | |
| CN103066823B (en) | Controller and control method of switch power source | |
| CN105356746A (en) | Conduction time generation circuit for power supply converter, and power supply converter | |
| CN103326546A (en) | Fixed turn-off time peak current type pulse sequence control method and fixed turn-off time peak current type pulse sequence control device | |
| CN104638913A (en) | Double-loop voltage type PFM (Pulse Frequency Modulation) control method for single-inductor double-output switch transformer and device for double-loop voltage type PFM control method | |
| CN102655371A (en) | Double-pulse cross-cycle modulation method for switching power supply and device thereof | |
| CN103414342A (en) | Fixed-frequency constant on-off time control method of dynamic voltage regulating switch converter | |
| CN106300964B (en) | Independent charge and discharge sequential single-inductance double-output switch converters method for controlling frequency conversion and its device | |
| CN203261226U (en) | Semi-hysteresis pulse train controlling device of switch power supply in continuous working mode | |
| CN104470158A (en) | Voltage-reduction structure LED driving circuit, and constant current driver and design method thereof | |
| CN101814832B (en) | Improved pulse sequence control method of switch power supply and device thereof | |
| CN104052280A (en) | Multi-valley point current type impulse sequence control method and device for continuous operating mode switching power supply | |
| CN201417403Y (en) | Constant power control device of switch power supply | |
| CN201352762Y (en) | Multi-level impulse sequence control device for switch power supply in pseudo continuous work mode | |
| CN101777832B (en) | Single-loop pulse regulating and controlling method and device of pseudo continuous mode switch power supply | |
| CN110460237B (en) | Control method and device for PCCM Boost converter | |
| CN203933397U (en) | Many valley point currents type pulse-sequence control device of continuous operation mode Switching Power Supply | |
| CN105186861B (en) | Pseudo- continuous conduction mode switch converters determine afterflow Duty ratio control method and its device | |
| CN204465341U (en) | A kind of single inductance dual output switch converters dicyclo voltage-type PFM control device | |
| CN202167985U (en) | Quasi-resonance control device and switching regulator comprising same | |
| CN204272471U (en) | Buck configuration LED drive circuit and constant-current driver thereof | |
| CN201656775U (en) | Switching power supply monocyclic fixed-frequency hysteresis-loop control device |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| CF01 | Termination of patent right due to non-payment of annual fee | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20150325 Termination date: 20180328 |