CN103166673B - Ultra broadband ICS wireless discharging-directly station - Google Patents

Abstract

The present invention relates to a kind of radio transmission system, particularly relate to a kind of ultra broadband ICS wireless discharging-directly station.Ultra broadband ICS wireless discharging-directly station of the present invention, comprises the first dual-mode antenna, analog down, digital module, simulation up-conversion and the second dual-mode antenna that connect in turn; Wherein, described digital module comprises the ADC analog-to-digital conversion module, DDC module, noise adaptive cancellation module, DUC module and the DAC D/A converter module that connect in turn; Described noise adaptive cancellation module comprises: the time delay abstraction module to the division of signal after DDC resume module being N number of subband signal, for carrying out the LMS module of Adaptive Signal Processing to N number of subband signal, and by interpolation time delay module that the N number of subband signal after LMS resume module is reconstructed.The present invention is used under the prerequisite of not obvious reduction performance, saves consumption of natural resource.

Description

Ultra broadband ICS wireless discharging-directly station

Technical field

The present invention relates to a kind of radio transmission system, particularly relate to a kind of ultra broadband ICS wireless discharging-directly station.

Background technology

Along with the develop rapidly of China's mobile communication cause, mobile communication subscriber amount just constantly increases, so that cellular plans is more and more less, base station location is more and more lower; Repeater is a kind of not enough for making up base station coverage in mobile network, expands base station range, fills the extremely effective equipment of one of coverage hole.

For ICS wireless discharging-directly station, its principle is general as shown in Figure 1, generally comprise the first dual-mode antenna, analog down, digital module, simulation up-conversion and the second dual-mode antenna, wherein, digital module mainly comprises the ADC analog-to-digital conversion module, DDC (the Digital Down Converter that connect in turn, digital down converter) module, DUC (Digital Up Converter, digital up converter) module and DAC D/A converter module.In said system, inevitably, a lot of noise can be produced to the transmitting-receiving process of the first antenna from the second antenna, the bandwidth disturbed due to required stress release treatment is wider, resource consumption is larger, if the design in theory with roomy ICS wireless discharging-directly station will with the ICS wireless discharging-directly station of narrow bandwidth be designed with same performance, the resource consumed is (band1/band2) ²; And general LMS module (or the deformation module of LMS module, such as Normalized LMS Algorithm etc.) that only adopts solves the problem of noise in prior art, above-mentioned way can only solve the problem of resource consumption by reducing performance.

Summary of the invention

Technical problem to be solved by this invention is, provides a kind of ultra broadband ICS wireless discharging-directly station, on the basis of existing LMS module, in conjunction with fft filters group, under the prerequisite of not obvious reduction performance, saves ample resources, to solve the deficiency of prior art.

In order to solve the problems of the technologies described above, ultra broadband ICS wireless discharging-directly station of the present invention, comprises the first dual-mode antenna, analog down, digital module, simulation up-conversion and the second dual-mode antenna that connect in turn; Wherein, described digital module comprises the ADC analog-to-digital conversion module, DDC module, noise adaptive cancellation module, DUC module and the DAC D/A converter module that connect in turn; Described noise adaptive cancellation module comprises: the time delay abstraction module to the division of signal after DDC resume module being N number of subband signal, for carrying out the LMS module of Adaptive Signal Processing to N number of subband signal, and by interpolation time delay module that the N number of subband signal after LMS resume module is reconstructed.Wherein, time delay abstraction module splits into 16 passages original signal, the function of Realization analysis filter.16 passages are merged into a passage by time delay abstraction module, realize the function of synthesis filter.

Further, described time delay abstraction module comprises:

N number of delay unit and N number of extracting unit: first delay unit and first extracting unit are by the data after DDC resume module, and every K data pick-up 1, obtains first subband signal, be designated as X ₀; Second delay unit and second extracting unit are by the data after DDC resume module, and after time delay clock, every K data pick-up 1, obtains second subband signal, be designated as X ₁; N number of delay unit and N number of extracting unit are by after the data delay N-1 clock after DDC resume module, and every K data pick-up 1, obtains N number of subband signal, be designated as X _n-1; N>=1; K is extracting multiple, K>=1;

First passage computing module: by above-mentioned N number of subband signal X ₀, X ₂... X _n-1carry out computing respectively, and the data that computing draws respectively are designated as V ₀, V ₂... V _n-1;

IFFT changes module: the data V drawn by first passage computing module ₀, V ₂... V _n-1respectively through IFFT change, and be designated as data by respectively through the data drawn after IFFT change ₀, data ₁... data _n-1;

Described interpolation time delay module comprises:

FFT changes module: IFFT is changed the data data that module draws ₀, data ₁... data _n-1after LMS resume module, then carry out FFT change, i.e. the data obtained are designated as U by the inversion of IFFT change ₀, U ₁... U _n-1;

Second channel computing module: FFT is changed the data U that module obtains ₀, U ₁... U _n-1carry out computing respectively, the data obtained are designated as Y ₀, Y ₁... Y _n-1;

N number of interpolating unit and N number of delay unit: the data obtained by second channel computing module carry out interpolation and time delay, specifically: insert K-1 zero between the adjacent values in the data that first interpolating unit and first delay unit obtain at second channel computing module, then time delay N-1 clock; K-1 zero is inserted, then time delay N-2 clock between adjacent values in the data that second interpolating unit and second delay unit obtain at second channel computing module; K-1 zero is inserted, then time delay 0 clock between adjacent values in the data that N number of interpolating unit and N number of delay unit obtain at second channel computing module; Finally obtain the signal after noise adaptive cancellation.Wherein K is the interpolation multiple of interpolating unit, such as K=8, then insert 7 zero between adjacent values.

In said process, change module for FFT, after being positioned at time delay abstraction module, the extracting unit of time delay abstraction module is for changing sampling rate, and therefore after time delay abstraction module, its speed diminishes, and at identical system clock, just can run multiple cycle.

Extracting unit in said process and interpolating unit are respectively used to change sampling rate, generally can usage data withdrawal device and the realization of data interpolating device.

Further, described first passage computing module comprises N number of path computation unit, with above-mentioned, the data that first passage computing module draws is designated as V ₀, V ₂... V _n-1, V _jfor a jth data that path computation unit calculates, V _jbe calculated as follows: V _j=X _j× (fir _j) ^t, N>=1, N-1>=j>=0;

Wherein, X _jfor a jth delay unit and a jth extracting unit) the jth subband signal that obtains; Fir is a row matrix, is expressed as follows: fir=[fir ₀, fir ₁, fir ₂..., fir _j... fir _l-1]; L>A × N, N are port number, A>1.Fir is prototype filter weights, considers the design effect of resource consumption and prototype filter, preferably makes the weights number L=64 of this prototype filter, so N=16, then have 16 passages.

(fir _j) ^trefer to fir _jtranspose of a matrix, is converted to column matrix by row matrix.

X _j=[X _j, X _j-1, X _j-2, X _j-3]; Namely four the up-to-date data after primary signal extracts are obtained;

Fir _j=[fir _j+0, fir _j+16, fir _j+32, fir _j+48]; J is channel number, and if any 16 passages, then j span is 0-15.Such as the 0th passage, fir ₀=[fir ₀, fir ₁₆, fir ₃₂, fir ₄₈].

Further, described second channel computing module comprises N number of path computation unit, with above-mentioned, the data that second channel computing module obtains is designated as Y ₀, Y ₁... Y _n-1, Y _ibe the data that i-th path computation unit calculates, Y _ibe calculated as follows: Y _i=U _i× (fir _i) ^t, N>=1, N-1>=i>=0;

Wherein, U _ifor i-th data that FFT change module obtains; Fir is a row matrix, is expressed as follows: fir=[fir ₀, fir ₁, fir ₂..., fir _i... fir _l-1]; L>A × N, N are port number, A>1.(fir _i) ^trefer to fir _itranspose of a matrix, is converted to column matrix by row matrix.

U _i=[U _i, U _i-1, U _i-2, U _i-3]; Namely four the up-to-date data after FFT change module are obtained;

Fir _i=[fir _15-i, fir _31-i, fir _47-i, fir _63-i], i is channel number, and if any 16 passages, then i span is 0-15.Such as the 0th passage, fir ₀=[fir ₁₅, fir ₃₁, fir ₄₇, fir ₆₃].

In said process, fir is calculated as follows:

Fir is prototype filter weights.By time delay abstraction module and interpolation time delay module, LMS module is carried out adopting different sample rates before and after signal transacting respectively.

$\underset{\underset{n\≠0}{n}}{\mathrm{\Σ}}\left|\underset{l}{\mathrm{\Σ}}p\right[l]p{[l-\mathrm{Nn}]|}^2\≤{\mathrm{\ϵ}}_r^2$

Wherein, n≤L/N-1; L is the weights number (such as L gets 64) of prototype filter, l<L-1; represent the distortion level of output, the design's value 10 ^-8.N is the port number (such as N=16, i.e. 16 passages) of second channel computing module.The meaning of this formula is exactly to make the distortion after reconstructing little

Next about the computing formula of energy:

$H\left(\mathrm{\&omega;}\right)=e^{-j{L}_a\mathrm{\&omega;}/2}\underset{n=0}{\overset{L_a^{\&prime;}}{\mathrm{\&Sigma;}}}2h\left(n\right)\cos \left((L_a^{\&prime;}+0.5-n)\mathrm{\&omega;}\right),L_a={2L}_a^{\&prime;}+1$

Wherein, La=L-1, namely weights number subtracts one; Such as L=64, then La=63;

Due to | H (w) | ²=H (w) * H (w) '; So there is Exp (-jLaw/2) * Exp (-jLaw/2) '=1;

| P (e ^jw) | ²=| H (w) | ², this formula represents the numerical value of energy at different frequency, and w span is 0-2 л.This formula illustrates the energy size of this group filter weights on different frequency w.

| P (e ^jw) | ²≤ ∈ sb, w ∈ [л/K, л], represents cut-off frequency energy; K is the extracting multiple of extracting unit.

Therefore the target of Semidefinite Programming and unbound document can be expressed as follows, target:

$\underset{\underset{1\&le;l\&le;L-1}{p\left[l\right]}}{\min }\frac{1}{2}{\&Integral;}_{\mathrm{\&pi;}/K}^{2\mathrm{\&pi;}-\mathrm{\&pi;}/K}{\left|P\left(e^{\mathrm{jw}}\right)\right|}^2\mathrm{dw}$

Constraints:

1.|P (e ^jw) | ²≤ ∈ sb, w ∈ [л/K, л]; Wherein, ∈ sb<10 ^-8, K is sampling multiple;

2.|P (e ^jw1) | ²-| P (e ^jw2) | ²≤ 0; W1>w2, w1 ∈ [л/K, л/N], w2 ∈ [л/K, л/N]; K is sampling multiple, and N is port number;

3.p[b]＝p[63-b]，0≤b≤31；

4. $\underset{l}{\mathrm{\&Sigma;}}p{\left[l\right]}^2=K/N;$

5. $\underset{l}{\mathrm{\&Sigma;}}p\left[l\right]=\sqrt{K},$

6. $\underset{\underset{n\&NotEqual;0}{n}}{\mathrm{\&Sigma;}}\left|\underset{l}{\mathrm{\&Sigma;}}p\right[l]p{[l-\mathrm{Nn}]|}^2\&le;{\mathrm{\&epsiv;}}_r^2.$

Prototype filter weights fir can be obtained after carrying out fmincon function Semidefinite Programming finally by matlab tool box software, because plan constraint condition is applicable to sub-band adaptive filtering design, so the prototype filter weights fir obtained more is conducive to the performance of adaptive-filtering.

Noise adaptive cancellation module in this patent be based on prototype filter design bank of filters (bank of filters has used fast fourier transform, therefore fft filters group is referred to as), the performance of fft filters group and the design of prototype filter have very large relation, because the design is applied to super large bandwidth, so the distortion process after reconstruct is of paramount importance, if the design of filter weights fir is more partial to distortion performance, other performances will weaken, and therefore the quality of the fewer signal of distortion is better.The present invention passes through to the restriction of the distortion level of output, and then obtain a good signal.Secondly, if the aliasing of each subband is fewer, then each sef-adapting filter influences each other fewer, same, by achieving the good design of filter weights fir, the aliasing of each subband is reduced to minimum.In addition, by the cooperation of time delay abstraction module, LMS module, interpolation time delay module, when not too reducing performance, save ample resources.

Accompanying drawing explanation

Fig. 1 is the theory diagram of ICS wireless discharging-directly station;

Fig. 2 is the theory diagram of digital module in ICS wireless discharging-directly station of the present invention;

Fig. 3 is the theory diagram of noise adaptive cancellation module in digital module of the present invention;

Fig. 4 is the detailed schematic diagram of noise adaptive cancellation module in digital module of the present invention;

Fig. 5 is the theory diagram of LMS module in noise adaptive cancellation module of the present invention;

Embodiment

Now the present invention is further described with embodiment by reference to the accompanying drawings.

Ultra broadband ICS wireless discharging-directly station of the present invention, comprises the first dual-mode antenna, analog down, digital module, simulation up-conversion and the second dual-mode antenna that connect in turn; Wherein, as shown in Figure 2, described digital module comprises the ADC analog-to-digital conversion module 1, DDC module 2, noise adaptive cancellation module 3, DUC module 4 and the DAC D/A converter module 5 that connect in turn.As shown in Figure 3, described noise adaptive cancellation module 3 comprises: the time delay abstraction module 31 to the division of signal after DDC resume module being N number of subband signal, for carrying out the LMS module 32 of Adaptive Signal Processing to N number of subband signal, and the interpolation time delay module 33 that the N number of subband signal after LMS module 32 being processed is reconstructed.Wherein, time delay abstraction module 31 splits into 16 passages original signal, the function of Realization analysis filter.16 passages are merged into a passage by time delay abstraction module 33, realize the function of synthesis filter.

In the present embodiment, adopt 16 passages, i.e. N=16.

Wherein, as shown in Figure 4, described time delay abstraction module 31 comprises:

16 (delay unit+extracting unit) (being also 16 delay units and 16 extracting units): first (delay unit+extracting unit) is by the data after DDC resume module, every 8 data pick-ups 1, obtain first subband signal, be designated as X ₀; Second (delay unit+extracting unit), by the data after DDC resume module, after time delay clock, every 8 data pick-ups 1, obtain second subband signal, are designated as X ₁; 16th (delay unit+extracting unit), by after 15 clocks of the data delay after DDC resume module, every 8 data pick-ups 1, obtain the 16th subband signal, are designated as X ₁₅; Wherein, the 1st (delay unit+extracting unit) does not have time delay.

First passage computing module: by above-mentioned 16 subband signal X ₀, X ₂... X ₁₅carry out computing respectively, and the data that computing draws respectively are designated as V ₀, V ₂... V ₁₅;

IFFT (Inverse Fast Fourier Transform, inverse fast Fourier transform) changes module: the data V drawn by first passage computing module ₀, V ₂... V ₁₅respectively through IFFT change, and be designated as data by respectively through the data drawn after IFFT change ₀, data ₁... data ₁₅;

Described interpolation time delay module 33 comprises:

FFT (Fast Fourier Transform, fast Fourier transform) changes module: IFFT is changed the data data that module draws ₀, data ₁... data ₁₅after LMS resume module, then carry out FFT change, i.e. the data obtained are designated as U by the inversion of IFFT change ₀, U ₁... U ₁₅;

Second channel computing module: FFT is changed the data U that module obtains ₀, U ₁... U ₁₅carry out computing respectively, the data obtained are designated as Y ₀, Y ₁... Y ₁₅;

16 (interpolating unit and delay unit) (being also 16 interpolating unit and 16 delay units): the data obtained by second channel computing module carry out interpolation and time delay, specifically: between the adjacent values in the data that first (interpolating unit and delay unit) obtains at second channel computing module, insert 0 zero, then time delay 1 clock; 1 zero is inserted, then time delay 2 clocks between adjacent values in the data that second (interpolating unit and delay unit) obtains at second channel computing module; 15 zero are inserted, then time delay 16 clocks between adjacent values in the data that 16th (interpolating unit and delay unit) obtains at second channel computing module; Finally obtain the signal after noise adaptive cancellation.

In said process, FFT for interpolation time delay module 33 changes module, after being positioned at time delay abstraction module 31, the extracting unit of time delay abstraction module 31 is for changing sampling rate, therefore after time delay abstraction module 31, its speed diminishes, and at identical system clock, just can run multiple cycle.

Extracting unit in said process and interpolating unit are respectively used to change sampling rate, generally can usage data withdrawal device and the realization of data interpolating device.

Described first passage computing module comprises 16 path computation unit, with above-mentioned, the data that first passage computing module draws is designated as V ₀, V ₂... V ₁₅, V _jfor a jth data that path computation unit calculates, V _jbe calculated as follows: V _j=X _j× (fir _j) ^t, 15>=j>=0.

Wherein, X _jfor the jth subband signal that jth (delay unit+extracting unit) obtains; Fir is a row matrix, is expressed as follows: fir=[fir ₀, fir ₁, fir ₂..., fir _j... fir _l-1]; L>A × N, N are port number, A>1.Fir is prototype filter weights, considers the design effect of resource consumption and prototype filter, makes the weights number L=64 of this prototype filter in the present embodiment.(fir _j) ^trefer to fir _jtranspose of a matrix, is converted to column matrix by row matrix.

X _j=[X _j, X _j-1, X _j-2, X _j-3]; Namely four the up-to-date data after primary signal extracts are obtained;

Fir _j=[fir _j+0, fir _j+16, fir _j+32, fir _j+48]; J is channel number, and j span is 0-15.Such as the 0th passage, fir ₀=[fir ₀, fir ₁₆, fir ₃₂, fir ₄₈].

Described second channel computing module comprises 16 path computation unit, with above-mentioned, the data that second channel computing module obtains is designated as Y ₀, Y ₁... Y ₁₅, Y _ibe the data that i-th path computation unit calculates, Y _ibe calculated as follows: Y _i=U _i× (fir _i) ^t, 15>=i>=0;

Wherein, U _ifor i-th data that FFT change module obtains; Fir is a row matrix, is expressed as follows: fir=[fir ₀, fir ₁, fir ₂..., fir _i... fir _l-1]; L>A × N, N are port number, A>1.(fir _i) ^trefer to fir _itranspose of a matrix, is converted to column matrix by row matrix.

U _i=[U _i, U _i-1, U _i-2, U _i-3]; Namely four the up-to-date data after FFT change module are obtained;

Fir _i=[fir _15-i, fir _31-i, fir _47-i, fir _63-i], i is channel number, and i span is 0-15.Such as the 0th passage, fir ₀=[fir ₁₅, fir ₃₁, fir ₄₇, fir ₆₃].

In said process, fir is calculated as follows:

Fir is prototype filter weights.By time delay abstraction module and interpolation time delay module, LMS module is carried out adopting different sample rates before and after signal transacting respectively, $\underset{\underset{n\&NotEqual;0}{n}}{\mathrm{\&Sigma;}}\left|\underset{l}{\mathrm{\&Sigma;}}p\right[l]p{[l-\mathrm{Nn}]|}^2\&le;{\mathrm{\&epsiv;}}_r^2$

Wherein, n≤L/N-1; L is the weights number (such as L gets 64) of prototype filter, l<L-1; represent the distortion level of output, the design's value 10 ^-8.N is the port number (such as N=16, i.e. 16 passages) of second channel computing module.The meaning of this formula is exactly to allow the distortion after reconstructing be less than

Next about the computing formula of energy:

$H\left(\mathrm{\&omega;}\right)=e^{-j{L}_a\mathrm{\&omega;}/2}\underset{n=0}{\overset{L_a^{\&prime;}}{\mathrm{\&Sigma;}}}2h\left(n\right)\cos \left((L_a^{\&prime;}+0.5-n)\mathrm{\&omega;}\right),L_a={2L}_a^{\&prime;}+1$

Wherein, La=L-1, namely weights number subtracts one; Such as L=64, then La=63;

Due to | H (w) | ²=H (w) * H (w) '; So there is Exp (-jLaw/2) * Exp (-jLaw/2) '=1;

| P (e ^jw) | ²=| H (w) | ², this formula represents the numerical value of energy at different frequency, and w span is 0-2 л.This formula illustrates the energy size of this group filter weights on different frequency w.

| P (e ^jw) | ²≤ ∈ sb, w ∈ [л/K, л], represents cut-off frequency energy; K is the extracting multiple of extracting unit.

Therefore the target of Semidefinite Programming and unbound document can be expressed as follows, target:

$\underset{\underset{1\&le;l\&le;L-1}{p\left[l\right]}}{\min }\frac{1}{2}{\&Integral;}_{\mathrm{\&pi;}/K}^{2\mathrm{\&pi;}-\mathrm{\&pi;}/K}{\left|P\left(e^{\mathrm{jw}}\right)\right|}^2\mathrm{dw}$

Constraints:

1.|P (e ^jw) | ²≤ ∈ sb, w ∈ [л/K, л]; Wherein, ∈ sb<10 _-8, K is sampling multiple;

2.|P (e ^jw1) | ²-| P (e ^jw2) | ²≤ 0; W1>w2, w1 ∈ [л/K, л/N], w2 ∈ [л/K, л/N]; K is sampling multiple, and N is port number;

3.p[b]＝p[63-b]，0≤b≤31；

4. $\underset{l}{\mathrm{\&Sigma;}}p{\left[l\right]}^2=K/N;$

5. $\underset{l}{\mathrm{\&Sigma;}}p\left[l\right]=\sqrt{K},$

6. $\underset{\underset{n\&NotEqual;0}{n}}{\mathrm{\&Sigma;}}\left|\underset{l}{\mathrm{\&Sigma;}}p\right[l]p{[l-\mathrm{Nn}]|}^2\&le;{\mathrm{\&epsiv;}}_r^2.$

Prototype filter weights fir can be obtained after carrying out fmincon function Semidefinite Programming by matlab tool box software, because plan constraint condition is applicable to sub-band adaptive filtering design, so the prototype filter weights fir obtained more is conducive to the performance of adaptive-filtering.

Wherein, as shown in Figure 5, described LMS module 32 adopts existing basic adaptive filter algorithm.Those skilled in the art obtains by consulting related data, repeats no more here.

Illustrating the cooperation by time delay abstraction module 31 of the present invention, LMS module 32, interpolation time delay module 33 below, when not too reducing performance, saving ample resources.

For real number signal, the sampling rate of 30.72mhz, the time window of 4us, system clock is 30.72mhz.Normalized LMS algorithm: the weights of needs are that 30.72*4 is about 128, so each cycle needs 128+128+1=257 multiplier.The design coordinates the Normalized LMS algorithm of LMS module 32 by time delay abstraction module 31, interpolation time delay module 33: fft filters group 16 passages, 8 times of sampling, (30.72/8) * 4 is about 16, so each cycle needs (16+16+1) * 16/8=66 multiplier.Therefore the algorithm of the design is 1/3.89 of Normalized LMS algorithm, has saved a large amount of resources.

Certainly, the algorithm of the design needs the support of fft filters group, the resource of fft filters group under following introduction: suppose that the weights number L of prototype filter is 64, then FFT needs (64+ (16/2) * log2 (16))/8 to be about 12 multipliers, so analysis and synthesis bank of filters aggregate demand 12*2 multiplier, therefore Subband adaptive filters needs 66+12*2=90 multiplier in theory.So this algorithm is 1/2.8 of Normalized LMS algorithm.

In addition, if signal is plural number, the resource of fft filters group expands as original twice, and the resource of LMS algorithm needs to expand as original four times: so Subband adaptive filters is 12*4+66*4=312 multiplier; Normalized LMS algorithm needs 257*4=1028 multiplier.Therefore the algorithm of this patent is 1/3.29 of Normalized LMS algorithm.

In sum, by the design of noise adaptive cancellation module of the present invention, when not too reducing performance, save ample resources.

Although specifically show in conjunction with preferred embodiment and describe the present invention; but those skilled in the art should be understood that; not departing from the spirit and scope of the present invention that appended claims limits; can make a variety of changes the present invention in the form and details, be protection scope of the present invention.

Claims (3)

1. ultra broadband ICS wireless discharging-directly station, is characterized in that: comprise the first dual-mode antenna, analog down, digital module, simulation up-conversion and the second dual-mode antenna that connect in turn; Wherein, described digital module comprises the ADC analog-to-digital conversion module, DDC module, noise adaptive cancellation module, DUC module and the DAC D/A converter module that connect in turn; Described noise adaptive cancellation module comprises: the time delay abstraction module to the division of signal after DDC resume module being N number of subband signal, for carrying out the LMS module of Adaptive Signal Processing to N number of subband signal, and by interpolation time delay module that the N number of subband signal after LMS resume module is reconstructed;

Described time delay abstraction module comprises:

N number of delay unit and N number of extracting unit: first delay unit and first extracting unit are by the data after DDC resume module, and every K data pick-up 1, obtains first subband signal, be designated as X ₀; Second delay unit and second extracting unit are by the data after DDC resume module, and after time delay clock, every K data pick-up 1, obtains second subband signal, be designated as X ₁; N number of delay unit and N number of extracting unit are by after the data delay N-1 clock after DDC resume module, and every K data pick-up 1, obtains N number of subband signal, be designated as X _n-1; Wherein, N>=1; K is extracting multiple, K>=1;

First passage computing module: by above-mentioned N number of subband signal X ₀, X ₂... X _n-1carry out computing respectively, and the data that computing draws respectively are designated as V ₀, V ₂... V _n-1;

IFFT changes module: the data V drawn by first passage computing module ₀, V ₂... V _n-1respectively through IFFT change, and be designated as data by respectively through the data drawn after IFFT change ₀, data ₁... data _n-1;

Described interpolation time delay module comprises:

FFT changes module: IFFT is changed the data data that module draws ₀, data ₁... data _n-1after LMS resume module, then carry out FFT change, i.e. the data obtained are designated as U by the inversion of IFFT change ₀, U ₁... U _n-1;

Second channel computing module: FFT is changed the data U that module obtains ₀, U ₁... U _n-1carry out computing respectively, the data obtained are designated as Y ₀, Y ₁... Y _n-1;

N number of interpolating unit and N number of delay unit: the data obtained by second channel computing module carry out interpolation and time delay, specifically: insert K-1 zero between the adjacent values in the data that first interpolating unit and first delay unit obtain at second channel computing module, then time delay N-1 clock; K-1 zero is inserted, then time delay N-2 clock between adjacent values in the data that second interpolating unit and second delay unit obtain at second channel computing module; K-1 zero is inserted, then time delay 0 clock between adjacent values in the data that N number of interpolating unit and N number of delay unit obtain at second channel computing module; Finally obtain the signal after noise adaptive cancellation; Wherein K is extracting multiple, K >=1;

Described first passage computing module comprises N number of path computation unit, with above-mentioned, the data that first passage computing module draws is designated as V ₀, V ₂... V _n-1, V _jfor a jth data that path computation unit calculates, V _jbe calculated as follows: V _j=X _j× (fir _j) ^t, N>=1, N-1>=j>=0;

Wherein, X _jfor the jth subband signal that a jth delay unit and a jth extracting unit obtain; Fir is a row matrix, is expressed as follows: fir=[fir ₀, fir ₁, fir ₂..., fir _j... fir _l-1]; L>A × N, N are port number, A>1; (fir _j) ^trefer to fir _jtranspose of a matrix;

Described second channel computing module comprises N number of path computation unit, with above-mentioned, the data that second channel computing module obtains is designated as Y ₀, Y ₁... Y _n-1, Y _ibe the data that i-th path computation unit calculates, Y _ibe calculated as follows: Y _i=U _i× (fir _i) ^t, N>=1, N-1>=i>=0;

Wherein, U _ifor i-th data that FFT change module obtains; Fir is a row matrix, is expressed as follows: fir=[fir ₀, fir ₁, fir ₂..., fir _j... fir _l-1]; L>A × N, N are port number, A>1; (fir _i) ^trefer to fir _itranspose of a matrix;

Described fir obtains after carrying out fmincon function Semidefinite Programming by matlab software, and target and the unbound document of its Semidefinite Programming are as follows:

A.|P (e ^jw) | ²≤ ∈ _sb, w ∈ [л/K, л]; Wherein, ∈ _sb<10 ^-8, K is sampling multiple;

b.|P(e ^jw1)| ²-|P(e ^jw2)| ²≤0；w1>w2，w1∈[л/K,л/N]，w2∈[л/K,л/N]；

K is sampling multiple, and N is port number;

c.p[b]＝p[63-b]，0≤b≤31；

d. $\underset{l}{\mathrm{\&Sigma;}}p{\left[l\right]}^2=K/N;$

e. $\underset{l}{\mathrm{\&Sigma;}}p\left[l\right]=\sqrt{K},$

f. $\underset{n\&NotEqual;0}{\underset{n}{\mathrm{\&Sigma;}}}{\left|\underset{l}{\mathrm{\&Sigma;}}p\right[l\left]p\right[l-\mathrm{Nn}\left]\right|}^2\&le;{\mathrm{\&epsiv;}}_r^2.$

2. ultra broadband ICS wireless discharging-directly station according to claim 1, is characterized in that: N=16.

3. ultra broadband ICS wireless discharging-directly station according to claim 1, is characterized in that: described fir obtains after carrying out fmincon function Semidefinite Programming by matlab software, and target and the unbound document of its Semidefinite Programming are as follows:

A.|P (e ^jw) | ²≤ ∈ _sb, w ∈ [л/K, л]; Wherein, ∈ _sb<10 ^-8, K is sampling multiple;

b.|P(e ^jw1)| ²-|P(e ^jw2)| ²≤0；w1>w2，w1∈[л/K,л/N]，w2∈[л/K,л/N]；

K is sampling multiple, and N is port number;

c.p[b]＝p[63-b]，0≤b≤31；

d. $\underset{l}{\mathrm{\&Sigma;}}p{\left[l\right]}^2=K/N;$

e. $\underset{l}{\mathrm{\&Sigma;}}p\left[l\right]=\sqrt{K},$

f. $\underset{n\&NotEqual;0}{\underset{n}{\mathrm{\&Sigma;}}}{\left|\underset{l}{\mathrm{\&Sigma;}}p\right[l\left]p\right[l-\mathrm{Nn}\left]\right|}^2\&le;{\mathrm{\&epsiv;}}_r^2.$