CN102882382A - Power-frequency power supplied electromagnetic device capable of running at magnetic flux frequency lower than power frequency - Google Patents
Power-frequency power supplied electromagnetic device capable of running at magnetic flux frequency lower than power frequency Download PDFInfo
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- CN102882382A CN102882382A CN2012103780487A CN201210378048A CN102882382A CN 102882382 A CN102882382 A CN 102882382A CN 2012103780487 A CN2012103780487 A CN 2012103780487A CN 201210378048 A CN201210378048 A CN 201210378048A CN 102882382 A CN102882382 A CN 102882382A
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Abstract
A power-frequency power supplied electromagnetic device capable of running at magnetic flux frequency lower than power frequency comprises a power frequency power source input device, a control device and a magnet winding. The electromagnetic device is characterized in that the magnet winding is provided with a plurality of coils with dotted terminals surrounding the same main flux return circuit, the control device comprises a phase shift circuit and a switch circuit, and voltage outputted by the power frequency power source input device produces multiple currents with mutual phase differences through the phase shift circuit. The switch circuit controls that positive half-waves of the currents are respectively inputted to the dotted terminals of the coils within a set positive half-wave time of frequency flux, and negative half-waves of the currents are respectively inputted to the dotted terminals of the coils within a set negative half-wave time of the frequency flux. By the electromagnetic device with above design, the problems of reliability and cost of an inverter used for changing frequency in the prior art can be avoided.
Description
Technical field
The present invention relates to a kind of calutron, relate in particular to the calutron that can be lower than the magnetic flux work of work frequency with the power frequency power supply, in International Patent Classification (IPC), classification can belong to G05F7/00.
Background technology
The frequency of the main flux of traditional calutrons such as alternating electromagnetic electromagnetic shaker and synchronous motor is identical with the power supply frequency, and prior art will change its operating rate, needs to change its power supply frequency.Prior art measure for this reason is to adopt inverter to change outside power frequency supply the power supply of required frequency into, therefore also brings the problems such as reliability, cost of inverter.
Summary of the invention
Technical problem to be solved by this invention is, proposes a kind ofly can be lower than the calutron of the magnetic flux work of work frequency with the power frequency power supply, can exempt for a change frequency and use the problems such as the reliability of inverter and cost of prior art.
The technical scheme that the present invention solve the technical problem is, a kind ofly can be lower than the calutron of the magnetic flux work of work frequency with the power frequency power supply, comprises power frequency supply input unit, control device and electromagnetism winding; It is characterized in that:
---described electromagnetism winding has a plurality of coils with Same Name of Ends around same main flux loop;
---described control device comprises phase-shift circuit and switching circuit, and the voltage of power frequency supply input unit output produces a plurality of electric currents of mutual phase difference through phase-shift circuit; The positive half wave of described each electric current of switching circuit control is inputted toward each Same Name of Ends of 1 of described coil respectively in the time at the positive half wave of setpoint frequency magnetic flux, and the negative half-wave of described each electric current is respectively each 1 Same Name of Ends input of past described coil in the negative hemiwave time of setpoint frequency magnetic flux.
According to this design, in common flux circuit, the synthetic generation cycle of positive half wave electric current that each coil is inputted successively phase shift is longer than the positive half wave magnetic flux of power frequency period, the synthetic generation cycle of the negative half-wave current of phase shift is longer than the negative half-wave magnetic flux of power frequency period, frequency thereby the reduction of calutron work magnetic flux successively.This switching frequency that designs each electric current is lower, compares traditional inverter and is conducive to reduce cost and improves reliability, and improve the EMC performance.
The further design of this technical scheme is: the cycle of described setpoint frequency magnetic flux is the integral multiple of power frequency supply half wave cycles, a plurality of electric currents phase difference successively of described regulation phase sequence is pi/2, the positive half wave of described electric current is complete positive half wave, and the negative half-wave of electric current is complete negative half-wave.But the work magnetic flux that this design synthetic waveform is better, thereby efficient and the EMC performance of raising calutron.
Technical scheme of the present invention and effect will be further described in embodiment by reference to the accompanying drawings.
Description of drawings
Fig. 1 is the embodiment of the invention 1 electromagnetic vibrator electrical block diagram;
Fig. 2 is the embodiment of the invention 2 electromagnetic vibrator electrical block diagrams;
Fig. 3 is the waveform schematic diagram of relevant signal in the embodiment of the invention 1 electromagnetic vibrator;
Fig. 4 is the waveform schematic diagram of relevant signal in the embodiment of the invention 2 electromagnetic vibrators.
Embodiment
The embodiment of the invention is electromagnetic vibrator, adopts traditional solenoid electromagnet magnetic structure: cylindrical permanent magnet armature in the cylindrical coil axis hole, axially reciprocating under the alternating flux effect that the electric current that passes into coil produces; The fundamental frequency of described alternating flux is the vibration frequency of electromagnetic vibrator.Adopting the fundamental frequency of alternating flux described in traditional electromagnetic vibrator of this magnetic structure is the power frequency supply frequency, and namely the vibration frequency of electromagnetic vibrator is the power frequency supply frequency.
The embodiment of the invention 1 electromagnetic vibrator circuit structure as shown in Figure 1 with the waveform of relevant signal as shown in Figure 3, relevant design comprises:
A) on cyl indrical former 4 lines and around 4 coil L1, L2, L3 and L4, the top of coil is masked as Same Name of Ends (being marked with in the drawings " * ");
B) top of coil L4 connects power frequency supply input phase terminal L, capacitor C1, C2 and C3 connect successively and are connected across the top of coil L1 and L4, the top of coil L2 connects being connected in series a little of capacitor C1, C2, and the top of coil L3 connects being connected in series a little of capacitor C2, C3;
C) end of coil L1, L2, L3 and L4 respectively is access to power frequency supply input neutral line terminal N through a two-way thyristor Q1, Q2, Q3 and Q4;
D) control utmost point G1, G2, G3 and the G4 of bidirectional thyristor Q1, Q2, Q3 and Q4 are access to respectively I0 mouth: I01, I02, I03 and an I04 of single-chip microcomputer 10 through a current-limiting resistance.Another I0 mouth I05 of single-chip microcomputer 10 is access to power frequency supply input phase terminal L through current-limiting resistance, obtains the required power frequency supply synchronizing signal of control;
E) capacitance of capacitor C1, C2 and C3 cooperates with the impedance parameter of coil L1, L2, L3 and L4, and the 1/2 π electrical degree so that the electric current that coil L1, L2, L3 and L4 pass through lags behind successively is shown in the waveform 1,2,3 and 4 of (1) among Fig. 3;
F) cycle of magnetic flux is set as 2 times of power frequency supply half wave cycles, its covers positive half wave time is the waveform 4 of (1) in coil L4, L1 and the L2 electric current such as Fig. 3 that pass through, 1 and 2 positive half wave, and negative hemiwave time covers is the waveform 2 of (1) in coil L2, L3 and the L4 electric current such as Fig. 3 that pass through, 3 and 4 negative half-wave;
G) the I0 mouth I05 of single-chip microcomputer 10 is access to power frequency supply phase terminal L through current-limiting resistance and obtains the required power frequency supply synchronizing signal of control shown in the square-wave waveform of (2) among Fig. 3;
H) single-chip microcomputer 10 plug-ins make I0 mouth I01, I02, I03 and the I04 of single-chip microcomputer 10 produce periodically that single pulsewidth is the serial square-wave signal of 1/4 π electrical degree shown in (3) among Fig. 3:
---from the 1st square wave rising edge of power frequency supply synchronizing signal, I04 sends square wave 14; After the 1/2 π electrical degree of interval, I01 sends square wave 11; After the 1/2 π electrical degree of interval, I02 sends square wave 12 again;
---from the 2nd square wave rising edge of power frequency supply synchronizing signal, I02 sends square wave 12; After the 1/2 π electrical degree of interval, I03 sends square wave 13; After the 1/2 π electrical degree of interval, I04 sends square wave 14 again;
---after this all from power frequency supply synchronizing signal odd number square wave rising edge, repeat above-mentioned from the 1st process that the square wave rising edge begins of power frequency supply synchronizing signal; From power frequency supply synchronizing signal even number square wave rising edge, repeat above-mentioned from the 2nd process that the square wave rising edge begins of power frequency supply synchronizing signal.
The operation result of foregoing circuit structure is:
---control utmost point G1, G2, G3 and the G4 of bidirectional thyristor Q1, Q2, Q3 and Q4 receives I0 mouth I01, I02, I03 and I04 above-mentioned 11,12,13, the 14 periodic serial square-wave signals of single-chip microcomputer 10, the electric current such as (1) waveform 1,2,3 among Fig. 3 and 4 that respectively coil L1, L2, L3 and L4 is passed through is implemented switch control: be triggered and the half-wave current conducting when receiving square-wave signal, see (4) solid line waveform among Fig. 3; (4) dotted line waveform among Fig. 3 is seen in the half-wave current cut-off when not receiving square-wave signal.For the purpose of clear, (5) have represented that (4) among Fig. 3 only have the situation of solid line waveform among Fig. 3;
---shown in (6) among Fig. 3, the magnetic flux that the waveform 4 of (1) in the electric current such as Fig. 3 that coil L4, L1 and L2 pass through, 1 and 2 positive half wave produce synthesizes the positive half wave of setpoint frequency magnetic flux to (5) each electric current in the synthetic result of the magnetic flux that produces in the cylindrical coil axis hole among Fig. 3; The magnetic flux that the waveform 2 of (1) in the electric current such as Fig. 3 that coil L2, L3 and L4 pass through, 3 and 4 negative half-wave produce synthesizes the negative half-wave of setpoint frequency magnetic flux.As seen the fundamental frequency of this resultant flux has been reduced to half of work frequency, and the vibration frequency of electromagnetic vibrator also is reduced to half of work frequency.
The embodiment of the invention 2 electromagnetic vibrator circuit structures as shown in Figure 2 with the waveform of relevant signal as shown in Figure 4, the difference of comparing embodiment 1 electromagnetic vibrator mainly is:
A) corresponding to the b of embodiment 1 design), c) and e), cancelled capacitor C1 and C2; Coil L1 transfers reversed polarity, changes the Same Name of Ends that non-same polarity meets L3 into, termination thyristor Q1 main electrode of the same name, so the electric current that coil L1 and L3 pass through is based on identical flow direction mutual deviation π electrical degree, capacitor C1 is therefore cancellation just; Coil L2 also transfers reversed polarity, changes the Same Name of Ends that non-same polarity meets L4 into, termination thyristor Q2 main electrode of the same name, so the electric current that coil L2 and L4 pass through is based on identical flow direction also mutual deviation π electrical degree, capacitor C2 is therefore cancellation just; The capacitance of capacitor C3 cooperates with the impedance parameter of coil L3, the electric current that coil L3 and L4 the are passed through 1/2 π electrical degree that lags behind successively, the electric current that namely coil L1, L2, L3 and L4 the are passed through 1/2 π electrical degree that lags behind successively is shown in the waveform 1,2,3 and 4 of (1) among Fig. 4;
B) f that designs corresponding to embodiment 1) item, the cycle that changes magnetic flux into is set as 1.5 times of power frequency supply half wave cycles, the waveform 2 of (1), 3 positive half wave in the electric current such as Fig. 4 that the waveform 4 of (1) in the electric current such as Fig. 4 that the time-interleaved covering coil of its positive half wave L4, L1 pass through, 1 positive half wave and coil L2, L3 pass through; Its negative hemiwave time alternately covers the waveform 3 of (1) in the electric current such as Fig. 4 that waveform 1,2 negative half-wave and coil L3, the L4 of (1) in the electric current such as Fig. 4 that coil L1, L2 pass through pass through, 4 negative half-wave;
G) corresponding to the h of embodiment 1 design), change I0 mouth I01, I02, I03 and I04 that single-chip microcomputer 10 plug-ins make single-chip microcomputer 10 into and produce periodically that single pulsewidth is the serial square-wave signal of 1/4 π electrical degree shown in (3) among Fig. 4:
---from the 1st square wave rising edge of power frequency supply synchronizing signal, I04 sends square wave 24; After the 1/2 π electrical degree of interval, I01 sends square wave 21; After the interval π electrical degree, I01 sends square wave 21 again; After the 1/2 π electrical degree of interval, I02 sends square wave 22 again; After the interval π electrical degree, I02 sends square wave 22 again; After the 1/2 π electrical degree of interval, I03 sends square wave 23 again; After the interval π electrical degree, I03 sends square wave 23 again; After the 1/2 π electrical degree of interval, I04 sends square wave 24 again;
---from the 4th square wave rising edge of power frequency supply synchronizing signal, repeat above-mentioned from the 1st process that the square wave rising edge begins of power frequency supply synchronizing signal; 3 square waves of every interval power frequency supply synchronizing signal repeat above-mentioned from the 1st process that the square wave rising edge begins of power frequency supply synchronizing signal afterwards.
The operation result of foregoing circuit structure is:
---the control utmost point G1 of bidirectional thyristor Q1, Q2, Q3 and Q4, G2, G3 and G4 receive I0 mouth I01, the I02,103 and I04 above-mentioned 21,22,23 and 24 periodic serial square-wave signals of single-chip microcomputer 10, implement switch control to what coil L1, L2, L3 and L4 passed through such as the electric current of (1) waveform 1,2,3 among Fig. 4 and 4 respectively: be triggered and the half-wave current conducting during square-wave signal as described in receiving, see (4) solid line waveform among Fig. 4; (4) dotted line waveform among Fig. 4 is seen in the half-wave current cut-off when not receiving square-wave signal.For the purpose of clear, (5) have represented that (4) among Fig. 4 only have the situation of solid line waveform among Fig. 4;
---(5) each electric current shown in (6) among Fig. 4, at first is the positive half wave that the waveform 4 of (1) in coil L4 and the L1 electric current such as Fig. 4 that pass through and magnetic flux that 1 positive half wave produces synthesize the setpoint frequency magnetic flux in the synthetic result of the magnetic flux that produces in the cylindrical coil axis hole among Fig. 4; Then, the magnetic flux that the waveform 1 of (1) and 2 negative half-wave produce in the electric current such as Fig. 4 that is passed through by coil L1 and L2 synthesizes the negative half-wave of setpoint frequency magnetic flux; Then, the magnetic flux that the waveform 2 of (1) and 3 positive half wave produce in the electric current such as Fig. 4 that is passed through by coil L2 and L3 synthesizes the positive half wave of setpoint frequency magnetic flux; Then, the magnetic flux that the waveform 3 of (1) and 4 negative half-wave produce in the electric current such as Fig. 4 that coil L3 and L4 pass through synthesizes the negative half-wave of setpoint frequency magnetic flux, so loop cycle.As seen the fundamental frequency of this resultant flux has been reduced to 2/3 of work frequency, and the vibration frequency of electromagnetic vibrator also is reduced to 2/3 of work frequency.
In embodiments of the present invention, by (5) among (5) and Fig. 4 among Fig. 3 as seen, it is complete sine-wave current that the positive half wave of setpoint frequency magnetic flux is converted to what flow through in the process of negative half-wave, thereby has preferably EMC performance.If the integral multiple of non-power frequency supply half wave cycles of the cycle of setpoint frequency magnetic flux and the non-pi/2 of each electric current phase difference successively, although also can synthesize the magnetic flux that is lower than work frequency, waveform, EMC performance and efficient are with variation.In addition, during the non-complete half-wave of the half-wave of described electric current, also can synthesize the magnetic flux that is lower than work frequency, but waveform, EMC performance and efficient are also with variation.
The embodiment of the invention all adopts capacitor to connect with coil as phase shifting component to consist of phase-shift circuit, can certainly adopt inductor as the phase shifting component formation phase-shift circuit of connecting with coil, but cost is higher.In addition, implement bidirectional thyristor time-delay triggering by single-chip microcomputer 10 built-in programs, the current first harmonics that the bidirectional thyristor that time-delay triggers is controlled will lag behind the current first harmonics that bidirectional thyristor that non-time-delay triggers is controlled, and namely also can reach phase shift, but the flux waveforms variation.
The control of switch in the embodiment of the invention all adopts bidirectional thyristor as switch, can certainly adopt the power electronic element such as IGBT similarly to control as switch, but to adopt bidirectional thyristor the most economical reliable.
The calutron of the embodiment of the invention is the solenoid electromagnet of electromagnetic vibrator, but principle of the present invention also can be applied to single-phase permanent-magnet synchronous motor.Especially for the two salient pole single-phase permanent-magnet synchronous motors that adopt the U-iron core, its coil is the centralized single-column shape structure around U-iron core yoke section, winding mode and control circuit thereof can be identical with the design of the embodiment of the invention, can obtain to be equivalent to 1/2 or 2/3 synchronous speed of work frequency.
Claims (2)
1. one kind can be lower than the calutron of the magnetic flux work of work frequency with power frequency power supply, comprises power frequency supply input unit, control device and electromagnetism winding; It is characterized in that:
---described electromagnetism winding has a plurality of coils with Same Name of Ends around same main flux loop;
---described control device comprises phase-shift circuit and switching circuit, and the voltage of power frequency supply input unit output produces a plurality of electric currents of mutual phase difference through phase-shift circuit; The positive half wave of described each electric current of switching circuit control is inputted toward each Same Name of Ends of 1 of described coil respectively in the time at the positive half wave of setpoint frequency magnetic flux, and the negative half-wave of described each electric current is respectively each 1 Same Name of Ends input of past described coil in the negative hemiwave time of setpoint frequency magnetic flux.
2. according to the described calutron of claim 1, it is characterized in that: the cycle of described setpoint frequency magnetic flux is the integral multiple of power frequency supply half wave cycles, a plurality of electric currents phase difference successively of described regulation phase sequence is pi/2, the positive half wave of described electric current is complete positive half wave, and the negative half-wave of electric current is complete negative half-wave.
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| CN201210378048.7A CN102882382B (en) | 2012-10-07 | 2012-10-07 | Power-frequency power supplied electromagnetic device capable of running at magnetic flux frequency lower than power frequency |
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| CN201210378048.7A CN102882382B (en) | 2012-10-07 | 2012-10-07 | Power-frequency power supplied electromagnetic device capable of running at magnetic flux frequency lower than power frequency |
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Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN86108447A (en) * | 1986-12-16 | 1987-08-12 | 顾正平 | AC asynchronous motor positive-negative revolution difference rate speed regulating method and device |
| CN1117663A (en) * | 1994-08-09 | 1996-02-28 | 王东奎 | inversion and frequency conversion method and device |
| CN1190278A (en) * | 1997-02-03 | 1998-08-12 | 北京凯奇新技术开发总公司 | High-voltage large-power frequency convertor without power network pollution |
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2012
- 2012-10-07 CN CN201210378048.7A patent/CN102882382B/en active Active
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN86108447A (en) * | 1986-12-16 | 1987-08-12 | 顾正平 | AC asynchronous motor positive-negative revolution difference rate speed regulating method and device |
| CN1117663A (en) * | 1994-08-09 | 1996-02-28 | 王东奎 | inversion and frequency conversion method and device |
| CN1190278A (en) * | 1997-02-03 | 1998-08-12 | 北京凯奇新技术开发总公司 | High-voltage large-power frequency convertor without power network pollution |
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