CN101997421B - Resonant converter provided with overcurrent protection device and control method thereof - Google Patents
Resonant converter provided with overcurrent protection device and control method thereof Download PDFInfo
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- CN101997421B CN101997421B CN200910168212.XA CN200910168212A CN101997421B CN 101997421 B CN101997421 B CN 101997421B CN 200910168212 A CN200910168212 A CN 200910168212A CN 101997421 B CN101997421 B CN 101997421B
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Abstract
The invention discloses a resonant converter, comprising a first input terminal, a second input terminal and an overcurrent protection device as well as a first resonant capacitor and a second resonant capacitor; wherein the input terminals are used for receiving an input voltage; the overcurrent protection device comprises a first diode provided with a cathode and a second diode provided with an anode and a cathode as well as a first voltage assembly, wherein the anode is coupled with the second input terminal; the first voltage assembly is provided with a negative terminal and a positive terminal, wherein the negative terminal is coupled with the first input terminal and the positive terminal is coupled with the cathode of the first diode; the first resonant capacitor is provided with a first terminal and a second terminal, wherein the first terminal is coupled with the negative terminal of the first voltage assembly, and the second terminal is coupled with the cathode of the second diode; and the second resonant capacitor is provided with a first terminal coupled with the second terminal of the first resonant capacitor.
Description
Technical field
The present invention relates to overcurrent protective device and method in a kind of resonant circuit, overcurrent protective device and method in espespecially a kind of DC-DC controlled resonant converter (DC/DC resonant converter).
Background technology
The development trend of DC to DC converter is as most power supply product, towards the future development of high efficiency (High efficiency), high power density (High power density), high reliability (Highreliability) and low cost (low cost).Resonant converter can be realized the advantages such as the Zero Current Switch of the switch no-voltage conducting of primary side and the rectifier diode of secondary side as LLC converter owing to having in full-load range, is more and more applied in recent years DC/DC converter.
But in actual applications, overcurrent protection (Over Current Protection:OCP) is a more crucial problem.In the time of overload or short circuit, the resonance current of resonant circuit is very large, if do not limit and protect, converter circuit can damage inefficacy because of excessive electric current.OCP circuit can be realized protection fast in overload or when short circuit to controlled resonant converter circuit, also can limit the impulse current while startup simultaneously.
For resonant circuit is carried out to OCP, first method is to improve the switching frequency of converter.By improving switching frequency, increase the impedance of resonant slots circuit to realize current limliting.This method is simple; but while there is following shortcoming: OCP protection; the switching frequency of circuit is far away higher than normal frequency of working; switching loss will greatly increase; the loss of magnet assembly also will be increased thereupon, and heat radiation is required to improve, and the stress of magnet assembly increases; design is in order to ensure also moving when the high frequency (OCP) very when magnet assembly, and the size of assembly also will increase greatly.
Second method is that frequency conversion adds pulse-width modulation (PWM) method.Implementation method: first increase the switching frequency of resonant circuit, in the time that frequency is increased to a certain degree, pwm circuit is started working, and reduces to be applied to voltage in resonant slots, and then realizes current limliting.This method control is comparatively complicated, and zero voltage switch under current-limit mode (ZVS) can be lost, and switching loss also can increase, very high to drive circuit requirement,, need to protect fast meanwhile.
The third method be adopt diode clamp resonant capacitance voltage to input voltage to realize current limliting.Fig. 1 and Fig. 5 show respectively the symmetrical half bridge type and the symmetrical bridge-type controlled resonant converter that adopt the method.In Fig. 1, semi-bridge type controlled resonant converter receives a direct current input voltage vin, comprise switch Qa and Qb, resonant inductance Ls, magnetizing inductance Lm, (Cr1 and Cr2 can have identical capacitance with Cr2 for clamping diode D1-D2, resonant capacitance Cr1, for example, can be the half of single resonant capacitance Cr capacitance, be Cr/2), transformer T, output rectifier diode Ds1-Ds2, output capacitance Cf, and load (LLC resonant circuit load on current limliting time show as current source characteristic, so locate to represent with current source Io).In Fig. 5, comprise switch Qa-Qd, (Ls1 and Ls2 can have identical inductance value to two symmetrical resonant inductance Ls1 with Ls2, for example, can be the half of single resonant inductance Ls inductance value, be Ls/2), (Lm1 and Lm2 can have identical inductance value to two symmetrical magnetizing inductance Lm1 with Lm2, for example, can be the half of single resonant inductance Lm inductance value, be Lm/2), four clamping diode D1-D4, Cr is coupled in respectively two nodes that connect D1 and D2 and D3 and D4, and the assembly of its secondary side is identical with Fig. 1.The method is simple, can realize Cycle by Cycle current limliting without extra control circuit, belongs to Passive Shape Control.Only need to increase diode, and resonant circuit adopts symmetrical structure.But the method is because clamping voltage is input direct voltage, and therefore the maximum voltage on resonant capacitance can only be just also input voltage, resonant capacitance both end voltage value can change and change along with input voltage, and clamping voltage is along with input voltage changes and changes.This is subject to certain restrictions resonant circuit design, and resonant circuit working range is also affected.
The 4th kind of method is to increase auxiliary transformer clamping resonant capacitance voltage.Be as shown in Figure 2 increase auxiliary transformer T1 and the common clamp resonant capacitance of the transformer T2 Cr voltage symmetric form half-bridge resonance circuit to secondary side output voltage V o.Voltage on resonant capacitance Cr is clamped to controlled resonant converter output voltage values Vo(output by auxiliary transformer T1 and clamping diode D1-D2 and regards a voltage source as).Increase auxiliary transformer T1 by design, can change clamping voltage value, realize the flexible design of clamping voltage.The method can make controlled resonant converter design not limited by clamping voltage, but need to increase extra magnet assembly transformer T1, introduces excess loss, Efficiency Decreasing, and cost increases, and also has the problems such as safety.
Lung biopsy is the method by increase clamp winding and clamping diode acting in conjunction clamp resonant capacitance voltage on transformer or resonant inductance.Fig. 3 increases respectively clamp winding Lm12 and Lm22 and diode D1-D2 and D3-D4 acting in conjunction clamp resonant capacitance Cr1-Cr2 and the Cr3-Cr4 voltage symmetrical half bridge type resonant circuit to input voltage vin on transformer T1 and T2, its primary side comprises switch Qa-Qd and resonant inductance Ls1-Ls2 (in like manner, Ls1 can have identical inductance value with Ls2, for example, Ls/2), its secondary side comprises output rectifier diode Ds1-Ds4, output capacitance Cf and current source Io.Fig. 4 increases clamp winding and the diode acting in conjunction clamp resonant capacitance voltage symmetrical half bridge type resonant circuit to input voltage on resonant inductance.It all comprises clamp winding from the different resonant inductance Ls1-Ls2 that are primary side of Fig. 3, and comprises magnetizing inductance Lm1-Lm2, and its secondary side is identical with Fig. 3.The method makes magnet assembly complex structure, and loss and cost increase, Efficiency Decreasing.
The over-current protection method of comprehensive above prior art can be found out: aforementioned every known techniques, if not control complexity, to increase exactly magnet assembly, and cause cost volume to increase, Efficiency Decreasing.The method of diode clamp resonant capacitance is comparatively simple, but because its clamping voltage value can only be input voltage, so exist direct functional relation between resonant capacitance magnitude of voltage and DC input voitage, due to the fluctuation of DC input voitage, clamping voltage value is changed, limited the working range of circuit, especially in the time that converter does dynamic load switching, because the DC input voitage value of converter is also the reduction of clamping voltage, be easy to occur clamp.Its circuit parameter design is restricted.
Duty is event, and inventor, in view of the disappearance of known techniques, is the idea of thinking and improve invention, can invent eventually this case it " controlled resonant converter of tool overcurrent protective device and control method thereof ".
Summary of the invention
The main purpose of this case is to provide a kind of controlled resonant converter and control method thereof of tool overcurrent protective device; in the time of controlled resonant converter secondary circuit short-circuit; overcurrent protection is provided; and solve the excessive problem of controlled resonant converter primary side switching current stress; also solved resonant capacitance voltage and can only be clamped at input voltage simultaneously; primary side switching current stress determines by input voltage completely, and controlled resonant converter circuit design parameter and working range such as are restricted at the problem.
The another main purpose of this case is to provide a kind of DC-DC controlled resonant converter, comprise a square-wave device, for generation of a voltage with square-wave waveform, comprise a first input end, be used for receiving a DC input voitage, one resonant slots, be coupled in this square-wave device, comprise one first resonant capacitance, and one resonant inductance be coupled in this first resonant capacitance, an and overcurrent protective device, be coupled between this first resonant capacitance and this first input end, comprise one first switch module, tool one first end and one second end, and one first voltage assembly, tool one negative pole end and a positive terminal, wherein this negative pole end is coupled in this first input end, and this positive terminal is coupled in this second end of this first switch module.
According to above-mentioned conception, this square-wave device is a bridge circuit, and more comprise one second input, be used for receiving this DC input voitage and one first brachium pontis and be coupled between this first input end and this second input, and this first brachium pontis comprises that one first diverter switch and one second diverter switch are coupled to this first diverter switch.
According to above-mentioned conception, wherein, this resonant slots more comprises one of tool one first end and one second end the second resonant capacitance, this the first resonant capacitance tool one first and 1 second end, this overcurrent protective device more comprises one of tool one first end and one second end second switch assembly and one of tool one negative pole end and positive terminal second voltage assembly, this first end of this first resonant capacitance is coupled in this negative pole end of this first voltage assembly, this second end of this first resonant capacitance is coupled in this second end of this second switch assembly, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, this positive terminal of this second voltage assembly is coupled in this second input, this second end of this second switch assembly is coupled in this first end of this first switch module, this second end of this second resonant capacitance is coupled in this positive terminal of this second voltage assembly, and this first end of this second resonant capacitance is coupled in this second end of this first resonant capacitance.
According to above-mentioned conception, this first is respectively one of each tool one anode and negative electrode first and one second clamping diode with this second switch assembly, and respectively this anode and this negative electrode of this diode are respectively this first end and this second end of this switch module.
According to above-mentioned conception, respectively this first is selected from a piezo-resistance (Varistor), a gas discharge tube (Gas tube), a unidirectional Transient Voltage Suppressor (TVS), a bidirectional transient voltage suppressor (TVS), a RC with this second voltage assembly system and composes in parallel circuit and by wherein arbitrary the MOSFET of gate and source electrode short circuit.
According to above-mentioned conception, this converter more comprises a magnetizing inductance, one transformer, one output rectification circuit, one output capacitance and a current source, and be a LLC controlled resonant converter, wherein, this the first resonant capacitance tool one first end and one second end, this overcurrent protective device more comprises one of tool one first end and one second end second switch assembly and one of tool one negative pole end and positive terminal second voltage assembly, this first end of this first resonant capacitance is coupled in this negative pole end of this first voltage assembly, this second end of this first resonant capacitance is coupled in this second end of this second switch assembly, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, this positive terminal of this second voltage assembly is coupled in this second input, this bridge circuit more comprises a switching switch circuit, this magnetizing inductance, each tool one first and 1 second end of this resonant inductance and this output capacitance, this switching switch circuit comprise each tool one first and 1 second end this first with this second diverter switch, this output rectification circuit comprises one of each tool one anode and negative electrode first and one second rectifier diode, this transformer comprises the secondary side winding of a first side winding and tool one first and 1 second end and a center tap, this first end of this first diverter switch is coupled in this negative pole end of this first voltage assembly, this second end of this first diverter switch is coupled in this first end of this second diverter switch, this second end of this second diverter switch is coupled in this positive terminal of this second voltage assembly, this first end of this resonant inductance is coupled in this second end of this first diverter switch, this first end of this magnetizing inductance is coupled in this second end of this resonant inductance, this second end of this magnetizing inductance is coupled in this second end of this second switch assembly, this first side winding parallel connection is electrically connected on this magnetizing inductance, this first end of this secondary side winding is coupled in this anode of this first rectifier diode, this second end of this secondary side winding is coupled in this anode of this second rectifier diode, this negative electrode of this first rectifier diode is coupled in this negative electrode of this second rectifier diode, this first end of this output capacitance is coupled in this negative electrode of this second rectifier diode, this second end of this output capacitance is coupled in this center tap, and this current source parallel connection is electrically connected on this output capacitance.
According to above-mentioned conception, this converter more comprises one of each tool one first end and one second end second, one the 3rd and 1 the 4th resonant capacitance, wherein, this the first resonant capacitance tool one first end and one second end, this overcurrent protective device more comprises one of tool one first end and one second end second switch assembly and one of tool one negative pole end and positive terminal second voltage assembly, this first end of this first resonant capacitance is coupled in this negative pole end of this first voltage assembly, this second end of this first resonant capacitance is coupled in this second end of this second switch assembly, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, this positive terminal of this second voltage assembly is coupled in this second input, this second end of this first resonant capacitance is coupled in this second end of this second switch assembly, this second end of this second resonant capacitance is coupled in this positive terminal of this second voltage assembly, this first end of this second resonant capacitance is coupled in this second end of this first resonant capacitance, this first end of the 3rd resonant capacitance is coupled in this second end of this second resonant capacitance and this second end of this second switch assembly, this first end of this first switch module is coupled in this second end of the 3rd resonant capacitance and this first end of the 4th resonant capacitance, and this second end of the 4th resonant capacitance is coupled in this second input.
According to above-mentioned conception, this bridge circuit is a full bridge structure, and comprises that one second brachium pontis is coupled between this first input end and this second input, and this brachium pontis comprises that one the 3rd diverter switch and one the 4th diverter switch are coupled to the 3rd diverter switch.
According to above-mentioned conception, this the first resonant capacitance tool one first and 1 second end, this overcurrent protective device more comprises one of each tool one first end and one second end the second to 1 the 4th switch module, this first end of this first resonant capacitance is coupled in this second end of this second switch assembly, this second end of this first resonant capacitance is coupled in this first end of the 4th switch module, this second end of this second switch assembly is coupled in this first end of this first switch module, this first end of the 3rd switch module is coupled in this first end of this second switch assembly, this second end of the 4th switch module is coupled in this second end of this first switch module, this first end of the 4th switch module is coupled in this second end of the 3rd switch module, this second input is coupled in this first end of the 3rd switch module, this negative pole end of this first voltage assembly is coupled in this first input end, and this positive terminal of this first voltage assembly is coupled in this second end of this first switch module.
According to above-mentioned conception, this first to the 4th switch module is respectively one of each tool one anode and a negative electrode the first to 1 the 4th clamping diode, and respectively this anode and this negative electrode of this diode are respectively this first end and this second end of this switch module.
According to above-mentioned conception, this converter is a LLC circuit, and more comprise one first and 1 second resonant inductance, one first and 1 second magnetizing inductance, one first transformer, one second transformer, one circuit of synchronous rectification, one first and 1 second output capacitance, one outputting inductance and a current source, wherein, this full bridge structure more comprises a switching switch circuit, this switching switch circuit be coupled in this first with this second input and this first and this second magnetizing inductance, this first magnetizing inductance is coupled in this second resonant inductance, this second resonant inductance is coupled in this second end of this resonant capacitance, this second magnetizing inductance is coupled in this first resonant inductance, this first resonant inductance is coupled in this first end of this first resonant capacitance, this is first transformer coupled in this first magnetizing inductance and this circuit of synchronous rectification, this is second transformer coupled in this second magnetizing inductance and this circuit of synchronous rectification, this first is all coupled in this circuit of synchronous rectification with this second output capacitance and this outputting inductance, and this current source parallel connection is electrically connected on this second output capacitance.
According to above-mentioned conception, this the first resonant capacitance tool one first and 1 second end, this overcurrent protective device more comprises second voltage assembly and one of each tool one first end and one second end second to 1 the 4th switch module of tool one negative pole end and a positive terminal, this first end of this first resonant capacitance is coupled in this second end of this second switch assembly, this second end of this first resonant capacitance is coupled in this first end of the 4th switch module, this second end of this second switch assembly is coupled in this first end of this first switch module, this first end of the 3rd switch module is coupled in this first end of this second switch assembly, this second end of the 4th switch module is coupled in this second end of this first switch module, this first end of the 4th switch module is coupled in this second end of the 3rd switch module, this negative pole end of this first voltage assembly is coupled in this first input end, this positive terminal of this first voltage assembly is coupled in this second end of this first switch module, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, and this positive terminal of this second voltage assembly is coupled in this second input.
According to above-mentioned conception, this converter is a LLC circuit, and more comprise one first and 1 second resonant inductance, one first and 1 second magnetizing inductance, one transformer, one circuit of synchronous rectification, one first and 1 second output capacitance, one outputting inductance and a current source, wherein, this full bridge structure more comprises a switching switch circuit, this switching switch circuit be coupled in this first with this second input and this first and this second resonant inductance, this first resonant inductance is coupled in this second magnetizing inductance, this second magnetizing inductance is coupled in this first end of this first resonant capacitance, this second resonant inductance is coupled in this first magnetizing inductance, this first magnetizing inductance is coupled in this second end of this first resonant capacitance, this transformer coupled in this first with this second magnetizing inductance and this circuit of synchronous rectification, this first is all coupled in this circuit of synchronous rectification with this second output capacitance and this outputting inductance, and this current source parallel connection is electrically connected on this second output capacitance.
According to above-mentioned conception, this converter more comprises one second and 1 the 3rd resonant capacitance, wherein this second with each tool one first and 1 second end of the 3rd resonant capacitance, this second end of this second resonant capacitance is coupled in this first end of this first resonant capacitance, and this first end of the 3rd resonant capacitance is coupled in this second end of this first resonant capacitance.
According to above-mentioned conception, this converter is a LLC circuit, and more comprise one first and 1 second resonant inductance, one first and 1 second magnetizing inductance, one transformer, one circuit of synchronous rectification, one first and 1 second output capacitance, one outputting inductance and a current source, wherein, this full bridge structure more comprises a switching switch circuit, this switching switch circuit be coupled in this first with this second input and this first and this second resonant inductance, this first resonant inductance is coupled in this second magnetizing inductance, this second magnetizing inductance is coupled in this first end of this second resonant capacitance, this second resonant inductance is coupled in this first magnetizing inductance, this first magnetizing inductance is coupled in this second end of the 3rd resonant capacitance, this transformer coupled in this first with this second magnetizing inductance and this circuit of synchronous rectification, this first is all coupled in this circuit of synchronous rectification with this second output capacitance and this outputting inductance, and this current source parallel connection is electrically connected on this second output capacitance.
Another main purpose of this case is to provide a kind of DC-DC controlled resonant converter; comprise an overcurrent protective device; comprise one first switch module; tool one first end and one second end; and one first voltage assembly; tool one negative pole end and a positive terminal, wherein this negative pole end is coupled in outer one of DC input voitage source positive terminal in addition, and this positive terminal of this first voltage assembly is coupled in this second end of this first switch module.
According to above-mentioned conception, this converter more comprises a square-wave device, for generation of the voltage with square-wave waveform, comprise a first input end, for receiving a DC input voitage, and a resonant slots, be coupled in this square-wave device, comprise one first resonant capacitance, and a resonant inductance, be coupled in this first resonant capacitance.
Time main purpose of this case be to provide a kind of for one first group of tool one overcurrent protective device, a resonant tank and a tool control method with the DC-DC controlled resonant converter of the switching switch circuit of one second group of switch, this overcurrent protective device, comprise: one first switch module, tool one first end and one second end; And one first voltage assembly, tool one negative pole end and a positive terminal, wherein this negative pole end is coupled in outer one of DC input voitage source positive terminal in addition, this positive terminal of this first voltage assembly is coupled in this second end of this first switch module, and the method comprises following step: an input voltage, a resonant capacitance voltage and a resonance current (a) are provided; (b) when this converter is at a normal resonance working stage, make this first group of switch conduction of this switching switch circuit; (c) reach after one first predetermined value when this resonant capacitance voltage exceedes this input voltage, make this overcurrent protective device conducting; And (d) in the time that this resonance current reduces since the maximum resonance current value of a forward, this first group of switch turn-offed.
According to above-mentioned conception, this step (b) more comprises following step: (b1) make this input voltage be carried on this resonant tank; (b2) make this resonance current from the zero maximum resonance current value that is increased to this forward; And (b3) make this resonant capacitance voltage be increased to the maximum clamping voltage value of a forward from the maximum clamping voltage value of a negative sense, wherein the maximum clamping voltage value of this forward is greater than this input voltage value.
According to above-mentioned conception, this this step (c) more comprises following step: (c1) make this resonant capacitance voltage be clamped at the maximum clamping voltage value of a forward; And (c2) make this resonance current be restricted to the maximum resonance current value of this forward.
According to above-mentioned conception, this step (d) more comprises following step: (d1) through a Dead Time, then make the mode conducting of this second group of switch with a zero voltage switching; (d2) apply one of this input voltage negative value on a resonant tank, make this resonance current start to decline from the maximum resonance current value of this forward; (d3) make this resonant capacitance voltage maintain maximum clamping voltage value a period of time of a forward; And (d4) when this resonance current drops to after one second predetermined value, this resonant capacitance voltage is also declined gradually, until this resonance current and this resonant capacitance voltage all drop to zero.
According to above-mentioned conception, this first group of switch be this second with the 4th diverter switch, this second group of switch be this first with the 3rd diverter switch, and this resonant tank be this first with this second resonant inductance, this first and this second magnetizing inductance and this first resonant capacitance.
For the present invention's above-mentioned purpose, feature and advantage can be become apparent, preferred embodiment cited below particularly, and coordinate appended graphicly, be described in detail below:
Brief description of the drawings
Fig. 1: be that the diode clamp resonant capacitance voltage of prior art is to the circuit diagram of the symmetrical half bridge type resonant circuit of DC input voitage;
Fig. 2: be that the employing auxiliary transformer clamping resonant capacitance voltage of prior art is to the circuit diagram of the symmetrical half bridge type resonant circuit of converter output secondary side;
Fig. 3: be prior art on transformer, increase clamp winding and clamping diode acting in conjunction with clamp resonant capacitance voltage the circuit diagram to the symmetrical half bridge type resonant circuit of DC input voitage;
Fig. 4: be prior art on resonant inductance, increase clamp winding and clamping diode acting in conjunction with clamp resonant capacitance voltage the circuit diagram to the symmetrical half bridge type resonant circuit of DC input voitage;
Fig. 5: the circuit diagram to the symmetrical bridge-type resonant circuit of DC bus input voltage with diode clamp resonant capacitance voltage that is prior art;
Fig. 6: be the circuit diagram of the present invention's first preferred embodiment of conceiving with the symmetrical half bridge type resonant circuit of diode clamp resonant capacitance voltage;
Fig. 7: be the circuit diagram of the present invention's second preferred embodiment of conceiving with the symmetrical bridge-type resonant circuit of diode clamp resonant capacitance voltage;
Fig. 8: be the circuit diagram of the present invention's the 3rd preferred embodiment of conceiving with the symmetrical half bridge type resonant circuit of diode clamp partial resonance capacitance voltage;
Fig. 9: be the circuit diagram of the present invention's the 4th preferred embodiment of conceiving with the symmetrical bridge-type resonant circuit of diode clamp partial resonance capacitance voltage;
Figure 10 A-F: the basic structure that is the various physical circuits of Vx1/Vx2 in the present invention's first to fourth preferred embodiment of conceiving;
Figure 11: the employing that is the present invention's the 5th preferred embodiment of conceiving increases the diode clamp resonant capacitance voltage of TVS to the circuit diagram of the symmetrical bridge-type resonant circuit of input direct voltage;
Figure 12: be that the diode clamp resonant capacitance voltage of the employing increase TVS as shown in Figure 11 is to the oscillogram of the waveform correlation of the symmetrical bridge-type resonant circuit of input direct voltage; And
Figure 13: be the circuit diagram of the present invention's the 5th preferred embodiment of conceiving with the symmetrical bridge-type resonant circuit of diode clamp resonant capacitance voltage.
Embodiment
The present invention is to provide a kind of current foldback circuit of controlled resonant converter; in the time of controlled resonant converter secondary circuit short-circuit; overcurrent protection is provided; and solve the excessive problem of controlled resonant converter primary side switching current stress; also solved resonant capacitance voltage and can only be clamped at input voltage simultaneously; primary side switching current stress determines by input voltage completely, and controlled resonant converter circuit design parameter and working range such as are restricted at the problem.
In the time of controlled resonant converter secondary circuit short-circuit, for example, by the acting in conjunction of semiconductor switch (clamping diode) and auxiliary circuit, by being clamped at higher than input direct voltage certain value of the voltage on resonant capacitance.Suppress primary side switching current stress thereby reach, design parameter and working range are not subject to the object of clamp circuit restriction substantially.Fig. 6 is the application of the present invention on half-bridge resonance circuit, the difference of itself and Fig. 1 is to have increased first and second voltage assembly Vx1 and Vx2, wherein Vx1 is coupled in the positive terminal of the negative electrode of D1 and additional direct voltage source (its magnitude of voltage is Vin), and Vx2 is coupled in the negative pole end of the anode of D2 and additional direct voltage source (its magnitude of voltage is Vin).Fig. 7 is the application of the present invention on full-bridge resonant circuit.Not the existing together of Fig. 7 and Fig. 5 be mainly also to have increased this first with this second voltage assembly Vx1 and Vx2, wherein Vx1 is coupled in the positive terminal of the negative electrode of D1 and D4 and additional direct voltage source (its magnitude of voltage is Vin), Vx2 is coupled in the negative pole end of the anode of D2 and D3 and additional direct voltage source (its magnitude of voltage is Vin), its secondary side is a full-bridge type circuit of synchronous rectification in addition, comprises four synchronous rectifier SR1-SR4, output capacitance Cf1-Cf2, outputting inductance Lf1 and load (representing with current source Io) herein.First and second preferred embodiment in above-mentioned Fig. 6 and Fig. 7, is the clamp adopting whole resonant capacitances, can certainly carry out clamp to partial resonance electric capacity, as shown in Fig. 8 and Fig. 9.Wherein the difference of Fig. 8 and Fig. 6 is that it has increased by two resonant capacitance Cr3 and Cr4, electrical connection is one another in series, and the second end of Cr1 and the second end of Cr4 are coupled in respectively the negative electrode of D2 and this negative pole end of additional direct voltage source, and the anode of D1 is coupled in respectively the second end of Cr3 and the first end of Cr4, and in Cr1-Cr4, only having Cr2, Cr3 is by clamp.The difference of Fig. 9 and Fig. 7 is except clamping capacitance Cr1 (being equivalent to the Cr in Fig. 7), (Cr2 is coupled in Cr1 and Lm2 in Fig. 9, to have increased separately two resonant capacitance Cr2-Cr3, Cr3 is coupled in Cr1 and Lm1), and in Cr1-Cr3, only have Cr1 by clamp.If Cr2, Cr3 become certain ratio with the voltage bearing on Cr1 in the present embodiment, close to the ratio of the voltage bearing on Vx1, Vx2 and Cr1, the voltage on Vx1 and Vx2 can be zero.
The present invention, by increasing extra voltage assembly Vx1/Vx2, can make clamping voltage higher than DC input voitage certain value.Wherein voltage assembly Vx1/Vx2 can be Figure 10 A, B, C, D, the cited partial circuit of E, F, also can realize by its combination or other form circuit.Wherein, Figure 10 A is piezo-resistance (Varistor), in the time that its two ends are born voltage and are less than its rated value, show as very large resistance, when the voltage bearing when its two ends is greater than its rated value, Varistor conducting, its voltage is reduced to rated voltage, shows as a voltage source.Figure 10 B is gas discharge tube (Gas tube), in the time that its two ends are born voltage and are less than rated value, show as open circuit, in the time that voltage is born at its two ends higher than rated value, Gas tube conducting short circuit, pressure drop is zero substantially, differs certain voltage poor from open circuit to short-circuit process, can be regarded as a controllable voltage source.Figure 10 C-D is unidirectional and bidirectional transient voltage suppressor (TVS), in the time that its two ends are born voltage and are less than its rated voltage, show as very large resistance, in the time that it bears voltage and is greater than its rated voltage, TVS avalanche breakdown, both end voltage is that avalanche voltage is load voltage value, shows as a voltage source.Figure 10 E is that RC composes in parallel network, and in the time that it flows through certain electric current, two ends can produce certain voltage difference, can regard a variable voltage source as.Figure 10 F is by the MOSFET of gate and source electrode short circuit, utilizes its avalanche breakdown effect, and avalanche voltage can be considered as voltage source.These assemblies or combinational network are all that self can to bear certain voltage poor, can be considered as a voltage source in circuit.This makes between clamping voltage value and DC input voitage is not direct functional relation, can make clamping voltage value higher than DC input voitage value, can avoid like this in dynamic process because of the DC input voitage clamp causing that fluctuates, make circuit design more flexible, parameter designing and circuit working scope etc. almost can not be subject to the restriction of clamping voltage.In the time of overload or short circuit, can effectively realize rapidly again the restriction of electric current.Have cost low, normal work does not affect efficiency, advantages of simple structure and simple.And can be applied to symmetric form half-bridge and full-bridge controlled resonant converter circuit, also can be used in the clamp circuit such as three current potentials and many current potentials controlled resonant converter circuit.
The symmetric form full-bridge resonance DC/DC converter of the diode of tool shown in Figure 11 and Transient Voltage Suppressor (TVS), for the 5th preferred embodiment of the present invention, now Qa, Qb, Qc and Qd are four primary side switches of controlled resonant converter, composition full-bridge type commutation circuit, in order to keep symmetrical structure, realize the voltage clamp to resonant capacitance Cr, resonant inductance Ls and first side winding are divided into two parts (Ls1 and Ls2 and Lm1 and Lm2), resonant capacitance Cr is in centre, whole circuit structure is about resonant capacitance symmetry, D1, D2, D3, D4 be four clamp semiconductor switchs (for example, diode), TVS1 and TVS2 are Transient Voltage Suppressor, it is a kind of concrete form of Vx1/Vx2 in the present invention, secondary side is that full-bridge synchronous rectification circuit is identical with the secondary side of Fig. 7, transformer is the structure of two transformers (T1+T2) primary side series connection secondary side parallel connection.
Figure 12 is the oscillogram of this most preferred embodiment work as shown in figure 11.The whole cycle is divided into 6 patterns, and Mode1, Mode2, Mode3, Mode4, Mode5 and Mode6 make a concrete analysis of as follows:
Mode1 (t0 ~ t1): circuit, at normal resonance working stage, clamp does not occur.Switch Qb & Qd conducting, input voltage vin is carried on resonant circuit loop, circuit generation resonance, resonance current ip starts to be increased to ip limit value from being approximately zero, resonant capacitance voltage is increased to the maximum clamping voltage V of forward clamp from the maximum clamping voltage-V clamp of negative sense, and this value is higher than the value (being Vin) of DC input voitage V bus.Secondary side synchronous rectifier SR1 and SR3 conducting.
Mode2 (t1 ~ t2): when resonant capacitance voltage Vcr exceedes after V bus certain value (Δ V), D2, D4, TVS1 and TVS2 conducting (id2 & Id4 and iTVS), clamp circuit starts to work, resonant capacitance voltage Vcr is clamped at V clamp, clamping voltage V clamp is than the high Δ V of DC bus input voltage V bus, this voltage drop is (VTVS) on TVS, the electric current (id2 & Id4) that flows through D2 and D4 when clamp also flows through TVS1 and TVS2 (iTVS) simultaneously, primary side resonance current is restricted to ip limit value, and secondary side synchronous rectifier SR1 and SR3 continue conducting.
Mode3 (t2-t3): turn-off at t2 moment switch Qb & Qd, through one section of Qa & Qc, Dead Times of not conducting of Qb & Qd, primary side current by the afterflow of Qa & Qc body diode after, switch Qa & Qc starts conducting in ZVS mode, the voltage being applied on resonant tank is-Vin, primary side current ip declines from ip limit value, voltage Vcr on resonant capacitance Cr is clamped on, clamping voltage value V clamp, but flow through clamping diode D2, the electric current (id2 & Id4 and iTVS) of D4 and TVS is declining gradually, drop to after certain value at electric current, the pressure drop at TVS two ends also starts to decline, during to t3, flow through clamping diode D2, the electric current of D4 and TVS drops to zero, and the pressure drop at TVS two ends also drops to and is approximately zero.
Seemingly, clamping diode is that D1 and D3 conducting are worked for Mode4 (t3-t4), Mode5 (t4-t5) and three patterns of Mode6 (t5-t6) and aforementioned Mode1 (t0 ~ t1), Mode2 (t1 ~ t2) and three Pattern Class of Mode3 (t2-t3).Be limited in-ip of primary side resonance current limit value.Be clamped at-V of resonant capacitance voltage Vcr clamp.
Mode1 (t0 ~ t1), Mode2 (t1 ~ t2), Mode3 (t2-t3), Mode4 (t3-t4), Mode5 (t4-t5) and Mode6 (t5-t6) have formed a complete cycle.
Fig. 8 and Fig. 9 separate resonant capacitance, and the method for clamp partial resonance capacitance voltage can further improve clamping voltage value.
The present invention, except applying to the half-bridge resonance circuit shown in Fig. 6 and Fig. 8, outside the full-bridge resonant circuit OCP clamp shown in Fig. 7 and Fig. 9, is also included in the OCP clamp of the converter such as three current potentials and many current potentials resonance to expand protective circuit.The present invention (for example can utilize single clamp semiconductor, diode) and voltage assembly carry out clamp on one side of DC bus, for example, Figure 13 shows the 5th preferred embodiment according to the present invention's conception, it is with a voltage assembly Vx1 and carries out clamp on one side of DC bus, and with the circuit diagram of the symmetrical bridge-type resonant circuit of diode clamp resonant capacitance voltage.The main difference of itself and Fig. 7 be in, it uses a voltage assembly Vx1 to carry out clamp, and in Fig. 7, uses two voltage assembly Vx1 and Vx2 to carry out clamp.Separately, the transformer T in Fig. 7 is replaced by two transformer T1 and T2 in Figure 13, and resonant inductance Ls1 and magnetizing inductance Lm2 transposition, and resonant inductance Ls2 and magnetizing inductance Lm1 transposition.And Fig. 6 is in Fig. 9, Figure 11 and Figure 13, this bridge circuit Qa-Qb or Qa-Qd are a square-wave device.Except Figure 13, in other preferred embodiment of the present invention, in order to make circuit symmetrical obtain better effect on DC bus both sides symmetrical clamp.This method is simple and easy to realize, and without extra control circuit, belongs to passive and controls, and reliability is very high.Can make circuit design more flexible, make parameter select not substantially to be subject to the restriction of clamp circuit, have advantages of that circuit working scope is large, and can change flexibly as required clamping voltage value, make it to realize within the specific limits decoupling zero with DC input voitage.Because only needing to increase partial circuit, therefore its cost is lower.
In sum, the present invention has disclosed a kind of controlled resonant converter and control method thereof of tool overcurrent protective device, in the time of controlled resonant converter secondary circuit short-circuit, overcurrent protection is provided, and solve the excessive problem of controlled resonant converter primary side switching current stress, simultaneously also solved resonant capacitance voltage and can only be clamped at input voltage, primary side switching current stress determines by input voltage completely, and controlled resonant converter circuit design parameter and working range such as are restricted at the problem; Thereby really there are its progressive and a novelty.
Even if can be thought and be to modify as all by the personage Ren Shi craftsman who is familiar with this skill therefore this case has described in detail by above-mentioned embodiment, so neither de-as Protector that attached claim is wanted.
Claims (19)
1. a DC-DC controlled resonant converter, is characterized in that, comprises:
One square-wave device, for generation of a voltage with square-wave waveform, comprising:
One first input end and one second input, for receiving a DC input voitage;
One resonant slots, is coupled in this square-wave device, comprising:
One first resonant capacitance; And
One resonant inductance, is coupled in this first resonant capacitance; And
One overcurrent protective device, is coupled between this first resonant capacitance and this first input end, comprising:
One first switch module, is semiconductor switch, tool one first and 1 second end; And
One first voltage assembly, be one to there is the assembly of voltage source characteristic, tool one negative pole end and a positive terminal, wherein this negative pole end is coupled in this first input end, and this positive terminal is coupled in this second end of this first switch module, this resonant slots more comprises one of tool one first end and one second end the second resonant capacitance, this the first resonant capacitance tool one first and 1 second end, this overcurrent protective device more comprises one of tool one first end and one second end second switch assembly and one of tool one negative pole end and positive terminal second voltage assembly, this second switch assembly is semiconductor switch, this second voltage assembly is one to have the assembly of voltage source characteristic, this first end of this first resonant capacitance is coupled in this negative pole end of this first voltage assembly, this second end of this first resonant capacitance is coupled in this second end of this second switch assembly, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, this positive terminal of this second voltage assembly is coupled in this second input, this second end of this second switch assembly is coupled in this first end of this first switch module, this second end of this second resonant capacitance is coupled in this positive terminal of this second voltage assembly, and this first end of this second resonant capacitance is coupled in this second end of this first resonant capacitance.
2. converter as claimed in claim 1, it is characterized in that, this first is respectively one of each tool one anode and negative electrode first and one second clamping diode with this second switch assembly, and respectively this anode and this negative electrode of this diode are respectively this first end and this second end of this switch module.
3. converter as claimed in claim 1, it is characterized in that, respectively this first is selected from a piezo-resistance (Varistor), a gas discharge tube (Gas tube), a unidirectional Transient Voltage Suppressor (TVS), a bidirectional transient voltage suppressor (TVS), a RC with this second voltage assembly system and composes in parallel circuit and by wherein arbitrary the MOSFET of gate and source electrode short circuit.
4. converter as claimed in claim 1, more comprise a magnetizing inductance, one transformer, one output rectification circuit, one output capacitance and a current source, and be a LLC controlled resonant converter, it is characterized in that, this the first resonant capacitance tool one first end and one second end, this overcurrent protective device more comprises one of tool one first end and one second end second switch assembly and one of tool one negative pole end and positive terminal second voltage assembly, this second switch assembly is semiconductor switch, this second voltage assembly is one to have the assembly of voltage source characteristic, this first end of this first resonant capacitance is coupled in this negative pole end of this first voltage assembly, this second end of this first resonant capacitance is coupled in this second end of this second switch assembly, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, this positive terminal of this second voltage assembly is coupled in this second input, this square-wave device is a bridge circuit, this bridge circuit more comprises a switching switch circuit, this magnetizing inductance, each tool one first and 1 second end of this resonant inductance and this output capacitance, this switching switch circuit comprises the first diverter switch and second diverter switch of each tool one first and 1 second end, this output rectification circuit comprises one of each tool one anode and negative electrode first and one second rectifier diode, this transformer comprises the secondary side winding of a first side winding and tool one first and 1 second end and a center tap, this first end of this first diverter switch is coupled in this negative pole end of this first voltage assembly, this second end of this first diverter switch is coupled in this first end of this second diverter switch, this second end of this second diverter switch is coupled in this positive terminal of this second voltage assembly, this first end of this resonant inductance is coupled in this second end of this first diverter switch, this first end of this magnetizing inductance is coupled in this second end of this resonant inductance, this second end of this magnetizing inductance is coupled in this second end of this second switch, this first side winding parallel connection is electrically connected on this magnetizing inductance, this first end of this secondary side winding is coupled in this anode of this first rectifier diode, this second end of this secondary side winding is coupled in this anode of this second rectifier diode, this negative electrode of this first rectifier diode is coupled in this negative electrode of this second rectifier diode, this first end of this output capacitance is coupled in this negative electrode of this second rectifier diode, this second end of this output capacitance is coupled in this center tap, and this current source parallel connection is electrically connected on this output capacitance.
5. converter as claimed in claim 1, more comprise one of each tool one first end and one second end second, one the 3rd and 1 the 4th resonant capacitance, it is characterized in that, this the first resonant capacitance tool one first end and one second end, this overcurrent protective device more comprises one of tool one first end and one second end second switch assembly and one of tool one negative pole end and positive terminal second voltage assembly, this second switch assembly is semiconductor switch, this second voltage assembly is one to have the assembly of voltage source characteristic, this first end of this first resonant capacitance is coupled in this negative pole end of this first voltage assembly, this second end of this first resonant capacitance is coupled in this second end of this second switch assembly, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, this positive terminal of this second voltage assembly is coupled in this second input, this first end of this second resonant capacitance is coupled in this second end of this first resonant capacitance, this first end of the 3rd resonant capacitance is coupled in this second end of this second resonant capacitance, this first end of this first switch module is coupled in this second end of the 3rd resonant capacitance and this first end of the 4th resonant capacitance, and this second end of the 4th resonant capacitance is coupled in this second input.
6. converter as claimed in claim 1, it is characterized in that, this square-wave device is a bridge circuit, and more comprise that one first brachium pontis is coupled between this first input end and this second input, and this first brachium pontis comprises one first diverter switch and one second diverter switch, wherein this second diverter switch is coupled to this first diverter switch.
7. converter as claimed in claim 6, it is characterized in that, this bridge circuit is a full bridge structure, and comprises that one second brachium pontis is coupled between this first input end and this second input, and this brachium pontis comprises that one the 3rd diverter switch and one the 4th diverter switch are coupled to the 3rd diverter switch.
8. converter as claimed in claim 7, it is characterized in that, this the first resonant capacitance tool one first and 1 second end, this overcurrent protective device more comprises one of each tool one first end and one second end the second to 1 the 4th switch module, this second to the 4th switch module is respectively semiconductor switch, this first end of this first resonant capacitance is coupled in this second end of this second switch assembly, this second end of this first resonant capacitance is coupled in this first end of the 4th switch module, this second end of this second switch assembly is coupled in this first end of this first switch module, this first end of the 3rd switch module is coupled in this first end of this second switch assembly, this second end of the 4th switch module is coupled in this second end of this first switch module, this first end of the 4th switch module is coupled in this second end of the 3rd switch module, this second input is coupled in this first end of the 3rd switch module, this negative pole end of this first voltage assembly is coupled in this first input end, and this positive terminal of this first voltage assembly is coupled in this second end of this first switch module.
9. converter as claimed in claim 8, it is characterized in that, this first to the 4th switch module is respectively one of each tool one anode and a negative electrode the first to 1 the 4th clamping diode, and respectively this anode and this negative electrode of this diode are respectively this first end and this second end of this switch module.
10. converter as claimed in claim 8, it is a LLC circuit, and more comprise one first and 1 second resonant inductance, one first and 1 second magnetizing inductance, one first transformer, one second transformer, one circuit of synchronous rectification, one first and 1 second output capacitance, one outputting inductance and a current source, it is characterized in that, this full bridge structure more comprises a switching switch circuit, this switching switch circuit be coupled in this first with this second input and this first and this second magnetizing inductance, this first magnetizing inductance is coupled in this second resonant inductance, this second resonant inductance is coupled in this second end of this first resonant capacitance, this second magnetizing inductance is coupled in this first resonant inductance, this first resonant inductance is coupled in this first end of this first resonant capacitance, this is first transformer coupled in this first magnetizing inductance and this circuit of synchronous rectification, this is second transformer coupled in this second magnetizing inductance and this circuit of synchronous rectification, this first is all coupled in this circuit of synchronous rectification with this second output capacitance and this outputting inductance, and this current source parallel connection is electrically connected on this second output capacitance.
11. converters as claimed in claim 7, it is characterized in that, this the first resonant capacitance tool one first and 1 second end, this overcurrent protective device more comprises second voltage assembly and one of each tool one first end and one second end second to 1 the 4th switch module of tool one negative pole end and a positive terminal, this second voltage assembly is one to have the assembly of voltage source characteristic, this second to the 4th switch module is respectively semiconductor switch, this first end of this first resonant capacitance is coupled in this second end of this second switch assembly, this second end of this first resonant capacitance is coupled in this first end of the 4th switch module, this second end of this second switch assembly is coupled in this first end of this first switch module, this first end of the 3rd switch module is coupled in this first end of this second switch assembly, this second end of the 4th switch module is coupled in this second end of this first switch module, this first end of the 4th switch module is coupled in this second end of the 3rd switch module, this negative pole end of this first voltage assembly is coupled in this first input end, this positive terminal of this first voltage assembly is coupled in this second end of this first switch module, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, and this positive terminal of this second voltage assembly is coupled in this second input.
12. converters as claimed in claim 11, it is a LLC circuit, and more comprise one first and 1 second resonant inductance, one first and 1 second magnetizing inductance, one transformer, one circuit of synchronous rectification, one first and 1 second output capacitance, one outputting inductance and a current source, it is characterized in that, this full bridge structure more comprises a switching switch circuit, this switching switch circuit be coupled in this first with this second input and this first and this second resonant inductance, this first resonant inductance is coupled in this second magnetizing inductance, this second magnetizing inductance is coupled in this first end of this first resonant capacitance, this second resonant inductance is coupled in this first magnetizing inductance, this first magnetizing inductance is coupled in this second end of this first resonant capacitance, this transformer coupled in this first with this second magnetizing inductance and this circuit of synchronous rectification, this first is all coupled in this circuit of synchronous rectification with this second output capacitance and this outputting inductance, and this current source parallel connection is electrically connected on this second output capacitance.
13. converters as claimed in claim 11, more comprise one second and 1 the 3rd resonant capacitance, it is characterized in that, this second with each tool one first and 1 second end of the 3rd resonant capacitance, this second end of this second resonant capacitance is coupled in this first end of this first resonant capacitance, and this first end of the 3rd resonant capacitance is coupled in this second end of this first resonant capacitance.
14. converters as claimed in claim 13, it is a LLC circuit, and more comprise one first and 1 second resonant inductance, one first and 1 second magnetizing inductance, one transformer, one circuit of synchronous rectification, one first and 1 second output capacitance, one outputting inductance and a current source, it is characterized in that, this full bridge structure more comprises a switching switch circuit, this first with this second resonant inductance and this first and each tool one first and 1 second end of this second magnetizing inductance, this switching switch circuit has one first and 1 second mid point, this switching switch circuit be coupled in this first with this second input, this first end of this first resonant inductance is coupled in this first mid point, this second end of this second resonant inductance is coupled in this second mid point, this second end of this first resonant inductance is coupled in this second end of this second magnetizing inductance, this first end of this second magnetizing inductance is coupled in this first end of this second resonant capacitance, this first end of this second resonant inductance is coupled in this first end of this first magnetizing inductance, this second end of this first magnetizing inductance is coupled in this second end of the 3rd resonant capacitance, this transformer coupled in this first with this second magnetizing inductance and this circuit of synchronous rectification, this first is all coupled in this circuit of synchronous rectification with this second output capacitance and this outputting inductance, and this current source parallel connection is electrically connected on this second output capacitance.
15. 1 kinds for one first group of tool one overcurrent protective device, a resonant tank and a tool control method with the DC-DC controlled resonant converter of the switching switch circuit of one second group of switch, it is characterized in that, this overcurrent protective device, comprise: one first switch module, for semiconductor switch, tool one first end and one second end, and one first voltage assembly, be one to there is the assembly of voltage source characteristic, tool one negative pole end and a positive terminal, wherein this negative pole end is coupled in outer one of DC input voitage source positive terminal in addition, this positive terminal of this first voltage assembly is coupled in this second end of this first switch module, this resonant tank more comprises first and second resonant capacitance of each tool one first end and one second end, this overcurrent protective device more comprises one of tool one first end and one second end second switch assembly and one of tool one negative pole end and positive terminal second voltage assembly, this second switch assembly is semiconductor switch, this second voltage assembly is one to have the assembly of voltage source characteristic, this first end of this first resonant capacitance is coupled in this negative pole end of this first voltage assembly, this second end of this first resonant capacitance is coupled in this second end of this second switch assembly, this negative pole end of this second voltage assembly is coupled in this first end of this second switch assembly, this positive terminal of this second voltage assembly is coupled in one of this outer DC input voitage in addition source negative pole end, this second end of this second switch assembly is coupled in this first end of this first switch module, this second end of this second resonant capacitance is coupled in this positive terminal of this second voltage assembly, this first end of this second resonant capacitance is coupled in this second end of this first resonant capacitance, and the method comprises following step:
(a) provide an input voltage, a resonant capacitance voltage and a resonance current;
(b) when this converter is at a normal resonance working stage, make this first group of switch conduction of this switching switch circuit;
(c) reach after one first predetermined value when this resonant capacitance voltage exceedes this input voltage, make this overcurrent protective device conducting; And
(d), in the time that this resonance current reduces since the maximum resonance current value of a forward, this first group of switch turn-offed.
16. methods as claimed in claim 15, is characterized in that, this step (b) more comprises following step:
(b1) this input voltage is carried on this resonant tank;
(b2) make this resonance current from the zero maximum resonance current value that is increased to this forward; And
(b3) make this resonant capacitance voltage be increased to the maximum clamping voltage value of a forward from the maximum clamping voltage value of a negative sense, wherein the maximum clamping voltage value of this forward is greater than this input voltage value.
17. methods as claimed in claim 15, is characterized in that, this step (c) more comprises following step:
(c1) make this resonant capacitance voltage be clamped at the maximum clamping voltage value of a forward; And
(c2) make this resonance current be restricted to the maximum resonance current value of this forward.
18. methods as claimed in claim 15, is characterized in that, this step (d) more comprises following step:
(d1), through a Dead Time, then make the mode conducting of this second group of switch with a zero voltage switching;
(d2) apply one of this input voltage negative value on this resonant tank, make this resonance current start to decline from the maximum resonance current value of this forward;
(d3) make this resonant capacitance voltage maintain maximum clamping voltage value a period of time of a forward; And
(d4), when this resonance current drops to after one second predetermined value, this resonant capacitance voltage is also declined gradually.
19. methods as claimed in claim 18, it is characterized in that, this DC-DC controlled resonant converter is a DC-DC controlled resonant converter as claimed in claim 13, wherein this first group of switch be this second with the 4th diverter switch, this second group of switch be this first with the 3rd diverter switch, and this resonant tank be this first with this second resonant inductance, this first and this second magnetizing inductance and this first resonant capacitance.
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Families Citing this family (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102201739B (en) * | 2011-05-27 | 2014-07-09 | 华北电力大学（保定） | Symmetrical half-bridge LLC resonant bidirectional DC-DC converter |
| JP5857489B2 (en) * | 2011-07-15 | 2016-02-10 | サンケン電気株式会社 | Resonant converter |
| CN104377960B (en) * | 2013-08-15 | 2018-04-20 | 南京博兰得电子科技有限公司 | Controlled resonant converter and its control method |
| CN104917364B (en) * | 2015-06-23 | 2018-01-02 | 杭州中恒派威电源有限公司 | A kind of new LLC current foldback circuits |
| CN106230264A (en) * | 2016-08-11 | 2016-12-14 | 国网天津市电力公司 | A kind of high-efficient single direction LLC resonance DC DC translation circuit topological structure |
| CN106160496A (en) * | 2016-08-17 | 2016-11-23 | 深圳市鼎硕同邦科技有限公司 | A kind of flat surface transformer magnetic integrated connection in series-parallel power-supply system for new-energy automobile |
| CN111669055B (en) | 2019-03-08 | 2021-05-28 | 台达电子企业管理（上海）有限公司 | Voltage conversion circuit and control method thereof |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101022247A (en) * | 2007-03-16 | 2007-08-22 | 艾默生网络能源有限公司 | Half bridge resonant transformer |
| CN101043182A (en) * | 2007-04-06 | 2007-09-26 | 艾默生网络能源有限公司 | Resonant transformer |
| CN101136592A (en) * | 2006-09-01 | 2008-03-05 | 台达电子工业股份有限公司 | Resonant converter and intermittent operation mode starting method |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH0757093B2 (en) * | 1988-03-14 | 1995-06-14 | 日本電信電話株式会社 | Series resonant converter |
| JPH09261959A (en) * | 1996-03-26 | 1997-10-03 | Meidensha Corp | Serial resonance |
-
2009
- 2009-08-14 CN CN200910168212.XA patent/CN101997421B/en active Active
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101136592A (en) * | 2006-09-01 | 2008-03-05 | 台达电子工业股份有限公司 | Resonant converter and intermittent operation mode starting method |
| CN101022247A (en) * | 2007-03-16 | 2007-08-22 | 艾默生网络能源有限公司 | Half bridge resonant transformer |
| CN101043182A (en) * | 2007-04-06 | 2007-09-26 | 艾默生网络能源有限公司 | Resonant transformer |
Non-Patent Citations (2)
| Title |
|---|
| JP平1-234052A 1989.09.19 |
| JP特开平9-261959A 1997.10.03 |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| FR3088155A1 (en) * | 2018-11-06 | 2020-05-08 | Valeo Siemens Eautomotive France Sas | ELECTRICAL SYSTEM AND METHOD FOR PROTECTING A DC / DC CONVERTER |
| EP3651328A1 (en) * | 2018-11-06 | 2020-05-13 | Valeo Siemens eAutomotive France SAS | Electrical method for protecting a dc/dc converter |
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