CN101978608B - 包含广播接收器电路并且具有天线的装置 - Google Patents
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Abstract
本发明涉及一种装置,包含广播接收器电路、用于接收广播信号的嵌入式天线和耦合在天线和接收器电路之间的调谐电路,所述调谐电路包含耦合到地的滤波器电路,其中调谐电路设计为具有在感兴趣的广播频带之下的第一频率处的第一谐振,和在所述广播频带之上的第二频率处的第二谐振,其中调谐电路包含具有到接收器电路的输出和到滤波器电路的输入的放大器,其中调谐电路具有在广播频带上实质上平坦的载噪比(CNR)。
Description
技术领域
本发明涉及一种装置,该装置包含广播接收器电路并且具有接收广播信号的天线,并且包含耦合在天线和接收器电路之间的调谐电路。
背景技术
在音频设备中,AM频率范围内的无线电接收通常通过提供内置铁氧体天线实现。这样的铁氧体天线配置用于无线电频谱的预定频带。铁氧体天线提供接收电磁波的磁部分的天线和具有附加电容的谐振电路的功能。随后的天线放大器的第一级可以具有宽带配置,且选择性在第二放大器级获得。
这样的铁氧体天线可能具有劣势,因为内部产生的电磁场(例如来自中央处理单元(CPU)、微型电子计(uC)等)作为噪声被接收。内置铁氧体天线的物理尺寸对于AM接收的灵敏度是关键因素。具有无线电接收器的音频设备的越发小型化需要更小的铁氧体,这导致了在无线电接收灵敏度上的不合需求的下降。
通过在房外放置AM天线,可以提高灵敏度,并且通过移走铁氧体,在印刷电路版(PCB)上额外的区域变得可用。这个被释放的区域可用于其他电路元件。
对于外置无线电天线,一个放置的选择可以是音频设备的耳机,包括到耳机的电线。这一点例如在US 2005/0285799A1中建议,其披露了通过环部分实现的耳机环天线,所述环部分包括电感器,并且其中到耳塞的导体包括铁氧体磁珠。在环部分中的每一个导体形成了匹配元件,在所述匹配元件中它匹配环天线的所需的接收频率。环天线片断互相耦合,且在Y型耦合器处耦合到导电的天线引线部分。可选地,两个天线环部分可以在耳机塞处直接相连。
然而,为了模拟铁氧体天线的存在和/或将环天线调谐到所需的频率范围,对天线环配置中的电感器的合适选择对于将天线匹配到接收器电路和频率范围至关重要。
对于外置天线放置的另一个选择在于耳机线的使用。对于这样的耳机线,可以推导接收曲线。然而,此曲线被测量为附着到自由空间的顶部的电线。在实际中,因为电线和人体接触,输入阻抗连续变化。这降低了天线的性能。天线性能的降低归因于反射。由于天线和无线电均设计为75欧姆输入阻抗,与人体耦合产生反射,导致辐射天线且降低了发射到无线电的功率。降低发射功率是存在问题的,因为许多无线电信道工作在比基于无线电信道的标准建议的场强更低的场强上。
因此,简而言之,耳机线作为天线的使用存在问题,天线对于随环境的变换很灵敏,且因此易于在频带上偏离/偏移。
发明内容
因此,本发明的目标是提供在开篇提及的类型的装置,其中信号的接收对于随环境的变化较不灵敏,且因此在频带上较不易偏离/偏移。
在本发明的第一方面,该装置包含广播接收器电路、接收广播信号的嵌入式天线和耦合在天线和接收器电路之间的调谐电路,其中调谐电路包含耦合到地的滤波器电路,其中调谐电路
-设计为在感兴趣的广播频带之下的第一频率处具有第一谐振,且在广播频带之上的第二频率处具有第二谐振,和
-包含具有到接收器电路的输出和到滤波器电路的输入的放大器,和
-提供载噪比(CNR),其在广播频带上基本平坦。
经证实,与特定的调谐电路结合使用嵌入式天线导致了在感兴趣的广播频带上的信号的接收以优异的方式满足了性能需求。本发明的发明人在此理解的是,基本平坦的载噪比,而不是经常采用的功率匹配,是获得好的性能的关键参数。这意味着,从天线注入到调谐电路的电压被转换为相对平坦的振幅响应。利用这样相对平坦的振幅响应,即使信号强度相对有限,也可以从噪声中识别信号。在应用接收信号的1mV/m的场强时,载噪比合适地在放大器之后为至少20dB。优选地,在这样的情况下,载噪比至少为30dB。
出于清楚起见,应留心到,术语“CNR”不同于术语“信噪比”。CNR定义了在解调之前,广播频带中某一频率处的信号的电平与在相同频率处的噪声的比率。信噪比涉及解调信号,即在接收器电路中解调之后。CNR涉及在相同频率(例如100MHz)处的噪声,信噪比涉及在特定频率(例如10KHz)的信号与在特定频率范围(例如0到20KHz)的噪声。
更适宜地,滤波器电路和放大器具有可比较的噪声电平。这经证实是提供了最优化的信号传送。经证实,由于在滤波器和放大器之间的不匹配,具有非常低的噪声电平的滤波器电路可以导致整个信号传送的恶化。显然,如果滤波器中的噪声电平过高,滤波器的载噪比降低且放大器不能够充分地放大信号。
更具体地,滤波器电路包括品质因数在30到100范围内的至少一个电感器。在此范围内的品质因数可导致充分低的噪声电平。
更进一步,嵌入式天线比对应于广播频带的波长要小。虽然嵌入式天线存在于离其它电子组件很短的距离处,并且因此对失真敏感,但具有相比波长小尺寸的天线的使用经证实是可行的。合适地,波长和天线尺寸的比率大于10,且优选的是大于50。利用电容性带状天线已经获得非常好的结果,但是可以可选地使用电感性天线。
而且,放大器优选设计为在驱动阻抗很低的情况下具有最适宜的噪声电平。传统上,接收器电路的输入面对约200欧姆的驱动阻抗(从接收器电路看向天线)。这很大程度上归因于具有较大长度的非嵌入式天线的存在。在本文的情形下,滤波器电路和嵌入式天线的阻抗加起来不到50欧姆,且甚至优选地在5-30欧姆范围内,更优选地为10-20欧姆。作为结果,放大器的设计也因此调整。
在优选实现中,将参照附图,解释使用具有输入电极的放大器,所述电极具有到基极的低连接电阻。特别地,由于输入电极形成具有与扩展表面区域的基极连接的双极型晶体管的一部分,获得了这样的低连接电阻。优选地,表面区域至少是这样的输入电极的传统值的两倍。
适宜地,放大器设计为具有常数振幅响应。这样的常数振幅响应意味着很小的波动,优选地低于3dB。在响应中较大的波动和变化导致放大器的增益的频率依赖性。这导致了在广播信道搜寻中的性能的下降。为了获得这种常数振幅响应,输入阻抗和滤波器电路的阻抗的很好的匹配是需要的。这种输入阻抗更优选地在电感性天线情况下在20Ω到500Ω的范围内,对于电容性天线在300Ω到2kΩ的范围内。
最适宜地,放大器优选地具有到输入电极的内部反馈。这是能够获得常数振幅响应的合适的方式,且特别地将提供适合电容性天线的输入阻抗的适当值。
放大器优选地包含第一和第二晶体管的共发共基放大器(cascode)。放大级别适宜为10-30dB的量级,更优选地为约20dB。在进一步的实现中,滤波器具有经典的双调谐滤波器拓扑,且天线是电容性带状天线。在移动电话装置的情况下,它位于远离其他天线的一边。
在进一步的实施例中,存在发射电路。该发射电路耦合到用于通过天线的音频信号的无线传输的滤波器电路,其中调谐电路设计为作为用于抑制发射信号中的谐波的滤波器操作。虽然传统上只接收广播信号,但近来的标准也允许在用于广播的频带内发射信号。这特别涉及到要在FM频率范围内作为调频(FM)信号以低功率电平发送的音频。在此的目标是发送音乐和来自便携式装置的其它音频到耦合到较大的扬声器的集成音频系统,包括汽车广播和家用音频系统。
已经发现最适宜的是,从发射电路到滤波器电路的耦合可利用电容器实现,通过此电容器,RF信号可以发送但DC信号被阻挡。电容为0.5nF或更大的电容器,例如1nF的电容器因此经证实是适宜的。在此实施例中,接收/发射开关存在于电容器和放大器以及发射电路之间。需要接收/发射开关,以防止发射电路中的放大信号直接进入接收电路,所述接收电路被设计用于低电平的信号。这种实现极好地符合了集成的期望和要求;接收/发射开关设计为包含广播接收器、放大器和发射电路的集成电路的一部分。电容器为分立元件,或可选地集成在封装内。为了满足电压稳定性的要求,接收/发射开关可以以第一和第二晶体管的串联连接实现。
优选地,发射电路的输出阻抗对应于放大器的输入阻抗。这导致了该重要特性,即天线上的电流响应在广播频带上基本平坦。该特性比在广播频带上提供平坦的电压响应更重要。输出阻抗例如在20Ω到2kΩ范围内。更优选地,输出阻抗相对低,因为具有较大输出阻抗的发射电路从电池中汲取更多的功率且因此带来效率的降低。100-500Ω的范围,尤其200-400Ω经证实是最优的,且其可以在使用电容性天线时实现。
在进一步的修改中,利用电阻器将开关向滤波器电路的输出极化到较高的电压。该修改提供了对于相对低的电源电压和ESD保护元件的存在的兼容性的解决方案。通常,集成电路的任意输入/输出端具有ESD保护,其在特定的配置中是二极管或晶体管。作为ESD保护的结果,输入/输出端通常具有在电源电压和零之间的电压摆动。然而,无线电信号,即在FM广播频带内的,被调制在地附近。它因此具有负的和正的部分。这些负的部分由于ESD保护将失去。因此,提出的解决方案是信号电平的转换,从而使无线电信号被调制在高于地的中心值附近。为了利用可用的最大电压范围,FM调制信号优选地在地电平和电压源之间适配。
适宜地,接收器电路具有到外置天线的输出,并且包含在外置天线和嵌入式天线之间选择的开关。这样的外置天线可集成在到耳机的线中。虽然在移动电话和耳机之间的通信可以无线建立,例如通过利用蓝牙协议的无线通信,但希望向用户提供使用有线耳机的选择。外置天线适宜通过不平衡变压器耦合到接收器电路。
附图说明
参照下文描述的实施例,本发明的这些和其它特性将是显而易见和明晰的。在附图中:
图1描述了第一实施例中的发明的系统的框图;
图2描述了根据第一实施例的嵌入式天线和调谐电路的电路图;
图3描述了调谐电路中的放大器的电路图;
图4描述了电容性天线的示意图;
图5描述了作为频率的函数的获得的增益;
图6描述了作为频率的函数的载噪比;
图7描述了作为频率的函数的双耳式天线和嵌入式天线之间的性能差异;
图8描述了包括接收和发射模式的电路的原理图;
图9描述了天线上的电压;和
图10描述了作为频率的函数的通过天线发射的电流。
具体实施方式
现在描述本发明的实施例。根据本发明的系统包含嵌入式天线、调谐电路和接收器电路。系统可以用于,例如接收像FM广播、DVB-H等的广播台和发射产生于手持产品的mp3音频信号到可利用的广播FM无线电设备,如汽车无线电设备。
图1描述了第一实施例中的发明的系统的电路框图。该实施例的系统包括接收器功能,但不包括发射器功能。它包含嵌入式天线30、滤波器电路10、放大器20和广播接收器电路50。滤波器电路10和放大器20一起构成了用于嵌入式天线30的调谐电路100。嵌入式天线30和调谐电路100的组合显示出对于感兴趣的广播频带的满意的接收性能。在本示例中,该感兴趣的广播频带是音频广播频带,尤其是87.5到108MHz或76到108MHz范围的FM广播频带。
嵌入式天线30和它的调谐电路100目的在于取代外置天线。对于同样的广播频带的传统的天线解决方案使用连接到用户的耳机的电线作为外置天线。图1也描述了这种外置天线60和用于适当信号转换的不平衡变压器61。这具有几个优势;第一,装置的用户可以选择它更优选的天线。第二,天线的性能对环境条件和附近信号的失真很敏感。经证实的是,嵌入式天线在某些使用条件下比外置天线具有显然更好的性能,反之亦然,并且,在几个广播频带可用(例如除FM之外DVB-H等)的情况下,这甚至对于广播频带的某些子范围、对于待接收信号的某些类型或对于选择的特定的广播频带是不同的。外置和嵌入式天线的可用性允许接收器电路50通过选择一个天线或在比较通过嵌入式天线30和外置天线60接收到的信号的基础上实现更好的错误纠正来优化接收性能。
如图1中进一步指出,最适宜的是,放大器20与接收器电路50集成到单一组件(即集成电路)中。其它的元件作为分立组件添加。然而,这不排除滤波器电路中的电容器和甚至小电感器集成到这样的集成电路中,或可选的,集成到用于集成电路的封装中。
图2描述了根据图1的第一实施例的嵌入式天线30和包含滤波器电路10和放大器20的调谐电路100的电路图。在此实施例中,滤波器电路10具有经典的双滤波器拓扑,其中第一和第二电感器13和14位于从天线30到放大器20的信号线19上。此实施例对于电容性嵌入式天线30最优化。在电感性嵌入式天线30的情况下,第一和第二电感器13和14的至少一个被电容器取代。滤波器电路10额外包含在信号线19与地之间并联连接的第三电感器15和电容器11,和在两个并联分支之间的信号线中限定的另外的电容器12。
本发明的关键处特别是利用此经典双滤波器拓扑获得的功能。它不排除同样的电气功能也可以利用其他的特定的电路产生。此功能包含在广播频带之下的第一频率处的第一谐振的存在,和在广播频带之上的第二频率处的第二谐振的存在。如图5等详细阐述的那样,第一频率例如是65MHz且第二频率例如是115MHz。利用线圈和电容器的值的准确的组合,将性能最大化到感兴趣的频带(例如在76到108MHz范围内)是可能的。此范围对应于FM广播频带的日本和US/欧洲版本。在此实施例中描述的特定的修改中,在信号线19中限定的串联电感器被划分成第一和第二电感器13和14。使用相对高电感的单一线圈是有风险的,线圈可能陷入广播频带内的谐振,导致不良性能。
最好在带宽的几何平均数概念下解释滤波器的操作。几何平均数由广播频带的所需的起始和终止频率定义。经证实,由在信号线19中的电感器13/14形成的且包括电容性嵌入式天线30的贡献的串联电路对于广播频带的几何平均数之上的频率是电感性的。然而,此串联电路对于广播频带的几何平均数之下的频率是电容性的。除串联电路之外,还存在并联电路,所述并联电路由嵌入式天线30的电容、第二电容器12的电容以及由并联连接的第一电容器11和第三电感器15耦合到地的电容和电感定义。
在此实施例中,在广播频带之下的第一频率处的第一谐振由并联电路和并联的串联电路的等效电容值产生。增加并联的电容降低此频率。在广播频带之上的第二频率处的第二谐振由并联电路和并联的串联电路的等效电感值产生。并联电路在此频率处是电感性的。此并联连接降低了总的电感,导致第二谐振的第二频率位于广播频带之上。
当第一和第二谐振发生在频带之下和之上时,电路表现为在感兴趣的广播频带内的串联谐振电路。利用组件值的某一集合,在频带内最大化性能是可能的。频带上的幅度响应可能具有波动,但RF载噪比可以最优化。然而,在频带上也应该有足够的绝对增益。注意到,未指示电感器的寄生电容,但其在电路的实现中很重要。寄生电容值取决于线圈的类型,且对于高频来说具有增大电感值的效果。
嵌入式天线30和滤波器电路10的组合是有效的,在上述描述中嵌入式天线30作为滤波器的一部分操作。这是可能的,因为嵌入式天线主要是电抗性的。外置天线不可避免的较长,通常具有波长的量级。本发明的嵌入式天线与波长相比较小。在此适宜的尺寸为小于波长的十分之一(0.1),更优选地为小于波长的二十分之一(0.05)或四十分之一(0.025)。作为结果,本发明的嵌入式天线30不具有大辐射电阻。这导致了总阻抗的高电抗性,从而使辐射电阻的转换是实际不可行的。
特别优选的是信号线19中的第二电容器12的存在。这个电容器的存在能够使放大器的输入阻抗调整到对于载噪比最优的值。
图3描述了本发明的调谐电路100中的放大器20的实现示例。放大器20具有第一晶体管21和第二晶体管22的拓扑。晶体管21和22适宜是双极型晶体管,但可以可选地使用CMOS晶体管。第一晶体管21具有输入电极26,所述输入电极26接收来自滤波器电路10的的信号。为了和滤波器电路10合适地匹配,放大器应具有低噪声性能。在集成放大器的情况下,在输入电极26是低电阻时这可以实现。特别地,输入电极26具有到半导体衬底中的下面区域(例如双极型晶体管的基极)的较大的连接面积。这里的词语“较大”是与普通晶体管相比而言的。特别地,输入电极26具有较大的表面积。其它电极的表面积相对较小,且为了满足价格要求因而保持较小。在集成放大器的情况下,合适地,在放大器内从第二晶体管22到输入电极26的反馈使得实现在广播频带上的恒定幅度响应。在此示例中存在电阻23、24和25,以适当地调整反馈和电流。
图4描述了嵌入式电容性天线30的电路图。在此示例中,天线可以是任意形状的导电片,且例如可以由导电胶带构成。天线30包含可以在导电片上任意位置的馈送点。馈送点位置只引起性能上些微的差异。每一个维度——长度、高度和厚度——低于波长的5%。厚度(T)可以低于波长的0.1%。这样的结构可以附在最终产品的塑料外壳上,几乎不会占用任何体积。导电片上的开口可以用来临时连接最终产品内的另外的部分。天线是嵌入式的,例如,它嵌入在,或者可以嵌入在通常由便携式装置形成的系统中。
嵌入式天线30适于装配在便携式装置例如移动电话的底面。这里的底面指当握住移动电话靠近人的耳朵以便进行电话通话时通常在底部的那一面。可选地,它可以是与其它天线的干扰相对小且可用的任何其他面。在基本为块状的设备中,一个可选的合适的面看来是与底面相对的顶面。这经证实是最小化用户的手效应的有利位置。
更优选的,天线在FM频带上是电容性的。电抗严重依赖结构和环境。对如此小的天线,辐射电阻和感应电压在FM频带上也相对恒定。天线馈电可以在金属薄片的中央或在角落。角落馈电细微地提高感应电压。
在便携式装置内嵌入天线经证实对于接收和发射是合适的。首先,对环境的敏感性相比外置天线变得有限。而且,便携式装置和任何与之接触的物体经证实在天线操作上具有积极的效果:尺寸比手机本身大的物体增加了天线辐射电阻。在这样的物体(包括装置)在天线的电容值上只引入细微的增加的同时,电容性嵌入式天线的感应电压以此方式增加。
图5指示了在频带上获得的增益。
增益是天线滤波器增益和放大器增益的组合。增益示出了在约70MHz处的第一最大值和在约110MHz处的第二最大值。最小值出现在90MHz。最大值处的增益接近25,最小值处的增益接近20。增益上的这样的差异可以理解为不存在问题,只要最小值具有足够的值,例如10dB。
频带上的RF载噪比经证实对于调谐电路的性能来说是更重要的。图6指示了在调谐电路的输出处对于电场强度1mV/m的RF载噪比。已描述的示例为从87.5MHz到108MHz(欧洲广播频带)范围内的频带。对于1mV/m的电场,噪声等于76nV(在200KHz BW)且接收到的信号为17uV。如图所示,CNR在87MHz处具有约32.5dB的值且在110MHz处约为33dB,同时其在约97MHz处最大值为33.5dB。这意味着其差异最大为1.5dB,因此基本是平坦的。创建具有在76到108MHz的广播频带上基本平坦的CNR的滤波器电路也是可能的。
图7描述了嵌入式天线与用作天线的耳机线相比,以dB为单位的性能差异随频率的变化。这幅图展示了耳机线实际表现更好,但差异最大为17dB。这种差异经证实是可接受的。
第二实施例
图8描述了本发明的系统的第二实施例的原理图。该系统还包含发射电路40。发射电路40通过能够抑制DC信号但可以发射RF信号的耦合器41耦合到滤波器电路10。耦合器例如利用足够大小(例如1nF或更大)的电容器41实现。为了将发射电路40和接收器电路50与单一天线30相组合,需要接收/发射开关42以防止来自发射电路40的放大后的信号进入接收器电路50,尤其是直接进入放大器20。在第一实现中,例如在耦合器41与发射器电路40和放大器之间提供单一接收/发射开关42,。在第二实现中,第二接收/发射开关43存在,从而在发射电路40和耦合器41之间有一个开关42,并且在滤波器电路10和放大器20之间有一个开关。
已经发现,本发明的滤波器电路10和嵌入式天线30不仅仅只对广播频带内的信号的接收有效,还对这样的广播频带的信号的发射模式有效。另外合适地,发射电路的输出阻抗与放大器的输入阻抗类似。特别地,阻抗的值在20欧姆到2千欧姆的量级,更优选地在100到400欧姆范围内。
应观察到,这里的电容性天线的性能明显优于传统的铁氧体电感性天线。这样的电感性天线在接收模式下提供很低的1到3uV的感应电压(对于电场强度E为1mV/m)。在发射模式下对于50nW的有效辐射功率(ERP)的电流消耗为20到50mA。电容性天线的使用导致了5到25uV的感应电压(对于在接收模式下电场强度E为1mV/m)。在发射模式下对于50nW的ERP电流需求为0.5到4mA。换句话说,在接收模式下感应电压是电感性天线的5-8倍。在发射模式下电流消耗只有电感性天线的5-10%。可以理解的是,这些值是针对电容性天线的最优化的天线设计和最优化的天线位置获得的。
甚至可能驱动通过天线的恒定电流,所述电流需要用来产生在整个感兴趣的频带内几乎相同的电场。这通过整形天线上的电压来实现这一点,所述电压可以整形以产生通过天线的相对恒定的电流。人们可以利用与用于接收的滤波器电路相同的滤波器电路实现这一点。可以添加源和电路之间额外的耦合电容器。
下面的图9指示了天线在整个频带上的以伏特为单位的电压。电压补偿了天线电容的电抗的频率依赖性。该图针对0.7伏特的源电压。
图10描述了指示在感兴趣频带上通过天线的以毫安为单位的电流的图。可以看到,电流基本恒定。该图针对0.7伏特的源电压。
附图标记:
10滤波器电路
11第一电容器
12第二电容器
13第一电感器
14第二电感器
15第三电感器
20放大器
21第一晶体管
22第二晶体管
23第一电阻器
24第二电阻器
25第三电阻器
26第一晶体管的输入电极
27放大器的输出
30嵌入式天线
40发射电路
41耦合电容器
42接收/发射开关
43第二接收/发射开关
50接收器电路
60非嵌入式天线
61不平衡变压器
Claims (12)
1.一种接收装置,所述装置包含广播接收器电路、用于接收广播信号的嵌入式天线和耦合在天线和接收器电路之间的调谐电路,所述调谐电路包含耦合到地的滤波器电路,其中调谐电路设计为具有在感兴趣的广播频带之下的第一频率处的第一谐振,和在所述广播频带之上的第二频率处的第二谐振,其中调谐电路包含具有到接收器电路的输出和到滤波器电路的输入的放大器,其中调谐电路具有在广播频带上实质上平坦的载噪比。
2.如权利要求1中所述的装置,其中滤波器电路和放大器具有可比较的噪声电平。
3.如权利要求1中所述的装置,其中嵌入式天线比对应于广播频带的波长小。
4.如权利要求1中所述的装置,其中放大器对于电感性天线具有在20Ω到500Ω范围内的输入阻抗,对于电容性天线具有在300Ω到2kΩ范围内的输入阻抗。
5.如权利要求4中所述的装置,其中放大器包含到输入的内部反馈。
6.如权利要求4中所述的装置,其中放大器的输入电极具有减小的电阻连接,从而减小放大器的噪声电平。
7.如权利要求6中所述的装置,其中输入电极连接到具有增加的表面积的双极型晶体管的基极。
8.如权利要求1中所述的装置,其中滤波器电路包含电感器,所述电感器具有从30到100范围内的品质因数。
9.如权利要求1中所述的装置,进一步包含耦合到滤波器电路的用于通过天线无线发射音频信号的发射电路,其中滤波器电路设计为用于抑制发射信号中的谐波的滤波器。
10.如权利要求1或9中所述的装置,其中天线是电容性天线。
11.如权利要求9中所述的装置,其中发射电路具有实质上等于放大器的输入阻抗的输出阻抗。
12.一种在广播接收器中接收信号的方法,所述方法包含下列步骤:
通过嵌入式天线接收广播信号;以及
所述嵌入式天线通过耦合在所述嵌入式天线与所述接收器的电路之间的调谐电路来传递接收信号,其中
所述调谐电路包括耦合到地的滤波器电路,其中所述调谐电路设置为具有在感兴趣的广播频带之下的第一频率处的第一谐振,和在所述广播频带之上的第二频率处的第二谐振,其中所述调谐电路包含具有到所述接收器的电路的输出和到滤波器电路的输入的放大器,其中所述调谐电路具有在广播频带上实质上平坦的载噪比。
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CN1625844A (zh) * | 2002-01-31 | 2005-06-08 | 皇家飞利浦电子股份有限公司 | 发射机和/或接收机模块 |
Also Published As
Publication number | Publication date |
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WO2009116007A1 (en) | 2009-09-24 |
CN101978608A (zh) | 2011-02-16 |
US9054773B2 (en) | 2015-06-09 |
US20110028114A1 (en) | 2011-02-03 |
EP2258049A1 (en) | 2010-12-08 |
EP2258049B1 (en) | 2018-02-21 |
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