CN101958648A - Forward converter with functions of secondary side post-regulation and zero voltage switching - Google Patents

Forward converter with functions of secondary side post-regulation and zero voltage switching Download PDF

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CN101958648A
CN101958648A CN2009101612019A CN200910161201A CN101958648A CN 101958648 A CN101958648 A CN 101958648A CN 2009101612019 A CN2009101612019 A CN 2009101612019A CN 200910161201 A CN200910161201 A CN 200910161201A CN 101958648 A CN101958648 A CN 101958648A
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connects
transistor
winding
secondary side
anode
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CN101958648B (en
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王志良
余金生
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GLACIAL TECHNOLOGY Co Ltd
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GLACIAL TECHNOLOGY Co Ltd
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Abstract

The invention discloses a forward converter with functions of secondary side post-regulation and zero voltage switching. The forward converter is characterized in that a primary side electric power loop adopts a single-transistor or twintransistor structure which is driven by a primary side drive circuit at a fixed work period ratio so as to enable the voltage waveform of a secondary side electric power winding to have a fixed pulse width; a secondary side electric power loop utilizes a controllable switch, and the controllable switch can adopts a magnetic amplifier or an N-channel MOS transistor so as to shield the frontal edge of the voltage waveform of the secondary side electric power winding; and the output voltage is stabilized, and the zero voltage switching of a primary side switch transistor is realized.

Description

The forward converter of voltage stabilizing and zero voltage switching behind the tool secondary side
[technical field]
The relevant a kind of forward converter of the present invention, the forward converter of voltage stabilizing and zero voltage switching behind particularly a kind of tool secondary side, its zero voltage switching that can reach the primary side switching transistor is to reduce switch cost and to improve conversion efficiency.
[background technology]
Fig. 1 and Fig. 2 show the single-transistor and the body frame structure of pair transistor forward converter of voltage stabilizing (primary side preregulation) and self-driven synchronous rectifier before the previous tool primary side respectively, wherein the secondary side error amplifying circuit detect output voltage sample and with a reference voltage comparison to produce an error signal; This error signal is optically coupled to primary side control circuit and converts the pulse wave width modulation of primary side switching transistor to that (pulse width modulation, PWM) drive signal is with regulated output voltage.
If previous forward converter operates in continuous conduction mode, then output voltage V OutCan be represented as
V out = N s N p D pri V in
, V wherein InBe input voltage; D PriVariable-operation period ratio (variable primary duty ratio) for the primary side switching transistor; N pBe the number of turns of primary side electric power winding, and N sThe number of turns for secondary side electric power winding.Work as V OutBe lower than its set point, increase D PriMake V OutRise; Work as V OutBe higher than its set point, reduce D PnMake V OutDescend.Therefore, modulation D PriCan stablize V OutThough voltage stabilizing is very simple before the primary side, it can't be reached the zero voltage switching (zero voltageswitching) of primary side switching transistor and suffer from higher switch cost.
Transformer T among Fig. 1 1With the transformer T among Fig. 2 2All comprise primary side electric power winding N p, it is connected to the primary side power circuit; Secondary side electric power winding N s, it is connected to the secondary side power circuit, and secondary side drives winding N d, it produces the drive signal of self-driven synchronous rectifier.Because of the N among Fig. 1 pT itself can't reset 1Iron core and N among Fig. 2 pT itself can reset 2Iron core, the single-transistor structure needs primary side replacement winding N rAnd double transistor structure does not need primary side replacement winding N rGenerally speaking, N rThe number of turns can less than, be equal to or greater than N pThe number of turns so that the maximum drain-source voltage of the primary side switching transistor in the single-transistor structure respectively greater than, be equal to or less than 2V InThe maximum drain-source voltage of the primary side switching transistor in the double transistor structure equals V InStain on the winding indicates the positive voltage terminal of reference polarity and the homopolar end of winding voltage.There is the stain end to be defined as with reference to the anode of (non-reality) polarity and not have the stain end and is defined as negative terminal with reference to (non-reality) polarity.If actual polarity is identical with reference polarity, then winding voltage is for just.If actual polarity is opposite with reference polarity, then winding voltage is for negative.Get magnetizing current to set up the interlinkage flux the iron circuit because of real transformer must leak from external circuit, this electromagnetic conversion can be modeled as magnetizing inductance L m(non-external) and primary side electric power winding N pIn parallel.The excitatory of transformer core magnetic circuit represented in the increase of magnetizing current and the demagnetization of transformer core magnetic circuit is represented in minimizing magnetizing current.
Primary side power circuit among Fig. 1 comprises Input voltage terminal V i, input reference voltage end V Ri, input filter capacitor C i, primary side replacement winding N r, replacement diode D 1, magnetizing inductance L m(non-external) and primary side electric power winding N pParallel connection, and switching transistor Q 1, it is a N channel metal-oxide half field effect transistor and has a grid, a drain electrode, one source pole and a leakage-source capacitance C 1(comprising parasitic capacitance and external capacitor), wherein C iAnode and negative terminal be connected to V respectively iWith V RiN rNo stain end with have the stain end to be connected to V respectively iWith D 1Negative electrode; D 1Anode be connected to V RiN pHave stain end and no stain end be connected to V respectively iWith Q 1Drain electrode; Q 1Source electrode be connected to V RiQ 1Grid be connected to primary side pulse wave width modulation drive circuit; L mWith C 1Can form a series connection resonant circuit.
Primary side power circuit among Fig. 2 comprises Input voltage terminal V i, input reference voltage end V Ri, input filter capacitor C i, the first replacement diode D 1, the second replacement diode D 2, the first switching transistor Q 1, second switch transistor Q 2, and magnetizing inductance L m(non-external) and primary side electric power winding N pParallel connection, wherein Q 1With Q 2Be all a N channel metal-oxide half field effect transistor and have a grid, a drain electrode and an one source pole; Q 1With Q 2Leakage-source capacitance (comprising parasitic capacitance and external capacitor) be respectively C 1With C 2C iAnode and negative terminal be connected to V respectively iWith V RiD 1Negative electrode and anode be connected to Q respectively 1Source electrode and V RiD 2Negative electrode and anode be connected to V respectively iWith Q 2Drain electrode; Q 1Drain electrode be connected to V iN pHave stain end and no stain end be connected to Q respectively 1Source electrode and Q 2Drain electrode; Q 2Source electrode be connected to V RiQ 1With Q 2Grid all be connected to primary side pulse wave width modulation drive circuit; L m, C 1With C 2Can form a series connection resonant circuit.
Secondary side power circuit among Fig. 1 and Fig. 2 all comprises secondary side and drives winding N d, secondary side electric power winding N s, synchronous rectifier SR forward f, flywheel synchronous rectifier SR w, resistance R forward 1, grid-source resistance R forward 2, flywheel grid-source resistance R 3, flywheel resistance R 4, output energy storage inductor L o, output filter capacitor C o, output voltage terminal V o, and output reference voltage end V Ro, SR wherein fWith SR wBe all a N channel metal-oxide half field effect transistor, it has a grid, a drain electrode and an one source pole; N dHave stain end and no stain end be connected to R respectively 1First end and R 4First end; R 1Second end and R 4Second end be connected to SR respectively fGrid and SR wGrid; R 2First end and second end be connected to SR respectively fGrid and source electrode; R 3First end and second end be connected to SR respectively wGrid and source electrode; N sHave stain end and no stain end be connected to SR respectively wDrain electrode and SR fDrain electrode; SR fWith SR wSource electrode all be connected to V RoL oFirst end and second end be connected to SR respectively wDrain electrode and V oC oAnode and negative terminal be connected to V respectively oWith V RoThe energy storage of inductor iron core magnetic circuit is represented in the increase of output energy storage inductor electric current and the energy of releasing of inductor iron core magnetic circuit is represented in the minimizing of exporting the energy storage inductor electric current.
Because of the operating principle of single-transistor structure is similar to the operating principle of double transistor structure, this paper only illustrates the operating principle of double transistor structure.Key waveforms in the switching cycle in Fig. 3 displayed map 2, wherein
Figure B2009101612019D00031
Be Q 1With Q 2Grid-source voltage (with reference to different source potential);
Figure B2009101612019D00032
Be Q 1With Q 2Drain-source voltage (with reference to different source potential);
Figure B2009101612019D00033
Be L mVoltage;
Figure B2009101612019D00034
Be L mElectric current; With Be respectively SR fWith SR wGrid-source voltage (with reference to the identical sources electrode potential);
Figure B2009101612019D00043
Be L oElectric current; V InBe input voltage; V OutBe output voltage; I OutBe output current, and Be the number of turns ratio of primary side to secondary side electric power winding.
t 0≤ t＜t 1During in, Open Q 1With Q 2Channel;
Figure B2009101612019D00046
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D00047
L mBe subjected to V InStrangulation and
Figure B2009101612019D00048
Via Q 2Channel, C iWith Q 1Channel make L mExcitatory; With a positive slope
Figure B2009101612019D000410
Increase linearly; N dInduced voltage make
Figure B2009101612019D000411
And
Figure B2009101612019D000412
SR fChannel open and SR wChannel off;
Figure B2009101612019D000413
Via C o, SR fChannel and N sMake L oEnergy storage;
Figure B2009101612019D000414
With a positive slope
Figure B2009101612019D000415
Increase linearly.
t 1≤ t＜t 2During in, Close Q 1With Q 2Channel; D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D000418
Figure B2009101612019D000419
Via C 2, C iWith C 1Make L mExcitatory; N dInduced voltage make
Figure B2009101612019D000420
And
Figure B2009101612019D000421
SR fChannel open and SR wChannel off;
Figure B2009101612019D000422
Via C o, SR fChannel and N sMake L oEnergy storage; C 1With C 2Reflected output current
Figure B2009101612019D000423
Charging;
Figure B2009101612019D000424
With a positive slope
Figure B2009101612019D000425
Increase linearly.
t 2≤ t＜t 3During in,
Figure B2009101612019D000426
Close Q 1With Q 2Channel;
Figure B2009101612019D000427
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D000428
Figure B2009101612019D000429
Via C 2, C iWith C 1Make L mDemagnetization; N dInduced voltage make And
Figure B2009101612019D000431
SR fChannel off and SR wChannel open;
Figure B2009101612019D000432
Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D000433
With a negative slope
Figure B2009101612019D000434
Reduce linearly; Because of N pThe areflexia output current is so it can be regarded as an open circuit; L m, C 1With C 2Forming a series connection resonant circuit makes
Figure B2009101612019D000435
Rise and
Figure B2009101612019D000436
Descend slightly.
t 3≤ t＜t 4During in,
Figure B2009101612019D00051
Close Q 1With Q 2Channel; D 1With D 2All be subjected to partially suitable and conducting;
Figure B2009101612019D00053
L mBe subjected to-V InReed system and
Figure B2009101612019D00054
Via D 2, C iWith D 1Make L mDemagnetization;
Figure B2009101612019D00055
With a negative slope Reduce linearly; N dInduced voltage make
Figure B2009101612019D00057
And SR fChannel off and SR wChannel open;
Figure B2009101612019D00059
Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D000510
With a negative slope
Figure B2009101612019D000511
Reduce linearly.
t 4≤ t＜t 5During in, Close Q 1With Q 2Channel; D 1With D 2All be subjected to contrary partially and end; L mDemagnetization fully;
Figure B2009101612019D000515
N dInduced voltage make
Figure B2009101612019D000516
And SR fChannel off and SR wChannel open;
Figure B2009101612019D000518
Via C oWith SR wChannel make L oReleasing can; With a negative slope
Figure B2009101612019D000520
Reduce linearly; Because of N pThe areflexia output current is so it can be regarded as an open circuit; L m, C 1With C 2Forming a series connection resonant circuit makes
Figure B2009101612019D000521
Descend and Rise slightly.
t 5≤ t＜t 0' during in, Close Q 1With Q 2Channel;
Figure B2009101612019D000524
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D000525
L mDemagnetization fully;
Figure B2009101612019D000526
N dInduced voltage make
Figure B2009101612019D000527
And SR fWith SR wChannel all close; Continuous outputting inductance electric current
Figure B2009101612019D000529
Force SR fWith SR wAll conductings of body diode;
Figure B2009101612019D000530
Via C oWith (1) SR fBody diode and N s(2) SR wBody diode make L oReleasing can; With a negative slope Reduce linearly; Because of SR fWith SR wAll conductings of body diode,
Figure B2009101612019D000533
By reed built in 0 and
Figure B2009101612019D000534
Be clamped at
Figure B2009101612019D000535
Cause
Figure B2009101612019D000536
Be a higher positive voltage and a Q 1With Q 2All at t=t 0' unlatching once again makes The forward converter of voltage stabilizing can't be reached the zero voltage switching of primary side switching transistor and suffer from higher switch cost before the tool primary side of prior art.
[summary of the invention]
For addressing the above problem, the invention provides the forward converter of voltage stabilizing and zero voltage switching behind a kind of tool secondary side, wherein the primary side power circuit can be but is not limited to single-transistor or double transistor structure, and only the primary side switching transistor is driven by the primary side drive circuit so that the voltage waveform of secondary side electric power winding has a fixing pulse bandwidth with a steady job period ratio; The secondary side power circuit utilizes a gate-controlled switch, and it can be but is not limited to a magnetic amplifier or a N channel metal-oxide half field effect transistor, with the leading edge of the voltage waveform that covers secondary side electric power winding; Regulated output voltage, and reach the zero voltage switching of primary side switching transistor.
The secondary side power circuit comprises secondary side and drives winding, secondary side electric power winding, forward synchronous rectifier, flywheel synchronous rectifier, gate-controlled switch, forward resistance, forward grid-source resistance, flywheel grid-source resistance (nonessential), flywheel resistance (nonessential), output energy storage inductor, output filter capacitor, output voltage terminal, and output reference voltage end, wherein this forward synchronous rectifier and this flywheel synchronous rectifier be all a N channel metal-oxide half field effect transistor, it has a grid, a drain electrode and an one source pole; This gate-controlled switch can be but is not limited to a magnetic amplifier or a N channel metal-oxide half field effect transistor, and it has a control end, one first channel end and a second channel end; Have the stain end and the no stain end of this secondary side electric power winding are connected to the first channel end and this forward drain electrode of synchronous rectifier of this gate-controlled switch respectively; The second channel end of this gate-controlled switch is connected to the drain electrode of this flywheel synchronous rectifier; This forward the source electrode of synchronous rectifier and this flywheel synchronous rectifier all be connected to this output reference voltage end; First end of this output energy storage inductor and second end are connected to drain electrode and this output voltage terminal of this flywheel synchronous rectifier respectively; The anode of this output filter capacitor and negative terminal are connected to this output voltage terminal and this output reference voltage end respectively.
This forward synchronous rectifier be subjected to this secondary side to drive winding to drive; This gate-controlled switch is driven by the secondary side pulse wave width modulation control circuit, and this flywheel synchronous rectifier can be driven by secondary side pulse wave width modulation control circuit or this secondary side driving winding.If this flywheel synchronous rectifier is driven by the secondary side pulse wave width modulation control circuit, then have the stain end and the no stain end of this secondary side driving winding are connected to this forward first end and this output reference voltage end of resistance respectively; This forward second end of resistance be connected to this forward grid of synchronous rectifier; Forward first end and second end of grid-source resistance are connected to this forward grid and source electrode of synchronous rectifier respectively for these.Drive if this flywheel synchronous rectifier is subjected to this secondary side to drive winding, then this secondary side have stain end and no stain end of driving winding is connected to this forward first end of resistance and first end of this flywheel resistance respectively; This forward second end of second end of resistance and this flywheel resistance be connected to this forward grid of synchronous rectifier and grid of this flywheel synchronous rectifier respectively; Forward first end and second end of grid-source resistance are connected to this forward grid and source electrode of synchronous rectifier respectively for these; First end of this flywheel grid-source resistance and second end are connected to the grid and the source electrode of this flywheel synchronous rectifier respectively.
Above-mentioned and other characteristic of the present invention and advantage will be well understood to more via following detailed description about preferred embodiment and correspondence pattern.
[description of drawings]
Fig. 1 and Fig. 2 show the single-transistor of prior art and the body frame structure of pair transistor forward converter respectively.
Key waveforms in the switching cycle in Fig. 3 displayed map 2.
Fig. 4 and Fig. 5 show the body frame structure according to first and second specific embodiment of the technology of the present invention respectively.
Key waveforms in the switching cycle in Fig. 6 displayed map 5.
Fig. 7 and Fig. 8 show the body frame structure according to the 3rd and the 4th specific embodiment of the technology of the present invention respectively.
Key waveforms in the switching cycle in Fig. 9 displayed map 8.
[primary clustering symbol description]
V InInput voltage terminal
V RiThe input reference voltage end
V InInput voltage
V oOutput voltage terminal
V RoThe output reference voltage end
V OutOutput voltage
Q 1, Q 2Switching transistor
Figure B2009101612019D00081
The drain-source voltage of switching transistor
Figure B2009101612019D00082
Grid-the source voltage of switching transistor
Figure B2009101612019D00083
Grid-the source voltage of synchronous rectifier forward
Figure B2009101612019D00084
Grid-the source voltage of flywheel synchronous rectifier
Transistorized grid-the source voltage of gate-controlled switch
Figure B2009101612019D00086
L mElectric current
Figure B2009101612019D00087
L oElectric current
SR wThe flywheel synchronous rectifier
SR fSynchronous rectifier forward
The SW gate-controlled switch
C i, C 1, C 2, C oElectric capacity
L o, L r, L mInductance
N r, N p, N s, N dWinding
D 1, D 2The replacement diode
R 1, R 2, R 3, R 4Resistance
[embodiment]
Fig. 4, Fig. 5, Fig. 7 and Fig. 8 show respectively according to the body frame structure of voltage stabilizing (secondary side post regulation) behind the tool secondary side of the present invention with the first, second, third and the 4th specific embodiment of zero voltage switching (zero voltageswitching), wherein the secondary side error amplifying circuit detect output voltage sample and with a reference voltage comparison to produce an error signal; This error signal feedback to secondary side pulse wave width modulation control circuit and the pulse wave width modulation drive signal that converts the secondary side gate-controlled switch to regulated output voltage.
If
Figure B2009101612019D00091
Be the steady job period ratio (constant primary dutyratio) of primary side switching transistor, then output voltage V OutCan be represented as
V out = N s N p D sec V in
, V wherein InBe input voltage; N pThe number of turns for primary side electric power winding; N sBe the number of turns of secondary side electric power winding, and
Figure B2009101612019D00093
Variable-operation period ratio (variablesecondary duty ratio) for the secondary side gate-controlled switch.(variable leading edgeblanking time) T of variable leading edge blanking time BlankCan be represented as
T blank = ( D pri * - D sec ) T s
, T wherein sBe switching cycle.Work as V OutBe lower than its set point, increase D SecOr reduce T BlankMake V OutRise; Work as V OutBe higher than its set point, reduce D SecOr increase T BlankMake V OutDescend.Therefore, modulation D SecOr T BlankCan stablize V OutIn addition, voltage stabilizing still can be reached the zero voltage switching of primary side switching transistor to reduce switch cost behind the secondary side.
Identical and the primary side power circuit of Fig. 5 and Fig. 8 of the primary side power circuit of Fig. 4 and Fig. 7 and the primary side power circuit of Fig. 1 and the primary side power circuit of Fig. 2 duplicate; Repeat no more, only the primary side switching transistor among Fig. 4, Fig. 5, Fig. 7 and Fig. 8 drives with a steady job period ratio primary side switching transistor among Fig. 1 and Fig. 2 with variable-operation period ratio driving herein.
Secondary side power circuit among Fig. 4, Fig. 5, Fig. 7 and Fig. 8 comprises secondary side and drives winding N d, secondary side electric power winding N s, synchronous rectifier SR forward f, flywheel synchronous rectifier SR w, controllable switch S W, resistance R forward 1, grid-source resistance R forward 2, flywheel grid-source resistance R 3(nonessential), flywheel resistance R 4(nonessential), output energy storage inductor L o, output filter capacitor C o, output voltage terminal V o, and output reference voltage end V Ro, SR wherein fWith SR wBe all a N channel metal-oxide half field effect transistor, it has a grid, a drain electrode and an one source pole; SW can be but is not limited to a magnetic amplifier or a N channel metal-oxide half field effect transistor, and it has a control end, one first channel end and a second channel end; N sHave stain end and no stain end be connected to first channel end and the SR of SW respectively fDrain electrode; The second channel end of SW is connected to SR wDrain electrode; SR fWith SR wSource electrode all be connected to V RoL oFirst end and second end be connected to SR respectively wDrain electrode and V oC oAnode and negative terminal be connected to V respectively oWith V Ro
SR fBe subjected to N dDrive; SW is driven by the secondary side pulse wave width modulation control circuit, and SR wCan be subjected to secondary side pulse wave width modulation control circuit (Fig. 4 and Fig. 5) or N d(Fig. 7 and Fig. 8) drives.If SR wDriven by the secondary side pulse wave width modulation control circuit, then N dHave stain end and no stain end be connected to R respectively 1First end and V RoR 1Second end be connected to SR fGrid; R 2First end and second end be connected to SR respectively fGrid and source electrode.If SR wBe subjected to N dDrive, then N dHave stain end and no stain end be connected to R respectively 1First end and R 4First end; R 1Second end and R 4Second end be connected to SR respectively fGrid and SR wGrid; R 2First end and second end be connected to SR respectively fGrid and source electrode; R 3First end and second end be connected to SR respectively wGrid and source electrode.
For ease of following explanation, this paper makes SW so that N channel metal-oxide half field effect transistor is real, and its control end, the first channel end and second channel end are respectively grid, drain electrode and source electrode.
Key waveforms in the switching cycle in Fig. 6 displayed map 5, wherein SR wDriven by the secondary side pulse wave width modulation control circuit.
t 0≤ t＜t 1During in,
Figure B2009101612019D00101
Open Q 1With Q 2Channel;
Figure B2009101612019D00102
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D00103
L mBe subjected to V InReed system and
Figure B2009101612019D00104
Via Q 2Channel, C iWith Q 1Channel make L mExcitatory;
Figure B2009101612019D00105
With a positive slope
Figure B2009101612019D00106
Increase linearly; N dInduced voltage make SR fChannel open.Provided according to the secondary side pulse wave width modulation control circuit
Figure B2009101612019D00108
With This interval can be divided into three subintervals:
t 0≤ t＜t 01During in, SW closes its channel to cover N sThe leading edge of voltage waveform; SR wOpen its channel to reduce the conducting loss of its body diode; Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D00113
With a negative slope
Figure B2009101612019D00114
Reduce linearly.
t 01≤ t＜t 02During in, SW closes its channel to cover N sThe leading edge of voltage waveform; SR wClose its channel to avoid at t=t 02The time SW and SR wFriendship get over conducting;
Figure B2009101612019D00115
Via C oWith SR wBody diode make L oReleasing can;
Figure B2009101612019D00116
With a negative slope
Figure B2009101612019D00117
Reduce linearly.
t 02≤ t＜t 1During in, SW opens its channel and SR wClose its channel;
Figure B2009101612019D00118
Via C o, SR fChannel, N sMake L with the channel of SW oEnergy storage;
Figure B2009101612019D00119
With a positive slope
Figure B2009101612019D001110
Increase linearly.The variable leading edge blanking time also can be represented as T as can be known by icon Blank=t 02-t 0And modulation t 02But also modulation T BlankWith regulated output voltage V Out
t 1≤ t＜t 2During in,
Figure B2009101612019D001111
Close Q 1With Q 2Channel;
Figure B2009101612019D001112
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D001113
Via C 2, C iWith C 1Make L mExcitatory; N dInduced voltage make
Figure B2009101612019D001115
SR fChannel open; The secondary side pulse wave width modulation control circuit is opened the channel of SW and is closed SR wChannel;
Figure B2009101612019D001116
Via C o, SR fChannel, N sMake L with the channel of SW oEnergy storage; C 1With C 2Reflected output current
Figure B2009101612019D001117
Charging;
Figure B2009101612019D001118
With a positive slope
Figure B2009101612019D001119
Increase linearly.
t 2≤ t＜t 3During in,
Figure B2009101612019D001120
Close Q 1With Q 2Channel;
Figure B2009101612019D001121
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D001122
Figure B2009101612019D001123
Via C 2, C iWith C 1Make L mDemagnetization; N dInduced voltage make
Figure B2009101612019D001124
SR fChannel off; Because of N pThe areflexia output current is so it can be regarded as an open circuit; L m, C 1With C 2Forming a series connection resonant circuit makes
Figure B2009101612019D00121
Rise and
Figure B2009101612019D00122
Descend slightly; The secondary side pulse wave width modulation control circuit is closed the channel of SW and is opened SR wChannel;
Figure B2009101612019D00123
Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D00124
With a negative slope
Figure B2009101612019D00125
Reduce linearly.
t 3≤ t＜t 4During in,
Figure B2009101612019D00126
Close Q 1With Q 2Channel; D 1With D 2All be subjected to partially suitable and conducting;
Figure B2009101612019D00128
L mBe subjected to-V InStrangulation and
Figure B2009101612019D00129
Via D 2, C iWith D 1Make L mDemagnetization;
Figure B2009101612019D001210
With a negative slope
Figure B2009101612019D001211
Reduce linearly; N dInduced voltage make
Figure B2009101612019D001212
SR fChannel off; The secondary side pulse wave width modulation control circuit is closed the channel of SW and is opened SR wChannel;
Figure B2009101612019D001213
Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D001214
With a negative slope
Figure B2009101612019D001215
Reduce linearly.
t 4≤ t＜t 5During in,
Figure B2009101612019D001216
Close Q 1With Q 2Channel;
Figure B2009101612019D001217
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D001218
L mDemagnetization fully;
Figure B2009101612019D001219
N dInduced voltage make
Figure B2009101612019D001220
SR fChannel off; The secondary side pulse wave width modulation control circuit is closed the channel of SW and is opened SR wChannel;
Figure B2009101612019D001221
Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D001222
With a negative slope
Figure B2009101612019D001223
Reduce linearly; Because of N pThe areflexia output current is so it can be regarded as an open circuit; L m, C 1With C 2Forming a series connection resonant circuit makes
Figure B2009101612019D001224
Descend and
Figure B2009101612019D001225
Rise slightly.
t 5≤ t＜t 0' during in, Close Q 1With Q 2Channel; D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D001228
L mDemagnetization fully;
Figure B2009101612019D001229
N dInduced voltage make
Figure B2009101612019D001230
SR fChannel open; The secondary side pulse wave width modulation control circuit is closed the channel of SW and is opened SR wChannel; Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D001232
With a negative slope
Figure B2009101612019D00131
Reduce linearly; Because of N pThe areflexia output current is so it can be regarded as an open circuit; L m, C 1With C 2Forming a series connection resonant circuit makes
Figure B2009101612019D00132
Descend and Rise slightly.
Cause
Figure B2009101612019D00134
And Q 1With Q 2All at t=t 0' unlatching once again makes
Figure B2009101612019D00135
The zero voltage switching that can reach the primary side switching transistor according to first and second specific embodiment of the present invention is to reduce switch cost.
Key waveforms in the switching cycle in Fig. 9 displayed map 8, wherein SR wBe subjected to N dDrive.
t 0≤ t＜t 1During in,
Figure B2009101612019D00136
Open Q 1With Q 2Channel;
Figure B2009101612019D00137
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D00138
L mBe subjected to V InReed system and
Figure B2009101612019D00139
Via Q 2Channel, C iWith Q 1Channel make L mExcitatory;
Figure B2009101612019D001310
With a positive slope
Figure B2009101612019D001311
Increase linearly; N dInduced voltage make
Figure B2009101612019D001312
And
Figure B2009101612019D001313
SR fChannel open and SR wChannel off.Provided according to the secondary side pulse wave width modulation control circuit
Figure B2009101612019D001314
This interval can be divided into two subintervals:
t 0≤ t＜t 02During in, SW closes its channel to cover N sThe leading edge of voltage waveform;
Figure B2009101612019D001315
Via C oWith SR wBody diode make L oReleasing can;
Figure B2009101612019D001316
With a negative slope
Figure B2009101612019D001317
Reduce linearly.
t 02≤ t＜t 1During in, SW opens its channel;
Figure B2009101612019D001318
Via C o, SR fChannel, N sMake L with the channel of SW oEnergy storage; With a positive slope
Figure B2009101612019D001320
Increase linearly.
t 1≤ t＜t 2During in,
Figure B2009101612019D001321
Close Q 1With Q 2Channel;
Figure B2009101612019D001322
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D001323
Via C 2, C iWith C 1Make L mExcitatory; N dInduced voltage make
Figure B2009101612019D001325
And
Figure B2009101612019D001326
SR fChannel open and SR wChannel off; The secondary side pulse wave width modulation control circuit is opened the channel of SW;
Figure B2009101612019D001327
Via C o, SR fChannel, N sMake L with the channel of SW oEnergy storage; C 1With C 2Reflected output current
Figure B2009101612019D001328
Charging;
Figure B2009101612019D001329
With a positive slope
Figure B2009101612019D00141
Increase linearly.
t 2≤ t＜t 3During in,
Figure B2009101612019D00142
Close Q 1With Q 2Channel;
Figure B2009101612019D00143
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D00144
Figure B2009101612019D00145
Via C 2, C iWith C 1Make L mDemagnetization; N dInduced voltage make And
Figure B2009101612019D00147
SR fChannel off and SR wChannel open; The secondary side pulse wave width modulation control circuit is closed the channel of SW;
Figure B2009101612019D00148
Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D00149
With a negative slope
Figure B2009101612019D001410
Reduce linearly; Because of N pThe areflexia output current is so it can be regarded as an open circuit; L m, C 1With C 2Forming a series connection resonant circuit makes
Figure B2009101612019D001411
Rise and
Figure B2009101612019D001412
Descend slightly.
t 3≤ t＜t 4During in, Close Q 1With Q 2Channel;
Figure B2009101612019D001414
D 1With D 2All be subjected to partially suitable and conducting;
Figure B2009101612019D001415
L mBe subjected to-V InStrangulation and
Figure B2009101612019D001416
Via D 2, C iWith D 1Make L mDemagnetization;
Figure B2009101612019D001417
With a negative slope
Figure B2009101612019D001418
Reduce linearly; N dInduced voltage make
Figure B2009101612019D001419
And
Figure B2009101612019D001420
SR fChannel off and SR wChannel open; The secondary side pulse wave width modulation control circuit is closed the channel of SW;
Figure B2009101612019D001421
Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D001422
With a negative slope
Figure B2009101612019D001423
Reduce linearly.
t 4≤ t＜t 5During in,
Figure B2009101612019D001424
Close Q 1With Q 2Channel;
Figure B2009101612019D001425
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D001426
L mDemagnetization fully;
Figure B2009101612019D001427
N dInduced voltage make
Figure B2009101612019D001428
And
Figure B2009101612019D001429
SR fChannel off and SR fChannel open; The secondary side pulse wave width modulation control circuit is closed the channel of SW;
Figure B2009101612019D001430
Via C oWith SR wChannel make L oReleasing can;
Figure B2009101612019D001431
With a negative slope
Figure B2009101612019D001432
Reduce linearly; Because of N pThe areflexia output current is so it can be regarded as an open circuit; L m, C 1With C 2Forming a series connection resonant circuit makes
Figure B2009101612019D00151
Descend and Rise slightly.
t 5≤ t＜t 0' during in,
Figure B2009101612019D00153
Close Q 1With Q 2Channel;
Figure B2009101612019D00154
D 1With D 2All be subjected to contrary partially and end;
Figure B2009101612019D00155
L mDemagnetization fully;
Figure B2009101612019D00156
N dInduced voltage make
Figure B2009101612019D00157
And
Figure B2009101612019D00158
SR fChannel open and SR wChannel off; The secondary side pulse wave width modulation control circuit is closed the channel of SW;
Figure B2009101612019D00159
Via C oWith SR wBody diode make L oReleasing can;
Figure B2009101612019D001510
With a negative slope
Figure B2009101612019D001511
Reduce linearly; Because of N pThe areflexia output current is so it can be regarded as an open circuit; L m, C 1With C 2Forming a series connection resonant circuit makes
Figure B2009101612019D001512
Descend and
Figure B2009101612019D001513
Rise slightly.
Cause
Figure B2009101612019D001514
And Q 1With Q 2All at t=t 0' unlatching once again makes
Figure B2009101612019D001515
The zero voltage switching that also can reach the primary side switching transistor according to the of the present invention the 3rd and the 4th specific embodiment is to reduce switch cost.
As shown in the above description, there is causality between the zero voltage switching of voltage stabilizing and primary side switching transistor behind the secondary side.The secondary side gate-controlled switch is in t 5≤ t＜t 0' during keep and close so that N pAreflexia output current and form an open circuit, and L m, C 1With C 2Sustainable resonance makes
Figure B2009101612019D001516
Drop to 0.
What should be specified is the primary side electric power winding N among Fig. 4 and Fig. 7 pThe position can with primary side switching transistor Q 1Location swap, Q only 1Drive signal must be with reference to Q 1Source electrode.In addition, voltage stabilizing modulation before the primary side
Figure B2009101612019D001517
To stablize V OutSo that different output voltages can't be directly corresponding to the variable-operation period ratio of identical primary side switching transistor; And voltage stabilizing modulation D behind the secondary side SecTo stablize V OutSo that different output voltages can be directly corresponding to the variable-operation period ratio of different secondary side gate-controlled switch.Therefore, behind the secondary side voltage stabilizing than primary side before voltage stabilizing be easy to stable organize output voltage.
Above-described embodiment only is explanation technological thought of the present invention and characteristics, its purpose makes the personage who has the knack of this skill can understand content of the present invention and is implementing according to this, when can't with qualification claim of the present invention, promptly the equalization of doing according to disclosed spirit generally changes or modifies, and must be encompassed in the claim of the present invention.

Claims (10)

1. the forward converter of voltage stabilizing and zero voltage switching comprises behind the tool secondary side:
One primary side power circuit, it comprises an Input voltage terminal and an input reference voltage end, and in order to receive an input voltage, an input filter capacitor is connected between this Input voltage terminal and this input reference voltage end;
One secondary side power circuit, it comprises an output voltage terminal and an output reference voltage end, in order to export an output voltage; And
One transducer, it is connected between this primary side power circuit and those secondary side power circuits; Wherein
This transducer comprises a first side winding and connects this primary side power circuit, and this first side winding comprises an anode and a negative terminal; One secondary side electric power winding connects this secondary side power circuit, and this secondary side electric power winding comprises an anode and a negative terminal, respectively to anode and negative terminal that should first side winding; And one secondary side drive winding, it comprises an anode and a negative terminal, respectively to anode and negative terminal that should first side winding;
This secondary side power circuit comprise one forward synchronous rectification transistor comprise a drain electrode, one source pole and a grid; One flywheel synchronous rectification transistor comprises a drain electrode, one source pole and a grid; One gate-controlled switch comprises one first end, one second end and a control end; One energy storage inductor; An and filter capacitor; Wherein this forward the drain electrode of synchronous rectification transistor connect the negative terminal of this secondary side electric power winding, this forward the source electrode of synchronous rectification transistor be connected this output reference voltage end with the source electrode of this flywheel synchronous rectification transistor, the drain electrode of this flywheel synchronous rectification transistor connects second end of this gate-controlled switch, and first end of this gate-controlled switch connects the anode of this secondary side electric power winding; This forward synchronous rectification transistor grid via one forward resistance connect this drives winding through secondary side anode, this forward is connected a grid source resistance forward between grid and the source electrode of synchronous rectification transistor, this connects this output reference voltage end through negative terminal that secondary side drives winding; The grid of this flywheel synchronous rectification transistor is connected a secondary side pulse wave width modulation control circuit with the control end of this gate-controlled switch; This energy storage inductor is connected between the drain electrode and this output voltage terminal of this flywheel synchronous rectification transistor; This filter capacitor is connected between this output voltage terminal and this output reference voltage end.
2. the forward converter of voltage stabilizing and zero voltage switching behind the tool secondary side according to claim 1, it is characterized in that, this primary side power circuit is a single-transistor switching circuit, and this single-transistor switching circuit comprises a switching transistor, and it comprises a drain electrode, one source pole and a grid; And a reset circuit, it comprises a replacement winding and a replacement diode; Wherein
The anode of this first side winding connects this Input voltage terminal; The negative terminal of this first side winding connects the drain electrode of this switching transistor; The source electrode of this switching transistor connects this input reference voltage end; The grid of this switching transistor connects side drive circuit one one times; The anode of this replacement diode connects this input reference voltage end; The negative electrode of this replacement diode connects the anode of this replacement winding; The negative terminal of this replacement winding connects this Input voltage terminal.
3. the forward converter of voltage stabilizing and zero voltage switching behind the tool secondary side according to claim 1, it is characterized in that, this primary side power circuit is a single-transistor switching circuit, and this single-transistor switching circuit comprises a switching transistor, and it comprises a drain electrode, one source pole and a grid; And a reset circuit, it comprises a replacement winding and a replacement diode; Wherein
The negative terminal of this first side winding connects this input reference voltage end; The anode of this first side winding connects the source electrode of this switching transistor; The drain electrode of this switching transistor connects this Input voltage terminal; The grid of this switching transistor connects side drive circuit one one times; The anode of this replacement diode connects this input reference voltage end, and the negative electrode of this replacement diode connects the anode of this replacement winding, and the negative terminal of this replacement winding connects this Input voltage terminal.
4. the forward converter of voltage stabilizing and zero voltage switching behind the tool secondary side according to claim 1, it is characterized in that, this primary side power circuit is a pair of transistor switching circuit, and this pair transistor switching circuit comprises one first switching transistor, and it comprises a drain electrode, one source pole and a grid; One second switch transistor, it comprises a drain electrode, one source pole and a grid; One first replacement diode; And one second replacement diode; Wherein
The drain electrode of this first switching transistor connects this Input voltage terminal; The source electrode of this first switching transistor connects the anode of this first side winding; The negative terminal of this first side winding connects this second switch transistor drain; The transistorized source electrode of this second switch connects this input reference voltage end; This first switching transistor is connected side drive circuit one one times with the transistorized grid of this second switch; The anode of this first replacement diode connects this input reference voltage end; The negative electrode of this first replacement diode connects the anode of this first side winding; The anode of this second replacement diode connects the negative terminal of this first side winding; The negative electrode of this second replacement diode connects this Input voltage terminal.
5. the forward converter of voltage stabilizing and zero voltage switching is characterized in that behind the tool secondary side according to claim 1, and this gate-controlled switch is a N channel MOS field-effect transistor or a magnetic amplifier.
6. the forward converter of voltage stabilizing and zero voltage switching comprises behind the tool secondary side:
One primary side power circuit, it comprises an Input voltage terminal and an input reference voltage end, and in order to receive an input voltage, an input filter capacitor is connected between this Input voltage terminal and this input reference voltage end;
One secondary side power circuit, it comprises an output voltage terminal and an output reference voltage end, in order to export an output voltage; And
One transducer, it is connected between this primary side power circuit and those secondary side power circuits; Wherein
This transducer comprises a first side winding and connects this primary side power circuit, and this first side winding comprises an anode and a negative terminal; One secondary side electric power winding connects this secondary side power circuit, and this secondary side electric power winding comprises an anode and a negative terminal, respectively to anode and negative terminal that should first side winding; And one secondary side drive winding, it comprises an anode and a negative terminal, respectively to anode and negative terminal that should first side winding;
This secondary side power circuit comprise one forward synchronous rectification transistor comprise a drain electrode, one source pole and a grid; One flywheel synchronous rectification transistor comprises a drain electrode, one source pole and a grid; One gate-controlled switch comprises one first end, one second end and a control end; One energy storage inductor; An and filter capacitor; Wherein
This forward the drain electrode of synchronous rectification transistor connect the negative terminal of this secondary side electric power winding, this forward the source electrode of synchronous rectification transistor be connected this output reference voltage end with the source electrode of this flywheel synchronous rectification transistor, the drain electrode of this flywheel synchronous rectification transistor connects second end of this gate-controlled switch, and first end of this gate-controlled switch connects the anode of this secondary side electric power winding; This forward synchronous rectification transistor grid via one forward resistance connect this and drive the anode of winding through secondary side, this forward is connected a grid source resistance forward between grid and the source electrode of synchronous rectification transistor; The grid of this flywheel synchronous rectification transistor connects this via a flywheel resistance and drives the negative terminal of winding through secondary side, is connected a flywheel grid source resistance between the grid of this flywheel synchronous rectification transistor and source electrode; The control end of this gate-controlled switch connects a secondary side pulse wave width modulation control circuit; This energy storage inductor is connected between the drain electrode and this output voltage terminal of this flywheel synchronous rectification transistor; This filter capacitor is connected between this output voltage terminal and this output reference voltage end.
7. the forward converter of voltage stabilizing and zero voltage switching behind the tool secondary side according to claim 6, it is characterized in that, this primary side power circuit is a single-transistor switching circuit, and this single-transistor switching circuit comprises a switching transistor, and it comprises a drain electrode, one source pole and a grid; And a reset circuit, it comprises a replacement winding and a replacement diode; Wherein
The anode of this first side winding connects this Input voltage terminal; The negative terminal of this first side winding connects the drain electrode of this switching transistor; The source electrode of this switching transistor connects this input reference voltage end; The grid of this switching transistor connects the primary side drive circuit; The anode of this replacement diode connects this input reference voltage end; The negative electrode of this replacement diode connects the anode of this replacement winding; The negative terminal of this replacement winding connects this Input voltage terminal.
8. the forward converter of voltage stabilizing and zero voltage switching behind the tool secondary side according to claim 6, it is characterized in that, this primary side power circuit is a single-transistor switching circuit, and this single-transistor switching circuit comprises a switching transistor, and it comprises a drain electrode, one source pole and a grid; And a reset circuit, it comprises a replacement winding and a replacement diode; Wherein
The negative terminal of this first side winding connects this input reference voltage end; The anode of this first side winding connects the source electrode of this switching transistor; The drain electrode of this switching transistor connects this Input voltage terminal; The grid of this switching transistor connects side drive circuit one one times; The anode of this replacement diode connects this input reference voltage end, and the negative electrode of this replacement diode connects the anode of this replacement winding, and the negative terminal of this replacement winding connects this Input voltage terminal.
9. the forward converter of voltage stabilizing and zero voltage switching behind the tool secondary side according to claim 6, it is characterized in that, this primary side power circuit is a pair of transistor switching circuit, and this pair transistor switching circuit comprises one first switching transistor, and it comprises a drain electrode, one source pole and a grid; One second switch transistor, it comprises a drain electrode, one source pole and a grid; One first replacement diode; And one second replacement diode; Wherein
The drain electrode of this first switching transistor connects this Input voltage terminal; The source electrode of this first switching transistor connects the anode of this first side winding; The negative terminal of this first side winding connects this second switch transistor drain; The transistorized source electrode of this second switch connects this input reference voltage end; This first switching transistor is connected side drive circuit one one times with the transistorized grid of this second switch; The anode of this first replacement diode connects this input reference voltage end; The negative electrode of this first replacement diode connects the anode of this first side winding; The anode of this second replacement diode connects the negative terminal of this first side winding; The negative electrode of this second replacement diode connects this Input voltage terminal.
10. the forward converter of voltage stabilizing and zero voltage switching is characterized in that behind the tool secondary side according to claim 6, and this gate-controlled switch is a N channel MOS field-effect transistor or a magnetic amplifier.
CN2009101612019A 2009-07-17 2009-07-17 Forward converter with functions of secondary side post-regulation and zero voltage switching Expired - Fee Related CN101958648B (en)

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US6980441B2 (en) * 2003-07-28 2005-12-27 Astec International Limited Circuit and method for controlling a synchronous rectifier in a power converter

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