CN101581947A - Voltage stabilizer - Google Patents
Voltage stabilizer Download PDFInfo
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- CN101581947A CN101581947A CN 200810099458 CN200810099458A CN101581947A CN 101581947 A CN101581947 A CN 101581947A CN 200810099458 CN200810099458 CN 200810099458 CN 200810099458 A CN200810099458 A CN 200810099458A CN 101581947 A CN101581947 A CN 101581947A
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- voltage stabilizer
- voltage
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- following stage
- phase margin
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Abstract
The invention provides a voltage regulator which is used for regulating input voltage into stable output voltage and comprises a following stage and a driving stage, wherein the driving stage receives the output of the following stage and outputs regulated voltage for load, and a dynamic compensating device of phase margins, which improves the phase margins with the increase of the load current of the load is connected between the following stage and the driving stage.
Description
Technical field
The present invention relates to a kind of voltage stabilizer, relate in particular to a kind of low pressure drop (Low Drop-out) voltage stabilizer.
Background technology
Nearly all electronic circuit all needs a stable voltage source that maintains in the certain tolerance scope, powers to guarantee its normal operation to specific features.This burning voltage is provided by voltage stabilizer.
Common voltage stabilizer mainly comprises: differential amplifier stage, driving stage (for example with P-FET, PNP as driving tube) and be used for output voltage is fed back to certain proportion the feedback circuit of differential amplifier stage.In existing voltage stabilizer technology, in order to keep the stability of output voltage, between differential amplifier stage and driving stage, add following stage usually, thereby moving to high frequency direction, the limit that makes differential amplifier stage introduce improves phase margin.But can introduce new limit behind the adding following stage, improvement has a negative impact to phase margin for it.So, can in said structure, add Miller RC compensation system and carry out the phase margin improvement, but do like this, often the influence owing to electric capacity causes voltage stabilizer to have the relatively poor shortcoming of transient response.
Therefore, it is effective to wish to seek a kind of phase margin improvement, the voltage stabilizer that has comparatively outstanding transient response simultaneously.
Summary of the invention
One aspect of the present invention provides a kind of voltage stabilizer, and it is used for input voltage is adjusted into stable output voltage, comprising: following stage; With the driving stage of accepting to export and load is exported burning voltage from described following stage; Between described following stage and described driving stage, be connected with the phase margin dynamic compensating device that increases phase margin with the load current of described load.
Another aspect of the present invention provides a kind of double mode working equipment, it comprises LDO Regulator and high power consumption voltage stabilizer, described double mode working equipment can switch between the high power consumption mode of the low-power consumption mode of LDO Regulator work and the work of high power consumption voltage stabilizer, it is characterized in that the voltage stabilizer that described LDO Regulator the invention described above provides on the one hand.
The present invention adds the load of a phase margin dynamic compensating device as following stage use increasing on the basis of method that following stage carries out phase compensation, and this phase margin dynamic compensating device increases along with the load current of load and improves phase margin.Thereby can be when the outstanding phase place of acquisition be improved effect, the counter productive of the reduction transient response that the Miller capacitance in the elimination use Miller RC compensation method is brought.
Description of drawings
Fig. 1 is the block diagram that the available technology adopting following stage carries out the voltage stabilizer of phase compensation;
Fig. 2 is a block diagram of implementing voltage stabilizer of the present invention;
Fig. 3 is the synoptic diagram of gain-frequency curve that shows the entire system of prior art voltage stabilizer as shown in Figure 1;
Fig. 4 is the physical circuit figure that realizes an embodiment of voltage stabilizer of the present invention;
Fig. 5 is the synoptic diagram of the gain-frequency curve of expression pressurizer system integral body;
Fig. 6 is the synoptic diagram of the phase place-frequency curve of expression following stage;
Fig. 7 is illustrated under the condition that load current is 5mA, does not add the voltage stabilizer of phase margin dynamic compensating device and the synoptic diagram of the gain-phase place-frequency curve of the entire system of the voltage stabilizer that adds the phase margin dynamic compensating device;
Fig. 8 is that contrast is used Miller RC phase compensating method and used the synoptic diagram of the system of phase compensating method of the present invention to the load current transient response;
Fig. 9 is an application example of voltage stabilizer of the present invention.
Embodiment
Usually, the method that utilize to increase following stage carry out phase compensation voltage stabilizer structured flowchart as shown in Figure 1, the differential amplifier stage 10, following stage 20, the driving stage 30 that comprise mutual cascade, and the feedback circuit 40 that feeds back to the differential amplifier stage input end from the output of driving stage 30.Voltage stabilizer is by regulating input voltage, at last by the stable output voltage of driving stage 30 outputs.Following stage and differential amplifier stage 10 cascades, it is used for the system phase nargin of whole voltage stabilizer is improved.Wherein, if can skipping over feedback circuit 40, the output voltage of driving stage 30 directly feeds back to differential amplifier stage 10.
Improvement of the present invention is, adds the load of phase margin dynamic compensating device 50 as following stage 20 after following stage 20, as shown in Figure 2.How the concrete structure of this phase margin dynamic compensating device 50 1 embodiment improves and will be elaborated in conjunction with Fig. 4 and Fig. 5 below the phase margin of system with concrete.
Fig. 3 shows the gain-frequency curve of the entire system of prior art voltage stabilizer as shown in Figure 1.Curve R wherein, S, T represents that respectively load current is 10 μ A, 1mA, each gain-frequency curve of system during 5mA. limit Pole1 is the limit that driving stage 30 is introduced, from above-mentioned curve as seen, along with load current increases, Pole1 moves to Pole1 ' and Pole1 to the direction that frequency increases gradually ".Pole2 is the limit that differential amplifier stage 10 is introduced, and Pole3 is the limit that following stage 20 is introduced, from above-mentioned curve as seen, and the frequency f of Pole2
Pole2Frequency f with Pole3
Pole3Can not change along with the variation of load current.Because the frequency of Pole3 is near the unit gain frequency place, so the pressurizer system phase margin is subjected to the frequency influence of the Pole3 of following stage 20 introducings.The above analysis, in the prior art pressurizer system, along with load current increases, the driving stage limit moves to the frequency augment direction, the influence that differential amplifier stage pole frequency and following stage pole frequency are not increased by load current promptly keeps size constant, and unit gain frequency moves to the frequency augment direction, causes system phase nargin to reduce like this, and then causes system's instability.
Improvement thinking of the present invention is to be connected to phase margin dynamic compensating device 50 between following stage 20 and driving stage 30, and this phase margin dynamic compensating device 50 can make the pole frequency f of following stage limit Pole3
Pole3Along with the increase of the load current of driving stage 30 and move (increase), that is to say the frequency f that makes following stage limit Pole3 to high frequency direction
Pole3Consistent with the variation tendency of unit gain frequency UGF, promptly, when moving after unit gain frequency UGF takes place the following stage pole frequency also with after move, suppress the trend that system phase nargin reduces along with the load current increase under the situation that does not add phase margin dynamic compensating device 50 like this, thereby improved the stability of system.
The pole frequency f of following stage limit Pole3 wherein
Pole3Increase with the increase of load current and to be based on following stage pole frequency computing formula
(R
OEquivalent parallel resistance between expression following stage and driving stage, C
OShunt capacitance between expression following stage and driving stage) obtains, as long as make parameters R in this formula
O, C
OOne of at least can reduce with the increase of load current, just can make f
Pole3Increase with load current increases.Among the embodiment below, the present invention considers from the convenience that realizes, has adopted to make R
OThe mode that reduces along with the load current increase.
Fig. 4 is the physical circuit figure of low dropout voltage regulator that realizes conduct one embodiment of voltage stabilizer of the present invention, below it is specifically described.Differential amplifier stage 10 among Fig. 1 is passed through two PMOS field effect transistor P1 and P2 and three NMOS field effect transistor N1, N2, N3 and is realized; Following stage 20 can be by realizing as the PMOS field effect transistor P3 of constant current source with as the source following stage that the PMOS field effect transistor P4 that follows pipe is formed; Driving stage 30 realizes that by a PMOS field effect transistor P6 such stabilivolt is also referred to as the low pressure drop stabilivolt; Phase margin dynamic compensating device 50 among Fig. 2 is realized by PMOS field effect transistor P5, in the present embodiment, it is as the load of following stage 20, promptly, the source electrode of PMOS field effect transistor P5 connects the source electrode (the forward voltage VDD among Fig. 4 just) of driving tube P6, play the effect of diode forward end, PMOS field effect transistor P5 grid and the line of the drain electrode output terminal that is connected the grid of driving tube P6 and following stage 20 on, play the effect of the negative end that is equivalent to diode.By such connection, the actual effect of playing the diode forward utilization of P5.Feedback circuit 40 is composed in series by Rtop and Rbot, in order to the proportional back that dwindles of output voltage is taken out and to be fed back to differential amplifier stage 10.Certainly in changing example, can not take out feedback voltage, and can directly output voltage be fed back to differential amplifier stage 10 by Rtop and Rbot series circuit.About differential amplifier stage 10, following stage 20, the concrete structure that driving stage 30 and feedback circuit 40 are realized, those skilled in the art can make rational variation to realization at different levels.For example differential amplifier stage 10 can be realized by bipolar transistor, and the also available emitter following level of following stage 20 is replaced; Except the form of the cited source following stage of present embodiment, can adopt other forms of following stage, for example replace the constant current source in the present embodiment and follow the source following stage that pipe is formed together by resistance; Driving stage 30 can be realized by the PNP transistor in addition, to substitute the PMOS field effect transistor in the present embodiment; The also available NMOS of PMOS pipe among Fig. 4 substitutes, and the also available PMOS of NMOS pipe substitutes, and for example, is exactly like this during the output negative voltage.The replacement that all these those skilled in the art can make according to technology general knowledge and change neither disengaging protection scope of the present invention.
Below in conjunction with Fig. 5 how the PMOS field effect transistor P5 as phase margin dynamic compensating device 50 being improved phase margin describes.Fig. 5 is the gain-frequency curve chart of system of the present invention, and it is 10 μ A that Fig. 5 enumerates load current, three kinds of situations that 1mA, 5mA increase gradually, and under these three kinds of situations, the gain-frequency curve of system is respectively by curve A, and curve B and curve C are represented.As shown in Figure 4, increase along with load current increases the voltage that is added between PMOS driving tube P6 source electrode and the grid, thereby the voltage that is applied on the pmos type field effect transistor P5 also increases.Along with voltage increases the characteristic that reduces, the forward resistance R of the pmos type field effect transistor P5 that connects as diode diminishes with the increase that its two ends apply voltage according to the equivalent output resistance of diode forward utilization.In addition, because the output resistance of the input resistance of driving stage and following stage is very big with respect to the resistance R of pmos type field effect transistor P5, especially under the situation of large load current, they can be ignored the influence of the frequency of calculating limit Pole3, thereby with R
OBe approximately resistance R, that is to say of the resistance value R decision of the pull-up resistor of following stage by the PMOS field effect transistor of the diode use of using as forward.
As shown in Figure 4, when the voltage stabilizer load current gradually when 10 μ A increase to 1mA and increase to 5mA again, be added in the source electrode of PMOS driving tube P6 and the voltage between grid and increase gradually, therefore, the voltage that is added in PMOS field effect transistor P5 also becomes big.According to the forward resistance of diode along with voltage increases the characteristic that reduces, substitution limit Pole3 frequency computation part formula
Calculate the frequency of the limit Pole3 of following stage introducing, the frequency f of visible limit Pole3
Pole3To increase along with the diminishing of resistance R of pmos type field effect transistor P5, and that is to say, and increase to 5mA along with the load current of voltage stabilizer increases to 1mA from 10 μ A, limit Pole3 moves to high frequency direction, and referring to Fig. 5, the frequency of limit Pole3 is from f
Pole3Increase to f
Pole3 'Increase to f again
Pole3 "
Fig. 6 is that expression is with the synoptic diagram of phase margin dynamic compensating device 50 as the phase place-frequency curve of the following stage of load.Along with pole frequency from f
Pole3Increase to f
Pole3 'Increase to f again
Pole3 ", the phase change that limit Pole3 introduces presents the trend of lifting shown in curve D among Fig. 6 arrives curve F again to curve E variation.
Fig. 7 is to be under the condition of 5mA at load current, does not add the voltage stabilizer (voltage stabilizer as shown in Figure 1) of phase margin dynamic compensating device 50 and adds the synoptic diagram of gain-phase place-frequency curve of the voltage stabilizer (voltage stabilizer as shown in Figure 2) of phase margin dynamic compensating device 50.Constant at load current, under the prerequisite for 5mA, 50 pairs of driving stage limits of phase margin dynamic compensating device and differential amplifier stage pole frequency do not exert an influence, therefore the voltage stabilizer and the gain-frequency curve of the entire system of the voltage stabilizer that adds phase margin dynamic compensating device 50 such as the curve H among Fig. 7 that do not add phase margin dynamic compensating device 50, shown in the G, curve H, G overlapped before running into the following stage limit.In the voltage stabilizer that does not add phase margin dynamic compensating device 50, the frequency of following stage limit can not increase along with the increase of load current, is equivalent to it and is positioned at roughly as shown in Figure 5 the frequency f when load current is 10 μ A all the time
Pole3And for the pressurizer system that has added phase margin dynamic compensating device 50, as mentioned before, the pole frequency of following stage can increase along with the increase of load current, also be poor greater than two frequencies that do not add phase margin dynamic compensating device 50 of the difference of the pole frequency of following stage and system zero gain frequency UGF, its corresponding phase place-frequency curve is also raised with respect to load current phase place-frequency curve hour along with the increase of load current, therefore do not use the voltage stabilizer and the phase place-frequency curve of the source following stage of the voltage stabilizer that has used phase margin dynamic compensating device 50 such as the curve I among Fig. 7 of phase margin dynamic compensating device 50, shown in the J, curve J has raised with respect to curve I.Curve M among Fig. 7, phase place-frequency curve that N represents not add the voltage stabilizer of phase margin dynamic compensating device 50 respectively and adds the voltage stabilizer total system of phase margin dynamic compensating device 50.Because the Overlay of the phase curve of following stage, make that comparing phase place at unit gain frequency UGF place with curve M in curve N obtains lifting (see among Fig. 7 shown in the PM1 and PM2), i.e. system phase nargin improve (increase).
In addition, those skilled in the art will find apparent that variable resistor device, can also use nmos type field effect transistor or simple diode except the PMOS field effect transistor and realize as phase margin dynamic compensating device 50.Except the variable resistor device, those skilled in the art can consider that also utilizing the variable capacitance device to wait realizes this phase margin dynamic compensating device 50 under the prerequisite that does not break away from inventive concept.
The present invention compares phase margin improvement method Miller RC phase compensation commonly used, owing to do not need to use electric capacity, can effectively improve the transient response of voltage stabilizer load current.The transient response of load current can be used: the load current transient changing causes the size of the voltage difference delta Vtr of system's output voltage to be weighed.
ΔVtr＝Ioutmax＊Δt/Cout+ΔVesr
Wherein, Δ t=1/Bwcl+ Δ Vpgate*Cpgate/Iss,
Ioutmax: maximum output current
Cout: external output capacitance
Δ Vesr: the voltage difference on the equivalent series resistance ESR of output capacitance:
Bwcl: closed-loop bandwidth
Δ Vpgate: the driving tube grid voltage is poor
Cpgate: the driving tube grid is equivalent capacity over the ground
Iss: the driving tube grid is discharge current over the ground.
Under the situation that other each parameters equate, if save Miller capacitance C in the Miller RC phase compensating method, the Cpgate value will reduce greatly, and Δ t reduces, and reduces thereby Δ Vtr is also corresponding.Fig. 8 shows and uses Miller RC phase compensating method and use the comparison diagram of the system of phase compensating method of the present invention to the load current transient response.By the simulation of simulation software, obtain comparing result as shown in Figure 8, curve X represents to use the transient response curve of Miller RC phase compensation scheme among the figure, and Y represents to use the transient response curve of phase margin dynamic compensation scheme acquisition of the present invention.As shown in Figure 8, in the scheme that adopts Miller RC phase compensation, when load current switched between minimum current and maximum current, the transient state fluctuating range was in the scope of 0.02 times of output voltage ideal value.In adopting the scheme of phase margin dynamic compensation of the present invention, when load current changed, the transient state fluctuating range of output voltage curve Y was 0.01 times of output voltage ideal value to the maximum less than half of curve X.Can find out that therefrom the load current transient response of using phase margin dynamic compensation method of the present invention than using Miller RC phase compensating method is good.
In addition, the present invention also can implement together in conjunction with Miller RC phase compensating method, thus can be in wideer scope the phase margin and the transient response of regulating system.At this moment, by reducing Miller capacitance C, the compensation that can obtain phase margin is better, but the poor slightly system of transient response.
Application of the present invention
Because voltage stabilizer of the present invention is better to the load current transient response, the voltage stabilizer that 50 pairs of phase margins of employing phase margin dynamic compensating device of the present invention are compensated is as LDO Regulator, be used in the double mode voltage stabilizer that can between low-power consumption mode and high power consumption mode, switch, can improve the switching noise that double mode voltage stabilizer switches between two kinds of patterns, especially improve the switching noise from the high power consumption mode to the low-power consumption mode.
Fig. 9 has provided the connection block diagram that voltage stabilizer of the present invention is applied to an example in the double mode working equipment.As shown in Figure 9, low-power consumption differential amplifier stage 10, following stage 20, phase margin dynamic compensating device 50, driving stage 30 and feedback circuit 40 have constituted the aforesaid voltage stabilizer of this instructions.Its as LDO Regulator with control by Enable Pin EN1 and EN2 separately with another high power consumption voltage stabilizer, thereby the output voltage that can select double mode working equipment is by still high energy consumption voltage stabilizer output of LDO Regulator output.Because it is good that voltage stabilizer of the present invention has transient response, therefore can improve switching noise well from the high energy consumption mode switch to low-power mode.Wherein, Enable Pin EN1 and EN2 can realize by hardware or software approach.In addition, the high energy consumption voltage stabilizer can use disclosed voltage stabilizer to realize equally, with the further switching noise that improves.
Claims (8)
1. a voltage stabilizer is used for input voltage is adjusted into stable output voltage, comprising:
Following stage; With
The driving stage of burning voltage is exported and load is exported in acceptance from described following stage;
It is characterized in that the load current that is connected with described load increases the phase margin dynamic compensating device that improves phase margin between described following stage and described driving stage.
2. voltage stabilizer as claimed in claim 1 is characterized in that, described phase margin dynamic compensating device is made of the variable resistor device, and the resistance of this variable resistor device reduces along with the increase that adds voltage thereon.
3. voltage stabilizer as claimed in claim 2 is characterized in that, described variable resistor device is made of diode, and this diode forward utilization is connected the output terminal of described following stage.
4. voltage stabilizer as claimed in claim 3 is characterized in that described diode is made of the metal-oxide-semiconductor field effect transistor of diode method of attachment.
5. voltage stabilizer as claimed in claim 4 is characterized in that described driving stage is made of metal-oxide-semiconductor field effect transistor, and the metal-oxide-semiconductor field effect transistor forward utilization of described diode method of attachment is connected between the source electrode and grid of the metal-oxide-semiconductor field effect transistor that constitutes driving stage.
6. as each described voltage stabilizer of claim 1-5, it is characterized in that described following stage is the source following stage.
7. voltage stabilizer as claimed in claim 6 is characterized in that, described source following stage constitutes by following pipe as constant current source and PMOS.
8. double mode working equipment, it comprises LDO Regulator and high power consumption voltage stabilizer, described double mode working equipment can switch between the high power consumption mode of the low-power consumption mode of LDO Regulator work and the work of high power consumption voltage stabilizer, it is characterized in that described LDO Regulator is a voltage stabilizer as claimed in claim 1.
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 200810099458 CN101581947B (en) | 2008-05-16 | 2008-05-16 | Voltage stabilizer |
| JP2009119207A JP5343698B2 (en) | 2008-05-16 | 2009-05-15 | Voltage regulator |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 200810099458 CN101581947B (en) | 2008-05-16 | 2008-05-16 | Voltage stabilizer |
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| CN101581947A true CN101581947A (en) | 2009-11-18 |
| CN101581947B CN101581947B (en) | 2013-01-23 |
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| CN 200810099458 Expired - Fee Related CN101581947B (en) | 2008-05-16 | 2008-05-16 | Voltage stabilizer |
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Cited By (7)
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| CN102566637A (en) * | 2010-12-31 | 2012-07-11 | 株式会社理光 | Low-voltage-difference linear voltage stabilizer |
| CN102650893A (en) * | 2011-02-25 | 2012-08-29 | 株式会社理光 | Low dropout linear regulator |
| CN102880217A (en) * | 2012-10-12 | 2013-01-16 | 西安启芯微电子有限公司 | Stabilized power circuit used in high-voltage direct current-direct current (DC-DC) converter |
| CN104635826A (en) * | 2014-12-12 | 2015-05-20 | 长沙景嘉微电子股份有限公司 | Simple linear power supply circuit |
| CN105406612A (en) * | 2015-12-17 | 2016-03-16 | 北方工业大学 | Radio frequency energy supply device for low-power-consumption nodes at tail end of Internet of things |
| CN113835463A (en) * | 2021-09-30 | 2021-12-24 | 西北工业大学太仓长三角研究院 | Small-area fast transient response all-on-chip integrated LDO (low dropout regulator) circuit |
| US11550349B2 (en) | 2018-10-31 | 2023-01-10 | Rohm Co., Ltd. | Linear power supply circuit |
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| JP2014164702A (en) * | 2013-02-27 | 2014-09-08 | Seiko Instruments Inc | Voltage regulator |
| CN105917285B (en) | 2013-09-26 | 2018-09-14 | 英特尔公司 | The low difference voltage regulator integrated with digital power gate driver |
| CN109905016B (en) * | 2019-03-22 | 2023-09-29 | 中国电子科技集团公司第十四研究所 | High-voltage power PMOSFET drive circuit |
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| JP2000242344A (en) * | 1999-02-25 | 2000-09-08 | Oki Micro Design Co Ltd | Voltage variation correcting circuit |
| JP2000284843A (en) * | 1999-03-31 | 2000-10-13 | Fuji Electric Co Ltd | Series regulator power source circuit |
| US6343222B1 (en) * | 1999-04-14 | 2002-01-29 | Ericsson Inc. | Dual mode power controllers and related method and radiotelephones |
| JP3750787B2 (en) * | 2000-01-14 | 2006-03-01 | 富士電機デバイステクノロジー株式会社 | Series regulator power circuit |
| US6246221B1 (en) * | 2000-09-20 | 2001-06-12 | Texas Instruments Incorporated | PMOS low drop-out voltage regulator using non-inverting variable gain stage |
| JP3643043B2 (en) * | 2001-03-08 | 2005-04-27 | 株式会社リコー | Voltage regulator and mobile phone device having the voltage regulator |
| US6518737B1 (en) * | 2001-09-28 | 2003-02-11 | Catalyst Semiconductor, Inc. | Low dropout voltage regulator with non-miller frequency compensation |
| US7088082B2 (en) * | 2003-12-16 | 2006-08-08 | Quick Logic Corporation | Regulator with variable capacitor for stability compensation |
| JP4421909B2 (en) * | 2004-01-28 | 2010-02-24 | セイコーインスツル株式会社 | Voltage regulator |
| US6975099B2 (en) * | 2004-02-27 | 2005-12-13 | Texas Instruments Incorporated | Efficient frequency compensation for linear voltage regulators |
| US7064531B1 (en) * | 2005-03-31 | 2006-06-20 | Micrel, Inc. | PWM buck regulator with LDO standby mode |
| JP2006318327A (en) * | 2005-05-16 | 2006-11-24 | Fuji Electric Device Technology Co Ltd | Differential amplification circuit and series regulator |
| JP2007280025A (en) * | 2006-04-06 | 2007-10-25 | Seiko Epson Corp | Power supply device |
| JP4814747B2 (en) * | 2006-08-30 | 2011-11-16 | セイコーＮｐｃ株式会社 | Constant voltage circuit |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN102566637A (en) * | 2010-12-31 | 2012-07-11 | 株式会社理光 | Low-voltage-difference linear voltage stabilizer |
| CN102566637B (en) * | 2010-12-31 | 2014-05-07 | 株式会社理光 | Low-voltage-difference linear voltage stabilizer and method for adjusting low-voltage-difference linear voltage stabilizer |
| CN102650893A (en) * | 2011-02-25 | 2012-08-29 | 株式会社理光 | Low dropout linear regulator |
| CN102650893B (en) * | 2011-02-25 | 2014-09-17 | 株式会社理光 | Low dropout linear regulator |
| CN102880217A (en) * | 2012-10-12 | 2013-01-16 | 西安启芯微电子有限公司 | Stabilized power circuit used in high-voltage direct current-direct current (DC-DC) converter |
| CN104635826A (en) * | 2014-12-12 | 2015-05-20 | 长沙景嘉微电子股份有限公司 | Simple linear power supply circuit |
| CN105406612A (en) * | 2015-12-17 | 2016-03-16 | 北方工业大学 | Radio frequency energy supply device for low-power-consumption nodes at tail end of Internet of things |
| US11550349B2 (en) | 2018-10-31 | 2023-01-10 | Rohm Co., Ltd. | Linear power supply circuit |
| CN113835463A (en) * | 2021-09-30 | 2021-12-24 | 西北工业大学太仓长三角研究院 | Small-area fast transient response all-on-chip integrated LDO (low dropout regulator) circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| JP2009277233A (en) | 2009-11-26 |
| CN101581947B (en) | 2013-01-23 |
| JP5343698B2 (en) | 2013-11-13 |
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