CN101371621B - A protection device for electronic converters, related converter and method - Google Patents
A protection device for electronic converters, related converter and method Download PDFInfo
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- CN101371621B CN101371621B CN2007800028128A CN200780002812A CN101371621B CN 101371621 B CN101371621 B CN 101371621B CN 2007800028128 A CN2007800028128 A CN 2007800028128A CN 200780002812 A CN200780002812 A CN 200780002812A CN 101371621 B CN101371621 B CN 101371621B
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/288—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps without preheating electrodes, e.g. for high-intensity discharge lamps, high-pressure mercury or sodium lamps or low-pressure sodium lamps
- H05B41/292—Arrangements for protecting lamps or circuits against abnormal operating conditions
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B39/00—Circuit arrangements or apparatus for operating incandescent light sources
- H05B39/04—Controlling
- H05B39/041—Controlling the light-intensity of the source
- H05B39/044—Controlling the light-intensity of the source continuously
- H05B39/045—Controlling the light-intensity of the source continuously with high-frequency bridge converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
- H02H7/00—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions
- H02H7/10—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers
- H02H7/12—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers
- H02H7/122—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for inverters, i.e. dc/ac converters
- H02H7/1227—Emergency protective circuit arrangements specially adapted for specific types of electric machines or apparatus or for sectionalised protection of cable or line systems, and effecting automatic switching in the event of an undesired change from normal working conditions for converters; for rectifiers for static converters or rectifiers for inverters, i.e. dc/ac converters responsive to abnormalities in the output circuit, e.g. short circuit
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
- H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
- H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
- Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10S323/00—Electricity: power supply or regulation systems
- Y10S323/907—Temperature compensation of semiconductor
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
- Emergency Protection Circuit Devices (AREA)
- Control Of Electric Motors In General (AREA)
- Rectifiers (AREA)
- Magnetic Heads (AREA)
- Measuring Fluid Pressure (AREA)
Abstract
A device for protecting an electronic converter, e.g. for halogen lamps, includes a comparator (10) having an output (Vo) as well as non-inverting (14) and inverting (12) inputs for receiving a first input signal (Vi(P)) indicative of the load applied to the converter and a second input signal (Vref(T DEG )) indicative of the temperature of the converter. The comparator (10) is in a non-inverting Schmitt-trigger configuration having an input-output characteristic with hysteresis. Consequently, the output (Vo) is switched from a first value (Vol) to a second value (Voh) to switch off the electronic converter as the first input signal (Vi(P)) exceeds a first threshold value (VT1). The output (Vo) is switched back from the second value (Voh) to the first value (Vol) to restart the electronic converter when the first input signal (Vi(P)) falls below a second threshold value (VT2). The second threshold value (VT2) is lower than the first threshold value (VT1), and both threshold values (VT1, VT2) are a function of the signal (Vref(T DEG)) indicative of the temperature of the converter. The converter is thus protected against both current overloads and temperature overloads.
Description
Technical field
The present invention relates to be used for the protection equipment of electronic commutator, and be pay special attention to its with the AC/DC converter incorporates that is used for Halogen lamp LED can applicable situation under and exploitation.
Background technology
Observe codes and standards fully in order to make electronic commutator; Fail safe must be held; Even under the situation of abnormal work situation, promptly be higher than under the situation of the maximum temperature that normal value that output applies or ambient temperature be higher than designer's suggestion at current loading.In addition, desirable characteristic is that in case this abnormal work situation stops, transducer resets automatically.
For the common topology apparatus that electronic commutator adopted is a kind of self-oscillation half-bridge that directly provides from the output voltage of bridge rectifier.For example, under the situation of the supply voltage of 50Hz, will be the pulse voltage of 100Hz from the output voltage of bridge rectifier.Locate each zero point at service voltage, and self-oscillation stops, and circuit element must periodically rekindle this half-bridge.This typically obtains by lighting capacitor; Capacitor is recharged the thresholding that reaches diac up to its voltage, and consequent discharge causes self-oscillation (again) beginning in this half-bridge.
Great majority overload/the overtemperature protection devices of up to now such transducer being advised comprise low impedance path, and this low impedance path makes lighting of half-bridge become impossible with to light capacitor parallelly connected.This solution has only when transducer is supplied to AC voltage and could fully work.Under the situation of DC supply voltage, to have only when transducer during for the first time by energy supply, it is essential that the lighting of half-bridge is only; Afterwards, can remain on any level under the thresholding of diac through the voltage of lighting capacitor.Like this, the work to transducer does not influence low impedance path through the existence parallelly connected with lighting capacitor.This means, if transducer is supplied to dc voltage, then protective device irregular working and can not guarantee desired fail safe.
Therefore, many overload/overtemperature protection devices of prior art comprise two differences and independently the level.Preceding level comprise heat sensitive element (for example, thermistor such as PTC or NTC) and (only) as by heat sensitive element testing to temperature function and act on and light capacitor.After level be exclusively used in protection to current overload, and on the specified point of some signal of telecommunication of circuit, detect and can represent overload conditions but temperature independent again signal usually; And after level affact at last and light on the capacitor.
Summary of the invention
The purpose of this invention is to provide a kind of improved overload/overtemperature protection device, the shortcoming and defect that it has avoided the front to describe.
The object of the invention is realized through the method for the equipment that is used to protect electronic commutator that provides according to embodiments of the invention, the electronic commutator that comprises this equipment and protection electronic commutator.
Be used to protect the equipment of electronic commutator to comprise comparator according to an embodiment of the invention with output and in-phase input end and inverting input; In-phase input end and inverting input are used to receive first input signal and second input signal that receives expression transducer temperature that expression is applied to the load of transducer; Comparator has the input-output characteristic of hysteresis under the homophase schmitt-trigger configuration; Output is transformed to second value to turn-off electronic commutator from first value when first input signal surpasses first threshold thus; And drop to second threshold value when following when first input signal; Output is returned first value to restart electronic commutator from second value by conversion, and second threshold value is lower than first threshold, and the first threshold and second threshold value all are the functions of second input signal; Wherein schmitt-trigger configuration is included in the output of comparator and the feedback path between the in-phase input end, and this feedback path comprises being connected in parallel of constant pressure source and diode.
Electronic commutator comprises that mentioned above being used to protect the equipment of electronic commutator according to an embodiment of the invention.
Protect the method for electronic commutator may further comprise the steps according to an embodiment of the invention:
-generation expression is applied to first signal of the load of transducer;
The secondary signal of-generation expression transducer temperature;
-comparator with output and in-phase input end and inverting input is provided; In-phase input end and inverting input are used to receive first input signal and second input signal; Comparator has the input-output characteristic of hysteresis under the homophase schmitt-trigger configuration; Output is transformed to second value from first value when first input signal surpasses first threshold thus, and drops to second threshold value when following when first input signal, and output is returned first value from second value by conversion; Second threshold value is lower than first threshold; And the first threshold and second threshold value all are the functions of second input signal, and wherein schmitt-trigger configuration is included in the output of comparator and the feedback path between the in-phase input end, and this feedback path comprises being connected in parallel of constant pressure source and diode;
-first signal and the secondary signal of expression transducer temperature that expression are applied to the load of transducer is applied to comparator, as first input signal and second input signal;
-when the output of comparator reaches first value and second value respectively, electronic commutator is turn-offed and restart.
Therefore, a kind of preferred implementation of device described here is AC/AC or DC/AC transducer, and it provides a kind of be suitable for the supplying with high frequency of 12V Halogen lamp LED, the low-voltage signal of insulation.
Active parts in the device preventing electronic-controlled installation described here (ECG) when power overload is applied to its output port (for example; Because wrong installation) reach undesirable high temperature, perhaps ambient temperature reaches than is used for the higher level of maximum recommended levels of work.
Device described here is also worked when transducer is supplied to dc voltage, and the complete scheme that prevents to transship with overtemperature further is provided.
Device described here has combined to relate to the information of the load at temperature and converter output end place, and generates the signal that is suitable for driver unit (for example stopping the vibration of half-bridge); This is being not always the case under situation of AC power supplies and under the situation of DC power supply.
Description of drawings
Now only with reference to the diagram in the accompanying drawing the present invention is described through example, wherein:
Fig. 1 is the block diagram of basic principle that constitutes the basis of device described herein;
Fig. 2 is the sketch map of the device work shown in Fig. 1;
Fig. 3 is the The general frame that includes the transducer of device described herein;
Figure 4 and 5 show some details of a possible embodiment of device described herein.
Embodiment
The block diagram of Fig. 1 shows device described herein " core ".This device consists essentially of the comparator 10 of use under the homophase schmitt-trigger configuration.
In this exemplary cases, inverting input 12 receives the signal Vref (T °) of the continuous voltage form relevant with temperature.Preferably, Vref (T °) be selected as with temperature rise the signal descends (as below better as described in the signal of generation).
Similarly; Under described exemplary cases; In-phase input end 14 receives the signal Vi (P) (like the signal that produces as described in more detail below) of continuous voltage forms, and this signal indication is in the power and the load of the output (not shown in Fig. 1) of associated converter circuit.
Particularly, the signal Vi (P) relevant with load is applied to the in-phase input end 14 of comparator 10 through resistance R 1.What be connected with the in-phase input end 14 of comparator 10 is another resistance R 2, and this resistance is connected with including with the circuit of the constant pressure source Vb of diode Do parallel connection.The negative pole of the anode of source Vb and diode Do is connected to the output that has output voltage V o of comparator 10.Preferably, through than duplicate supply+/-single-power voltage Vcc mode that Vcc more be prone to obtain is to comparator 10 power supplies.
That kind shown in the chart of Fig. 2 is the bi-level signals that between low level Vol (typically equaling 0.5V) and high level Voh (typically equaling Vcc-1.5V), change from the output voltage V o (ordinate) of comparator 10.Particularly, the curve chart of Fig. 2 shows the input-output characteristic of the function of the signal Vi (P) (abscissa) circuit, that conduct is relevant with load among Fig. 1.For example, can suppose: Vi (P) is that for example (be not must directly) be proportional with the power of the output of associated converter.
The curve chart of Fig. 2 shows typical hysteresis circulation: on a certain upper limit VT1 of Vi (P) (being that power output is too high), output voltage V o arrives high level Voh.Have only when signal Vi (P) is lower than another lower limit VT2 of Vi (P), output voltage V o just turns back to low level Vol, wherein VT2＜VT1.
Output signal Vo can be used to stop the half-bridge of associated converter.Particularly; When (because too high) when reaching high level Voh from the power output of associated converter; Vo (through any known way that need not here to do to describe in detail) stops the work of transducer, and keeps this state (being Vo=Voh) to cause Vi (P) to descend and drop to below the value VT2 up to lacking of output voltage.At that point, the Vo that transducer is in low level Vol restarts.
The appearance of overload can show to the user, advantageously for example impels the mode (unusual condition appears in this expression) of flick of lamp to show through the Vo that reaches high level Voh.
The work of installing shown in Fig. 1 also can receive the domination of the signal Vref relevant with temperature (T °).
In fact, the circuit analysis of installing shown in Fig. 1 shows that the value of VT1 can be represented as:
V wherein
γBe forward voltage, promptly when Vo=Vol makes diode current flow at diode
On voltage.This voltage has the opposite direction at the electric current of the output of comparator 10.
Similarly, the circuit analysis of installing shown in Fig. 1 shows that the value of VT2 can be represented as:
Now, the influence of Vb is obvious, the poor (V because Vb can be conditioned
OH-Vb) very little, prevent that like this VT2 from possibly become negative or too near zero.Explanation is in addition, and generator Vb guarantees: when in circuit, having exemplary voltages, threshold value VT2 will never become negative; Under the situation of that kind, rekindling of transducer will become impossible.
Two formula being announced in the preceding text make following situation become clear: the value of the signal relevant with temperature (being Vref (T °)) is directly depended in " position " of the circulation that lags behind, and " width " of the circulation that lags behind, promptly poor VTH=VT1-VT2=(V
OH-V
OL-Vb-V
γ) * R1/R2, can pass through Vb and V
γBe used for regulating.
Preceding text have been given prominence to some Fundamentals.
At first, because existence and the characteristic of signal Vi (P), the device of just having described is suitable for carrying out overload (that is, overcurrent) defencive function: too high if load becomes, Vi subsequently (P) rises and causes Vo to arrive Voh, thereby has interrupted the work of transducer.
Secondly; Because existence and the characteristic of signal Vref (T °); The device of just having described is suitable for carrying out heat (that is, overtemperature) defencive function: too high if temperature becomes, Vref subsequently (T °) descends and causes Vo to arrive Voh; From and interrupt the work (because VT1＜Vi (P)) of transducer, make transducer because overtemperature and can being turned off.Afterwards, Vi (P) can restart with constant decline sometime and this transducer.If temperature is still very high, then this transducer will only short-term operation before closing once more.
Under arbitrary situation of being considered in the above, the appearance of unusual condition can be conveyed to the user, for example, passes on through passage of scintillation light/flash of light.
In addition, it should be understood that the increase of temperature causes VT1 and VT2 to descend together, make temperature high more, then the value of Vi (P) is just more little, and this will cause Vo to arrive high level Voh.Therefore descend for the rising of the work upper limit of overload protection setting along with temperature; Like this interrelated guaranteed that the temperature of the parts in the equipment will never reach too high value.
Fig. 3 shows protective device possibly use in the framework of transducer of describing hereinbefore; This transducer will offer the light source 26 of the secondary coil that is connected to transformer Tr from the electrical power of power supply 20 (for example, supply voltage) through line filter 22 and half bridge rectifier 24.Source 26 can comprise for example one or more Halogen lamp LED, fluorescent lamp, high flux LED etc.
In that respect, it will be appreciated by those skilled in the art that device described herein is suitable for being used in combination with dc-dc converter based on half-bridge topology.Those skilled in the art also will be appreciated that; Except with the device-dependent details of the protection of being discussed hereinbefore and some specified points of mentioning hereinafter; Therefore the block diagram of Fig. 3 need not provide more detailed description at this substantially corresponding to itself known converter layouts in the prior art.
In brief, the primary coil with transformer Tr of polarization inductance L c drives through half-bridge arrangement, and this half-bridge arrangement comprises:
-two electronic switches (for example MOSFET or BJT) Ta, Tb, each electronic switch have related grid inductance L a, Lb, and
-two capacitor Ca, Cb, each capacitor have related protection diode Da, Db.
Two electronic switch Ta, Tb are alternately switched on and off through the control circuit 38 with related diac 30.Basically, diac 30 is placed between the intermediate point of grid and voltage divider of electronic switch Ta, Tb, and this voltage divider comprises:
-be connected to rectifier 24 output " on " resistance R s, and
-be connected to the D score resistance R d1 on ground, the capacitor Cs that is connected in parallel with resistance R d1 through switch Td2.
Another resistance R d2 is connected to the grid of electronic switch Tb; Resistance R d2 is suitable for being connected to ground through switch Td1.Resistance R ds representes the intrinsic resistance that each active parts (for example MOSFET or BJT) shows at its output basically.
Switch Td1 and Td2 drive through the output voltage V o of comparator 10, and (being shown in dotted line) protection diode D2 preferably is set to: its positive pole is connected to the output voltage V o of comparator 10 and its negative pole is connected to control circuit 38.
Preferably, switch Td1 is driven by voltage Vo through switch off delay circuit (not shown in Fig. 3).This switch off delay circuit can be through being connected to switch Td1 the capacitor of drive end realize.In addition, switch Td1 is through being driven by Vo with the diode parallel resistor.This diode allows the quick connection of Td1, and resistance will keep Td1 connection certain hour with capacitor.This switch off delay circuit is optional, and prevents the parasitic oscillation of half-bridge when closing generation.
In Fig. 3, the diode Do of Fig. 1 and voltage source V b (are expressed as separated components so that outstanding relative V parameter b and V
γImportance) be connected in parallel and represent simply with the form of Zener diode Vz that this Zener diode has the negative pole that is connected to comparator 10.In fact this Zener diode Vz can be regarded as and be equal to being connected in parallel of voltage source V b (wherein Vb is the avalanche voltage of Zener diode) and diode Do, and this diode Do has the V of equaling
γForward voltage.
Circuit permission by parts R s, Cs and diac 30 form locates to light half-bridge at each zero point of service voltage.
There is dc voltage in intermediate point between Ca and Cb, and this dc voltage is superimposed with high frequency (vibration) ripple on it, and the amplitude of this ripple depends on the load that applies in the converter output end place.
This correlation is used to generate the signal Vi (P) relevant with load in order to present the in-phase input end to comparator 10.Relevant sensing apparatus also comprises except comprising the first resistance R a1 parallelly connected with diode Da: the capacitor Cd that is connected to the secondary coil of transformer Tr; Add the network that includes two resistance R a2 and Rb basically, this network comprises the voltage divider that places between capacitor Cd and the ground.
The function of resistance R a1 will be given illustrated in detail in the decline of this specification.
The value of Ra2 and Rb is selected; So that make characteristic frequency fp=1/ (2* π * Cd (Ra2+Rb)) more much lower than the minimum frequency of oscillation that is applied on the half-bridge arrangement; But than by the typical frequencies of the supply voltage of rectification (for example 100Hz-200Hz) height, make the voltage that occurs through Ra2 and Rb only be illustrated in the intermediate point place any ripple magnitude that influences that exist, that do not receive low-frequency power voltage between capacitor Ca and the Cb usually.
The voltage divider that includes resistance R a2 and Rb measures this ripple signal and through resistance R c it is presented to the quasi-peak detector network that comprises the diode Dp that is loaded with RC network.This RC network comprises charging and the capacitor Cp of discharge time constant and being connected in parallel of resistance R d of common qualification detector.
Therefore, the continuous voltage on capacitor Cp is illustrated in the load (in fact, proportional with it) that converter output end (being transformer Tr) place applies.
Place service voltage Vcc and another voltage divider between the ground to comprise two resistance R 3 and R4 to produce the relevant signal Vref (T °) with temperature that rises and descend with temperature, wherein said voltage divider has the NTC parallelly connected with R4 (negative temperature coefficient) resistance (shown in solid line) and/or has the PTC parallelly connected with R3 (positive temperature coefficient) resistance (shown in dotted line).
This specific device is preferably to produce the signal Vref (T °) relevant with temperature at present in the many devices that possibly replace; This signal is as the function of temperature, and these possible alternatives comprise the device that for example is suitable for producing the signal that increases with the temperature rising.
Fixed resistance R3 parallelly connected with NTC and/or PTC resistance and R4 are used to make the thermal voltage/temperature profile linearisation of NTC/PTC resistance and eliminate tolerance.
In the diagrammatic sketch of Fig. 3, shown in broken lines in order to represent that these connections can be only to be used under the situation of the transducer of AC power supplies, working or also under the situation of DC power supply, working and arbitrarily be provided with according to this protection of looking for from the output of comparator 10 to being connected of switch Td1 and Td2.
As represented, the intrinsic resistance that resistance R d2 (and Rd1) expression active parts such as MOSFET or BJT show at its output.As described to the introductory section of this description, if low impedance path is parallel to capacitor Cs, then half-bridge can not be rekindled after the zero point of service voltage, so that transducer will stop.
This also shall not be applied to the situation of DC work, and low impedance path is for example through connecting, and promptly close switch Td1 is formed parallelly connected with base stage and the emitter of " downside " switch Tb.
Preferably; Impedance is low; Make all from diac 30 and/or from the electric current of the inductor Lb resistance R d2 that flows through; So that disadvantageous the rekindling or the fault of half-bridge (for example owing to the continuous operation that under the situation of the disadvantageous driving of MOSFET or BJT Tb, causes half-bridge cause) of avoiding Tb, this exists owing to the overheated danger that causes self-destruction subsequently.
Fig. 4 shows the possible way of realization of switch Td2.This is made up of the MOSFET with high relatively channel resistance basically, also can conduct the peak current of hundreds of mA.Suppose that resistance R d21 connects with MOSFET Td2 being desirable in the restriction of the duration of work (promptly under the situation of Td2 conducting) of Td2 from the peak current of capacitor Cs.
Fig. 5 shows the possible way of realization of switch Td1 when protection equipment also must be worked under the DC of transducer electric power thus supplied.
This comprises having the very MOSFET Td1 of low ohmic channel again, and owing to reason described above, MOSFET Td1 has related diode Dd1.This diode is a Schottky diode, and it is used to avoid: when Td1 was switched on (being conducting), the threshold voltage Vbe that the total voltage on Td1 and Dd1 can become and be higher than Tb made it to stop.Diode Dd1 under any circumstance is useful so that avoid: in the half-bridge normal work period, when the voltage through Lb when negative, can undesirably the flow through body diode of Td1 of electric current.
Resistance R a1 is biasing resistor basically, and this resistance has following effect: after switch Td1 no longer valid, allowing half-bridge to rekindle under the situation of DC power supply.In fact, when the work of half-bridge is interrupted, coupling capacitor Cb discharge, and the lighting no longer can cooperate and quicken its self-oscillation of low side switch Tb with half-bridge.On the contrary, resistance R a1 guarantees that the intermediate point between Ca and Cb keeps polarization (being in positive voltage), makes capacitor Cb always be recharged.
Under the situation of AC power supplies, Ra1 is unnecessary, because under any circumstance between Ca and Cb, all there is pulse voltage.Therefore this voltage always shows certain variation (being dv/dt) in time, some electric charges that this is enough to shift in capacitor C a and Cb, make between the two intermediate point always (positively) polarize.
Therefore, under the situation of not damaging cardinal principle of the present invention, details and embodiment can, even suitably change, and the scope of the present invention that does not break away from accompanying claims and limited with reference to the content only described through example.
Claims (26)
1. equipment that is used to protect electronic commutator; Said equipment comprises the comparator (10) of have output (Vo) and in-phase input end (14) and inverting input (12); Said in-phase input end (14) and said inverting input (12) be used to receive expression be applied to said transducer load first input signal (Vi (P)) with receive second input signal (Vref (T °)) of representing said transducer temperature; Said comparator (10) has the input-output characteristic of hysteresis under the homophase schmitt-trigger configuration; Said output (Vo) is transformed to second value (Voh) to turn-off said electronic commutator from first value (Vol) when said first input signal (Vi (P)) surpasses first threshold (VT1) thus; And drop to second threshold value (VT2) when following when said first input signal (Vi (P)); Said output (Vo) is returned said first value (Vol) to restart said electronic commutator from said second value (Voh) by conversion; Said second threshold value (VT2) is lower than said first threshold (VT1); And said first threshold (VT1) and second threshold value (VT2) all are the functions of said second input signal (Vref (T °)); It is characterized in that said schmitt-trigger configuration is included in the said output (Vo) of said comparator (10) and the feedback path between the said in-phase input end (14), said feedback path comprises being connected in parallel of constant pressure source (Vb) and diode (Do).
2. equipment as claimed in claim 1 is characterized in that, said first input signal (Vi (P)) and said second input signal (Vref (T °)) are applied to the said in-phase input end (14) and the said inverting input (12) of said comparator (10) respectively.
3. according to claim 1 or claim 2 equipment is characterized in that in said feedback path, the negative pole of the anode of said constant pressure source (Vb) and said diode (Do) is the said output (Vo) of said comparator (10).
4. like each described equipment in claim 1 or 2, it is characterized in that said being connected in parallel of said constant pressure source (Vb) and said diode (Do) is made up of Zener diode.
5. according to claim 1 or claim 2 equipment is characterized in that, said equipment comprise voltage divider (R1, R2), in order to said first input signal (Vi (P)) is applied to the respective input (14) of said comparator (10).
6. equipment as claimed in claim 5 is characterized in that, (R1 R2) comprises resistance (R2) to said voltage divider, and said resistance is included in the said output (Vo) and the said feedback path between the said in-phase input end (14) of said comparator (10).
7. according to claim 1 or claim 2 equipment is characterized in that said second input signal (Vref (T °)) descends along with the rising of said transducer temperature.
8. according to claim 1 or claim 2 equipment is characterized in that, said equipment comprises that further (NTC is PTC) to produce said second input signal (Vref (T °)) of the said transducer temperature of expression at least one temperature sensitive element.
9. equipment as claimed in claim 8 is characterized in that, said temperature sensitive element comprises at least one in negative temperature coefficient (NTC) resistance and positive temperature coefficient (PTC) resistance.
10. equipment as claimed in claim 9 is characterized in that, said at least one resistance in said negative temperature coefficient (NTC) resistance and said positive temperature coefficient (PTC) resistance have the fixed resistance parallelly connected with it (R3, R4).
11. equipment as claimed in claim 8 is characterized in that, (NTC, PTC) (R3, one of branch road R4) is associated said temperature sensitive element with voltage divider.
12. equipment as claimed in claim 11 is characterized in that, (R3 R4) is arranged to that (R3, last branch road (R3) R4) and the intermediate point place between the following branch road (R4) produce said second input signal (Vref (T °)) at said voltage divider to said voltage divider.
13. equipment as claimed in claim 12 is characterized in that, said temperature sensitive element is selected from following element:
-be included in the last branch road of said voltage divider positive temperature coefficient (PTC) resistance and
-be included in negative temperature coefficient (NTC) resistance in the following branch road of said voltage divider.
14. equipment according to claim 1 or claim 2 is characterized in that, said equipment comprises ripple sensing circuit (Cd, Ra2; Rb, Rc, Dp; Cp Rd) goes up the ripple that exists with sensing in said load (Tr), is applied to said first input signal (Vi (P)) of the load on the said transducer as expression.
15. equipment as claimed in claim 14, wherein said transducer comprises half-bridge arrangement, on said half-bridge arrangement, is applied with frequency of oscillation, is characterised in that; Said ripple sensing circuit (Cd, Ra2, Rb, Rc; Dp, Cp Rd) comprises resonant circuit (Cd, Ra2; Rb), (characteristic frequency that Rb) has significantly is lower than the frequency of oscillation on the said half-bridge arrangement that is applied in the said transducer to said resonant circuit for Cd, Ra2.
16. equipment as claimed in claim 14 is characterized in that, said ripple sensing circuit (Cd, Ra2; Rb, Rc, Dp; Cp Rd) comprises quasi-peak detector network (Dp, Rd; Cp), derive continuous basically signal in order to the said ripple from said load (Tr), said continuous basically signal is applied to said first input signal (Vi (P)) of the load on the said transducer corresponding to expression.
17. equipment according to claim 1 or claim 2; It is characterized in that; Said equipment comprises at least one switch (Td1; Td2), said at least one switch by the control of the said output (Vo) of said comparator (10) in order to (Td1 interrupts the work of said transducer when Td2) closed at said at least one switch.
18. equipment as claimed in claim 17 is characterized in that, be provided with to light capacitor (Cs) lighting said transducer, and said at least one switch (Td2) is connected to provide and the said parallelly connected low impedance path (Rd1) of capacitor (Cs) of lighting.
19. equipment as claimed in claim 18 is characterized in that, said at least one switch (Td2) has the protective resistance (Rd21) of being connected, when said at least one electronic switch (Td2) is closed, to limit from the said peak current of lighting capacitor (Cs).
20. equipment as claimed in claim 17; Wherein said transducer comprises that high side electronic switch (Ta) and the downside electronic switch (Tb) alternately connected with to said load (Tr) present; Said high side and downside electronic switch (Ta; Tb) have corresponding base stage port and emitter port, it is characterized in that, said at least one switch (Td1) is configured between the base stage of said downside electronic switch (Tb) and emitter, produce low impedance path (Rd2).
21. equipment as claimed in claim 20; It is characterized in that; Said at least one switch (Td1) has protection diode (Dd1) relatedly, is higher than the threshold voltage of said downside electronic switch (Tb) to prevent that voltage on said at least one switch (Td1) and said protection diode (Dd1) from becoming.
22. equipment as claimed in claim 21 is characterized in that, said protection diode (Dd1) is a Schottky diode.
23. equipment according to claim 1 or claim 2; Wherein said load (Tr) be disposed in and have two commutation condensers (Ca, in rectifier bridge configuration Cb), said two commutation condenser (Ca; Cb) between it, has the intermediate point that is connected to said load (Tr); It is characterized in that said equipment comprises and said rectifier device (Ca, biasing resistor (Ra1) of one (Ca) parallel connection in Cb).
24. one kind comprises the electronic commutator according to each described equipment in the claim 1 to 23.
25. a method of protecting electronic commutator, this method may further comprise the steps:
-generate (Cd, Ra2, Rb, Rc, Dp, Cp, Rd) expression is applied to first signal (Vi (P)) of the load of said transducer;
-generation (PTC, NTC, R3, Ra) secondary signal (Vref (T °)) of the said transducer temperature of expression;
-comparator (10) of have output (Vo) and in-phase input end (14) and inverting input (12) is provided; In-phase input end (14) and inverting input (12) are used to receive first input signal (Vi (P)) and second input signal (Vref (T °)); Said comparator (10) has the input-output characteristic of hysteresis under the homophase schmitt-trigger configuration; Said output (Vo) is transformed to second value (Voh) from first value (Vol) when said first input signal (Vi (P)) surpasses first threshold (VT1) thus; And drop to second threshold value (VT2) when following when said first input signal (Vi (P)); Said output (Vo) is returned said first value (Vol) from said second value (Voh) by conversion; Said second threshold value (VT2) is lower than said first threshold (VT1); And said first threshold (VT1) and second threshold value (VT2) all are the functions of said second input signal (Vref (T °)), and wherein said schmitt-trigger configuration is included in the said output (Vo) of said comparator (10) and the feedback path between the said in-phase input end (14), and said feedback path comprises being connected in parallel of constant pressure source (Vb) and diode (Do);
-expression is applied to said first signal (Vi (P)) of the load of said transducer and representes that the secondary signal (Vref (T °)) of said transducer temperature is applied to said comparator (10), as said first input signal (Vi (P)) and second input signal (Vref (T °));
-when the said output (Vo) of said comparator (10) reaches said first value (Vol) and said second value (Voh) respectively, said electronic commutator is turn-offed and restart.
26. method as claimed in claim 25 is characterized in that, said method comprises the step that generates as said second input signal (Vref (T °)) of the signal that reduces along with the temperature rising of said transducer.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| EP06425032A EP1811816B1 (en) | 2006-01-24 | 2006-01-24 | A protection device for electronic converters, related converter and method |
| EP06425032.7 | 2006-01-24 | ||
| PCT/EP2007/050580 WO2007085580A1 (en) | 2006-01-24 | 2007-01-22 | A protection device for electronic converters, related converter and method |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101371621A CN101371621A (en) | 2009-02-18 |
| CN101371621B true CN101371621B (en) | 2012-07-18 |
Family
ID=36586121
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2007800028128A Expired - Fee Related CN101371621B (en) | 2006-01-24 | 2007-01-22 | A protection device for electronic converters, related converter and method |
Country Status (12)
| Country | Link |
|---|---|
| US (1) | US7965527B2 (en) |
| EP (1) | EP1811816B1 (en) |
| KR (1) | KR101339063B1 (en) |
| CN (1) | CN101371621B (en) |
| AT (1) | ATE405137T1 (en) |
| CA (1) | CA2636442A1 (en) |
| DE (1) | DE602006002238D1 (en) |
| ES (1) | ES2310898T3 (en) |
| PL (1) | PL1811816T3 (en) |
| TW (1) | TW200738066A (en) |
| WO (1) | WO2007085580A1 (en) |
| ZA (1) | ZA200805276B (en) |
Families Citing this family (11)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7834561B2 (en) * | 2008-02-01 | 2010-11-16 | Pacific Tech Microelectronics | Systems and methods for powering a light emitting diode lamp |
| EP2263422B1 (en) * | 2008-04-01 | 2011-11-09 | Osram AG | Electronic converter circuit with improved protection device and corresponding method |
| US20100156598A1 (en) * | 2008-12-18 | 2010-06-24 | Leung Ting Kwok | Rfid medical devices and systems for reading physiological parameter |
| EP2242336A1 (en) * | 2009-04-02 | 2010-10-20 | OSRAM Gesellschaft mit beschränkter Haftung | A converter device for driving light sources, corresponding method and computer program product |
| CN102714910B (en) * | 2009-12-04 | 2014-10-29 | 赤多尼科两合股份有限公司 | Controlling circuit of driver of lighting means |
| EP2481267B1 (en) * | 2009-12-04 | 2014-02-12 | OSRAM GmbH | A method for controlling the operation of an electronic converter, and a corresponding electronic converter, lighting system and software product |
| CN201656433U (en) * | 2010-02-05 | 2010-11-24 | 国基电子（上海）有限公司 | Overheat protection circuit and electronic equipment using overheat protection circuit |
| JP5294335B2 (en) * | 2010-06-18 | 2013-09-18 | 三菱電機株式会社 | Semiconductor device |
| GB201309340D0 (en) * | 2013-05-23 | 2013-07-10 | Led Lighting Consultants Ltd | Improvements relating to power adaptors |
| DE102016114384A1 (en) * | 2016-08-03 | 2018-02-08 | Pilz Gmbh & Co. Kg | Protective device for monitoring a technical system with a pressure-sensitive sensor |
| CN110244111B (en) * | 2019-07-19 | 2021-06-29 | 广东浪潮大数据研究有限公司 | Plate-end power supply near-end and far-end voltage detection device |
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|---|---|---|---|---|
| US5008771A (en) * | 1988-12-13 | 1991-04-16 | Sgs-Thomson Microelectronics S.R.L. | Diagnostic circuit for units providing current control and protection against excessive heat dissipation for semiconductor power devices |
| CN2221267Y (en) * | 1994-09-24 | 1996-02-28 | 陈为匡 | Device for protecting power semiconductor device |
| US6222322B1 (en) * | 1997-09-08 | 2001-04-24 | Q Technology Incorporated | Ballast with lamp abnormal sensor and method therefor |
| US20040070910A1 (en) * | 2002-09-30 | 2004-04-15 | Zenko Gergintschew | Method for driving a semiconductor switch and circuit configuration with a semiconductor switch |
Family Cites Families (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US6856098B2 (en) * | 2001-07-02 | 2005-02-15 | Éclairage Contraste | Converter for converting an AC power main voltage to a voltage suitable for driving a lamp |
| KR100813732B1 (en) * | 2003-05-07 | 2008-03-13 | 도시바 마쯔시따 디스플레이 테크놀로지 컴퍼니, 리미티드 | El display and driving method of el display |
| US7149098B1 (en) * | 2006-01-04 | 2006-12-12 | System General Corporation | Over-power protection apparatus with programmable over-current threshold |
-
2006
- 2006-01-24 PL PL06425032T patent/PL1811816T3/en unknown
- 2006-01-24 DE DE602006002238T patent/DE602006002238D1/en active Active
- 2006-01-24 EP EP06425032A patent/EP1811816B1/en not_active Not-in-force
- 2006-01-24 ES ES06425032T patent/ES2310898T3/en active Active
- 2006-01-24 AT AT06425032T patent/ATE405137T1/en not_active IP Right Cessation
-
2007
- 2007-01-22 US US12/087,786 patent/US7965527B2/en not_active Expired - Fee Related
- 2007-01-22 CA CA002636442A patent/CA2636442A1/en not_active Abandoned
- 2007-01-22 CN CN2007800028128A patent/CN101371621B/en not_active Expired - Fee Related
- 2007-01-22 TW TW096102291A patent/TW200738066A/en unknown
- 2007-01-22 KR KR1020087020633A patent/KR101339063B1/en not_active IP Right Cessation
- 2007-01-22 WO PCT/EP2007/050580 patent/WO2007085580A1/en active Application Filing
-
2008
- 2008-06-18 ZA ZA200805276A patent/ZA200805276B/en unknown
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5008771A (en) * | 1988-12-13 | 1991-04-16 | Sgs-Thomson Microelectronics S.R.L. | Diagnostic circuit for units providing current control and protection against excessive heat dissipation for semiconductor power devices |
| CN2221267Y (en) * | 1994-09-24 | 1996-02-28 | 陈为匡 | Device for protecting power semiconductor device |
| US6222322B1 (en) * | 1997-09-08 | 2001-04-24 | Q Technology Incorporated | Ballast with lamp abnormal sensor and method therefor |
| US20040070910A1 (en) * | 2002-09-30 | 2004-04-15 | Zenko Gergintschew | Method for driving a semiconductor switch and circuit configuration with a semiconductor switch |
Also Published As
| Publication number | Publication date |
|---|---|
| TW200738066A (en) | 2007-10-01 |
| EP1811816B1 (en) | 2008-08-13 |
| US7965527B2 (en) | 2011-06-21 |
| CN101371621A (en) | 2009-02-18 |
| US20090034307A1 (en) | 2009-02-05 |
| PL1811816T3 (en) | 2009-01-30 |
| EP1811816A1 (en) | 2007-07-25 |
| KR101339063B1 (en) | 2013-12-09 |
| ZA200805276B (en) | 2009-09-30 |
| ES2310898T3 (en) | 2009-01-16 |
| KR20080096792A (en) | 2008-11-03 |
| WO2007085580A1 (en) | 2007-08-02 |
| ATE405137T1 (en) | 2008-08-15 |
| CA2636442A1 (en) | 2007-08-02 |
| DE602006002238D1 (en) | 2008-09-25 |
| AU2007209404A1 (en) | 2007-08-02 |
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