CN101355321A - Multiple power conversion apparatus and multiple transformer - Google Patents
Multiple power conversion apparatus and multiple transformer Download PDFInfo
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- CN101355321A CN101355321A CNA2008101091680A CN200810109168A CN101355321A CN 101355321 A CN101355321 A CN 101355321A CN A2008101091680 A CNA2008101091680 A CN A2008101091680A CN 200810109168 A CN200810109168 A CN 200810109168A CN 101355321 A CN101355321 A CN 101355321A
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Abstract
A multiple power conversion apparatus, having a multiple transformer (20) that distributes m phase alternating current input to an initial winding to (m*n) secondary windings; a m groups of multiple power converters. The multiple power converters are formed by connecting n level single phase inverters (3a to 3f) that convert alternating current induced by each secondary winding to that of variable voltage or variable frequency in series; the secondary windings of the multiple transformer (20) has a phase difference with 60/n degrees among n level single phase inverters (3a to 3f) corresponding to output in same phase and a phase difference with 60/(n*m) degrees among m*n single unit inverters corresponding to all m phase. Therefore, high order harmonic current in lower order can be reduced.
Description
Technical field
The present invention relates to a kind of multiple power conversion apparatus, and wherein employed multiple transformer of a plurality of single-phase unit inverters (cell inverter) that are connected in series.
Background technology
In the variable-speed operation of high pressure (for example more than the 3kV) motor,, often use the multiple power conversion apparatus of the single-phase unit inverter that is connected in series for the high capacity of realizing inverter and the improvement of output waveform.This multiple power conversion apparatus, use a kind of multiple transformer (multiple transformer) of exporting the different three-phase alternating voltage of a plurality of phase places from 3 cross streams power supplys, a secondary winding of each U, V, W phase 20 degree that offset one by one for example in patent documentation 1, have been proposed to make, offset the one by one methods of 10 degree of the phase place that each two of remaining every phases are amounted to six secondary winding.Thus, by being equivalent to the combination of 18 impulse commutations and 36 impulse commutations, reduced power high-order harmonic generation.
Then, will input to motor by the single phase alternating current (A.C.) signal that their output of multiple connection obtains.It is characterized in that, in this device,, can under the situation of not using output transformer, directly apply high voltage to motor by quantity that increases single-phase unit inverter or the direct voltage that improves smmothing capacitor portion.Therefore, the power loss that causes because of output transformer can be ignored, power converter efficiently can be realized.At this moment, in order to reduce power high-order harmonic generation, adjust by phase place the secondary winding of multiple transformer, will go to the input phase of the single-phase unit inverter of each mutually pairing n of output (n is a natural number), the 60/n degree that offsets one by one is so that make it all identical mutually with each output.Thus, by carrying out the 6n impulse commutationization, can reduce number of times than (6n-1), (6n+1) inferior low high order harmonic component.These all are known contents, for the multiple power conversion apparatus that utilizes it, put down in writing in patent documentation 2.
[patent documentation 1] spy opens flat 10-337042 communique
No. 5625545 specification of [patent documentation 2] United States Patent (USP)
But in the technology of each patent documentation, Dang Gexiang jointly offsets 60/n when spending one by one, under the few situation of the such progression of n=2, to have irreducible high order harmonic component number of times be 11 times, more than 13 times, compare the problem of the higher harmonic current of residual low order with n=3 or at 4 o'clock.In addition, when several windings that as patent documentation 1, make up each phase a part of, also might produce the possibility of (6k+1), (6k-1) (k the is a positive integer) higher harmonic current beyond inferior.
Summary of the invention
Given this, problem of the present invention is, a kind of multiple power conversion apparatus that can reduce the higher harmonic current of low order more, and wherein employed multiple transformer are provided.
In order to solve above-mentioned problem, multiple power conversion apparatus of the present invention possesses: when n, m are natural number, distribute to (the multiple transformer of individual secondary winding of m * n) with being input to m cross streams electricity in the elementary winding; With m group multiple power converter, described multiple power converter is connected in series with n the single-phase unit inverter that the alternating current that will distribute to described each secondary winding is transformed to the alternating current of variable voltage or variable frequency and forms, wherein, the secondary winding of described multiple transformer, export the phase difference that has the 60/n degree between the described single-phase unit of pairing n level inverter respectively at homophase, at the mutually pairing (phase difference between the individual single-phase unit of m * n) inverter the is 60/ respectively (degree of m * n) of all m.
The secondary current of multiple transformer comprises the higher harmonic current that single-phase unit inverter is produced, and exists composition and the composition that does not rely on mains ripple based on mains ripple in this higher harmonic current.
(degree of m * n) can reduce the composition that do not rely on mains ripple, promptly be lower than (6n-1), (6n+1) inferior higher harmonic current to be 60/ respectively by the phase difference between the mutually pairing m * n of all m single-phase unit inverter.In addition, the electric capacity by being adjusted at the smmothing capacitor that is provided with in the single-phase unit inverter or the impedance of multiple transformer reduce the mains ripple of smmothing capacitor, reduce mains ripple, reduce the higher harmonic current composition based on mains ripple.In addition, the output of described multiple power conversion apparatus is made as U, V, W3 three-phase, the phase of input signals of going to described single-phase unit inverter from the secondary winding of described multiple transformer is poor, according to the order of (U, V, W), (W, U, V) or (V, W, U), lag behind one by one or leading 20/n degree.
According to the present invention, can reduce the more higher harmonic current of low order.
Description of drawings
Fig. 1 is the pie graph of the multiple power conversion apparatus of first embodiment of the invention.
Fig. 2 is the pie graph of multiple power conversion apparatus as a comparative example.
Fig. 3 is to based on the source current of emulation and its fft analysis result, the figure that first execution mode and comparative example are compared.
Fig. 4 is to the high order harmonic component composition based on the source current of emulation, the figure that first execution mode and comparative example are compared.
Fig. 5 is the pie graph of the multiple power conversion apparatus of second embodiment of the invention.
Fig. 6 is the pie graph of the multiple power conversion apparatus of third embodiment of the invention.
Among the figure: the civilian power supply of 1-, 2,20,21,22,23-multiple transformer, 3a, 3b, 3c, 3d, 3e, 3f, 31a, 31b, 31c, 31d, 31e, 31f, 31g, 31h, 31i, 31j, the single-phase unit of 31k, 31L-inverter, the 4-motor, 100,105,110, the 120-multiple power conversion apparatus, 301a-diode rectification portion, 302a-smmothing capacitor portion, the 303a-inverter part, the P-neutral point.
Embodiment
(first execution mode)
The multiple power conversion apparatus of present embodiment, 2 grades of multiple modes of employing n=2.
Among Fig. 1, multiple power conversion apparatus 100 possesses: the multiple transformer 20 that is connected with the civilian power supply 1 of the three-phase of m=3; And, 6 the single- phase unit inverter 3a, 3b, 3c, 3d, 3e, the 3f that are connected with multiple transformer 20,2 single-phase unit inverter 3a that output is connected in series and 3b, 3c and 3d, 3e are connected with motor 4 with after 3f three is connected.Wherein, 2 grades of single-phase unit inverter 3a, 3b that output is connected in series constitute the multiple power converter, and single- phase unit inverter 3c, 3d and single- phase unit inverter 3e, 3f constitute the multiple power converter too.That is, multiple power conversion apparatus 100 possesses: multiple transformer 20 with output by three 3 groups of multiple power converters that are connected.In addition, in Fig. 1, multiple power conversion apparatus 100 can be connected with motor 4 with three-phase Y tie lines by neutral point P is set, but also can connect by the △ tie lines.
Multiple transformer 20 possesses elementary winding and 6 three-phase secondary winding that Y connects, and three-phase power is distributed to 6 secondary winding.In addition, secondary winding U, V, W mutually between the single-phase unit inverter (3a and 3b, 3c and 3d, 3e and 3f) of homophase, the phase difference that keeps the 60/n=30 degree one by one, the multiple power converter of the same one-level of each phase keeps the phase difference of 60/6=10 degree one by one.That is, for whole phase, amounting to 6 and (between the individual single-phase unit of=3 phases * n) inverter, keep the phase difference of 60/6=10 degree one by one in correspondence.For example, the phase place of the secondary winding of multiple transformer 20 is adjusted to 0 degree (U phase 3a) ,-30 degree (U phase 3b), 10 degree (V phase 3c) ,-20 degree (V phase 3d), 20 degree (W phase 3e) ,-10 degree (U phase 3f) respectively.Under this situation, according to the order of U → V → W, leading one by one 10 degree of phase place (0 degree → 10 degree → 20 degree and-30 degree →-20 degree →-10 degree).
Here, for secondary winding, be insulated between the single-phase unit inverter of homophase, each is utilized star-like sawtooth tie lines or △ type sawtooth tie lines mutually, possess the phase angle.Wherein, the sawtooth tie lines is meant each is provided with a plurality of windings mutually, and the tie lines that carries out in the mode of the winding that strides across other phases.Wherein, put down in writing star-like sawtooth tie lines and △ type sawtooth tie lines among Fig. 1, but can use star-like sawtooth also can use under the situation of △ type sawtooth when the offsetting prescribed phases, it all is the same using any one result.For example, under the situation that 10 degree lag behind, can utilize star-like sawtooth tie lines, also can utilize △ sawtooth tie lines from leading 20 degree of △ tie lines from star-like tie lines hysteresis 10 degree.
The individual interchange output of each phase n (=2) of multiple transformer 20 is transfused to single-phase unit inverter 3a, 3b (U exports usefulness mutually), 3c, 3d (V exports usefulness mutually), 3e, 3f (W exports usefulness mutually).Single- phase unit inverter 3a, 3b, 3c, 3d, 3e, 3f possess the 301a of diode rectification portion, the 302a of smmothing capacitor portion and based on the inverter part 303a of switch element, three-phase ac power are transformed to the single-phase alternating current of any amplitude, frequency.Promptly, for single- phase unit inverter 3a, 3b, 3c, 3d, 3e, 3f, by the 301a of diode rectification portion that is made of three phase bridge three-phase alternating current is transformed to direct current, smoothed capacitor department 302a is level and smooth for this direct current, and is input to inverter part 303a.In addition, the pulsating voltage of the 302a of smmothing capacitor portion possesses 2 times frequency of the supply frequency of civilian power supply 1.
Have again, for inverter part 303a, switch element S1, the S2 and switch element S3, the S4 that are connected in series are connected in parallel, be in first state that connection (ON) state, switch element S2, S3 are in disconnection (OFF) state at switch element S1, S4, be in on-state with switch element S2, S3, switch element S1, S4 are under second state of off-state, the polarity upset of output voltage.In addition, inverter part 303a also makes switch element S1, S2, S3, S4 all be in off-state sometimes, and the angle of flow of the motor current that flows in the control motor 4 changes the average voltage that motor 4 is applied.In addition, by changing switching frequency, make the rotation speed change of motor 4.
In addition, switch element S1, S2, S3, the S4 of the single-phase unit inverter 3a that is connected in series, switch element S1, S2, S3, S4 with single-phase unit inverter 3b are controlled by the while on-off respectively, and output is to 2 times voltage of the direct voltage of the 302a of smmothing capacitor portion charging.That is, three multiple power converters by three-phase Y tie lines, come 2 times of driven motor 4 with the output voltage of multiple transformer 20 by output.In addition, on switch element S1, S2, S3, the S4, be connected with commutation diode respectively, the caused back electromotive force of the internal driving of motor 4 is commutated.Combination pch-FET and nch-FET in addition, in Fig. 1,, also can use FET, if then can easily constitute turner though switch element S1, S2, S3, S4 have used IGBT.
Then, in order to represent the effect of present embodiment, the alternate example that does not have phase place to offset of the output voltage of multiple transformer is described.Fig. 2 is the pie graph of 2 grades of multiple comparative examples, in this comparative example, the secondary winding of multiple transformer 2 together is connected with the △ tie lines with star-like tie lines mutually with U, V, W, is 0 degree ,-30 degree (U to), 0 degree ,-30 degree (V phase), 0 degree ,-30 degree (W phase) from single-phase unit inverter 3a to the phase place of 3f input, the alternate phase difference that do not exist.In addition, positive numeral is big more, and the expression phase place is leading.Equally, under the situation of n=3, each is made of 3 single-phase unit inverters, and the phase place of the secondary winding of multiple transformer is public at U, V, W mutually, 0 degree that for example offsets one by one ,-20 degree ,-40 degree.In addition, under the situation of n=4, each is made of 4 single-phase unit inverters, and the phase place of the secondary winding of multiple transformer is public at U, V, W mutually, 0 degree that for example offsets one by one ,-15 degree ,-30 degree ,-45 degree.
Then, relatively present embodiment and comparative example reduce effect to high order harmonic component and describe.The condenser voltage Vdc of the 302a of smmothing capacitor portion comprises ripple component, and this condenser voltage Vdc is divided into direct voltage VDC and Vdc pulsation (inverter output frequency 2 times).In addition, the secondary current of multiple transformer 2 comprises the higher harmonic current composition that the switch by inverter part 303a causes.In other words, flowing based on the higher harmonic current of direct voltage VDC, promptly do not relying on the higher harmonic current of Vdc pulsation, and flowing and depend on the higher harmonic current of Vdc pulsation.
At first, do not have under the situation that phase place offsets in that such each of comparative example is alternate, the secondary current of multiple transformer 2 is divided into the electric current composition and the electric current composition that depends on the Vdc pulsation of the pulsation of the condenser voltage Vdc that does not rely on the 302a of smmothing capacitor portion, with each composition as U, V, each phase of W and, as approximate as (1) formula, (2) formula.In addition, Vdc flip-flop is divided into the same-phase composition and modelling with the effect of U, V, each phase of W.
Do not rely on the x primary current composition (comparative example) of Vdc pulsation: ω x ≡ x secondary frequencies
Ixs·{sin(ωx·t)+sin(ωx·t)+sin(ωx·t)}＝3·Ixs·sin(ωx·t)(1)
Depend on the x primary current composition (comparative example) of Vdc pulsation: ω c ≡ Vdc ripple frequency=2 * inverter output frequency
Ixr·{sin(ωc·t)·sin(ωx·t)+sin(ωc·t-2·120°)·sin(ωx·t)+sin(ωc·t+2·120°)·sin(ωx·t)}＝0 (2)
That is, in comparative example, the main residual higher harmonic current composition that does not rely on the Vdc pulsation, the higher harmonic current composition that depends on the Vdc pulsation is eliminated fully.
Then, under the situation of the phase place that offsetted as first execution mode, (1) formula and (2) formula are rewritten as (3) formula and (4) formula.Wherein, in the formula ± among, symbol+expression makes the situation of leading one by one 10 degree of phase place, symbol-phase antirepresentation make lag behind the one by one situations of 10 degree of phase place according to the order of U → V → W.
Do not rely on the x primary current composition of Vdc pulsation:
Ixs·{sin(ωx·t)+sin(ωx·t±x·10°)+sin(ωx·t±x·20°)} (3)
Depend on the x primary current composition of Vdc pulsation:
Ixr·{sin(ωc·t)·sin(ωx·t)+sin(ωc·t-2·120°)·sin(ωx·t±x·10°)+sin(ωc·t+2·120°)·sin(ωx·t±x·20°)} (4)
In addition, for first～the 3rd of (4) formula, it is such to be rewritten as (5) formula～(7) formula respectively.
sin(ωc·t)·sin(ωx·t)＝1/2·{cos(ωx-ωc)·t-cos(ωx+ωc)·t} (5)
sin(ωc·t-2·120°)·sin(ωx·t±x·10°)＝1/2·[cos{(ωx-ωc)·t±x·10°+240°}-cos{(ωx+ωc)·t±x·10°-240°}] (6)
sin(ωc·t+2·120°)·sin(ωx·t±x·20°)＝1/2·[cos{(ωx-ωc)·t±x·20°-240°}-cos{(ωx+ωc)·t±x·20°+240°}] (7)
According to foregoing as can be known, by the phase place of each phase that offsets,, become Vdc ripple frequency ω c and based on the jitter components (ω n ± ω c) (displacement) of high order harmonic component ω x based on x high order harmonic component of Vdc pulsation.
Have again,, the inverter output frequency is made as the 50Hz identical with supply frequency (that is ω c=2 π * 100Hz), as (8) formula～(13) formula, obtain the size of the inferior high order harmonic component composition of x (=9,11,13,15), as the occurrence of first execution mode.In addition, be set at the situation that makes leading one by one 10 degree of phase place with the order of U → V → W.
09 high order harmonic components
The Vdc ripple component; X (=11 times)-Vdc pulse (2 times):
1/2·I11r·{cos(ω9·t)+cos(ω9·t+110°+240°)+cos(ω9·t+220°-240°)}
＝1/2·I11r·{2.92·cos(ω9·t)+0.51·sin(ω9·t)}
＝1.48·I11r·sin(ω9·t+80.1°) (8)
Vdc flip-flop; X=9 time: do not have
0 11 high order harmonic components
The Vdc ripple component; X (=13 times)-Vdc pulse (2 times):
1/2·I13r·{cos(ω11·t)+cos(ω11·t+130°+240°)+cos(ω11·t+260°-240°)}
＝1/2·I13r·{2.92·cos(ω11·t)+0.51·sin(ω11·t)}
＝1.48·I13r·sin(ω11·t+80.1°) (9)
Vdc flip-flop; X=11 time:
I11s·{sin(ω11·t)+sin(ω11·t+110°)+sin(ωω11·t+220°)}
＝I11s·{0.3·cos(ω11·t)-0.11·sin(ω11·t)}
＝0.32·I11s·sin(ω11·t-69.9°)(10)
0 13 high order harmonic components
The Vdc ripple component; X (=11 times)+Vdc pulse (2 times):
1/2·I11r·{-cos(ω13·t)-cos(ω13·t+110°-240°)-cos(ω13·t+220°+240°)}
＝1/2·I11r·{-0.19·cos(ω13·t)+0.21·sin(ω13·t)}
＝0.14·I11r·sin(ω13·t-42.1°)(11)
Vdc flip-flop; X=13 time:
I13s·{sin(ω13·t)+sin(ω13·t+130°)+sin(ω13·t+260°)}
＝I13s·{-0.21·cos(ω13·t)+0.19·sin(ω13·t)}
＝0.28·I13s·sin(ω13·t-47.9°)(12)
0 15 high order harmonic components
The Vdc ripple component; X (=13 times)+Vdc pulse (2 times):
1/2·I13r·{-cos(ω15·t)-cos(ω15·t+130°-240°)-cos(ω15·t+260°+240°)}
＝1/2·I13r·{0.11·cos(ω15·t)-0.3·sin(ω15·t)}
＝0.16·I13r·sin(ω15·t-20.1°)(13)
Vdc flip-flop; X=15 time: do not have
According to aforementioned calculation, 11 times, the 13 times high order harmonic component amplitudes based on direct voltage VDC of comparative example are 3I11s, 3I13s, and 11 times, 13 times high order harmonic component amplitudes of present embodiment are about 0.3I11s, 0.3I13s, and the high order harmonic component amplitude falls and is low to moderate 1/10 approximately.Replace, based on the Vdc ripple component, 9 times, 11 times high order harmonic component amplitude increases.But,, can reduce high order harmonic component amplitude based on the Vdc pulsation by increasing the smmothing capacitor electric capacity of single-phase unit inverter.In addition, by improving the impedance of multiple transformer, also can reduce the high order harmonic component composition.In addition, in comparative example, owing to the higher harmonic current composition based on direct voltage VDC is main, so, even waiting, adjustment smmothing capacitor electric capacity reduces the Vdc pulsation, can not fully reduce high order harmonic component.
That is,,, compare, can be reduced to the more high order harmonic component of high order with the comparative example that reduces less than the high order harmonic component of (6n+1) by phase place with the secondary winding of identical size offsetting multiple transformer 2 according to present embodiment.Thus, even if the few multiple power conversion apparatus 100 of progression also can fully reduce higher harmonic current.
Fig. 3, Fig. 4 have represented simulation result.Among Fig. 3, the current waveform and FFT (fast Fourier transform) analysis result of expression source current (A) are as the simulation result of comparative example shown in Figure 2 and present embodiment shown in Figure 1 (n=2).Fig. 3 (a) is the current waveform of comparative example, and Fig. 3 (c) is the current waveform of present embodiment, and present embodiment wave distortion comparatively speaking is few.In addition, the fft analysis result of Fig. 3 (b) expression comparative example, the fft analysis result of Fig. 3 (d) expression present embodiment.Basic wave 50Hz has produced 11 time, the 13 time high order harmonic components equal with 12 pulse diodes/brilliant lock rectifier, (6n ± 1) inferior high order harmonic component in a large number in the comparative example relatively.Relative with it, though produced 9 times, 11 times high order harmonic component in the present embodiment, compare with comparative example and significantly reduce.
In addition, Fig. 4 represents their each high order harmonic component components in proportions (%).White hollow bar is represented comparative example, oblique line rod expression first execution mode.In addition, for 9 times, 11 times high order harmonic component amplitudes,, also can be reduced by the condenser capacitance that increases the smmothing capacitor 302a of portion, the impedance of multiple transformer 20.
In addition, by adjusting the secondary winding of multiple transformer 20, for example, will be to U, V, the input phase of single-phase unit inverter 3a～3f that the mutually pairing every phase of W is 2, picture 0 degree,-30 degree (U phase), 10 degree,-20 degree (V phase),-10 degree,-40 degree (W phase) like this, according to W, U, the order of V makes the leading one by one 10 (=30/n) degree of phase place, perhaps, picture 0 degree,-30 degree (U phase),-20 degree,-50 degree (V phase),-10 degree,-40 degree (W phase) like this, according to V, W, the order of U makes phase place, and leading one by one 10 (=30/n) degree can obtain equal effect.
In addition, the multiple power conversion apparatus of present embodiment, as long as will offset the 60/n=30 degree one by one to the input phase difference of the single-phase unit inverter (3a and 3b, 3c and 3d, 3e and 3f) of homophase, to whole phase, amount to 6 (in the individual single-phase unit of=3 phases * n) inverter in correspondence, keep respectively relatively the phase difference of 60/3n=10 degree to get final product, it doesn't matter with the absolute value of phase place.For example, the phase place of each single-phase unit inverter (3a and 3b, 3c and 3d, 3e and 3f) is 15 degree ,-15 degree (U mutually), 25 degree ,-5 degree (V phase), 5 degree ,-25 degree (W phase), also can obtain same effect.
In addition, the 301a of diode rectification portion shown in Figure 1 can replace diode bridge, uses thyristors such as thyristor, replaces and constitutes transducer (converter).This displacement is carried out all diode rectification portions of each single-phase inverter 3a～3f.Thus, in the present embodiment, compare with comparative example and can significantly reduce power high-order harmonic generation.
(second execution mode)
Then, to second execution mode of the present invention, focus on that the difference with first execution mode describes.In first execution mode, according to leading one by one 10 degree of the order phase place of U, V, W phase, and in second execution mode, 10 degree one by one lag behind.Thus, though do not represent calculating formula, same with first execution mode, 11 times, 13 times high order harmonic component compositions that cause because of direct voltage VDC reduce, and as the high order harmonic component composition based on the Vdc pulsation, produce 13 times, 15 times composition in second execution mode.
The multiple power conversion apparatus 110 of Fig. 5 and the first execution mode something in common are, adjust the secondary winding phase place of multiple transformer 21, U, V, W mutually between the single-phase unit inverter (3a and 3b, 3c and 3d, 3e and 3f) of homophase, have the phase difference of 60/n=30 degree respectively; For whole phase, at (the phase difference that has the 60/3n=10 degree in the individual single-phase unit of=3 phases * n) inverter respectively that amounts to 6 of correspondence.But, be with the difference of first execution mode, the secondary winding of multiple transformer 21 as 0 degree (U phase 3a) ,-30 degree (U phase 3b) ,-10 degree (V phase 3c) ,-40 degree (V phase 3b) ,-20 degree (W phase 3e) ,-50 degree (W phase 3f), makes phase lag.In addition, same with first execution mode, by increase the Vdc pulsation is reduced, thereby reduce the high order harmonic component amplitude by smmothing capacitor electric capacity.
In addition, different with Fig. 5, by adjusting the secondary winding of multiple transformer 21, for example, according to the input phase of giving U, V, mutually pairing per two the single-phase unit inverter 3a～3f of W, be that 0 degree ,-30 degree (U phase) ,-10 degree ,-40 degree (V phase), 10 degree ,-20 degree (W phase) are such, make phase place 10 degree that lag behind one by one according to the order of W, U, V; Perhaps, be that 0 degree ,-30 degree (U phase), 20 degree ,-10 degree (V phase), 10 degree ,-20 degree (W phase) are such, make phase place 10 degree that lag behind one by one according to the order of V, W, U, also can obtain and the equal effect of the situation of Fig. 5.In addition, they and first execution mode are same, as long as the phase difference of offsetting the 60/n=30 degree one by one for the input phase maintenance of the single-phase unit inverter (3a and 3b, 3c and 3d, 3e and 3f) of homophase, for whole phase, amount to 6 (in the individual single-phase unit of=3 phases * n) inverter in correspondence, relatively misplace the one by one phase difference of 60/3n=10 degree of maintenance gets final product, and it doesn't matter with the absolute value of phase place.In addition, same with the record of first execution mode, no matter use which of △ sawtooth and star-like sawtooth, as long as the phase place of the regulation that can offset is equivalence.
In sum, in the present embodiment, utilized the multiple power conversion apparatus of multiple transformer to compare, had the effect that can significantly reduce power high-order harmonic generation with comparative example.
(the 3rd execution mode)
First execution mode is though explanation is that for each phase, 4 single-phase unit inverters also can be connected in series for the situation of each n=2 that 2 single-phase unit inverters are connected in series.Among Fig. 6, the multiple power conversion apparatus 120 of third embodiment of the invention, to U, V, each phase of W, the multiple respectively individual single-phase unit inverter 31a～31L of n=4 that is connected with.Multiple transformer 22, be respectively the mode of 0 degree ,-15 degree ,-30 degree ,-45 degree (U phase) ,-5 degree ,-20 degree ,-35 degree ,-50 degree (V phase) ,-10 degree ,-25 degree ,-40 degree ,-55 degree (W phase) according to the input phase of giving each single-phase inverter, adjust the secondary winding phase place.
In addition, except Fig. 6, as long as (input of 31a～31d, 31e～31h, 31I～31L) has the phase difference of lag or lead 60/n=15 degree one by one to 4 single-phase unit inverters of each phase, for whole phase, (the phase difference that keeps the 60/3n=5 degree in the individual single-phase unit of the 3 phases * n) inverter respectively that corresponding amounts to 12.Thus, same with first execution mode, can reduce as a comparative example, be equivalent to 24 impulse commutations structure 23 times, the 25 times high order harmonic component amplitudes that can't reduce.
In addition, though do not illustrate, but under the situation of n=3 too, if each situation about exporting mutually for n level, m mutually, the phase difference that then keeps the 60/n degree respectively by the input phase between each phase n single-phase unit inverter, (phase difference of degree of m * n) can reduce high order harmonic component thereby compare with comparative example for wholely keeping 60/ between n * m the single-phase unit inverter respectively in amounting to of correspondence.In addition, be made as more than the 3kV with voltage between lines, can drive the motor of high pressure by output voltage with multiple power conversion apparatus.
(the 4th execution mode)
Then, the difference to the 4th execution mode of the present invention and first execution mode～the 3rd execution mode describes.In the present embodiment, in the power-converting device of three-phase output, each phase n of multiple connection single-phase unit inverter.With one as the U phase, relative U phase lag output 120 degree are made as the V phase mutually, leading 120 degree are made as the W phase time mutually, give the phase difference of secondary winding from the elementary winding of multiple transformer, leading one by one or 20/ degree that lags behind according to the order of (U, V, W), (W, U, V) or (V, W, U) then, and then is corresponding secondary winding phase lag 120 degree of V according to phase place, the mode of leading 120 degree of the corresponding secondary winding phase place of W, the secondary phase place of adjustment multiple transformer.For example, under the situation of n=2, be made as 0 the degree ,-30 the degree (U phase) ,-110 the degree (=10-120) ,-140 (=-20-120) (V phase) degree, 140 (=20+120) degree, 110 (=-10+120) degree (W phase).In the present embodiment,, adjust the secondary phase place of multiple transformer, mate the phase place of Vdc pulsation by the phase difference (120 degree) of considering each phase.The 4th execution mode and first execution mode are same, have the effect that can reduce based on the high order harmonic component amplitude of direct voltage VDC.
Claims (8)
1, a kind of multiple power conversion apparatus possesses: when n, m are natural number, distribute to (the multiple transformer of individual secondary winding of m * n) with being input to m cross streams electricity in the elementary winding; With m group multiple power converter, described multiple power converter is connected in series with n the single-phase unit inverter that the alternating current that will distribute to described each secondary winding is transformed to the alternating current of variable voltage or variable frequency and forms, wherein,
The secondary winding of described multiple transformer is exported the phase difference that has the 60/n degree between the described single-phase unit of pairing n level inverter respectively at homophase, at the mutually pairing (phase difference between the individual single-phase unit of m * n) inverter the is 60/ respectively (degree of m * n) of all m.
2, a kind of multiple power conversion apparatus possesses: when n, m are natural number, distribute to (the multiple transformer of individual secondary winding of m * n) with being input to m cross streams electricity in the elementary winding; With m group multiple power converter, described multiple power converter is connected in series with n the single-phase unit inverter that the alternating current that will distribute to described each secondary winding is transformed to the alternating current of variable voltage or variable frequency and forms, wherein,
The secondary winding of described multiple transformer is exported the phase difference that has the 60/n degree between the described single-phase unit of pairing n level inverter respectively at homophase, with the alternate phase difference of the pairing single-phase unit of the one-level inverter (degree of m * n) that is 60/ respectively.
3, multiple power conversion apparatus according to claim 1 is characterized in that,
As m=3, when the output of described multiple power conversion apparatus is made as U, V, the output of W three-phase,
The phase difference of the secondary winding of described multiple transformer lags behind or leading 20/n degree one by one according to the order of (U, V, W), (W, U, V) or (V, W, U).
4, a kind of multiple power conversion apparatus, possess the three-phase alternating current that will be input to elementary winding and distribute to multiple transformer and three groups of multiple power converters of 6 secondary winding, described multiple power converter, being connected in series with 2 single-phase unit inverters that the alternating current that will distribute to described each secondary winding is transformed to the alternating current of variable voltage or variable frequency forms, wherein
The secondary winding of described multiple transformer is exported the phase difference that has 30 degree between pairing 2 described single-phase unit inverters at homophase, and the phase difference between all 3 mutually pairing 6 single-phase unit inverters is 10 degree.
5, a kind of multiple power conversion apparatus possesses: when n is natural number, distribute to the multiple transformer of 3 * n secondary winding with being input to 3 cross streams electricity in the elementary winding; With 3 groups of multiple power converters, described each multiple power converter, being connected in series with n the single-phase unit inverter that the alternating current that will distribute to described each secondary winding is transformed to the alternating current of variable voltage or variable frequency forms, the phase difference output that has 120 degree each other one by one, 3 phase load devices are driven, wherein
The secondary winding of described multiple transformer is exported the phase difference that has the 60/n degree between pairing n the described single-phase unit inverter respectively at homophase,
Described 3 phase load devices, first is the U phase mutually, and these U phase lag output 120 degree is the V phase mutually relatively, and what described relatively U mutually leading 120 spent is the W phase mutually,
Described multiple transformer, phase difference from elementary winding to secondary winding, order according to (U, V, W), (W, U, V) or (V, W, U), lag behind one by one or leading 20/n degree, and, mutually pairing secondary winding phase lag 120 degree of V, leading 120 degree of the mutually pairing secondary winding phase place of W.
6, multiple power conversion apparatus according to claim 1 is characterized in that,
By electric capacity that is increased in the smmothing capacitor that is provided with in the described single-phase unit inverter or the impedance of adjusting described multiple transformer, reduce the mains ripple of described smmothing capacitor.
7, multiple power conversion apparatus according to claim 1 is characterized in that,
The output voltage of described multiple power conversion apparatus is more than the 3kV on online the voltage.
8, a kind of multiple transformer, when n, m are natural number, be input to m cross streams electricity in the elementary winding distribute to (the individual secondary winding of m * n),
Described secondary winding is exported the phase difference that has the 60/n degree between pairing n described secondary winding respectively at homophase, and the phase difference between the mutually pairing m * n of all m described secondary winding is respectively 60/ (m * n) spend.
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| JP2007136417A JP4512117B2 (en) | 2007-05-23 | 2007-05-23 | Multiple power conversion device and multiple transformer |
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| CN101958659A (en) * | 2009-07-20 | 2011-01-26 | 通用电气公司 | Be used for direct current power is converted to system, the method and apparatus of alternating electromotive force |
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| Publication number | Publication date |
|---|---|
| JP4512117B2 (en) | 2010-07-28 |
| CN101355321B (en) | 2011-07-13 |
| JP2008295149A (en) | 2008-12-04 |
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