CN101330261A - Switch power circuit - Google Patents
Switch power circuit Download PDFInfo
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- CN101330261A CN101330261A CNA2007100421195A CN200710042119A CN101330261A CN 101330261 A CN101330261 A CN 101330261A CN A2007100421195 A CNA2007100421195 A CN A2007100421195A CN 200710042119 A CN200710042119 A CN 200710042119A CN 101330261 A CN101330261 A CN 101330261A
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Abstract
The invention relates to the switching power supply technique and discloses a switching power supply circuit which comprises an error amplifier, a modulator and a compensation capacitor. The output terminal of the error amplifier is connected with the modulator and the compensation capacitor. The switching power supply circuit further comprises a voltage clamping circuit which is connected with the output terminal of the error amplifier. The modulator can adopt a pulse frequency modulator or a pulse width modulator. The switching power supply circuit can effectively increase the transient response speed of the switching power source, allow the switching power source to function stably under different working voltages and simplify the compensation circuit.
Description
Technical field
The present invention relates to power technique fields, particularly a kind of switching power circuit.
Background technology
In present switching power circuit, (ErrorAmplifier is EA) with a pulse width modulator (PWM) or the pulse frequency modulation device (PFM) with certain dynamic range to generally include an error amplifier.The output of error amplifier is connected to pulse width modulator (PWM) or pulse frequency modulation device (PFM), error amplifier is an operational transconductance amplifier (OperationalTransconductance Amplifier, OTA), it has bigger output area, usually maximum output voltage is the supply voltage of this amplifier, minimum is the ground of this amplifier, promptly has " rail-to-rail " fan-out capability.Error amplifier comes the difference of comparison reference voltage and feedback voltage, and at voltage of error amplifier output output, pulse width modulator (PWM) or pulse frequency modulation device (PFM) are according to error amplifier output end voltage output signal according to difference.For pulsewidth or the arteries and veins frequency of stablizing the modulator output signal, hang a building-out capacitor at the output of error amplifier usually.When the output of error amplifier surpasses the dynamic range of pulsewidth or pulse frequency modulation device, the pulsewidth of the output signal of switching power circuit or arteries and veins can not change frequently, output minimum output energy state or highest energy output state.Because the influence of the output current finite sum output capacitance of error amplifier, when changing, the Switching Power Supply load can cause the pulsewidth or the arteries and veins of switching power circuit output signal frequently can not in time change, reduce the transient response characteristic of Switching Power Supply, cause vibration when serious, especially under the situation that the error amplifier working power can change.In order to improve the response characteristic of Switching Power Supply, the way that adopts is to improve the operating frequency of Switching Power Supply usually, and connects bigger building-out capacitor at the output of operational transconductance amplifier.
Figure 1 shows that a kind of common pulse-width modulation switching power supply circuit, this pulse-width modulation switching power supply circuit comprises an operational transconductance amplifier OTA and a comparator, building-out capacitor of operational transconductance amplifier OTA output termination.Operational transconductance amplifier OTA compares feedback voltage FB with reference voltage REF, and exports a pulse width modulation controlled voltage COMP.Comparator relatively produces the variable square-wave signal PWMO of a pulsewidth (duty ratio) with the ramp signal OSC_ramp of pulse width modulation controlled voltage COMP and oscillator generation.Operational transconductance amplifier OTA has the rail-to-rail fan-out capability, and promptly the maximum output voltage of OTA can reach the supply voltage VDD of OTA, and minimum output voltage can reach ground GND.As shown in Figure 3, the ramp signal OSC_ramp maximum output voltage that oscillator produces is that OSC_peak, minimum output voltage are OSC_valley, when the pulse width modulation controlled voltage COMP of output exceeds the voltage range of OSC_ramp, the duty ratio of the pulse-width modulation square-wave signal of comparator output just can not change, the dynamic range that exceeds Switching Power Supply, there is rising edge lag time T in pulse-width modulation square-wave signal PWMO
LRWith trailing edge lag time T
LF, at this moment will have too much electric charge and be charged in the output capacitance, perhaps the electric charge of output capacitance can not get in time replenishing, and causes output voltage ripple big, ripple longer duration, thereby the transient response ability of reduction Switching Power Supply.And cause the common needs that overcharge or put excessively of output capacitance to adopt bigger building-out capacitor in the lag time in Fig. 3 in order to compensate, and bigger building-out capacitor can make the loop bandwidth of error amplifier further reduce, and reduces the transient response of loop.
Summary of the invention
The technical problem to be solved in the present invention provides a kind of switching power circuit, and this switching power circuit transient response speed is fast, and the stability under the different operating supply voltage is high, and compensating circuit is simple.
For solving the problems of the technologies described above, switching power circuit of the present invention comprises error amplifier, modulator, building-out capacitor, and the same modulator of error amplifier output, building-out capacitor link to each other, and also comprise voltage clamp circuit, are connected in the error amplifier output.
Described modulator can be pulse frequency modulation device or pulse width modulator.
Switching power circuit of the present invention, increase voltage clamp circuit at the error amplifier output, make error amplifier output end voltage peak a little more than modulator comparison signal ceiling voltage, as long as minimum slightly sample is lower than the comparison signal minimum voltage, this feedback voltage one changes, modulator can be determined the signal of output according to variable quantity at once, has improved the response speed of circuit.Simultaneously because error amplifier output end voltage peak, minimum behind the adding voltage clamp circuit are determined value, therefore can not exist the working power voltage of error amplifier can influence the situation that circuit responds, make switching power circuit more stable in whole operating voltage range, can simplify the design of compensating circuit.
Description of drawings
Fig. 1 is a kind of common pulse-width modulation switching power supply circuit;
Fig. 2 is an embodiment schematic diagram of switching power circuit of the present invention;
Fig. 3 is an each point change in voltage sequential schematic diagram in the switching power circuit shown in Figure 1;
Fig. 4 is an each point change in voltage sequential schematic diagram in the switching power circuit shown in Figure 2;
Fig. 5 is one of implementation method of voltage clamp circuit;
Fig. 6 be voltage clamp circuit implementation method two;
Fig. 7 is a pulse frequency modulation switching power circuit of the present invention;
Fig. 8 is the switching power source control circuit of current control mode of the present invention.
Embodiment
Below in conjunction with the drawings and the specific embodiments the present invention is described in further detail.
As can be seen from Figure 3, increase the transient response ability of control system, at first need to shorten rising edge lag time T among Fig. 3
LRWith trailing edge lag time T
LF, when changing appearred in error amplifier feedback voltage FB, switching power circuit can carry out the adjustment frequently of pulsewidth or arteries and veins fast like this, made output be stabilized in a certain fixed value.In the switching power circuit of the present invention, mainly utilize a voltage clamp circuit, the output voltage of error amplifier is clamped down within the dynamic adjustments scope of pulsewidth or arteries and veins frequency (PWM or PFM) modulator, and voltage clamp circuit is connected on the output of error amplifier.In pulse width control circuit, the output voltage COMP of error amplifier is clamped at the minimum voltage OSC_valley of clamper low-voltage lowerClamp a little less than the ramp signal OSC_ramp of oscillator generation, and clamper high voltage upperClamp is a little more than the ceiling voltage OSC_peak of ramp signal OSC_ramp, pulse width modulator just can be operated under the highest or the lowest duty cycle like this, can satisfy simultaneously the characteristics of fast transient response, for example, the crest voltage of ramp signal OSC_ramp is 2.5V, its valley point voltage is 0.5V, the output voltage COMP of error amplifier can clamp down at minimum voltage 0.4V so, ceiling voltage is clamped down at 2.6V, and modulator enters the time that duty ratio can make and will shorten greatly like this.If supply voltage is 5V, the maximum output voltage of error amplifier also will reach 5V, and modulator can carry out the modulation of duty ratio when the output voltage COMP of error amplifier drops to 2.5V.Under same Slew Rate (slew rate), after output voltage error amplifier COMP is clamped down on, pulse width modulator enters the time of modulation and has only 1/25 of original required time, transient response improves greatly, can change fast owing to duty ratio simultaneously, the building-out capacitor that is connected to the error amplifier output also can reduce greatly, thereby reaction speed is further improved.
The error amplifier voltage clamp circuit must have following properties, when the output voltage COMP of error amplifier is elevated to clamper high voltage upperClamp, voltage clamp circuit absorbs certain electric current, make COMP can be stabilized in clamper high voltage upperClamp, and when COMP is reduced to clamper low-voltage lowerClamp, voltage clamp circuit can be emitted certain electric current, voltage is stabilized near the clamper low-voltage lowerClamp, and when the output voltage of working as error amplifier is between the clamper high voltage is with the clamper low-voltage, voltage clamp circuit neither absorbs does not emit electric current yet, voltage clamp circuit can the mushing error amplifier work, pulse width modulator can be worked normally.Fig. 5 and Fig. 6 are two kinds of implementations of this voltage clamp circuit.
Among Fig. 5, voltage clamp circuit comprises the first operational amplifier OP1, the second operational amplifier OP2, the first field effect transistor M1, the second field effect transistor M2, the normal phase input end of the first operational amplifier OP1 meets a fixing clamper high voltage upperClamp, inverting input connects the operational transconductance amplifier output, the output termination first field effect transistor M1 grid, the first field effect transistor M1 source end and drain terminal connect operational transconductance amplifier output and ground respectively; The normal phase input end of the second operational amplifier OP2 meets a fixing clamper low-voltage lowerClamp, inverting input connects the operational transconductance amplifier output, the output termination second field effect transistor M2 grid, the second field effect transistor M2 source end and drain terminal connect operational transconductance amplifier output and DC power supply respectively.The first operational amplifier OP1 maximum output voltage that is used for clamping down on operational transconductance amplifier OTA wherein, when the output voltage COMP that clamps down on operational transconductance amplifier OTA rises near clamper high voltage upperClamp, the first operational amplifier OP1 can control the conducting of the first field effect transistor M1, sponge the output current of operational transconductance amplifier OTA, make the maximum output voltage of clamping down on operational transconductance amplifier OTA be stabilized in clamper high voltage upperClamp; The second operational amplifier OP2 is used for clamping down on the minimum output voltage of operational transconductance amplifier OTA, when the output voltage COMP that clamps down on operational transconductance amplifier OTA descends near clamper low-voltage lowerClamp, the second operational amplifier OP2 controls the conducting of the second field effect transistor M2, discharge certain electric current and compensate the electric current that operational transconductance amplifier OTA absorbs, make the minimum output voltage of operational transconductance amplifier OTA be stabilized in clamper low-voltage lowerClamp.
Figure 6 shows that another voltage clamp circuit, comprise the 5th field effect transistor M5, the 6th field effect transistor M6, the 3rd field effect transistor M3, the 4th field effect transistor M4, the 6th field effect transistor M6 grid and drain terminal short circuit, by fixed bias current I_biasl biasing, its source termination one is clamper low-voltage lowerClamp fixedly; The grid short circuit of the 5th field effect transistor M5 and the 6th field effect transistor M6, its drain terminal connects power supply, source termination operational transconductance amplifier OTA output; The grid of the 3rd field effect transistor M3 and drain terminal short circuit are setovered by a constant-current bias I_bias2, and its source termination one is clamper high voltage upperClamp fixedly; The grid short circuit of the 4th field effect transistor M4 and the 3rd field effect transistor M3, its source termination operational transconductance amplifier OTA output, drain terminal ground connection.
The 5th field effect transistor M5 and the 6th field effect transistor M6 are used for clamping down on the minimum output voltage of operational transconductance amplifier OTA among Fig. 6, in the time of near operational transconductance amplifier OTA output end voltage COMP is reduced to clamper low-voltage lowerClamp, the 5th field effect transistor M5 can increase and conducting because of source end and grid voltage, and the beginning output current compensates the electric current of operational transconductance amplifier OTA absorption and operational transconductance amplifier OTA output end voltage COMP is stabilized near the clamper low-voltage lowerClamp.The maximum output voltage that the 3rd field effect transistor M3 and the 4th field effect transistor M4 are used for clamping down on operational transconductance amplifier OTA among Fig. 6, in the output end voltage COMP of operational transconductance amplifier OTA uphill process, the VGS of the 4th field effect transistor M4 (gate source voltage of metal-oxide-semiconductor) can increase, the 4th field effect transistor M4 meeting conducting when the output end voltage COMP of operational transconductance amplifier OTA rises near clamper high voltage upperClamp, and beginning to absorb certain electric current, the output end voltage COMP of operational transconductance amplifier OTA is stabilized near the clamper high voltage upperClampl the most at last.
In the voltage clamp circuit that Fig. 5 and Fig. 6 provide,, can substitute corresponding field effect transistor with BJT and realize the voltage clamp function based on identical operation principle.
Fig. 3 is the change procedure of each signal in the switching power circuit at present commonly used shown in Figure 1. the output end voltage COMP voltage as operational transconductance amplifier OTA needs rising edge lag time T by the minimum minimum voltage OSC_valley that is elevated to the ramp signal OSC_ramp of oscillator generation as we can see from the figure
LRDuring this period of time, the duty ratio of pulse-width modulation square-wave signal PWMO immobilizes, and is the maximum duty cycle state, has too much electric charge in during this period of time to be charged in the output capacitance.Be reduced to the process need trailing edge lag time T of the ceiling voltage OSC_peak of the ramp signal OSC_ramp that oscillator produces from maximum output voltage at the output end voltage COMP of operational transconductance amplifier OTA
LF, during this period of time the duty ratio of pulse-width modulation square-wave signal PWMO is fixed as the lowest duty cycle state, does not have electric charge to be charged in the output capacitance during this period of time, and it is very big to cause output voltage to reduce.From Fig. 3, also can see, if the supply voltage VDD change of operational transconductance amplifier can cause trailing edge lag time T
LFVery big changing value is arranged, in full voltage range, cause the instability of pulse width modulator output voltage easily, bring the difficulty of compensation.
Behind the voltage clamp circuit of Fig. 4 for employing intensifier circuit transient response, the situation of change of each point voltage.Rising edge lag time T as we can see from the figure
LRWith trailing edge lag time T
LFTwo times obviously reduce, and like this as long as feedback voltage FB one changes, pulse width modulator can be determined the duty ratio of output according to variable quantity at once, improves the response speed of circuit.Simultaneously because clamper low-voltage lowerClamp and clamper high voltage upperClamp are fixed values, therefore can not exist operational transconductance amplifier OTA supply voltage can influence the situation of circuit response, make switching power circuit more stable in whole operating voltage range, can simplify the design of compensating circuit.
Above embodiment is that example is analyzed with the pulse-width modulation, as shown in Figure 7, also can adopt identical control method theory to improve the control circuit transient response speed for the pulse frequency modulation control circuit.In the pulse frequency modulation control circuit, the operational transconductance amplifier output end voltage need be clamped down on being a bit larger tham the voltage that frequency controller can linear change, make modulation circuit just can realize highest frequency work and low-limit frequency work.
More than analyze for voltage mode control, also can adopt same circuit to strengthen the transient response of control circuit for the current control mode circuit, as shown in Figure 8, adopt multi-input comparator as pulse width modulator, the multi-input comparator in-phase input end connects the error amplifier output, multi-input comparator one inverting input connects the oscillator sawtooth signal, and another inverting input connects the inductor current feedback signal.The output end voltage of operational transconductance amplifier OTA is limited near the dynamic range of multi-input comparator, make modulator just can realize maximum output duty cycle and minimum output duty cycle, reduce circuit and enter the time of operate as normal from maximum or minimum duty cycle, thus the transient response of intensifier circuit.
Claims (10)
1, a kind of switching power circuit comprises error amplifier, modulator, building-out capacitor, and the same modulator of error amplifier output, building-out capacitor link to each other, and it is characterized in that, also comprise voltage clamp circuit, are connected in the error amplifier output.
2, switching power circuit according to claim 1 is characterized in that, described modulator is the pulse frequency modulation device.
3, switching power circuit according to claim 1 is characterized in that, described modulator is a pulse width modulator.
4, switching power circuit according to claim 3 is characterized in that, described pulse width modulator is voltage-type control.
5, switching power circuit according to claim 4 is characterized in that, described pulse width modulator is a comparator, and the comparator inverting input connects the error amplifier output, and the comparator normal phase input end connects ramp signal.
6, switching power circuit according to claim 5 is characterized in that, ramp signal is sawtooth waveforms or triangular wave.
7, switching power circuit according to claim 3 is characterized in that, described pulse width modulator is current type control.
8, switching power circuit according to claim 7, it is characterized in that, described pulse width modulator is a multi-input comparator, the multi-input comparator in-phase input end connects the error amplifier output, multi-input comparator one inverting input connects the oscillator sawtooth signal, and another inverting input connects the inductor current feedback signal.
9, according to each described switching power circuit in the claim 1 to 8, it is characterized in that, voltage clamp circuit comprises first operational amplifier, second operational amplifier, first field effect transistor, second field effect transistor, the normal phase input end of first operational amplifier connects a fixing clamper high voltage, inverting input connects the error amplifier output, output termination first fet gate, the first field effect transistor source end and drain terminal connect error amplifier output and ground respectively; The normal phase input end of second operational amplifier connects a fixing clamper low-voltage, and inverting input connects the error amplifier output, output termination second fet gate, and the second field effect transistor source end and drain terminal connect error amplifier output and DC power supply respectively.
10, according to each described switching power circuit in the claim 1 to 8, it is characterized in that, voltage clamp circuit comprises the 5th field effect transistor, the 6th field effect transistor, the 3rd field effect transistor, the 4th field effect transistor, the 6th fet gate and drain terminal short circuit, by fixed bias current biasing, its source termination one is the clamper low-voltage source fixedly; The grid short circuit of the 5th field effect transistor and the 6th field effect transistor, its drain terminal connects power supply, source termination error amplifier output; The grid of the 3rd field effect transistor and drain terminal short circuit are setovered by a constant current, and its source termination one is the clamper high voltage source fixedly; The grid short circuit of the 4th field effect transistor and the 3rd field effect transistor, its source termination error amplifier output, drain terminal ground connection.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNA2007100421195A CN101330261A (en) | 2007-06-18 | 2007-06-18 | Switch power circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNA2007100421195A CN101330261A (en) | 2007-06-18 | 2007-06-18 | Switch power circuit |
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| CN101330261A true CN101330261A (en) | 2008-12-24 |
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| CNA2007100421195A Pending CN101330261A (en) | 2007-06-18 | 2007-06-18 | Switch power circuit |
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Cited By (17)
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| CN101841240A (en) * | 2010-04-12 | 2010-09-22 | 无锡中星微电子有限公司 | Power supply converter and error amplifier |
| CN101882875A (en) * | 2010-04-13 | 2010-11-10 | 矽创电子股份有限公司 | The power supply device of adjustable switching frequency |
| CN102545662A (en) * | 2011-01-03 | 2012-07-04 | 快捷韩国半导体有限公司 | Switch control circuit, converter using the same, and switch control method |
| CN101989330B (en) * | 2009-08-07 | 2013-01-09 | 上海华虹Nec电子有限公司 | High-frequency radio frequency identification device (RFID) tag circuit and chip |
| CN103051177A (en) * | 2012-12-20 | 2013-04-17 | 矽力杰半导体技术(杭州)有限公司 | Quick response control circuit and control method thereof |
| CN105187022A (en) * | 2015-09-07 | 2015-12-23 | 重庆西南集成电路设计有限责任公司 | Error amplifier, transconductance amplifier and gain amplifier for composing DC-DC converter |
| CN105337500A (en) * | 2014-06-27 | 2016-02-17 | 意法半导体研发(深圳)有限公司 | Power converter and method for adjusting linear transient response of power converter |
| CN103986324B (en) * | 2009-10-28 | 2016-08-17 | 立锜科技股份有限公司 | The control circuit of buck-boost power converter and method |
| CN106919217A (en) * | 2017-03-27 | 2017-07-04 | 上海华力微电子有限公司 | A kind of clamp voltage circuit |
| CN107453588A (en) * | 2017-07-25 | 2017-12-08 | 杰华特微电子（杭州）有限公司 | Regulating error circuit and method and power converting circuit |
| CN108092502A (en) * | 2017-12-27 | 2018-05-29 | 西安电子科技大学 | The wide loading range adjusting and voltage-reduction switch capacitor DC-DC converter of double mode |
| CN108418410A (en) * | 2018-03-16 | 2018-08-17 | 上海艾为电子技术股份有限公司 | Soft starting circuit with output voltage feedback |
| CN111865314A (en) * | 2020-07-03 | 2020-10-30 | 同济大学 | Analog front end circuit of analog-to-digital converter |
| CN112636758A (en) * | 2020-12-22 | 2021-04-09 | 电子科技大学 | Sampling hold circuit used in snapshot type readout circuit |
| CN112769403A (en) * | 2020-12-30 | 2021-05-07 | 深圳芯智汇科技有限公司 | Error amplifier, DC converter, and electronic device |
| CN114095002A (en) * | 2021-09-28 | 2022-02-25 | 荣湃半导体（上海）有限公司 | Voltage clamping circuit |
| CN114649935A (en) * | 2020-12-17 | 2022-06-21 | 圣邦微电子（北京）股份有限公司 | Switch converter and control circuit thereof |
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2007
- 2007-06-18 CN CNA2007100421195A patent/CN101330261A/en active Pending
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| CN101989330B (en) * | 2009-08-07 | 2013-01-09 | 上海华虹Nec电子有限公司 | High-frequency radio frequency identification device (RFID) tag circuit and chip |
| CN103986324B (en) * | 2009-10-28 | 2016-08-17 | 立锜科技股份有限公司 | The control circuit of buck-boost power converter and method |
| CN101841240A (en) * | 2010-04-12 | 2010-09-22 | 无锡中星微电子有限公司 | Power supply converter and error amplifier |
| WO2011127688A1 (en) * | 2010-04-12 | 2011-10-20 | 无锡中星微电子有限公司 | Power-switching device and error amplifier |
| CN101841240B (en) * | 2010-04-12 | 2012-08-29 | 无锡中星微电子有限公司 | Power supply converter and error amplifier |
| CN101882875A (en) * | 2010-04-13 | 2010-11-10 | 矽创电子股份有限公司 | The power supply device of adjustable switching frequency |
| CN102545662A (en) * | 2011-01-03 | 2012-07-04 | 快捷韩国半导体有限公司 | Switch control circuit, converter using the same, and switch control method |
| CN103051177A (en) * | 2012-12-20 | 2013-04-17 | 矽力杰半导体技术(杭州)有限公司 | Quick response control circuit and control method thereof |
| CN103051177B (en) * | 2012-12-20 | 2015-03-11 | 矽力杰半导体技术(杭州)有限公司 | Quick response control circuit and control method thereof |
| CN105337500B (en) * | 2014-06-27 | 2018-05-04 | 意法半导体研发(深圳)有限公司 | Power inverter and the method responded for adjusting the linear transient of power inverter |
| CN105337500A (en) * | 2014-06-27 | 2016-02-17 | 意法半导体研发(深圳)有限公司 | Power converter and method for adjusting linear transient response of power converter |
| CN105187022B (en) * | 2015-09-07 | 2017-11-10 | 重庆西南集成电路设计有限责任公司 | Form the error amplifier and trsanscondutance amplifier and gain amplifier of DC DC converters |
| CN105187022A (en) * | 2015-09-07 | 2015-12-23 | 重庆西南集成电路设计有限责任公司 | Error amplifier, transconductance amplifier and gain amplifier for composing DC-DC converter |
| CN106919217B (en) * | 2017-03-27 | 2019-03-26 | 上海华力微电子有限公司 | A kind of clamp voltage circuit |
| CN106919217A (en) * | 2017-03-27 | 2017-07-04 | 上海华力微电子有限公司 | A kind of clamp voltage circuit |
| CN107453588A (en) * | 2017-07-25 | 2017-12-08 | 杰华特微电子（杭州）有限公司 | Regulating error circuit and method and power converting circuit |
| CN107453588B (en) * | 2017-07-25 | 2023-08-29 | 杰华特微电子股份有限公司 | Error adjusting circuit and method and power supply conversion circuit |
| CN108092502B (en) * | 2017-12-27 | 2019-11-22 | 西安电子科技大学 | The wide loading range adjusting and voltage-reduction switch capacitor DC-DC converter of double mode |
| CN108092502A (en) * | 2017-12-27 | 2018-05-29 | 西安电子科技大学 | The wide loading range adjusting and voltage-reduction switch capacitor DC-DC converter of double mode |
| CN108418410A (en) * | 2018-03-16 | 2018-08-17 | 上海艾为电子技术股份有限公司 | Soft starting circuit with output voltage feedback |
| CN111865314A (en) * | 2020-07-03 | 2020-10-30 | 同济大学 | Analog front end circuit of analog-to-digital converter |
| CN114649935A (en) * | 2020-12-17 | 2022-06-21 | 圣邦微电子（北京）股份有限公司 | Switch converter and control circuit thereof |
| CN112636758A (en) * | 2020-12-22 | 2021-04-09 | 电子科技大学 | Sampling hold circuit used in snapshot type readout circuit |
| CN112769403A (en) * | 2020-12-30 | 2021-05-07 | 深圳芯智汇科技有限公司 | Error amplifier, DC converter, and electronic device |
| CN114095002A (en) * | 2021-09-28 | 2022-02-25 | 荣湃半导体（上海）有限公司 | Voltage clamping circuit |
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