CN101154884A - Current mode width pulse modulation booster circuit and its feedback signal sensing method - Google Patents
Current mode width pulse modulation booster circuit and its feedback signal sensing method Download PDFInfo
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- CN101154884A CN101154884A CNA2006101524688A CN200610152468A CN101154884A CN 101154884 A CN101154884 A CN 101154884A CN A2006101524688 A CNA2006101524688 A CN A2006101524688A CN 200610152468 A CN200610152468 A CN 200610152468A CN 101154884 A CN101154884 A CN 101154884A
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Abstract
The invention relates to a method of sensing feedback signal, which includes the following steps: (a)a pulse-width modulation signal provided with one cycle is provided; (b)during the continuous period of the pulse cycle, a capacitor is charged by a current supply to form an equivalent slope compensation ramp signal; (c)during the continuous period of the pulse cycle, an inductance current flowing through a boost inductance is put to flow through an equivalent resistance so as to form an equivalent inductance current signal; (d) a feed back signal is formed by taking advantage of the coupling characteristic of the capacitor and matching with the equivalent slope compensation ramp signal and the equivalent inductance current signal.
Description
Technical field
The present invention relates to a kind of current mode width pulse modulation booster circuit (current mode pulse width modulationboost circuit) and feedback signal sensing method thereof, relate to a kind of current mode width pulse modulation booster circuit and feedback signal sensing method thereof in particular with direct sensing inductive current (inductorcurrent) and slope-compensation ramp signal (slope compensation ramp signal) function.
Background technology
Fig. 1 is a conventional current mode width pulse modulation booster circuit 10, and it comprises a boosting unit 11, a bleeder circuit 19, an error amplifier 12, a comparator 13, an inductive current generator (inductor current generator) 14, one slope-compensation slope generator (slope compensation ramp generator) 15, one oscillator 16, a pulsewidth generator 17 and a buffer (buffer) 18.One voltage V
INBoost to produce a higher VD V by described boosting unit 11
OUTDescribed boosting unit 11 comprises an input capacitance C1, a boost inductance L, a MOS transistor T, a rectifier diode D and an output capacitance C2.Described input capacitance C1 is in order to filter described voltage V
INRipple voltage (ripple voltage).When described MOS transistor T is in conducting state, described rectifier diode D is a reverse bias, and this moment, the electric current described boost inductance L that will forward flow through and rose the voltage of described boost inductance L; Yet electric current be not transient flow through described boost inductance L, increase but be linear, therefore can set up an electromagnetic field.At this moment, when described MOS transistor T was in conducting state, the electric current of output was provided by described output capacitance C2 fully.When described MOS transistor T was in cut-off state, described boost inductance L is stored energy again, and therefore the described electromagnetic field of being stored among the described boost inductance L will be released; At this moment, polarity of voltage on the described boost inductance L will be inverted, make described boost inductance L discharge its energy of storing, make described rectifier diode D connect the end of described boost inductance L (being node N3) simultaneously and obtain than described voltage V to described output capacitance C2
INAlso high voltage, this strand energy provides a load current, and is simultaneously described output capacitance C2 charging again.Described bleeder circuit 19 is made of two series resistance R1 and R2.One branch pressure voltage V
F1Then take out, deliver to a described error amplifier 12 and a reference voltage V by a node N2 who connects described resistance R 1 and R2
REFCompare, to produce an error signal EO.Subsequently, described error signal EO will be by a described comparator 13 and a feedback signal V
SUMCompare.The output of described comparator 13 (is V
F2) then together be input to described pulsewidth generator 17 with an oscillator signal S1 from described oscillator 16.The drive signal S that described pulsewidth generator 17 is produced
DRA gate control signal S who produces through described buffer 18 again
G(that is, adjust described drive signal S with the time of adjusting described MOS transistor T conducting
DRPulse duration (pulse duration)), and then control described VD V
OUT
Described inductive current generator 14 receives a voltage signal V from described node N3
SEN, after mechanism (for example through a resistance or a transduction amplifier (transconductance the amplifier)) effect of a voltage transitions electric current of its inside and generate an inductive current I who flows through described boost inductance L
SENFig. 2 (a) is to difference acquisition point N31, N32 and the N33 of voltage signal VSEN described in 2 (c) illustration routine techniques.The described voltage signal V of Fig. 2 (a)
SENThough both are accurate than other for the acquisition mode, yet than power consumption.The described voltage signal V of Fig. 2 (b) and 2 (c)
SENThe acquisition mode is compared the advantage with lossless (lossless) with Fig. 2 (a), yet but has the problem of low accuracy and coupling respectively.And described voltage signal V
SENAfter the effect of described inductive current generator 14, described inductive current I
SENTo be easy to cause distortion (distortion).In addition, the purpose of described slope-compensation slope generator 15 is for solving in current mode converter (current mode converters), when it is operated down and described drive signal S in continuous conduction mode (continuous conduction)
DRWork period greater than 50% o'clock, generation open loop instability (open-loop instability), subharmonic oscillation (sub-harmonicoscillation) and to the too sensitive problems such as (noise sensitivity) of noise.Described slope-compensation slope generator 15 receives an oscillator signal S2 from described oscillator 16, again after mechanism (a for example transduction amplifier) effect of a voltage transitions electric current of its inside and generate a slope-compensation ramp signal I
SLOSimilarly, described slope-compensation ramp signal l
SLOAfter the effect of described slope-compensation slope generator 15, be easy to cause distortion.At last, described inductive current I
SENWith described slope-compensation ramp signal I
SLOThe resistance R of flowing through
f, produce described feedback signal V at a node N1 place
SUM
Summary of the invention
One aspect of the present invention provides a kind of current mode width pulse modulation booster circuit, by a feedback signal generation unit that comprises a current source and an electric capacity, directly measure a described current mode width pulse modulation booster circuit inductive current inside and an equivalent slope-compensation ramp signal (equivalent slope compensation ramp signal), forming a feedback signal and to adjust a direct current output voltage, and the distorted signals that is caused when reducing inductance measuring electric current in the routine techniques and producing the slope-compensation ramp signal.
Another aspect of the present invention provides a kind of feedback signal sensing method that is applied in the current mode width pulse modulation booster circuit, by the inductive current of the boost inductance of flowing through in the described booster circuit of direct measurement with by a current source slope characteristics formed one equivalent slope-compensation ramp signal that charging is had to an electric capacity, to produce a feedback signal and to adjust a direct current output voltage.
The present invention discloses a kind of current mode width pulse modulation booster circuit, and it comprises a boosting unit, a bleeder circuit, an error amplifier, a comparator, a pulsewidth generator and a feedback signal generation unit.Described boosting unit comprises a boost inductance and a switch, and described boosting unit boosts a voltage to produce a direct current output voltage.Described bleeder circuit utilizes described VD to produce a branch pressure voltage.Described error amplifier comparison one reference voltage and described branch pressure voltage are to produce an error signal.A more described error signal of described comparator and a feedback signal are to produce one first signal.Described pulsewidth generator receive described first signal and from the secondary signal of an oscillator to produce one the 3rd signal, wherein said the 3rd signal is in order to control described switch.Described feedback signal generation unit and the coupling of described boosting unit are to produce described feedback signal, and wherein said feedback signal comprises the equivalent inductance current signal and an equivalent slope-compensation ramp signal of the described boost inductance of flowing through.
The present invention discloses in addition a kind of feedback signal sensing method that is applied to a current mode width pulse modulation booster circuit, and it comprises following steps: a pulse-width signal that has one-period (period) (a) is provided; (b) in the pulse duration in described cycle (pulse duration), one electric capacity is charged, to form an equivalent slope-compensation ramp signal by a current source; (c) in the described pulse duration, make an inductive current of the flowing through a boost inductance equivalent resistance of flowing through, to form an equivalent inductor current signal; (d) utilize the coupled characteristic of described electric capacity, and cooperate described equivalent slope-compensation ramp signal and described equivalent inductance current signal to form a feedback signal.In one embodiment of the invention, described feedback signal is taken from the contact of described current source and described electric capacity.
Current mode width pulse modulation booster circuit of the present invention is because of direct inductance measuring electric current and utilize described feedback signal generation unit directly to produce described equivalent slope-compensation ramp signal, and do not relate to the use of voltage transitions electric current mechanism (voltage-to-current transfer structure), therefore compare with routine techniques, the present invention has the following advantages: (1) reduces the distortion of feedback signal; (2) because directly measure and the generation signal, so have preferred reaction rate; (3) can exempt the problem of opening loop stability in the routine techniques.
Description of drawings
One current mode width pulse modulation booster circuit of Fig. 1 routine;
The difference acquisition point of Fig. 2 (a)～2 (c) illustration routine techniques voltage signal; And
The current mode width pulse modulation booster circuit of Fig. 3 one embodiment of the invention.
Embodiment
Fig. 3 is the current mode width pulse modulation booster circuit 20 of one embodiment of the invention, and it comprises a boosting unit 21, a bleeder circuit 29, an error amplifier 22, a comparator 23, a pulsewidth generator 27, a buffer 28 and a feedback signal generation unit 24.Described boosting unit 21 comprises rectifier diode D ', that a boost inductance L ', a MOS transistor T ', one be connected with the contact P1 of described MOS transistor T ' with described boost inductance L ' in order to filter described voltage V
INThe input capacitance C3 and of ripple voltage be connected output capacitance C5 between a described rectifier diode D ' and the earth terminal, wherein said output capacitance C5 is in order to produce a direct current output voltage V
OUTDescribed bleeder circuit 29 utilizes described VD V
OUTProduce a branch pressure voltage V
F3Described bleeder circuit 29 comprises first resistance R 3 and that is connected with described rectifier diode D ' and is connected second resistance R 4 between described first resistance R 3 and the described earth terminal, wherein said branch pressure voltage V
F3Take from the node P3 of described first resistance R 3 of a connection and described second resistance R 4.Described error amplifier 22 is a reference voltage V relatively
REFWith described branch pressure voltage V
F3To produce an error signal E ' O.Described comparator 23 more described error signal E ' O and a feedback signal V '
SUMTo produce a signal V
F4Described pulsewidth generator 27 receives described signal V
F4With a signal S from an oscillator 26
OSCTo produce a signal S '
DR, wherein said signal S '
DRIn order to control described MOS transistor T '.Described buffer 28 ' for what choose wantonly, it promotes described signal S '
DRDriving force, to form a gate control signal S '
GTo control described MOS transistor T '.Described feedback signal generation unit 24 is coupled to produce described feedback signal V ' with described boosting unit 21
SUM, wherein said feedback signal V '
SUMThe equivalent inductance current signal (not shown) and the equivalent slope-compensation ramp signal (not shown) that comprise the described boost inductance L ' that flows through.Described feedback signal generation unit 24 comprises a capacitor C 4 and a current source I who connects with described capacitor C 4
sOne end of described capacitor C 4 and described boost inductance L ' and the contact P1 of described MOS transistor T ' are coupled.Another end points coupling of described current source Is and described capacitor C 4.
The current mode width pulse modulation booster circuit 20 of the described embodiment of Fig. 3 and the feedback signal V ' of the described current mode width pulse modulation booster circuit 10 of Fig. 1
SUMThe production method difference, below will describe feedback signal V ' of the present invention in detail
SUMMethod for sensing.
When described MOS transistor T ' conducting, by described voltage V
INThe inductive current IL ' of the generation and the described boost inductance L ' that flows through will flow to earth terminal by the MOS transistor T ' of described conducting.Described inductive current IL ' is in the formed current potential V ' of node P1
SENCan be by drawing with following formula (1),
V′
SEN＝V
IN×DTs×Rds/L (1)
Wherein DTs represents described the 4th signal S '
DRPulse duration (that is, the time of described MOS transistor T ' conducting), the inductance value that resistance when Rds represents described MOS transistor T ' conducting and L represent described boost inductance L '.Because described current potential V '
SENTherefore the message that contains described inductive current IL ' is also referred to as the equivalent inductance current signal, itself and described voltage V
IN, the resistance value Rds when described boost inductance L ', described MOS transistor T ' conducting and described pulsewidth generator a work period (duty cycle) relevant.In addition, described current source I
sWhen described MOS transistor T ' conducting,, therefore will between node P1 and P2, set up a potential difference V to described capacitor C 4 chargings
SLO, it can be by drawing with following formula (2),
V
SLO＝I
s×DTs/C (2)
Wherein DTs represents described the 4th signal S '
DRPulse duration (that is, the time of described MOS transistor T ' conducting), C represents the capacitance of described capacitor C 4.Because described potential difference V
SLO(that is its slope characteristics that is represented is similar to the 3rd signal S that described oscillator 26 is produced when, described capacitor C 4 being charged to contain the relevant message of described slope-compensation ramp signal
OSC), therefore be also referred to as equivalent slope-compensation ramp signal, itself and described current source I
s, described capacitor C 4 and described pulsewidth generator 27 the described work period relevant.Therefore utilize the coupled characteristic of described capacitor C 4, by the feedback signal V ' of node P2 taking-up
SUMBe described equivalent inductance current signal and equivalent slope-compensation ramp signal sum.That is to say,
V′
SUM＝V′
SEN+V
SLO＝V
IN×DTs×Rds/L+I
s×DTs/C
＝(V
tN×Rds/L+I
s/C)×DTs (3)
(V in its Chinese style (3)
IN* Rds/L+I
s/ C) have a characteristic of fixed slope.
By above explanation as can be known, current mode width pulse modulation booster circuit of the present invention and feedback signal sensing method thereof are because by a feedback signal generation unit that comprises a current source and an electric capacity, directly measure described current mode width pulse modulation booster circuit inductive current inside and be directly changed into an equivalent inductor current signal; Simultaneously, utilize described current source to the charging of described electric capacity and directly produce an equivalent slope-compensation ramp signal with slope characteristics, and directly form a feedback signal at the tie point of described current source and described electric capacity.Therefore the present invention compares with routine techniques and has the distortion that (1) reduces feedback signal; (2) has preferred reaction rate; (3) avoid out the advantage of loop stability problem.
Technology contents of the present invention and technical characterstic disclose as above, yet the those skilled in the art still may make various the substituting and revising of spirit of the present invention that do not break away from based on teaching of the present invention and announcement.Therefore, protection scope of the present invention should be not limited to the content that embodiment discloses, and should comprise various of the present invention the substituting and modification that do not break away from, and is contained by appended claims.
Claims (18)
1. feedback signal sensing method, it is applied to a current mode width pulse modulation booster circuit, it is characterized in that comprising following steps:
(a) provide a pulse-width signal with one-period;
(b) in a pulse duration in described cycle, one electric capacity is charged, to form an equivalent slope-compensation ramp signal by a current source;
(c) in the described pulse duration, make an inductive current of the flowing through a boost inductance equivalent resistance of flowing through, to form an equivalent inductor current signal; With
(d) utilize the coupled characteristic of described electric capacity, and cooperate described equivalent slope-compensation ramp signal and described equivalent inductance current signal to form a feedback signal.
2. feedback signal sensing method according to claim 1 is characterized in that described pulse-width signal is positioned at described current mode width pulse modulation booster circuit switch inside in order to conducting one in the described pulse duration.
3. feedback signal sensing method according to claim 2 is characterized in that described switch is a MOS transistor.
4. feedback signal sensing method according to claim 1 is characterized in that described equivalent slope-compensation ramp signal is a voltage signal and is defined by following formula:
I
s×DT
s/C
I wherein
sThe electric current of representing described current source, DT
sRepresent the described pulse duration, C represents the capacitance of described electric capacity.
5. feedback signal sensing method according to claim 1 is characterized in that described equivalent slope-compensation ramp signal is a potential difference across described electric capacity two ends.
6. feedback signal sensing method according to claim 1 is characterized in that described equivalent resistance is one to be in the MOS transistor of conducting state.
7. feedback signal sensing method according to claim 1 is characterized in that described equivalent inductance current signal is a voltage signal and is defined by following formula:
V
IN×DT
s×Rds/L
V wherein
INBe the voltage of the voltage source of the described inductive current of a generation, DT
sRepresent the described pulse duration, Rds represents described equivalent resistance, and L represents the inductance value of described boost inductance.
8. feedback signal sensing method according to claim 1 is characterized in that described feedback signal is described equivalent slope-compensation ramp signal and described equivalent inductance current signal sum.
9. feedback signal sensing method according to claim 1 is characterized in that described feedback signal takes from the contact of described current source and described electric capacity.
10. current mode width pulse modulation booster circuit is characterized in that comprising:
One boosting unit comprises a boost inductance and a switch, and described booster circuit boosts a voltage to produce a direct current output voltage;
One bleeder circuit, it utilizes described VD to produce a branch pressure voltage;
One error amplifier, its comparison one reference voltage and described branch pressure voltage are to produce an error signal;
One comparator, its a more described error signal and a feedback signal are to produce one first signal;
One pulsewidth generator, its receive described first signal and from the secondary signal of an oscillator to produce one the 3rd signal, wherein said the 3rd signal is in order to control described switch; With
One feedback signal generation unit, itself and the coupling of described boosting unit are to produce described feedback signal, and wherein said feedback signal comprises the equivalent inductance current signal and an equivalent slope-compensation ramp signal of the described boost inductance of flowing through.
11. current mode width pulse modulation booster circuit according to claim 10 is characterized in that described boosting unit further comprises:
One rectifier diode, it is connected with the contact of described switch with described boost inductance; With
One output capacitance, it is connected between a described diode and the earth terminal to produce described VD.
12., it is characterized in that described bleeder circuit comprises according to the described current mode width pulse modulation booster circuit of claim 11:
One first resistance, it is connected with described rectifier diode; With
One second resistance, it is connected between described first resistance and the described earth terminal, and wherein said branch pressure voltage is taken from the contact of described first resistance and described second resistance.
13. current mode width pulse modulation booster circuit according to claim 10, it is characterized in that further comprising a buffer, described buffer is connected with the output of described pulsewidth generator, is used to promote the driving force of described the 3rd signal to control described switch.
14. current mode width pulse modulation booster circuit according to claim 10 is characterized in that described feedback signal generation unit comprises:
One electric capacity, the contact coupling of one end and described boost inductance and described switch; With
One current source, another end points coupling of itself and described electric capacity.
15. current mode width pulse modulation booster circuit according to claim 14 is characterized in that described equivalent slope-compensation ramp signal is produced described electric capacity charging when the described switch conduction by described current source.
16. current mode width pulse modulation booster circuit according to claim 14 is characterized in that described equivalent slope-compensation ramp signal is relevant with a work period of described current source, described electric capacity and described pulsewidth generator.
17. current mode width pulse modulation booster circuit according to claim 10 is characterized in that described equivalent inductance current signal is that a voltage signal and the resistance value during with described switch conduction are relevant.
18. current mode width pulse modulation booster circuit according to claim 10, it is characterized in that described equivalent inductance current signal is a voltage signal, the work period of its resistance value during with described voltage, described boost inductance, described switch conduction and described pulsewidth generator is relevant.
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|---|---|---|---|
| CNA2006101524688A CN101154884A (en) | 2006-09-29 | 2006-09-29 | Current mode width pulse modulation booster circuit and its feedback signal sensing method |
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Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101339209B (en) * | 2008-08-08 | 2012-02-29 | 欣旺达电子股份有限公司 | Method for on-load detection in boosted circuit using impulse width |
| CN103179323A (en) * | 2011-12-26 | 2013-06-26 | 广明光电股份有限公司 | Digital signal transmission receiving device and method |
| CN101534094B (en) * | 2009-04-14 | 2013-11-06 | 无锡中星微电子有限公司 | Compensating circuit |
| CN112583078A (en) * | 2020-12-17 | 2021-03-30 | 西安稳先半导体科技有限责任公司 | Battery pack, battery protection chip and electronic product |
| CN112615072A (en) * | 2020-12-17 | 2021-04-06 | 西安稳先半导体科技有限责任公司 | Battery pack, battery protection chip and electronic product |
| CN114333729A (en) * | 2021-12-30 | 2022-04-12 | 昆山龙腾光电股份有限公司 | Liquid crystal display module, display control circuit and method thereof, and liquid crystal display device |
| WO2022127671A1 (en) * | 2020-12-17 | 2022-06-23 | 西安稳先半导体科技有限责任公司 | Battery assembly, battery protection chip, and electronic product |
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2006
- 2006-09-29 CN CNA2006101524688A patent/CN101154884A/en active Pending
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101339209B (en) * | 2008-08-08 | 2012-02-29 | 欣旺达电子股份有限公司 | Method for on-load detection in boosted circuit using impulse width |
| CN101534094B (en) * | 2009-04-14 | 2013-11-06 | 无锡中星微电子有限公司 | Compensating circuit |
| CN103179323A (en) * | 2011-12-26 | 2013-06-26 | 广明光电股份有限公司 | Digital signal transmission receiving device and method |
| CN112583078A (en) * | 2020-12-17 | 2021-03-30 | 西安稳先半导体科技有限责任公司 | Battery pack, battery protection chip and electronic product |
| CN112615072A (en) * | 2020-12-17 | 2021-04-06 | 西安稳先半导体科技有限责任公司 | Battery pack, battery protection chip and electronic product |
| WO2022127671A1 (en) * | 2020-12-17 | 2022-06-23 | 西安稳先半导体科技有限责任公司 | Battery assembly, battery protection chip, and electronic product |
| CN114333729A (en) * | 2021-12-30 | 2022-04-12 | 昆山龙腾光电股份有限公司 | Liquid crystal display module, display control circuit and method thereof, and liquid crystal display device |
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