CN101001021A - Linear charger - Google Patents

Linear charger Download PDF

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Publication number
CN101001021A
CN101001021A CN 200710002183 CN200710002183A CN101001021A CN 101001021 A CN101001021 A CN 101001021A CN 200710002183 CN200710002183 CN 200710002183 CN 200710002183 A CN200710002183 A CN 200710002183A CN 101001021 A CN101001021 A CN 101001021A
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current
metal oxide
oxide semiconductor
semiconductor transistor
battery module
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CN 200710002183
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CN100442629C (en
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刘智民
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Via Technologies Inc
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Via Technologies Inc
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Abstract

A linear charger includes a current generator, for charging a cell module ; a current detector, for outputing a sensing potential which corresponds to the current produced by the current generator; an operational amplifier, the output end of which is coupled with the control end of the current generator, and a multi-station selector. Under a predetermined current charge mode, a first reference potential and a sensing potential are respectively coupled with a first and second input end of the operational amplifier by the multi-station selector, to this end, the current generator can output a predetermined current. Under a predetermined voltage charge mode, a second reference potential and a potential of the cell module are respectively coupled with a first and second input end of the operational amplifier by the multi-station selector, to this end, the potential of the cell module is adjusted to a predetermined potential.

Description

Linear charger
Technical field
The invention relates to a kind of linear charger (linear battery charger).
Background technology
The operation of linear charger generally includes constant-current charge pattern (constant current chargemode) and constant-voltage charge pattern (constant voltage charge mode).When charging cell module, the linear-charging circuit at first can be with this constant-current charge pattern this battery module that charges, up to the current potential (V of this battery module Bat) reach a certain level after, just change with this constant-voltage charge pattern this battery module that charges.With 4.2 volts lithium batteries is example, and linear charger is at first with this constant-current charge pattern this lithium battery that charges.Treat that this lithium cell charging to 4.1 volt, this linear-charging circuit can switch to this constant-voltage charge pattern and continue current potential (V with this lithium battery Bat) charge to 4.2 volts.This constant-voltage charge pattern is to be used for avoiding overcharging this lithium battery, to prolong the useful life of this lithium battery.
Fig. 1 is a conventional linear charger 100.This conventional linear charger 100 has charging transistor gmp, in order to charging cell module 102.The running of this conventional linear charger 100 is as follows.Under the constant-current charge pattern, first switch SW 1Conducting and second switch SW 2Not conducting.The first operational amplifier OP 1, the second operational amplifier OP 2, transistor g Mnc, with this charging transistor g MpFormed loop can make the sensing resistor R that flows through SnsElectric current I maintain fixed value, its size is by coupling this second operational amplifier OP 2The first reference potential V Ref1Decision.Capacitor C cWith resistance R cForm this linear charger 100 needed frequency compensated circuit under this constant-current charge pattern.Under the constant-voltage charge pattern, this 1 not conducting of first switch SW and second switch SW 2Conducting.The 3rd operational amplifier OP 3, transistor g Mnv, with this charging transistor g MpFormed loop can make the current potential V of this battery module BatMaintain the second reference potential V Ref2Capacitor C zWith resistance R zForm this linear charger 100 needed frequency compensated circuit under this constant-voltage charge pattern.
Can proper operation under this constant-current charge pattern and this constant-voltage charge pattern in order to ensure this conventional linear charger 100, the operational amplifier OP that conventional linear charger 100 is adopted 1, OP 2, and OP 3Be necessary for the have low offset voltage accurate operational amplifier of (low offset).Therefore, the cost of conventional linear charger 100 is quite high.
In addition, the very big (capacitor C especially of the frequency compensated circuit of conventional linear charger 100 zWith resistance R z), will on this conventional linear charger 100, occupy bigger area.
Summary of the invention
The invention provides a kind of linear charger (linear battery charger) of novelty, not only significantly reduce the use amount of accurate operational amplifier, more significantly reduce the occupied area of its frequency compensated circuit.
Linear charger provided by the present invention comprises first current generator, current detector, first operational amplifier and multiplex's choice device.This first current generator produces first electric current, and couples battery module with this battery module that charges.This current detector couples this first current generator, in order to produce the sensing current potential corresponding with this first electric current.This first operational amplifier has first input end, second input and output.The output of this first operational amplifier couples the control end of this first current generator.Under the constant-current charge pattern, this multiplex's choice device can be coupled to first reference potential and this sensing current potential respectively first and second input of this first operational amplifier.It is the definite value electric current that this first operational amplifier can be kept this first electric current by this.Under the constant-voltage charge pattern, this multiplex's choice device can be coupled to the current potential of second reference potential and this battery module respectively first and second input of this first operational amplifier.This first operational amplifier can be adjusted the current potential of this battery module by this to the definite value current potential.
For above and other objects of the present invention, feature and advantage can be become apparent, cited below particularlyly go out preferred embodiment, and cooperate appended graphic elaborating.
Description of drawings
Fig. 1 is the embodiment of a conventional linear charger;
Fig. 2 is an embodiment of linear charger of the present invention;
Fig. 3 is another embodiment of linear charger of the present invention;
Fig. 4 is another embodiment of linear charger of the present invention;
Fig. 5 is another embodiment of linear charger of the present invention; And
Fig. 6 is another embodiment of linear charger of the present invention.
[main element label declaration]
100～conventional linear charger; 102～battery module;
104,106,108, the stitch contact of the chip of 110～conventional linear charger 100 part;
200～linear charger; 202～the first current generators;
204～current detector; 206～multiplex (MUX) choice device;
208～battery module;
300～linear charger; 302～voltage level control circuit;
400～linear charger; 402～frequency compensated circuit;
404～dividing point; 406～frequency compensator;
408～battery module; 410～multiplex (MUX) choice device;
500～linear charger;
C～variable capacitance; C1～first electric capacity;
C 2, C 21, C 22, C 2n～the second electric capacity;
C BatThe electric capacity of～battery module;
C c, C z～be used for frequency compensated electric capacity;
C L～load capacitance;
CMP, CMP 1, CMP 2, CMP n～comparator;
g Mp, g Mnc, g Mnv～transistor;
I 1With I 2～first and second electric current;
M 1, M 2, M 3～metal oxide semiconductor transistor;
Mux 1, mux 2～multiplexer;
OP 1, OP 2, OP 3～operational amplifier;
R 1, R 2～resistance; R BatThe resistance of～battery module;
R c, R z～be used for frequency compensated resistance;
R L～load resistance; R Sns～sensing resistor;
SW, SW 1, SW 2, SW n～switch;
V BatThe current potential of～battery module; V DD～power supply;
V g～the first metal oxide semiconductor transistor M 1Grid potential;
V Sns～sensing current potential;
V Ref1, V Ref2, V Ref3, V Ref31, V Ref32, V Ref3n～reference potential.
Embodiment
Fig. 2 is one embodiment of the invention.Linear charger 200 comprises first current generator 202, current detector 204, the first operational amplifier OP 1, and multiplex's choice device 206.This first current generator 202 couples battery module 208 with this battery module 208 that charges.The electric current that this first current generator is produced is first electric current I 1This current detector 204 couples this first current generator 202, and to should first electric current I 1Size output sensing current potential V SnsThis first operational amplifier OP 1, tool first input end (non-inverting input as shown in the figure), second input (inverting input as shown in the figure) and output.This first operational amplifier OP 1Output couple the control end of this first current generator 202, to control this first electric current I 1Size.Under the constant-current charge pattern, this multiplex's choice device 206 is with the first reference potential V Ref1And this sensing current potential V SnsBe coupled to this first operational amplifier OP respectively 1First and second input.Under the constant-voltage charge pattern, this multiplex's choice device 206 is with the second reference potential V Ref2And the current potential V of this battery module BatBe coupled to this first operational amplifier OP respectively 1First and second input.
In the embodiment shown in Figure 2, this first current generator 202 is the first metal oxide semiconductor transistor M 1, its drain electrode couples this battery module 208, and its grid couples this first operational amplifier OP 1Output as the control end of this first current generator 202.In addition, this current detector 204 comprises the second metal oxide semiconductor transistor M 2With sensing resistor R SnsThe grid of this second metal oxide semiconductor transistor M2 and this first metal oxide semiconductor transistor M 1Grid be coupled in together and this first and second metal oxide semiconductor transistor M 1With M 2Has identical grid source electrode pressure drop.Therefore, this second metal oxide semiconductor transistor M 2Second electric current I that is produced 2Can with this first electric current I 1Proportional relation, its size be by this first with this second metal oxide semiconductor transistor M 1With M 2Area ratio decision.This sensing resistor R SnsBe coupled to the second metal oxide semiconductor transistor M 2Drain electrode, in order to this second electric current I 2Convert this sensing current potential V to SnsIn another embodiment, this sensing resistor R SnsCan be variable resistor, in order to guarantee this second metal oxide semiconductor transistor M 2Be operable in the saturation region.
Consult Fig. 2, this multiplex's choice device 206 can be by two multiplexer mux 1With mux 2Form.Under this constant-current charge pattern, this multiplexer mux 1With this first reference potential V Ref1Import this first operational amplifier OP 1Inverting input, and this multiplexer mux 2With this sensing current potential V SnsImport this first operational amplifier OP 1Non-inverting input.This first electric current I 1When becoming big, this second electric current I 2Can become big thereupon, cause this sensing current potential V SnsRise.This first operational amplifier OP 1This sensing current potential V relatively SnsWith this first reference potential V Ref1After, its output end signal can promote this first metal oxide semiconductor transistor M 1Grid voltage V g, cause this first metal oxide semiconductor transistor M 1Grid source electrode pressure reduction diminish this first electric current I 1Down adjusted back original level.Under this constant-voltage charge pattern, this multiplexer mux 1With this second reference potential V Ref2Import this first operational amplifier OP 1Inverting input, and this multiplexer mux 2Current potential V with this battery module BatImport this first operational amplifier OP 1Non-inverting input.The current potential V of this battery module BatDo not reach this second reference potential V as yet Ref2The time, this first operational amplifier OP 1Can downgrade this first metal oxide semiconductor transistor M 1Grid voltage V g, cause this first electric current I 1 to become big, with this battery module 208 that charges to this second reference potential V Ref2
Can find that by embodiment shown in Figure 2 the present invention only needs accurate operational amplifier (the first operational amplifier OP of a low offset voltage (lowoffset) 1).Compare with conventional linear charger, the present invention significantly reduces the use amount of accurate operational amplifier.
Another advantage of the present invention is to reduce the stitch number of chip.Linear charger 200 with Fig. 2 is an example, and sensing resistor R is only arranged SnsBe connected on outward outside the chip, all the other elements all are incorporated into chip internal.The chip part of this linear charger 200 only needs three stitch to connect power end V respectively DD, this battery module 208 and this sensing resistor R SnsReview the conventional linear charger 100 of Fig. 1, this measuring resistance R Sns, this charging transistor g MpCapacitor C z, and resistance R zBe all outward element.So the chip of conventional linear charger 100 part needs four stitch 104,106,108 and 110 at least.
Fig. 3 is an another embodiment of the present invention.Linear charger 300 than the linear charger more than 200 of Fig. 2 voltage level control circuit 302.This voltage level control circuit 302 is coupled to this second metal oxide semiconductor transistor M 2Drain electrode and this sensing resistor R SnsBetween, comprising the 3rd metal oxide semiconductor transistor M 3And the second operational amplifier OP 2The 3rd metal oxide semiconductor transistor M 3Source electrode couple this second metal oxide semiconductor transistor M respectively with drain electrode 2Drain electrode and this sensing resistor R SnsThe 3rd metal oxide semiconductor transistor M 3Grid by this second operational amplifier OP 2Output control.In this embodiment, this second operational amplifier OP 2Noninverting and inverting input couple this first metal oxide semiconductor transistor M respectively 1Drain electrode and this second electric metal oxide semi conductor transistor M 2Drain electrode.The acting as of this voltage level control circuit 302 make this first with this second metal oxide semiconductor transistor M 1With M 2(its value is V to have same drain voltage Bat), with guarantee this first with this second metal oxide semiconductor transistor M 1With M 2First and second electric current I that is produced 1With I 2Become fixed proportion.
Fig. 4 is an another embodiment of the present invention.Linear charger 400 than the linear charger more than 300 of Fig. 3 frequency compensated circuit 402.As the embodiment of Fig. 4, this frequency compensated circuit 402 comprises a plurality of resistance (R 1With R 2), dividing point 404, frequency compensator 406 and variable capacitance C.These resistance R 1With R 2And this dividing point 404 is serially connected with between this battery module 408 and the earth terminal.The current potential V of this battery module BatThrough these resistance R 1With R 2Export this multiplex's choice device 410 to by this dividing point 404 after the dividing potential drop.This frequency compensator 406 is coupled between this battery module 408 and this dividing point 404.This variable capacitance C is coupled between this frequency compensator 406 and this earth terminal.Under this constant-voltage charge pattern, this frequency compensated circuit 402 provides zero point (zero), in order to eliminate unnecessary limit in the loop.The size at this zero point is 1/ (R 1C).
The frequency compensation capacitor C that frequency compensated circuit 402 employed variable capacitance C and the conventional linear charger 100 of Fig. 4 adopted cWith C zMake comparisons, can find the end ground connection of the variable capacitance C that both maximum differences are that Fig. 4 adopts.Therefore the electric capacity that frequency compensated circuit of the present invention adopted can be MOS capacitor (MOS capacitor), the frequency compensation capacitor C that volume is adopted much smaller than conventional linear charger 100 cWith C z
Fig. 5 is an another embodiment of the present invention.The difference of the linear charger 400 of this linear charger 500 and Fig. 4 is the implementation method of variable capacitance C.The variable capacitance that Fig. 5 adopted comprises first capacitor C 1, second capacitor C 2, to should second capacitor C 2Switch SW and comparator C MP.The output of this comparator C MP couples this switch SW to control this switch SW.During this switch SW conducting, this second capacitor C 2This first capacitor C in parallel 1The first input end of this comparator C MP and second input are imported the 3rd reference potential V respectively Ref3With this sensing current potential V Sns, use making this switch SW under the state of low load current, be conducting, otherwise be not conducting.
Embodiment with Fig. 5 is an example, under this constant-voltage charge pattern, and the current potential V of this battery module 502 BatThe limit that is provided (pole) can change along with load.(light load, for example, the mobile phone that uses while charging has the high capacity resistance R this moment at low load current L) under the state, the frequency of this limit is extremely low.Therefore the compensation zero point that needs extremely low frequency is to obtain higher phase place limit (phase margin).Otherwise under high load currents (high load) state, the frequency of this limit is higher.Therefore the compensation zero point that needs a high frequency is to obtain higher phase place limit.The embodiment of Fig. 5 is by this first capacitor C 1, this second capacitor C 2, this switch SW and this comparator C MP reach the demand.As shown in the figure, the 3rd reference potential V Ref3Couple the non-inverting input of comparator C MP, and this sensing current potential V SnsCouple the inverting input of comparator C MP.Under the situation of this low load current, this sensing current potential V SnsDrop to and be lower than the 3rd reference potential V Ref3This comparator C MP makes this switch SW conducting.At this moment, the value at this compensation zero point is 1/ (R 1(C 1+ C 2)).Otherwise, under the situation of this high load currents, this sensing current potential V SnsRise to and exceed the 3rd reference potential V Ref3This comparator C MP makes this not conducting of switch SW.At this moment, the value at this compensation zero point is 1/ (R 1C 1).
Fig. 6 is the distortion of the embodiment of Fig. 5, wherein uses more groups the above-mentioned second electric capacity (C 21, C 22C 2n), the pairing switch (SW of these second electric capacity 1, SW 2SW n) and a plurality of comparator (CMP of controlling each switch 1, CMP 2CMP n).Cooperate specially designed a plurality of reference potential (V Ref31, V Ref32V Ref3n), linear charger shown in Figure 6 provides more compensation to select for system zero point.
The disclosed circuit of the present invention not only can be used as linear charger and uses, and also can be used as low dropout voltage regulator (Low Drop Out regulator, LDO regulator).
Though the present invention discloses as above with preferred embodiment; so it is not in order to limit scope of the present invention; any those skilled in the art; without departing from the spirit and scope of the present invention; when can doing a little change and retouching, so protection scope of the present invention is as the criterion when looking appended the claim scope person of defining.

Claims (8)

1. linear charger, comprising:
First current generator produces first electric current and couples battery module, in order to this battery module that charges;
Current detector couples this first current generator, in order to produce the sensing current potential corresponding to this first size of current;
First operational amplifier, first and second input of tool and output, this output couples the control end of this first current generator; And
Multiplex's choice device, in order under the constant-current charge pattern, first reference potential and this sensing current potential are coupled to first and second input of this first operational amplifier respectively, and under the constant-voltage charge pattern, the current potential of second reference potential and this battery module is coupled to first and second input of this first operational amplifier respectively.
2. linear charger according to claim 1, wherein this first current generator is first metal oxide semiconductor transistor, its drain electrode couples this battery module, and its grid couples the output of this first operational amplifier this control end as this first current generator.
3. linear charger according to claim 2, wherein this current detector comprises second metal oxide semiconductor transistor and sensing resistor, the drain electrode of this second metal oxide semiconductor transistor couples this sensing resistor and its grid and is coupled in the grid of this first metal oxide semiconductor transistor, use make this second metal oxide semiconductor transistor of flowing through second current ratio in this first electric current, this sensing resistor is this sensing current potential with this second current conversion.
4. linear charger according to claim 3 wherein also comprises the voltage level control circuit between the drain electrode of this second metal oxide semiconductor transistor and this sensing resistor, comprising:
The 3rd metal oxide semiconductor transistor, its source electrode and drain electrode couple drain electrode and this sensing resistor of this second metal oxide semiconductor transistor respectively; And
Second operational amplifier, its first input end and second input couple the drain electrode of this second metal oxide semiconductor transistor and the drain electrode of this first metal oxide semiconductor transistor respectively, and its output couples the grid of the 3rd metal oxide semiconductor transistor.
5. linear charger according to claim 3 wherein also comprises frequency compensated circuit between this battery module and this multiplex's choice device, comprising:
A plurality of resistance and dividing point are serially connected with between this battery module and the earth terminal, and the current potential of this battery module exports this multiplex's choice device to by this dividing point behind these electric resistance partial pressures;
Frequency compensator is coupled between this battery module and this dividing point; And
Variable capacitance couples this frequency compensator to this earth terminal;
Wherein, under this constant-voltage charge pattern, this frequency compensated circuit provides zero point, and its size is got inverse for this constant resistance after the resistance value between this battery module and this dividing point multiply by this variable capacitance.
6. linear charger according to claim 5, wherein this variable capacitance comprises:
First electric capacity;
The switch and second electric capacity, during this switch conduction, this second electric capacity this first electric capacity in parallel;
Comparator, in order to control this switch, the first input end of this comparator and second input are imported the 3rd reference potential and this sensing current potential respectively, use to make this switch be conducting under the state of low load current, otherwise are not conducting.
7. linear charger according to claim 5, wherein this variable capacitance can be MOS capacitor.
8. linear charger according to claim 1, wherein this sensing resistor can be variable resistor.
CNB2007100021830A 2006-09-01 2007-01-12 Linear charger Active CN100442629C (en)

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US82428906P 2006-09-01 2006-09-01
US60/824,289 2006-09-01

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CN100442629C CN100442629C (en) 2008-12-10

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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102931955A (en) * 2012-11-12 2013-02-13 上海中科高等研究院 Multi-way comparator circuit
CN107769331A (en) * 2017-11-22 2018-03-06 深圳市森树强电子科技有限公司 The charging management method and device of a kind of mixed mode
CN113448371A (en) * 2020-03-27 2021-09-28 矽统科技股份有限公司 Constant current charging device

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TWI514735B (en) 2012-10-05 2015-12-21 Leadtrend Tech Corp Controller for controlling a power converter to output constant power and related method thereof
TWI739363B (en) * 2020-03-27 2021-09-11 矽統科技股份有限公司 Constant current charging device
TWI790966B (en) * 2022-05-10 2023-01-21 茂達電子股份有限公司 Switching charger for supplying stable power

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2733446B2 (en) * 1994-08-12 1998-03-30 株式会社京三製作所 Power control device control method
US6404251B1 (en) * 2000-03-27 2002-06-11 Linear Technology Corporation Systems and methods for linearly varying a pulse-width modulation signal with a control signal
KR100572160B1 (en) * 2001-09-14 2006-04-19 가부시키가이샤 리코 Secondary battery charging circuit

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102931955A (en) * 2012-11-12 2013-02-13 上海中科高等研究院 Multi-way comparator circuit
CN102931955B (en) * 2012-11-12 2016-01-06 中国科学院上海高等研究院 Multichannel comparator circuit
CN107769331A (en) * 2017-11-22 2018-03-06 深圳市森树强电子科技有限公司 The charging management method and device of a kind of mixed mode
CN113448371A (en) * 2020-03-27 2021-09-28 矽统科技股份有限公司 Constant current charging device
CN113448371B (en) * 2020-03-27 2023-02-17 矽统科技股份有限公司 Constant current charging device

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TWI325672B (en) 2010-06-01
CN100442629C (en) 2008-12-10
TW200814493A (en) 2008-03-16

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