CN100483963C - Orthogonal lower mixing frequency digital template matching pulse ultra wide band radio signal receiving method - Google Patents
Orthogonal lower mixing frequency digital template matching pulse ultra wide band radio signal receiving method Download PDFInfo
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Abstract
A method for receiving radio pulse signal includes applying high sampling rate ADC after frequency is mixed under orthogonality and applying flexible and match-correlated master plate being able to regulate adaptively and being set with different shifting positions in digital master plate-match.
Description
Technical field
The present invention relates to a kind of pulse ultra wide band radio signal receiving method of orthogonal lower mixing frequency digital masterplate coupling, being supported in the Wireless Personal Network physical layer simultaneously carries out impulse radio (IR) or has the high-performance of the ultra-wideband impulse signal of carrier wave (Carrier-modulated) to receive and demodulation, can carry out succinct practical circuit design and realization, it is integrated to be easy to chip, belongs to the reception technique field of wireless pulse signals.
Background technology
The burst pulse super-broadband tech is a kind of wireless communication technology of the non-sinusoidal waveform burst pulse transmission data of utilizing nanosecond, and its signal spectrum scope is very wide, usually more than 500MHz, has strong security, antijamming capability is strong and unique advantage such as transmission rate height.For fear of the interference to other civil equipment, FCC (FCC) has stipulated that UWB (ultra broadband) must operate in 3.1～10.6GHz frequency range, and transmitting power is no more than-41.3dBm/Hz.For example, the MBOK-UWB that we proposed (M unit biorthogonal keying-ultra broadband) scheme is based on burst pulse radiotechnics principle, its radio-frequency front-end has adopted the media of discrete pulse signal as the information of transmission, and designed signal spectrum is in 3.1～4.6GHz scope, and width surpasses 1GHz.Still there are some problems in the practicability of ultrawideband at present, mainly is that channel model research cost and power consumption insufficient, transceiver chip are more high, and technical standards such as 802.15.3a do not have final conclusion always yet.
What one of traditional burst pulse ultra broadband method of reseptance adopted is pure simulation Rake correlation technique, promptly when the Rake of multipath signal receives, simulate relevantly by a series of different analog signal masterplates that postpone and antenna receiving signal, again correlated results is carried out digital sample and merging.This kind mode is very high to the required precision of analog delay line structural design, and chip realizes that difficulty is bigger, and especially under the high situation of chip and data rate, performance is difficult to be guaranteed; Studies show that under the bigger situation of the shake time of delay of each analog signal, the accumulation of error that simulation is relevant can influence the performance of reception.
Another kind of traditional method of reseptance has utilized the pure digi-tal correlation technique, promptly signal is carried out the AD sampling of high sample rate on rf frequency, carries out processing such as Digital Down Convert (DDC), correlation reception afterwards again.For high-speed data applications, this kind mode is high for the sample rate requirement of analog to digital converter (ADC), need pay bigger hardware and realize cost, and bring huge power consumption.Therefore this kind scheme is to the bigger limitation of the same existence of high-speed data applications.
Summary of the invention
The objective of the invention is to propose a kind of pulse ultra wide band radio signal receiving method of orthogonal lower mixing frequency digital masterplate coupling, adopted I/Q two-way analog frequency mixing to receive the mode that combines with the relevant Rake of numeral coupling, can carry out succinct practical circuit design and realization, it is integrated to be easy to chip; Because its reception and demodulation of supporting impulse radio simultaneously and the UWB pulse signal of these two kinds of forms of carrier wave being arranged, thereby strengthened its versatility greatly at different signal launch scenarios.
The invention is characterized in that described method contains following steps successively:
Step 1 received signal through the radio-frequency front-end of forming by serial by antenna, low noise amplifier, I/Q two-way Analogue mixer and low pass filter successively after, obtain zero intermediate frequency analog baseband signal through frequency spectrum shift; The local oscillation signal frequency of described I/Q two-way Analogue mixer is determined by following mode: the piconet framework of being worked out according to the ultra-wideband communication system scheme and launch user-selected center frequency points of getting, choose the local oscillation signal of the sine wave signal of same frequency as this frequency mixer, this I/Q two-way local oscillation signal keeps orthogonality;
The zero intermediate frequency analog baseband signal of this AFE (analog front end) of step 2 output is delivered to the ADC that sample rate is higher than the spreading rate twice and is carried out the sampling of zero intermediate frequency baseband signal, generates the digital baseband signal of I/Q two-way;
The I/Q two-way high-speed figure baseband signal that step 3 obtains step 2 is sent into a relevant Rake receiver of numeral coupling that is integrated on the digital integrated circuit chip, numeric field according to the following steps to described I/Q two-way high-speed figure baseband signal carry out frequency and estimation regularly and correction, the numeral coupling is relevant and Rake reception and frame synchronization are caught, the output signal that obtains is carried out spreading code despreading and channel decoding successively, recovers original transmission signal:
Step 3.1 is carried out frequency correction to the I/Q two-way high-speed figure baseband signal of input successively according to the following steps with a frequency correction circuit:
Step 3.1.1 I/Q two-way digital baseband signal I ' (n), Q ' (n) sends into phase discriminator in the carrier recovery loop that comprises the polarity type carrier recovery loop, extracts phase error signal ε by following algorithm
c(n):
ε
c(n)=I ' (n) * Q ' (n), n is the sampled point label;
Step 3.1.2 is phase error signal ε
c(n) the second order digital loop filters of importing in this carrier recovery loop carries out filtering, and its sequential is:
The phase error accumulating signal φ (n+1) of n+1 sampled point is:
φ(n+1)＝φ(n)+K
1f(n)+K
2ε
c(n)，
The frequency error accumulating signal f (n+1) of n+1 sampled point is:
f(n+1)＝f(n)+ε
c(n)，
Wherein, constant K
1And K
2Be the filter factor of this second order digital loop filters, when the sample rate f of described ADC
sDuring much larger than the natural frequency of loop:
K
2＝2ηω
nT
s?
ω
n=2 π f
nBe the natural angular frequency of loop, η is a damping coefficient, T
s=1/f
s
Step 3.1.3 is the input of the phase error accumulating signal φ (n+1) that obtains through described loop filtering as local digital controlled oscillator in the described loop, to adjust the frequency of local oscillation signal;
Step 3.1.4 multiplies each other the I/Q two-way digital baseband signal I (m), the Q (m) that are input to the frequency correction loop and output cos φ (n), the sin φ (n) of local digital controlled oscillator, carry out phase place rotation, thus obtain through the I/Q two-way digital baseband signal I ' of frequency correction (m), Q ' (m):
I′(m)＝I(m)×cosφ(n)+Q(m)×sinφ(n)
Q′(m)＝Q(m))×cosφ(n)-I(m)×sinφ(n)
The difference of m and n is the computing time-delay of described whole carrier recovery loop;
Step 3.2 is corrected loop with a timing and according to following steps the output signal of described frequency correction circuit is done regularly to correct:
Step 3.2.1 utilize through the I way word baseband signal I ' of frequency correction (n) with the main path position of channel estimator output, obtain main footpath signal;
Step 3.2.2 obtains main footpath correlation Corr (n) to a main footpath of signal input, described main footpath correlator;
Step 3.2.3 local masterplate signal and described main footpath signal send into one early correlator obtain a footpath correlation Corr (n-1) early, this morning, directly correlation was the cross correlation value of the local masterplate signal and the signal in main footpath signal unit sampling interval of morning, this this locality masterplate signal is produced by local masterplate signal generator, its initial value is the standard signal of transmitter emission in the known single chip, and adjusts signal according to masterplate and carry out phase delay or in advance;
Step 3.2.4 sends into a slow correlator to described local masterplate signal of step 3.2.3 and described main footpath signal, obtain a footpath correlation Corr (n+1) late, this slow footpath correlation is local masterplate signal and the main directly cross correlation value of the signal in a slow unit sampling interval of signal;
Step 3.2.5 resulting main footpath correlation Corr (n), early footpath correlation Corr (n-1), footpath correlation Corr (n+1) sends into a timing error extractor late, calculates signal of timing error ε by following formula
t(n):
ε
t(n)＝sign(Corr(n))*[Corr(n+1)-Corr(n-1)]：
The signal of timing error ε that step 3.2.6 obtains step 3.2.5
t(n) send into the timing error value that single order digital lowpass loop filter obtains accumulating:
Its sequential is: E
t(n)=E
t(n-1)+K
1ε
t(n),
Constant K
1Be the filter factor of this filter, K
1＜1;
Whether step 3.27 reaches preset threshold with the accumulated error value that a comparator comes determining step 3.2.6 to obtain, if reach preset threshold then the zero clearing of accumulated error value, send a masterplate simultaneously and adjust signal, control local masterplate signal generator the phase delay of local masterplate signal or carry the previous unit sampling interval, and the output masterplate is adjusted the numeral coupling relevant Rake receiving circuit of signal after giving and is regularly corrected realizing; Take to shift to an earlier date or postpone to depend on the polarity of accumulated error,, then shift to an earlier date if just, otherwise, postpone;
The I way word baseband signal I ' that the masterplate that step 3.3 obtains step 3.2.7 is adjusted signal and process frequency correction (n) sends into a relevant and Rake receiving circuit of numeral coupling, calculates the output of this Rake correlation reception circuit according to the following steps:
Step 3.3.1 sends into channel estimator to this digital baseband signal with the signal masterplate of several different deviation posts of being exported by local masterplate signal generator, search a main path position corresponding and corresponding with the big correlation of several times successively inferior path position through the signal correction computing with maximum related value, described related operation is meant: calculate the product of two input signals and add up by each sampled point, the procurement process of main path position is the process of sign synchronization; The masterplate that step 3.2.7 obtains is adjusted signal and in the time interval of double channel estimating the masterplate signal that main footpath reaches selected each time footpath is adjusted;
The main footpath that step 3.3.2 obtains according to step 3.3.1 and the position in each time footpath, (n) sending into a correlator bank respectively with the directly corresponding masterplate signal of the main footpath that obtains and selected each time through the I way word baseband signal I ' of frequency correction, the described method of 3.3.1 is carried out related operation respectively set by step, obtain the signal after numeral is mated, be sent to the Rake combiner;
Step 3.3.3Rake combiner merges time number in footpath by the scheme of setting and is at least one, no maximum;
The multipath energy that step 3.3.4Rake combiner is made of the pairing correlated results in main footpath and each time footpath is weighted than criterion than criterion or equal gain combining according to the maximum merging and adds up, obtain a total energy, i.e. the output I ＂ (n) of this Rake correlation reception circuit;
Step 4 is sent to a frame synchronization grabber to the output signal I ＂ (n) of the Rake correlation reception that step 3.3.4 obtains, according to the following steps the Rake correlation reception signal of output frame after synchronously:
Step 4.1 is sent to a vertical sync circuit to the output signal I ＂ (n) that step 3.3.4 obtains, the polarity of this signal as the information data position, search can be found the frame separator corresponding to the output of this information data position, thus the original position of locating frame head and locator data information;
The ＂ ' of I as a result that step 4.2 obtains step 4.1 (n) is sent to follow-up spreading code despreading module and channel decoder.
The pulse ultra wide band radio signal receiving method of the orthogonal lower mixing frequency digital masterplate coupling that the present invention proposes, its advantage mainly comprises: combine orthogonal lower mixing frequency and digital masterplate mates the two, thereby avoided the relevant Rake receiver that reaches of traditional analog to high-precision analog delay-line structure designing requirement, avoided the relevant requirement that reaches the Rake receiver to high sampling rate ADC of conventional digital simultaneously, thereby simplified hardware configuration and realized cost, and improved the reliability that technology realizes; Numeric field high power over-sampling can adapt to the various possible waveform of pulse process channel in the chip better in conjunction with mating relevant masterplate flexibly; Have very high baseband bandwidth, be beneficial to and realize fast and high-precision frequency deviation correction; Support impulse radio simultaneously and have the UWB signal of carrier schemes to receive, have stronger versatility; Have the circuit design and the realization of succinct practicality and structure law, it is integrated to be easy to chip.
Description of drawings:
Fig. 1 is the schematic block circuit diagram of the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.
Fig. 2 is the schematic block circuit diagram of the frequency correction loop in the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.
Fig. 3 is the schematic block circuit diagram that loop is corrected in the timing in the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.
Fig. 4 is the schematic block circuit diagram that the numeral coupling is relevant and Rake receives in the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.
Fig. 5 is the schematic block circuit diagram that frame synchronization is caught in the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.
Embodiment:
The pulse ultra wide band radio signal receiving method that the orthogonal lower mixing frequency digital masterplate that the present invention proposes mates, its pairing receiver is correlated with by radio-frequency front-end, zero intermediate frequency baseband sampling circuit, numeral coupling and Rake reception three parts are formed (serial structure):
(1) radio-frequency front-end is made up of antenna, low noise amplifier (LNA), I/Q two-way Analogue mixer and low pass filter, processing such as the signal that receives mixing under the corresponding levels are simulated through amplification, I/Q two-way, low-pass filtering obtain the zero intermediate frequency analog baseband signal through frequency spectrum shift;
(2) the zero intermediate frequency analog baseband signal of radio-frequency front-end output enters zero intermediate frequency baseband sampling circuit; I/Q two-way zero intermediate frequency analog baseband signal is delivered to ADC that sample rate is higher than the spreading rate twice and is sampled and quantize, and generates the digital baseband signal of I/Q two-way;
(3) the high-speed figure baseband signal of sample circuit output is admitted to the relevant Rake receiver of numeral coupling, the estimation of signal being carried out frequency and timing at numeric field receives with correction, the relevant Rake of reaching of numeral coupling, frame synchronization is caught, the output signal that obtains is carried out spreading code despreading and channel decoding successively, recover original transmission signal.
In the said structure, definite method of the local oscillation signal frequency of I/Q two-way Analogue mixer is:
The piconet framework of being worked out according to the ultra-wideband communication system scheme and launch user-selected center frequency points of getting is chosen the local oscillation signal of the sine wave signal of same frequency as frequency mixer, realizing the frequency spectrum shift of signal, thus the baseband signal of obtaining.I/Q two-way local oscillation signal should keep orthogonality.
In the said structure, definite method of the sample rate of ADC is:
The sample rate of ADC should be far above spreading rate.Concrete multiple is chosen the characteristic (change in polarity in duty ratio, the chip etc.) that should consider to send impulse waveform, for example 4 times or 8 times.In this programme, the sample rate of ADC has also determined the temporal resolution precision of multipath Rake receiver diameter simultaneously.
For example spreading rate is 500Mbps, and during 4 times of the sample rate code fetch sheet speed of ADC, the ADC sample rate requires about 2Gsps, and the time resolution precision of diameter was 1/ (2Gsps)=0.5 nanosecond.
In the said structure, the relevant Rake receiver of numeral coupling can be realized by FPGA (field programmable gate array), also can go up at ASIC (application-specific integrated circuit (ASIC)) and realize.
At first provide communication speciality term related in this method, it is explained as follows:
1) chip: the used unit signal of expression information in the digital communication, its form is a calibration pulse waveform or standardized digital signal sequence usually; Each information bit or information symbol can be represented by several chips through particular arrangement;
2) spreading rate/character rate: spreading rate is the several times of character rate normally, and concrete multiple equals to represent the number of the used chip of each symbol;
3) the relevant Rake of numeral coupling receives: in the digital communication, in order to realize the received signal to noise ratio maximization, adopt the relevant reception of carrying out signal of coupling to handle usually; In order to solve the energy dissipation that multipath channel is brought, adopt Rake structure (the multidiameter delay coupling is correlated with and its weighting is as a result merged) usually simultaneously to collect multipath energy effectively, to improve demodulation performance;
4) frequency and estimation regularly: utilize the burst that receives,, obtain received signal and the relative frequency and the information of timing offset of transmitting, thereby carry out frequency and regularly correction effectively by the computing and the processing of respective algorithms;
5) synchronization acquistion of symbol and frame: by transmitting terminal emission known array, the process that receiving terminal utilizes algorithm to realize catching the original position of each symbol is the synchronization acquistion of symbol; The process that receiving terminal utilizes the algorithm realization to catch the original position of each signal frame is caught for frame synchronization; The original position of frame is by frame separator sign;
6) spreading code despreading: spread spectrum communication utilizes the information bit of polarity (' 0 ' or ' 1 ') expression or the information symbol of a plurality of chips, and its expression sequence is a spreading code; Utilization receives that the polarity decision of each chip sends is that the process of which kind of information bit or information symbol is the spreading code despreading;
7) channel decoding: often the information bit that sends is carried out forward error correction channel in the digital communication, increase redundant information, to increase the reliability of communication; The operation of receiving terminal correspondence (i.e. removal redundancy is also corrected a mistake) is called channel decoding;
The minimum metric of time-delay between each footpath when 8) Jing temporal resolution precision: Rake receives multipath;
9) baseband signal: in the digital communication without the signal of carrier modulation;
10) down mixing of simulation: with analog signal and the local oscillation signal that receives the also process of low-pass filtering that multiplies each other; This process has realized signal by the frequency spectrum shift process of radio frequency to base band;
11) local oscillation signal of down-conversion mixer: be generally the single frequency sinusoidal signal, its frequency configuration wants consistent with the centre frequency that transmits;
12) carrier recovery loop: the form of the algorithm of Frequency Estimation and correction loop commonly used realizes that this loop is called carrier recovery loop; This loop is made up of phase discriminator, loop filter, NCO (digital controlled oscillator) usually;
13) phase discriminator: the circuit that utilizes input signal to extract phase error signal in the carrier recovery loop is called phase discriminator;
14) loop natural frequency: the intrinsic parameter of carrier recovery loop is determined by parameters such as loop gains;
15) correlator (related operation): the corresponding computing of multiplying each other and adding up between the digital signal that realizes input and one group of digital signal with its equal in length; Wherein the latter is called local masterplate signal;
For example input signal is x (n), n=1, and 2 ... N, local masterplate signal are y (n), n=1, and 2 ... N, then the output result of correlator (related operation) (claiming cross correlation value again) is:
16) main directly signal: carry out related operation by input signal with the signal masterplate of different deviation posts, and choose maximum, can obtain the main path position of signal, thereby obtain main footpath signal;
17) main directly correlator: input signal is the correlator of main footpath signal; Its output is called main footpath correlation;
18) channel estimating: utilize known transmission targeting sequencing that receiver is trained, carry out related operation by input signal with the signal masterplate of different deviation posts, and choose several maximums, can obtain the position and the gain thereof in several footpaths that need merge (main footpath and each time footpath) of signal; The information of these positions and gain is the result of channel estimating;
19) multipath energy: the pairing correlated results in the main footpath that channel estimating provides and each time footpath is its multipath energy;
20) merging of multipath energy: multipath energy is weighted by certain criterion adds up, obtain a total energy;
21) the maximum merging than criterion: the correlation size in main footpath and each time footpath determines the weighted value when its energy merges; The footpath that energy is big more, it merges weighting big more (proportional);
22) equal gain combining criterion: main footpath and the gain of each time footpath when energy merges equate.
Below in conjunction with accompanying drawing, introduce content of the present invention in detail; When wherein using above-mentioned communication speciality term, see also above explanation as needs:
Fig. 1 is the schematic block circuit diagram of the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.As shown in Figure 1, signal receives through antenna, enters low noise amplifier (LNA) and amplifies, and simulates down mixing with the I/Q two-way local oscillation signal of this locality generation then, carries out low-pass filtering afterwards again.The choosing method of local oscillation signal frequency is: the piconet framework of being worked out according to the ultra-wideband communication system scheme and launch user-selected center frequency points of getting, choose the local oscillation signal of the sine wave signal of same frequency as frequency mixer, to realize the frequency spectrum shift of signal, obtain baseband signal.
If adopt the impulse radio scheme during signal emission, then descend mixing operation to be equivalent to promptly obtain corresponding baseband signal after the filtering to carrying out frequency spectrum shift with logical radiofrequency signal; If adopt during the signal emission carrier modulation scheme is arranged, following mixing and low-pass filtering merging effect are equivalent to the signal that will be modulated to centre frequency and carry out frequency spectrum shift, down-convert to baseband signal.Therefore no matter be IR or carrier schemes is arranged, all will obtain base-band data signal after handling through radio-frequency front-end, offer the back level and handle.
The analog baseband signal of radio-frequency front-end output is sampled by ADC, obtains the baseband signal of numeric field; The ADC sample rate should be higher than the Nyquist sample frequency, is convenient to mate when digital baseband is handled relevant.
The digital signal that sampling obtains enters the relevant Rake receiver of base-band digital coupling and handles, numeric field to signal carry out that frequency and estimation regularly and correction, numeral coupling are relevant, Rake merging, frame synchronization catch, the output signal that obtains is carried out spreading code despreading and channel decoding successively, recover original transmission signal.
The handling process of numeral Rake receiver is: the signal demand that sampling obtains at first carries out frequency and estimation and correction regularly.Because the frequency of the local oscillation signal that down-conversion mixer adopts may have deviation with the centre frequency that transmits, therefore the baseband signal that obtains might not be strict zero intermediate frequency, need carry out frequency correction.The speed and the baseband bandwidth of frequency correction are in close relations, and baseband bandwidth is high more, the relative velocity of frequency correction algorithm fast more (being achieved correction in the less chip of number); And the baseband bandwidth of this structure respective signal is very high, therefore helps frequency correction.The deviation of the reference clock crystal oscillator of transmitter and receiver can be introduced the timing offset of sampling simultaneously, also should be corrected.Signal after overfrequency and timing correction enters the relevant Rake receiver module of numeral coupling; Adjust digital matching stencil by self adaptation, can processing channel change the signal waveform variation that brings.Multipath according to channel estimating distributes, and maximum and time several big related operation results that receive the footpath are delivered to the Rake combiner, and the energy that carries out multipath signal merges, and obtains effective diversity gain, improves the signal to noise ratio of equivalence.The signal demand of the relevant Rake receiver module output of numeral coupling carries out the synchronization acquistion of frame.Signal after the frame synchronization enters spreading code despreading module and channel decoder, carries out spreading code and separates and extend to channel decoding, thereby recover the data message of original transmission.
Below be the arthmetic statement and the specific implementation method thereof of each several part:
Fig. 2 is the schematic block circuit diagram of the frequency correction loop in the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.As shown in Figure 2, the frequency correction algorithm of this method can adopt the carrier recovery loop of standard, and the specific implementation method is:
1) I/Q two-way digital baseband signal I ' (n), Q ' (n) sends into the phase discriminator of carrier recovery loop, extracts phase error signal ε
c(n) (also can adopt the carrier recovery loop of polarity type herein, the simplification error extracting method); Its extracting method is:
ε
c(n)=I ' (n) * Q ' (n), wherein n is the sampled point label;
2) phase error signal ε
c(n) the second order digital loop filters of importing in this carrier recovery loop carries out filtering, and its sequential is:
The phase error accumulating signal φ (n+1) of n+1 sampled point is:
φ(n+1)＝φ(n)+K
1f(n)+K
2ε
c(n)，
The frequency error accumulating signal f (n+1) of n+1 sampled point is:
f(n+1)＝f(n)+ε
c(n)
Wherein, constant K
1And K
2Be the filter factor of this second order digital loop filters, when the sample rate f of ADC
sDuring much larger than the natural frequency of loop, this two parameter can be determined by following formula:
K
2＝2ηω
nT
s?
Wherein, ω
n=2 π f
nBe the natural angular frequency of loop, η is a damping coefficient, T
s=1/f
s
3) the input of the phase error accumulating signal φ (n+1) that obtains through loop filtering, to adjust the frequency of local oscillation signal as local digital controlled oscillator in the loop;
4) the I/Q two-way digital baseband signal I (m) that is input to the frequency correction loop, Q (m) and output cos φ (n), the sin φ (n) of local digital controlled oscillator are multiplied each other, carry out phase place rotation, thus obtain through the I/Q two-way digital baseband signal I ' of frequency correction (m), Q ' (m):
I′(m)＝I(m)×cosφ(n)+Q(m)×sinφ(n)
Q′(m)＝Q(m)×cosφ(n)-I(m)×sinφ(n)
Wherein m and the difference of n are that the computing time-delay of whole carrier recovery loop (realizes relevant with particular hardware; Because the phase place rotation is a continuous process, so this computing time-delay does not have strict constraint).
Fig. 3 is the schematic block circuit diagram that loop is corrected in the timing in the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.As shown in Figure 3, the timing correct algorithm of this method can adopt " ring sooner or later " correlation technique, and the specific implementation method is:
1) utilize through the I way word baseband signal I ' of frequency correction (n) with the main path position of channel estimator output, obtain main footpath signal;
2) a main footpath of signal input, main footpath correlator, obtain main footpath correlation Corr (n);
3) local masterplate signal and main footpath signal send into one early correlator obtain a footpath correlation Corr (n-1) early, this morning, directly correlation was the cross correlation value of the local masterplate signal and the signal in main footpath signal unit sampling interval of morning, this this locality masterplate signal is produced by local masterplate signal generator, its initial value is the standard signal of transmitter emission in the known single chip, and adjusts signal according to masterplate and carry out phase delay or in advance;
4) 3) described local masterplate signal sends into a slow correlator with main footpath signal, obtains a footpath correlation Corr (n+1) late, this late footpath correlation be local masterplate signal and the cross correlation value of the signal in a main footpath slow unit sampling interval of signal;
5) resulting main footpath correlation Corr (n), early footpath correlation Corr (n-1), footpath correlation Corr (n+1) sends into a timing error extractor late, calculates signal of timing error ε by following formula
t(n):
ε
t(n)＝sign(Corr(n))*[Corr(n+1)-Corr(n-1)]；
6) 5) the signal of timing error ε that obtains
t(n) send into the timing error value that single order digital lowpass loop filter obtains accumulating: its sequential is:
E
t(n)＝E
t(n-1)+K
1ε
t(n)；
Constant K wherein
1Be filter coefficient, set (being no more than 1 usually) by system schema;
7) judge 6 with a comparator) whether the error that obtains reach preset threshold and (set by system schema, for example main footpath correlation 1/2), if reach preset threshold then the zero clearing of accumulated error value, send a masterplate simultaneously and adjust signal, control local masterplate signal generator the phase delay of local masterplate signal or carry the previous unit sampling interval, and the output masterplate is adjusted the numeral coupling relevant Rake receiving circuit of signal after giving and is regularly corrected realizing;
Take to shift to an earlier date or postpone to depend on the polarity of accumulated error,, then shift to an earlier date if just, otherwise, postpone;
Fig. 4 is the schematic block circuit diagram that the numeral coupling is relevant and Rake receives in the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.As shown in Figure 4, the channel estimating of this method, numeral coupling specific implementation method relevant and that Rake merges are:
1) the I way word baseband signal I ' through frequency correction (n) is sent into channel estimator with the signal masterplate of several different deviation posts of being exported by local masterplate signal generator, search a main path position corresponding with maximum related value and corresponding with the big correlation of several times successively inferior path position through the signal correction computing, the procurement process of main path position is the process of sign synchronization;
2) according to 1) the main footpath that obtains and the position in each time footpath, (n) sending into a correlator bank respectively with the directly corresponding masterplate signal of the main footpath that obtains and selected each time through the I way word baseband signal I ' of frequency correction, carry out numeral coupling related operation respectively, obtain the signal after numeral is mated, be sent to the Rake combiner;
3) the Rake combiner merges choosing by the system schema setting of time footpath number, is at least one, no maximum;
4) multipath energy that is made of the pairing correlated results in main footpath and each time footpath of Rake combiner is weighted than criterion than criterion or equal gain combining according to the maximum merging and adds up, obtain a total energy, the i.e. output I ＂ (n) of this Rake correlation reception circuit, which kind of selects for use merge set by system schema than criterion, the merging by multipath energy has realized the significantly improvement of receptivity under the multipath channel;
The sample rate of prime ADC is higher than the twice of spreading rate, and the temporal resolution precision of Rake receiver diameter is by the sample rate decision of ADC.For example spreading rate is 500Mbps, and during 4 times of the sample rate code fetch sheet speed of ADC, the ADC sample rate requires about 2Gsps, and the time resolution precision of diameter was 1/ (2Gsps)=0.5 nanosecond.
As shown in Figure 4, this method is according to the result of channel estimating, neatly the used local masterplate signal of numeral coupling related operation is carried out the self adaptation adjustment, obtain the current local masterplate signal that the self adaptation effect is arranged that meets the interior pulse of chip of channel effect, the specific implementation method is:
1) method of self adaptation adjustment masterplate is LMS (Minimum Mean Square Error) algorithm: the Initial Channel Assignment response is ω (0)=ω
Est, i.e. the response of the result of channel estimating " tap line one time-delay " multipath model, and n=0; Make x (n) send signal, the signal (herein use through I road signal I ' frequency correction after (n)) of y (n) for receiving for transmitter; Upgrade n=n+1, order:
E (n)=y (n)-ω
T(n-1) x (n), the i.e. margin of error;
ω (n)=ω (n-1)+μ (n) x (n) e (n), i.e. updating value of channel response; Wherein μ (n) is set by system schema, for example the statistic of arbitrary constant or input signal;
After process is upgraded a period of time thus, can calculate the matching stencil of self adaptation effect: t (n)=ω
T(n) x (n);
2) regularly correcting masterplate that loop obtains adjusts signal and in the time interval of double channel estimating the masterplate signal in main footpath and selected each time footpath is adjusted;
The advantage that this method is compared traditional zero intermediate frequency digital receive method is, numeric field high power over-sampling has a plurality of sampled points in the single chip, in conjunction with mating relevant masterplate flexibly, can adapt to the various possible waveform of pulse process channel in the chip better; And the baseband signal of traditional zero intermediate frequency transceiver all is simple 1 or 0 information (BSPK polar modulation), the different waveform characteristic (change in polarity in duty ratio, the chip etc.) that the ultra-wideband pulse that very difficult processing correctly receives has.
As shown in Figure 4, adopted self adaptation to adjust the sign synchronization acquisition algorithm of dependent thresholds in this method, can realize very low mistake synchronous probability and missed synchronization probability, realized high performance sign synchronization, the specific implementation method is:
1) in order to prevent that accidental noise from causing searching wrong main path position, can introduce affirmation mechanism: have only main footpath correlation to surpass preset threshold, and when the position of main footpath correlation correspondence is all at same deviation post in several times are searched for continuously, think that just main path position is correct.
2) in the symbol synchronization process, for the situation of avoiding occurrent " correlation surpasses threshold value " causes the mistake symbol synchronous; Threshold value needs to improve adaptively by the following method: after capturing main path position, dependent thresholds is adjusted circuit with a dependent thresholds, be adjusted into current main directly correlation
Promptly
And be sent to channel estimator; Like this then can avoid the synchronous generation of mistake effectively.
Fig. 5 is the schematic block circuit diagram that frame synchronization is caught in the pulse ultra-broad band method of wireless reception of orthogonal lower mixing frequency digital masterplate coupling.As shown in Figure 5, the specific implementation method is:
With the output signal I ＂ (n) of Rake correlation reception input as the frame synchronization capture circuit; As the information data position, search can be found the frame separator corresponding to the output of this information data position the polarity of this signal, thus the original position of locating frame head and locator data information, and achieve frame is synchronous.
Output signal I ' the ＂ (n) of the Rake correlation reception after the frame synchronization delivers to follow-up spreading code despreading module and channel decoder, and spreading code despreading algorithm is corresponding with launching technique institute with the channel decoding algorithm, sets by system schema; Spreading code is separated and is extended to the bit stream that obtains after the channel decoding and be final data, enters data-interface and sends into the upper strata and handle.
As previously mentioned, according to the present invention, the pulse ultra-broad band wireless receiver implementation of orthogonal lower mixing frequency digital masterplate coupling has been avoided the limitation of the relevant relevant Rake receiver with pure digi-tal of traditional pure simulation to high-speed data applications, has simplified hardware configuration and has realized cost; Numeric field high power over-sampling can adapt to the various possible waveform of pulse process channel in the chip better in conjunction with mating relevant masterplate flexibly; Be beneficial to the correction of frequency departure; Support impulse radio simultaneously and have the UWB signal of carrier schemes to receive, have stronger versatility; Have the circuit design and the realization of succinct practicality and structure law, it is integrated to be easy to chip.
Claims (5)
1. the pulse ultra wide band radio signal receiving method of orthogonal lower mixing frequency digital masterplate coupling is characterized in that described method contains following steps successively:
Step 1 received signal through the radio-frequency front-end of forming by serial by antenna, low noise amplifier, I/Q two-way Analogue mixer and low pass filter successively after, obtain zero intermediate frequency analog baseband signal through frequency spectrum shift; The local oscillation signal frequency of described I/Q two-way Analogue mixer is determined by following mode: the piconet framework of being worked out according to the ultra-wideband communication system scheme and launch user-selected center frequency points of getting, choose the local oscillation signal of the sine wave signal of same frequency as this frequency mixer, this I/Q two-way local oscillation signal keeps orthogonality;
The zero intermediate frequency analog baseband signal of this AFE (analog front end) of step 2 output is delivered to the analog to digital converter (ADC) that sample rate is higher than the spreading rate twice and is carried out the sampling of zero intermediate frequency baseband signal, generates the digital baseband signal of I/Q two-way;
The I/Q two-way high-speed figure baseband signal that step 3 obtains step 2 is sent into a relevant Rake receiver of numeral coupling that is integrated on the digital integrated circuit chip, numeric field according to the following steps to I/Q two-way digital baseband signal carry out frequency and estimation regularly and correction, the numeral coupling is relevant and Rake reception and frame synchronization are caught, the output signal that obtains is carried out spreading code despreading and channel decoding successively, recovers original transmission signal:
Step 3.1 is carried out frequency correction to the I/Q two-way high-speed figure baseband signal of input successively according to the following steps with a frequency correction circuit:
Step 3.1.1 I/Q two-way digital baseband signal I ' (n), Q ' (n) sends into phase discriminator in the carrier recovery loop that comprises the polarity type carrier recovery loop, extracts phase error signal ε by following algorithm
c(n):
ε
c(n)=I ' (n) * Q ' (n), n is the sampled point label;
Step 3.1.2 is phase error signal ε
c(n) the second order digital loop filters of importing in this carrier recovery loop carries out filtering, and its sequential is:
The phase error accumulating signal φ (n+1) of n+1 sampled point is:
φ(n+1)＝φ(n)+K
1f(n)+K
2ε
c(n)
The frequency error accumulating signal f (n+1) of n+1 sampled point is:
f(n+1)＝f(n)+ε
c(n)，
Wherein, constant K
1And K
2Be the filter factor of this second order digital loop filters, when the sample rate f of described ADC
sDuring much larger than the natural frequency of loop:
ω
n=2 π f
nBe the natural angular frequency of loop, η is a damping coefficient, T
s=1/f
s
Step 3.1.3 is the input of the phase error accumulating signal φ (n+1) that obtains through described loop filtering as local digital controlled oscillator in the described loop, to adjust the frequency of local oscillation signal;
Step 3.1.4 multiplies each other the I/Q two-way digital baseband signal I (m), the Q (m) that are input to the frequency correction loop and output cos φ (n), the sin φ (n) of local digital controlled oscillator, carry out phase place rotation, thus obtain through the I/Q two-way digital baseband signal I ' of frequency correction (m), Q ' (m):
I′(m)＝I(m)×cosφ(n)+Q(m)×sinφ(n)
Q′(m)＝Q(m)×cosφ(n)-I(m)×sinφ(n)
The difference of m and n is the computing time-delay of described whole carrier recovery loop;
Step 3.2 is corrected loop with a timing and according to following steps the output signal of described frequency correction circuit is done regularly to correct:
Step 3.2.1 utilize through the I way word baseband signal I ' of frequency correction (n) with the main path position of channel estimator output, obtain main footpath signal;
Step 3.2.2 obtains main footpath correlation Corr (n) to a main footpath of signal input, described main footpath correlator;
Step 3.2.3 local masterplate signal and described main footpath signal send into one early correlator obtain a footpath correlation Corr (n-1) early, this morning, directly correlation was the cross correlation value of the local masterplate signal and the signal in main footpath signal unit sampling interval of morning, this this locality masterplate signal is produced by local masterplate signal generator, its initial value is the standard signal of transmitter emission in the known single chip, and adjusts signal according to masterplate and carry out phase delay or in advance;
Step 3.2.4 sends into a slow correlator to described local masterplate signal of step 3.2.3 and described main footpath signal, obtain a footpath correlation Corr (n+1) late, this slow footpath correlation is local masterplate signal and the main directly cross correlation value of the signal in a slow unit sampling interval of signal;
Step 3.2.5 resulting main footpath correlation Corr (n), early footpath correlation Corr (n-1), footpath correlation Corr (n+1) sends into a timing error extractor late, calculates signal of timing error ε by following formula
t(n):
ε
t(n)＝sign(Corr(n))*[Corr(n+1)-Corr(n-1)]；
The signal of timing error ε that step 3.2.6 obtains step 3.2.5
t(n) send into the timing error value that single order digital lowpass loop filter obtains accumulating:
Its sequential is: E
t(n)=E
t(n-1)+K
1ε
t(n),
Constant K
1Be the filter factor of this filter, K
1＜1;
Whether step 3.2.7 reaches preset threshold with the accumulated error value that a comparator comes determining step 3.2.6 to obtain, if reach preset threshold then the zero clearing of accumulated error value, send a masterplate simultaneously and adjust signal, control local masterplate signal generator the phase delay of local masterplate signal or carry the previous unit sampling interval, and the output masterplate is adjusted the numeral coupling relevant Rake receiving circuit of signal after giving and is regularly corrected realizing; Take to shift to an earlier date or postpone to depend on the polarity of accumulated error,, then shift to an earlier date if just, otherwise, postpone;
The I way word baseband signal I ' that the masterplate that step 3.3 obtains step 3.2.7 is adjusted signal and process frequency correction (n) sends into a relevant and Rake receiving circuit of numeral coupling, calculates the output of this Rake correlation reception circuit according to the following steps:
Step 3.3.1 sends into channel estimator to this digital baseband signal with the signal masterplate of several different deviation posts of being exported by local masterplate signal generator, search a main path position corresponding and corresponding with the big correlation of several times successively inferior path position through the signal correction computing with maximum related value, described related operation is meant: calculate the product of two input signals and add up by each sampled point, the procurement process of main path position is the process of sign synchronization; The masterplate that step 3.2.7 obtains is adjusted signal and in the time interval of double channel estimating the masterplate signal that main footpath reaches selected each time footpath is adjusted;
The main footpath that step 3.3.2 obtains according to step 3.3.1 and the position in each time footpath, (n) sending into a correlator bank respectively with the directly corresponding masterplate signal of the main footpath that obtains and selected each time through the I way word baseband signal I ' of frequency correction, the described method of 3.3.1 is carried out related operation respectively set by step, obtain the signal after numeral is mated, be sent to the Rake combiner;
Step 3.3.3Rake combiner merges time number in footpath and is at least one, no maximum;
The multipath energy that step 3.3.4Rake combiner is made of the pairing correlated results in main footpath and each time footpath is weighted than criterion than criterion or equal gain combining according to the maximum merging and adds up, obtain a total energy, i.e. the output I ＂ (n) of this Rake correlation reception circuit;
Step 4 is sent to a frame synchronization grabber to the output signal I ＂ (n) of the Rake correlation reception that step 3.3.4 obtains, according to the following steps the Rake correlation reception signal of output frame after synchronously:
Step 4.1 is sent to a vertical sync circuit to the output signal I ＂ (n) that step 3.3.4 obtains, the polarity of this signal as the information data position, search can be found the frame separator corresponding to the output of this information data position, thus the original position of locating frame head and locator data information;
The output of the Rake correlation reception circuit after step 4.2 finishes step 4.1 frame synchronization I ＂ ' as a result (n) is sent to follow-up spreading code despreading module and channel decoder.
2. the pulse ultra wide band radio signal receiving method of orthogonal lower mixing frequency digital masterplate coupling according to claim 1, it is characterized in that, according to Minimum Mean Square Error LMS algorithm, the channel estimation results that obtains according to step 3.3.1 and through the I road signal I ' after the frequency correction (n), the self adaptation masterplate adjuster by this LMS algorithm of utilization obtains a matching stencil t (n) that the self adaptation effect is arranged.
3. the pulse ultra wide band radio signal receiving method of orthogonal lower mixing frequency digital masterplate coupling according to claim 1, it is characterized in that, in order to prevent that accidental noise from causing searching wrong main path position, after step 3.3.1, introduce following confirmation method: have only main footpath correlation to surpass preset threshold, and when the position of main footpath correlation correspondence is all at same deviation post in several times are searched for continuously, think that just main path position is correct.
4. the pulse ultra wide band radio signal receiving method of orthogonal lower mixing frequency digital masterplate coupling according to claim 3, it is characterized in that, for the situation of avoiding occurrent " main footpath correlation surpasses threshold value " causes the mistake symbol synchronous, threshold value needs to improve adaptively by the following method: after capturing correct main path position, dependent thresholds is adjusted circuit with dependent thresholds, be adjusted into current main footpath correlation
, and be sent to channel estimator.
5. the pulse ultra wide band radio signal receiving method of orthogonal lower mixing frequency digital masterplate coupling according to claim 1, it is characterized in that described received signal is that the Wireless Personal Network physical layer communicates the impulse radio that is utilized or the ultra-wideband impulse signal of carrier wave is arranged.
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