CN100448148C - DC zero-voltage switched full-bridged converter of diode mutual inductor clamp - Google Patents
DC zero-voltage switched full-bridged converter of diode mutual inductor clamp Download PDFInfo
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- CN100448148C CN100448148C CNB2007100192618A CN200710019261A CN100448148C CN 100448148 C CN100448148 C CN 100448148C CN B2007100192618 A CNB2007100192618 A CN B2007100192618A CN 200710019261 A CN200710019261 A CN 200710019261A CN 100448148 C CN100448148 C CN 100448148C
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Abstract
The invention is concerned with zero-voltage-switching full bridge DC converter to clamp diode with current transformer. It belongs to DC converter and relates to DC power supply Vin, two invert bridge legs, resonant inductance, clamp circuit, transformer, rectifier and filtering circuit, current transformers, rectifier circuit of current transformers and DC power supply Vc. The clamp diode circuit eliminates voltage surge, pinnacle and the wastage arose by the inverted renew to the output rectifying tube, reduces the voltage stress of the output rectifying tube. The current transformer quickly reduces the current and improves the work condition of clamp diode.
Description
One, technical field
The Zero-voltage switch full-bridge direct current converter that diode of the present invention adds the current transformer clamp belongs to the DC converter of transformation of electrical energy device.
Two, background technology
In powerful DC converting occasion, full-bridge converter is realized easily soft switch and is adopted constant frequency control to obtain using widely owing to switching tube.Recent two decades comes, and soft switch control strategy of a lot of full-bridge converters and circuit topology have occurred.Phase shifting control full-bridge converter of zero-voltage switch and phase shifting control zero-voltage and zero-current switch full-bridge converter all can be realized the soft switch of switching tube.But no matter be zero voltage switch or zero-voltage and zero-current switch full-bridge converter, because existing oppositely, recovers the secondary rectifier diode, the leakage inductance of transformer (or additional resonant inductance) is just together with the junction capacitance generation resonance of exporting rectifying tube, can bear the peak voltage of twice at least on the diode, therefore must select kenotron, this also just means the forward conduction voltage drop that increases the secondary rectifier diode.Richard Redl, Nathan O.Sokal andLaszlo Balogh, " A novel soft-switching full-bridge DC/DC converter:analysis; design considerations; and experimental results at 1.5kW; 100kHz; " in Proc.IEEE PESC, 1990, pp.162-172 discloses a kind of Zero-voltage switch full-bridge direct current converter, a resonant inductance and two clamping diodes are introduced in former limit at transformer, have not only kept the soft switching characteristic of switching tube, have eliminated due to voltage spikes and voltage oscillation on the output rectifying tube simultaneously effectively.
But, when this converter is operated in underloading even no-load condition, the junction capacitance discharge regime of clamping diode, the energy that discharges can't be transferred to load end, can only be stored in the resonant inductance, force the many conductings of clamping diode once, electric current is the poor of resonant inductance electric current and transformer primary current in the clamping diode, this moment, the transformer primary current was approximately zero, electric current approximates the resonant inductance electric current in the clamping diode, because resonant inductance is by the switching tube of leading-bridge and clamping diode short circuit, inductive current remains unchanged, so electric current remains unchanged in approximate half switch periods in the clamping diode.Two clamping diodes are a switch periods alternate conduction, and are straight-through easily if the turn-off speed of clamping diode is fast inadequately, cause the damage of clamping diode.
Three, summary of the invention
The objective of the invention is to defective at above-mentioned converter, develop the Zero-voltage switch full-bridge direct current converter that a kind of diode adds the current transformer clamp, no matter which kind of loading condition converter is operated under can reduce to flow through electric current in the clamping diode effectively fast, improves conversion efficiency
Diode adds the Zero-voltage switch full-bridge direct current converter of current transformer clamp, comprises DC power supply V
In, first inverter bridge leg and second inverter bridge leg, resonant inductance, clamp circuit, isolating transformer, rectification and filter circuit, current transformer, current transformer rectification circuit, DC power supply V
cWherein the first inverter bridge leg forward of being made up of first switching tube and the 3rd switching tube series connection back is connected in parallel on DC power supply V
InPositive-negative output end; The same forward of being made up of second switch pipe and the 4th switching tube series connection back of second inverter bridge leg is connected in parallel on DC power supply V
InPositive-negative output end, four switching tubes of above-mentioned first to fourth individual diodes also in parallel separately and a parasitic capacitance; Clamp circuit is composed in series by two clamping diode forwards, and this clamp circuit is connected in reverse parallel in the first inverter bridge leg two ends and the second inverter bridge leg two ends, clamping diode parasitic capacitance also in parallel separately; Two secondary windings with the number of turn of the secondary of isolating transformer are in series, and wherein the series connection point of two secondary windings links to each other with the negative terminal of current rectifying and wave filtering circuit, and two other disjunct terminal links to each other with two anodes of rectification and filter circuit respectively; Resonant inductance and the former limit of above-mentioned isolating transformer windings in series, these series arm two ends are connected in the series connection point of two switching tubes of the series connection point of two switching tubes of first inverter bridge leg and second inverter bridge leg respectively; One end of the former limit of current transformer winding links to each other with the series connection point of the former limit of resonant inductance and isolating transformer winding, the other end links to each other with two clamping diode series connection points of clamp circuit, the secondary of current transformer connects the current transformer rectification circuit, and the current transformer rectification circuit has two kinds of rectifier systems: way of full-wave rectification and full-bridge rectification mode.When the current transformer rectification circuit adopted way of full-wave rectification, the secondary of current transformer was two identical windings of the number of turn, and the different name end of two windings links to each other, and disjunct in addition two terminals are connected on two inputs of current transformer rectification circuit respectively; When the current transformer rectification circuit adopted the full-bridge rectification mode, the secondary of current transformer had only a winding, connects two inputs of current transformer rectification circuit respectively; The output of current transformer rectification circuit meets DC power supply V
cAmong the present invention, the alternative DC power supply V of three place's DC power supply is arranged
c, first kind of connection: the positive-negative output end of current transformer rectification circuit meets input DC power V respectively
InPositive and negative terminal; Second kind of connection: the positive-negative output end of current transformer rectification circuit connects output voltage V respectively
oPositive and negative terminal; The third connection: the positive-negative output end of current transformer rectification circuit connects the positive and negative terminal to the auxiliary voltage source of control and drive circuitry respectively;
The present invention's major technique characteristics compared with prior art are, owing to added the clamping diode circuit, the voltage oscillation and the due to voltage spikes that cause because of the reverse recovery of exporting rectifying tube have been eliminated, reduced the voltage stress of output rectifying tube, and eliminated of the loss of output rectifying tube because of oppositely recovering to cause, simultaneously, the current transformer of introducing, can reduce to flow through electric current in the clamping diode effectively fast, improve operational environment at clamping diode.
Four, description of drawings
Accompanying drawing 1 and accompanying drawing 2 are two kinds of embodiment electrical block diagrams of Zero-voltage switch full-bridge direct current converter of the present invention.
Accompanying drawing 3 and accompanying drawing 4 are respectively the groundwork waveform schematic diagram of Zero-voltage switch full-bridge direct current converter of the present invention at fully loaded and underloading (or unloaded).
Accompanying drawing 5 ~ 21st, the equivalent circuit structure schematic diagram of Zero-voltage switch full-bridge direct current converter of the present invention.
Main designation in the above-mentioned accompanying drawing: V
In, supply voltage.Q
1～Q
4, switching tube.C
1～C
4, parasitic capacitance.D
1～D
4, body diode.L
r, resonant inductance.T
r, isolating transformer.D
5, D
6, clamping diode.D
R1, D
R2, output rectifier diode.C
DR1, C
DR2, output rectifier diode junction capacitance.C
5, C
6, clamping diode junction capacitance.L
f, filter inductance.C
f, filter capacitor.R
Ld, load.V
o, output voltage.V
Rect, voltage after the rectification of transformer secondary.V
AB, A and B point-to-point transmission voltage.T
s, current transformer.The turn ratio of n, the former secondary of current transformer.D
R3～D
R6, current transformer output rectifier diode.V
c, auxiliary control source voltage.
Five, embodiment
Shown in accompanying drawing 1 and the accompanying drawing 2 is two kinds of electrical block diagrams of the Zero-voltage switch full-bridge direct current converter of the auxiliary winding of band transformer.By DC power supply V
In, two inverter bridge leg 1 and 2, resonant inductance 3, clamp circuit 4, isolating transformer 5, rectification and filter circuit 6, current transformer 7, current transformer rectification circuit 8 and auxiliary control source voltage V
cForm.Q
1～Q
4Be four main switches, D
1～D
4Be respectively switching tube Q
1～Q
4Body diode, C
1～C
4Be respectively switch Q
1～Q
4Parasitic capacitance, L
rBe resonant inductance, T
rBe isolating transformer, D
5, D
6Be clamping diode, D
R1And D
R2Be the output rectifier diode, L
fBe output inductor, C
fBe output filter capacitor, R
LdBe load, T
sBe current transformer, D
R3～D
R6It is current transformer output rectifier diode.This converter using phase shifting control, switching tube Q
1And Q
3Be ahead of switching tube Q respectively
4And Q
2A phase place claims switching tube Q
1And Q
3First inverter bridge leg of forming is a leading-bridge, switching tube Q
2And Q
4Second inverter bridge leg of forming then is a lagging leg.Resonant inductance 3 and above-mentioned isolating transformer 5 former limit windings in series, two switching tube Q of the resonant inductance other end and first inverter bridge leg 1 in this series arm
1, Q
3Series connection point A link to each other the other end of isolating transformer 5 former limit windings and two switching tube Q of second inverter bridge leg 2
2, Q
4Series connection point B link to each other; Characteristics of the present invention are the series connection point C of resonant inductance 3 and isolating transformer 5 former limit windings and two clamping diode D of clamp circuit 4
5, D
6Series connection point D does not directly link to each other, but seals in the former limit winding of current transformer 7 between a C and some D.Current transformer 7 secondary windings connect current transformer rectification circuit 8; The output of current transformer rectification circuit 8 meets direct voltage source V
c9, among the present invention, the alternative DC power supply V of three place's DC power supply is arranged
c9, the first kinds of connections: the positive-negative output end of current transformer rectification circuit 8 meets input DC power V respectively
InPositive and negative terminal; Second kind of connection: the positive-negative output end of current transformer rectification circuit 8 connects output voltage V respectively
oPositive and negative terminal; The third connection: the positive-negative output end of current transformer rectification circuit 8 connects the positive and negative terminal to the auxiliary voltage source of control and drive circuitry respectively; According to V
cAmplitude can select the rectifier system of current transformer rectification circuit 8, if V
cAmplitude is lower, can select way of full-wave rectification shown in the accompanying drawing 1 for use.If V
cAmplitude can be selected full-bridge rectification mode shown in the accompanying drawing 2 for use than higher.
Be main circuit structure with accompanying drawing 1 below, 3～13 narrate concrete operation principle of the present invention in conjunction with the accompanying drawings.The operation principle difference of the present invention when different loads discussed below in two kinds of situation, and a kind of situation is fully loaded, and main waveform as shown in Figure 3; Another kind of situation is a underloading, and main waveform as shown in Figure 4.
Before analyzing, make the following assumptions: 1. all switching tubes and diode are desirable device, rectifier diode D
R1And D
R2And clamping diode D
5And D
6Except, they all equivalence be an ideal diode and an electric capacity parallel connection, recover to be used for simulated inverse; 2. all inductance, electric capacity and transformer are ideal element.
At first analyze the operation principle that the present invention is operated in full load conditions.By accompanying drawing 3 as can be known whole converter a switch periods 18 kinds of switch mode are arranged, be respectively [t
0[t in the past],
0, t
1], [t
1, t
2], [t
2, t
3], [t
3, t
4], [t
4, t
5], [t
5, t
6], [t
6, t
7], [t
7, t
8], [t
8, t
9], [t
9, t
10], [t
10, t
11], [t
11, t
12], [t
12, t
13], [t
13, t
14], [t
14, t
15], [t
15, t
16], [t
16, t
17], [t
17, t
18] (seeing accompanying drawing 3), wherein, [t
0In the past, t
9] be the preceding half period, [t
9, t
18] be the later half cycle.Below the working condition of each switch mode is made a concrete analysis of.
1. switch mode 1[t
0[corresponding to accompanying drawing 5] in the past]
t
0In the past, switching tube Q
1And Q
4Conducting, secondary rectifier diode D
R1Conducting, rectifier diode D
R2End.
2. switch mode 2[t
0, t
1] [corresponding to accompanying drawing 6]
t
0Moment on-off switching tube Q
1, primary current i
pGive capacitor C
1Capacitor C is given in charging simultaneously
3Discharge, the A point voltage descends.Because capacitor C is arranged
1And C
3, switching tube Q
1Be that no-voltage is turn-offed.Junction capacitance C
DR2Discharge, primary current i
pWith resonant inductance i
LrResonance descends.Because C point current potential is all the time greater than zero, so clamping diode D
6Can not conducting.Simultaneously because junction capacitance C
DR2Discharge, secondary voltage reduces, and original edge voltage reduces thereupon, and B point voltage clamp is zero, so C point current potential must be less than input voltage V
In, so clamping diode D
6Also can not conducting.t
1Constantly, capacitor C
3Voltage drop to zero, promptly A point current potential reduce to zero, diode D
3Conducting.
3. switch mode 3[t
1, t
2] [corresponding to accompanying drawing 7]
Diode D
3After the conducting, can no-voltage open switching tube Q
3When A point current potential reduced to zero, the C point voltage did not also drop to zero, at this moment rectifier diode D
R2Junction capacitance C
DR2Continue discharge, the resonant inductance current i
LrWith primary current i
pContinue to descend.t
2Constantly, rectifier diode D
R2Junction capacitance C
DR2Discharge finishes, diode D
R2Conducting, C point voltage drop to zero.
4. switch mode 4[t
2, t
3] [corresponding to accompanying drawing 8]
Rectifier diode D
R1And D
R2Conducting simultaneously, in zero-bit, A, B, 3 current potentials of C are zero at this moment, the resonant inductance current i with the former secondary voltage pincers of transformer
LrWith primary current i
pEquate, be in nature afterflow state, and remain unchanged always.
5. switch mode 5[t
3, t
4] [corresponding to accompanying drawing 9]
t
3Moment on-off switching tube Q
4, current i
LrGive capacitor C
4Capacitor C is given in charging simultaneously
2Discharge.Because capacitor C
2And C
4Existence, switching tube Q
4Be that no-voltage is turn-offed.Because rectifier diode D
R1And D
R2All conductings, so the former secondary voltage of transformer is zero, voltage V
ABDirectly be added in resonant inductance L
rOn, therefore, during this period, resonant inductance L in fact
rWith junction capacitance C
2, C
4In resonance work.To t
4Constantly, capacitor C
4Voltage rise to DC power supply voltage V
In, capacitor C
2Voltage drop to zero, diode D
2The nature conducting.
6. switch mode 6[t
4, t
5] [corresponding to accompanying drawing 10]
Diode D
2After the conducting, can no-voltage open switching tube Q
2This moment primary current i
pBe not enough to provide load current, rectifier diode D
R1And D
R2Conducting simultaneously, the former secondary voltage of transformer are zero, so DC power supply voltage V
InAll be added in resonant inductance L
rTwo ends, the resonant inductance current i
LrEqual primary current i
p, both are linear to descend.
7. switch mode 7[t
5, t
6] [corresponding to accompanying drawing 11]
To t
5Constantly, resonant inductance current i
LrWith primary current i
pAll drop to zero, and negative direction increases primary current i
pOppositely the back is by switching tube Q
2And Q
3Path is provided, and load current still provides the loop by two rectifier diodes, and the former secondary voltage of transformer is still zero.Up to t
6Constantly, primary current i
pReach the load current of conversion, rectifier diode D to former limit
R1Turn-off.
8. switch mode 8[t
6, t
7] [corresponding to accompanying drawing 12]
At t
6Constantly, resonant inductance L
rWith rectifier diode junction capacitance C
DR1Rectifier diode D is given in resonance work
R1Junction capacitance C
DR1Charging, primary current i
pWith resonance inductive current i
LrContinuing increases.
During this period of time, the B point voltage is fixed on DC power supply voltage V
In, and the former limit of transformer winding voltage V
BCBecause rectifier diode junction capacitance C
DR1Charging also rise simultaneously, so C point current potential is descending always.To t
7Constantly, rectifier diode junction capacitance C
DR1Voltage rise to 2V
InN
2/ n
1, this moment, the C point voltage dropped to zero, clamping diode D
6Conducting is with voltage V
BCPincers is at DC power supply voltage V
In, so rectifier diode junction capacitance C
DR1Voltage by pincers at 2V
InN
2/ n
1
9. switch mode 9[t
7, t
8] [corresponding to accompanying drawing 13]
As clamping diode D
6After the conducting, primary current i
pStep drops to the filter inductance electric current of converting former limit, and negative sense increases.Have electric current from current transformer T this moment
sThe end of the same name of former limit winding flows out, and senses secondary and flows into from end of the same name, makes current transformer export rectifier diode D
R4Conducting, direct voltage V
cOppositely be added on the secondary winding, sense former limit, voltage is V
cN, voltage direction are that the right side is just being born in a left side, and promptly D point current potential is higher than the C point, because the D point voltage is zero, so bear the positive right voltage of bearing in a left side on the resonant inductance, and size is V
cN, so resonant inductance current i
LrSnap back reduces.It and primary current i
pDifference from clamping diode D
6In flow through.To t
8Constantly, current i
pAnd i
LrEquate that this mode finishes, clamping diode D
6Turn-off.
10. switch mode 10[t
8, t
9] [corresponding to accompanying drawing 14]
Clamping diode D
6Turn-off, do not have electric current to flow through current transformer T
s, current transformer output rectifier diode D
R4Turn-off.Circuit enters steady operation, and former limit provides energy to secondary, primary current i
pWith the resonant inductance current i
LrEquate.
Following surface analysis the present invention is operated in the operation principle of underloading situation.By accompanying drawing 4 as can be known whole converter a switch periods 12 kinds of switch mode are arranged, be respectively [t
0[t in the past],
0, t
1], [t
1, t
2], [t
2, t
3], [t
3, t
4], [t
4, t
5], [t
5, t
6], [t
6, t
7], [t
7, t
8], [t
8, t
9], [t
9, t
10], [t
10, t
11], (seeing accompanying drawing 4), wherein, [t
0In the past, t
5] be the preceding half period, [t
5, t
11] be the later half cycle.Below the working condition of each switch mode is made a concrete analysis of.
1. switch mode 1[t
0[corresponding to accompanying drawing 15] in the past]
t
0In the past, switching tube Q
1Conducting, switching tube Q
3Turn-off, but, do not have electric current to give parasitic capacitance C because transformer primary current and resonance inductive current all are zero
3Charging, A, B, C, D four point voltages all are DC power supply voltage V
In, so the former secondary voltage of transformer is zero.Filter inductance electric current this moment zero passage, secondary rectifier diode D
R1And D
R2End the junction capacitance C of filter inductance and output rectifier diode
DR1, C
DR2Resonance takes place.
2. switch mode 2[t
0, t
1] [corresponding to accompanying drawing 16]
t
0Constantly open switching tube Q
4, switching tube Q
4Be open-minded firmly, the B point voltage drops to 0, transformer original edge voltage rising DC power supply voltage V
In, secondary voltage rises, voltage V after the transformer secondary voltage is greater than the rectification of transformer secondary
RectAfter, secondary rectifier diode D
R1Conducting.The filter inductance electric current begins to rise, and transformer primary current and resonance inductive current rise together.The A point voltage remains on DC power supply voltage V
InConstant, C, D point voltage slightly descend, and remain on DC power supply voltage V substantially
In
3. switch mode 3[t
1, t
2] [corresponding to accompanying drawing 17]
t
1Moment on-off switching tube Q
1, open switching tube Q
3, the A point voltage drops to 0 rapidly, and the resonant inductance electric current begins to descend resonant inductance L
r, clamping diode D
5, D
6Junction capacitance C
5, C
6And secondary rectifier diode D
R2Junction capacitance C
DR2Carry out resonance, junction capacitance C
6With junction capacitance C
DR2Discharge, the junction capacitance C of clamping diode
5Charging.C, D point voltage descend together, and have electric current from current transformer T this moment
sThe end of the same name of former limit winding flows out, and senses secondary and flows into from end of the same name, makes current transformer export rectifier diode D
R4Conducting, direct voltage V
cOppositely be added on the secondary winding, sense former limit, voltage is V
cN, voltage direction are that the right side is just being born in a left side, and promptly D point current potential is higher than the C point.Flow through secondary rectifier diode D
R1Electric current reduce, if load is very light, dropped to before 0 at the C point voltage, flow through secondary rectifier diode D
R1Electric current dropped to 0, secondary rectifier diode D
R1End secondary rectifier diode D
R1, D
R2Junction capacitance C
DR1, C
DR2Series connection and resonance inductance L
r, clamping diode D
5, D
6Junction capacitance C
5, C
6Continue resonance, resonant inductance electric current and transformer primary current continue to reduce, and C, D point voltage continue to descend, up to t
2Constantly, the D point voltage drops to 0, clamping diode D
6Conducting.
4. switch mode 4[t
2, t
3] [corresponding to accompanying drawing 18]
Clamping diode D
6Conducting, D point voltage by pincers 0, current transformer T
sVoltage is V on the winding of former limit
cN, voltage direction be the negative right side, a left side just, so the D point voltage by pincers at V
cN, this moment, the B point voltage was 0, so transformer T
rOriginal edge voltage also is V
cN converts secondary, is approximately 0, secondary rectifier diode D
R1, D
R2Junction capacitance C
DR1, C
DR2Continue discharge, the discharging current equal and opposite in direction is so flow through transformer primary current i
pBe 0, resonant inductance electric current and primary current i
pDifference from clamping diode D
6In flow through.Bear the positive right negative voltage in a left side this moment on the resonant inductance, size is V
cN, so resonant inductance current i
LrSnap back reduces.
5. switch mode 5[t
3, t
4] [corresponding to accompanying drawing 19]
t
3Constantly, secondary rectifier diode D
R1, D
R2Junction capacitance C
DR1, C
DR2Discharge into 0, rectifier diode D
R1And D
R2Conducting simultaneously, their electric current is respectively half of filter inductance electric current.The resonant inductance electric current continues to reduce.
6. switch mode 6[t
4, t
5] [corresponding to accompanying drawing 20]
t
4Constantly, the filter inductance electric current drops to 0 back oppositely, filter inductance and secondary rectifier diode D
R1, D
R2Junction capacitance generation resonance.
7. switch mode 7[t
5, t
6] [corresponding to accompanying drawing 21]
t
4Constantly, resonant inductance electric current and clamping diode D
6Electric current drops to 0, clamping diode D
6, current transformer output rectifier diode D
R4End.Circuit enters steady operation, transformer T
rPrimary current, resonant inductance electric current all are 0.
As seen from the above description, the Zero-voltage switch full-bridge direct current converter of the belt current instrument transformer of the present invention's proposition has following advantage:
1. clamping diode can have been eliminated due to voltage spikes and the voltage oscillation on the output rectifying tube effectively, reduces the voltage stress of output rectifying tube.
2. owing to increased current transformer, can reduce to flow through electric current in the clamping diode effectively fast, improve conversion efficiency.
3. improve the condition of work of clamping diode under the underloading situation, improve the reliability of system.
4. can realize the zero voltage switch of switching tube.
Claims (3)
1, a kind of diode adds the Zero-voltage switch full-bridge direct current converter of current transformer clamp, comprises DC power supply V
In, first inverter bridge leg (1) and second inverter bridge leg (2), resonant inductance (3), clamp circuit (4), isolating transformer (5), rectification and filter circuit (6), wherein by the first switching tube (Q
1) and the 3rd switching tube (Q
3) first inverter bridge leg (1) forward formed of series connection back is connected in parallel on DC power supply V
InPositive-negative output end; By second switch pipe (Q
2) and the 4th switching tube (Q
4) the same forward of second inverter bridge leg (2) formed of series connection back is connected in parallel on DC power supply V
InPositive-negative output end, four switching tube (Q of above-mentioned first to fourth
1, Q
2, Q
3, Q
4) individual diodes also in parallel separately and a parasitic capacitance; Clamp circuit (4) is by two clamping diode (D
5, D
6) forward is composed in series, this clamp circuit (4) is connected in reverse parallel in first inverter bridge leg (1) two ends and second inverter bridge leg (2) two ends, clamping diode (D
5, D
6) parasitic capacitance also in parallel separately; Two secondary windings with the number of turn of the secondary of isolating transformer (5) are in series, and wherein the series connection point of two secondary windings links to each other with the negative terminal of current rectifying and wave filtering circuit (6), the first rectifier diode (D of the end of the same name of the first secondary winding and rectification and filter circuit (6)
R1) negative electrode link to each other the different name end of the second secondary winding and the second rectifier diode (D
R2) negative electrode link to each other; Resonant inductance (3) and the former limit of above-mentioned isolating transformer (5) windings in series, these series arm two ends are connected in two switching tube (Q of first inverter bridge leg (1) respectively
1, Q
3) series connection point (A) and two switching tube (Q of second inverter bridge leg (2)
2, Q
4) series connection point (B); It is characterized in that also comprising current transformer (7), current transformer rectification circuit (8), DC power supply V
c(9), an end of the former limit of described current transformer (7) winding links to each other two clamping diode (D of the other end and clamp circuit (4) with the series connection point (C) of resonant inductance (3) with the former limit of isolating transformer (5) winding
5, D
6) series connection point (D) links to each other, the secondary of current transformer (7) connects current transformer rectification circuit (8); Described current transformer rectification circuit (8) adopts way of full-wave rectification, and the secondary of current transformer (7) is two identical windings of the number of turn, and the different name end of two windings links to each other, tie point and DC power supply V
c(9) negative terminal links to each other, the 3rd rectifier diode (D of first secondary winding end summation current transformer of the same name rectification circuit (8)
R3) negative electrode link to each other the 4th rectifier diode (D of the second secondary winding different name end and current transformer rectification circuit (8)
R4) negative electrode link to each other.
2, diode according to claim 1 adds the Zero-voltage switch full-bridge direct current converter of current transformer clamp, it is characterized in that, the way of full-wave rectification that wherein said current transformer rectification circuit (8) adopts is replaced by the full-bridge rectification mode, the secondary of the current transformer (7) of this moment has only a winding, its two ends connect two inputs of current transformer rectification circuit (8) respectively, and the output of current transformer rectification circuit (8) meets DC power supply Vc (9).
3, diode according to claim 1 adds the Zero-voltage switch full-bridge direct current converter of current transformer clamp, it is characterized in that, described current transformer rectification circuit (8) and DC power supply are connected with the connection at one of three places, to substitute DC power supply V
c(9): the connection at first place is that the positive-negative output end of current transformer rectification circuit (8) meets input DC power V respectively
InPositive and negative terminal; The connection at second place is that the positive-negative output end of current transformer rectification circuit (8) connects output voltage V respectively
oPositive and negative terminal; The connection at the 3rd place is that the positive-negative output end of current transformer rectification circuit (8) connects the positive and negative terminal to the auxiliary voltage source of control and drive circuitry respectively.
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| CN101562399B (en) * | 2009-05-08 | 2011-03-30 | 华中科技大学 | Full-bridge double-output direct current-alternating current converter |
| CN101572488B (en) * | 2009-06-09 | 2011-08-10 | 华中科技大学 | Dual output DC-DC converter for multiplexing bridge arm |
| CN101814840B (en) * | 2010-03-11 | 2012-04-25 | 南京航空航天大学 | Zero voltage switch full-bridge direct-current converter with diode and auxiliary transformer clamping |
| CN102097972B (en) * | 2011-02-15 | 2013-06-19 | 南京航空航天大学 | Resonance device used in driver of piezoelectric actuator |
| CN103098360A (en) | 2011-08-12 | 2013-05-08 | 英特赛尔美国股份有限公司 | Clamp circuits for power converters |
| CN110061650B (en) * | 2019-05-17 | 2020-11-06 | 南京航空航天大学 | Single-stage isolated three-phase bidirectional AC/DC converter and control method |
| CN110474550B (en) * | 2019-08-21 | 2020-11-10 | 阳光电源股份有限公司 | Flying capacitor type NPC three-level topology |
| CN112713795A (en) * | 2020-12-30 | 2021-04-27 | 燕山大学 | Single-phase high-frequency chain matrix type inverter and modulation method |
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