RU2803413C1 - Method of pulse-doppler radiolocation and device with autodyne transmitter for its implementation - Google Patents

Abstract

FIELD: radio equipment.

SUBSTANCE: invention relates to systems of short-range radar (SRR) with determination of range by measuring the delay time of a radio pulse reflected from an object of location and the relative speed of movement according to the Doppler frequency shift. It can be used in systems for detecting and determining the parameters of movement of targets in a controlled area, for example, in systems for preventing collisions of vehicles. In the claimed method, radio pulses are obtained at the output of the RF generator by impacting the RF generator with a sequence of paired trigger pulses with steep fronts, while forming coherent oscillations inside the paired radio pulses relative to the trigger pulses. The first radio pulses of each pair are probing, and the second pulses are receiving. The oscillation frequency of the probing radio pulses is switched to the value of the intermediate frequency (IF) relative to the frequency of the receiving radio pulses, the probing radio pulses are emitted into the controlled space and radio pulses reflected from the target are received and mixed with the natural oscillations of the RF generator during the formation of receiving radio pulses in it, causing autodyne changes in the amplitude of oscillations in the RF generator as well as current and/or voltage in its power supply circuit in the form of RF radio pulses, after which autodyne changes are isolated in the form of RF radio pulses. The RF radio pulses are mixed in a quadrature mixer with the reference IF oscillations and converted to the low Doppler frequency region in the form of quadrature video pulses and , after which a sample of instantaneous values of quadrature video pulses and is stored, according to the values of which further information is obtained about the presence of the target, the range and parameters of its movement. A pulse-Doppler radar device with an autodyne transceiver for implementing the method is also claimed.

EFFECT: increased range of the SRR, increased reliability of detection and the accuracy of determining the parameters of the target movement by achieving coherence of probing oscillations and receiving radio pulses, as well as reducing the consumption of the supply current and the level of radiation leakage due to the transfer of the autodyne generator to a pulsed mode of operation, as well as simplifying the design of the high-frequency (HF) part of the SRR.

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Description

The invention relates to short-range radar systems (SLRS) with range determination by measuring the delay time of a radio pulse reflected from a location object and the relative speed of movement according to the Doppler frequency shift. Can be used in systems for detecting and determining the movement parameters of targets in a controlled area, for example, in vehicle collision avoidance systems.

There are known devices for radio pulse location of a controlled space with determination of the range to a target by measuring the delay time of radio pulses reflected from the object, stated, for example, in [1-19]. The operating principle of these devices is based on the time separation of the processes of generating probing and receiving reflected radio signals (see pp. 334-363, [20]). In this case, the reception of reflected radio signals is carried out at a certain period of time after the emission of probing radio pulses, which correspond to the target detection range. The devices contain sources of probing radio pulses, separate antennas for reception and transmission or antenna switches and one common antenna, receivers. The disadvantages of such devices are the complexity and bulkiness of the design of the microwave transceiver module, which creates a problem in their on-board design, in which efficiency, small dimensions, weight and cost of components are the determining factors.

There are known radar devices that also operate in the radio pulse mode [21-27]. These devices are made on the basis of a self-oscillator in a super-regenerative mode, which combines the functions of a transmitter of probing radio pulses and a receiver of radio signals reflected from the target. Thanks to this combination, super-regenerative transceivers provide the simplest microwave module design. The disadvantage of devices based on superregenerators is the low accuracy of determining the relative speed of the target due to the lack of Doppler selection of signals received from the target.

There are known devices in which the functions of transmitter and receiver are also performed by a single cascade - a self-oscillator (actually, an autodyne), operating in the so-called autodyne mode [26-35]. The principle of operation of these devices is based on the autodyne effect, which consists of changes with the Doppler frequency of oscillation parameters (amplitude and frequency), as well as current and/or voltage in the bias circuit of the active element under the influence of radiation reflected from the target. Registration (selection) of these changes as an autodyne signal and its processing provide information about the relative speed of the target using the Doppler frequency, and information about the range from measuring the amplitude of the signal reflected from the target and the Doppler frequency. The disadvantage of such devices is the low accuracy of determining the distance to the target.

There are known devices in which an autodyne transceiver operates in the mode of pulse modulation of radiation [36-51]. In this case, the reception of the reflected radio signal and its isolation are carried out during the emission of the probing radio pulse, when the time the delay of the reflected radio signal is less than the duration sounding radio pulses ( ) [52,53]. In this case, the process of extracting information about the reflected signal is carried out based on the difference in the phases of the emitted and received radio signals due to their mutual coherence. The relative movement of the target and the radar device causes corresponding changes in the phase difference of these radio signals. These phase changes in the power circuit of the autodyne generator and/or at the output of the amplitude detector connected to the oscillatory system of the autodyne are converted into video pulses with a duration . Isolating and “stretching” in time these video pulses for the period of their repetition by temporary gating by a sample-and-hold circuit and subsequent filtering, the Doppler signal is generated. This signal is used to measure speed, determine the target’s current position relative to the initial one, and solve the problem of detecting it.

Structurally simple location devices with radio pulse radiation are also known [54,55], made on the basis of an autodyne generator. The devices contain a series-connected unit for generating clock pulses, an autodyne generator with an antenna attached to it, and means for isolating and amplifying the autodyne signal. These devices use the principle of forming paired radio pulses at the same frequency, of which the first radio pulse is a sounding pulse, and the second is a receiving pulse. In this case, the reflected radio pulse, during its reception, is mixed with the second radio pulse of the same pair generated by the autodyne generator, when the delay time of the reflected radio pulse coincides with the time interval between the pairs. As a result of this mixing, an autodyne reaction occurs in the form of a change in its operating mode: the amplitude of oscillations, current and/or voltage in the generator power circuit. Isolating these changes as a useful signal provides information about the target. In the device according to the patent [54], these mode changes occur with the Doppler frequency, which makes it possible to select a target both by range and by the speed of its movement.

The disadvantages of the devices stated in the materials [36-54] are the inability to detect stationary and slowly moving objects and determine the current distance to the target, since their operating principle is based on receiving and processing Doppler signals [52,53]. At the same time, flicker fluctuations of the oscillation parameters of the autodyne generator limit the maximum range of the SBRL.

The method of radio pulse location of the device stated in [55] consists of generating an amplitude-modulated (AM) first radio pulse of a pair, emitting it in the direction of the target, receiving part of the radiation reflected from the target, and exposing the received radiation to the autodyne generator during the formation of the next radio pulse of the pair, isolating the autodyne signal at the AM frequency of the emitted radio pulse in the generator, amplifying and comparing the amplitude of the autodyne signal with the threshold level.

An analysis of the technical solution stated in [55] showed that this device uses an energetically unfavorable type of modulation—amplitude—as probing radiation. With this type of modulation, even at 100% modulation depth, the power of the lateral components of the oscillation is approximately one-third (0.375) relative to the peak power value or half of the power of the unmodulated carrier oscillation (see page 88, [56]). In addition, it is known that receiving a signal from AM using an autodyne generator is also not optimal. The impact of a reflected radio signal on an autodyne oscillator with the same carrier frequency causes its capture. In this case, the AM of the influencing radio signal in a synchronized self-oscillator is limited (see pp. 54-55, [57], pp. 149-164, [58]). For this reason, the resulting response of the self-oscillator as a radar receiving device to the influence of an AM signal is reduced or may be completely absent. Therefore, the known device [55] has significant losses in the energy of signals, both transmitter and receiver, and, accordingly, in the range of its operation as a radar device. An additional disadvantage of this device is the low accuracy of determining the relative speed of the target due to the lack of Doppler selection of target signals, since its operating principle is based on obtaining range information only from the delay time of the reflected signals.

There are also known technical solutions that are proposed in the methods and device of pulse-Doppler location for detecting targets in a controlled range selection zone and determining their movement parameters, described in patents [59-62]. The essence of the inventions for the method and device is most fully described in US patent US5864313, publ. 06/26/1999, MPK⁶ G01S7/28. Process for determining the intermediate frequency deviation in frequency pulsed radar systems / R. Speck et al. [62]. In terms of technical essence, operating principle and achieved positive effect, the device and methods described in this patent are the closest analogues (prototypes) to the proposed technical solution.

The prototype device contains (see Fig. 1, [62]) an antenna, a high-frequency (HF) generator with the ability to electrically control the frequency (voltage controlled generator - VCO), an (HF) mixer, the first and second controlled RF signal switches (UPVCS) , power divider (PD) of difference frequency (RF) signals, first and second quadrature mixers of RF signals, phase shifter for two quadrature outputs 0° and 90° of the intermediate frequency (IF) reference signal, first and second sample-and-hold devices (SSD), synchronization and control unit (SCU). The high-frequency port of the RF generator is connected to the switched terminal of the first UPVChS, the antenna is connected to the switched terminal of the second UPVChS, the S terminals of the first and second UPVChS are connected to each other, the E pin of the first UPVChS is connected to the heterodyne input of the RF mixer, the E pin of the second UPVChS is connected to the signal gathering of the RF mixer , and the output of the RF mixer is connected to the input of the power divider of RF signals, the outputs of which are connected to the signal inputs of the first and second quadrature mixers of RF signals, while the outputs of the latter are connected to the signal inputs of the first and second UVH. The first output of the BSU is connected to the control input of the RF generator frequency, the second output of the BSU is connected to the control inputs of the UPVChS, the third output of the IF reference signal is connected to the input of the phase shifter, the quadrature outputs of which are connected to the heterodyne inputs of the first and second quadrature mixers of the RF signals, and the fourth output of the BSU is connected to the UVH control inputs.

The BSU contains a clock generator, the outputs of which are connected to the input of the pulse shaper for controlling the UPVChS and the frequency of the RF generator, as well as to the input of the frequency multiplier of the IF reference signal.

According to the description of the principle of operation set forth in [62], the method of pulse-Doppler location of the prototype device consists in the fact that the frequency of the output oscillations of the HF generator during the formation of probing radio pulses is switched to an IF value relative to the oscillation frequency during the rest of the repetition period of the probing radio pulses, when RF generator oscillations are heterodyne, emit probing radio pulses into the controlled space, receive radio pulses reflected from the target and mix them with heterodyne oscillations of the HF generator, convert radio pulses received from the target into RF radio pulses, mix the latter in a quadrature mixer with reference IF oscillations, convert RF radio pulses into low Doppler frequency region in the form of quadrature video pulses And , then sample the instantaneous values of the quadrature video pulses And , and from the sample values they obtain information about the presence of a target, range and parameters of its movement.

In this case, the reference oscillations of the IF are obtained by multiplying the frequency of the output oscillations of the clock generator; the same oscillations of the clock generator synchronize the moments of formation of probing radio pulses and switching the frequency of the RF generator.

Regarding the sampling of instantaneous values of quadrature video pulses And in [62], four ways to implement them were proposed. According to the first method, the specified sampling is performed at regular periodic time intervals within each quadrature video pulse And . According to the second method, the specified sampling is performed at a variety of points located in a checkerboard pattern according to the phase of the quadrature video pulses And . According to the third method, the specified sampling is performed at multiple points staggered in phase, and with the sampling points shifted in time from one radio pulse received from the target to the next radio pulse by a time delay that is equal to the duration of the sampling pulse divided by the number of sample values in them . According to the fourth method, it is proposed to perform sampling similarly to the first method, but by increasing the width of the probing radio pulse so that it extends to many sampling points.

The main disadvantage of the prototype is the following. Oscillations of probing radio pulses and heterodyne oscillations, differing in frequency by the IF value, are generated by the same RF generator in time sequence, that is, both signals are never present at the output of the RF generator at the same time. The coherence of these oscillations, which is set by the clock generator relative to the moments of switching the frequency of the HF generator, due to the natural instability and unpredictable departures of the generation frequency, is disrupted with an increase in the delay time of the radio pulses reflected from the target, that is, the range to the target. This leads to nonlinearity in the dependence of the oscillation phase of reflected radio pulses on the delay time, and also, as a consequence, to a change in the value of the RF signal at the output of the RF mixer, a decrease in the signal-to-noise ratio and distortion of video pulses And at the output of the quadrature mixer (see description and diagrams of Fig. 8, [62]). The noted phenomena intensify with increasing frequency range of the carrier radiation, especially in the millimeter wave range. They are the reason for the reduction in the maximum range of the SBRL, the reliability of detection and the accuracy of determining the parameters of target movement.

Additional disadvantages of the prototype are the high current consumption in the power circuit, since the RF generator operates continuously. The presence of leakage of RF generator radiation complicates the solution of the problem of electromagnetic compatibility and secrecy of operation in conditions of an increased number of radio equipment. The design complexity of the RF part of the device is also a disadvantage of the prototype. These disadvantages create the problem of using the prototype device in an on-board SBRL. For example, in target detection sensors in the control zone, as well as in vehicle collision avoidance systems.

Thus, the technical problem to which the claimed invention is aimed is to eliminate the disadvantages of the prototype, namely: increasing the range of the SBRL, increasing the reliability of detection and the accuracy of determining the parameters of target motion by improving the coherence of oscillations of probing and heterodyne radio pulses, as well as reducing current consumption power supply and the level of radiation leakage due to the transfer of the RF generator to a pulsed operating mode, as well as simplifying the design of the RF part of the SBRL by eliminating the RF mixer, the first and second UPVChS while maintaining the functionality and energy parameters of the prototype, which affect the range of the SBRL.

To achieve this goal, the RF generator is “transferred to the autodyne mode [55],” which should be understood, according to the definition [63], as equipping the RF generator with an autodyne signal extraction unit (SU). In this case, the combination of the RF generator and the BW of the autodyne signal becomes the so-called autodyne generator (or simply autodyne), performing the functions of an (autodyne) transceiver. In an autodyne generator, under the influence of paired trigger pulses, a sequence of pairs of radio pulses is formed. In these pairs, the first radio pulse is a sounding pulse, and the second is a receiving pulse. The frequency of the probing radio pulse relative to the frequency of the receiving radio pulse is shifted by the IF value. The coherence of the oscillations of each of the generated radio pulses is ensured by shock excitation of the HF generator, in which the initial phase and amplitude of the oscillations are imposed by a trigger pulse with a steep edge, and the generation frequency becomes a multiple of the repetition frequency of pulses with a reduced noise level (see author's certificate SU1292161A1 [64] and page 37-40 in the book [65]). In this case, the coherence of the resulting oscillations is achieved relative to the oscillations of the master clock generator, which creates conditions for their use as simple transceiver devices for pulse-Doppler radars.

The solution to this problem is achieved by the proposed method of pulse-Doppler radar, which consists in the fact that the HF generator is impacted by a sequence of paired trigger pulses with steep edges, while oscillations coherent relative to the frequency of the trigger pulses are formed in the HF generator during each radio pulse, and the frequency of the first radio pulses of each pair is shifted relative to the frequency of the second radio pulses by an IF value, the controlled space is irradiated with radio pulses generated in the HF generator, the first radio pulses of each pair reflected from a target located in this space are received and they act on the HF generator during the formation of the second radio pulse in it, mixed oscillations of the received radio pulse with the natural oscillations of the RF generator, causing autodyne changes in the amplitude of the oscillations, as well as current and/or voltage in the power supply circuit of the RF generator with RF, highlight autodyne changes in the form of RF radio pulses, mix them with the reference oscillations of the IF in a quadrature mixer, convert RF radio pulses into the region of low Doppler frequencies in the form of quadrature video pulses And , then sample the instantaneous values of the quadrature video pulses And , and from the sample values, information about the presence of a target, range and parameters of its movement is then obtained.

The proposed device with an autodyne transceiver for pulse-Doppler radar systems contains an antenna, an RF generator configured to electrically control the generation frequency, a power divider (PD) of RF signals, the first and second quadrature mixers of RF signals, a phase shifter for two quadrature outputs of reference IF signals, first and second sample-storage devices, as well as a programmable synchronization and control unit (PSCU), wherein the high-frequency port of the RF generator is connected to the antenna, the outputs of the RF signal power divider are connected to the signal inputs of the first and second quadrature mixers of RF signals, the first output of the RF signal is connected to control input with the frequency of the RF generator, and the third output is connected to the input of the phase shifter, the quadrature outputs of which are connected to the heterodyne inputs of the first and second quadrature RF signal mixers, while the outputs of the latter are connected to the signal inputs of sample-and-hold devices, to solve the specified problem between the second output of the RF control unit and the start input of the RF generator, an impact excitation pulse generator (IPUG) is introduced, and a block for separating the autodyne RF signal is introduced between the RF generator and the RF signal power divider. The PBSU contains a clock generator, the outputs of which are connected to the inputs of a programmable multiplier and frequency divider, as well as a pulse selector for three inputs.

The analysis of the above-mentioned technical solutions in the field of using an autodyne as a transceiver in pulse-Doppler radars showed that the known devices [54,55] in their essence and principle of operation, as well as the achieved technical indicators, differ significantly from the proposed technical solution and cannot be opposed to the claimed device. Alternative solutions in this and related fields of technology were also considered (see, for example, patents [1-19], [36-51]; EP2159597A2; JP4392428B2; US2423644, US2467670, US3390391, US3454946, US4521778, US6587072 B1, US7420 503 B2, US20080246650A1; US20100265121A1) and literature (see [20, 28, 52, 53], pp. 279-285, Fig. 9.5, 9.6 [66]; pp. 164-169, [67]; pp. 517-530, Fig. 11.4 - 11.6 [68] and also [69,70]). As a result, it was established that the known pulse-Doppler radar devices are made primarily on the basis of separate transmitter and receiver units. Consequently, the proposed technical solution is novel, since the authors do not know of devices for a similar purpose containing features that appear in the proposed invention as distinctive features.

Analysis of the patent search results showed that the proposed solution does not follow clearly from the prior art. It follows that the search did not reveal the known influence of the essential features of the proposed technical solution on achieving the specified technical result. Consequently, the claimed technical solution meets the patentability condition “inventive step”.

The invention is aimed at improving the parameters and characteristics of SBRL intended for solving a wide range of problems of detection, range measurement and determination of target movement parameters. The solution to these problems is in demand in many sectors of human activity, for example, in systems for monitoring technological parameters in production and transport, in agriculture and medicine, in security systems and military affairs, in robotics, technologies for non-contact sensing of objects and scientific research, which is necessary for satisfying ever-increasing human needs. Thus, the claimed invention meets the criterion of “industrial applicability”.

The essence of the invention is illustrated by drawings.

In fig. Figure 1 shows a block diagram of a device with an autodyne transceiver for pulse-Doppler radar systems.

In fig. Figure 2 shows a block diagram of an embodiment of the BSU in the form of a programmable synchronization and control unit of the BSU.

In fig. Figure 3 shows options for performing an autodyne (AD) with isolating the autodyne signal by changing the current in the power circuit of the autodyne generator (AG) ( a ) and by changing the amplitude of oscillations ( b ).

In fig. Figure 4 shows timing diagrams of signals at characteristic points of a device with an autodyne transceiver for pulse-Doppler radar systems: ( a ) - output voltage for controlling the frequency of an autodyne generator; ( b ) - output voltage of the shock excitation pulse generator of the autodyne generator; ( c ) - reference oscillations of intermediate frequency; ( d ) - output bursts of pulses synchronizing samples of the first and second ADC-1 and ADC-2; ( d ) - output oscillations of the autodyne generator during the formation of pairs of radio pulses on the first and second frequency accordingly; ( e ) - oscillations of radio pulses reflected from the target; ( g ) - converted oscillations at the output of the autodyne transceiver; ( z ) - output signal at the output quadrature mixer; ( and ) - output signal at the output quadrature mixer.

The essence of the proposed pulse-Doppler radar method will be discussed below when describing the operation of the device.

A device with an autodyne transceiver for pulse-Doppler radar systems (see Fig. 1) contains antenna A, an autodyne transceiver (or simply autodyne - AD), made on the basis of an RF generator with the ability to electrically control the generation frequency and an autodyne signal extraction unit, a power divider DM of RF signals, first SM-I and second SM-Q quadrature mixers of RF signals, phase shifter PV for two quadrature outputs of the reference IF signal, first ADC-1 and second ADC-2 analog-to-digital converters, programmable synchronization and control unit PBSU, and also a digital signal processing unit DBSP.

Antenna A is connected to the high-frequency port of the autodyne AD, and its third output of the RF signal is connected to the input of the power divider DM of the RF signal. The DM outputs are connected to the signal inputs of the first SM-I and the second SM-Q quadrature RF signal mixers. In this case, the outputs of the first SM-I and second SM-Q quadrature RF signal mixers are connected to the signal inputs of the first ADC-1 and the second ADC-2, respectively, and the outputs of the latter are connected to the signal inputs of the digital signal processing unit DBSP. The first output of the programmable synchronization and control unit PBSU is connected to the input (number 1) for controlling the frequency of generation of the autodyne AD, and the second output of the PBSU through the shock excitation pulse generator GIUV is connected to the input (under number 2) starting the autodyne AD. The third output of the PBSU is connected to the input of the PV phase shifter of the reference IF signal, the quadrature outputs of which are connected to the heterodyne inputs of the first SM-I and the second SM-Q quadrature mixers of RF signals, and the fourth output of the PBSU is connected to the clock inputs of the first ADC-1 and the second ADC-2 .

The programmable synchronization and control unit PBSU contains (see Fig. 2) a TG clock generator, a programmable PUCH multiplier and a PDCH frequency divider, an SI pulse selector for three inputs, as well as a transceiver port 5 of the ShKP programming command bus. In this case, the outputs of the TG clock generator are connected to the inputs of the PUCH and MAP, and the programmable outputs of the latter (PUC and MAP) are connected to the inputs of the SI pulse selector for three inputs. The first, second, third and fourth outputs of the PBSU are connected to the programmable outputs of the MAP, PUCH and SI.

The BCOS contains means for digital signal processing, as well as bus transceivers (not shown in Fig. 1), which are connected via the ShKP programming command bus and the ShVD output data bus to the fifth transceiver port of the PBSU and the end data consumer, respectively (see Fig. 1) .

Autodyne AD (see Fig. 3) contains an autodyne generator AG, made, for example, on the basis of a generator diode D2 (a Gunn diode or an avalanche-flight diode) placed in the AG resonator, and an isolation unit (BV) of an autodyne RF signal. Options for implementing IM based on generator diodes with BV autodyne signal according to the first option (in the power supply circuit) are described in article [63] (see Fig. 14 and Fig. 21). The BV can be made in the form of a broadband current sensor DT, connected between the output of diode D2 and the second output of the autodyne AD (see Fig. 3, a ). As current sensors, a resistor, inductance, current transformer, parallel oscillating circuit or a circuit with transformer-capacitive coupling of circuits are usually used in series in the power circuit (see Fig. 74, monographs [71]). In the patent [48] (see Fig. 1, 4 and 5), to increase the speed and, accordingly, expand the frequency band of the autodyne RF signal, it is proposed to use a Wilkinson divider circuit formed by microstrip lines as a BW.

According to the second version, the autodyne RF signal extraction unit (BU) can be made on the basis of a detector diode D3 placed in the AG resonator (see Fig. 3, b ) or in the transmission line connected to the resonator, as shown in Fig. 2 patents of the Russian Federation RU2295911C1 (published on March 27, 2007, bulletin No. 9) and in Fig. 6 a and 9 a of article [63]. To ensure electrical tuning of the generation frequency, a varicap can be placed in the AG resonator (see pp. 80-84, [72]). The AG on a Gunn diode is started by applying a voltage pulse to the power circuit (see Fig. 15, [63], patent [64]), and the LPD by applying a current pulse (see Fig. 22, [63]). The BV output of the autodyne signal is connected to the third pin of the AD. Electrical control of the IM generation frequency through its first output in both variants is carried out by means of a varicap D1 placed in the AG oscillatory system.

Autodyne AD can also be made in the form of a generator module based on one or more transistors, into the power circuit of which a resistor or electronic circuit is connected in series to convert autodyne current changes into autodyne signal voltage (see, for example, figures 18 to 23 of the patent [34 ]). To adjust the frequency, a varicap is usually connected to the resonator of the RF generator (see Fig. 44c, 45c, [34]). The shock start of the HF generator can be carried out through the generator power circuit (see Fig. 43, [34]), as well as through the control circuits of amplifiers made on bipolar or field-effect transistors [73, 74].

The GIUV shock excitation pulse generator, designed to generate trigger pulses with a steep edge of picosecond duration, is used to obtain coherent oscillations of radio pulses in the AG. In this case, the duration of the front of the GIUV output pulses for excitation of incremental [75] (increasing) oscillations in the RF generator is usually chosen equal to half the oscillation period of the RF generator, and the amplitude of the pulses must be at least an order of magnitude higher than the intrinsic noise level of the RF generator (see Section 5.6 "Approximate procedure for designing and calculating the frequency converter", pp. 103-108, books [65]).

Studies of radio pulse generators based on Gunn diodes of the 3-cm wavelength range have shown that the conditions for the coherence of radio pulses are met when triggered by pulses with a front duration of about 50 picoseconds and an amplitude of shock excitation while passing the Gunn diode threshold voltage of at least 0.01 Volt [76]. In this case, a reduction in frequency noise was obtained compared to noise in the continuous generation mode by 35 dB at a distance of 1 kHz from the carrier. Amplitude noise in the radio pulse frequency multiplication mode is reduced by 2...2.5 dB. For radio pulse generators on LPD, frequency noise suppression reaches 50 dB [77]. The results of studies of the phase stability of oscillations in radio pulse generators based on Gunn diodes showed that with trigger pulse durations of less than 2 ns, circuit-independent microwave generators based on Gunn diodes make it possible to obtain instability (divergence) of the initial phase of 2...2.5° with an observation duration of 200 ns [ 78, 79].

Technical solutions for creating GIUV are widely known (see chapter 7.8. “Pulse shapers and generators with picosecond fronts”, pp. 118-136, manuals [80]; section 3.4. “Sources of probing radio pulse signals”, pp. 108-114, monographs [81]). GIUVs can be made on the basis of transmission lines, tunnel diodes, switched bit lines, avalanche S-diodes and S-transistors, optoelectronic drivers, charge storage diodes (CSDs), drift diodes, high-speed transistors and integrated circuits. The calculation of a subnanosecond pulse generator based on DNS is described in [82], and examples of their use in GIUV for radio pulse generators made on Gunn diodes and field-effect transistors are given in the descriptions of patents [64,74]. Descriptions of GIUVs made on avalanche transistors and S-diodes for radio pulse generators on Gunn diodes are presented in Fig. 3.7, 3.8 and 3.9 of the monograph [81].

Antenna A can have different designs, depending on the requirements for the radiation pattern and operating frequency range, for example, in the form of a slot or strip vibrator, horn, dielectric rod, spiral antenna or wave channel type (see pages 115, 149, respectively). 218, 239, 260, [83]).

The power divider of the DM RF signals divides the signal into two in-phase channels; it can be made in the form of a tee (coaxial, microstrip, waveguide in the E-plane), according to the Wilkinson divider circuit on microstrip lines [84] or a compact double ring bridge proposed in utility model patent RU190044U1 [85].

The first SM-I and second SM-Q quadrature RF signal mixers are identical and can be made using semiconductor diodes using a balanced frequency converter circuit (see page 102, Fig. 5.26, [86]).

The PV phase shifter for two quadrature outputs ensures that relative to the input signal, two IF signals are received at the outputs, shifted in phase by plus and minus 45 degrees. Depending on the frequency range, the PV can be made on the basis of inductance and capacitance according to the rules known in the theory of electrical circuits (see pp. 92-94, Fig. 6.11, [87]) or a compact directional coupler proposed in the patent for a utility model can be used RU187315U1 [88].

The programmable synchronization and control unit PBSU can be made on the basis of “hard” logic, programmable logic integrated circuits (FPGAs) or using specialized microcircuits and have a different functional structure. One example of a “flexible” implementation of a PBSU is presented in the block diagram of Fig. 2. This circuit is implemented on the Si5368 chip, containing a reference clock generator and two independent programmable frequency multipliers/dividers and pulse shapers with low jitter (jitter) phase of output oscillations in the frequency range from 2 kHz to 1.4 GHz (see Silicon website Laboratories: http://www.silabs.com). The PBSU contains a TG clock generator, a programmable PFC multiplier and a PFC frequency divider, as well as an SI pulse selector for three inputs. In this case, the output of the TG clock generator is connected to the inputs of the PDCH and MAP, and the programmable outputs “a” and “b” of the PDCH and “b” PDCH are connected to the inputs of the SI pulse selector for three inputs. For communication with other blocks of the proposed device, the PBSU contains the first, second, third and fourth outputs, which are connected to the programmable outputs “a” MAP, “b” MAP, “a” PUCH and to the SI output, respectively. Transceiver port 5 of the PBSU is connected to the programming pins of the Si5368 microcircuit and is intended for connecting the ShKP programming command bus for communication with the central control center.

It is preferable to use high-speed ADC microcircuits as ADC-1 and ADC-2 [89,90]. For example, the AD9689 chip from Analog Devices is a dual 14-bit ADC with a JESD204B interface, speed 2.6 GB/s (see website: https://www.analog.com/ru/products/ad9689.html# product-overview). This ADC is capable of directly sampling analog signals with -3 dB bandwidth up to 9 GHz. Similar ADCs such as DAC38RF82 and DAC38RF89 are produced by Texas Instruments.

The digital signal processing unit DBSP (see Fig. 1) is not the subject of the present invention; it can be made on the basis of a signal processor, for example, a controller of the MSP430X1XX family [91]. The controller contains: read-only memory (ROM) storing the signal processing program; a high-speed computing core that performs the functions of digital signal processing (spectral analysis, digital signal filtering and data generation, indication); random access memory (RAM), which performs the functions of storing current values and signal processing results; Serial port bus transceivers for transmitting and exchanging information via the ShKP programming command bus with the PBSU and via the ShVD output data bus with the end user - the on-board computer.

It should be noted that the composition of the proposed device may include additional or other elements that do not change the essence of the invention. For example, a conventional or low-noise bandpass amplifier with a linear amplitude characteristic in the operating range of signal levels can be installed in front of the DM power divider (see page 60, Fig. 4.3b, [86]).

A device with an autodyne transceiver for pulse-Doppler radar systems operates as follows.

After supplying the supply voltage to the device in the BCOS (see Fig. 1), in accordance with the algorithm of its operation, the computing core includes the “Initialization” command [91], which configures peripheral devices, allocates internal memory, sets the values of internal variables, and copies the executable code from a low-performance ROM to a high-performance RAM and sending commands to the PBSU via the ShKP bus that set the multiplication and division coefficients, as well as the algorithm for generating synchronization and control signals.

After passing the programming commands in the PBSU (see Fig. 2), the TG clock generator is started. The output pulses of the TG are supplied to a programmable MAP divider and a PFC frequency multiplier. Pulses are generated at the output “a” of the MAP control the autodyne generation frequency (see Fig. 4, a ), arriving at the first output of the PBSU and at the input “a” of the SI pulse selector. At output “b” of the MAP, periodic pairs of pulses are formed triggering autodyne generation (see Fig. 4, b ), having a duration , which arrive at the second output of the PBSU and at the input “b” of the SI pulse selector. Harmonic oscillations are formed at the output “a” of the PUCH IF (see Fig. 4, c ) arriving at the third output of the PBSU. At output “b” of the PUCH, clock pulses are generated for the first and second ADC-1 and ADC-2, which are supplied to input “c” of the SI pulse selector. From the SI output of a burst of synchronization pulses samples (see Fig. 4, d ) of the first and second ADC-1 and ADC-2 are sent to the fourth output of the PBSU.

As can be seen from the timing diagram of Fig. 4, a , pulse formation control of the autodyne generation frequency in each pair begins immediately after the cutoff of the first pulse autodyne generation starts (see Fig. 4, b ) and ends after the cutoff of the second pulse launch. Therefore, the radio pulses excited in the autodyne IM under the influence of the shock excitation pulse generator GIUV Each pair has a different generation frequency. In the first radio pulse of the pair, oscillations are excited at a frequency , and the second - at frequency (see Fig. 4, d ). Duration impulses frequency control corresponds to delay time the second radio pulse of the pair relative to its first radio pulse. It is obvious that the period repetition of pairs of radio pulses to maintain unambiguity in determining the distance to the target must exceed the maximum delay time radio pulse reflected from the target , Where - maximum distance to target; - speed of propagation of electromagnetic radiation. Synchronization pulse bursts samples of the first and second ADC-1 and ADC-2 (see Fig. 4, d ) take place only during the formation of the second radio pulse of each pair.

Periodic sequence of paired pulses starting autodyne generation (see Fig. 4, b ) from the second output of the PBSU, after the formation of pulses with picosecond edges in the GIUV, is supplied to the second input of the AD. The first impulses in pairs provide conditions for excitation of coherent oscillations at a frequency in an autodyne generator AG , For example, , determined by the voltage value on varicap AG. The radio pulses generated in this case generation (see Fig. 4, d ) are converted by antenna A into electromagnetic radiation, which, in accordance with its radiation pattern, is emitted into the controlled space as a sounding radio signal . The expression for this radio signal is:

Where

- amplitude of the probing radio signal;

- rectangular envelope of the probing radio signal;

- circular frequency of the probing radio signal;

- integer, frequency multiplication factor of the probing radio signal;

- circular frequency of the clock generator;

And - the duration of the probing radio pulses and their repetition period, respectively;

- initial phase th radio pulse, imposed by the trigger pulse;

- integer, serial number of the probing radio pulse.

After completing the process of forming the first (probing) radio pulse of each pair under the influence of pulses supplied to the varicap frequency control (see Fig. 4, a ) generation, the natural frequency of the AG resonator is switched to the frequency . Detained for a while delay pulses triggering the second radio pulses of the pairs provide in the AG the conditions for excitation of coherent oscillations at the frequency , For example, . The radio pulses generated in this case generation (see Fig. 4, e ) are also emitted by antenna A in accordance with its radiation pattern into the controlled space, but are not used as sounding signals. We will conditionally call these radio pulses reception , since during their formation the signals reflected from the target are received and separated in the AG power circuit. The expression for receiving radio pulses generated in the AG has the form:

Where

- amplitude of the receiving radio signal;

- unit function of the envelope of the receiving radio signal;

- circular frequency of the receiving radio signal;

- integer, multiplication factor of the frequency of the receiving radio signal;

- circular frequency of the clock generator;

And - the duration of radio pulses and their repetition period, respectively;

- delay time of the second (receiving) radio pulse of the pair relative to the first;

- initial phase th radio pulse, imposed by the trigger pulse;

- integer, serial number of the receiving radio pulse.

After completing the process of forming the second (receiving) radio pulse of each pair, under the influence of the pulse supplied to the varicap frequency control (see Fig. 4, a ) generation, the natural frequency of the AG resonator is switched to the frequency probing radio pulse. Probe frequencies and reception radio signals differ by the amount intermediate frequency ( ), which is also a multiple of the frequency TG clock generator, for example . At frequency from the third output of the PBSU, harmonic oscillations are supplied to the input of the quadrature phase shifter PV (see Fig. 4, c ) , which after the PV are divided equally and become quadrature And . These oscillations, which then arrive at the heterodyne inputs of the first SM-I and second SM-Q quadrature mixers, are described by the following expressions:

Where

- amplitude of the intermediate frequency signal;

- intermediate frequency;

- integer, intermediate frequency multiplication factor;

- integer, frequency multiplication factor of the probing radio signal;

- integer, multiplication factor of the frequency of the receiving radio signal.

If there is a target in the radiation field of antenna A (we assume for simplicity that the target is a point one), the electromagnetic radiation reflected from it is received by antenna A, converted into electrical radio signals and acts on the autodyne generator IM. (see Fig. 4, f ). We write the expression for these radio signals in the form:

Where

- amplitude of the probing radio signal;

- dimensionless attenuation coefficient of the amplitude of the emitted signal along the propagation path to the target and back, reduced to antenna port A;

- the delay time of the reflected radiation from the target, in the general case variable;

- current distance to the target, generally variable;

- speed of propagation of radio waves;

- initial phase th radio pulse, imposed by the trigger pulse;

- integer;

- phase shift associated with the reflective properties of the target;

- average power of the sounding radio signal;

- minimum detectable (threshold) signal;

- antenna gain A;

- radiation wavelength;

- effective scattering area of the target;

- speed of propagation of electromagnetic radiation;

- unit function for the envelope of the reflected signal.

The effect of radio signals reflected from the target on the autodyne generator AG consists in mixing the oscillations of radio frequency pulses received by antenna A with natural oscillations of AG at a frequency and their nonlinear interaction. This interaction causes an autodyne effect in the AG, which, depending on the ratio of the magnitude of the frequency difference and half-bandwidth synchronization of hypertension manifests itself in different ways (see pp. 13-24, [58]).

Bandwidth half-width AG synchronization, as is known (see pp. 257-262, formula (5.73), [92]), is determined by the internal parameters of the generator and the relative level of the influencing signal:

Where

- half-width of the generator synchronization band;

- external quality factor of the generator oscillatory system;

- the angle between the line of the device (active element) of the generator and its hodograph line of the impedance of the oscillatory system and load (see Fig. 5.16, p. 260, [92]);

- generator non-isochronism coefficient.

As a result of calculating the half-width of the synchronization band according to formula (6) at , which corresponds to the case of a strong signal and a close distance from the SBRL to the target, at a frequency at And we get , i.e. 20 MHz.

If you select intermediate frequency within the half-width of the synchronization bandwidth , then the generator frequency is captured by the influencing signal and the frequency conversion process is absent. If the inequality A beating mode is observed in the generator, which is accompanied by amplitude-frequency modulation of the generator oscillations and significant nonlinear distortions of the autodyne signal [93]. If the strong inequality holds in the AG there are quasi-harmonic changes (beats) in the amplitude and frequency of oscillations, as well as the average value of current and/or voltage in the AG power circuit with a difference frequency . The manifestation of the autodyne effect in this case resembles the phenomenon of frequency conversion in conventional mixers, therefore autodynes that use this effect are called autodyne frequency converters, or simply autodyne (generating) mixers [93-95]. It is obvious that the last condition is satisfied by the choice of an intermediate frequency of the order , that is, 300 MHz or more. Improving the “linearity” of frequency conversion, as can be seen from expression (6), is facilitated by stabilizing the frequency of the AG through, for example, the use of an additional high-quality resonator in the generator, the natural frequency of which is controlled using the adjustable capacitance of a varactor diode, a varicap, or by means of switchable pin diodes (see Fig. 25, [96]; pp. 120-129, [97]).

The converted signal released in the power circuit (see Fig. 3, a ) or through a detector diode (see Fig. 3, b ) Blood pressure (see Fig. 4, g ) at RF is described by the following expression:

Where

- autodyne gain coefficient of the AD, characterizing the transmission of the signal reflected from the target into the RF signal at the output of the AD;

- unit function of the converted signal;

- phase shift of the probing radiation as it propagates to the target and back;

- initial phase of the converted signal;

- difference, in this case, intermediate frequency of the converted AD signal;

- delay time of radiation reflected from the target;

- current distance to the target;

- duration of probing and receiving radio pulses;

- repetition period of paired radio pulses;

- delay time of the second (receiving) radio pulse of the pair relative to the first.

The converted signal (7) received at the third output of the AD is divided equally by the power divider DM and is supplied to the signal inputs of the first SM-I and second SM-Q quadrature mixers. As a result of the nonlinear interaction of RF signals (7) and reference (3), (4) IF oscillations in the SM-I and SM-Q mixers, the signals are converted to the region of low Doppler frequencies. At the same time, at the exits And mixer signals And (see Fig. 4, h and 4, i ) are formed in the form of video pulses. The expressions obtained for these video pulses have the form:

Where

- amplitude factor of the output signals of mixers SM-I and SM-Q;

- conversion factor of mixers SM-I and SM-Q;

- single

function of the converted signal at the outputs of mixers SM-I and SM-Q;

, - in-phase and orthogonal components of the mixers’ own noise and the noise of the autodyne generator AG, converted to the outputs of the SM-I and SM-Q mixers;

The first terms in (8) and (9), representing the result of transformation of the reflected signal in the autodyne AD and mixers SM-I and SM-Q, contain information about the range to the target, speed and direction of its movement. At the same time, for real-life speeds of target movement, the condition is true that during the time Under the influence of the probing radio pulse, the distance between antenna A and the target will practically not change. Then, according to (8) and (9), the received video pulses at the outputs And quadrature mixer remain practically constant during their formation (see Fig. 4, h and 4, and ). Therefore, they look in the form of step functions of time, while the “height” of the steps is proportional to the level of the reflected signal, and their sign (up or down) depends on the current phase difference between the oscillations emitted by the autodyne and those reflected from the target. With relative movement of the target, instantaneous changes in the height of video pulses occur at the Doppler frequency [98]. Under the condition of uniform and linear motion of the target in time t, the phase incursion in (8) and (9)

Where

- initial phase shift, which is determined by the position of the object at the moment of time ;

- Doppler frequency;

- relative radial speed between the SBRL and the location object.

Taking into account (10), expressions (8) and (9) have the form:

Second terms And in (8), (9) and (11), (12) display the result of converting the intrinsic noise of the autodyne generator AG and mixers SM-I and SM-Q. The presence of these noises is expressed in noise modulation of the height of the video pulses And at the outputs of mixers SM-I and SM-Q. It should be noted that the noise components And at the outputs of mixers SM-I and SM-Q represent independent stationary normal processes with a zero average value. There is no mutual correlation between these components. In addition, due to the significant frequency difference the first in a pair (probing) and the second (receiving) radio pulses, the influence of flicker noise from mixers and an autodyne generator is negligible and the distribution of the spectral noise density is uniform.

From the outputs of the mixers SM-I and SM-Q (see Fig. 1), video pulses with noise components are then supplied, respectively, to the signal inputs of ADC-1 and ADC-2, where the operation of sampling signals (11) and (12) in time is first performed . During sampling pulses (see diagram in Fig. 4, d ) in ADC-1 and ADC-2, instantaneous values of signals (11) and (12) are sampled and stored in the form of pulses, the amplitude of which is equal to the instantaneous values of these signals (see diagrams in Fig. 4, h and 4, i ). The levels of these pulses are further converted into digital values in ADC-1 and ADC-2, which, in the form of parallel code, enter the RAM of the DBSP as data arrays received for the received signal from -th probing radio pulse:

Where

, - digital samples of instantaneous values of the received signal from th probing radio pulse received for th clock pulse (here );

- number of samples per time .

At the same time, the noise components And at the outputs of the SM-I and SM-Q mixers as a result of sampling and digitization of instantaneous sample values due to the ergodicity of the processes on average across implementations and counts retain their RMS noise level in data sets (13) and (14) Noise level value can be calculated or measured experimentally and taken into account in the work program of the BTsOS.

It should be noted that in the proposed device, by appropriate programming of the PBSU, the sampling of instantaneous values of quadrature video pulses And can be carried out using any of the four methods described in [62]. According to the first method, the specified sampling is performed at regular periodic time intervals within each quadrature video pulse And . According to the second method, sampling is performed at many points located in a checkerboard pattern according to the phase of the quadrature video pulses And . According to the third method, sampling is performed at multiple points staggered in phase, and with the sampling points shifted in time from one radio pulse received from the target to the next radio pulse by a time delay that is equal to the duration of the sampling pulse divided by the number of sample values in them. According to the fourth method, it is proposed to perform sampling similarly to the first method, but by increasing the width of the probing radio pulse so that it extends to many sampling points.

Processing the received data in arrays (13) and (14) of the BTsOS allows one to calculate the amplitude and phase of the reflected signal, as well as its signal-to-noise ratio, from the values of the quadrature components, as well as its signal-to-noise ratio and solve the problem of target detection at a given range. The distance to the target is determined by the value of the time delay between paired radio pulses, and by the values of the change in phase and its sign of the reflected signal, the speed (based on the Doppler frequency) and direction of the target's movement are determined. The current results of signal processing are transmitted via the bus transceiver BTsOS at a given rate via the SHVD bus to the end user.

The coherence of oscillations of the generated radio pulses in the proposed device, as follows from the presented description, is set not relative to the moments of switching the generation frequency, as in the prototype device, but relative to the moments of shock excitation of the generator oscillations during the formation of each radio pulse of the pair. Natural instabilities and deviations in the generation frequency during such formation of radio pulses practically do not violate their coherence with an increase in the delay time of the radio pulses reflected from the target, that is, the range to the target. This leads to a linear dependence of the oscillation phase of reflected radio pulses on the delay time and a constant value of the intermediate frequency signal at the mixer output, and as a consequence, the absence of nonlinear distortions of video pulses And at the output of the quadrature mixer and increasing the signal-to-noise ratio. As a result of increasing the signal-to-noise ratio, the proposed device and method provide an increase in the range of the SBRL, the reliability of detection and the accuracy of determining the parameters of target movement. In addition, the proposed technical solution removes the fundamental limitation on increasing the SBRL carrier frequency and moving to the more promising millimeter wave range.

It should also be noted that the pulsed operating mode of the autodyne generator ensured a decrease in the level of radiation leakage, an increase in the secrecy of the SBRL operation and a decrease in power current consumption. By eliminating the RF mixer, the first and second controlled switches of high-frequency signals while maintaining the functionality and energy parameters of the prototype, which affect the range of the SBRL, a simplification of the design of the RF part of the SBRL has been achieved. The indicated quality indicators, as well as efficiency, small dimensions, weight and low cost of components for the proposed device create advantages for its use in promising airborne SBRLs.

The proposed method and device were implemented in the form of a working prototype of an 8-mm range SBRL, made on the basis of an autodyne oscillator based on a Gunn diode with signal extraction based on a change in the oscillation amplitude through a Schottky diode installed in the resonator of the generator chamber. The generator was started via the power circuit by paired voltage pulses with an amplitude of 4.5 V, with a rise of no more than 0.1 ns, a repetition period of 5 μs, and a duration of 15 ns. The delay time between radio pulses varied from 30 to 1000 ns. Number of counts during radio pulse emission (sampling pulse frequency GHz). At the same time, the range resolution of the SBRL was m. The results of laboratory studies of the sample showed that the potential of the SBRL in the Doppler frequency band kHz is dB. Tests of a prototype in an open area with corner reflectors and a passenger car confirmed the possibility of determining the distance to the target with an error of about 1 m at distances from 10 to 300 m.

Thus, the technical problem to which the claimed invention is aimed has been successfully completed. At the same time, the applicability of the proposed device in SBRL designed to detect targets at a given range and determine the parameters of their movement, including in systems for preventing collisions of vehicles, is shown.

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Claims (9)

1. A method of pulse-Doppler radar, including the formation at the output of a high-frequency (HF) generator of probing radio pulses, the oscillation frequency of which is shifted by an intermediate frequency (IF) relative to the oscillation frequency during the rest of the repetition period of the probing radio pulses, the probing radio pulses are emitted into the controlled space and received radio pulses reflected from the target; in a quadrature mixer, difference frequency (RF) radio pulses are mixed with reference IF oscillations and converted to the low Doppler frequency region in the form of quadrature video pulses And , after which a sample of instantaneous values of quadrature video pulses is stored And , from the values of which information is then obtained about the presence of a target, range and parameters of its movement, characterized in that the radio pulses at the output of the HF generator are obtained by shock excitation of the HF generator with a sequence of paired trigger pulses with steep edges, while forming inside these paired radio pulses relative to the trigger pulses coherent oscillations, and the first radio pulses of each pair are probing, and the second are receiving; the oscillations of the radio pulses reflected from the target are mixed with the natural oscillations of the HF generator during the formation of receiving radio pulses in it, causing autodyne changes in the HF generator amplitude of oscillations, as well as current and/or voltage in its power supply circuit in the form of RF radio pulses, after which autodyne changes are isolated in the form of RF radio pulses and sent to a quadrature mixer. 2. The method according to claim 1, characterized in that the frequency of the probing radio pulses is chosen to be at a distance from the frequency of the receiving radio pulses by an amount at least an order of magnitude greater than half the synchronization bandwidth of the HF generator caused by the influence of the reflected radio signal. 3. The method according to claim 1, characterized in that the duration of the front of the shock excitation pulses is chosen such that it is equal to half the oscillation period of the HF generator, and the amplitude of the pulses is at least an order of magnitude higher than the intrinsic noise level of the HF generator. 4. A device for pulse-Doppler radar with an autodyne transceiver, containing an antenna, an RF generator configured to electrically control the generation frequency, an RF signal power divider, the first and second quadrature RF signal mixers, a phase shifter for two quadrature outputs of the reference IF signals, the first and a second sampling-storage device, as well as a programmable synchronization and control unit (PSCU), wherein the outputs of the RF signal power divider are connected to the signal inputs of the first and second quadrature mixers of RF signals, the first output of the PBSU is connected to the control input of the RF generator frequency, the third output of the PBSU is connected to the input of the phase shifter of the reference IF signals, the quadrature outputs of which are connected to the heterodyne inputs of the first and second quadrature mixers of the RF signals, while the outputs of the latter are connected to the signal inputs of the first and second sample-storage devices, and the fourth output of the BSSU is connected to the control inputs of the sample-storage devices , characterized in that between the second output of the PBSU and the start input of the RF generator, an impact excitation pulse generator (HIUV) is introduced, between the HF generator and the input of the RF signal power divider, an autodyne signal extraction unit (BU) is introduced, and the high-frequency port of the RF generator is connected to the antenna. 5. The device according to claim 4, characterized in that the PBSU contains the first, second, third and fourth outputs, a clock generator connected to the inputs of a programmable frequency multiplier (PFC) and a frequency divider (PDF), as well as a pulse selector for three inputs, inputs which are connected to the programmable outputs “a” MAP, “b” MAP and “b” PUCH, while the first, second, third and fourth conclusions of the PBSU are connected to the programmable outputs “a” MAP, “b” MAP, “a” PUCH and output of the pulse selector to three inputs, respectively. 6. The device according to claim 4, characterized in that the unit for isolating the autodyne RF signal is made in the form of a current sensor connected in series to the power circuit of the RF generator, which can be used as a resistor, inductance, transformer, parallel oscillating circuit, circuit with transformer-capacitive circuit coupling or a Wilkinson power divider made on microstrip lines. 7. The device according to claim 4, characterized in that the unit for isolating the autodyne RF signal is made on the basis of a detector diode placed in the resonator of the RF generator or in the transmission line connected to the resonator. 8. The device according to claim 4, characterized in that the RF generator is made with frequency stabilization by an additional external high-Q resonator, the natural frequency of which is controlled using the adjustable capacitance of a varactor diode, a varicap, or by means of switching p-i-n diodes. 9. The device according to claim 4, characterized in that analog-to-digital converters are connected to the outputs of the first and second quadrature RF signal mixers as sample-storage devices.