WO2024106323A1 - Power supply device - Google Patents

Power supply device Download PDF

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Publication number
WO2024106323A1
WO2024106323A1 PCT/JP2023/040536 JP2023040536W WO2024106323A1 WO 2024106323 A1 WO2024106323 A1 WO 2024106323A1 JP 2023040536 W JP2023040536 W JP 2023040536W WO 2024106323 A1 WO2024106323 A1 WO 2024106323A1
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WO
WIPO (PCT)
Prior art keywords
switching element
leg
side switching
power
shift amount
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PCT/JP2023/040536
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French (fr)
Japanese (ja)
Inventor
山下貢
▲高▼橋亮平
高橋充
岩田裕貴
野村将彦
萩田和洋
▲高▼山雅貴
大沼喜也
宅間春介
Original Assignee
株式会社アイシン
長岡パワーエレクトロニクス株式会社
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Application filed by 株式会社アイシン, 長岡パワーエレクトロニクス株式会社 filed Critical 株式会社アイシン
Publication of WO2024106323A1 publication Critical patent/WO2024106323A1/en

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac

Definitions

  • the present invention relates to a power supply device that charges and discharges a battery installed in a vehicle.
  • Patent documents 1-3 describe power conversion devices. Furthermore, patent documents 4 and 5 describe switching power supply devices. The power conversion devices of patent documents 1-3 and the switching power supply devices of patent documents 4 and 5 are used, for example, to output a DC voltage of a first voltage value capable of charging a battery, or to output a DC voltage of a second voltage value lower than the first voltage value.
  • Patent Documents 1-3 and the switching power supply devices of Patent Documents 4 and 5 are large in overall device size and cost.
  • the control becomes complicated and output cannot be easily achieved.
  • the power supply device has a first leg in which a high-side switching element and a low-side switching element are connected in series, and a second leg in which a high-side switching element and a low-side switching element are connected in series, which are arranged in parallel with each other, and includes an inverter that converts AC power to DC power, and a converter that is provided with an insulated multi-port transformer having a primary winding, a secondary winding, and a tertiary winding and converts the DC power from the inverter into DC power composed of a DC voltage of a first voltage value that charges a battery.
  • the converter has an input unit that oscillates the DC power from the inverter at a predetermined period and inputs it to the primary winding, a first conversion unit that converts the AC power generated in the secondary winding into DC power composed of a DC voltage of the first voltage value, and a second conversion unit that converts the AC power generated in the tertiary winding into DC power composed of a DC voltage of a second voltage value lower than the first voltage value, and the second conversion unit converts the AC power generated in the tertiary winding into DC power composed of a DC voltage of the second voltage value by synchronous rectification.
  • FIG. 2 is a circuit diagram showing a configuration of a power supply device.
  • 4 is a timing chart of the power supply device when charging the battery.
  • 10 is a diagram illustrating a positive current and a negative current flowing in a second conversion unit.
  • FIG. 1 is a timing chart of the power supply device when outputting DC power based on the output from the battery.
  • the power supply device is capable of charging and discharging a battery mounted on a vehicle, and can output DC power consisting of DC voltages with different voltage values from each of a number of terminals.
  • the power supply device 1 of this embodiment will be described below.
  • FIG. 1 is a circuit diagram of the power supply device 1. As shown in FIG. 1, the power supply device 1 is configured with an inverter 10, a converter 20, a reactor coil 30, and a control unit 50. Each functional unit is constructed with hardware or software, or both, with a CPU as the core component, in order to perform the processes related to the output of the DC power described above.
  • the inverter 10 converts AC power into DC power and outputs it.
  • AC power refers to power composed of an AC voltage whose voltage value oscillates at a predetermined cycle. Specifically, the AC voltage oscillates at a commercial frequency (e.g., 50 Hz or 60 Hz) and corresponds to an AC voltage of 200 V (effective value) taken from a commercial power source supplied in a single-phase three-wire system.
  • DC power refers to power composed of a DC voltage that has a constant voltage value (excluding ripple voltage) relative to a reference voltage.
  • the inverter 10 is supplied with AC power from a commercial power source.
  • the inverter 10 converts the AC power composed of such AC voltage into DC power including a DC voltage.
  • the inverter 10 is provided with a pair of output units 10A, 10B, and outputs the converted DC power to the converter 20 described later via the pair of output units 10A, 10B.
  • the inverter 10 has a first leg 11 and a second leg 12.
  • the first leg 11 and the second leg 12 are arranged in parallel with each other with respect to the output units 10A and 10B.
  • one end 11A of the first leg 11 and one end 12A of the second leg 12 are connected to the output unit 10A
  • the other end 11B of the first leg 11 and the other end 12B of the second leg 12 are connected to the output unit 10B.
  • the first leg 11 has a high-side switching element 11H and a low-side switching element 11L connected in series.
  • n-type MOS-FETs metal-oxide-semiconductor field-effect transistors
  • the drain terminal of the switching element 11H is connected to the end 11A
  • the source terminal is connected to the drain terminal of the switching element 11L.
  • the source terminal of the switching element 11L is connected to the end 11B.
  • the gate terminals of the switching elements 11H and 11L are connected to the control unit 50.
  • diodes 11HD and 11LD are provided between the source terminals and drain terminals of the switching elements 11H and 11L, with the anode terminals connected to the source terminals and the cathode terminals connected to the drain terminals.
  • the second leg 12 also has a high-side switching element 12H and a low-side switching element 12L connected in series.
  • n-type MOS-FETs are used for the switching elements 12H and 12L.
  • the drain terminal of the switching element 12H is connected to the end 12A, and the source terminal is connected to the drain terminal of the switching element 12L.
  • the source terminal of the switching element 12L is connected to the end 12B.
  • the gate terminals of the switching elements 12H and 12L are connected to the control unit 50.
  • Diodes 12HD and 12LD are provided between the source terminals and drain terminals of the switching elements 12H and 12L, with the anode terminals connected to the source terminals and the cathode terminals connected to the drain terminals.
  • a capacitor 15 is provided across output section 10A and output section 10B of inverter 10. Capacitor 15 smoothes the DC voltage converted by inverter 10.
  • the reactor coil 30 has one terminal 30B connected to a first node 11N between two switching elements (switching element 11H and switching element 11L) in the first leg 11.
  • the first node 11N between the two switching elements in the first leg 11 is a line (e.g., a wiring pattern on a board or a cable such as a harness) connecting the source terminal of switching element 11H and the drain terminal of switching element 11L.
  • a line e.g., a wiring pattern on a board or a cable such as a harness
  • the reactor coil 30 has two terminals 30A, 30B, and the terminal 30B is connected to the first node 11N.
  • the second node 12N between the two switching elements in the second leg 12 is a line (e.g., a wiring pattern on a board or a cable such as a harness) connecting the source terminal of the switching element 12H and the drain terminal of the switching element 12L. Of course, it may be the source terminal of the switching element 12H or the drain terminal of the switching element 12L.
  • the terminal 30A of the reactor coil 30 is connected to one terminal of the supply unit 2 to which AC power is supplied, and the other terminal of the supply unit 2 is connected to the second node 12N. Therefore, the inverter 10 converts AC power into DC power by the switching element 11H and switching element 11L of the first leg 11 and the switching element 12H and switching element 12L of the second leg 12.
  • the converter 20 converts the DC power from the inverter 10 into DC power composed of a DC voltage of a first voltage value capable of charging the battery 3.
  • the DC power from the inverter 10 is the DC power output from the output parts 10A and 10B of the inverter 10.
  • the battery 3 is a battery mounted on the vehicle that is charged by the power supply device 1, and is charged based on the DC power output from the converter 20.
  • the battery 3 is charged with a DC voltage of a predetermined voltage value, but the voltage value of the DC voltage that constitutes the DC power output from the inverter 10 is about the voltage value (200V) of the AC voltage input to the inverter 10.
  • the converter 20 boosts the voltage value of the DC voltage output from the inverter 10 to a DC voltage of a voltage value (equivalent to the "first voltage value", for example several hundred V) required for charging the battery 3.
  • the converter 20 of this embodiment has an input section 21, a first conversion section 22, a second conversion section 23, and a multi-port transformer (hereinafter referred to as "transformer") 24.
  • the transformer 24 is configured as an insulated type having a primary winding 24A, a secondary winding 24B, and a tertiary winding 24C.
  • the input unit 21 oscillates the DC power from the inverter 10 at a predetermined period and inputs it to the primary winding 24A.
  • the input unit 21 has a third leg 211 and a fourth leg 212, which are provided in parallel with each other with respect to the output units 10A and 10B. Therefore, one end 211A of the third leg 211 and one end 212A of the fourth leg 212 are connected to the output unit 10A, and the other end 211B of the third leg 211 and the other end 212B of the fourth leg 212 are connected to the output unit 10B.
  • the third leg 211 has a high-side switching element S1 (hereinafter referred to as “switching element S1”) and a low-side switching element S2 (hereinafter referred to as “switching element S2”) connected in series.
  • the switching elements S1 and S2 are n-type MOS-FETs.
  • the drain terminal of the switching element S1 is connected to the end 211A, and the source terminal is connected to the drain terminal of the switching element S2.
  • the source terminal of the switching element S2 is connected to the end 211B.
  • the gate terminals of the switching elements S1 and S2 are connected to the control unit 50.
  • diodes S1D and S2D are provided, with the anode terminal connected to the source terminal and the cathode terminal connected to the drain terminal.
  • the fourth leg 212 has a high-side switching element S3 (hereinafter referred to as “switching element S3”) and a low-side switching element S4 (hereinafter referred to as “switching element S4") connected in series.
  • the switching elements S3 and S4 are n-type MOS-FETs.
  • the drain terminal of the switching element S3 is connected to the end 212A, and the source terminal is connected to the drain terminal of the switching element S4.
  • the source terminal of the switching element S4 is connected to the end 212B.
  • the gate terminals of the switching elements S3 and S4 are connected to the control unit 50.
  • diodes S3D and S4D are provided, with the anode terminals connected to the source terminals and the cathode terminals connected to the drain terminals.
  • the primary winding 24A is provided across a third node 211N between two switching elements (switching element S1 and switching element S2) in the third leg 211 and a fourth node 212N between two switching elements (switching element S3 and switching element S4) in the fourth leg 212.
  • the winding start end of the primary winding 24A is connected to the third node 211N
  • the winding end end of the primary winding 24A is connected to the fourth node 212N.
  • the first conversion unit 22 converts the AC power generated in the secondary winding 24B into DC power composed of a DC voltage of a first voltage value.
  • the first conversion unit 22 has a fifth leg 221 and a sixth leg 222, and the fifth leg 221 and the sixth leg 222 are provided in parallel with each other with respect to the terminals 20A and 20B of the converter 20.
  • one end 221A of the fifth leg 221 and one end 222A of the sixth leg 222 are connected to the terminal 20A, and the other end 221B of the fifth leg 221 and the other end 222B of the sixth leg 222 are connected to the terminal 20B.
  • the fifth leg 221 has a high-side switching element S5 (hereinafter referred to as “switching element S5") and a low-side switching element S6 (hereinafter referred to as “switching element S6") connected in series.
  • the switching elements S5 and S6 are n-type MOS-FETs.
  • the drain terminal of the switching element S5 is connected to the end 221A, and the source terminal is connected to the drain terminal of the switching element S6.
  • the source terminal of the switching element S6 is connected to the end 221B.
  • the gate terminals of the switching elements S5 and S6 are connected to the control unit 50.
  • diodes S5D and S6D are provided, with the anode terminals connected to the source terminals and the cathode terminals connected to the drain terminals.
  • the sixth leg 222 has a high-side switching element S7 (hereinafter referred to as “switching element S7”) and a low-side switching element S8 (hereinafter referred to as “switching element S8”) connected in series.
  • the switching elements S7 and S8 are n-type MOS-FETs.
  • the drain terminal of the switching element S7 is connected to the end 222A, and the source terminal is connected to the drain terminal of the switching element S8.
  • the source terminal of the switching element S8 is connected to the end 222B.
  • the gate terminals of the switching elements S7 and S8 are connected to the control unit 50.
  • diodes S7D and S8D are provided, with the anode terminal connected to the source terminal and the cathode terminal connected to the drain terminal.
  • the secondary winding 24B described above is provided across a fifth node 221N between two switching elements (switching element S5 and switching element S6) in the fifth leg 221 and a sixth node 222N between two switching elements (switching element S7 and switching element S8) in the sixth leg 222.
  • the winding start end of the secondary winding 24B is connected to the fifth node 221N via the reactor L, and the winding end end of the secondary winding 24B is connected to the sixth node 222N.
  • a first capacitor 25 is provided across terminals 20A and 20B of the converter 20.
  • the first capacitor 25 smoothes the DC voltage that constitutes the AC power converted by the first conversion unit 22.
  • the second conversion unit 23 converts the AC power generated in the tertiary winding 24C into DC power composed of a DC voltage of a second voltage value (e.g., 12 V) lower than the first voltage value.
  • the tertiary winding 24C has a first tertiary winding 24CA and a second tertiary winding 24CB.
  • the first tertiary winding 24CA and the second tertiary winding 24CB are provided by connecting the end of the first tertiary winding 24CA to the beginning of the second tertiary winding 24CB.
  • a switching element (corresponding to the "first switching element") S9 with a drain terminal connected is provided at the beginning of the first tertiary winding 24CA, and a switching element (corresponding to the "second switching element") S10 with a drain terminal connected is provided at the end of the second tertiary winding 24CB.
  • the source terminal of the switching element S9 and the source terminal of the switching element S10 are connected to the terminal 20D.
  • the gate terminals of the switching elements S9 and S10 are connected to the control unit 50.
  • diodes S9D and S10D are provided, with the anode terminal connected to the source terminal and the cathode terminal connected to the drain terminal.
  • the winding end of the first tertiary winding 24CA and the winding start of the second tertiary winding 24CB are connected to one terminal of the third reactor coil 23L.
  • the other terminal of the third reactor coil 23L is connected to the terminal 20C.
  • the second conversion unit 23 is also provided with a diode 23D1 and a diode 23D2.
  • the anode terminal of the diode 23D1 is connected to the winding start of the first tertiary winding 24CA, and the anode terminal of the diode 23D2 is connected to the winding end of the second tertiary winding 24CB.
  • the cathode terminal of the diode 23D1 and the cathode terminal of the diode 23D2 are connected to each other and to the terminal 20C via the resistor R. Furthermore, the cathode terminal of the diode 23D1 and the cathode terminal of the diode 23D2 are connected to the terminal 20D via the capacitor 27. Therefore, the resistor R and the capacitor 27 form a snubber circuit. Furthermore, a second capacitor 26 is provided across terminals 20C and 20D.
  • the second conversion unit 23 converts the AC power generated in the tertiary winding 24C into DC power composed of a DC voltage of a second voltage value by synchronous rectification using switching elements S9 and S10.
  • the control unit 50 drives each of the multiple switching elements provided in the inverter 10. Specifically, the control unit 50 alternates between the open/closed state of the switching elements 11H and 12L and the open/closed state of the switching elements 11L and 12H. That is, the control unit 50 alternately drives the switching elements 11H and 11L of the first leg 11, and alternately drives the switching elements 12H and 12L at the system frequency of the second leg 12. This allows the inverter 10 to convert the AC power supplied from the supply unit 2 into DC power based on the driving of the switching elements of the first leg 11 and the second leg 12, as described above.
  • the control unit 50 also drives each of the multiple switching elements provided in the converter 20.
  • FIG. 2 shows a timing chart for charging the battery 3.
  • the control unit 50 drives the switching elements S1-S10 in accordance with the timing chart shown in FIG. 2.
  • the control unit 50 drives the switching elements S1-S10 while switching them sequentially between eight states, from state 1 to state 8.
  • the period t1-t9 corresponds to one cycle of control by the control unit 50.
  • the first state is the state between t1 and t2 in FIG. 2, and in this first state, the control unit 50 closes the switching elements S1, S3, S6, S7, S9, and S10, and opens the switching elements S2, S4, S5, and S8.
  • the second state is the state between t2 and t3 in FIG. 2, and in this second state, the control unit 50 closes the switching elements S1, S3, S5, S7, S9, and S10, and opens the switching elements S2, S4, S6, and S8.
  • the third state is the state between t3 and t4 in FIG. 2, and in this third state, the control unit 50 closes the switching elements S1, S4, S5, S7, and S10, and opens the switching elements S2, S3, S6, S8, and S9.
  • the fourth state is the state between t4 and t5 in FIG. 2, and in this fourth state, the control unit 50 closes the switching elements S1, S4, S5, S8, and S10, and opens the switching elements S2, S3, S6, S7, and S9.
  • the fifth state is the state between t5 and t6 in FIG. 2, and in this fifth state, the control unit 50 closes the switching elements S2, S4, S5, S8, S9, and S10, and opens the switching elements S1, S3, S6, and S7.
  • the sixth state is the state between t6 and t7 in FIG. 2, and in this sixth state, the control unit 50 closes the switching elements S2, S4, S6, S8, S9, and S10, and opens the switching elements S1, S3, S5, and S7.
  • the seventh state is the state between t7 and t8 in FIG. 2, and in this seventh state, the control unit 50 closes the switching elements S2, S3, S6, S8, and S9, and opens the switching elements S1, S4, S5, S7, and S10.
  • the eighth state is the state between t8 and t9 in FIG. 2, and in this eighth state, the control unit 50 closes the switching elements S2, S3, S6, S7, and S9, and opens the switching elements S1, S4, S5, S8, and S10.
  • the switching element S1 of the third leg 211 and the switching element S4 of the fourth leg 212 are shifted to the closed state by a preset first shift amount ⁇ 1. That is, in the example of FIG. 2, the switching element S1 of the third leg 211 is closed at t1, and then the switching element S4 of the fourth leg 212 is closed at t3 after the first shift amount ⁇ 1 has elapsed. Therefore, the switching element S1 of the third leg 211 and the switching element S4 of the fourth leg 212 are shifted to the open state by a shift amount ⁇ 1. That is, the switching element S1 of the third leg 211 is opened at t5, and then the switching element S4 of the fourth leg 212 is opened at t7 after the first shift amount ⁇ 1 has elapsed.
  • the switching element S2 of the third leg 211 and the switching element S3 of the fourth leg 212 are shifted to the closed state by the first shift amount ⁇ 1. That is, in the example of FIG. 2, the switching element S2 of the third leg 211 is closed at t5, and then the switching element S3 of the fourth leg 212 is closed at t7 after the first shift amount ⁇ 1 has elapsed. Therefore, the switching element S2 of the third leg 211 and the switching element S3 of the fourth leg 212 are shifted to the open state by the first shift amount ⁇ 1. That is, the switching element S2 of the third leg 211 is opened at t9, and then the switching element S3 of the fourth leg 212 is opened at t11 after the first shift amount ⁇ 1 has elapsed.
  • the switching element S5 of the fifth leg 221 and the switching element S8 of the sixth leg 222 are shifted to the closed state by the first shift amount ⁇ 1. That is, in the example of FIG. 2, the switching element S5 of the fifth leg 221 is closed at t2, and then the switching element S8 of the sixth leg 222 is closed at t4 after the first shift amount ⁇ 1 has elapsed. Therefore, the switching element S5 of the fifth leg 221 and the switching element S8 of the sixth leg 222 are shifted to the open state by the first shift amount ⁇ 1. That is, the switching element S5 of the fifth leg 221 is opened at t6, and then the switching element S8 of the sixth leg 222 is opened at t8 after the first shift amount ⁇ 1 has elapsed.
  • the switching element S6 of the fifth leg 221 and the switching element S7 of the sixth leg 222 are shifted to the closed state by the first shift amount ⁇ 1. That is, in the example of FIG. 2, the switching element S6 of the fifth leg 221 is closed at t6, and then the switching element S7 of the sixth leg 222 is closed at t8 after the first shift amount ⁇ 1 has elapsed. Therefore, the switching element S6 of the fifth leg 221 and the switching element S7 of the sixth leg 222 are shifted to the open state by the first shift amount ⁇ 1. That is, in the example of FIG. 2, the switching element S6 of the fifth leg 221 is opened at t10, and then the switching element S7 of the sixth leg 222 is opened at t12 after the first shift amount ⁇ 1 has elapsed.
  • the switching element S5 of the fifth leg 221 is closed a second shift amount ⁇ 2 after the switching element S1 of the third leg 211 is closed.
  • the second shift amount ⁇ 2 is smaller than the first shift amount ⁇ 1.
  • the second shift amount ⁇ 2 can be set based on a power command value of the DC power output from the first conversion unit 22 and a power calculation value of the DC power output from the first conversion unit 22.
  • the power command value of the DC power output from the first conversion unit 22 is a command value requested from a higher-level system to the power supply device 1 (more specifically, the control unit 50) as the DC power to be output from the power supply device 1.
  • the control unit 50 sets a first voltage value of the DC voltage constituting the DC power output from the first conversion unit 22 based on the power command value, and sets a current value of the DC current output from the first conversion unit 22.
  • the second shift amount ⁇ 2 is set based on a pre-stored arithmetic expression so as to realize a current of this current value. This arithmetic expression is shown as the following equation (1).
  • V1 is the potential across both ends of the primary winding 24A
  • V2' is the potential across both ends of the secondary winding 24B and the reactor L (i.e., between the fifth node 221N and the sixth node 222N)
  • P is the output power
  • ⁇ 2 is the second shift amount
  • ⁇ is the switching frequency of the switching element
  • L is the inductance value of the reactor L.
  • the power calculation value of the DC power output from the first conversion unit 22 is a calculation value calculated by multiplying the voltage value (preferably the first voltage value) of the DC voltage (output voltage) output from the first conversion unit 22 by the current value of the DC current (consumption current) output from the first conversion unit 22.
  • the voltage value (preferably the first voltage value) of the DC voltage (output voltage) output from the first conversion unit 22 is measured by a voltage sensor (e.g., a voltmeter) not shown, and the current value of the DC current (consumption current) output from the first conversion unit 22 is measured by a current sensor (e.g., an ammeter) not shown.
  • the control unit 50 can calculate the power calculation value based on these two detection results.
  • the control unit 50 controls the converter 20 by feedback control so that the power calculation value is equal to the power command value.
  • the second shift amount ⁇ 2 is set to half the first shift amount ⁇ 1. Therefore, as shown in FIG. 2, the switching element S5 of the fifth leg 221 is closed at t2, which is the second shift amount ⁇ 2 after t1 at which the switching element S1 of the third leg 211 is closed. Also, when the battery 3 is being charged, the switching element S5 of the fifth leg 221 is opened at the second shift amount ⁇ 2 after t5 at which the switching element S1 of the third leg 211 is opened. That is, when the battery 3 is being charged, as shown in FIG. 2, the switching element S5 of the fifth leg 221 is opened at t6, which is the second shift amount ⁇ 2 after t5 at which the switching element S1 of the third leg 211 is opened.
  • the switching element S7 of the sixth leg 222 When the battery 3 is being charged, the switching element S7 of the sixth leg 222 is closed the second shift amount ⁇ 2 after the switching element S3 of the fourth leg 212 is closed. That is, as shown in FIG. 2, the switching element S7 of the sixth leg 222 is closed at t8, which is the second shift amount ⁇ 2 after t7, when the switching element S3 of the fourth leg 212 is closed.
  • the switching element S7 of the sixth leg 222 is opened the second shift amount ⁇ 2 after t3, when the switching element S3 of the fourth leg 212 is opened. That is, when the battery 3 is being charged, as shown in FIG. 2, the switching element S7 of the sixth leg 222 is opened at t4, which is the second shift amount ⁇ 2 after t3, when the switching element S3 of the fourth leg 212 is opened.
  • the second conversion unit 23 is driven by synchronous rectification.
  • the switching element S9 and the switching element S10 are driven by synchronous rectification.
  • the switching element S9 is in an open state from t3 to t5
  • the switching element S10 is in an open state from t7 to t9.
  • a current having a waveform as indicated by I9 flows through the switching element S9
  • a current having a waveform as indicated by I10 flows through the switching element S10.
  • the control unit 50 closes the switching element S9, which is in the open state, when a forward current flows through the diode S9D.
  • the second conversion unit 23 rectifies the electrical energy stored in the second tertiary winding 24CB, a current flows through the third reactor coil 23L, the second capacitor 26, and the diode S10D.
  • the control unit 50 closes the switching element S10, which is in the open state, when a forward current flows through the diode S10D.
  • the power consumption of the diode S9D or the diode S10D is a value obtained by multiplying the current by the forward voltage.
  • the power consumption in switching element S9 or switching element S10 is the product of the square of the drain current and the on-resistance. Since the power consumption in switching element S9 or switching element S10 is sufficiently smaller than the power consumption in diode S9D or diode S10D, the loss is reduced and the decrease in efficiency (conversion efficiency) in second conversion unit 23 can be suppressed. Therefore, by driving second conversion unit 23 as described above, it is possible to output a voltage efficiently.
  • the positive current is the current flowing through the third reactor coil 23L, the second capacitor 26, and the switching element S9, or the current flowing through the third reactor coil 23L, the second capacitor 26, and the switching element S10.
  • FIG. 3A a positive current (I>0) and a negative current (I ⁇ 0) flow through the third reactor coil 23L.
  • the positive current is the current flowing through the third reactor coil 23L, the second capacitor 26, and the switching element S9, or the current flowing through the third reactor coil 23L, the second capacitor 26, and the switching element S10.
  • the negative current is the current flowing through the switching element S9, the second capacitor 26, and the third reactor coil 23L, or the current flowing through the switching element S10, the second capacitor 26, and the third reactor coil 23L.
  • the current in order for such a negative current to flow through the second conversion unit 23, the current must flow through switching element S9 and switching element S10, so in addition to diodes S9D and S10D, switching elements S9 and S10 are provided in the second conversion unit 23.
  • the second conversion unit 23 has a snubber circuit formed by the resistor R and the capacitor 27.
  • switching element S9 is open from t3 to t5, and switching element S10 is open from t7 to t9.
  • the second voltage value of the DC voltage output from the second conversion unit 23 can be changed depending on the period during which switching element S9 is open and the period during which switching element S10 is open.
  • the period during which switching element S9 is open and the period during which switching element S10 is open correspond to (carrier period/2) - first shift amount ⁇ 1. Therefore, in this embodiment, the DC voltage of the second voltage value can be controlled based on the first shift amount ⁇ 1.
  • the second conversion unit 23 can also generate DC power consisting of a DC voltage of a second voltage value based on the electrical energy stored in the battery 3.
  • the supply of DC power from the supply unit 2 is stopped, and the DC power of the battery 3 is transmitted from the secondary winding 24B of the transformer 24 to the primary winding 24A, and from the primary winding 24A to the tertiary winding 24C.
  • FIG. 4 shows a timing chart of the control unit 50 driving each of the multiple switching elements provided in the converter 20 when DC power is output from the second conversion unit 23 based on such DC power from the battery 3.
  • the control unit 50 drives the switching elements S1-S10 while switching them sequentially between eight states from the first state to the eighth state.
  • the first state in which DC power is output from the second conversion unit 23 based on DC power from the battery 3 is the state between t1 and t2 in FIG. 4.
  • the control unit 50 closes the switching elements S1, S3, S5, S7, S9, and S10, and opens the switching elements S2, S4, S6, and S8.
  • the second state is the state between t2 and t3 in FIG. 4, and in this second state, the control unit 50 closes the switching elements S1, S3, S5, S8, S9, and S10, and opens the switching elements S2, S4, S6, and S7.
  • the third state is the state between t3 and t4 in FIG. 4, and in this third state, the control unit 50 closes the switching elements S1, S4, S5, S8, and S10, and opens the switching elements S2, S3, S6, S7, and S9.
  • the fourth state is the state between t4 and t5 in FIG. 2, and in this fourth state, the control unit 50 closes the switching elements S1, S4, S6, S8, and S10, and opens the switching elements S2, S3, S5, S7, and S9.
  • the fifth state is the state between t5 and t6 in FIG. 2, and in this fifth state, the control unit 50 closes the switching elements S2, S4, S6, S8, S9, and S10, and opens the switching elements S1, S3, S5, and S7.
  • the sixth state is the state between t6 and t7 in FIG. 2, and in this sixth state, the control unit 50 closes the switching elements S2, S4, S6, S7, S9, and S10, and opens the switching elements S1, S3, S5, and S8.
  • the seventh state is the state between t7 and t8 in FIG. 2, and in this seventh state, the control unit 50 closes the switching elements S2, S3, S6, S7, and S9, and opens the switching elements S1, S4, S5, S8, and S10.
  • the eighth state is the state between t8 and t9 in FIG. 2, and in this eighth state, the control unit 50 closes the switching elements S2, S3, S5, S7, and S9, and opens the switching elements S1, S4, S6, S8, and S10.
  • Switching elements S1, S2, S3, and S4 are driven in the same manner as when charging battery 3 described above. That is, as shown in FIG. 4, switching element S1 of third leg 211 and switching element S4 of fourth leg 212 are shifted by a preset first shift amount ⁇ 1 to be in a closed state, and switching element S1 of third leg 211 and switching element S4 of fourth leg 212 are shifted by a first shift amount ⁇ 1 to be in an open state.
  • the switching element S2 of the third leg 211 and the switching element S3 of the fourth leg 212 are shifted by the first shift amount ⁇ 1 and are put into a closed state, and the switching element S2 of the third leg 211 and the switching element S3 of the fourth leg 212 are shifted by the first shift amount ⁇ 1 and are put into an open state.
  • the switching element S5 of the fifth leg 221 and the switching element S8 of the sixth leg 222 are shifted by the first shift amount ⁇ 1 and put into a closed state
  • the switching element S5 of the fifth leg 221 and the switching element S8 of the sixth leg 222 are shifted by the first shift amount ⁇ 1 and put into an open state.
  • the switching element S6 of the fifth leg 221 and the switching element S7 of the sixth leg 222 are shifted by the first shift amount ⁇ 1 and are put into a closed state, and the switching element S6 of the fifth leg 221 and the switching element S7 of the sixth leg 222 are shifted by the first shift amount ⁇ 1 and are put into an open state.
  • the switching element S5 of the fifth leg 221 When generating DC power consisting of a DC voltage of the second voltage value based on the electric energy charged in the battery 3, the switching element S5 of the fifth leg 221 is closed the second shift amount ⁇ 2 before the switching element S1 of the third leg 211 is closed. That is, as shown in FIG. 4, the switching element S5 of the fifth leg 221 is closed at t8, which is the second shift amount ⁇ 2 before t9, when the switching element S1 of the third leg 211 is closed. Also, the switching element S5 of the fifth leg 221 is opened the second shift amount ⁇ 2 before the switching element S1 of the third leg 211 is opened. That is, as shown in FIG. 4, the switching element S5 of the fifth leg 221 is opened at t4, which is the second shift amount ⁇ 2 before t5, when the switching element S1 of the third leg 211 is opened.
  • the switching element S7 of the sixth leg 222 is closed the second shift amount ⁇ 2 before the switching element S3 of the fourth leg 212 is closed. That is, as shown in FIG. 4, the switching element S7 of the sixth leg 222 is closed at t6, which is the second shift amount ⁇ 2 before t7, when the switching element S3 of the fourth leg 212 is closed. Also, the switching element S7 of the sixth leg 222 is opened the second shift amount ⁇ 2 before the switching element S3 of the fourth leg 212 is opened. That is, as shown in FIG. 4, the switching element S7 of the sixth leg 222 is opened at t10, which is the second shift amount ⁇ 2 before t9, when the switching element S3 of the fourth leg 212 is opened.
  • switching element S9 is open between t3 and t5
  • switching element S10 is open between t7 and t9.
  • the switching elements of the inverter 10 and the converter 20 are described as n-type MOS-FETs.
  • the switching elements may be p-type MOS-FETs or switching elements other than FETs (e.g., IGBTs or bipolar transistors).
  • the inverter 10 and converter 20 are described as converting AC power to DC power using switching elements, but the inverter 10 may also be configured to convert AC power to DC power using diodes.
  • control unit 50 drives the switching element in the first state to the eighth state, and each state is described. However, it is also possible to drive the switching element based on more than eight states from the first state to the eighth state, or based on seven states or less. In addition, the state of the switching element in each state is merely an example, and it is also possible to drive the switching element in a form different from that of the above embodiment.
  • the AC power supplied to the inverter 10 is described as AC power from a commercial power source, but the AC power supplied to the inverter 10 may be AC power different from the AC power of the commercial power source.
  • the tertiary winding 24C of the transformer 24 is described as being composed of a first tertiary winding 24CA and a second tertiary winding 24CB, but the tertiary winding 24C may be a single winding or may be three or more windings.
  • the average value of the composite current of the current flowing through the first tertiary winding 24CA and the current flowing through the second tertiary winding 24CB is zero.
  • the average value of the composite current of the current flowing through the first tertiary winding 24CA and the current flowing through the second tertiary winding 24CB does not have to be zero.
  • the current flowing through the first tertiary winding 24CA and the current flowing through the second tertiary winding 24CB may be a current in which a predetermined DC current is superimposed.
  • the DC voltage of the second voltage value is described as being controlled based on the first shift amount ⁇ 1, but the DC voltage of the second voltage value may also be controlled by, for example, feedback control.
  • the second shift amount ⁇ 2 is described as being set based on the power command value of the DC power output from the first conversion unit 22 and the power calculation value of the DC power output from the first conversion unit 22.
  • the second shift amount ⁇ 2 may be configured to be set in advance, or may be configured to be changed as appropriate depending on, for example, the type of load on the converter 20.
  • the characteristic configuration of the power supply device 1 is that a first leg 11 in which a high-side switching element 11H and a low-side switching element 11L are connected in series and a second leg 12 in which a high-side switching element 12H and a low-side switching element 12L are connected in series are provided in parallel with each other, an inverter 10 that converts AC power to DC power, and an isolated transformer (multi-port transformer) 24 having a primary winding 24A, a secondary winding 24B, and a tertiary winding 24C are provided, and the DC power from the inverter 10 is configured as a DC voltage of a first voltage value that charges a battery 3.
  • the converter 20 has an input section 21 that oscillates the DC power from the inverter 10 at a predetermined period and inputs it to the primary winding 24A, a first conversion section 22 that converts the AC power generated in the secondary winding 24B into DC power composed of a DC voltage of a first voltage value, and a second conversion section 23 that converts the AC power generated in the tertiary winding 24C into DC power composed of a DC voltage of a second voltage value lower than the first voltage value, and the second conversion section 23 converts the AC power generated in the tertiary winding 24C into DC power composed of a DC voltage of the second voltage value by synchronous rectification.
  • This characteristic configuration makes it possible to output DC power consisting of a DC voltage of a first voltage value from the first conversion unit 22 of the converter 20, and at the same time output DC power consisting of a DC voltage of a second voltage value from the second conversion unit 23. Furthermore, the above-mentioned characteristic configuration makes it possible to easily output DC power consisting of a DC voltage of a first voltage value and DC power consisting of a DC voltage of a second voltage value with a simple configuration.
  • the input section 21 includes a third leg 211 in which a high-side switching element S1 and a low-side switching element S2 are connected in series, and a fourth leg 212 in which a high-side switching element S3 and a low-side switching element S4 are connected in series, which are provided in parallel to each other;
  • the first conversion section 22 includes a fifth leg 221 in which a high-side switching element S5 and a low-side switching element S6 are connected in series, and a sixth leg 222 in which a high-side switching element S7 and a low-side switching element S8 are connected in series, which are provided in parallel to each other;
  • the high-side switching element S1 of the third leg 211 and the low-side switching element S4 of the fourth leg 212 are shifted by a preset first shift amount to be in a closed state;
  • the low-side switching element S2 of the third leg 211 and the fourth leg 212 are shifted by a preset first shift amount to be in a
  • the high-side switching element S3 of the fifth leg 221 and the low-side switching element S8 of the sixth leg 222 are closed with a shift of the first shift amount
  • the high-side switching element S5 of the fifth leg 221 and the low-side switching element S8 of the sixth leg 222 are closed with a shift of the first shift amount
  • the low-side switching element S6 of the fifth leg 221 and the high-side switching element S7 of the sixth leg 222 are closed with a shift of the first shift amount
  • the high-side switching element S5 of the fifth leg 221 is closed a second shift amount smaller than the first shift amount by which the high-side switching element S1 of the third leg 211 is closed
  • the high-side switching element SS7 of the sixth leg 222 is closed a second shift amount by which the high-side switching element S3 of the fourth leg 212 is closed.
  • the battery 3 can be charged based on the AC power supplied to the inverter 10, and at the same time, a DC voltage with a voltage value different from the DC voltage that charges the battery 3 can be supplied to a load other than the battery.
  • the input unit 21 includes a third leg 211 in which a high-side switching element S1 and a low-side switching element S2 are connected in series, and a fourth leg 212 in which a high-side switching element S3 and a low-side switching element S4 are connected in series, which are provided in parallel to each other;
  • the first conversion unit 22 includes a fifth leg 221 in which a high-side switching element S5 and a low-side switching element S6 are connected in series, and a sixth leg 222 in which a high-side switching element S7 and a low-side switching element S8 are connected in series, which are provided in parallel to each other;
  • the high-side switching element S1 of the third leg 211 and the low-side switching element S3 of the fourth leg 212 are shifted by a preset first shift amount to be in a closed state; and the low-side switching element S2 of the third leg 211 and the high-side switching element S3 of the fourth leg 212 are shifted by a first
  • the high-side switching element S5 of the fifth leg 221 and the low-side switching element S8 of the sixth leg 222 are closed with a shift of a first shift amount
  • the low-side switching element S6 of the fifth leg 221 and the high-side switching element S7 of the sixth leg 222 are closed with a shift of a first shift amount
  • the high-side switching element S5 of the fifth leg 221 is closed a second shift amount smaller than the first shift amount after the high-side switching element S1 of the third leg 211 is closed
  • the high-side switching element S7 of the sixth leg 222 is closed a second shift amount before the high-side switching element S3 of the fourth leg 212 is opened.
  • the tertiary winding 24C is composed of a first tertiary winding 24CA and a second tertiary winding 24CB, and the average value of the combined current of the current flowing through the first tertiary winding 24CA and the current flowing through the second tertiary winding 24CB can be set to zero.
  • the DC voltage of the second voltage value is controlled based on the first shift amount.
  • the output of the DC voltage of the second voltage value can also be performed based on the control of the output of the DC voltage of the first voltage value. Therefore, it is possible to output DC voltages of different voltage values with simple control.
  • the second shift amount is set based on the power command value of the DC power output from the first conversion unit 22 and the power calculation value of the DC power output from the first conversion unit 22.
  • the second shift amount can be easily set. Therefore, it is possible to output DC voltages of different voltage values with simple control.
  • the second shift amount is ⁇ 2
  • the switching frequency of the switching element is ⁇
  • the inductance value of the reactor is L
  • the second shift amount is It is preferable to set the value based on the above.
  • the second shift amount ⁇ 2 can be easily set using the potential V1 across the primary winding 24A, the potential V2' across the secondary winding 24B and the reactor, the output power P, the switching frequency ⁇ of the switching element, and the inductance value L of the reactor.
  • the tertiary winding 24C is composed of a first tertiary winding 24CA and a second tertiary winding 24CB, and the first tertiary winding 24CA and the second tertiary winding 24CB are connected to each other at the end of the first tertiary winding 24CA and the beginning of the winding of the second tertiary winding 24CB, and the second conversion unit 23 is composed of a switching element (first switching element) S9 having a drain terminal connected to the beginning of the winding of the first tertiary winding 24CA, a switching element (second switching element) S10 having a drain terminal connected to the end of the winding of the second tertiary winding 24CB, and an anode terminal connected to the source terminal of the switching element S9, It may include a diode (first diode) S9D having a cathode terminal connected to the drain terminal of the switching
  • the power consumption in switching element S9 and switching element S10 is much smaller than the power consumption in diodes S9D and S10D, so the loss is small and the decrease in efficiency (conversion efficiency) in the second conversion unit 23 can be suppressed. Therefore, it is possible to output the voltage efficiently.
  • the switching element S9 and the switching element S10 are driven by synchronous rectification.
  • This configuration makes it possible to improve the efficiency of the second conversion unit 23 compared to when the second conversion unit 23 is driven by diode rectification. Furthermore, when no load is connected to the second conversion unit 23, it is possible to pass a positive current as shown in FIG. 3(B) or a negative current as shown in FIG. 3(C) through the second conversion unit 23, making it possible to make the average current value zero as shown in FIG. 3(A).
  • the second conversion unit 23 further includes a diode (third diode) 23D1 having an anode terminal connected to the winding start end of the first tertiary winding 24CA, a diode (fourth diode) 23D2 having an anode terminal connected to the winding end end of the second tertiary winding 24CB, a resistor R provided between the cathode terminal of the diode 23D1 and the cathode terminal of the diode 23D2 and the other terminal of the third reactor coil 23L, and a capacitor (second capacitor) 27 provided between the cathode terminal of the diode 23D1 and the source terminal of the switching element S9.
  • a diode (third diode) 23D1 having an anode terminal connected to the winding start end of the first tertiary winding 24CA
  • a diode (fourth diode) 23D2 having an anode terminal connected to the winding end end end of the second tertiary winding
  • the electrical energy stored in the first tertiary winding 24CA can be reduced by passing a current through the diode 23D1, resistor R, and third reactor coil 23L
  • the electrical energy stored in the second tertiary winding 24CB can be reduced by passing a current through the diode 23D2, resistor R, and third reactor coil 23L.
  • the present invention can be used in power supply devices.

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Abstract

A power supply device according to the present invention includes: an inverter in which a first leg having a switching element and a switching element and a second leg having a switching element and a switching element are provided in parallel with each other; and a converter provided with a multiport transformer having a primary winding, a secondary winding, and a tertiary winding. The converter includes an input unit that amplifies DC power from the inverter at a predetermined cycle and inputs the power to the primary winding, a first conversion unit that converts AC power generated in the secondary winding into DC power, and a second conversion unit that converts AC power generated in the tertiary winding into DC power. The second conversion unit converts AC power generated in the tertiary winding into DC power by means of synchronous rectification.

Description

電源装置Power Supplies
　本発明は、車両に搭載されるバッテリを充放電する電源装置に関する。 The present invention relates to a power supply device that charges and discharges a battery installed in a vehicle.
　従来、交流電力の入力に応じて、互いに異なる電圧値の直流電圧を出力する電源装置が利用されている。このような電源装置として、例えば下記に出典を示す特許文献１－５に記載のものがある。 Conventionally, power supply devices have been used that output DC voltages with different voltage values in response to AC power input. Examples of such power supply devices include those described in Patent Documents 1-5, the sources of which are shown below.
　特許文献１－３には電力変換装置が記載されている。また、特許文献４及び５にはスイッチング電源装置が記載されている。特許文献１－３の電力変換装置及び特許文献４及び５のスイッチング電源装置は、例えばバッテリを充電可能な第１電圧値の直流電圧の出力や、第１電圧値よりも低い第２電圧値の直流電圧の出力に利用される。 Patent documents 1-3 describe power conversion devices. Furthermore, patent documents 4 and 5 describe switching power supply devices. The power conversion devices of patent documents 1-3 and the switching power supply devices of patent documents 4 and 5 are used, for example, to output a DC voltage of a first voltage value capable of charging a battery, or to output a DC voltage of a second voltage value lower than the first voltage value.
特開２０１６－１４０１２６号公報JP 2016-140126 A 特開２０１６－１５８３５３号公報JP 2016-158353 A 国際公開２０１５／１７４３３１号公報International Publication No. 2015/174331 特開２００８－２０６３０４号公報JP 2008-206304 A 特開２００９－２３２５０２号公報JP 2009-232502 A
　特許文献１－３の電力変換装置や、特許文献４及び５のスイッチング電源装置は、装置全体のサイズが大きくなり、コストも高くなる。また、例えばマルチポートトランスを用いて互いに異なる電圧値の直流電圧を同時に出力する場合には、制御が複雑となり容易に出力することができない。 The power conversion devices of Patent Documents 1-3 and the switching power supply devices of Patent Documents 4 and 5 are large in overall device size and cost. In addition, for example, when using a multi-port transformer to simultaneously output DC voltages of different voltage values, the control becomes complicated and output cannot be easily achieved.
　そこで、容易に互いに異なる電圧値の直流電圧を出力することが可能な電源装置が求められる。 Therefore, there is a demand for a power supply device that can easily output DC voltages with different voltage values.
　本発明に係る電源装置の特徴構成は、ハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第１レグとハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第２レグとが互いに並列に設けられ、交流電力を直流電力に変換するインバータと、一次巻線、二次巻線、及び三次巻線を有する絶縁型のマルチポートトランスが設けられ、前記インバータからの前記直流電力を、バッテリを充電する第１電圧値の直流電圧で構成される直流電力に変換するコンバータと、を備え、前記コンバータは、前記インバータからの前記直流電力を所定の周期で振幅させて前記一次巻線に入力する入力部と、前記二次巻線に生じる交流電力を、前記第１電圧値の直流電圧で構成される直流電力に変換する第１変換部と、前記三次巻線に生じる交流電力を、前記第１電圧値よりも低い第２電圧値の直流電圧で構成される直流電力に変換する第２変換部と、を有し、前記第２変換部は、前記三次巻線に生じる交流電力を、同期整流により前記第２電圧値の直流電圧で構成される直流電力に変換する点にある。 The power supply device according to the present invention has a first leg in which a high-side switching element and a low-side switching element are connected in series, and a second leg in which a high-side switching element and a low-side switching element are connected in series, which are arranged in parallel with each other, and includes an inverter that converts AC power to DC power, and a converter that is provided with an insulated multi-port transformer having a primary winding, a secondary winding, and a tertiary winding and converts the DC power from the inverter into DC power composed of a DC voltage of a first voltage value that charges a battery. The converter has an input unit that oscillates the DC power from the inverter at a predetermined period and inputs it to the primary winding, a first conversion unit that converts the AC power generated in the secondary winding into DC power composed of a DC voltage of the first voltage value, and a second conversion unit that converts the AC power generated in the tertiary winding into DC power composed of a DC voltage of a second voltage value lower than the first voltage value, and the second conversion unit converts the AC power generated in the tertiary winding into DC power composed of a DC voltage of the second voltage value by synchronous rectification.
　このような特徴構成とすれば、コンバータの第１変換部から第１電圧値の直流電圧で構成される直流電力を出力すると同時に、第２変換部から第２電圧値の直流電圧で構成される直流電力を出力することが可能となる。また、上述した特徴構成によれば、第１電圧値の直流電圧で構成される直流電力の出力と、第２電圧値の直流電圧で構成される直流電力の出力とを、簡素な構成で容易に行うことが可能となる。 With such a characteristic configuration, it is possible to output DC power consisting of a DC voltage of a first voltage value from the first conversion unit of the converter, and at the same time output DC power consisting of a DC voltage of a second voltage value from the second conversion unit. Furthermore, with the above-mentioned characteristic configuration, it is possible to easily output DC power consisting of a DC voltage of a first voltage value and DC power consisting of a DC voltage of a second voltage value with a simple configuration.
は、電源装置の構成を示す回路図である。FIG. 2 is a circuit diagram showing a configuration of a power supply device. は、バッテリの充電時の電源装置のタイミングチャートである。4 is a timing chart of the power supply device when charging the battery. は、第２変換部に流れる正電流及び負電流を説明する図である。10 is a diagram illustrating a positive current and a negative current flowing in a second conversion unit. FIG. は、バッテリからの出力に基づいて直流電力を出力する時の電源装置のタイミングチャートである。1 is a timing chart of the power supply device when outputting DC power based on the output from the battery.
　本発明に係る電源装置は、車両に搭載されるバッテリを充放電することが可能であって、複数の端子の夫々から互いに異なる電圧値の直流電圧で構成される直流電力を出力することができる。以下、本実施形態の電源装置１について説明する。 The power supply device according to the present invention is capable of charging and discharging a battery mounted on a vehicle, and can output DC power consisting of DC voltages with different voltage values from each of a number of terminals. The power supply device 1 of this embodiment will be described below.
　図１は、電源装置１の回路図である。図１に示されるように、電源装置１は、インバータ１０、コンバータ２０、リアクトルコイル３０、及び制御部５０を備えて構成される。各機能部は、上述した直流電力の出力に係る処理を行うために、ＣＰＵを中核部材としてハードウェア又はソフトウェア或いはその両方で構築されている。 FIG. 1 is a circuit diagram of the power supply device 1. As shown in FIG. 1, the power supply device 1 is configured with an inverter 10, a converter 20, a reactor coil 30, and a control unit 50. Each functional unit is constructed with hardware or software, or both, with a CPU as the core component, in order to perform the processes related to the output of the DC power described above.
　インバータ１０は、交流電力を直流電力に変換して出力する。本実施形態では、交流電力とは、電圧値が所定の周期で振幅する交流電圧から構成される電力をいう。具体的には、交流電圧は、商用周波数（例えば５０Ｈｚや６０Ｈｚ）で振幅し、単相三線式で供給される商用電源から取り出した２００Ｖ（実効値）の交流電圧が相当する。直流電力とは、基準電圧に対して一定の電圧値（リップル電圧は除く）となる直流電圧から構成される電力をいう。本実施形態では、インバータ１０には商用電源による交流電力が供給される。インバータ１０は、このような交流電圧で構成される交流電力を、直流電圧を含む直流電力に変換する。インバータ１０は、一対の出力部１０Ａ,１０Ｂが設けられており、変換した直流電力をこの一対の出力部１０Ａ,１０Ｂを介して後述するコンバータ２０に出力する。 The inverter 10 converts AC power into DC power and outputs it. In this embodiment, AC power refers to power composed of an AC voltage whose voltage value oscillates at a predetermined cycle. Specifically, the AC voltage oscillates at a commercial frequency (e.g., 50 Hz or 60 Hz) and corresponds to an AC voltage of 200 V (effective value) taken from a commercial power source supplied in a single-phase three-wire system. DC power refers to power composed of a DC voltage that has a constant voltage value (excluding ripple voltage) relative to a reference voltage. In this embodiment, the inverter 10 is supplied with AC power from a commercial power source. The inverter 10 converts the AC power composed of such AC voltage into DC power including a DC voltage. The inverter 10 is provided with a pair of output units 10A, 10B, and outputs the converted DC power to the converter 20 described later via the pair of output units 10A, 10B.
　インバータ１０は、第１レグ１１と第２レグ１２とを有する。第１レグ１１、及び第２レグ１２は、出力部１０Ａ,１０Ｂに対して互いに並列に設けられる。これにより、第１レグ１１の一方の端部１１Ａと、第２レグ１２の一方の端部１２Ａとが、出力部１０Ａに接続され、第１レグ１１の他方の端部１１Ｂと、第２レグ１２の他方の端部１２Ｂとが、出力部１０Ｂに接続される。 The inverter 10 has a first leg 11 and a second leg 12. The first leg 11 and the second leg 12 are arranged in parallel with each other with respect to the output units 10A and 10B. As a result, one end 11A of the first leg 11 and one end 12A of the second leg 12 are connected to the output unit 10A, and the other end 11B of the first leg 11 and the other end 12B of the second leg 12 are connected to the output unit 10B.
　第１レグ１１は、直列に接続されたハイサイドのスイッチング素子１１Ｈ及びローサイドのスイッチング素子１１Ｌを有する。本実施形態では、スイッチング素子１１Ｈ及びスイッチング素子１１Ｌは、ｎ型ＭＯＳ－ＦＥＴ（metal-oxide-semiconductor field-effect transistor）が用いられる。スイッチング素子１１Ｈは、ドレーン端子が端部１１Ａに接続され、ソース端子がスイッチング素子１１Ｌのドレーン端子に接続される。スイッチング素子１１Ｌのソース端子は端部１１Ｂに接続される。スイッチング素子１１Ｈ及びスイッチング素子１１Ｌの夫々のゲート端子は、制御部５０に接続される。また、スイッチング素子１１Ｈ及びスイッチング素子１１Ｌの夫々のソース端子とドレーン端子との間には、アノード端子がソース端子に接続され、カソード端子がドレーン端子に接続されたダイオード１１ＨＤ,１１ＬＤが設けられる。 The first leg 11 has a high-side switching element 11H and a low-side switching element 11L connected in series. In this embodiment, n-type MOS-FETs (metal-oxide-semiconductor field-effect transistors) are used for the switching elements 11H and 11L. The drain terminal of the switching element 11H is connected to the end 11A, and the source terminal is connected to the drain terminal of the switching element 11L. The source terminal of the switching element 11L is connected to the end 11B. The gate terminals of the switching elements 11H and 11L are connected to the control unit 50. In addition, diodes 11HD and 11LD are provided between the source terminals and drain terminals of the switching elements 11H and 11L, with the anode terminals connected to the source terminals and the cathode terminals connected to the drain terminals.
　また、第２レグ１２は、直列に接続されたハイサイドのスイッチング素子１２Ｈ及びローサイドのスイッチング素子１２Ｌを有する。本実施形態では、スイッチング素子１２Ｈ及びスイッチング素子１２Ｌも、ｎ型ＭＯＳ－ＦＥＴが用いられる。スイッチング素子１２Ｈは、ドレーン端子が端部１２Ａに接続され、ソース端子がスイッチング素子１２Ｌのドレーン端子に接続される。スイッチング素子１２Ｌのソース端子は端部１２Ｂに接続される。スイッチング素子１２Ｈ及びスイッチング素子１２Ｌの夫々のゲート端子は、制御部５０に接続される。また、スイッチング素子１２Ｈ及びスイッチング素子１２Ｌの夫々のソース端子とドレーン端子との間には、アノード端子がソース端子に接続され、カソード端子がドレーン端子に接続されたダイオード１２ＨＤ,１２ＬＤが設けられる。 The second leg 12 also has a high-side switching element 12H and a low-side switching element 12L connected in series. In this embodiment, n-type MOS-FETs are used for the switching elements 12H and 12L. The drain terminal of the switching element 12H is connected to the end 12A, and the source terminal is connected to the drain terminal of the switching element 12L. The source terminal of the switching element 12L is connected to the end 12B. The gate terminals of the switching elements 12H and 12L are connected to the control unit 50. Diodes 12HD and 12LD are provided between the source terminals and drain terminals of the switching elements 12H and 12L, with the anode terminals connected to the source terminals and the cathode terminals connected to the drain terminals.
　インバータ１０の出力部１０Ａと出力部１０Ｂとに亘ってコンデンサ１５が設けられる。コンデンサ１５は、インバータ１０により変換された直流電圧を平滑する。 A capacitor 15 is provided across output section 10A and output section 10B of inverter 10. Capacitor 15 smoothes the DC voltage converted by inverter 10.
　リアクトルコイル３０は、第１レグ１１における２つのスイッチング素子（スイッチング素子１１Ｈ及びスイッチング素子１１Ｌ）の間の第１ノード１１Ｎに一方の端子３０Ｂが接続される。第１レグ１１における２つのスイッチング素子の間の第１ノード１１Ｎとは、スイッチング素子１１Ｈのソース端子とスイッチング素子１１Ｌのドレーン端子とを接続する線（例えば基板の配線パターンや、ハーネス等のケーブル）である。もちろん、スイッチング素子１１Ｈのソース端子や、スイッチング素子１１Ｌのドレーン端子であってもよい。リアクトルコイル３０は２つの端子３０Ａ,３０Ｂを有しており、端子３０Ｂが第１ノード１１Ｎに接続される。 The reactor coil 30 has one terminal 30B connected to a first node 11N between two switching elements (switching element 11H and switching element 11L) in the first leg 11. The first node 11N between the two switching elements in the first leg 11 is a line (e.g., a wiring pattern on a board or a cable such as a harness) connecting the source terminal of switching element 11H and the drain terminal of switching element 11L. Of course, it may be the source terminal of switching element 11H or the drain terminal of switching element 11L. The reactor coil 30 has two terminals 30A, 30B, and the terminal 30B is connected to the first node 11N.
　リアクトルコイル３０の他方の端子３０Ａと第２レグ１２における２つのスイッチング素子（スイッチング素子１２Ｈ及びスイッチング素子１２Ｌ）の間の第２ノード１２Ｎとに亘って、交流電力が供給される。第２レグ１２における２つのスイッチング素子の間の第２ノード１２Ｎとは、スイッチング素子１２Ｈのソース端子とスイッチング素子１２Ｌのドレーン端子とを接続する線（例えば基板の配線パターンや、ハーネス等のケーブル）である。もちろん、スイッチング素子１２Ｈのソース端子や、スイッチング素子１２Ｌのドレーン端子であってもよい。リアクトルコイル３０の端子３０Ａは交流電力が供給される供給部２の一方の端子に接続され、供給部２の他方の端子は第２ノード１２Ｎに接続される。したがって、インバータ１０は、第１レグ１１が有するスイッチング素子１１Ｈ及びスイッチング素子１１Ｌと、第２レグ１２が有するスイッチング素子１２Ｈ及びスイッチング素子１２Ｌとにより、交流電力を直流電力に変換する。 AC power is supplied across the other terminal 30A of the reactor coil 30 and a second node 12N between the two switching elements (switching element 12H and switching element 12L) in the second leg 12. The second node 12N between the two switching elements in the second leg 12 is a line (e.g., a wiring pattern on a board or a cable such as a harness) connecting the source terminal of the switching element 12H and the drain terminal of the switching element 12L. Of course, it may be the source terminal of the switching element 12H or the drain terminal of the switching element 12L. The terminal 30A of the reactor coil 30 is connected to one terminal of the supply unit 2 to which AC power is supplied, and the other terminal of the supply unit 2 is connected to the second node 12N. Therefore, the inverter 10 converts AC power into DC power by the switching element 11H and switching element 11L of the first leg 11 and the switching element 12H and switching element 12L of the second leg 12.
　コンバータ２０は、インバータ１０からの直流電力を、バッテリ３を充電可能な第１電圧値の直流電圧で構成される直流電力に変換する。インバータ１０からの直流電力とは、インバータ１０の出力部１０Ａ,１０Ｂから出力される直流電力である。バッテリ３とは、電源装置１が充電する車両に搭載されるバッテリであって、コンバータ２０から出力される直流電力に基づいて充電される。バッテリ３の充電は、所定の電圧値の直流電圧で行われるが、インバータ１０から出力される直流電力を構成する直流電圧の電圧値は、インバータ１０に入力される交流電圧の電圧値（２００Ｖ）程度である。コンバータ２０は、インバータ１０から出力される直流電圧の電圧値を、バッテリ３の充電に必要な電圧値（「第１電圧値」に相当し、例えば数百Ｖ）の直流電圧に昇圧する。 The converter 20 converts the DC power from the inverter 10 into DC power composed of a DC voltage of a first voltage value capable of charging the battery 3. The DC power from the inverter 10 is the DC power output from the output parts 10A and 10B of the inverter 10. The battery 3 is a battery mounted on the vehicle that is charged by the power supply device 1, and is charged based on the DC power output from the converter 20. The battery 3 is charged with a DC voltage of a predetermined voltage value, but the voltage value of the DC voltage that constitutes the DC power output from the inverter 10 is about the voltage value (200V) of the AC voltage input to the inverter 10. The converter 20 boosts the voltage value of the DC voltage output from the inverter 10 to a DC voltage of a voltage value (equivalent to the "first voltage value", for example several hundred V) required for charging the battery 3.
　本実施形態のコンバータ２０は、入力部２１、第１変換部２２、第２変換部２３、及びマルチポートトランス（以下「トランス」とする）２４を有する。本実施形態では、トランス２４は一次巻線２４Ａと二次巻線２４Ｂと三次巻線２４Ｃとを有する、絶縁型で構成される。 The converter 20 of this embodiment has an input section 21, a first conversion section 22, a second conversion section 23, and a multi-port transformer (hereinafter referred to as "transformer") 24. In this embodiment, the transformer 24 is configured as an insulated type having a primary winding 24A, a secondary winding 24B, and a tertiary winding 24C.
　入力部２１は、インバータ１０からの直流電力を、所定の周期で振幅させて一次巻線２４Ａに入力する。入力部２１は、第３レグ２１１及び第４レグ２１２を有し、第３レグ２１１と第４レグ２１２とは、出力部１０Ａ,１０Ｂに対して互いに並列に設けられる。したがって、第３レグ２１１の一方の端部２１１Ａと、第４レグ２１２の一方の端部２１２Ａとが、出力部１０Ａに接続され、第３レグ２１１の他方の端部２１１Ｂと、第４レグ２１２の他方の端部２１２Ｂとが、出力部１０Ｂに接続される。 The input unit 21 oscillates the DC power from the inverter 10 at a predetermined period and inputs it to the primary winding 24A. The input unit 21 has a third leg 211 and a fourth leg 212, which are provided in parallel with each other with respect to the output units 10A and 10B. Therefore, one end 211A of the third leg 211 and one end 212A of the fourth leg 212 are connected to the output unit 10A, and the other end 211B of the third leg 211 and the other end 212B of the fourth leg 212 are connected to the output unit 10B.
　第３レグ２１１は、直列に接続されたハイサイドのスイッチング素子Ｓ１（以下「スイッチング素子Ｓ１」とする）及びローサイドのスイッチング素子Ｓ２（以下「スイッチング素子Ｓ２」とする）を有する。スイッチング素子Ｓ１及びスイッチング素子Ｓ２は、ｎ型ＭＯＳ－ＦＥＴが用いられる。スイッチング素子Ｓ１は、ドレーン端子が端部２１１Ａに接続され、ソース端子がスイッチング素子Ｓ２のドレーン端子に接続される。スイッチング素子Ｓ２のソース端子は端部２１１Ｂに接続される。スイッチング素子Ｓ１及びスイッチング素子Ｓ２の夫々のゲート端子は、制御部５０に接続される。また、スイッチング素子Ｓ１及びスイッチング素子Ｓ２の夫々のソース端子とドレーン端子との間には、アノード端子がソース端子に接続され、カソード端子がドレーン端子に接続されたダイオードＳ１Ｄ,Ｓ２Ｄが設けられる。 The third leg 211 has a high-side switching element S1 (hereinafter referred to as "switching element S1") and a low-side switching element S2 (hereinafter referred to as "switching element S2") connected in series. The switching elements S1 and S2 are n-type MOS-FETs. The drain terminal of the switching element S1 is connected to the end 211A, and the source terminal is connected to the drain terminal of the switching element S2. The source terminal of the switching element S2 is connected to the end 211B. The gate terminals of the switching elements S1 and S2 are connected to the control unit 50. In addition, between the source terminal and drain terminal of the switching elements S1 and S2, diodes S1D and S2D are provided, with the anode terminal connected to the source terminal and the cathode terminal connected to the drain terminal.
　第４レグ２１２は、直列に接続されたハイサイドのスイッチング素子Ｓ３（以下「スイッチング素子Ｓ３」とする）及びローサイドのスイッチング素子Ｓ４（以下「スイッチング素子Ｓ４」とする）を有する。スイッチング素子Ｓ３及びスイッチング素子Ｓ４は、ｎ型ＭＯＳ－ＦＥＴが用いられる。スイッチング素子Ｓ３は、ドレーン端子が端部２１２Ａに接続され、ソース端子がスイッチング素子Ｓ４のドレーン端子に接続される。スイッチング素子Ｓ４のソース端子は端部２１２Ｂに接続される。スイッチング素子Ｓ３及びスイッチング素子Ｓ４の夫々のゲート端子は、制御部５０に接続される。また、スイッチング素子Ｓ３及びスイッチング素子Ｓ４の夫々のソース端子とドレーン端子との間には、アノード端子がソース端子に接続され、カソード端子がドレーン端子に接続されたダイオードＳ３Ｄ,Ｓ４Ｄが設けられる。 The fourth leg 212 has a high-side switching element S3 (hereinafter referred to as "switching element S3") and a low-side switching element S4 (hereinafter referred to as "switching element S4") connected in series. The switching elements S3 and S4 are n-type MOS-FETs. The drain terminal of the switching element S3 is connected to the end 212A, and the source terminal is connected to the drain terminal of the switching element S4. The source terminal of the switching element S4 is connected to the end 212B. The gate terminals of the switching elements S3 and S4 are connected to the control unit 50. In addition, between the source terminals and drain terminals of the switching elements S3 and S4, diodes S3D and S4D are provided, with the anode terminals connected to the source terminals and the cathode terminals connected to the drain terminals.
　一次巻線２４Ａは、第３レグ２１１における２つのスイッチング素子（スイッチング素子Ｓ１及びスイッチング素子Ｓ２）の間の第３ノード２１１Ｎと、第４レグ２１２における２つのスイッチング素子（スイッチング素子Ｓ３及びスイッチング素子Ｓ４）の間の第４ノード２１２Ｎとに亘って設けられる。本実施形態では、一次巻線２４Ａの巻き始め端が第３ノード２１１Ｎに接続され、一次巻線２４Ａの巻き終わり端が第４ノード２１２Ｎに接続される。 The primary winding 24A is provided across a third node 211N between two switching elements (switching element S1 and switching element S2) in the third leg 211 and a fourth node 212N between two switching elements (switching element S3 and switching element S4) in the fourth leg 212. In this embodiment, the winding start end of the primary winding 24A is connected to the third node 211N, and the winding end end of the primary winding 24A is connected to the fourth node 212N.
　二次巻線２４Ｂには、一次巻線２４Ａと二次巻線２４Ｂとの巻数比に応じた電流（交番電流）が流れ、また、一次巻線２４Ａと二次巻線２４Ｂとの巻数比に応じた電圧（交番電圧）が生じる。第１変換部２２は、二次巻線２４Ｂに生じる交流電力を、第１電圧値の直流電圧で構成される直流電力に変換する。第１変換部２２は、第５レグ２２１及び第６レグ２２２を有し、第５レグ２２１と第６レグ２２２とは、コンバータ２０の端子２０Ａ,２０Ｂに対して互いに並列に設けられる。したがって、第５レグ２２１の一方の端部２２１Ａと、第６レグ２２２の一方の端部２２２Ａとが、端子２０Ａに接続され、第５レグ２２１の他方の端部２２１Ｂと、第６レグ２２２の他方の端部２２２Ｂとが、端子２０Ｂに接続される。 A current (alternating current) according to the turn ratio between the primary winding 24A and the secondary winding 24B flows through the secondary winding 24B, and a voltage (alternating voltage) according to the turn ratio between the primary winding 24A and the secondary winding 24B is generated. The first conversion unit 22 converts the AC power generated in the secondary winding 24B into DC power composed of a DC voltage of a first voltage value. The first conversion unit 22 has a fifth leg 221 and a sixth leg 222, and the fifth leg 221 and the sixth leg 222 are provided in parallel with each other with respect to the terminals 20A and 20B of the converter 20. Therefore, one end 221A of the fifth leg 221 and one end 222A of the sixth leg 222 are connected to the terminal 20A, and the other end 221B of the fifth leg 221 and the other end 222B of the sixth leg 222 are connected to the terminal 20B.
　第５レグ２２１は、直列に接続されたハイサイドのスイッチング素子Ｓ５（以下「スイッチング素子Ｓ５」とする）及びローサイドのスイッチング素子Ｓ６（以下「スイッチング素子Ｓ６」とする）を有する。スイッチング素子Ｓ５及びスイッチング素子Ｓ６は、ｎ型ＭＯＳ－ＦＥＴが用いられる。スイッチング素子Ｓ５は、ドレーン端子が端部２２１Ａに接続され、ソース端子がスイッチング素子Ｓ６のドレーン端子に接続される。スイッチング素子Ｓ６のソース端子は端部２２１Ｂに接続される。スイッチング素子Ｓ５及びスイッチング素子Ｓ６の夫々のゲート端子は、制御部５０に接続される。また、スイッチング素子Ｓ５及びスイッチング素子Ｓ６の夫々のソース端子とドレーン端子との間には、アノード端子がソース端子に接続され、カソード端子がドレーン端子に接続されたダイオードＳ５Ｄ,Ｓ６Ｄが設けられる。 The fifth leg 221 has a high-side switching element S5 (hereinafter referred to as "switching element S5") and a low-side switching element S6 (hereinafter referred to as "switching element S6") connected in series. The switching elements S5 and S6 are n-type MOS-FETs. The drain terminal of the switching element S5 is connected to the end 221A, and the source terminal is connected to the drain terminal of the switching element S6. The source terminal of the switching element S6 is connected to the end 221B. The gate terminals of the switching elements S5 and S6 are connected to the control unit 50. In addition, between the source terminals and drain terminals of the switching elements S5 and S6, diodes S5D and S6D are provided, with the anode terminals connected to the source terminals and the cathode terminals connected to the drain terminals.
　第６レグ２２２は、直列に接続されたハイサイドのスイッチング素子Ｓ７（以下「スイッチング素子Ｓ７」とする）及びローサイドのスイッチング素子Ｓ８（以下「スイッチング素子Ｓ８」とする）を有する。スイッチング素子Ｓ７及びスイッチング素子Ｓ８は、ｎ型ＭＯＳ－ＦＥＴが用いられる。スイッチング素子Ｓ７は、ドレーン端子が端部２２２Ａに接続され、ソース端子がスイッチング素子Ｓ８のドレーン端子に接続される。スイッチング素子Ｓ８のソース端子は端部２２２Ｂに接続される。スイッチング素子Ｓ７及びスイッチング素子Ｓ８の夫々のゲート端子は、制御部５０に接続される。また、スイッチング素子Ｓ７及びスイッチング素子Ｓ８の夫々のソース端子とドレーン端子との間には、アノード端子がソース端子に接続され、カソード端子がドレーン端子に接続されたダイオードＳ７Ｄ,Ｓ８Ｄが設けられる。 The sixth leg 222 has a high-side switching element S7 (hereinafter referred to as "switching element S7") and a low-side switching element S8 (hereinafter referred to as "switching element S8") connected in series. The switching elements S7 and S8 are n-type MOS-FETs. The drain terminal of the switching element S7 is connected to the end 222A, and the source terminal is connected to the drain terminal of the switching element S8. The source terminal of the switching element S8 is connected to the end 222B. The gate terminals of the switching elements S7 and S8 are connected to the control unit 50. In addition, between the source terminal and drain terminal of the switching elements S7 and S8, diodes S7D and S8D are provided, with the anode terminal connected to the source terminal and the cathode terminal connected to the drain terminal.
　上述した二次巻線２４Ｂは、第５レグ２２１における２つのスイッチング素子（スイッチング素子Ｓ５及びスイッチング素子Ｓ６）の間の第５ノード２２１Ｎと、第６レグ２２２における２つのスイッチング素子（スイッチング素子Ｓ７及びスイッチング素子Ｓ８）の間の第６ノード２２２Ｎとに亘って設けられる。本実施形態では、二次巻線２４Ｂの巻き始め端が、リアクトルＬを介して第５ノード２２１Ｎに接続され、二次巻線２４Ｂの巻き終わり端が第６ノード２２２Ｎに接続される。 The secondary winding 24B described above is provided across a fifth node 221N between two switching elements (switching element S5 and switching element S6) in the fifth leg 221 and a sixth node 222N between two switching elements (switching element S7 and switching element S8) in the sixth leg 222. In this embodiment, the winding start end of the secondary winding 24B is connected to the fifth node 221N via the reactor L, and the winding end end of the secondary winding 24B is connected to the sixth node 222N.
　コンバータ２０の端子２０Ａと端子２０Ｂとに亘って第１コンデンサ２５が設けられる。第１コンデンサ２５は、第１変換部２２により変換された交流電力を構成する直流電圧を平滑する。 A first capacitor 25 is provided across terminals 20A and 20B of the converter 20. The first capacitor 25 smoothes the DC voltage that constitutes the AC power converted by the first conversion unit 22.
　三次巻線２４Ｃには、一次巻線２４Ａと三次巻線２４Ｃとの巻数比に応じた電流（交番電流）が流れ、また、一次巻線２４Ａと三次巻線２４Ｃとの巻数比に応じた電圧（交番電圧）が生じる。第２変換部２３は、三次巻線２４Ｃに生じる交流電力を、第１電圧値よりも低い第２電圧値（例えば１２Ｖ）の直流電圧で構成される直流電力に変換する。 A current (alternating current) according to the turn ratio between the primary winding 24A and the tertiary winding 24C flows through the tertiary winding 24C, and a voltage (alternating voltage) according to the turn ratio between the primary winding 24A and the tertiary winding 24C is generated. The second conversion unit 23 converts the AC power generated in the tertiary winding 24C into DC power composed of a DC voltage of a second voltage value (e.g., 12 V) lower than the first voltage value.
　本実施形態では、三次巻線２４Ｃは、第１三次巻線２４ＣＡと第２三次巻線２４ＣＢとを有する。第１三次巻線２４ＣＡと第２三次巻線２４ＣＢとは、第１三次巻線２４ＣＡの巻き終わり端と第２三次巻線２４ＣＢの巻き始め端とが接続して設けられる。第１三次巻線２４ＣＡの巻き始め端には、ドレーン端子が接続されたスイッチング素子（「第１スイッチング素子」に相当）Ｓ９が設けられ、第２三次巻線２４ＣＢの巻き終わり端には、ドレーン端子が接続されたスイッチング素子（「第２スイッチング素子」に相当）Ｓ１０が設けられる。スイッチング素子Ｓ９のソース端子とスイッチング素子Ｓ１０のソース端子とは端子２０Ｄに接続される。スイッチング素子Ｓ９及びスイッチング素子Ｓ１０の夫々のゲート端子は、制御部５０に接続される。なお、スイッチング素子Ｓ９及びスイッチング素子Ｓ１０の夫々のソース端子とドレーン端子との間には、アノード端子がソース端子に接続され、カソード端子がドレーン端子に接続されたダイオード（「第１ダイオード」, 「第２ダイオード」に相当）Ｓ９Ｄ,Ｓ１０Ｄが設けられる。 In this embodiment, the tertiary winding 24C has a first tertiary winding 24CA and a second tertiary winding 24CB. The first tertiary winding 24CA and the second tertiary winding 24CB are provided by connecting the end of the first tertiary winding 24CA to the beginning of the second tertiary winding 24CB. A switching element (corresponding to the "first switching element") S9 with a drain terminal connected is provided at the beginning of the first tertiary winding 24CA, and a switching element (corresponding to the "second switching element") S10 with a drain terminal connected is provided at the end of the second tertiary winding 24CB. The source terminal of the switching element S9 and the source terminal of the switching element S10 are connected to the terminal 20D. The gate terminals of the switching elements S9 and S10 are connected to the control unit 50. In addition, between the source terminal and drain terminal of each of the switching elements S9 and S10, diodes S9D and S10D (corresponding to the "first diode" and "second diode") are provided, with the anode terminal connected to the source terminal and the cathode terminal connected to the drain terminal.
　第１三次巻線２４ＣＡの巻き終わり端及び第２三次巻線２４ＣＢの巻き始め端は、第３リアクトルコイル２３Ｌの一方の端子に接続される。第３リアクトルコイル２３Ｌの他方の端子は、端子２０Ｃに接続される。また、第２変換部２３は、ダイオード２３Ｄ１とダイオード２３Ｄ２とが設けられている。ダイオード２３Ｄ１のアノード端子は、第１三次巻線２４ＣＡの巻き始め端に接続され、ダイオード２３Ｄ２のアノード端子は、第２三次巻線２４ＣＢの巻き終わり端に接続される。また、ダイオード２３Ｄ１のカソード端子とダイオード２３Ｄ２のカソード端子とは互いに接続され、抵抗器Ｒを介して端子２０Ｃに接続される。更に、ダイオード２３Ｄ１のカソード端子とダイオード２３Ｄ２のカソード端子とはコンデンサ２７を介して端子２０Ｄに接続される。したがって、抵抗器Ｒとコンデンサ２７とでスナバ回路が形成されている。更に、端子２０Ｃと端子２０Ｄとに亘って第２コンデンサ２６が設けられる。第２変換部２３は、三次巻線２４Ｃに生じる交流電力を、スイッチング素子Ｓ９とスイッチング素子Ｓ１０とにより、同期整流により第２電圧値の直流電圧で構成される直流電力に変換する。 The winding end of the first tertiary winding 24CA and the winding start of the second tertiary winding 24CB are connected to one terminal of the third reactor coil 23L. The other terminal of the third reactor coil 23L is connected to the terminal 20C. The second conversion unit 23 is also provided with a diode 23D1 and a diode 23D2. The anode terminal of the diode 23D1 is connected to the winding start of the first tertiary winding 24CA, and the anode terminal of the diode 23D2 is connected to the winding end of the second tertiary winding 24CB. The cathode terminal of the diode 23D1 and the cathode terminal of the diode 23D2 are connected to each other and to the terminal 20C via the resistor R. Furthermore, the cathode terminal of the diode 23D1 and the cathode terminal of the diode 23D2 are connected to the terminal 20D via the capacitor 27. Therefore, the resistor R and the capacitor 27 form a snubber circuit. Furthermore, a second capacitor 26 is provided across terminals 20C and 20D. The second conversion unit 23 converts the AC power generated in the tertiary winding 24C into DC power composed of a DC voltage of a second voltage value by synchronous rectification using switching elements S9 and S10.
　制御部５０は、インバータ１０に設けられる複数のスイッチング素子の夫々を駆動する。具体的には、制御部５０は、スイッチング素子１１Ｈ及びスイッチング素子１２Ｌの開閉状態と、スイッチング素子１１Ｌ及びスイッチング素子１２Ｈの開閉状態とを交互に切り替える。すなわち、制御部５０は、第１レグ１１はスイッチング素子１１Ｈとスイッチング素子１１Ｌとを交互に駆動して、第２レグ１２は系統周波数でスイッチング素子１２Ｈとスイッチング素子１２Ｌとを交互に駆動する。これにより、上述したように、インバータ１０が第１レグ１１及び第２レグ１２が有するスイッチング素子の駆動に基づいて供給部２から供給される交流電力を直流電力に変換することが可能となる。 The control unit 50 drives each of the multiple switching elements provided in the inverter 10. Specifically, the control unit 50 alternates between the open/closed state of the switching elements 11H and 12L and the open/closed state of the switching elements 11L and 12H. That is, the control unit 50 alternately drives the switching elements 11H and 11L of the first leg 11, and alternately drives the switching elements 12H and 12L at the system frequency of the second leg 12. This allows the inverter 10 to convert the AC power supplied from the supply unit 2 into DC power based on the driving of the switching elements of the first leg 11 and the second leg 12, as described above.
　また、制御部５０は、コンバータ２０に設けられる複数のスイッチング素子の夫々を駆動する。図２には、バッテリ３を充電する際のタイミングチャートが示される。制御部５０は、図２に示されるタイミングチャートに沿ってスイッチング素子Ｓ１－Ｓ１０を駆動する。本実施形態では、制御部５０は、スイッチング素子Ｓ１－Ｓ１０を、第１状態－第８状態の８個の状態に、順次、切り替えながら駆動する。図２の例では、ｔ１－ｔ９の期間が制御部５０による制御上の１周期に相当する。 The control unit 50 also drives each of the multiple switching elements provided in the converter 20. FIG. 2 shows a timing chart for charging the battery 3. The control unit 50 drives the switching elements S1-S10 in accordance with the timing chart shown in FIG. 2. In this embodiment, the control unit 50 drives the switching elements S1-S10 while switching them sequentially between eight states, from state 1 to state 8. In the example of FIG. 2, the period t1-t9 corresponds to one cycle of control by the control unit 50.
　第１状態は図２のｔ１－ｔ２の間の状態であり、この第１状態では、制御部５０は、スイッチング素子Ｓ１,Ｓ３,Ｓ６,Ｓ７,Ｓ９,Ｓ１０を閉状態にし、スイッチング素子Ｓ２,Ｓ４,Ｓ５,Ｓ８を開状態にする。 The first state is the state between t1 and t2 in FIG. 2, and in this first state, the control unit 50 closes the switching elements S1, S3, S6, S7, S9, and S10, and opens the switching elements S2, S4, S5, and S8.
　第２状態は図２のｔ２－ｔ３の間の状態であり、この第２状態では、制御部５０は、スイッチング素子Ｓ１,Ｓ３,Ｓ５,Ｓ７,Ｓ９,Ｓ１０を閉状態にし、スイッチング素子Ｓ２,Ｓ４,Ｓ６,Ｓ８を開状態にする。 The second state is the state between t2 and t3 in FIG. 2, and in this second state, the control unit 50 closes the switching elements S1, S3, S5, S7, S9, and S10, and opens the switching elements S2, S4, S6, and S8.
　第３状態は図２のｔ３－ｔ４の間の状態であり、この第３状態では、制御部５０は、スイッチング素子Ｓ１,Ｓ４,Ｓ５,Ｓ７,Ｓ１０を閉状態にし、スイッチング素子Ｓ２,Ｓ３,Ｓ６,Ｓ８,Ｓ９を開状態にする。 The third state is the state between t3 and t4 in FIG. 2, and in this third state, the control unit 50 closes the switching elements S1, S4, S5, S7, and S10, and opens the switching elements S2, S3, S6, S8, and S9.
　第４状態は図２のｔ４－ｔ５の間の状態であり、この第４状態では、制御部５０は、スイッチング素子Ｓ１,Ｓ４,Ｓ５,Ｓ８,Ｓ１０を閉状態にし、スイッチング素子Ｓ２,Ｓ３,Ｓ６,Ｓ７,Ｓ９を開状態にする。 The fourth state is the state between t4 and t5 in FIG. 2, and in this fourth state, the control unit 50 closes the switching elements S1, S4, S5, S8, and S10, and opens the switching elements S2, S3, S6, S7, and S9.
　第５状態は図２のｔ５－ｔ６の間の状態であり、この第５状態では、制御部５０は、スイッチング素子Ｓ２,Ｓ４,Ｓ５,Ｓ８,Ｓ９,Ｓ１０を閉状態にし、スイッチング素子Ｓ１,Ｓ３,Ｓ６,Ｓ７を開状態にする。 The fifth state is the state between t5 and t6 in FIG. 2, and in this fifth state, the control unit 50 closes the switching elements S2, S4, S5, S8, S9, and S10, and opens the switching elements S1, S3, S6, and S7.
　第６状態は図２のｔ６－ｔ７の間の状態であり、この第６状態では、制御部５０は、スイッチング素子Ｓ２,Ｓ４,Ｓ６,Ｓ８,Ｓ９,Ｓ１０を閉状態にし、スイッチング素子Ｓ１,Ｓ３,Ｓ５,Ｓ７を開状態にする。 The sixth state is the state between t6 and t7 in FIG. 2, and in this sixth state, the control unit 50 closes the switching elements S2, S4, S6, S8, S9, and S10, and opens the switching elements S1, S3, S5, and S7.
　第７状態は図２のｔ７－ｔ８の間の状態であり、この第７状態では、制御部５０は、スイッチング素子Ｓ２,Ｓ３,Ｓ６,Ｓ８,Ｓ９を閉状態にし、スイッチング素子Ｓ１,Ｓ４,Ｓ５,Ｓ７,Ｓ１０を開状態にする。 The seventh state is the state between t7 and t8 in FIG. 2, and in this seventh state, the control unit 50 closes the switching elements S2, S3, S6, S8, and S9, and opens the switching elements S1, S4, S5, S7, and S10.
　第８状態は図２のｔ８－ｔ９の間の状態であり、この第８状態では、制御部５０は、スイッチング素子Ｓ２,Ｓ３,Ｓ６,Ｓ７,Ｓ９を閉状態にし、スイッチング素子Ｓ１,Ｓ４,Ｓ５,Ｓ８,Ｓ１０を開状態にする。 The eighth state is the state between t8 and t9 in FIG. 2, and in this eighth state, the control unit 50 closes the switching elements S2, S3, S6, S7, and S9, and opens the switching elements S1, S4, S5, S8, and S10.
　ここで、理解を容易にするために、１周期におけるスイッチＳ１－Ｓ８の夫々が閉状態になる期間と、スイッチＳ１－Ｓ８の夫々が開状態になる期間とは互いに等しいものとする。 To make it easier to understand, it is assumed that the period during which each of the switches S1-S8 is in a closed state during one cycle is equal to the period during which each of the switches S1-S8 is in an open state.
　図２に示されるように、第３レグ２１１のスイッチング素子Ｓ１と第４レグ２１２のスイッチング素子Ｓ４とは、予め設定された第１シフト量θ１だけずらして閉状態にされる。すなわち、図２の例では、ｔ１において第３レグ２１１のスイッチング素子Ｓ１が閉状態されてから、第１シフト量θ１だけ経過した後、ｔ３において第４レグ２１２のスイッチング素子Ｓ４が閉状態にされる。したがって、第３レグ２１１のスイッチング素子Ｓ１と第４レグ２１２のスイッチング素子Ｓ４とは、第１シフト量θ１だけずれて開状態になる。すなわち、ｔ５において第３レグ２１１のスイッチング素子Ｓ１が開状態されてから、第１シフト量θ１だけ経過した後、ｔ７において第４レグ２１２のスイッチング素子Ｓ４が開状態にされる。 As shown in FIG. 2, the switching element S1 of the third leg 211 and the switching element S4 of the fourth leg 212 are shifted to the closed state by a preset first shift amount θ1. That is, in the example of FIG. 2, the switching element S1 of the third leg 211 is closed at t1, and then the switching element S4 of the fourth leg 212 is closed at t3 after the first shift amount θ1 has elapsed. Therefore, the switching element S1 of the third leg 211 and the switching element S4 of the fourth leg 212 are shifted to the open state by a shift amount θ1. That is, the switching element S1 of the third leg 211 is opened at t5, and then the switching element S4 of the fourth leg 212 is opened at t7 after the first shift amount θ1 has elapsed.
　また、第３レグ２１１のスイッチング素子Ｓ２と第４レグ２１２のスイッチング素子Ｓ３とは、第１シフト量θ１だけずらして閉状態にされる。すなわち、図２の例では、ｔ５において第３レグ２１１のスイッチング素子Ｓ２が閉状態されてから、第１シフト量θ１だけ経過した後、ｔ７において第４レグ２１２のスイッチング素子Ｓ３が閉状態にされる。したがって、第３レグ２１１のスイッチング素子Ｓ２と第４レグ２１２のスイッチング素子Ｓ３とは、第１シフト量θ１だけずれて開状態になる。すなわち、ｔ９において第３レグ２１１のスイッチング素子Ｓ２が開状態されてから、第１シフト量θ１だけ経過した後、ｔ１１において第４レグ２１２のスイッチング素子Ｓ３が開状態にされる。 Furthermore, the switching element S2 of the third leg 211 and the switching element S3 of the fourth leg 212 are shifted to the closed state by the first shift amount θ1. That is, in the example of FIG. 2, the switching element S2 of the third leg 211 is closed at t5, and then the switching element S3 of the fourth leg 212 is closed at t7 after the first shift amount θ1 has elapsed. Therefore, the switching element S2 of the third leg 211 and the switching element S3 of the fourth leg 212 are shifted to the open state by the first shift amount θ1. That is, the switching element S2 of the third leg 211 is opened at t9, and then the switching element S3 of the fourth leg 212 is opened at t11 after the first shift amount θ1 has elapsed.
　また、第５レグ２２１のスイッチング素子Ｓ５と第６レグ２２２のスイッチング素子Ｓ８とは、第１シフト量θ１だけずらして閉状態にされる。すなわち、図２の例では、ｔ２において第５レグ２２１のスイッチング素子Ｓ５が閉状態されてから、第１シフト量θ１だけ経過した後、ｔ４において第６レグ２２２のスイッチング素子Ｓ８が閉状態にされる。したがって、第５レグ２２１のスイッチング素子Ｓ５と第６レグ２２２のスイッチング素子Ｓ８とは、第１シフト量θ１だけずれて開状態になる。すなわち、ｔ６において第５レグ２２１のスイッチング素子Ｓ５が開状態されてから、第１シフト量θ１だけ経過した後、ｔ８において第６レグ２２２のスイッチング素子Ｓ８が開状態にされる。 Furthermore, the switching element S5 of the fifth leg 221 and the switching element S8 of the sixth leg 222 are shifted to the closed state by the first shift amount θ1. That is, in the example of FIG. 2, the switching element S5 of the fifth leg 221 is closed at t2, and then the switching element S8 of the sixth leg 222 is closed at t4 after the first shift amount θ1 has elapsed. Therefore, the switching element S5 of the fifth leg 221 and the switching element S8 of the sixth leg 222 are shifted to the open state by the first shift amount θ1. That is, the switching element S5 of the fifth leg 221 is opened at t6, and then the switching element S8 of the sixth leg 222 is opened at t8 after the first shift amount θ1 has elapsed.
　更に、第５レグ２２１のスイッチング素子Ｓ６と第６レグ２２２のスイッチング素子Ｓ７とは、第１シフト量θ１だけずらして閉状態にされる。すなわち、図２の例では、ｔ６において第５レグ２２１のスイッチング素子Ｓ６が閉状態されてから、第１シフト量θ１だけ経過した後、ｔ８において第６レグ２２２のスイッチング素子Ｓ７が閉状態にされる。したがって、第５レグ２２１のスイッチング素子Ｓ６と第６レグ２２２のスイッチング素子Ｓ７とは、第１シフト量θ１だけずれて開状態になる。すなわち、図２の例では、ｔ１０において第５レグ２２１のスイッチング素子Ｓ６が開状態されてから、第１シフト量θ１だけ経過した後、ｔ１２において第６レグ２２２のスイッチング素子Ｓ７が開状態にされる。 Furthermore, the switching element S6 of the fifth leg 221 and the switching element S7 of the sixth leg 222 are shifted to the closed state by the first shift amount θ1. That is, in the example of FIG. 2, the switching element S6 of the fifth leg 221 is closed at t6, and then the switching element S7 of the sixth leg 222 is closed at t8 after the first shift amount θ1 has elapsed. Therefore, the switching element S6 of the fifth leg 221 and the switching element S7 of the sixth leg 222 are shifted to the open state by the first shift amount θ1. That is, in the example of FIG. 2, the switching element S6 of the fifth leg 221 is opened at t10, and then the switching element S7 of the sixth leg 222 is opened at t12 after the first shift amount θ1 has elapsed.
　また、バッテリ３の充電時は、第５レグ２２１のスイッチング素子Ｓ５は、第３レグ２１１のスイッチング素子Ｓ１が閉状態にされてから、第２シフト量θ２だけ後において閉状態にされる。第２シフト量θ２とは第１シフト量θ１よりも小さいものである。 When the battery 3 is being charged, the switching element S5 of the fifth leg 221 is closed a second shift amount θ2 after the switching element S1 of the third leg 211 is closed. The second shift amount θ2 is smaller than the first shift amount θ1.
　例えば、第２シフト量θ２は、第１変換部２２から出力する直流電力の電力指令値と、第１変換部２２から出力された直流電力の電力算定値とに基づいて設定することが可能である。第１変換部２２から出力する直流電力の電力指令値とは、上位システムから電源装置１（詳しくは、制御部５０）に、電源装置１から出力する直流電力として要求される指令値である。制御部５０は、電力指令値により、第１変換部２２から出力する直流電力を構成する直流電圧の第１電圧値を設定し、第１変換部２２から出力する直流電流の電流値を設定する。この電流値の電流を実現するように、予め記憶されている演算式に基づいて、第２シフト量θ２を設定する。以下の（１）式としてこの演算式が示される。 For example, the second shift amount θ2 can be set based on a power command value of the DC power output from the first conversion unit 22 and a power calculation value of the DC power output from the first conversion unit 22. The power command value of the DC power output from the first conversion unit 22 is a command value requested from a higher-level system to the power supply device 1 (more specifically, the control unit 50) as the DC power to be output from the power supply device 1. The control unit 50 sets a first voltage value of the DC voltage constituting the DC power output from the first conversion unit 22 based on the power command value, and sets a current value of the DC current output from the first conversion unit 22. The second shift amount θ2 is set based on a pre-stored arithmetic expression so as to realize a current of this current value. This arithmetic expression is shown as the following equation (1).
Figure JPOXMLDOC01-appb-M000002
 　ただし、Ｖ１は一次巻線２４Ａの両端の電位、Ｖ２´は二次巻線２４Ｂ及びリアクトルＬの両端（すなわち、第５ノード２２１Ｎと第６ノード２２２Ｎとの間）の電位、Ｐは出力電力、θ２は第２シフト量、ωはスイッチング素子のスイッチング周波数、ＬはリアクトルＬのインダクタンス値である。
Figure JPOXMLDOC01-appb-M000002
 where V1 is the potential across both ends of the primary winding 24A, V2' is the potential across both ends of the secondary winding 24B and the reactor L (i.e., between the fifth node 221N and the sixth node 222N), P is the output power, θ2 is the second shift amount, ω is the switching frequency of the switching element, and L is the inductance value of the reactor L.
　一方、第１変換部２２から出力された直流電力の電力算定値とは、第１変換部２２から出力される直流電圧（出力電圧）の電圧値（好ましくは第１電圧値）と、第１変換部２２から出力される直流電流（消費電流）の電流値との積により算定した算定値である。 On the other hand, the power calculation value of the DC power output from the first conversion unit 22 is a calculation value calculated by multiplying the voltage value (preferably the first voltage value) of the DC voltage (output voltage) output from the first conversion unit 22 by the current value of the DC current (consumption current) output from the first conversion unit 22.
　第１変換部２２から出力される直流電圧（出力電圧）の電圧値（好ましくは第１電圧値）は、図示しない電圧センサ（例えば電圧計）により計測し、第１変換部２２から出力される直流電流（消費電流）の電流値は、図示しない電流センサ（例えば電流計）により計測するとよい。これら２つの検出結果に基づいて制御部５０が電力算定値を算定することが可能である。制御部５０は、電力算定値が電力指令値と等しくなるように、フィードバック制御によりコンバータ２０を制御する。 The voltage value (preferably the first voltage value) of the DC voltage (output voltage) output from the first conversion unit 22 is measured by a voltage sensor (e.g., a voltmeter) not shown, and the current value of the DC current (consumption current) output from the first conversion unit 22 is measured by a current sensor (e.g., an ammeter) not shown. The control unit 50 can calculate the power calculation value based on these two detection results. The control unit 50 controls the converter 20 by feedback control so that the power calculation value is equal to the power command value.
　図２の例では、第２シフト量θ２は第１シフト量θ１の２分の１としている。したがって、図２に示されるように、第５レグ２２１のスイッチング素子Ｓ５は、第３レグ２１１のスイッチング素子Ｓ１が閉状態にされるｔ１よりも第２シフト量θ２だけ後のｔ２において閉状態にされる。また、バッテリ３の充電時は、第５レグ２２１のスイッチング素子Ｓ５は、第３レグ２１１のスイッチング素子Ｓ１が開状態にされる第２シフト量θ２だけ後において開状態にされる。すなわち、バッテリ３の充電時は、図２に示されるように、第５レグ２２１のスイッチング素子Ｓ５は、第３レグ２１１のスイッチング素子Ｓ１が開状態にされるｔ５よりも第２シフト量θ２だけ後のｔ６において開状態にされる。 In the example of FIG. 2, the second shift amount θ2 is set to half the first shift amount θ1. Therefore, as shown in FIG. 2, the switching element S5 of the fifth leg 221 is closed at t2, which is the second shift amount θ2 after t1 at which the switching element S1 of the third leg 211 is closed. Also, when the battery 3 is being charged, the switching element S5 of the fifth leg 221 is opened at the second shift amount θ2 after t5 at which the switching element S1 of the third leg 211 is opened. That is, when the battery 3 is being charged, as shown in FIG. 2, the switching element S5 of the fifth leg 221 is opened at t6, which is the second shift amount θ2 after t5 at which the switching element S1 of the third leg 211 is opened.
　また、バッテリ３の充電時は、第６レグ２２２のスイッチング素子Ｓ７は、第４レグ２１２のスイッチング素子Ｓ３が閉状態にされる第２シフト量θ２だけ後において閉状態にされる。すなわち、図２に示されるように、第６レグ２２２のスイッチング素子Ｓ７は、第４レグ２１２のスイッチング素子Ｓ３が閉状態にされるｔ７よりも第２シフト量θ２だけ後のｔ８において閉状態にされる。また、バッテリ３の充電時は、第６レグ２２２のスイッチング素子Ｓ７は、第４レグ２１２のスイッチング素子Ｓ３が開状態にされる第２シフト量θ２だけ後において開状態にされる。すなわち、バッテリ３の充電時は、図２に示されるように、第６レグ２２２のスイッチング素子Ｓ７は、第４レグ２１２のスイッチング素子Ｓ３が開状態にされるｔ３よりも第２シフト量θ２だけ後のｔ４において開状態にされる。 When the battery 3 is being charged, the switching element S7 of the sixth leg 222 is closed the second shift amount θ2 after the switching element S3 of the fourth leg 212 is closed. That is, as shown in FIG. 2, the switching element S7 of the sixth leg 222 is closed at t8, which is the second shift amount θ2 after t7, when the switching element S3 of the fourth leg 212 is closed. When the battery 3 is being charged, the switching element S7 of the sixth leg 222 is opened the second shift amount θ2 after t3, when the switching element S3 of the fourth leg 212 is opened. That is, when the battery 3 is being charged, as shown in FIG. 2, the switching element S7 of the sixth leg 222 is opened at t4, which is the second shift amount θ2 after t3, when the switching element S3 of the fourth leg 212 is opened.
　また、上述したように、第２変換部２３は同期整流により駆動される。具体的には、スイッチング素子Ｓ９及びスイッチング素子Ｓ１０が同期整流により駆動される。本実施形態では、図２に示されるように、スイッチング素子Ｓ９はｔ３からｔ５の間に亘って開状態とされ、スイッチング素子Ｓ１０はｔ７からｔ９の間に亘って開状態とされる。これにより、図２に示されるように、スイッチング素子Ｓ９には、Ｉ９で示されるような波形の電流が流れ、スイッチング素子Ｓ１０には、Ｉ１０で示されるような波形の電流が流れる。 Furthermore, as described above, the second conversion unit 23 is driven by synchronous rectification. Specifically, the switching element S9 and the switching element S10 are driven by synchronous rectification. In this embodiment, as shown in FIG. 2, the switching element S9 is in an open state from t3 to t5, and the switching element S10 is in an open state from t7 to t9. As a result, as shown in FIG. 2, a current having a waveform as indicated by I9 flows through the switching element S9, and a current having a waveform as indicated by I10 flows through the switching element S10.
　例えば、第２変換部２３が第１三次巻線２４ＣＡに蓄えられた電気エネルギーを整流する場合には、第３リアクトルコイル２３Ｌ、第２コンデンサ２６、ダイオードＳ９Ｄを介して電流が流れる。制御部５０は、ダイオードＳ９Ｄにおいて順方向に電流が流れたタイミングで、開状態にあるスイッチング素子Ｓ９を閉状態にする。同様に、第２変換部２３が第２三次巻線２４ＣＢに蓄えられた電気エネルギーを整流する場合には、第３リアクトルコイル２３Ｌ、第２コンデンサ２６、ダイオードＳ１０Ｄを介して電流が流れる。制御部５０は、ダイオードＳ１０Ｄにおいて順方向に電流が流れたタイミングで、開状態にあるスイッチング素子Ｓ１０を閉状態にする。ダイオードＳ９ＤやダイオードＳ１０Ｄに順方向に電流が流れている場合、ダイオードＳ９ＤやダイオードＳ１０Ｄにおける消費電力は、当該電流と順方向電圧との積からなる値となる。一方、スイッチング素子Ｓ９やスイッチング素子Ｓ１０にドレーン電流が流れている場合、スイッチング素子Ｓ９やスイッチング素子Ｓ１０における消費電力は、当該ドレーン電流の平方とオン抵抗との積からなる値となる。スイッチング素子Ｓ９やスイッチング素子Ｓ１０における消費電力は、ダイオードＳ９ＤやダイオードＳ１０Ｄにおける消費電力よりも十分に小さいため、損失が小さくなり、第２変換部２３における効率（変換効率）の低下を抑制できる。したがって、上記のように第２変換部２３を駆動することで、効率よく電圧を出力することが可能となる。 For example, when the second conversion unit 23 rectifies the electrical energy stored in the first tertiary winding 24CA, a current flows through the third reactor coil 23L, the second capacitor 26, and the diode S9D. The control unit 50 closes the switching element S9, which is in the open state, when a forward current flows through the diode S9D. Similarly, when the second conversion unit 23 rectifies the electrical energy stored in the second tertiary winding 24CB, a current flows through the third reactor coil 23L, the second capacitor 26, and the diode S10D. The control unit 50 closes the switching element S10, which is in the open state, when a forward current flows through the diode S10D. When a forward current flows through the diode S9D or the diode S10D, the power consumption of the diode S9D or the diode S10D is a value obtained by multiplying the current by the forward voltage. On the other hand, when a drain current flows through switching element S9 or switching element S10, the power consumption in switching element S9 or switching element S10 is the product of the square of the drain current and the on-resistance. Since the power consumption in switching element S9 or switching element S10 is sufficiently smaller than the power consumption in diode S9D or diode S10D, the loss is reduced and the decrease in efficiency (conversion efficiency) in second conversion unit 23 can be suppressed. Therefore, by driving second conversion unit 23 as described above, it is possible to output a voltage efficiently.
　また、本実施形態の第２変換部２３は、端子２０Ｃと端子２０Ｄとの間に負荷が接続されていない場合には、第３リアクトルコイル２３Ｌに流れる電流（平均値）を零にする必要がある。このとき、第３リアクトルコイル２３Ｌには、図３の（Ａ）に示されるように、正電流（Ｉ＞０）と負電流（Ｉ＜０）とが流れる。正電流は、図３の（Ｂ）に示されるように、第３リアクトルコイル２３Ｌ、第２コンデンサ２６、スイッチング素子Ｓ９を介して流れる電流や、第３リアクトルコイル２３Ｌ、第２コンデンサ２６、スイッチング素子Ｓ１０を介して流れる電流である。負電流は、図３の（Ｃ）に示されるように、スイッチング素子Ｓ９、第２コンデンサ２６、第３リアクトルコイル２３Ｌを介して流れる電流や、スイッチング素子Ｓ１０、第２コンデンサ２６、第３リアクトルコイル２３Ｌを介して流れる電流である。特に、このような負電流を第２変換部２３に流れるようにするには、スイッチング素子Ｓ９やスイッチング素子Ｓ１０を介して電流が流れる必要があるため、ダイオードＳ９ＤやダイオードＳ１０Ｄだけでなく、第２変換部２３にスイッチング素子Ｓ９やスイッチング素子Ｓ１０が設けられる。 In addition, in the second conversion unit 23 of this embodiment, when no load is connected between the terminals 20C and 20D, it is necessary to make the current (average value) flowing through the third reactor coil 23L zero. At this time, as shown in FIG. 3A, a positive current (I>0) and a negative current (I<0) flow through the third reactor coil 23L. As shown in FIG. 3B, the positive current is the current flowing through the third reactor coil 23L, the second capacitor 26, and the switching element S9, or the current flowing through the third reactor coil 23L, the second capacitor 26, and the switching element S10. As shown in FIG. 3C, the negative current is the current flowing through the switching element S9, the second capacitor 26, and the third reactor coil 23L, or the current flowing through the switching element S10, the second capacitor 26, and the third reactor coil 23L. In particular, in order for such a negative current to flow through the second conversion unit 23, the current must flow through switching element S9 and switching element S10, so in addition to diodes S9D and S10D, switching elements S9 and S10 are provided in the second conversion unit 23.
　また、上述したように、第２変換部２３には、抵抗器Ｒとコンデンサ２７とでスナバ回路が形成されている。これにより、スイッチング素子Ｓ９及びスイッチング素子Ｓ１０の双方が開状態であるときに、第１三次巻線２４ＣＡに蓄えられた電気エネルギーを、ダイオード２３Ｄ１、抵抗器Ｒ、第３リアクトルコイル２３Ｌを介して電流を流すことで低減でき、第２三次巻線２４ＣＢに蓄えられた電気エネルギーを、ダイオード２３Ｄ２、抵抗器Ｒ、第３リアクトルコイル２３Ｌを介して電流を流すことで低減できる。 As described above, the second conversion unit 23 has a snubber circuit formed by the resistor R and the capacitor 27. As a result, when both the switching element S9 and the switching element S10 are in the open state, the electrical energy stored in the first tertiary winding 24CA can be reduced by passing a current through the diode 23D1, the resistor R, and the third reactor coil 23L, and the electrical energy stored in the second tertiary winding 24CB can be reduced by passing a current through the diode 23D2, the resistor R, and the third reactor coil 23L.
　また、上述したように、スイッチング素子Ｓ９はｔ３からｔ５の間に亘って開状態とされ、スイッチング素子Ｓ１０はｔ７からｔ９の間に亘って開状態とされる。第２変換部２３から出力される直流電圧の第２電圧値は、スイッチング素子Ｓ９が開状態とされる期間、及びスイッチング素子Ｓ１０が開状態とされる期間により変更することが可能である。このスイッチング素子Ｓ９が開状態にされる期間、及びスイッチング素子Ｓ１０が開状態にされる期間は、（キャリア周期／２）－第１シフト量θ１に相当する。したがって、本実施形態では、第２電圧値の直流電圧は、第１シフト量θ１に基づいて制御することが可能である。 As described above, switching element S9 is open from t3 to t5, and switching element S10 is open from t7 to t9. The second voltage value of the DC voltage output from the second conversion unit 23 can be changed depending on the period during which switching element S9 is open and the period during which switching element S10 is open. The period during which switching element S9 is open and the period during which switching element S10 is open correspond to (carrier period/2) - first shift amount θ1. Therefore, in this embodiment, the DC voltage of the second voltage value can be controlled based on the first shift amount θ1.
　ここで、第２変換部２３はバッテリ３に充電されている電気エネルギーに基づいて第２電圧値の直流電圧で構成される直流電力を生成することも可能である。この場合には、供給部２からの直流電力の供給が停止され、バッテリ３の直流電力がトランス２４の二次巻線２４Ｂから一次巻線２４Ａに電力伝送され、一次巻線２４Ａから三次巻線２４Ｃへ電力伝送される。このようなバッテリ３からの直流電力に基づいて、第２変換部２３から直流電力を出力する場合における、制御部５０によるコンバータ２０に設けられる複数のスイッチング素子の夫々を駆動するタイミングチャートが図４に示される。この場合も、制御部５０は、スイッチング素子Ｓ１－Ｓ１０を、第１状態－第８状態の８個の状態に、順次、切り替えながら駆動する。 Here, the second conversion unit 23 can also generate DC power consisting of a DC voltage of a second voltage value based on the electrical energy stored in the battery 3. In this case, the supply of DC power from the supply unit 2 is stopped, and the DC power of the battery 3 is transmitted from the secondary winding 24B of the transformer 24 to the primary winding 24A, and from the primary winding 24A to the tertiary winding 24C. FIG. 4 shows a timing chart of the control unit 50 driving each of the multiple switching elements provided in the converter 20 when DC power is output from the second conversion unit 23 based on such DC power from the battery 3. In this case, the control unit 50 drives the switching elements S1-S10 while switching them sequentially between eight states from the first state to the eighth state.
　バッテリ３からの直流電力に基づいて、第２変換部２３から直流電力を出力する場合における第１状態は図４のｔ１－ｔ２の間の状態であり、この第１状態では、制御部５０は、スイッチング素子Ｓ１,Ｓ３,Ｓ５,Ｓ７,Ｓ９,Ｓ１０を閉状態にし、スイッチング素子Ｓ２,Ｓ４,Ｓ６,Ｓ８を開状態にする。 The first state in which DC power is output from the second conversion unit 23 based on DC power from the battery 3 is the state between t1 and t2 in FIG. 4. In this first state, the control unit 50 closes the switching elements S1, S3, S5, S7, S9, and S10, and opens the switching elements S2, S4, S6, and S8.
　第２状態は図４のｔ２－ｔ３の間の状態であり、この第２状態では、制御部５０は、スイッチング素子Ｓ１,Ｓ３,Ｓ５,Ｓ８,Ｓ９,Ｓ１０を閉状態にし、スイッチング素子Ｓ２,Ｓ４,Ｓ６,Ｓ７を開状態にする。 The second state is the state between t2 and t3 in FIG. 4, and in this second state, the control unit 50 closes the switching elements S1, S3, S5, S8, S9, and S10, and opens the switching elements S2, S4, S6, and S7.
　第３状態は図４のｔ３－ｔ４の間の状態であり、この第３状態では、制御部５０は、スイッチング素子Ｓ１,Ｓ４,Ｓ５,Ｓ８,Ｓ１０を閉状態にし、スイッチング素子Ｓ２,Ｓ３,Ｓ６,Ｓ７,Ｓ９を開状態にする。 The third state is the state between t3 and t4 in FIG. 4, and in this third state, the control unit 50 closes the switching elements S1, S4, S5, S8, and S10, and opens the switching elements S2, S3, S6, S7, and S9.
　第４状態は図２のｔ４－ｔ５の間の状態であり、この第４状態では、制御部５０は、スイッチング素子Ｓ１,Ｓ４,Ｓ６,Ｓ８,Ｓ１０を閉状態にし、スイッチング素子Ｓ２,Ｓ３,Ｓ５,Ｓ７,Ｓ９を開状態にする。 The fourth state is the state between t4 and t5 in FIG. 2, and in this fourth state, the control unit 50 closes the switching elements S1, S4, S6, S8, and S10, and opens the switching elements S2, S3, S5, S7, and S9.
　第５状態は図２のｔ５－ｔ６の間の状態であり、この第５状態では、制御部５０は、スイッチング素子Ｓ２,Ｓ４,Ｓ６,Ｓ８,Ｓ９,Ｓ１０を閉状態にし、スイッチング素子Ｓ１,Ｓ３,Ｓ５,Ｓ７を開状態にする。 The fifth state is the state between t5 and t6 in FIG. 2, and in this fifth state, the control unit 50 closes the switching elements S2, S4, S6, S8, S9, and S10, and opens the switching elements S1, S3, S5, and S7.
　第６状態は図２のｔ６－ｔ７の間の状態であり、この第６状態では、制御部５０は、スイッチング素子Ｓ２,Ｓ４,Ｓ６,Ｓ７,Ｓ９,Ｓ１０を閉状態にし、スイッチング素子Ｓ１,Ｓ３,Ｓ５,Ｓ８を開状態にする。 The sixth state is the state between t6 and t7 in FIG. 2, and in this sixth state, the control unit 50 closes the switching elements S2, S4, S6, S7, S9, and S10, and opens the switching elements S1, S3, S5, and S8.
　第７状態は図２のｔ７－ｔ８の間の状態であり、この第７状態では、制御部５０は、スイッチング素子Ｓ２,Ｓ３,Ｓ６,Ｓ７,Ｓ９を閉状態にし、スイッチング素子Ｓ１,Ｓ４,Ｓ５,Ｓ８,Ｓ１０を開状態にする。 The seventh state is the state between t7 and t8 in FIG. 2, and in this seventh state, the control unit 50 closes the switching elements S2, S3, S6, S7, and S9, and opens the switching elements S1, S4, S5, S8, and S10.
　第８状態は図２のｔ８－ｔ９の間の状態であり、この第８状態では、制御部５０は、スイッチング素子Ｓ２,Ｓ３,Ｓ５,Ｓ７,Ｓ９を閉状態にし、スイッチング素子Ｓ１,Ｓ４,Ｓ６,Ｓ８,Ｓ１０を開状態にする。 The eighth state is the state between t8 and t9 in FIG. 2, and in this eighth state, the control unit 50 closes the switching elements S2, S3, S5, S7, and S9, and opens the switching elements S1, S4, S6, S8, and S10.
　ここで、理解を容易にするために、１周期におけるスイッチＳ１－Ｓ８の夫々が閉状態になる期間と、スイッチＳ１－Ｓ８の夫々が開状態になる期間とは互いに等しいものとする。 To make it easier to understand, it is assumed that the period during which each of the switches S1-S8 is in a closed state during one cycle is equal to the period during which each of the switches S1-S8 is in an open state.
　スイッチング素子Ｓ１、スイッチング素子Ｓ２、スイッチング素子Ｓ３、及びスイッチング素子Ｓ４は、上述したバッテリ３の充電時と同様に駆動される。すなわち、図４に示されるように、第３レグ２１１のスイッチング素子Ｓ１と第４レグ２１２のスイッチング素子Ｓ４とは、予め設定された第１シフト量θ１だけずらして閉状態にされ、第３レグ２１１のスイッチング素子Ｓ１と第４レグ２１２のスイッチング素子Ｓ４とは、第１シフト量θ１だけずれて開状態にされる。 Switching elements S1, S2, S3, and S4 are driven in the same manner as when charging battery 3 described above. That is, as shown in FIG. 4, switching element S1 of third leg 211 and switching element S4 of fourth leg 212 are shifted by a preset first shift amount θ1 to be in a closed state, and switching element S1 of third leg 211 and switching element S4 of fourth leg 212 are shifted by a first shift amount θ1 to be in an open state.
　また、第３レグ２１１のスイッチング素子Ｓ２と第４レグ２１２のスイッチング素子Ｓ３とは、第１シフト量θ１だけずらして閉状態にされ、第３レグ２１１のスイッチング素子Ｓ２と第４レグ２１２のスイッチング素子Ｓ３とは、第１シフト量θ１だけずれて開状態にされる。 Furthermore, the switching element S2 of the third leg 211 and the switching element S3 of the fourth leg 212 are shifted by the first shift amount θ1 and are put into a closed state, and the switching element S2 of the third leg 211 and the switching element S3 of the fourth leg 212 are shifted by the first shift amount θ1 and are put into an open state.
　また、第５レグ２２１のスイッチング素子Ｓ５と第６レグ２２２のスイッチング素子Ｓ８とは、第１シフト量θ１だけずらして閉状態にされ、第５レグ２２１のスイッチング素子Ｓ５と第６レグ２２２のスイッチング素子Ｓ８とは、第１シフト量θ１だけずれて開状態にされる。 Furthermore, the switching element S5 of the fifth leg 221 and the switching element S8 of the sixth leg 222 are shifted by the first shift amount θ1 and put into a closed state, and the switching element S5 of the fifth leg 221 and the switching element S8 of the sixth leg 222 are shifted by the first shift amount θ1 and put into an open state.
　更に、第５レグ２２１のスイッチング素子Ｓ６と第６レグ２２２のスイッチング素子Ｓ７とは、第１シフト量θ１だけずらして閉状態にされ、第５レグ２２１のスイッチング素子Ｓ６と第６レグ２２２のスイッチング素子Ｓ７とは、第１シフト量θ１だけずれて開状態にされる。 Furthermore, the switching element S6 of the fifth leg 221 and the switching element S7 of the sixth leg 222 are shifted by the first shift amount θ1 and are put into a closed state, and the switching element S6 of the fifth leg 221 and the switching element S7 of the sixth leg 222 are shifted by the first shift amount θ1 and are put into an open state.
　また、バッテリ３に充電された電気エネルギーに基づいて第２電圧値の直流電圧で構成される直流電力を生成する時は、第５レグ２２１のスイッチング素子Ｓ５は、第３レグ２１１のスイッチング素子Ｓ１が閉状態にされてから、第２シフト量θ２だけ前において閉状態にされる。すなわち、図４に示されるように、第５レグ２２１のスイッチング素子Ｓ５は、第３レグ２１１のスイッチング素子Ｓ１が閉状態にされるｔ９から第２シフト量θ２だけ前のｔ８において閉状態にされる。また、第５レグ２２１のスイッチング素子Ｓ５は、第３レグ２１１のスイッチング素子Ｓ１が開状態にされる第２シフト量θ２だけ前において開状態にされる。すなわち、図４に示されるように、第５レグ２２１のスイッチング素子Ｓ５は、第３レグ２１１のスイッチング素子Ｓ１が開状態にされるｔ５から第２シフト量θ２だけ前のｔ４において開状態にされる。 When generating DC power consisting of a DC voltage of the second voltage value based on the electric energy charged in the battery 3, the switching element S5 of the fifth leg 221 is closed the second shift amount θ2 before the switching element S1 of the third leg 211 is closed. That is, as shown in FIG. 4, the switching element S5 of the fifth leg 221 is closed at t8, which is the second shift amount θ2 before t9, when the switching element S1 of the third leg 211 is closed. Also, the switching element S5 of the fifth leg 221 is opened the second shift amount θ2 before the switching element S1 of the third leg 211 is opened. That is, as shown in FIG. 4, the switching element S5 of the fifth leg 221 is opened at t4, which is the second shift amount θ2 before t5, when the switching element S1 of the third leg 211 is opened.
　また、第６レグ２２２のスイッチング素子Ｓ７は、第４レグ２１２のスイッチング素子Ｓ３が閉状態にされてから、第２シフト量θ２だけ前において閉状態にされる。すなわち、図４に示されるように、第６レグ２２２のスイッチング素子Ｓ７は、第４レグ２１２のスイッチング素子Ｓ３が閉状態にされるｔ７から第２シフト量θ２だけ前のｔ６において閉状態にされる。また、第６レグ２２２のスイッチング素子Ｓ７は、第４レグ２１２のスイッチング素子Ｓ３が開状態にされる第２シフト量θ２だけ前において開状態にされる。すなわち、図４に示されるように、第６レグ２２２のスイッチング素子Ｓ７は、第４レグ２１２のスイッチング素子Ｓ３が開状態にされるｔ９から第２シフト量θ２だけ前のｔ１０において開状態にされる。 Also, the switching element S7 of the sixth leg 222 is closed the second shift amount θ2 before the switching element S3 of the fourth leg 212 is closed. That is, as shown in FIG. 4, the switching element S7 of the sixth leg 222 is closed at t6, which is the second shift amount θ2 before t7, when the switching element S3 of the fourth leg 212 is closed. Also, the switching element S7 of the sixth leg 222 is opened the second shift amount θ2 before the switching element S3 of the fourth leg 212 is opened. That is, as shown in FIG. 4, the switching element S7 of the sixth leg 222 is opened at t10, which is the second shift amount θ2 before t9, when the switching element S3 of the fourth leg 212 is opened.
　また、図４に示されるように、スイッチング素子Ｓ９はｔ３からｔ５の間に亘って開状態とされ、スイッチング素子Ｓ１０はｔ７からｔ９の間に亘って開状態とされる。これにより、バッテリ３に充電された電気エネルギーに基づいて第２電圧値の直流電圧で構成される直流電力を生成する時も、バッテリ３を充電する時と同様に、図４に示されるように、スイッチング素子Ｓ９には、Ｉ９で示されるような波形の電流が流れ、スイッチング素子Ｓ１０には、Ｉ１０で示されるような波形の電流が流れる。したがって、第１三次巻線２４ＣＡを流れる電流と第２三次巻線２４ＣＢを流れる電流との合成電流の平均値が零に設定可能である。 Also, as shown in FIG. 4, switching element S9 is open between t3 and t5, and switching element S10 is open between t7 and t9. As a result, when generating DC power consisting of a DC voltage of the second voltage value based on the electrical energy stored in battery 3, a current having a waveform as shown by I9 flows through switching element S9, and a current having a waveform as shown by I10 flows through switching element S10, as shown in FIG. 4, in the same way as when charging battery 3. Therefore, the average value of the combined current of the current flowing through first tertiary winding 24CA and the current flowing through second tertiary winding 24CB can be set to zero.
　以上のように構成することで、交流電力により電源装置１によりバッテリ３を充電する際に、バッテリ３を充電することが可能な第１電圧値の直流電圧で構成される直流電圧を出力すると共に、第２電圧値の直流電圧値で構成される直流電圧を出力することが可能となる。また、バッテリ３からの直流電力により、第２電圧値の直流電圧値で構成される直流電圧を出力することが可能となる。 By configuring as described above, when the power supply device 1 charges the battery 3 with AC power, it is possible to output a DC voltage consisting of a DC voltage of a first voltage value capable of charging the battery 3, and to output a DC voltage consisting of a DC voltage value of a second voltage value. In addition, it is possible to output a DC voltage consisting of a DC voltage value of the second voltage value using DC power from the battery 3.
〔その他の実施形態〕
　上記実施形態では、インバータ１０及びコンバータ２０が有するスイッチング素子が、ｎ型ＭＯＳ－ＦＥＴであるとして説明したが、スイッチング素子はｐ型ＭＯＳ－ＦＥＴでもよいし、ＦＥＴとは異なるスイッチング素子（例えばＩＧＢＴやバイポーラトランジスタ）であってもよい。 Other embodiments
In the above embodiment, the switching elements of the inverter 10 and the converter 20 are described as n-type MOS-FETs. However, the switching elements may be p-type MOS-FETs or switching elements other than FETs (e.g., IGBTs or bipolar transistors).
　上記実施形態では、インバータ１０及びコンバータ２０がスイッチング素子により交流電力を直流電力に変換するとして説明したが、インバータ１０はダイオードにより交流電力を直流電力に変換するように構成してもよい。 In the above embodiment, the inverter 10 and converter 20 are described as converting AC power to DC power using switching elements, but the inverter 10 may also be configured to convert AC power to DC power using diodes.
　上記実施形態では、制御部５０がスイッチング素子を第１状態－第８状態により駆動し、夫々の状態を挙げて説明した。しかしながら、第１状態－第８状態の８個の状態よりも多い状態に基づいて駆動することも可能であるし、７個以下の状態に基づいて駆動することも可能である。また、夫々の状態におけるスイッチング素子の状態は例示であって、上記実施形態とは異なる形態でスイッチング素子を駆動することも可能である。 In the above embodiment, the control unit 50 drives the switching element in the first state to the eighth state, and each state is described. However, it is also possible to drive the switching element based on more than eight states from the first state to the eighth state, or based on seven states or less. In addition, the state of the switching element in each state is merely an example, and it is also possible to drive the switching element in a form different from that of the above embodiment.
　上記実施形態では、インバータ１０に供給される交流電力は、商用電源による交流電力であるとして説明したが、インバータ１０に供給される交流電力は、商用電源の交流電力とは異なる交流電力であってもよい。 In the above embodiment, the AC power supplied to the inverter 10 is described as AC power from a commercial power source, but the AC power supplied to the inverter 10 may be AC power different from the AC power of the commercial power source.
　上記実施形態では、トランス２４の三次巻線２４Ｃは、第１三次巻線２４ＣＡと第２三次巻線２４ＣＢとから構成されるとして説明したが、三次巻線２４Ｃは１つの巻線であってもよいし、３つ以上の巻線であってもよい。 In the above embodiment, the tertiary winding 24C of the transformer 24 is described as being composed of a first tertiary winding 24CA and a second tertiary winding 24CB, but the tertiary winding 24C may be a single winding or may be three or more windings.
　上記実施形態では、第１三次巻線２４ＣＡを流れる電流と第２三次巻線２４ＣＢを流れる電流との合成電流の平均値が零であるとして説明したが、第１三次巻線２４ＣＡを流れる電流と第２三次巻線２４ＣＢを流れる電流との合成電流の平均値は零でなくてもよく、例えば第１三次巻線２４ＣＡを流れる電流と第２三次巻線２４ＣＢを流れる電流とが、所定の直流電流に重畳されたような電流であってもよい。 In the above embodiment, it has been described that the average value of the composite current of the current flowing through the first tertiary winding 24CA and the current flowing through the second tertiary winding 24CB is zero. However, the average value of the composite current of the current flowing through the first tertiary winding 24CA and the current flowing through the second tertiary winding 24CB does not have to be zero. For example, the current flowing through the first tertiary winding 24CA and the current flowing through the second tertiary winding 24CB may be a current in which a predetermined DC current is superimposed.
　上記実施形態では、第２電圧値の直流電圧は、第１シフト量θ１に基づいて制御されるとして説明したが、第２電圧値の直流電圧は、例えばフィードバック制御により制御してもよい。 In the above embodiment, the DC voltage of the second voltage value is described as being controlled based on the first shift amount θ1, but the DC voltage of the second voltage value may also be controlled by, for example, feedback control.
　上記実施形態では、第２シフト量θ２は、第１変換部２２から出力する直流電力の電力指令値と、第１変換部２２から出力された直流電力の電力算定値とに基づいて設定されるとして説明した。しかしながら、第２シフト量θ２は、予め設定しておくように構成してもよいし、例えばコンバータ２０の負荷の種類に応じて適宜、変更するように構成することも可能である。 In the above embodiment, the second shift amount θ2 is described as being set based on the power command value of the DC power output from the first conversion unit 22 and the power calculation value of the DC power output from the first conversion unit 22. However, the second shift amount θ2 may be configured to be set in advance, or may be configured to be changed as appropriate depending on, for example, the type of load on the converter 20.
〔上記実施形態の概要〕
　以下、上記において説明した電源装置１の概要について説明する。 [Summary of the above embodiment]
The power supply device 1 described above will now be outlined.
（１）本発明に係る電源装置１の特徴構成は、ハイサイドのスイッチング素子１１Ｈ及びローサイドのスイッチング素子１１Ｌが直列に接続された第１レグ１１とハイサイドのスイッチング素子１２Ｈ及びローサイドのスイッチング素子１２Ｌが直列に接続された第２レグ１２とが互いに並列に設けられ、交流電力を直流電力に変換するインバータ１０と、一次巻線２４Ａ、二次巻線２４Ｂ、及び三次巻線２４Ｃを有する絶縁型のトランス（マルチポートトランス）２４が設けられ、インバータ１０からの直流電力を、バッテリ３を充電する第１電圧値の直流電圧で構成される直流電力に変換するコンバータ２０と、を備え、コンバータ２０は、インバータ１０からの直流電力を所定の周期で振幅させて一次巻線２４Ａに入力する入力部２１と、二次巻線２４Ｂに生じる交流電力を、第１電圧値の直流電圧で構成される直流電力に変換する第１変換部２２と、三次巻線２４Ｃに生じる交流電力を、第１電圧値よりも低い第２電圧値の直流電圧で構成される直流電力に変換する第２変換部２３と、を有し、第２変換部２３は、三次巻線２４Ｃに生じる交流電力を、同期整流により第２電圧値の直流電圧で構成される直流電力に変換する点にある。 (1) The characteristic configuration of the power supply device 1 according to the present invention is that a first leg 11 in which a high-side switching element 11H and a low-side switching element 11L are connected in series and a second leg 12 in which a high-side switching element 12H and a low-side switching element 12L are connected in series are provided in parallel with each other, an inverter 10 that converts AC power to DC power, and an isolated transformer (multi-port transformer) 24 having a primary winding 24A, a secondary winding 24B, and a tertiary winding 24C are provided, and the DC power from the inverter 10 is configured as a DC voltage of a first voltage value that charges a battery 3. The converter 20 has an input section 21 that oscillates the DC power from the inverter 10 at a predetermined period and inputs it to the primary winding 24A, a first conversion section 22 that converts the AC power generated in the secondary winding 24B into DC power composed of a DC voltage of a first voltage value, and a second conversion section 23 that converts the AC power generated in the tertiary winding 24C into DC power composed of a DC voltage of a second voltage value lower than the first voltage value, and the second conversion section 23 converts the AC power generated in the tertiary winding 24C into DC power composed of a DC voltage of the second voltage value by synchronous rectification.
　本特徴構成によれば、コンバータ２０の第１変換部２２から第１電圧値の直流電圧で構成される直流電力を出力すると同時に、第２変換部２３から第２電圧値の直流電圧で構成される直流電力を出力することが可能となる。また、上述した特徴構成によれば、第１電圧値の直流電圧で構成される直流電力の出力と、第２電圧値の直流電圧で構成される直流電力の出力とを、簡素な構成で容易に行うことが可能となる。 This characteristic configuration makes it possible to output DC power consisting of a DC voltage of a first voltage value from the first conversion unit 22 of the converter 20, and at the same time output DC power consisting of a DC voltage of a second voltage value from the second conversion unit 23. Furthermore, the above-mentioned characteristic configuration makes it possible to easily output DC power consisting of a DC voltage of a first voltage value and DC power consisting of a DC voltage of a second voltage value with a simple configuration.
（２）（１）に記載の電源装置１において、入力部２１は、ハイサイドのスイッチング素子Ｓ１及びローサイドのスイッチング素子Ｓ２が直列に接続された第３レグ２１１とハイサイドのスイッチング素子Ｓ３及びローサイドのスイッチング素子Ｓ４が直列に接続された第４レグ２１２とが互いに並列に設けられ、第１変換部２２は、ハイサイドのスイッチング素子Ｓ５及びローサイドのスイッチング素子Ｓ６が直列に接続された第５レグ２２１とハイサイドのスイッチング素子Ｓ７及びローサイドのスイッチング素子Ｓ８が直列に接続された第６レグ２２２とが互いに並列に設けられ、第３レグ２１１のハイサイドのスイッチング素子Ｓ１と第４レグ２１２のローサイドのスイッチング素子Ｓ４とが予め設定された第１シフト量だけずらして閉状態にされ、第３レグ２１１のローサイドのスイッチング素子Ｓ２と第４レグ２１２のハイサイドのスイッチング素子Ｓ３とが第１シフト量だけずらして閉状態にされ、第５レグ２２１のハイサイドのスイッチング素子Ｓ５と第６レグ２２２のローサイドのスイッチング素子Ｓ８とが第１シフト量だけずらして閉状態にされ、第５レグ２２１のローサイドのスイッチング素子Ｓ６と第６レグ２２２のハイサイドのスイッチング素子Ｓ７とが第１シフト量だけずらして閉状態にされ、バッテリ３の充電時は、第５レグ２２１のハイサイドのスイッチング素子Ｓ５は、第３レグ２１１のハイサイドのスイッチング素子Ｓ１が閉状態にされる第１シフト量よりも小さい第２シフト量だけ後において閉状態にされ、第６レグ２２２のハイサイドのスイッチング素子ＳＳ７は、第４レグ２１２のハイサイドのスイッチング素子Ｓ３が閉状態にされる第２シフト量だけ後において閉状態にされると好適である。 (2) In the power supply device 1 described in (1), the input section 21 includes a third leg 211 in which a high-side switching element S1 and a low-side switching element S2 are connected in series, and a fourth leg 212 in which a high-side switching element S3 and a low-side switching element S4 are connected in series, which are provided in parallel to each other; the first conversion section 22 includes a fifth leg 221 in which a high-side switching element S5 and a low-side switching element S6 are connected in series, and a sixth leg 222 in which a high-side switching element S7 and a low-side switching element S8 are connected in series, which are provided in parallel to each other; the high-side switching element S1 of the third leg 211 and the low-side switching element S4 of the fourth leg 212 are shifted by a preset first shift amount to be in a closed state; and the low-side switching element S2 of the third leg 211 and the fourth leg 212 are shifted by a preset first shift amount to be in a closed state. The high-side switching element S3 of the fifth leg 221 and the low-side switching element S8 of the sixth leg 222 are closed with a shift of the first shift amount, the high-side switching element S5 of the fifth leg 221 and the low-side switching element S8 of the sixth leg 222 are closed with a shift of the first shift amount, the low-side switching element S6 of the fifth leg 221 and the high-side switching element S7 of the sixth leg 222 are closed with a shift of the first shift amount, and when charging the battery 3, the high-side switching element S5 of the fifth leg 221 is closed a second shift amount smaller than the first shift amount by which the high-side switching element S1 of the third leg 211 is closed, and the high-side switching element SS7 of the sixth leg 222 is closed a second shift amount by which the high-side switching element S3 of the fourth leg 212 is closed.
　本構成によれば、インバータ１０に供給される交流電力に基づいて、バッテリ３の充電を行うと同時に、バッテリ３を充電する直流電圧の電圧値とは異なる電圧値の直流電圧を、バッテリとは異なる負荷に対して供給することができる。 With this configuration, the battery 3 can be charged based on the AC power supplied to the inverter 10, and at the same time, a DC voltage with a voltage value different from the DC voltage that charges the battery 3 can be supplied to a load other than the battery.
（３）（１）に記載の電源装置１において、入力部２１は、ハイサイドのスイッチング素子Ｓ１及びローサイドのスイッチング素子Ｓ２が直列に接続された第３レグ２１１とハイサイドのスイッチング素子Ｓ３及びローサイドのスイッチング素子Ｓ４が直列に接続された第４レグ２１２とが互いに並列に設けられ、第１変換部２２は、ハイサイドのスイッチング素子Ｓ５及びローサイドのスイッチング素子Ｓ６が直列に接続された第５レグ２２１とハイサイドのスイッチング素子Ｓ７及びローサイドのスイッチング素子Ｓ８が直列に接続された第６レグ２２２とが互いに並列に設けられ、第３レグ２１１のハイサイドのスイッチング素子Ｓ１と第４レグ２１２のローサイドのスイッチング素子Ｓ３とが予め設定された第１シフト量だけずらして閉状態にされ、第３レグ２１１のローサイドのスイッチング素子Ｓ２と第４レグ２１２のハイサイドのスイッチング素子Ｓ３とが第１シフト量だけずらして閉状態にされ、第５レグ２２１のハイサイドのスイッチング素子Ｓ５と第６レグ２２２のローサイドのスイッチング素子Ｓ８とが第１シフト量だけずらして閉状態にされ、第５レグ２２１のローサイドのスイッチング素子Ｓ６と第６レグ２２２のハイサイドのスイッチング素子Ｓ７とが第１シフト量だけずらして閉状態にされ、第２変換部２３が、バッテリ３に充電された電気エネルギーに基づいて第２電圧値の直流電圧で構成される直流電力を生成する時は、第５レグ２２１のハイサイドのスイッチング素子Ｓ５は、第３レグ２１１のハイサイドのスイッチング素子Ｓ１が閉状態にされてから、第１シフト量よりも小さい第２シフト量だけ前において閉状態にされ、第６レグ２２２のハイサイドのスイッチング素子Ｓ７は、第４レグ２１２のハイサイドのスイッチング素子Ｓ３が開状態にされてから、第２シフト量だけ前において閉状態にされると好適である。 (3) In the power supply device 1 described in (1), the input unit 21 includes a third leg 211 in which a high-side switching element S1 and a low-side switching element S2 are connected in series, and a fourth leg 212 in which a high-side switching element S3 and a low-side switching element S4 are connected in series, which are provided in parallel to each other; the first conversion unit 22 includes a fifth leg 221 in which a high-side switching element S5 and a low-side switching element S6 are connected in series, and a sixth leg 222 in which a high-side switching element S7 and a low-side switching element S8 are connected in series, which are provided in parallel to each other; the high-side switching element S1 of the third leg 211 and the low-side switching element S3 of the fourth leg 212 are shifted by a preset first shift amount to be in a closed state; and the low-side switching element S2 of the third leg 211 and the high-side switching element S3 of the fourth leg 212 are shifted by a first shift amount to be in a closed state. When the second conversion unit 23 generates DC power consisting of a DC voltage of a second voltage value based on the electric energy stored in the battery 3, the high-side switching element S5 of the fifth leg 221 and the low-side switching element S8 of the sixth leg 222 are closed with a shift of a first shift amount, the low-side switching element S6 of the fifth leg 221 and the high-side switching element S7 of the sixth leg 222 are closed with a shift of a first shift amount, and the high-side switching element S5 of the fifth leg 221 is closed a second shift amount smaller than the first shift amount after the high-side switching element S1 of the third leg 211 is closed, and the high-side switching element S7 of the sixth leg 222 is closed a second shift amount before the high-side switching element S3 of the fourth leg 212 is opened.
　本構成によれば、インバータ１０に交流電力が供給されていない場合において、バッテリ３に充電されている電気エネルギーに基づいて、バッテリ３の出力電圧の電圧値とは異なる電圧値の直流電圧を、バッテリ３とは異なる負荷に対して供給することができる。 With this configuration, when AC power is not being supplied to the inverter 10, a DC voltage with a voltage value different from the voltage value of the output voltage of the battery 3 can be supplied to a load other than the battery 3 based on the electrical energy stored in the battery 3.
（４）（１）又は（２）に記載の電源装置１において、三次巻線２４Ｃは、第１三次巻線２４ＣＡと第２三次巻線２４ＣＢとから構成され、第１三次巻線２４ＣＡを流れる電流と第２三次巻線２４ＣＢを流れる電流との合成電流の平均値が零にも設定可能とする。 (4) In the power supply device 1 described in (1) or (2), the tertiary winding 24C is composed of a first tertiary winding 24CA and a second tertiary winding 24CB, and the average value of the combined current of the current flowing through the first tertiary winding 24CA and the current flowing through the second tertiary winding 24CB can be set to zero.
（５）（２）又は（３）に記載の電源装置１において、第２電圧値の直流電圧は、第１シフト量に基づいて制御されると好適である。 (5) In the power supply device 1 described in (2) or (3), it is preferable that the DC voltage of the second voltage value is controlled based on the first shift amount.
　本構成によれば、第２電圧値の直流電圧の出力も、第１電圧値の直流電圧の出力の制御に基づいて行うことができる。したがって、互いに異なる電圧値の直流電圧を簡素な制御で出力することが可能となる。 With this configuration, the output of the DC voltage of the second voltage value can also be performed based on the control of the output of the DC voltage of the first voltage value. Therefore, it is possible to output DC voltages of different voltage values with simple control.
（６）（２）又は（３）に記載の電源装置１において、第２シフト量は、第１変換部２２から出力する直流電力の電力指令値と、第１変換部２２から出力された直流電力の電力算定値とに基づいて設定されると好適である。 (6) In the power supply device 1 described in (2) or (3), it is preferable that the second shift amount is set based on the power command value of the DC power output from the first conversion unit 22 and the power calculation value of the DC power output from the first conversion unit 22.
　本構成によれば、第２シフト量の設定を容易に行うことができる。したがって、互いに異なる電圧値の直流電圧を簡素な制御で出力することが可能となる。 With this configuration, the second shift amount can be easily set. Therefore, it is possible to output DC voltages of different voltage values with simple control.
（７）（２）又は（３）に記載の電源装置１において、一次巻線２４Ａの両端の電位をＶ１、二次巻線２４Ｂ及びリアクトルの両端の電位をＶ２´、出力電力をＰ、第２シフト量をθ２、スイッチング素子のスイッチング周波数をω、リアクトルのインダクタンス値をＬとすると、
第２シフト量は、
Figure JPOXMLDOC01-appb-M000003
 に基づいて設定されると好適である。 (7) In the power supply device 1 described in (2) or (3), assuming that the potential across the primary winding 24A is V1, the potential across the secondary winding 24B and the reactor is V2', the output power is P, the second shift amount is θ2, the switching frequency of the switching element is ω, and the inductance value of the reactor is L,
The second shift amount is
Figure JPOXMLDOC01-appb-M000003
 It is preferable to set the value based on the above.
　本構成によれば、一次巻線２４Ａの両端の電位Ｖ１、二次巻線２４Ｂ及びリアクトルの両端の電位Ｖ２´、出力電力Ｐ、スイッチング素子のスイッチング周波数ω、及びリアクトルのインダクタンス値Ｌにより、第２シフト量θ２を容易に設定することが可能となる。 With this configuration, the second shift amount θ2 can be easily set using the potential V1 across the primary winding 24A, the potential V2' across the secondary winding 24B and the reactor, the output power P, the switching frequency ω of the switching element, and the inductance value L of the reactor.
（８）（１）又は（２）に記載の電源装置１において、三次巻線２４Ｃは、第１三次巻線２４ＣＡと第２三次巻線２４ＣＢとから構成され、第１三次巻線２４ＣＡと第２三次巻線２４ＣＢとは、第１三次巻線２４ＣＡの巻き終わり端と第２三次巻線２４ＣＢの巻き始め端とが互いに接続されており、第２変換部２３は、第１三次巻線２４ＣＡの巻き始め端にドレーン端子が接続されたスイッチング素子（第１スイッチング素子）Ｓ９と、第２三次巻線２４ＣＢの巻き終わり端にドレーン端子が接続されたスイッチング素子（第２スイッチング素子）Ｓ１０と、スイッチング素子Ｓ９のソース端子にアノード端子が接続され、スイッチング素子Ｓ９のドレーン端子にカソード端子が接続されたダイオード（第１ダイオード）Ｓ９Ｄと、スイッチング素子Ｓ１０のソース端子にアノード端子が接続され、スイッチング素子Ｓ１０のドレーン端子にカソード端子が接続されたダイオード（第２ダイオード）Ｓ１０Ｄと、第１三次巻線２４ＣＡの巻き終わり端に一方の端子が接続される第３リアクトルコイル（リアクトルコイル）２３Ｌと、第３リアクトルコイル２３Ｌの他方の端子とスイッチング素子Ｓ９のソース端子及びスイッチング素子Ｓ１０のソース端子とに亘って設けられる第２コンデンサ（第１コンデンサ）２６とを含むことが可能である。 (8) In the power supply device 1 described in (1) or (2), the tertiary winding 24C is composed of a first tertiary winding 24CA and a second tertiary winding 24CB, and the first tertiary winding 24CA and the second tertiary winding 24CB are connected to each other at the end of the first tertiary winding 24CA and the beginning of the winding of the second tertiary winding 24CB, and the second conversion unit 23 is composed of a switching element (first switching element) S9 having a drain terminal connected to the beginning of the winding of the first tertiary winding 24CA, a switching element (second switching element) S10 having a drain terminal connected to the end of the winding of the second tertiary winding 24CB, and an anode terminal connected to the source terminal of the switching element S9, It may include a diode (first diode) S9D having a cathode terminal connected to the drain terminal of the switching element S9, a diode (second diode) S10D having an anode terminal connected to the source terminal of the switching element S10 and a cathode terminal connected to the drain terminal of the switching element S10, a third reactor coil (reactor coil) 23L having one terminal connected to the winding end of the first tertiary winding 24CA, and a second capacitor (first capacitor) 26 provided across the other terminal of the third reactor coil 23L and the source terminal of the switching element S9 and the source terminal of the switching element S10.
　本構成によれば、スイッチング素子Ｓ９やスイッチング素子Ｓ１０における消費電力は、ダイオードＳ９ＤやダイオードＳ１０Ｄにおける消費電力よりも十分に小さいため、損失が小さくなり、第２変換部２３における効率（変換効率）の低下を抑制できる。したがって、効率よく電圧を出力することが可能となる。 With this configuration, the power consumption in switching element S9 and switching element S10 is much smaller than the power consumption in diodes S9D and S10D, so the loss is small and the decrease in efficiency (conversion efficiency) in the second conversion unit 23 can be suppressed. Therefore, it is possible to output the voltage efficiently.
（９）（８）に記載の電源装置１において、スイッチング素子Ｓ９及びスイッチング素子Ｓ１０は、同期整流により駆動されると好適である。 In the power supply device 1 described in (9) and (8), it is preferable that the switching element S9 and the switching element S10 are driven by synchronous rectification.
　本構成によれば、第２変換部２３をダイオード整流により駆動した場合に比べて、第２変換部２３の効率を向上することが可能となる。また、第２変換部２３に負荷が接続されていない場合において、図３の（Ｂ）に示されるような正電流や、図３の（Ｃ）に示されるような負電流を、第２変換部２３に流し、図３の（Ａ）に示されるように電流の平均値を零にすることが可能となる。 This configuration makes it possible to improve the efficiency of the second conversion unit 23 compared to when the second conversion unit 23 is driven by diode rectification. Furthermore, when no load is connected to the second conversion unit 23, it is possible to pass a positive current as shown in FIG. 3(B) or a negative current as shown in FIG. 3(C) through the second conversion unit 23, making it possible to make the average current value zero as shown in FIG. 3(A).
（１０）（９）に記載の電源装置１において、第２変換部２３は、アノード端子が第１三次巻線２４ＣＡの巻き始め端に接続されたダイオード（第３ダイオード）２３Ｄ１と、アノード端子が第２三次巻線２４ＣＢの巻き終わり端に接続されたダイオード（第４ダイオード）２３Ｄ２と、ダイオード２３Ｄ１のカソード端子及びダイオード２３Ｄ２のカソード端子と第３リアクトルコイル２３Ｌの他方の端子とに亘って設けられる抵抗器Ｒと、ダイオード２３Ｄ１のカソード端子とスイッチング素子Ｓ９のソース端子とに亘って設けられるコンデンサ（第２コンデンサ）２７とを更に含むと好適である。 (10) In the power supply device 1 described in (9), it is preferable that the second conversion unit 23 further includes a diode (third diode) 23D1 having an anode terminal connected to the winding start end of the first tertiary winding 24CA, a diode (fourth diode) 23D2 having an anode terminal connected to the winding end end of the second tertiary winding 24CB, a resistor R provided between the cathode terminal of the diode 23D1 and the cathode terminal of the diode 23D2 and the other terminal of the third reactor coil 23L, and a capacitor (second capacitor) 27 provided between the cathode terminal of the diode 23D1 and the source terminal of the switching element S9.
　本構成によれば、スイッチング素子Ｓ９及びスイッチング素子Ｓ１０の双方が開状態である場合であっても、第１三次巻線２４ＣＡに蓄えられた電気エネルギーを、ダイオード２３Ｄ１、抵抗器Ｒ、第３リアクトルコイル２３Ｌを介して電流を流すことで低減でき、第２三次巻線２４ＣＢに蓄えられた電気エネルギーを、ダイオード２３Ｄ２、抵抗器Ｒ、第３リアクトルコイル２３Ｌを介して電流を流すことで低減できる。 With this configuration, even when both switching element S9 and switching element S10 are in the open state, the electrical energy stored in the first tertiary winding 24CA can be reduced by passing a current through the diode 23D1, resistor R, and third reactor coil 23L, and the electrical energy stored in the second tertiary winding 24CB can be reduced by passing a current through the diode 23D2, resistor R, and third reactor coil 23L.
　本発明は、電源装置に用いることが可能である。 The present invention can be used in power supply devices.
　１：電源装置、３：バッテリ、１０：インバータ、１１：第１レグ、１１Ｈ：スイッチング素子、１１Ｌ：スイッチング素子、１２：第２レグ、１２Ｈ：スイッチング素子、１２Ｌ：スイッチング素子、２０：コンバータ、２１：入力部、２２：第１変換部、２３：第２変換部、２３Ｄ１：ダイオード（第３ダイオード）、２３Ｄ２：ダイオード（第４ダイオード）、２３Ｌ：第３リアクトルコイル（リアクトルコイル）、２４：トランス（マルチポートトランス）、２４Ａ：一次巻線、２４Ｂ：二次巻線、２４Ｃ：三次巻線、２４ＣＡ：第１三次巻線、２４ＣＢ：第２三次巻線、２６：第２コンデンサ（第１コンデンサ）、２７：コンデンサ（第２コンデンサ）、２１１：第３レグ、２１２：第４レグ、２２１：第５レグ、２２２：第６レグ、Ｓ１：スイッチング素子、Ｓ２：スイッチング素子、Ｓ３：スイッチング素子、Ｓ４：スイッチング素子、Ｓ５：スイッチング素子、Ｓ６：スイッチング素子、Ｓ７：スイッチング素子、Ｓ８：スイッチング素子、Ｓ９：スイッチング素子（第１スイッチング素子）、Ｓ９Ｄ：ダイオード（第１ダイオード）、Ｓ１０：スイッチング素子（第２スイッチング素子）、Ｓ１０Ｄ：ダイオード（第２ダイオード） 1: Power supply, 3: Battery, 10: Inverter, 11: First leg, 11H: Switching element, 11L: Switching element, 12: Second leg, 12H: Switching element, 12L: Switching element, 20: Converter, 21: Input section, 22: First conversion section, 23: Second conversion section, 23D1: Diode (third diode), 23D2: Diode (fourth diode), 23L: Third reactor coil (reactor coil), 24: Transformer (multi-port transformer), 24A: Primary winding, 24B: Secondary winding, 24C: Tertiary winding, 24CA: First tertiary winding, 24CB: Second tertiary Winding, 26: second capacitor (first capacitor), 27: capacitor (second capacitor), 211: third leg, 212: fourth leg, 221: fifth leg, 222: sixth leg, S1: switching element, S2: switching element, S3: switching element, S4: switching element, S5: switching element, S6: switching element, S7: switching element, S8: switching element, S9: switching element (first switching element), S9D: diode (first diode), S10: switching element (second switching element), S10D: diode (second diode)

Claims (10)

  1. 　ハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第１レグとハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第２レグとが互いに並列に設けられ、交流電力を直流電力に変換するインバータと、
    　一次巻線、二次巻線、及び三次巻線を有する絶縁型のマルチポートトランスが設けられ、前記インバータからの前記直流電力を、バッテリを充電する第１電圧値の直流電圧で構成される直流電力に変換するコンバータと、を備え、
    　前記コンバータは、前記インバータからの前記直流電力を所定の周期で振幅させて前記一次巻線に入力する入力部と、前記二次巻線に生じる交流電力を、前記第１電圧値の直流電圧で構成される直流電力に変換する第１変換部と、前記三次巻線に生じる交流電力を、前記第１電圧値よりも低い第２電圧値の直流電圧で構成される直流電力に変換する第２変換部と、を有し、
    　前記第２変換部は、前記三次巻線に生じる交流電力を、同期整流により前記第２電圧値の直流電圧で構成される直流電力に変換する電源装置。     an inverter in which a first leg in which a high-side switching element and a low-side switching element are connected in series and a second leg in which a high-side switching element and a low-side switching element are connected in series are provided in parallel with each other, and which converts AC power into DC power;
    a converter that is provided with an insulated multi-port transformer having a primary winding, a secondary winding, and a tertiary winding, and that converts the DC power from the inverter into DC power configured with a DC voltage of a first voltage value for charging a battery;
    the converter has an input unit that amplifies the DC power from the inverter at a predetermined period and inputs it to the primary winding, a first conversion unit that converts the AC power generated in the secondary winding into DC power composed of a DC voltage of the first voltage value, and a second conversion unit that converts the AC power generated in the tertiary winding into DC power composed of a DC voltage of a second voltage value lower than the first voltage value,
    The second conversion unit is a power supply device that converts the AC power generated in the tertiary winding into DC power constituted by a DC voltage of the second voltage value by synchronous rectification.
  2. 　前記入力部は、ハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第３レグとハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第４レグとが互いに並列に設けられ、
    　前記第１変換部は、ハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第５レグとハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第６レグとが互いに並列に設けられ、
    　前記第３レグの前記ハイサイドのスイッチング素子と前記第４レグの前記ローサイドのスイッチング素子とが予め設定された第１シフト量だけずらして閉状態にされ、
    　前記第３レグの前記ローサイドのスイッチング素子と前記第４レグの前記ハイサイドのスイッチング素子とが前記第１シフト量だけずらして閉状態にされ、
    　前記第５レグの前記ハイサイドのスイッチング素子と前記第６レグの前記ローサイドのスイッチング素子とが前記第１シフト量だけずらして閉状態にされ、
    　前記第５レグの前記ローサイドのスイッチング素子と前記第６レグの前記ハイサイドのスイッチング素子とが前記第１シフト量だけずらして閉状態にされ、
    　前記バッテリの充電時は、前記第５レグの前記ハイサイドのスイッチング素子は、前記第３レグの前記ハイサイドのスイッチング素子が閉状態にされる、前記第１シフト量よりも小さい第２シフト量だけ後において閉状態にされ、前記第６レグの前記ハイサイドのスイッチング素子は、前記第４レグの前記ハイサイドのスイッチング素子が閉状態にされる前記第２シフト量だけ後において閉状態にされる請求項１に記載の電源装置。     the input unit includes a third leg in which a high-side switching element and a low-side switching element are connected in series, and a fourth leg in which a high-side switching element and a low-side switching element are connected in series, the third leg being provided in parallel with the fourth leg;
    The first conversion unit includes a fifth leg in which a high-side switching element and a low-side switching element are connected in series, and a sixth leg in which a high-side switching element and a low-side switching element are connected in series, the fifth leg being provided in parallel with the high-side switching element and the low-side switching element;
    the high-side switching element of the third leg and the low-side switching element of the fourth leg are shifted by a preset first shift amount to be in a closed state;
    the low-side switching element of the third leg and the high-side switching element of the fourth leg are closed with a shift of the first shift amount;
    the high-side switching element of the fifth leg and the low-side switching element of the sixth leg are closed with a shift of the first shift amount;
    the low-side switching element of the fifth leg and the high-side switching element of the sixth leg are closed with a shift of the first shift amount;
    2. The power supply device according to claim 1, wherein, during charging of the battery, the high-side switching element of the fifth leg is closed a second shift amount smaller than the first shift amount after the high-side switching element of the third leg is closed, and the high-side switching element of the sixth leg is closed a second shift amount after the high-side switching element of the fourth leg is closed.
  3. 　前記入力部は、ハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第３レグとハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第４レグとが互いに並列に設けられ、
    　前記第１変換部は、ハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第５レグとハイサイドのスイッチング素子及びローサイドのスイッチング素子が直列に接続された第６レグとが互いに並列に設けられ、
    　前記第３レグの前記ハイサイドのスイッチング素子と前記第４レグの前記ローサイドのスイッチング素子とが予め設定された第１シフト量だけずらして閉状態にされ、
    　前記第３レグの前記ローサイドのスイッチング素子と前記第４レグの前記ハイサイドのスイッチング素子とが前記第１シフト量だけずらして閉状態にされ、
    　前記第５レグの前記ハイサイドのスイッチング素子と前記第６レグの前記ローサイドのスイッチング素子とが前記第１シフト量だけずらして閉状態にされ、
    　前記第５レグの前記ローサイドのスイッチング素子と前記第６レグの前記ハイサイドのスイッチング素子とが前記第１シフト量だけずらして閉状態にされ、
    　前記第２変換部が、前記バッテリに充電された電気エネルギーに基づいて前記第２電圧値の直流電圧で構成される直流電力を生成する時は、前記第５レグの前記ハイサイドのスイッチング素子は、前記第３レグの前記ハイサイドのスイッチング素子が閉状態にされてから、前記第１シフト量よりも小さい第２シフト量だけ前において閉状態にされ、前記第６レグの前記ハイサイドのスイッチング素子は、前記第４レグの前記ハイサイドのスイッチング素子が閉状態にされ、前記第２シフト量だけ前において閉状態にされる請求項１に記載の電源装置。     the input unit includes a third leg in which a high-side switching element and a low-side switching element are connected in series, and a fourth leg in which a high-side switching element and a low-side switching element are connected in series, the third leg being provided in parallel with the fourth leg;
    The first conversion unit includes a fifth leg in which a high-side switching element and a low-side switching element are connected in series, and a sixth leg in which a high-side switching element and a low-side switching element are connected in series, the fifth leg being provided in parallel with the high-side switching element and the low-side switching element;
    the high-side switching element of the third leg and the low-side switching element of the fourth leg are shifted by a preset first shift amount to be in a closed state;
    the low-side switching element of the third leg and the high-side switching element of the fourth leg are closed with a shift of the first shift amount;
    the high-side switching element of the fifth leg and the low-side switching element of the sixth leg are closed with a shift of the first shift amount;
    the low-side switching element of the fifth leg and the high-side switching element of the sixth leg are closed with a shift of the first shift amount;
    2. The power supply device according to claim 1, wherein, when the second conversion unit generates DC power constituted by a DC voltage of the second voltage value based on the electrical energy charged in the battery, the high-side switching element of the fifth leg is closed a second shift amount smaller than the first shift amount after the high-side switching element of the third leg is closed, and the high-side switching element of the sixth leg is closed a second shift amount before the high-side switching element of the fourth leg is closed.
  4. 　前記三次巻線は、第１三次巻線と第２三次巻線とから構成され、前記第１三次巻線を流れる電流と前記第２三次巻線を流れる電流との合成電流の平均値が零にも設定可能な請求項１又は２に記載の電源装置。 The power supply device according to claim 1 or 2, wherein the tertiary winding is composed of a first tertiary winding and a second tertiary winding, and the average value of the combined current of the current flowing through the first tertiary winding and the current flowing through the second tertiary winding can be set to zero.
  5. 　前記第２電圧値の直流電圧は、前記第１シフト量に基づいて制御される請求項２又は３に記載の電源装置。 The power supply device according to claim 2 or 3, wherein the DC voltage of the second voltage value is controlled based on the first shift amount.
  6. 　前記第２シフト量は、前記第１変換部から出力する直流電力の電力指令値と、前記第１変換部から出力された直流電力の電力算定値とに基づいて設定される請求項２又は３に記載の電源装置。 The power supply device according to claim 2 or 3, wherein the second shift amount is set based on a power command value of the DC power output from the first conversion unit and a power calculation value of the DC power output from the first conversion unit.
  7. 　一次巻線の両端の電位をＶ１、二次巻線及びリアクトルの両端の電位をＶ２´、出力電力をＰ、第２シフト量をθ２、スイッチング素子のスイッチング周波数をω、リアクトルのインダクタンス値をＬとすると、
    　前記第２シフト量は、
    Figure JPOXMLDOC01-appb-M000001
     に基づいて設定される請求項２又は３に記載の電源装置。     If the potential across the primary winding is V1, the potential across the secondary winding and the reactor is V2', the output power is P, the second shift amount is θ2, the switching frequency of the switching element is ω, and the inductance value of the reactor is L, then:
    The second shift amount is
    Figure JPOXMLDOC01-appb-M000001
     The power supply device according to claim 2 or 3, which is set based on the above.
  8. 　前記三次巻線は、第１三次巻線と第２三次巻線とから構成され、
    　前記第１三次巻線と前記第２三次巻線とは、前記第１三次巻線の巻き終わり端と前記第２三次巻線の巻き始め端とが互いに接続されており、
    　前記第２変換部は、前記第１三次巻線の巻き始め端にドレーン端子が接続された第１スイッチング素子と、前記第２三次巻線の巻き終わり端にドレーン端子が接続された第２スイッチング素子と、前記第１スイッチング素子のソース端子にアノード端子が接続され、前記第１スイッチング素子のドレーン端子にカソード端子が接続された第１ダイオードと、前記第２スイッチング素子のソース端子にアノード端子が接続され、前記第２スイッチング素子のドレーン端子にカソード端子が接続された第２ダイオードと、前記第１三次巻線の巻き終わり端に一方の端子が接続されるリアクトルコイルと、前記リアクトルコイルの他方の端子と前記第１スイッチング素子のソース端子及び前記第２スイッチング素子のソース端子とに亘って設けられる第１コンデンサとを含む請求項１又は２に記載の電源装置。     the tertiary winding is composed of a first tertiary winding and a second tertiary winding,
    The first tertiary winding and the second tertiary winding are connected to each other at a winding end of the first tertiary winding and a winding start end of the second tertiary winding,
    3. The power supply device according to claim 1, wherein the second conversion unit includes: a first switching element having a drain terminal connected to a winding start end of the first tertiary winding; a second switching element having a drain terminal connected to a winding end end of the second tertiary winding; a first diode having an anode terminal connected to a source terminal of the first switching element and a cathode terminal connected to a drain terminal of the first switching element; a second diode having an anode terminal connected to a source terminal of the second switching element and a cathode terminal connected to a drain terminal of the second switching element; a reactor coil having one terminal connected to the winding end end of the first tertiary winding; and a first capacitor provided across the other terminal of the reactor coil and the source terminal of the first switching element and the source terminal of the second switching element.
  9. 　前記第１スイッチング素子及び前記第２スイッチング素子は、前記同期整流により駆動される請求項８に記載の電源装置。 The power supply device according to claim 8, wherein the first switching element and the second switching element are driven by the synchronous rectification.
  10. 　前記第２変換部は、アノード端子が前記第１三次巻線の巻き始め端に接続された第３ダイオードと、アノード端子が前記第２三次巻線の巻き終わり端に接続された第４ダイオードと、前記第３ダイオードのカソード端子及び前記第４ダイオードのカソード端子と前記リアクトルコイルの他方の端子とに亘って設けられる抵抗器と、前記第３ダイオードのカソード端子と前記第１スイッチング素子のソース端子とに亘って設けられる第２コンデンサとを更に含む請求項９に記載の電源装置。 The power supply device according to claim 9, wherein the second conversion unit further includes a third diode having an anode terminal connected to the winding start end of the first tertiary winding, a fourth diode having an anode terminal connected to the winding end end of the second tertiary winding, a resistor provided between the cathode terminal of the third diode, the cathode terminal of the fourth diode, and the other terminal of the reactor coil, and a second capacitor provided between the cathode terminal of the third diode and the source terminal of the first switching element.
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JP2020028216A (en) * 2018-08-10 2020-02-20 シェンヂェン ヴイマックス ニュー エネルギー カンパニー リミテッドＳｈｅｎｚｈｅｎ ＶＭＡＸ Ｎｅｗ Ｅｎｅｒｇｙ Ｃｏ．，Ｌｔｄ． Phase shift control method for charging circuit
JP6996661B1 (en) * 2020-02-21 2022-01-17 住友電気工業株式会社 Power converter, vehicle including it and control method
JP2022011002A (en) * 2020-06-29 2022-01-17 シャープ株式会社 Power regenerative snubber circuit and power supply
JP6964825B1 (en) * 2020-12-08 2021-11-10 三菱電機株式会社 Power conversion unit and power conversion device

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