WO2023197661A1 - 非对称半桥变换电路的控制器、电源模组及电子设备 - Google Patents

非对称半桥变换电路的控制器、电源模组及电子设备 Download PDF

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Publication number
WO2023197661A1
WO2023197661A1 PCT/CN2022/140118 CN2022140118W WO2023197661A1 WO 2023197661 A1 WO2023197661 A1 WO 2023197661A1 CN 2022140118 W CN2022140118 W CN 2022140118W WO 2023197661 A1 WO2023197661 A1 WO 2023197661A1
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Prior art keywords
circuit
voltage
controller
output voltage
conversion circuit
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PCT/CN2022/140118
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English (en)
French (fr)
Inventor
孙程豪
戴宝磊
伍梁
郭志强
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华为数字能源技术有限公司
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Publication of WO2023197661A1 publication Critical patent/WO2023197661A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only

Definitions

  • the present application relates to power supply technology, and in particular to a controller of an asymmetrical half-bridge (AHB) conversion circuit and the power module and electronic equipment in which it is located.
  • ALB asymmetrical half-bridge
  • DC conversion circuits usually include half-bridge circuits, transformers and rectifier circuits.
  • the primary winding circuit of the transformer receives the input voltage from the input power supply through the half-bridge circuit, and the secondary winding circuit is used to provide the output voltage to power the load.
  • the transformer also includes an auxiliary winding circuit for supplying power to the power circuit of the controller.
  • the controller's power circuit When the power module is started, the controller's power circuit is generally powered by the input voltage of the input power supply.
  • the auxiliary winding circuit of the transformer supplies power to the controller's power circuit. Therefore, the operating status of the DC conversion circuit will affect the power supply stability of the controller's power circuit, thereby affecting the stability of the power supply module and electronic equipment where the controller is located.
  • This application provides a controller, power module and electronic equipment for an asymmetric half-bridge conversion circuit, which are used to solve the problem that the operating status of a DC conversion circuit such as an asymmetric half-bridge conversion circuit affects the power circuit of the controller and the power supply module where the controller is located.
  • the first aspect of the present application provides a controller for the asymmetric half-bridge conversion circuit, which can be used to control the operating state of the asymmetric half-bridge conversion circuit.
  • the controller controls the asymmetric half-bridge conversion circuit to operate in a continuous operating state
  • the output voltage of the asymmetric half-bridge conversion circuit is the rated output voltage.
  • the controller determines that the output voltage of the asymmetric half-bridge conversion circuit is higher than the first preset value, it controls the asymmetric half-bridge conversion circuit to run in a suspended working state.
  • the asymmetric half-bridge conversion circuit operates in the suspended working state, when the controller determines that the output voltage of the auxiliary winding circuit in the asymmetric half-bridge conversion circuit is less than or equal to the second preset value, the asymmetric half-bridge conversion is controlled.
  • the circuit's resonant capacitor is discharged.
  • the controller determines that the output voltage of the power circuit in the asymmetric half-bridge conversion circuit is less than or equal to the third preset value
  • the controller controls the asymmetric half-bridge conversion circuit.
  • the resonant capacitor discharges.
  • the controller provided in this embodiment can control the resonant capacitor of the asymmetric half-bridge conversion circuit to discharge after the asymmetric half-bridge conversion circuit runs in the suspended state, so that the output voltage of the power circuit has a voltage value higher than that of the controller.
  • the preset voltage value of the low-voltage protection prevents the controller from restarting due to low-voltage protection and improves the stability of the power module and electronic equipment where the asymmetric half-bridge conversion circuit is located.
  • the controller provided in this embodiment will not increase the ripple of the output voltage of the asymmetric half-bridge conversion circuit when controlling the discharge of the resonant capacitor, nor will it introduce noise from the input power supply.
  • the controller when the controller determines that the output voltage of the asymmetric half-bridge conversion circuit is less than or equal to the rated output voltage, the controller controls the asymmetric half-bridge conversion circuit to switch from a suspended operating state to a continuous operating state. . Therefore, the controller provided in this embodiment can promptly control the asymmetric half-bridge conversion circuit to resume its continuous working state after the output voltage of the asymmetric half-bridge conversion circuit returns to normal, further improving the power supply mode of the asymmetric half-bridge conversion circuit. group and electronic equipment stability.
  • the controller specifically controls the asymmetric half-bridge conversion circuit to operate in a manner such that both the auxiliary power transistor and the main power transistor of the half-bridge conversion circuit in the asymmetric half-bridge conversion circuit are turned off. Suspended working status. Therefore, the controller provided in this embodiment can control the asymmetric half-bridge conversion circuit to no longer process the received input voltage and provide an output voltage after the load level of the power module in which it is located drops, thus avoiding the need for the power module to The output voltage is too high and damages the load.
  • the controller controls the auxiliary power transistor in the half-bridge circuit of the asymmetric half-bridge conversion circuit to be turned on to discharge the resonant capacitor in the half-bridge circuit.
  • the output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be increased faster, the output voltage of the power module can be reduced faster, and the output voltage of the power module to the load can be reduced as much as possible to be greater than the first preset value. Protect loads more effectively.
  • the controller controls the auxiliary power transistor in the half-bridge circuit of the asymmetric half-bridge conversion circuit to periodically turn on to discharge the resonant capacitor in the half-bridge circuit. Since the resonant capacitor in the half-bridge circuit discharges periodically, the output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be increased in a stepwise manner, preventing the voltage from increasing too quickly and damaging the circuit components, thereby improving the asymmetric half-bridge conversion. The stability of the power module and electronic equipment where the circuit is located.
  • the controller controls the auxiliary power transistor and the main power transistor in the half-bridge circuit of the asymmetric half-bridge conversion circuit to periodically alternately conduct, so that the resonant capacitor in the half-bridge circuit discharges.
  • the controller controls the auxiliary power tube to turn on and the main power tube to turn off, the resonant capacitor discharges, and the voltage value of the output voltage of the controller's power circuit increases; when the controller controls the auxiliary power tube to turn off and the main power tube to turn on,
  • the input voltage produces a primary winding voltage on both sides of the primary winding.
  • the primary winding voltage is coupled through the transformer to produce an auxiliary winding voltage on the auxiliary winding.
  • the voltage value of the output voltage of the auxiliary winding circuit increases, and the voltage value of the output voltage of the power supply circuit of the controller increases.
  • the output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit are increased in a stepwise manner to avoid damage to the circuit components due to excessive increase, thereby improving the stability of the power module and electronic equipment where the asymmetric half-bridge conversion circuit is located.
  • the controller when the load level of the power module drops, the controller can control the resonant capacitor to start discharging. And when controlling the discharge of the resonant capacitor, the controller only needs to control the conduction or cutoff of the main power tube and the auxiliary power tube in the asymmetric half-bridge conversion circuit, making its configuration simple and more suitable for use in various products.
  • the controller determines that the capacitor voltage of the resonant capacitor drops to less than or equal to the preset capacitor voltage value, and then controls the resonant capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the capacitance voltage of the resonant capacitor from being too low and affect the asymmetric half-bridge conversion circuit from returning to a continuous operating state, further improving the stability of the power module and electronic equipment where the asymmetric half-bridge conversion circuit is located. sex.
  • the controller determines that the voltage value of the output voltage of the auxiliary winding circuit has increased to greater than or equal to the fourth preset value, and then controls the resonant capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the output voltage of the auxiliary winding circuit from being too high and damage the power circuit and the controller, further improving the stability of the power module and electronic equipment where the asymmetric half-bridge conversion circuit is located.
  • the controller may determine that the voltage value of the output voltage of the power circuit has increased to greater than or equal to the fifth preset value, and then control the resonant capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the output voltage of the power circuit from being too high and damage the controller, further improving the stability of the power module and electronic equipment where the asymmetric half-bridge conversion circuit is located.
  • the controller controls the auxiliary power transistor and the main power transistor in the half-bridge circuit of the asymmetric half-bridge conversion circuit to turn off, so that the resonant capacitor stops discharging. Therefore, in the scenario where the load level of the power module drops, the controller in this embodiment only needs to control the on or off of the main power tube and the auxiliary power tube in the asymmetric half-bridge conversion circuit to control the resonant capacitor to stop discharging. , making it simple to configure and more suitable for use in various products.
  • a second aspect of this application provides a power module, including an asymmetric half-bridge conversion circuit, an auxiliary winding circuit, a power circuit and a controller.
  • the asymmetric half-bridge conversion circuit includes: half-bridge circuit, transformer and rectifier circuit.
  • the half-bridge circuit includes a main power tube, an auxiliary power tube and a resonant capacitor.
  • the asymmetric half-bridge conversion circuit is used to receive the input voltage, perform voltage conversion processing on the input voltage, and then provide the output voltage to the load.
  • the auxiliary winding circuit is used to power the power circuit.
  • a power circuit is used to power the controller.
  • the controller can be used to control asymmetric half-bridge conversion circuits.
  • the controller controls the asymmetric half-bridge conversion circuit to operate in a continuous operating state
  • the output voltage of the asymmetric half-bridge conversion circuit is the rated output voltage.
  • the controller determines that the output voltage of the symmetrical half-bridge conversion circuit is higher than the first preset value, it controls the asymmetrical half-bridge conversion circuit to run in a suspended working state.
  • the controller determines that the output voltage of the auxiliary winding circuit in the asymmetric half-bridge conversion circuit is less than or equal to the second preset value, the asymmetric half-bridge conversion is controlled.
  • the circuit's resonant capacitor is discharged.
  • the controller determines that the output voltage of the power circuit in the asymmetric half-bridge conversion circuit is less than or equal to the third preset value, the controller controls the asymmetric half-bridge conversion circuit.
  • the resonant capacitor discharges.
  • the controller can control the resonant capacitor of the asymmetric half-bridge conversion circuit to discharge after the asymmetric half-bridge conversion circuit is running in the suspended state, so that the output voltage of the power circuit can be The value is higher than the preset voltage value of the controller's low-voltage protection, thereby preventing the controller from restarting due to low-voltage protection and improving the stability of the power module and its electronic equipment.
  • the controller provided in this embodiment will not increase the ripple of the output voltage of the asymmetric half-bridge conversion circuit when controlling the discharge of the resonant capacitor, nor will it introduce noise from the input power supply.
  • the controller when the controller determines that the output voltage of the asymmetric half-bridge conversion circuit is less than or equal to the rated output voltage, the controller controls the asymmetric half-bridge conversion circuit to switch from a suspended operating state to a continuous operating state. . Therefore, in the power module provided by this embodiment, the controller can timely control the asymmetric half-bridge conversion circuit to return to the continuous working state after the output voltage of the asymmetric half-bridge conversion circuit returns to normal, further improving the efficiency of the power module and its The stability of the electronic equipment in which it is located.
  • the controller specifically controls the asymmetric half-bridge conversion circuit to operate in a manner such that both the auxiliary power transistor and the main power transistor of the half-bridge conversion circuit in the asymmetric half-bridge conversion circuit are turned off. Suspended working status. Therefore, in the power module provided by this embodiment, the controller can control the asymmetric half-bridge conversion circuit to no longer process the received input voltage and provide an output voltage after the load level of the power module in which it is located drops. This avoids the output voltage of the power module being too high and damaging the load.
  • the controller controls the auxiliary power transistor in the half-bridge circuit of the asymmetric half-bridge conversion circuit to be turned on to discharge the resonant capacitor in the half-bridge circuit.
  • the output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be increased faster, the output voltage of the power module can be reduced faster, and the output voltage of the power module to the load can be reduced as much as possible to be greater than the first preset value. Protect loads more effectively.
  • the controller controls the auxiliary power transistor in the half-bridge circuit of the asymmetric half-bridge conversion circuit to periodically turn on to discharge the resonant capacitor in the half-bridge circuit. Since the resonant capacitor in the half-bridge circuit discharges periodically, the output voltage of the auxiliary winding circuit and the output voltage of the power circuit can be increased in a stepwise manner, preventing the voltage from increasing too quickly and damaging the circuit components, thus improving the efficiency of the power module and its The stability of the electronic equipment in which it is located.
  • the controller controls the auxiliary power transistor and the main power transistor in the half-bridge circuit of the asymmetric half-bridge conversion circuit to periodically conduct alternately to discharge the resonant capacitor in the half-bridge circuit.
  • the controller controls the auxiliary power tube to turn on and the main power tube to turn off, the resonant capacitor discharges, and the voltage value of the output voltage of the controller's power circuit increases;
  • the controller controls the auxiliary power tube to turn off and the main power tube to turn on,
  • the input voltage produces a primary winding voltage on both sides of the primary winding.
  • the primary winding voltage is coupled through the transformer to produce an auxiliary winding voltage on the auxiliary winding.
  • the voltage value of the output voltage of the auxiliary winding circuit increases, and the voltage value of the output voltage of the power supply circuit of the controller increases.
  • the output voltage of the auxiliary winding circuit and the output voltage of the power circuit are increased in a stepwise manner to avoid damage to the circuit components due to excessive increase, thereby improving the stability of the power module and the electronic equipment in which it is located.
  • the controller in the power module can control the resonant capacitor to start discharging. And when controlling the discharge of the resonant capacitor, the controller only needs to control the conduction or cutoff of the main power tube and the auxiliary power tube in the asymmetric half-bridge conversion circuit, making its configuration simple and more suitable for use in various products.
  • the controller determines that the capacitor voltage of the resonant capacitor drops to less than or equal to the preset capacitor voltage value, and then controls the resonant capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the capacitor voltage of the resonant capacitor from being too low and affect the asymmetric half-bridge conversion circuit from returning to a continuous operating state, further improving the stability of the power module and the electronic equipment in which it is located.
  • the controller determines that the voltage value of the output voltage of the auxiliary winding circuit has increased to greater than or equal to the fourth preset value, and then controls the resonant capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the output voltage of the auxiliary winding circuit from being too high and damaging the power circuit and the controller, further improving the stability of the power module and the electronic equipment in which it is located.
  • the controller may determine that the voltage value of the output voltage of the power circuit has increased to greater than or equal to the fifth preset value, and then control the resonant capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the output voltage of the power circuit from being too high and damage the controller, further improving the stability of the power module and the electronic equipment in which it is located.
  • the controller controls the auxiliary power transistor and the main power transistor in the half-bridge circuit of the asymmetric half-bridge conversion circuit to turn off, so that the resonant capacitor stops discharging. Therefore, in this embodiment, when the load level of the power module drops, the controller of the power module only needs to control the conduction of the main power tube and the auxiliary power tube in the asymmetric half-bridge conversion circuit to control the resonant capacitor to stop discharging. Or cut off to make it simple to configure and more suitable for use in various products.
  • the DC conversion circuit is an asymmetric half-bridge conversion circuit as an example.
  • the DC conversion circuit may also be an active clamp flyback conversion, etc.
  • a third aspect of this application provides an electronic device, including a controller of an asymmetric half-bridge conversion circuit as described in any one of the first aspect of this application.
  • a fourth aspect of this application provides an electronic device, including the power module according to any one of the second aspect of this application.
  • FIG. 1 is a schematic diagram of an electronic device provided by this application.
  • FIG. 2 is another schematic diagram of an electronic device provided by this application.
  • FIG. 3 is a schematic diagram of a power module provided by an embodiment of the present application.
  • Figure 4 is a schematic diagram of a power module
  • Figure 5 is a schematic diagram of the voltage waveform of the power module of Figure 4 in a scenario where the load level drops;
  • Figure 6 is a schematic diagram of another existing controller and its power module
  • Figure 7 is a schematic diagram of a power module provided by an embodiment of the present application.
  • Figure 8 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops;
  • FIG. 9 is a schematic diagram of an embodiment of the power module provided by this application.
  • FIG. 10 is a schematic diagram of an embodiment of the power module provided by this application.
  • Figure 11 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops;
  • FIG. 12 is a schematic diagram of an embodiment of the power module provided by this application.
  • Figure 13 is a schematic diagram of the control signals of the controller provided by this application in a scenario where the load level of the power module drops;
  • Figure 14 is a schematic diagram of the control signals of the controller provided by the embodiment of the present application.
  • Figure 15 is a schematic diagram of an embodiment of the controller provided by the present application controlling the resonant capacitor discharge of the AHB conversion circuit;
  • Figure 16 is a schematic diagram of changes in the capacitance voltage of the resonant capacitor of the AHB conversion circuit provided by this application;
  • Figure 17 is a schematic diagram of another embodiment of the controller provided by the present application controlling the resonant capacitor discharge of the AHB conversion circuit;
  • Figure 18 is a schematic diagram of the half-bridge circuit in another AHB conversion circuit provided by this application.
  • Figure 19 is a schematic diagram of the half-bridge circuit in another AHB conversion circuit provided by this application.
  • FIG. 20 is a schematic diagram of an embodiment of the power module provided by this application.
  • FIG. 21 is a schematic diagram of an embodiment of the power module provided by this application.
  • Figure 22 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops;
  • FIG. 23 is a schematic diagram of an embodiment of the power module provided by this application.
  • Figure 24 is a schematic diagram of the control signals of the controller provided by this application in a scenario where the load level of the power module drops;
  • FIG. 25 is a schematic diagram of the control signals of the controller provided by the embodiment of the present application.
  • Figure 26 is a schematic diagram of an embodiment of the controller provided by the present application controlling the discharge of the clamp capacitor of the ACF conversion circuit;
  • Figure 27 is a schematic diagram of changes in capacitance voltage of the clamp capacitor of the ACF conversion circuit provided by this application.
  • Figure 28 is a schematic diagram of another embodiment of the controller provided by the present application controlling the discharge of the clamp capacitor of the ACF conversion circuit.
  • FIG. 1 is a schematic diagram of an electronic device provided by this application.
  • the electronic device 10 includes a power module 11 and a load 12 .
  • the power module 11 receives the input voltage V 1 provided by the input power supply 13 and provides the output voltage V 2 to power the load 12 .
  • the electronic device 10 may include multiple power modules 11 , and the multiple power modules 11 provide multiple output voltages V 2 to power the load 12 .
  • the electronic device 10 may include multiple loads 12 , and the power module 11 provides multiple output voltages V 2 to respectively power the multiple loads 12 .
  • the electronic device 10 may include multiple loads 12 and multiple power modules 11 , and the multiple power modules 11 may respectively supply power to the multiple loads 12 .
  • the electronic device 10 may receive output voltages V 1 from multiple input power supplies 13 .
  • electronic device 10 may include one or more input power supplies 13 .
  • the electronic device 10 may be an electronic device such as a mobile phone, a computer, a tablet, or a home appliance.
  • the load 12 includes an internal circuit of the electronic device 10 or an external electronic device of the electronic device 10 .
  • FIG. 2 is another schematic diagram of an electronic device provided by this application.
  • the electronic device 10 includes a power module 11 .
  • the power module 11 receives the input voltage V 1 provided by the input power supply 13 and provides the output voltage V 2 to power the load 12 .
  • the electronic device 10 includes multiple power modules 11 , and the multiple power modules 11 can provide multiple output voltages V 2 to power the load 12 .
  • the power module 11 in the electronic device 10 can provide multiple output voltages V 2 to power multiple loads 12 respectively.
  • the electronic device 10 may include multiple power modules 11 , and the multiple power modules 11 respectively provide output voltages V 2 for multiple loads 12 .
  • electronic device 10 may receive multiple input power supplies 13 .
  • electronic device 10 may include input power source 13 .
  • the electronic device 10 may be an adapter, a charging pile, or other equipment.
  • an adapter can also be called a charger, a charging head, a switching power supply, a power converter, etc.
  • the load 12 may be an electronic device such as a mobile phone, a computer, a tablet, or a home appliance.
  • load 12 may be other internal circuitry of electronic device 10 .
  • FIG. 3 is a schematic diagram of a power module provided by an embodiment of the present application.
  • the power module 11 includes a direct current (DC) conversion circuit 111 , an auxiliary winding circuit 112 , a power circuit 113 and a controller 114 .
  • the DC conversion circuit 111 is used to receive the input voltage V 1 provided by the input power supply 13 and provide the output voltage V 2 to the load 12 .
  • the DC conversion circuit 111 supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112 .
  • the auxiliary winding circuit 112 is coupled with the DC conversion circuit 111 to generate the auxiliary winding voltage V 3 on the auxiliary winding.
  • the auxiliary winding circuit 112 converts the auxiliary winding voltage V 3 into the output voltage V 4 and provides the output voltage V 4 to the power supply circuit 113 .
  • the power supply circuit 113 converts the output voltage V 4 of the auxiliary winding circuit 112 into the output voltage V 5 and provides the output voltage V 5 to the control circuit 114 .
  • the controller 114 is used to control the DC conversion circuit 111.
  • the DC conversion circuit 111 may include an asymmetrical half-bridge (AHB) conversion circuit or an active clamp flyback (ACF) conversion circuit.
  • FIG. 4 is a schematic diagram of a power module.
  • the power module 11 includes a DC conversion circuit 111 , an auxiliary winding circuit 112 , a power circuit 113 and a controller 114 .
  • the DC conversion circuit 111 may include a half-bridge circuit 1110, a transformer 1112, and a rectifier circuit 1114.
  • the transformer 1112 includes a primary winding 1111 and a secondary winding 1113.
  • the transformer 1112 also includes an auxiliary winding 1121 in the auxiliary winding circuit 112 .
  • the secondary winding 1113 is coupled to the primary winding 1111, and the auxiliary winding 1121 is coupled to the primary winding 1111.
  • the half-bridge circuit 1110 is used to receive the input voltage V 1 provided by the input power supply 13 and provide the output voltage V 10 according to the control signal of the controller 114 .
  • the input voltage V 1 and the output voltage V 10 may be in a voltage range.
  • the half-bridge circuit 1110 usually includes a main power transistor, an auxiliary power transistor and a capacitor.
  • the DC conversion circuit 111 includes an AHB conversion circuit and an ACF conversion circuit.
  • the capacitor in the half-bridge circuit 1110 of the AHB conversion circuit is the resonant capacitor C r .
  • the capacitor in the half-bridge circuit 1110 of the ACF conversion circuit is the clamping capacitor C c .
  • the primary winding 1111 of the transformer 1112 is used to receive the output voltage V 10 of the half-bridge circuit 1110 and generate the primary winding voltage V 11 on the primary winding 1111 .
  • the secondary winding 1113 of the transformer 1112 is coupled with the primary winding 1111 of the transformer 1112, and the secondary winding voltage V 12 is generated on the secondary winding 1113.
  • the winding voltage V 11 and the secondary winding voltage V 12 may be in a voltage range.
  • the rectifier circuit 1114 is used to receive the secondary winding voltage V 12 generated on the secondary winding 1113 and convert it into an output voltage V 2 .
  • the output voltage V 2 can be a voltage range.
  • the auxiliary winding circuit 112 is used to supply power to the power supply circuit 113 .
  • the auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled with the primary winding 1111 of the transformer 1112 .
  • the primary winding voltage V 11 on the primary winding 1112 is coupled to generate the auxiliary winding voltage V 3 on the auxiliary winding 1121 .
  • the output voltage V 4 is provided to the power supply circuit 113 .
  • the auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifier module 1122.
  • the auxiliary winding voltage V3 and the output voltage V4 can be in a voltage range.
  • the power circuit 113 is used to power the controller 114 .
  • the power supply circuit 113 receives the output voltage V 4 of the auxiliary winding circuit 112 and provides the output voltage V 5 to the controller 114 .
  • the power circuit 113 may include a voltage stabilizing circuit.
  • the output voltage V 5 can be a voltage range.
  • the controller 114 is used to control the operating state of the DC conversion circuit 111.
  • the controller 114 may send the control signal G to the half-bridge circuit 1110 of the DC conversion circuit 111, thereby controlling the operating state of the DC conversion circuit 111.
  • the operating status of the DC changing circuit 111 usually includes a continuous working status and a suspended working status.
  • the continuous working state can also be called the normal working state, the controller's normal wave sending state, etc.
  • the suspended working state can also be called intermittent working state, BURST working state, intermittent wave sending state of the controller, etc.
  • the controller 114 needs to adjust the operating state of the DC conversion circuit 111 to reduce the output voltage V 2 of the DC conversion circuit 111 to prevent the output voltage V 2 of the power module 11 from being too high and damaging the load 12 .
  • FIG. 5 is a schematic diagram of the voltage waveform of the power module of FIG. 4 in a scenario where the load level drops.
  • the impact of the drop of the load level L of the load 12 on the existing controller 114 and the power module 11 in which it is located will be described in detail below with reference to the power module 11 shown in FIG. 4 .
  • the load level L of the load 12 is the normal load L 1 .
  • the controller 114 controls the DC conversion circuit 111 to be in a continuous operating state, and the voltage value of the output voltage V 2 of the DC conversion circuit 111 is the rated output voltage V 20 .
  • the rated output voltage V 20 is the rated output voltage of the DC conversion circuit 111 in a continuous operating state.
  • the rated output voltage V 20 can be a voltage range.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is V 40 .
  • the voltage value V 40 is the rated input voltage of the auxiliary winding circuit 112 .
  • the voltage value V 40 may be a voltage range in which the output voltage V 5 of the power supply circuit 113 has a voltage value V 50 .
  • the voltage value V 50 is the rated input voltage of the controller 114 .
  • the voltage value V 50 may be a voltage range.
  • the load level L of load 12 drops from normal load L 1 to light load L 2 .
  • the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state. Furthermore, the controller 114 reduces the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1111, so that the voltage value of the primary winding voltage V 11 of the primary winding 1111 decreases. Correspondingly, the voltage value of the secondary winding voltage V 13 decreases, which can reduce the voltage value of the output voltage V 2 of the DC conversion circuit 111 .
  • the voltage value of the auxiliary winding voltage V3 decreases.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 usually cannot effectively reduce the output voltage of the DC conversion circuit 111 only by reducing the conduction frequency or conduction time of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1111. The voltage value of V2 . As a result, after time t 1 , the voltage value of the output voltage V 2 of the DC conversion circuit 111 will continue to increase.
  • the voltage value of the output voltage V 2 of the DC conversion circuit 111 increases to a value greater than or equal to the first preset value V 21 . If the voltage value of the output voltage V 2 of the conversion circuit 111 is too high, the load 12 will be damaged. In order to prevent the voltage value of the output voltage V 2 of the DC conversion circuit 111 from continuing to increase, the controller 114 needs to control the DC conversion circuit 111 to operate in a suspended operating state.
  • the voltage value V 21 is recorded as the first preset value, and the voltage value V 21 is the maximum output voltage of the DC conversion circuit 111 .
  • the voltage value V 21 is smaller than the rated output voltage V 20 of the DC conversion circuit 111 and is smaller than the overvoltage protection voltage of the DC conversion circuit 111 .
  • the DC conversion circuit 111 After time t 2 , the DC conversion circuit 111 is in a suspended operating state, causing the primary winding voltage V 11 of the primary winding circuit 1111 in the DC conversion circuit 111 to decrease. Accordingly, the voltage value of the output voltage V 2 of the DC conversion circuit 111 decreases. Since the auxiliary winding 1121 is coupled to the primary winding 1111, the primary winding voltage V 11 of the primary winding 1111 decreases, which causes the voltage value of the auxiliary winding voltage V 3 of the auxiliary winding 1121 to decrease. Correspondingly, the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 will restart due to low-voltage protection.
  • the voltage value V 51 is the under-voltage protection voltage of the controller 114 . It takes a period of time for the controller 114 to complete the restart process, which results in the controller 14 being unable to control the operating status of the DC transformer circuit 111 during this period, thereby affecting the stability of the power module 11 and the electronic device 10 where the controller 114 is located.
  • the voltage value of the output voltage V 5 of the power supply circuit 113 drops to less than or equal to the third preset value V 52 .
  • the third preset value V 52 is greater than the under-voltage protection voltage V 51 of the controller 114 and less than the rated input voltage V 50 of the controller 114 .
  • the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state.
  • the voltage value of the primary winding voltage V 11 increases. An increase in the voltage value of the primary winding voltage V 11 can lead to an increase in the voltage value of the auxiliary winding voltage V 3 .
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases.
  • the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • an increase in the voltage value of the primary winding voltage V 11 will also cause an increase in the voltage value of the secondary winding voltage V 12 , thereby increasing the voltage value of the output voltage V 2 of the DC conversion circuit 111 .
  • the controller 114 needs to control the DC conversion circuit 111 to operate in a suspended working state.
  • the DC conversion circuit 111 operates in a suspended state, which can cause the voltage value of the primary winding voltage V 11 to decrease. Accordingly, the voltage value of the output voltage V 2 of the DC conversion circuit 111 decreases.
  • a drop in the voltage value of the primary winding voltage V 11 will also cause a drop in the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 . Accordingly, the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 needs to control the DC conversion circuit 111 to operate in a continuous working state.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases.
  • the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the DC conversion circuit 111 operates in a continuous operating state, which will increase the voltage value of the output voltage V 2 of the DC conversion circuit 111 .
  • the controller 114 in the existing power module 11 can avoid restarting due to under-voltage protection, it will also cause the output voltage V 2 of the DC conversion circuit 111 to have a large ripple. Therefore, the existing controller 114 and the power module 11 in which it is located will cause the output voltage V 2 of the DC conversion circuit 111 to have a large ripple, thus affecting the stability of the power module 11 .
  • FIG. 6 is a schematic diagram of another existing controller and its power module.
  • the auxiliary winding circuit 112 in the power module 11 is connected to the input power supply 13 through the switch K.
  • the controller 114 controls the DC conversion circuit 111 to run in a suspended operating state, and the controller 114 controls the switch K to turn on.
  • the input power supply 13 supplies power to the power circuit 113 through the switch K and the auxiliary winding circuit 112, thereby preventing the controller 114 from restarting due to under-voltage protection.
  • the noise of the input power supply 13 will also be transmitted to the inside of the power module 11 through the switch K, affecting the electromagnetic compatibility (EMC) of the power module 11 .
  • EMC electromagnetic compatibility
  • This application provides a controller of a DC conversion circuit and its power module and electronic equipment, which can solve the stability and electromagnetic compatibility problems of the controller, its power module and electronic equipment in the prior art. Defects such as increased output voltage ripple.
  • FIG. 7 is a schematic diagram of a power module provided by an embodiment of the present application.
  • the power module 11 shown in FIG. 7 can be applied in the electronic device 10 shown in FIG. 1 or 2 .
  • the power module 11 includes a DC conversion circuit 111 , an auxiliary winding circuit 112 , a power circuit 113 and a controller 114 .
  • the DC conversion circuit 111 may include a half-bridge circuit 1110, a transformer 1112, and a rectifier circuit 1114.
  • the transformer 1112 includes a primary winding 1111 and a secondary winding 1113.
  • the transformer 1112 also includes an auxiliary winding 1121 in the auxiliary winding circuit 112 .
  • the secondary winding 1113 is coupled to the primary winding 1111, and the auxiliary winding 1121 is coupled to the primary winding 1111.
  • the half-bridge circuit 1110 is used to receive the input voltage V 1 provided by the input power supply 13 and provide the output voltage V 10 to the primary winding 1111 according to the control signal of the controller 114 .
  • the half-bridge circuit 1110 usually includes a main power transistor, an auxiliary power transistor and a capacitor.
  • the DC conversion circuit 111 in the embodiment of the present application includes an AHB conversion circuit and an ACF conversion circuit.
  • the DC conversion circuit 111 includes an AHB conversion circuit
  • the capacitor in the half-bridge circuit 1110 is a resonant capacitor C r .
  • the DC conversion circuit 111 includes an ACF conversion circuit, and the capacitor in the half-bridge circuit 1110 is a clamping capacitor C c .
  • the main power transistor and the auxiliary power transistor are Metal-Oxide-Semiconductor Field-Effect Transistor (MOS).
  • MOS Metal-Oxide-Semiconductor Field-Effect Transistor
  • the main power transistor and the auxiliary power transistor may also be triodes or other types of transistors such as insulated gate bipolar transistors (IGBTs).
  • the primary winding 1111 of the transformer 1112 is used to receive the output voltage V 10 of the half-bridge circuit 1110 and generate the primary winding voltage V 11 .
  • the secondary winding 1113 of the transformer 1112 is coupled with the primary winding 1111 of the transformer 1112, and the secondary winding voltage V 3 is generated on the secondary winding 1113.
  • the rectifier circuit 1114 is used to receive the secondary winding voltage V 3 on the secondary winding 1113 and convert it into an output voltage V 2 .
  • the auxiliary winding circuit 112 is used to supply power to the power supply circuit 113 .
  • the auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled with the primary winding 1111 of the transformer 1112 .
  • the primary winding voltage V 11 on the primary winding 1112 is coupled to generate the auxiliary winding voltage V 3 on the auxiliary winding 1121 .
  • the output voltage V 4 is provided to the power supply circuit 113 .
  • the auxiliary winding circuit 112 includes an auxiliary winding 1121 and a rectifier module 1122.
  • the power circuit 113 is used to power the controller 114 .
  • the power supply circuit 113 receives the output voltage V 4 of the auxiliary winding circuit 112 and provides the output voltage V 5 to the controller 114 . That is, the DC conversion circuit 111 supplies power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 coupled with the primary winding 1111 of its transformer 1112 .
  • power circuit 113 includes a voltage stabilizing circuit.
  • the controller 114 is used to control the operating state of the DC conversion circuit 111.
  • the controller 114 is also used to detect the output voltage V 2 of the DC conversion circuit 111 , the output voltage V 4 of the winding circuit 112 , the output voltage V 5 of the power supply circuit 113 or the capacitance voltage V c of the capacitor in the half-bridge circuit 1110 and other voltages. value changes.
  • the controller 114 is also used to control the operating state of the DC conversion circuit 111 according to changes in the one or more voltage values.
  • the control 114 controls the operating state of the DC conversion circuit 111 by controlling the operating state of the half-bridge circuit 1110 in the DC conversion circuit 111 .
  • the controller 114 can control the on and off of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110, thereby controlling the operating status of the half-bridge circuit 1110.
  • the controller 114 can adjust the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110, and accordingly adjust the output voltage V 10 of the half-bridge circuit 1110.
  • changes in the output voltage V 10 of the half-bridge circuit 1110 will cause changes in the primary winding voltage V 11 .
  • changes in the primary winding voltage V 11 can cause changes in the secondary winding voltage V 12 and the auxiliary winding voltage V 3 .
  • changes in the secondary winding voltage V 12 may cause the output voltage V 2 of the DC conversion circuit 111 to change.
  • changes in the auxiliary winding voltage V 3 may cause the output voltage V 4 of the auxiliary winding circuit 112 to change.
  • the output voltage V 4 of the auxiliary winding circuit 112 may cause a change in the output voltage V 5 of the power supply circuit 113 .
  • the DC conversion circuit 111 can provide the output voltage V 2 to power the load 12 .
  • the input voltage V 1 is converted into the output voltage V 2 through the half-bridge circuit 1110, the primary winding 1111, the secondary winding 1113 and the rectifier circuit 1114 of the DC conversion circuit 111.
  • the DC conversion circuit 111 can supply power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 .
  • the primary winding voltage V 11 can be generated in the primary winding 1111 .
  • the primary winding voltage V 11 can generate an auxiliary winding voltage V 3 on the auxiliary winding 1121 of the transformer 1112 .
  • the auxiliary winding voltage V 3 is processed by the auxiliary winding circuit 1121 to provide an output voltage V 4 to power the power supply circuit 113 of the controller 114 .
  • Figure 8 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops. The following describes the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops, with reference to FIGS. 7 and 8 .
  • the load level L of the load 12 is the normal load L 1 .
  • the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state.
  • the controller 114 controls the output voltage V 2 of the DC conversion circuit 111 to be at the rated voltage value.
  • Output voltage V 20 The voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is V 40 .
  • the voltage value of the output voltage V 5 of the power supply circuit 113 is V 50 .
  • the voltage value of the capacitor voltage V c of the capacitor in the half-bridge circuit 1111 is V C1 .
  • V C1 is the capacitance voltage of the capacitor when the DC conversion circuit 111 operates in a continuous operating state.
  • the load level L of load 12 drops from normal load L 1 to light load L 2 .
  • the voltage value of the output voltage V 2 of the DC conversion circuit 111 will increase to be greater than the rated output voltage V 20 .
  • the controller 114 can control the DC conversion circuit 111 to operate in a continuous operating state. Furthermore, the controller 114 controls the DC conversion circuit 111 to reduce the voltage value of the output voltage V 2 . That is, the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V 2 of the DC conversion circuit 111 and the rated output voltage V 20 . The controller 114 controls the DC conversion circuit 111 Reduce the voltage value of the output voltage V2 .
  • the controller 114 sends the control signal G to control the operating status of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110, so that the voltage value of the primary winding voltage V 11 decreases.
  • the controller 114 can reduce the sending frequency of the control signal G, thereby reducing the conduction frequency of the main power transistor and the auxiliary power transistor.
  • the controller 114 can reduce the duty cycle of the control signal G, thereby reducing the conduction time of the main power transistor and the auxiliary power transistor.
  • the controller 114 can control the DC conversion circuit 111 to operate in a suspended state, and can also reduce the output voltage V 2 voltage value.
  • the above two embodiments may not be able to effectively reduce the voltage value of the output voltage V 2 of the DC conversion circuit 111 , and the voltage value of the output voltage V 2 of the DC conversion circuit 111 will continue to increase after time t 1 .
  • the drop of the load level L causes the voltage value of the output voltage V 2 of the DC conversion circuit 111 to be higher than the rated output voltage V 20 .
  • the primary winding voltage V 11 charges the capacitor in the half-bridge circuit 1110 , and the voltage value of the capacitor voltage V c of the capacitor in the half-bridge circuit 1110 increases from VC1 to VC2 .
  • V C2 is the maximum charging voltage of the capacitor in the half-bridge circuit 1110.
  • the controller 114 determines that the voltage value of the output voltage V 2 of the DC conversion circuit 111 is greater than or equal to the first preset value V 21 , and the controller 114 controls the DC conversion circuit 111 to suspend operation. That is, the controller 114 controls the DC conversion circuit 111 to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V 2 of the DC conversion circuit 111 and the first preset value V 21 . Specifically, the controller 114 controls both the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110 to turn off.
  • the first preset value V 21 may be the peak voltage of the DC conversion circuit 111 .
  • the peak voltage of the DC conversion circuit 111 is greater than the rated output voltage V 20 and less than the overvoltage protection voltage of the DC conversion circuit 111 .
  • the controller 114 controls the DC conversion circuit 111 to operate in a suspended working state.
  • the voltage value of the output voltage V 10 of the half-bridge circuit 1110 decreases, causing the voltage value of the primary winding voltage V 11 on the primary winding 1111 to decrease.
  • the voltage value of the primary winding voltage V 11 on the primary winding 1111 decreases, which will cause the secondary winding voltage V 12 on the secondary winding 1113 to decrease.
  • the voltage value of the output voltage V 2 of the DC conversion circuit 111 decreases.
  • the voltage value of the primary winding voltage V 11 on the primary winding 1111 decreases, which will cause the voltage value of the auxiliary winding voltage V 3 to decrease.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the voltage value of the output voltage V4 of the auxiliary winding circuit 112 drops to less than or equal to the second preset value V41 , or the voltage value of the output voltage V5 of the power supply circuit 113 drops to less than Or equal to the third preset value V 52 .
  • the voltage value V 41 is recorded as the second preset value.
  • the voltage value V 41 is greater than the lowest input voltage of the power circuit 113 and less than the rated input voltage V 40 of the power circuit 113 .
  • the voltage value V 52 is recorded as the third preset value.
  • the voltage value V 52 is greater than the under-voltage protection voltage V 51 of the controller 114 and less than the rated input voltage V 50 of the controller 114
  • the controller 114 determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is less than or equal to the second preset value V 41 , and the controller 114 controls the capacitor discharge in the half-bridge circuit 1110 . That is, the controller 114 controls the capacitor discharge in the half-bridge circuit 1110 based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the second preset value V 41 .
  • the controller 114 determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is less than or equal to the third preset value V 52 , and the controller 114 controls the capacitor discharge in the half-bridge circuit 1110 . That is, the controller 114 controls the capacitor discharge in the half-bridge circuit 1110 based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the third preset value V 52 .
  • the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110 to be turned on, so that the capacitor of the half-bridge circuit 1110 is discharged.
  • the auxiliary power tube in the half-bridge circuit 1110 is turned on, the primary winding 1111 and the capacitor and auxiliary power tube of the half-bridge circuit 1110 can form a discharge circuit.
  • the capacitor in the half-bridge circuit 1110 is discharged, generating a primary winding voltage V 11 on the primary winding 1111 .
  • the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110 to be turned on periodically, so that the capacitor of the half-bridge circuit 1110 is discharged.
  • the auxiliary power in the half-bridge circuit 1110 is turned on, the primary winding 1111, the capacitor of the half-bridge circuit 1110, and the auxiliary power tube of the half-bridge circuit 1110 can form a discharge loop.
  • the auxiliary power transistor is periodically turned on, which can cause the capacitor in the half-bridge circuit 1110 to be periodically discharged.
  • the DC conversion circuit 111 includes an AHB conversion circuit, and the controller 114 controls the discharge of the resonant capacitor in the half-bridge circuit 1110 of the AHB conversion circuit.
  • the DC conversion circuit 111 includes an ACF conversion circuit, and the controller 114 controls the discharge of the clamp capacitor in the half-bridge circuit 1110 of the ACF conversion circuit.
  • the half-bridge circuit 1110 of the DC conversion circuit 111 may include multiple capacitors, and the controller 114 controls the discharge of the multiple capacitors in the half-bridge circuit 1110.
  • the voltage value of the capacitance voltage Vc of the capacitor in the half-bridge circuit 1110 decreases.
  • the capacitor in the half-bridge circuit 1110 is discharged, causing the voltage value of the primary winding voltage V 11 on the primary winding 1111 to increase.
  • an increase in the voltage value of the primary winding voltage V 11 will cause an increase in the voltage value of the auxiliary winding voltage V 3 .
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the voltage value of the output voltage V 5 of the power circuit 113 will not drop below the under-voltage protection voltage V 51 of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.
  • the controller 114 provided in the embodiment of the present application controls the discharge of the capacitor in the primary winding circuit 1111 of the DC conversion circuit 111, so that the voltage value of the output voltage V 5 of the power supply circuit 113 is higher than the preset value of the low-voltage protection of the controller 114.
  • the voltage value V 51 thus prevents the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the controller 114 controls the capacitor in the half-bridge circuit 1110 to discharge, the primary winding voltage V 11 generated on the primary winding 1111 is only used to increase the output voltage V 4 of the auxiliary winding circuit 112 and the output voltage V 5 of the power circuit 113 , as shown in the F2 direction in Figure 7.
  • the controller 114 and the power module 111 in which it is located can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V 2 of the DC conversion circuit 111. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.
  • the controller 114 provided in the embodiment of the present application controls the discharge of the capacitor in the DC conversion circuit 111 without introducing noise from the input power supply 13, and can prevent the noise from affecting the DC conversion circuit 111, the power module 11 where it is located, and the electronics. Electromagnetic compatibility of device 10. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the controller 114 can also determine the value of the capacitance voltage V c of the capacitor in the half-bridge circuit 1110 and the auxiliary winding circuit.
  • the voltage value of the output voltage V 4 of the power supply circuit 112 or the voltage value of the output voltage V 5 of the power supply circuit 113 controls the capacitor in the half-bridge circuit 1110 to stop discharging.
  • the controller 114 controls the auxiliary power transistor of the half-bridge circuit 1110 to turn off, and the discharge loop formed by the primary winding 1111, the capacitor of the half-bridge circuit 1110, and the auxiliary power transistor is disconnected. Accordingly, the capacitor in the half-bridge circuit 1110 stops discharging.
  • the DC conversion circuit 111 includes an AHB conversion circuit, and the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110 to stop discharging.
  • the DC conversion circuit 111 includes an ACF conversion circuit, and the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110 to stop discharging.
  • the half-bridge circuit 1110 of the DC conversion circuit 111 may further include multiple capacitors, and the controller 114 controls the multiple capacitors in the half-bridge circuit 1110 to stop discharging.
  • the capacitance voltage V c of the capacitor in the half-bridge circuit 1110 drops to less than or equal to the preset capacitance voltage value V C3 .
  • the controller 114 determines that the capacitor voltage V c of the capacitor in the half-bridge circuit 1110 drops to less than or equal to the preset capacitor voltage value V C3 , and the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging.
  • the preset capacitor voltage value V C3 may be greater than or equal to the voltage value V C1 of the capacitor voltage of the capacitor in the half-bridge circuit 1110 when the DC conversion circuit 111 operates in the continuous operating state.
  • the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging based on the comparison result between the capacitance voltage V c of the capacitor in the half-bridge circuit 1110 and the preset capacitor voltage value V C3 . Therefore, the controller 114 can control the capacitor in the half-bridge circuit 1110 to stop discharging, thereby preventing the capacitor voltage from being too low and affecting the DC conversion circuit 111 to resume continuous operation, further improving the stability of the power module 11 and the electronic device 10 in which it is located.
  • the controller 114 determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is greater than or equal to the fourth preset value V 42 , and the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging.
  • the voltage value V 42 is recorded as the fourth preset value, and the voltage value V 42 may be the highest input voltage of the power circuit 113 .
  • the voltage value V 42 is greater than the rated input voltage V 40 of the power circuit 113 and less than the overvoltage protection voltage of the power circuit 113 .
  • the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the fourth preset value V 42 . Therefore, the controller 114 can control the capacitor in the half-bridge circuit 1110 to stop discharging, which can prevent the output voltage V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller 114 and its The stability of the power module 11 and the electronic device 10 where it is located.
  • the voltage value of the output voltage V 5 of the power circuit 113 increases to a value greater than or equal to the fifth preset value V 53 .
  • the controller 114 determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is greater than or equal to the fifth preset value V 53 , and the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging.
  • the voltage value V 53 is recorded as the fifth preset value.
  • the voltage value V 53 is greater than the rated input voltage V 50 of the controller 114 and less than the overvoltage protection voltage of the controller 114 .
  • the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the fifth preset value V 53 . Therefore, the controller 114 can control the capacitor in the half-bridge circuit 1110 to stop discharging, thereby preventing the output voltage V4 of the power circuit 113 from being too high and damaging the controller 114, further improving the efficiency of the controller 114 and the power module where it is located. 11. Stability of the electronic device 10.
  • the voltage value of the capacitor voltage Vc stops decreasing.
  • the voltage value of the primary winding voltage V 11 decreases, causing the auxiliary winding voltage V 3 to decrease.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 can control the capacitor of the half-bridge circuit 1110 to discharge again.
  • the specific process is as described in the above embodiment and will not be described again. That is, the controller 114 can control the capacitor of the half-bridge circuit 1110 to discharge again based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the second preset value V 41 .
  • the controller 114 may control the capacitor of the half-bridge circuit 1110 to discharge again based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the third preset value V 52 .
  • the controller 114 will also control the operation of the DC conversion circuit 111 according to the voltage value of the output voltage V 2 of the DC conversion circuit 111 The status switches from suspended working status to continuous working status. After time t 2 , the controller 114 controls the DC conversion circuit 111 to operate in a suspended operating state, and accordingly the voltage value of the output voltage V 2 of the DC conversion circuit 111 decreases.
  • the controller 114 controls the DC The operating state of the conversion circuit 111 switches from the suspended operating state to the continuous operating state. In one embodiment, after the capacitor in the half-bridge circuit 1110 stops discharging and the voltage value of the output voltage V 2 of the DC conversion circuit 111 drops to less than or equal to the rated voltage V 20 , the controller 114 controls the DC conversion circuit 111 The running state switches from the suspended working state to the continuous working state.
  • the controller 114 determines that the voltage value of the output voltage V 2 of the DC conversion circuit 111 drops to less than or equal to the rated output voltage V 20 , and controls the operating state of the DC conversion circuit 111 to switch from a suspended operating state to a continuous operating state. That is, the controller 114 controls the operation state of the DC conversion circuit 111 to switch from the pause operation state to the continuous operation state based on the comparison result between the voltage value of the output voltage V 2 of the DC conversion circuit 111 and the rated output voltage V 20 .
  • the controller 114 controls the DC conversion circuit 111 to operate in a suspended operating state. After time t5 , the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state. After time t 5 , the voltage value of the output voltage V 2 of the DC conversion circuit 111 increases to the rated output voltage V 20 , the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases to V 40 , and the output voltage V of the power supply circuit 113 The voltage value of 5 is increased to V 50 .
  • the controller 114 can stop discharging before the capacitor voltage value of the capacitor in the half-bridge circuit 1110 drops to less than V C1 , so that the operating state of the DC conversion circuit 111 can be changed from the paused state more quickly.
  • the working state is switched to a continuous working state, so the control 114 provided by the embodiment of the present application can improve the performance of the power module 11 and the electronic device 10 where it is located.
  • FIG. 9 is a schematic diagram of an embodiment of the power module provided by this application.
  • the power module 11 shown in FIG. 9 can be applied to the electronic device 10 shown in FIG. 1 or 2 .
  • the power supply module 11 shown in FIG. 9 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power supply circuit 113 and a controller 114.
  • the AHB conversion circuit 111a is used to receive the input voltage V 1 of the input power supply 13 and provide the output voltage V 2 to power the load 12 .
  • the AHB conversion circuit 111a supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112.
  • the auxiliary winding circuit 112 is coupled with the AHB conversion circuit 111a, and the auxiliary winding voltage V 3 is generated on the auxiliary winding 1121.
  • the auxiliary winding circuit 112 converts the auxiliary winding voltage V 3 into an output voltage V 4 to provide power to the power supply circuit 113 .
  • the power circuit 113 supplies power to the control circuit 114 .
  • the controller 114 is used to control the operating state of the AHB conversion circuit 111a.
  • FIG. 10 is a schematic diagram of an embodiment of the power module provided by this application.
  • the power module 11 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power circuit 113 and a controller 114.
  • the AHB conversion circuit 111a in the power module 11 includes a half-bridge circuit 1110a, a transformer 1112a and a rectifier circuit 1114a.
  • the transformer 1112a includes a primary winding 1111a and a secondary winding 1113a.
  • the transformer 1112a also includes an auxiliary winding 1121 in the auxiliary winding circuit 112.
  • the secondary winding 1113a is coupled to the primary winding 1111a
  • the auxiliary winding 1121 is coupled to the primary winding 1111a.
  • the half-bridge circuit 1110a is used to receive the input voltage V 1 provided by the input power supply 13 and provide the output voltage V 10 to the primary winding 1111a according to the control signal of the controller 114 .
  • the half-bridge circuit 1110a usually includes a main power transistor, an auxiliary power transistor and a resonant capacitor.
  • the primary winding 1111a of the transformer 1112a is used to receive the output voltage V 10 of the half-bridge circuit 1110a and generate the primary winding voltage V 11 .
  • the secondary winding 1113a of the transformer 1112a is coupled with the primary winding 1111a of the transformer 1112a, and the secondary winding voltage V 3 is generated on the secondary winding 1113a.
  • the rectifier circuit 1114a is used to receive the secondary winding voltage V 3 on the secondary winding 1113a and convert it into the output voltage V 2 .
  • the auxiliary winding circuit 112 is used to supply power to the power supply circuit 113 .
  • the auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111a of the transformer 1112a.
  • the primary winding voltage V 11 on the primary winding 1112a is coupled to generate the auxiliary winding voltage V 3 on the auxiliary winding 1121.
  • the output voltage V 4 is provided to the power supply circuit 113 .
  • the auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifier module 1122.
  • the power circuit 113 is used to power the controller 114 .
  • the power supply circuit 113 receives the output voltage V 4 of the auxiliary winding circuit 112 and provides the output voltage V 5 to the controller 114 . That is, the AHB conversion circuit 111a supplies power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 coupled with the primary winding 1111 of its transformer 1112a.
  • power circuit 113 includes a voltage stabilizing circuit.
  • the controller 114 is used to control the operating state of the AHB conversion circuit 111a.
  • the controller 114 is also used to detect the output voltage V 2 of the AHB conversion circuit 111a, the output voltage V 4 of the auxiliary winding circuit 112, the output voltage V 5 of the power supply circuit 113, or the capacitance voltage V Cr of the resonant capacitor C r in the half-bridge circuit 1110a. voltage value and other changes in multiple voltage values.
  • the controller 114 is also used to control the operating state of the AHB conversion circuit 111a according to changes in the one or more voltage values.
  • the control 114 sends the control signal G to control the operating state of the half-bridge circuit 1110a in the AHB conversion circuit 111a, thereby controlling the operating state of the AHB conversion circuit 111a.
  • the operating state of the AHB conversion circuit 111a usually includes a continuous operating state and a suspended operating state.
  • the continuous working state can also be called the normal working state, the controller's normal wave sending state, etc.
  • the suspended working state can also be called intermittent working state, BURST working state, intermittent wave sending state of the controller, etc.
  • the controller 114 may send a control signal G to control the turn-on and turn-off of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a.
  • the controller 114 adjusts the frequency or duty cycle of the control signal G to control the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a, thereby adjusting the output voltage V 10 of the half-bridge circuit 1110a accordingly.
  • the output voltage V 10 of the half-bridge circuit 1110a will cause the primary winding voltage V 11 to change.
  • changes in the primary winding voltage V 11 can cause changes in the secondary winding voltage V 12 and the auxiliary winding voltage V 3 .
  • changes in the secondary winding voltage V 12 may cause the output voltage V 2 of the AHB conversion circuit 111a to change.
  • changes in the auxiliary winding voltage V 3 may cause the output voltage V 4 of the auxiliary winding circuit 112 to change.
  • the output voltage V 4 of the auxiliary winding circuit 112 may cause a change in the output voltage V 5 of the power supply circuit 113 .
  • the AHB conversion circuit 111a can provide the output voltage V2 to power the load 12.
  • the input voltage V 1 is converted into the output voltage V 2 through the half-bridge circuit 1110a, the primary winding 1111a, the secondary winding 1113a and the rectifier circuit 1114a in the AHB conversion circuit 111a.
  • the AHB conversion circuit 111a can supply power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 .
  • the primary winding voltage V 11 can be generated in the primary winding 1111a.
  • the primary winding voltage V 11 can generate an auxiliary winding voltage V 3 on the auxiliary winding 1121 of the transformer 1112a.
  • the auxiliary winding voltage V 3 is processed by the auxiliary winding circuit 1121 to provide an output voltage V 4 to power the power supply circuit 113 of the controller 114 .
  • Figure 11 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops. The following describes in detail the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops, with reference to FIGS. 10 and 11 .
  • the load level L of the load 12 is the normal load L 1 .
  • the controller 114 controls the AHB conversion circuit 111a to run in a continuous operating state.
  • the controller 114 controls the output voltage V 2 of the AHB conversion circuit 111a to be the rated voltage value.
  • Output voltage V 20 The voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is V 40 .
  • the voltage value of the output voltage V 5 of the power supply circuit 113 is V 50 .
  • the voltage value of the capacitance voltage V Cr of the resonant capacitor C r in the half-bridge circuit 1111a is V Cr1 .
  • V Cr1 is the capacitance voltage of the resonant capacitor C r when the AHB conversion circuit 111a operates in a continuous operating state.
  • the load level of load 12 drops from normal load L 1 to light load L 2 .
  • the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a increases to greater than the rated output voltage V 20 .
  • the controller 114 can control the AHB conversion circuit 111a to operate in a continuous operating state. Furthermore, the controller controls the AHB conversion circuit 111a to reduce the voltage value of the output voltage V2 . That is, the controller 114 controls the AHB conversion circuit 111a to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V 2 of the AHB conversion circuit 111a and the rated output voltage V 20 . The controller 114 controls the AHB conversion circuit 111a Reduce the voltage value of the output voltage V2 .
  • the controller 114 sends the control signal G to control the operating status of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a, so that the voltage value of the primary winding voltage V 11 decreases.
  • the controller 114 can reduce the sending frequency of the control signal G, thereby reducing the conduction frequency of the main power transistor and the auxiliary power transistor.
  • the controller 114 can reduce the duty cycle of the control signal G, thereby reducing the conduction time of the main power transistor and the auxiliary power transistor.
  • the controller 114 can control the AHB conversion circuit 111a to run in a suspended working state, and can also reduce the output voltage V 2 Voltage value.
  • the above two embodiments may not be able to effectively reduce the voltage value of the output voltage V 2 of the AHB conversion circuit 111a, and the voltage value of the output voltage V2 of the AHB conversion circuit 111a will continue to increase after time t1 .
  • the drop of the load level L causes the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a to be higher than the rated voltage V 20 .
  • the primary winding voltage V 11 charges the resonant capacitor C r in the half-bridge circuit 1110a, and the voltage value of the capacitance voltage V Cr of the resonant capacitor C r in the half-bridge circuit 1110a increases from V Cr1 to V Cr2 .
  • V Cr2 is the maximum charging voltage of the resonant capacitor C r in the half-bridge circuit 1110a.
  • the controller 114 determines that the voltage value of the output voltage V 2 of the AHB conversion circuit 111a is greater than or equal to the first preset value V 21 , and the controller 114 controls the AHB conversion circuit 111a to suspend operation. That is, the controller 114 controls the AHB conversion circuit 111a to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a and the first preset value V 21 . Specifically, the controller 114 controls both the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a to turn off.
  • the first preset value V 21 may be the peak voltage of the AHB conversion circuit 111a.
  • the peak voltage of the AHB conversion circuit 111a is greater than the rated voltage V 20 and less than the overvoltage protection voltage of the AHB conversion circuit 111a.
  • the controller 114 controls the AHB conversion circuit 111a to run in a suspended working state.
  • the voltage value of the primary winding voltage V 11 on the primary winding 1111 a in the AHB conversion circuit 111 a decreases, causing the secondary winding voltage V 12 to decrease, and causing the auxiliary winding voltage V 3 to decrease.
  • the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a decreases, the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110a to discharge.
  • the controller 114 determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is less than or equal to the second preset value V 41 , and the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110a to discharge. That is, the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110a to discharge based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the second preset value V 41 .
  • the controller 114 determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is less than or equal to the third preset value V 52 , and the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110a to discharge. That is, the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110a to discharge based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the third preset value V 52 .
  • the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110a to be turned on, so that the resonant capacitor C r in the half-bridge circuit 1110a is discharged.
  • the primary winding 1111a, the resonant capacitor C r of the half-bridge circuit 1110a, and the auxiliary power transistor of the half-bridge circuit 1110a may form a discharge circuit.
  • the resonant capacitor C r of the half-bridge circuit 1110a is discharged, which can generate the primary winding voltage V 11 on the primary winding 1111a.
  • the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110a to be turned on periodically, so that the resonant capacitor C r in the half-bridge circuit 1110a is discharged.
  • the auxiliary power transistor of the half-bridge circuit 1110a is turned on, the primary winding 1111a, the resonant capacitor C r of the half-bridge circuit 1110a, and the auxiliary power transistor of the half-bridge circuit 1110a can form a discharge loop.
  • the auxiliary power transistor of the half-bridge circuit 1110a is turned on periodically, which can cause the resonant capacitor C r in the half-bridge circuit 1110a to be discharged periodically.
  • the voltage value of the capacitance voltage V Cr of the resonant capacitor Cr in the half-bridge circuit 1110a decreases.
  • the resonant capacitor C r in the half-bridge circuit 1110a is discharged, causing the voltage value of the primary winding voltage V 11 on the primary winding 1111a to increase.
  • an increase in the voltage value of the primary winding voltage V 11 will cause an increase in the voltage value of the auxiliary winding voltage V 3 .
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the voltage value of the output voltage V 5 of the power circuit 113 will not drop below the under-voltage protection voltage V 51 of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.
  • the controller 114 provided in the embodiment of the present application controls the discharge of the resonant capacitor C r in the half-bridge circuit 1110a of the AHB conversion circuit 111a, so that the voltage value of the output voltage V 5 of the power supply circuit 113 is higher than the undervoltage protection voltage of the controller 114 V 51 , thereby preventing the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the voltage value of the primary winding voltage V 11 generated on the primary winding 1111a after discharge is small. At this time, the primary winding voltage V 11 generated on the primary winding 1111a is smaller than the secondary winding voltage V 12 on the secondary winding 1113, which will not cause the output voltage V 2 of the AHB conversion circuit 111a to increase.
  • the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110a to discharge, the primary winding voltage V 11 generated on the primary winding 1111a is only used to increase the output voltage V 4 of the auxiliary winding circuit 112 and the output of the power supply circuit 113 Voltage V 5 , as shown in the F2 direction in Figure 10. Therefore, the controller 114 and the power module 111 provided by the embodiment of the present application can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V 2 of the AHB conversion circuit 111a. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.
  • the controller 114 provided in the embodiment of the present application controls the resonant capacitor C r in the half-bridge circuit 1110a of the AHB conversion circuit 111a without introducing noise from the input power supply 13, and can avoid the noise from affecting the AHB conversion circuit 111a and its location. Electromagnetic compatibility of power module 11 and electronic equipment 10 . Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the controller 114 can also adjust the capacitance voltage V Cr of the resonant capacitor C r in the half-bridge circuit 1110a.
  • the value of the output voltage V 4 of the auxiliary winding circuit 112 or the voltage value of the output voltage V 5 of the power supply circuit 113 controls the resonant capacitor C r in the half-bridge circuit 1110a to stop discharging.
  • the controller 114 controls the auxiliary power tube in the half-bridge circuit 1110a to turn off, and the discharge loop formed by the primary winding 1111a, the resonant capacitor C r of the half-bridge circuit 1110a, and the auxiliary power tube of the half-bridge circuit 1110a is turned off. open.
  • the resonant capacitor C r of the half-bridge circuit 1110a stops discharging.
  • the capacitance voltage V Cr of the resonant capacitor Cr of the half-bridge circuit 1110a drops to less than or equal to the preset capacitance voltage value V Cr3 .
  • the controller 114 determines that the capacitance voltage V Cr of the resonant capacitor C r of the half-bridge circuit 1110a drops to less than or equal to the preset capacitance voltage value V Cr3 , and the controller 114 controls the resonant capacitance C of the half-bridge circuit 1110a rStop discharging.
  • the preset capacitance voltage value V Cr3 may be greater than or equal to the voltage value V Cr1 of the capacitance voltage of the resonant capacitance Cr of the half-bridge circuit 1110a when the AHB conversion circuit 111a operates in the continuous operating state. That is, the controller 114 controls the resonant capacitor Cr of the half-bridge circuit 1110a to stop discharging based on the comparison result between the capacitance voltage V Cr of the resonant capacitor C r of the half-bridge circuit 1110a and the preset capacitor voltage value V Cr3 .
  • the controller 114 can stop discharging through the resonant capacitor C r of the half-bridge circuit 1110a, and can prevent the capacitance voltage V Cr of the resonant capacitor C r from being too low and affecting the restoration of the continuous working state of the AHB conversion circuit 111a, further improving the efficiency of the power module 11 and the stability of the electronic device 10 in which it is located.
  • the controller 114 determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is greater than or equal to the fourth preset value V 42 , and the controller 114 controls the resonant capacitor Cr of the half-bridge circuit 1110a to stop discharging. That is, the controller 114 controls the resonant capacitor C r of the half-bridge circuit 1110a to stop discharging based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the fourth preset value V 42 .
  • the controller 114 can stop discharging through the resonant capacitor C r of the half-bridge circuit 1110a, and can prevent the output voltage V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller 114. and the stability of the power module 11 and the electronic device 10 where it is located.
  • the controller 114 determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is greater than or equal to the fifth preset value V 53 , and the controller 114 controls the resonant capacitor C r of the half-bridge circuit 1110a to stop discharging. That is, the controller 114 controls the resonant capacitor C r of the half-bridge circuit 1110a to stop discharging based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the fifth preset value V 53 .
  • the controller 114 can stop discharging by controlling the resonant capacitor C r of the half-bridge circuit 1110a to prevent the output voltage V4 of the power supply circuit 113 from being too high and damaging the controller 114, further improving the efficiency of the controller 114 and its power supply. Stability of module 11 and electronic device 10.
  • the voltage value of the capacitance voltage V Cr of the resonant capacitor Cr stops decreasing.
  • the voltage value of the primary winding voltage V 11 decreases, causing the auxiliary winding voltage V 3 to decrease.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 may control the resonant capacitor C r of the half-bridge circuit 1110 a to discharge again. The specific process is as described in the above embodiment and will not be described again.
  • the controller 114 can control the resonant capacitor C r of the half-bridge circuit 1110a to discharge again based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the second preset value V 41 .
  • the controller 114 may control the resonant capacitor C r of the half-bridge circuit 1110a to discharge again based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the third preset value V 52 .
  • the controller 114 will also control the AHB conversion circuit 111a according to the voltage value of the output voltage V2 of the AHB conversion circuit 111a.
  • the operating status switches from suspended working status to continuous working status.
  • the controller 114 controls the AHB conversion circuit 111 a to operate in a suspended operating state, and accordingly the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a decreases.
  • the controller 114 controls the AHB conversion circuit The operating status of 111a switches from the suspended working status to the continuous working status.
  • the controller 114 determines that the voltage value of the output voltage V 2 of the AHB conversion circuit 111a drops to less than or equal to the rated voltage V 20 , and controls the operating state of the AHB conversion circuit 111a to switch from the suspended operating state to the continuous operating state. That is, the controller 114 controls the operation state of the AHB conversion circuit 111a to switch from the pause operation state to the continuous operation state based on the comparison result between the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a and the rated voltage V 20 .
  • the voltage value of the output voltage V 2 of the AHB conversion circuit 111a returns to the rated voltage V 20
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 returns to V 40
  • the output voltage V 5 of the power supply circuit 113 The voltage value returns to V 50 .
  • FIG. 12 is a schematic diagram of an embodiment of the power module provided by this application.
  • FIG. 12 shows a schematic diagram of some circuits in the power module 11 shown in FIG. 10 .
  • the power module 11 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power circuit 113 and a controller 114.
  • the AHB conversion circuit 111a includes a half-bridge circuit 1110a, a transformer 1112a and a rectifier circuit 1114a.
  • the transformer 1112a includes a primary winding 1111a and a secondary winding 1113a.
  • the transformer 1112a also includes an auxiliary winding 1121 in the auxiliary winding circuit 112.
  • the secondary winding 1113a is coupled to the primary winding 1111a
  • the auxiliary winding 1121 is coupled to the primary winding 1111a.
  • the half-bridge circuit 1110a includes a main power transistor Q L , an auxiliary power transistor Q H and a resonant capacitor C r .
  • the main power tube QL , the auxiliary power tube QH and the resonant capacitor Cr form an asymmetric half-bridge topology.
  • the first end of the resonant capacitor C r is connected to the opposite end of the primary winding 1111a, and the second end of the resonant capacitor C r is connected to the drain of the auxiliary power tube Q H.
  • the source of the auxiliary power tube QH is connected to the same terminal of the primary winding 1111a and the drain of the main power tube QL .
  • the source of the main power tube Q L is grounded.
  • the gate of the main power transistor Q L is used to receive the second control signal GH from the controller 114 .
  • the gate of the auxiliary power transistor Q H is used to receive the first control signal GL from the controller 114 .
  • the rectifier circuit 1114a includes a capacitor C 1 and a diode D 2 .
  • the anode of diode D 2 is connected to the same terminal of secondary winding 1113a.
  • the two ends of the capacitor C 1 are respectively connected to the cathode of the diode D 2 and the opposite terminal of the secondary winding 1113a.
  • the auxiliary winding circuit 112 includes an auxiliary winding 1121 and a rectifier module 1122.
  • Rectification module 1122 may include diode D 1 .
  • the anode of the diode D 1 is connected to the same terminal of the auxiliary winding 1121
  • the cathode of the diode D 1 and the different terminal of the auxiliary winding 1121 are connected to the power circuit 113 .
  • the power circuit 113 may include a boost circuit.
  • the power circuit 113 may also be a buck (BUCK) circuit, a buck-boost (BUCK-BOOST) circuit, etc.
  • the power circuit 113 may also be a voltage stabilizing circuit such as a low dropout linear voltage regulator circuit (low dropout regulator, LDO).
  • the controller 114 includes a detection unit 1141 and a driving unit 1142.
  • the power circuit 113 may be connected to the power supply pin of the driving unit 1142 .
  • the power supply pin may be the pin labeled " Vdd " shown in Figure 12.
  • the detection unit 1141 is used to detect the output voltage V 2 of the AHB conversion circuit 111a, the voltage value of the output voltage V4 of the auxiliary winding circuit 112, the voltage value of the output voltage V5 of the power supply circuit 113, or the half-bridge circuit 1110a of the AHB conversion circuit 111a. Changes in various voltage values among the voltage values of the capacitor voltage V Cr of the resonant capacitor C r .
  • the driving circuit 1142 is used to control the operating state of the AHB conversion circuit 111a according to the change of one or more voltage values.
  • the detection unit 1141 can detect the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a by connecting point A of the output end of the secondary winding circuit 1114 a in FIG. 12 .
  • the detection unit 1141 can detect the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 by connecting point B of the output end of the auxiliary winding circuit 112 in FIG. 12 .
  • the detection unit 1141 can detect the voltage value of the output voltage V 5 of the power supply circuit 113 by connecting point C of the output end of the power supply circuit 113 in FIG. 12 .
  • the detection unit 1141 can detect the voltage value of the capacitance voltage V Cr of the resonant capacitor C r by connecting points D on either side of the resonant capacitor C r in FIG. 12 .
  • the driving unit 1142 is used to control the operating state of the AHB conversion circuit 111a. Among them, the driving unit 1142 controls the on and off of the main power transistor Q L and the auxiliary power transistor Q H by sending the control signal G L /G H , thereby controlling the operating state of the AHB conversion circuit 111a.
  • the driving unit 1142 shown in FIG. 12 can send the control signal GH through its pin labeled " GH ", and can send the control signal GH through its pin labeled " GL " The pin sends the control signal GL .
  • the pin numbers in Figure 12 are only examples. In actual applications, other numbered pins of the driving unit 1142 can also be used to implement the functions of the pins shown in Figure 12 .
  • the driving unit 1142 controls the main power tube QL to be turned on or off by sending a first control signal GL to the main power tube QL .
  • the driving unit 1142 controls the auxiliary power tube QH to be turned on or off by sending the second control signal GH to the auxiliary power tube QH .
  • the first control signal GL and the second control signal GH sent by the controller 114 may include high-level signals or low-level signals.
  • the main power transistor QL is turned on according to the first control signal GL
  • the auxiliary power transistor QH is turned on according to the second control signal GH .
  • the main power transistor QL is turned off according to the first control signal GL
  • the auxiliary power transistor QH is turned off according to the second control signal GH .
  • Figure 13 is a schematic diagram of the control signals of the controller provided by this application in a scenario where the load level of the power module drops. The following describes the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops.
  • the load level of load 12 is normal load L 1 .
  • the controller 114 controls the AHB conversion circuit 111a to operate in a continuous operating state, and controls the voltage value of the output voltage V 2 of the AHB conversion circuit 111a to be the rated voltage V 20 .
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is V 40 .
  • the voltage value of the output voltage V 5 of the power supply circuit 113 is V 50 .
  • the voltage value of the capacitance voltage V Cr of the resonant capacitor C r in the half-bridge circuit 1111a is V Cr1 .
  • FIG 14 is a schematic diagram of the control signals of the controller provided by the embodiment of the present application.
  • each of the control signals G 1 , G 2 , G 3 ... sent by the controller 114 includes a first control signal GL sent to the main power tube Q L or a first control signal GL sent to the auxiliary power tube Q H Second control signal G H .
  • the controller 114 controls the main power transistor QL and the auxiliary power transistor QH to periodically turn on and off alternately, and the half-bridge circuit 1110a can generate the primary winding voltage V 11 in the primary winding 1111a.
  • the primary winding voltage V 11 on the primary winding 1111a can generate the secondary winding voltage V 12 on the secondary winding 1113a, and can generate the auxiliary winding voltage V 3 on the auxiliary winding 1121.
  • the rectifier circuit 1114a provides the output voltage V 2 to the load 12
  • the auxiliary winding circuit 112 provides the output voltage V 4 to the power supply circuit 113
  • the output voltage V 5 of the power supply circuit 113 to the controller 115 is V 50 .
  • the load level of load 12 drops from normal load L 1 to light load L 2 .
  • the voltage value of the output voltage V2 of the AHB conversion circuit 111a increases to greater than the rated voltage V20 .
  • the controller 114 controls the AHB conversion circuit 111a to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V 2 of the AHB conversion circuit 111a and the rated voltage V 20 .
  • the controller 114 controls the AHB conversion circuit 111a reduces the voltage value of the output voltage V2 .
  • the detection unit 1141 of the controller 114 detects the output voltage V 2 of the AHB conversion circuit 111 a and determines that the output voltage V 2 of the AHB conversion circuit 111 a is greater than the rated voltage V 20 .
  • the controller 114 controls the AHB conversion circuit 111a to operate in a continuous working state.
  • the controller 114 reduces the transmission frequency of the first control signal GL and the second control signal GH , or reduces the transmission frequency of the first control signal GL and the second control signal GH. Duty cycle of signal G H. As shown in FIG.
  • the frequencies of the control signals G 4 , G 5 , and G 6 sent by the controller 114 after time t 1 are smaller than the frequencies of the control signals G 1 , G 2 , and G 3 periodically sent before time t 1 .
  • the frequency at which the main power transistor QL and the auxiliary power transistor QH are turned on and off is reduced, causing the voltage value of the output voltage V2 of the AHB conversion circuit 111a to decrease.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the above method may not effectively reduce the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a, and the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a will continue to increase.
  • the voltage value of the output voltage V 2 of the AHB conversion circuit 111a is higher than the rated voltage V 20 .
  • the primary winding voltage V 11 charges the resonant capacitor C r in the half-bridge circuit 1110a, and the voltage value of the capacitance voltage V Cr of the resonant capacitor C r in the half-bridge circuit 1110a increases from V Cr1 to V Cr2 .
  • the controller 114 controls the AHB conversion circuit 111a to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a and the first preset value V 21 .
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 2 of the AHB conversion circuit 111a and determines that the voltage value of the output voltage V 2 of the AHB conversion circuit 111a is greater than or equal to the first preset value V 21 .
  • the driving unit 1142 of the controller 114 stops sending the first control signal GL and the second control signal GH , thereby controlling the AHB conversion circuit 111a to operate in a suspended working state.
  • the AHB conversion circuit 111a does not process the input voltage V 1 it receives, and the output voltage V 2 of the AHB conversion circuit 111a decreases.
  • the controller 114 controls the AHB conversion circuit 111a to run in a suspended working state.
  • the voltage value of the primary winding voltage V 11 on the primary winding 1111 a in the AHB conversion circuit 111 a decreases, causing the secondary winding voltage V 12 to decrease, and causing the auxiliary winding voltage V 3 to decrease.
  • the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a decreases, the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110a to discharge.
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is less than or equal to the second preset value. V41 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn on the auxiliary power transistor QH .
  • the resonant capacitor C r of the half-bridge circuit 1110a, the primary winding 1111a and the power transistor QH of the half-bridge circuit 1110a form a discharge loop, and the resonant capacitor C r of the half-bridge circuit 1110a begins to discharge.
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 5 of the power supply circuit 113 and determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is less than or equal to the third preset value V 52 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn on the auxiliary power transistor QH .
  • the resonant capacitor C r of the half-bridge circuit 1110a, the primary winding 1111a and the power transistor QH of the half-bridge circuit 1110a form a discharge loop, and the resonant capacitor C r of the half-bridge circuit 1110a begins to discharge.
  • the voltage value of the capacitance voltage V Cr of the resonant capacitor Cr in the half-bridge circuit 1110a decreases.
  • the resonant capacitor C r in the half-bridge circuit 1110a is discharged, causing the voltage value of the primary winding voltage V 11 on the primary winding 1111a to increase.
  • the voltage value of the auxiliary winding voltage V 3 increases, the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the voltage value of the output voltage V 5 of the power circuit 113 will not drop below the under-voltage protection voltage V 51 of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.
  • the controller 114 provided in the embodiment of the present application controls the discharge of the resonant capacitor C r in the half-bridge circuit 1110a of the AHB conversion circuit 111a, so that the voltage value of the output voltage V 5 of the power supply circuit 113 is higher than the undervoltage protection voltage of the controller 114 V 51 , thereby preventing the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the voltage value of the primary winding voltage V 11 generated on the primary winding 1111a after discharge is small. At this time, the primary winding voltage V 11 generated on the primary winding 1111a is smaller than the secondary winding voltage V 12 on the secondary winding 1113, which will not cause the output voltage V 2 of the AHB conversion circuit 111a to increase.
  • the controller 114 controls the resonant capacitor C r in the half-bridge circuit 1110a to discharge, the primary winding voltage V 11 generated on the primary winding 1111a is only used to increase the output voltage V 4 of the auxiliary winding circuit 112 and the output of the power supply circuit 113 Voltage V 5 . Therefore, the controller 114 and the power module 111 provided by the embodiment of the present application can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V 2 of the AHB conversion circuit 111a. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.
  • the controller 114 provided in the embodiment of the present application controls the resonant capacitor C r in the half-bridge circuit 1110a of the AHB conversion circuit 111a, so as not to introduce noise from the input power supply 13 and avoid affecting the AHB conversion circuit 111a and its power supply. Electromagnetic compatibility of module 11 and electronic device 10. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the controller 114 can also control the resonant capacitor C r in the half-bridge circuit 1110a of the AHB conversion circuit 111a to stop discharging.
  • the capacitance voltage V Cr of the resonant capacitor Cr of the half-bridge circuit 1110a drops to less than or equal to the preset capacitance voltage value V Cr3 .
  • the preset capacitance voltage value V Cr3 may be greater than or equal to the voltage value V Cr1 of the capacitance voltage of the resonant capacitance Cr of the half-bridge circuit 1110a when the AHB conversion circuit 111a operates in the continuous operating state.
  • the controller 114 controls the resonant capacitor Cr of the half-bridge circuit 1110a to stop discharging based on the comparison result between the capacitance voltage V Cr of the resonant capacitor C r of the half-bridge circuit 1110a and the preset capacitor voltage value V Cr3 .
  • the detection unit 1141 of the controller 114 detects the capacitance voltage V Cr of the resonant capacitor C r of the half-bridge circuit 1110a and determines that the capacitance voltage V Cr of the resonant capacitor C r of the half-bridge circuit 1110a is less than or equal to the preset capacitance voltage value V Cr3 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn off the auxiliary power transistor QH .
  • the controller 114 can stop discharging through the resonant capacitor C r of the half-bridge circuit 1110a, and can prevent the capacitance voltage V Cr of the resonant capacitor C r from being too low and affecting the restoration of the continuous working state of the AHB conversion circuit 111a, further improving the efficiency of the power module 11 and the stability of the electronic device 10 in which it is located.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases to greater than or equal to the fourth preset value V 42 .
  • the controller 114 controls the resonant capacitor C r of the half-bridge circuit 1110a to stop discharging based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the fourth preset value V 42 .
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is less than or equal to the preset capacitor voltage value V Cr3 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn off the auxiliary power transistor QH .
  • the discharge loop formed by the resonant capacitor C r of the half-bridge circuit 1110a, the primary winding 1111a, and the power transistor QH of the half-bridge circuit 1110a is disconnected, and the resonant capacitor C r of the half-bridge circuit 1110a stops discharging.
  • the controller 114 can stop discharging through the resonant capacitor C r of the half-bridge circuit 1110a, and can prevent the output voltage V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller 114. and the stability of the power module 11 and the electronic device 10 where it is located.
  • the voltage value of the output voltage V 5 of the power circuit 113 is increased to greater than or equal to the fifth preset value V 53 .
  • the controller 114 controls the resonant capacitor C r of the half-bridge circuit 1110a to stop discharging based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the fifth preset value V 53 .
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 5 of the power supply circuit 113 and determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is greater than or equal to the fifth preset value V 53 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn off the auxiliary power transistor QH .
  • the discharge loop formed by the resonant capacitor C r of the half-bridge circuit 1110a, the primary winding 1111a, and the power transistor QH of the half-bridge circuit 1110a is disconnected, and the resonant capacitor C r of the half-bridge circuit 1110a stops discharging.
  • the controller 114 can stop discharging by controlling the resonant capacitor C r of the half-bridge circuit 1110a to prevent the output voltage V4 of the power supply circuit 113 from being too high and damaging the controller 114, further improving the efficiency of the controller 114 and its power supply. Stability of module 11 and electronic device 10.
  • the voltage value of the capacitance voltage V Cr of the resonant capacitor Cr stops decreasing.
  • the voltage value of the primary winding voltage V 11 decreases, causing the auxiliary winding voltage V 3 to decrease.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 may control the resonant capacitor C r of the half-bridge circuit 1110 a to discharge again. The specific process is as described in the above embodiment and will not be described again.
  • the controller 114 will also control the AHB conversion circuit 111a according to the voltage value of the output voltage V2 of the AHB conversion circuit 111a.
  • the operating status switches from suspended working status to continuous working status.
  • the controller 114 controls the AHB conversion circuit 111 a to operate in a suspended operating state, and accordingly the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a decreases.
  • the controller 114 controls the AHB conversion circuit The operating status of 111a switches from the suspended working status to the continuous working status.
  • the voltage value of the output voltage V 2 of the AHB conversion circuit 111a drops to less than or equal to the rated output voltage V 20 .
  • the controller 114 controls the operating state of the AHB converting circuit 111a to switch from the suspended operating state to the continuous operating state based on the comparison result between the voltage value of the output voltage V2 of the AHB converting circuit 111a and the rated output voltage V20 .
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a and determines that the voltage value of the output voltage V 2 of the AHB conversion circuit 111 a is less than or equal to the rated output voltage V 20 .
  • the driving unit 1142 of the controller 114 periodically sends the first control signal GL and the second control signal GH , and controls the main power tube QL and the auxiliary power tube QH to be turned on and off periodically, so that the AHB conversion circuit 111a Restore continuous working status.
  • the first control signal GL and the second control signal GH sent by the controller 114 are recorded as G 7 , G 8 , G 9 . . .
  • the specific implementation of each control signal G 7 , G 8 , G 9 ... is the same as shown in Figure 14 and will not be described again.
  • the voltage value of the output voltage V 2 of the AHB conversion circuit 111a returns to the rated output voltage V 20
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 returns to V 40
  • the output voltage V of the power supply circuit 113 The voltage value of 5 returns to V 50 .
  • Figure 15 is a schematic diagram of an embodiment of the controller provided by the present application controlling the resonant capacitor discharge of the AHB conversion circuit.
  • the difference between Figure 15 and Figure 13 is that the controller 114 controls the resonant capacitor C r of the primary winding circuit 1111a in the AHB conversion circuit 111a to periodically discharge. Description will be given below with reference to Figure 11 and Figure 15 .
  • the controller 114 controls the auxiliary power transistor Q H in the half-bridge circuit 1110a to periodically turn on, so that the resonant capacitor C r in the half-bridge circuit 1110a discharges. Specifically, the controller 114 does not send the first control signal GL to the main power tube QL , so that the main power tube QL is turned off. Furthermore, the controller 114 periodically sends the second control signal GH to the auxiliary power transistor QH , so that the auxiliary power transistor QH is periodically turned on.
  • the auxiliary power transistor QH of the half-bridge circuit 1110a When the auxiliary power transistor QH of the half-bridge circuit 1110a is turned on, the primary winding 1111a, the resonant capacitor C r of the half-bridge circuit 1110a, and the auxiliary power transistor QH of the half-bridge circuit 1110a can form a discharge loop. Correspondingly, the auxiliary power transistor Q H of the half-bridge circuit 1110a is turned on periodically, which can cause the resonant capacitor C r in the half-bridge circuit 1110a to be discharged periodically.
  • the controller 114 controls the period T1 during which the auxiliary power transistor Q H is turned on periodically, which can be pre-configured, or the controller 114 can be based on the capacitance voltage V Cr of the current resonant capacitor C r or the stored value. Electric energy is calculated. In one embodiment, when the voltage value of the capacitance voltage V Cr of the resonant capacitor C r is higher or more electric energy is stored, the period T1 can be set smaller. In an embodiment, the period T1 may also be the same as the period of the control signals G 1 , G 2 , G 3 . . . or G 4 , G 5 , G 6 . . . In the embodiment of the present application, the duration for which the controller 114 controls the auxiliary power transistor Q H to be turned on or off in each cycle may be the same or different.
  • FIG 16 is a schematic diagram of changes in the capacitance voltage of the resonant capacitor of the AHB conversion circuit provided by this application.
  • the resonant capacitor C r is periodically discharged, and the capacitance voltage V Cr of the resonant capacitor C r decreases stepwise from V Cr2 .
  • the capacitance voltage V Cr of the resonant capacitor C r decreases stepwise as the auxiliary power transistor Q H is periodically turned on.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 also shows a step-like increase
  • the voltage value of the output voltage V 5 of the power supply circuit 113 also shows a step-like increase.
  • the controller 114 controls the resonant capacitor C r in the AHB conversion circuit 111 a to discharge periodically, which can cause the capacitance voltage V Cr of the resonant capacitor C r to decrease in a stepwise manner to avoid falling too fast and affecting the operation of the AHB conversion circuit 111 a. Improved the stability of power module 11. Moreover, the controller 114 controls the resonant capacitor C r in the AHB conversion circuit 111a to periodically discharge, which can increase the output voltage V 4 of the auxiliary winding circuit 112 and the output voltage V 5 of the power supply circuit 113 in a stepwise manner, thus preventing the voltage from increasing too quickly. and damage the circuit components, thereby improving the stability of the power module 11.
  • Figure 17 is a schematic diagram of another embodiment of the controller provided by the present application controlling the resonant capacitor discharge of the AHB conversion circuit.
  • the difference between Figure 17 and Figure 15 is that the controller 114 controls the auxiliary power tube Q H and the main power tube Q L in the primary winding circuit 1111a of the AHB conversion circuit 111a to periodically alternately conduct, so that the resonant capacitor C r periodically discharges .
  • the controller 114 periodically controls the main power tube QL and the auxiliary power tube QH to turn on alternately, and controls the auxiliary power tube QH and the main power tube QL to not turn on at the same time. Specifically, the controller 114 periodically sends the second control signal GH to the auxiliary power tube QH and the first control signal GL to the main power tube QL in sequence, so that the auxiliary power tube QH and the main power tube Q L is turned on in sequence, and the auxiliary power tube Q H and the main power tube Q L are not turned on at the same time.
  • the auxiliary power transistor QH of the half-bridge circuit 1110a When the auxiliary power transistor QH of the half-bridge circuit 1110a is turned on, the primary winding 1111a, the resonant capacitor C r of the half-bridge circuit 1110a, and the auxiliary power transistor QH of the half-bridge circuit 1110a can form a discharge loop.
  • the change of the capacitance voltage V Cr of the resonant capacitor C r can be seen in Figure 16.
  • the controller 114 controls the auxiliary power transistor QH to turn on first and the main power transistor QL to turn on later.
  • the controller 114 controls the auxiliary power transistor QH to turn on and the main power transistor QL to turn off. Specifically, the controller 114 sends the second control signal GH to the auxiliary power tube QH and does not send the first control signal GL to the main power tube QL .
  • the resonant capacitor C r , the primary winding a and the auxiliary power tube Q H form a current loop, and the resonant capacitor C r is discharged.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the controller 114 controls the auxiliary power transistor QH to turn off and the main power transistor QL to turn on. Specifically, the controller 114 does not send the second control signal GH to the auxiliary power tube QH and sends the first control signal GL to the main power tube QL .
  • the input voltage V 1 , primary winding a, and main power tube Q L form a loop.
  • the input voltage V 1 generates the primary winding voltage V 11 on both sides of the primary winding a.
  • the primary winding voltage V 11 is coupled through the transformer 1112a to generate the auxiliary winding voltage V 3 on the auxiliary winding c.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the controller 114 controls the resonant capacitor C r of the primary side winding circuit 1111 a in the AHB conversion circuit 111 a to periodically discharge, which can cause the capacitance voltage V Cr of the resonant capacitor C r to decrease in a stepwise manner to avoid falling too fast and affecting the AHB conversion circuit. 111a operation, thus improving the stability of the power module 111. Furthermore, the controller 114 controls the resonant capacitor C r of the primary winding circuit 1111a in the AHB conversion circuit 111a to periodically discharge, which can increase the output voltage V 4 of the auxiliary winding circuit 112 and the output voltage V 5 of the power supply circuit 113 in a stepwise manner. This avoids damage to circuit components due to excessive lifting, thereby improving the stability of the power module 111.
  • the controller 114 in each cycle, can control the main power transistor Q L to turn on first and the auxiliary power transistor Q H to turn on later.
  • the period T2 during which the controller 114 controls the main power transistor Q L and the auxiliary power transistor Q H to periodically conduct alternately may be pre-configured, or may be determined by the controller 114 according to the current resonant capacitance C r The capacitor voltage V Cr or stored electrical energy is calculated. In one embodiment, when the voltage value of the capacitance voltage V Cr of the resonant capacitor C r is higher or more electric energy is stored, the period T2 can be set smaller. In one embodiment, the period T2 may be the same as the period of the control signals G 1 , G 2 , G 3 .
  • the controller 114 controls the conduction time of the main power transistor QL and the conduction time of the auxiliary power transistor QH , which may be the same or different.
  • the duty ratios of the first control signal GL and the second control signal GH sent by the controller 114 may be the same or different.
  • FIG 18 is a schematic diagram of a half-bridge circuit in another AHB conversion circuit provided by this application.
  • the half-bridge circuit 1110a1 includes a main power transistor QL , an auxiliary power transistor QH and a resonant capacitor Cr .
  • the source of the main power tube QL is connected to the opposite end of the primary winding 1111a and the drain of the auxiliary power tube QH .
  • the source of the auxiliary power tube Q H is connected to the first end of the resonant capacitor C r and grounded.
  • the second terminal of the resonant capacitor C r is connected to the same terminal of the primary winding 1111a.
  • the half-bridge circuit 1110a1 shown in Figure 18 can replace the half-bridge circuit 1110a in Figure 12.
  • the functions and control logic of the half-bridge circuit 1110a1 are the same as those of the half-bridge circuit 1110a.
  • FIG 19 is a schematic diagram of a half-bridge circuit in another AHB conversion circuit provided by this application.
  • the half-bridge circuit 1110a2 includes a main power transistor QL , an auxiliary power transistor QH and a resonant capacitor Cr .
  • the same terminal of the primary winding 1111a is connected to the drain of the main power transistor QL and the first terminal of the resonant capacitor C r .
  • the second end of the resonant capacitor C r is connected to the source of the auxiliary power tube Q H.
  • the source of the main power tube Q L is grounded.
  • the drain of the auxiliary power tube Q H is connected to ground.
  • the half-bridge circuit 1110a2 shown in Figure 19 can replace the half-bridge circuit 1110a in Figure 12.
  • the functions and control logic of the half-bridge circuit 1110a2 are the same as those of the half-bridge circuit 1110a.
  • the controller 114 provided in the embodiment of the present application only needs to control the on or off of the main power transistor Q L and the auxiliary power transistor Q H in the AHB conversion circuit 111 a when the load level L of the power module 11 drops. Therefore, the controller 114 provided by the embodiment of the present application can not only improve the stability of the AHB conversion circuit 111a, power module 11, and electronic device 10 where it is located, but also has a simple configuration and is more suitable for use in various products.
  • FIG. 20 is a schematic diagram of an embodiment of a power module provided by this application.
  • the power module 11 shown in FIG. 20 can be applied to the electronic device 10 shown in FIG. 1 or 2 .
  • the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113 and a controller 114.
  • the ACF conversion circuit 111b is used to receive the input voltage V 1 of the input power supply 13 and provide the output voltage V 2 to power the load 12 .
  • the ACF conversion circuit 111b supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112.
  • the auxiliary winding circuit 112 is coupled with the ACF conversion circuit 111b, and the auxiliary winding voltage V 3 is generated on the auxiliary winding 1121.
  • the auxiliary winding circuit 112 converts the auxiliary winding voltage V 3 into an output voltage V 4 to provide power to the power supply circuit 113 .
  • the power circuit 113 supplies power to the control circuit 114 .
  • the controller 114 is used to control the operating state of the ACF conversion circuit 111b.
  • FIG. 21 is a schematic diagram of an embodiment of the power module provided by this application.
  • the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113 and a controller 114.
  • the ACF conversion circuit 111b in the power module 11 includes a half-bridge circuit 1110b, a transformer 1112b and a rectifier circuit 1114b.
  • the transformer 1112b includes a primary winding 1111b and a secondary winding 1113b.
  • the transformer 1112b also includes an auxiliary winding 1121 in the auxiliary winding circuit 112.
  • the secondary winding 1113b is coupled to the primary winding 1111b
  • the auxiliary winding 1121 is coupled to the primary winding 1111b.
  • the half-bridge circuit 1110b is used to receive the input voltage V 1 provided by the input power supply 13 and provide the output voltage V 10 to the primary winding 1111b according to the control signal of the controller 114 .
  • the half-bridge circuit 1110b usually includes a main power transistor, an auxiliary power transistor and a clamping capacitor.
  • the primary winding 1111b of the transformer 1112b is used to receive the output voltage V 10 of the half-bridge circuit 1110b and generate the primary winding voltage V 11 .
  • the secondary winding 1113b of the transformer 1112b is coupled with the primary winding 1111b of the transformer 1112b, and the secondary winding voltage V 3 is generated on the secondary winding 1113b.
  • the rectifier circuit 1114b is used to receive the secondary winding voltage V 3 on the secondary winding 1113b and convert it into the output voltage V 2 .
  • the auxiliary winding circuit 112 is used to supply power to the power supply circuit 113 .
  • the auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111b of the transformer 1112b.
  • the primary winding voltage V 11 on the primary winding 1112b is coupled to generate the auxiliary winding voltage V 3 on the auxiliary winding 1121.
  • the output voltage V 4 is provided to the power supply circuit 113 .
  • the auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifier module 1122.
  • the power circuit 113 is used to power the controller 114 .
  • the power supply circuit 113 receives the output voltage V 4 of the auxiliary winding circuit 112 and provides the output voltage V 5 to the controller 114 . That is, the ACF conversion circuit 111b supplies power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 coupled with the primary winding 1111 of its transformer 1112b.
  • power circuit 113 includes a voltage stabilizing circuit.
  • the controller 114 is used to control the operating state of the ACF conversion circuit 111b.
  • the controller 114 is also used to detect the output voltage V 2 of the ACF conversion circuit 111b, the output voltage V 4 of the auxiliary winding circuit 112, the output voltage V 5 of the power supply circuit 113, or the capacitance voltage V of the clamping capacitor C c in the half-bridge circuit 1110b. Changes in multiple voltage values such as the voltage value of Cc .
  • the controller 114 is also used to control the operating state of the ACF conversion circuit 111b according to changes in the one or more voltage values.
  • the control 114 sends the control signal G to control the operating state of the half-bridge circuit 1110b in the ACF conversion circuit 111b, thereby controlling the operating state of the ACF conversion circuit 111b.
  • the operating states of the ACF conversion circuit 111b generally include a continuous operating state and a suspended operating state.
  • the continuous working state can also be called the normal working state, the controller's normal wave sending state, etc.
  • the suspended working state can also be called intermittent working state, BURST working state, intermittent wave sending state of the controller, etc.
  • the controller 114 can send a control signal G to control the turn-on and turn-off of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b.
  • the controller 114 adjusts the frequency or duty cycle of the control signal G to control the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b, thereby adjusting the output voltage V 10 of the half-bridge circuit 1110b accordingly.
  • the output voltage V 10 of the half-bridge circuit 1110b will cause the primary winding voltage V 11 to change.
  • changes in the primary winding voltage V 11 can cause changes in the secondary winding voltage V 12 and the auxiliary winding voltage V 3 .
  • changes in the secondary winding voltage V 12 may cause the output voltage V 2 of the ACF conversion circuit 111b to change.
  • changes in the auxiliary winding voltage V 3 may cause the output voltage V 4 of the auxiliary winding circuit 112 to change.
  • the output voltage V 4 of the auxiliary winding circuit 112 may cause a change in the output voltage V 5 of the power supply circuit 113 .
  • the ACF conversion circuit 111b can provide the output voltage V2 to power the load 12.
  • the input voltage V 1 is converted into the output voltage V 2 through the half-bridge circuit 1110b, the primary winding 1111b, the secondary winding 1113b and the rectifier circuit 1114b in the ACF conversion circuit 111b.
  • the ACF conversion circuit 111b can supply power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 .
  • the primary winding voltage V 11 can be generated in the primary winding 1111b.
  • the primary winding voltage V 11 can generate an auxiliary winding voltage V 3 on the auxiliary winding 1121 of the transformer 1112b.
  • the auxiliary winding voltage V 3 is processed by the auxiliary winding circuit 1121 to provide an output voltage V 4 to power the power supply circuit 113 of the controller 114 .
  • Figure 22 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops. The following describes in detail the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops, with reference to FIG. 22 and FIG. 21 .
  • the load level L of the load 12 is the normal load L 1 .
  • the controller 114 controls the ACF conversion circuit 111b to run in a continuous operating state.
  • the controller 114 controls the output voltage V 2 of the ACF conversion circuit 111b to be at the rated voltage value.
  • Output voltage V 20 The voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is V 40 .
  • the voltage value of the output voltage V 5 of the power supply circuit 113 is V 50 .
  • the voltage value of the capacitance voltage V Cc of the clamping capacitor C c in the half-bridge circuit 1111b is V Cc1 .
  • V Cc1 is the capacitance voltage of the clamping capacitor C c when the ACF conversion circuit 111b operates in a continuous operating state.
  • the load level of load 12 drops from normal load L 1 to light load L 2 .
  • the voltage value of the output voltage V 2 of the ACF conversion circuit 111b increases to be greater than the rated output voltage V 20 .
  • the controller 114 can control the ACF conversion circuit 111 b to operate in a continuous operating state. Furthermore, the controller controls the ACF conversion circuit 111b to reduce the voltage value of the output voltage V2 . That is, the controller 114 controls the ACF conversion circuit 111b to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b and the rated output voltage V 20 . The controller 114 controls the ACF conversion circuit 111 b Reduce the voltage value of the output voltage V2 .
  • the controller 114 sends the control signal G to control the operating status of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b, so that the voltage value of the primary winding voltage V 11 decreases.
  • the controller 114 can reduce the sending frequency of the control signal G, thereby reducing the conduction frequency of the main power transistor and the auxiliary power transistor.
  • the controller 114 can reduce the duty cycle of the control signal G, thereby reducing the conduction time of the main power transistor and the auxiliary power transistor.
  • the controller 114 can control the ACF conversion circuit 111b to run in a suspended working state, and can also reduce the output voltage V 2 Voltage value.
  • the above two embodiments may not be able to effectively reduce the voltage value of the output voltage V 2 of the ACF conversion circuit 111b. After time t 1 , the voltage value of the output voltage V 2 of the ACF conversion circuit 111b will continue to increase.
  • the drop of the load level L causes the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b to be higher than the rated voltage V 20 .
  • the primary winding voltage V 11 charges the clamping capacitor C c in the half-bridge circuit 1110b, and the voltage value of the capacitance voltage V Cc of the clamping capacitor C c in the half-bridge circuit 1110b increases from V Cc1 to V Cc2 .
  • V Cc2 is the maximum charging voltage of the clamping capacitor C c in the half-bridge circuit 1110b.
  • the controller 114 determines that the voltage value of the output voltage V 2 of the ACF conversion circuit 111b is greater than or equal to the first preset value V 21 , and the controller 114 controls the ACF conversion circuit 111b to suspend operation. That is, the controller 114 controls the ACF conversion circuit 111b to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b and the first preset value V 21 . Specifically, the controller 114 controls both the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b to turn off.
  • the first preset value V 21 may be the peak voltage of the ACF conversion circuit 111b.
  • the peak voltage of the ACF conversion circuit 111b is greater than the rated voltage V 20 and less than the overvoltage protection voltage of the ACF conversion circuit 111b.
  • the controller 114 controls the ACF conversion circuit 111b to operate in a suspended working state.
  • the voltage value of the primary winding voltage V 11 on the primary winding 1111 b in the ACF conversion circuit 111 b decreases, causing the secondary winding voltage V 12 to decrease, and causing the auxiliary winding voltage V 3 to decrease.
  • the voltage value of the output voltage V 2 of the ACF conversion circuit 111b decreases, the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110b to discharge.
  • the controller 114 determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is less than or equal to the second preset value V 41 , and the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110b to discharge . That is, the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110b to discharge based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the second preset value V 41 .
  • the controller 114 determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is less than or equal to the third preset value V 52 , and the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110b to discharge. That is, the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110b to discharge based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the third preset value V 52 .
  • the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110b to be turned on, so that the clamping capacitor C c in the half-bridge circuit 1110b is discharged.
  • the primary winding 1111b, the clamping capacitor C c of the half-bridge circuit 1110b, and the auxiliary power transistor of the half-bridge circuit 1110b can form a discharge circuit.
  • the clamping capacitor C c of the half-bridge circuit 1110b is discharged, which can generate the primary winding voltage V 11 on the primary winding 1111b.
  • the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110b to be turned on periodically, so that the clamping capacitor C c in the half-bridge circuit 1110b is discharged.
  • the auxiliary power transistor of the half-bridge circuit 1110b is turned on, the primary winding 1111b, the clamping capacitor C c of the half-bridge circuit 1110b, and the auxiliary power transistor of the half-bridge circuit 1110b can form a discharge loop.
  • the auxiliary power transistor of the half-bridge circuit 1110b is turned on periodically, which can cause the clamping capacitor C c in the half-bridge circuit 1110b to be discharged periodically.
  • the voltage value of the capacitance voltage V Cc of the clamping capacitor C c in the half-bridge circuit 1110b decreases.
  • the clamping capacitor C c in the half-bridge circuit 1110b is discharged, causing the voltage value of the primary winding voltage V 11 on the primary winding 1111b to increase.
  • an increase in the voltage value of the primary winding voltage V 11 will cause an increase in the voltage value of the auxiliary winding voltage V 3 .
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the voltage value of the output voltage V 5 of the power circuit 113 will not drop below the under-voltage protection voltage V 51 of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.
  • the controller 114 provided in the embodiment of the present application controls the discharge of the clamping capacitor C c in the half-bridge circuit 1110b of the ACF conversion circuit 111b, so that the voltage value of the output voltage V 5 of the power supply circuit 113 is higher than the under-voltage protection of the controller 114 voltage V 51 , thereby preventing the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the voltage value of the primary winding voltage V 11 generated on the primary winding 1111b after discharge is small. At this time, the primary winding voltage V 11 generated on the primary winding 1111b is smaller than the secondary winding voltage V 12 on the secondary winding 1113, which will not cause the output voltage V 2 of the ACF conversion circuit 111b to increase.
  • the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110b to discharge, the primary winding voltage V 11 generated on the primary winding 1111 b is only used to increase the output voltage V 4 of the auxiliary winding circuit 112 and the power supply circuit 113
  • the output voltage V 5 is shown in the F2 direction in Figure 21. Therefore, the controller 114 and the power module 111 in which it is provided in the embodiment of the present application can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V 2 of the ACF conversion circuit 111b. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.
  • the controller 114 provided in the embodiment of the present application controls the clamping capacitor C c in the half-bridge circuit 1110b of the ACF conversion circuit 111b, so as not to introduce noise from the input power supply 13 and avoid the noise from affecting the ACF conversion circuit 111b and its location.
  • the controller 114 can also adjust the capacitance voltage V Cc of the clamping capacitor C c in the half-bridge circuit 1110b.
  • the voltage value, the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 or the voltage value of the output voltage V 5 of the power supply circuit 113 controls the clamping capacitor C c in the half-bridge circuit 1110b to stop discharging.
  • the controller 114 controls the auxiliary power tube in the half-bridge circuit 1110b to turn off, and the discharge loop formed by the primary winding 1111b, the clamping capacitor C c of the half-bridge circuit 1110b, and the auxiliary power tube of the half-bridge circuit 1110b disconnect.
  • the clamping capacitor C c of the half-bridge circuit 1110b stops discharging.
  • the capacitance voltage V Cc of the clamping capacitor C c of the half-bridge circuit 1110 b drops to less than or equal to the preset capacitance voltage value V Cc3 .
  • the controller 114 determines that the capacitance voltage V Cc of the clamping capacitor C c of the half-bridge circuit 1110b drops to less than or equal to the preset capacitance voltage value V Cc3 , and the controller 114 controls the clamping of the half-bridge circuit 1110b Capacitor C c stops discharging.
  • the preset capacitor voltage value V Cc3 may be greater than or equal to the capacitance voltage V Cc1 of the clamping capacitor C c of the half-bridge circuit 1110 b when the ACF conversion circuit 111 b operates in the continuous operating state. That is, the controller 114 controls the clamp capacitor C c of the half-bridge circuit 1110 b to stop discharging based on the comparison result between the capacitor voltage V Cc of the clamp capacitor C c of the half-bridge circuit 1110 b and the preset capacitor voltage value V Cc3 .
  • the controller 114 can stop discharging through the clamping capacitor C c of the half-bridge circuit 1110 b, and can avoid the capacitance voltage V Cc of the clamping capacitor C c being too low and affecting the ACF conversion circuit 111 b to resume continuous operation, further improving the power supply mode.
  • the controller 114 determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is greater than or equal to the fourth preset value V 42 , and the controller 114 controls the clamping capacitor C c of the half-bridge circuit 1110b to stop discharging. . That is, the controller 114 controls the clamp capacitor C c of the half-bridge circuit 1110 b to stop discharging based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the fourth preset value V 42 .
  • the controller 114 can stop discharging through the clamping capacitor C c of the half-bridge circuit 1110b, which can prevent the output voltage V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller. 114 and the stability of the power module 11 and electronic equipment 10 in which it is located.
  • the controller 114 determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is greater than or equal to the fifth preset value V 53 , and the controller 114 controls the clamping capacitor C c of the half-bridge circuit 1110b to stop discharging. That is, the controller 114 controls the clamp capacitor C c of the half-bridge circuit 1110 b to stop discharging based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the fifth preset value V 53 .
  • the controller 114 can stop discharging by controlling the clamping capacitor C c of the half-bridge circuit 1110 b to prevent the output voltage V 4 of the power supply circuit 113 from being too high and damaging the controller 114 , further improving the efficiency of the controller 114 and its location.
  • the controller 114 may control the clamping capacitor C c of the half-bridge circuit 1110 b to discharge again. The specific process is as described in the above embodiment and will not be described again.
  • the controller 114 can control the clamping capacitor C c of the half-bridge circuit 1110 b to discharge again based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the second preset value V 41 .
  • the controller 114 may control the clamping capacitor C c of the half-bridge circuit 1110 b to discharge again based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the third preset value V 52 .
  • the controller 114 will also control the ACF conversion circuit according to the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b
  • the operating status of 111b switches from the suspended working status to the continuous working status.
  • the controller 114 controls the ACF conversion circuit 111 b to operate in a suspended operating state, and accordingly the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b decreases.
  • the controller 114 controls the operating state of the ACF conversion circuit 111b to switch from the suspended operating state to the continuous operating state.
  • the controller 114 controls the ACF conversion The operating state of the circuit 111b is switched from the suspended operating state to the continuous operating state.
  • the controller 114 determines that the voltage value of the output voltage V 2 of the ACF conversion circuit 111b drops to less than or equal to the rated voltage V 20 , and controls the operating state of the ACF conversion circuit 111b to switch from the suspended operating state to the continuous operating state. That is, the controller 114 controls the operation state of the ACF conversion circuit 111b to switch from the pause operation state to the continuous operation state based on the comparison result between the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b and the rated voltage V 20 .
  • the voltage value of the output voltage V 2 of the ACF conversion circuit 111b returns to the rated voltage V 20
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 returns to V 40
  • the output voltage V 5 of the power supply circuit 113 The voltage value returns to V 50 .
  • FIG. 23 is a schematic diagram of an embodiment of the power module provided by this application.
  • FIG. 23 shows a schematic diagram of some circuits in the power module 11 shown in FIG. 21 .
  • the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113 and a controller 114.
  • the ACF conversion circuit 111b includes a half-bridge circuit 1110b, a transformer 1112b and a rectifier circuit 1114b.
  • the transformer 1112b includes a primary winding 1111b and a secondary winding 1113b.
  • the transformer 1112b also includes an auxiliary winding 1121 in the auxiliary winding circuit 112.
  • the secondary winding 1113b is coupled to the primary winding 1111b
  • the auxiliary winding 1121 is coupled to the primary winding 1111b.
  • the half-bridge circuit 1110b includes a main power transistor Q L , an auxiliary power transistor Q H and a clamping capacitor C c .
  • the main power tube Q L , the auxiliary power tube Q H and the clamping capacitor C c form an active clamp flyback half-bridge topology.
  • the first end of the clamping capacitor C c is connected to the opposite end of the primary winding 1111b, and the second end of the clamping capacitor C c is connected to the drain of the auxiliary power tube Q H.
  • the source of the auxiliary power tube QH is connected to the same terminal of the primary winding 1111b and the drain of the main power tube QL .
  • the source of the main power tube Q L is grounded.
  • the gate of the main power transistor Q L is used to receive the second control signal GH from the controller 114 .
  • the gate of the auxiliary power transistor Q H is used to receive the first control signal GL from the controller 114 .
  • the rectifier circuit 1114b includes a capacitor C 1 and a diode D 2 .
  • the anode of diode D 2 is connected to the same terminal of secondary winding 1113b.
  • the two ends of the capacitor C 1 are respectively connected to the cathode of the diode D 2 and the opposite terminal of the secondary winding 1113b.
  • the auxiliary winding circuit 112 includes an auxiliary winding 1121 and a rectifier module 1122.
  • Rectification module 1122 may include diode D 1 .
  • the anode of the diode D 1 is connected to the same terminal of the auxiliary winding 1121
  • the cathode of the diode D 1 and the different terminal of the auxiliary winding 1121 are connected to the power circuit 113 .
  • the power circuit 113 may include a boost circuit.
  • the power circuit 113 may also be a buck (BUCK) circuit, a buck-boost (BUCK-BOOST) circuit, etc.
  • the power circuit 113 may also be a voltage stabilizing circuit such as a low dropout linear voltage regulator circuit (low dropout regulator, LDO).
  • the controller 114 includes a detection unit 1141 and a driving unit 1142.
  • the power circuit 113 may be connected to the power supply pin of the driving unit 1142 .
  • the supply pin may be the pin labeled " Vdd " shown in Figure 23.
  • the detection unit 1141 is used to detect the output voltage V 2 of the ACF conversion circuit 111 b , the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 , the voltage value of the output voltage V 5 of the power supply circuit 113 or the half-bridge circuit 1110 b of the ACF conversion circuit 111 b Changes in various voltage values among the voltage values of the capacitor voltage V Cc of the medium clamping capacitor C c .
  • the driving circuit 1142 is used to control the operating state of the ACF conversion circuit 111b according to the change of one or more voltage values.
  • the detection unit 1141 can detect the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b by connecting point A of the output end of the secondary winding circuit 1114 b in FIG. 23 .
  • the detection unit 1141 can detect the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 by connecting point B of the output end of the auxiliary winding circuit 112 in FIG. 23 .
  • the detection unit 1141 can detect the voltage value of the output voltage V 5 of the power supply circuit 113 by connecting point C of the output end of the power supply circuit 113 in FIG. 23 .
  • the detection unit 1141 can detect the voltage value of the capacitance voltage V Cc of the clamp capacitor C c by connecting points D on either side of the clamp capacitor C c in FIG. 23 .
  • the driving unit 1142 is used to control the operating state of the ACF conversion circuit 111b. Among them, the driving unit 1142 controls the on and off of the main power transistor Q L and the auxiliary power transistor Q H by sending the control signal G L /G H , thereby controlling the operating state of the ACF conversion circuit 111b.
  • the driving unit 1142 shown in FIG. 23 can send the control signal GH through its pin labeled " GH ", and can send the control signal GH through its pin labeled " GL " The pin sends the control signal GL .
  • the pin numbers in Figure 23 are only examples, and in actual applications, pins with other numbers on the driving unit 1142 can also be used to implement the functions of the pins shown in Figure 23 .
  • the driving unit 1142 controls the main power tube QL to be turned on or off by sending a first control signal GL to the main power tube QL .
  • the driving unit 1142 controls the auxiliary power tube QH to be turned on or off by sending the second control signal GH to the auxiliary power tube QH .
  • the first control signal GL and the second control signal GH sent by the controller 114 may include high-level signals or low-level signals.
  • the main power transistor QL is turned on according to the first control signal GL
  • the auxiliary power transistor QH is turned on according to the second control signal GH .
  • the main power transistor QL is turned off according to the first control signal GL
  • the auxiliary power transistor QH is turned off according to the second control signal GH .
  • Figure 24 is a schematic diagram of the control signals of the controller provided by this application in a scenario where the load level of the power module drops. The following describes the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops, with reference to FIG. 22 , FIG. 23 and FIG. 24 .
  • the load level of load 12 is normal load L 1 .
  • the controller 114 controls the ACF conversion circuit 111b to operate in a continuous operating state, and controls the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b to be the rated voltage V 20 .
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is V 40 .
  • the voltage value of the output voltage V 5 of the power supply circuit 113 is V 50 .
  • the voltage value of the capacitance voltage V Cc of the clamping capacitor C c in the half-bridge circuit 1111b is V Cc1 .
  • FIG 25 is a schematic diagram of the control signals of the controller provided by the embodiment of the present application.
  • each of the control signals G1 , G2 , G3 ... sent by the controller 114 includes a first control signal GL sent to the main power tube QL or a first control signal GL sent to the auxiliary power tube QH .
  • Second control signal G H Second control signal.
  • the controller 114 controls the main power transistor QL and the auxiliary power transistor QH to periodically turn on and off alternately, and the half-bridge circuit 1110b can generate the primary winding voltage V 11 in the primary winding 1111b.
  • the primary winding voltage V 11 on the primary winding 1111b can generate the secondary winding voltage V 12 on the secondary winding 1113b, and can generate the auxiliary winding voltage V 3 on the auxiliary winding 1121.
  • the rectifier circuit 1114b provides the output voltage V 2 to the load 12
  • the auxiliary winding circuit 112 provides the output voltage V 4 to the power supply circuit 113
  • the output voltage V 5 of the power supply circuit 113 to the controller 115 is V 50 .
  • the load level of load 12 drops from normal load L 1 to light load L 2 .
  • the voltage value of the output voltage V2 of the ACF conversion circuit 111b increases to greater than the rated voltage V20 .
  • the controller 114 controls the ACF conversion circuit 111b to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b and the rated voltage V 20 .
  • the controller 114 controls the ACF conversion circuit.
  • 111b reduces the voltage value of the output voltage V 2 .
  • the detection unit 1141 of the controller 114 detects the output voltage V 2 of the ACF conversion circuit 111 b and determines that the output voltage V 2 of the ACF conversion circuit 111 b is greater than the rated voltage V 20 .
  • the controller 114 controls the ACF conversion circuit 111b to operate in a continuous working state, and the controller 114 reduces the transmission frequency of the first control signal GL and the second control signal GH , or reduces the transmission frequency of the first control signal GL and the second control signal GH. Duty cycle of signal G H. As shown in FIG.
  • the frequencies of the control signals G 4 , G 5 , and G 6 sent by the controller 114 after time t 1 are smaller than the frequencies of the control signals G 1 , G 2 , and G 3 periodically sent before time t 1 .
  • the frequency at which the main power transistor QL and the auxiliary power transistor QH are turned on and off is reduced, causing the voltage value of the output voltage V2 of the ACF conversion circuit 111b to decrease.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the above method may not effectively reduce the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b, and the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b will continue to increase.
  • the voltage value of the output voltage V 2 of the ACF conversion circuit 111b is higher than the rated voltage V 20 .
  • the primary winding voltage V 11 charges the clamping capacitor C c in the half-bridge circuit 1110b, and the voltage value of the capacitance voltage V Cc of the clamping capacitor C c in the half-bridge circuit 1110b increases from V Cc1 to V Cc2 .
  • the voltage value of the output voltage V 2 of the ACF conversion circuit 111b increases to a value greater than or equal to the first preset value V 21 .
  • the controller 114 controls the ACF conversion circuit 111b to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b and the first preset value V 21 .
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 2 of the ACF conversion circuit 111b, and determines that the voltage value of the output voltage V 2 of the ACF conversion circuit 111b is greater than or equal to the first preset value V 21 .
  • the driving unit 1142 of the controller 114 stops sending the first control signal GL and the second control signal GH , thereby controlling the ACF conversion circuit 111b to operate in a suspended working state.
  • the ACF conversion circuit 111b does not process the input voltage V 1 it receives, and the output voltage V 2 of the ACF conversion circuit 111b decreases.
  • the controller 114 controls the ACF conversion circuit 111b to operate in a suspended working state.
  • the voltage value of the primary winding voltage V 11 on the primary winding 1111 b in the ACF conversion circuit 111 b decreases, causing the secondary winding voltage V 12 to decrease, and causing the auxiliary winding voltage V 3 to decrease.
  • the voltage value of the output voltage V 2 of the ACF conversion circuit 111b decreases, the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V 5 of the power supply circuit 113 decreases.
  • the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110b to discharge.
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is less than or equal to the second preset value. V41 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn on the auxiliary power transistor QH .
  • the clamping capacitor C c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor QH of the half-bridge circuit 1110b form a discharge loop, and the clamping capacitor C c of the half-bridge circuit 1110b begins to discharge.
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 5 of the power supply circuit 113 and determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is less than or equal to the third preset value V 52 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn on the auxiliary power transistor QH .
  • the clamping capacitor C c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor QH of the half-bridge circuit 1110b form a discharge loop, and the clamping capacitor C c of the half-bridge circuit 1110b begins to discharge.
  • the voltage value of the capacitance voltage V Cc of the clamping capacitor C c in the half-bridge circuit 1110b decreases.
  • the clamping capacitor C c in the half-bridge circuit 1110b is discharged, causing the voltage value of the primary winding voltage V 11 on the primary winding 1111b to increase.
  • the voltage value of the auxiliary winding voltage V 3 increases, the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the voltage value of the output voltage V 5 of the power circuit 113 will not drop below the under-voltage protection voltage V 51 of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.
  • the controller 114 provided in the embodiment of the present application controls the discharge of the clamping capacitor C c in the half-bridge circuit 1110b of the ACF conversion circuit 111b, so that the voltage value of the output voltage V 5 of the power supply circuit 113 is higher than the under-voltage protection of the controller 114 voltage V 51 , thereby preventing the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the voltage value of the primary winding voltage V 11 generated on the primary winding 1111b after discharge is small. At this time, the primary winding voltage V 11 generated on the primary winding 1111b is smaller than the secondary winding voltage V 12 on the secondary winding 1113, which will not cause the output voltage V 2 of the ACF conversion circuit 111b to increase.
  • the controller 114 controls the clamping capacitor C c in the half-bridge circuit 1110b to discharge, the primary winding voltage V 11 generated on the primary winding 1111 b is only used to increase the output voltage V 4 of the auxiliary winding circuit 112 and the power supply circuit 113 Output voltage V 5 . Therefore, the controller 114 and the power module 111 in which it is provided in the embodiment of the present application can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V 2 of the ACF conversion circuit 111b. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.
  • the controller 114 provided in the embodiment of the present application controls the clamping capacitor C c in the half-bridge circuit 1110b of the ACF conversion circuit 111b, so as not to introduce noise from the input power supply 13 and avoid affecting the ACF conversion circuit 111b and its location. Electromagnetic compatibility of power module 11 and electronic equipment 10 . Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.
  • the controller 114 can also control the clamp capacitor C c in the half-bridge circuit 1110b of the ACF conversion circuit 111b to stop discharging.
  • the capacitance voltage V Cc of the clamping capacitor C c of the half-bridge circuit 1110 b drops to less than or equal to the preset capacitance voltage value V Cc3 .
  • the preset capacitor voltage value V Cc3 may be greater than or equal to the capacitance voltage V Cc of the clamping capacitor C c of the half-bridge circuit 1110 b when the ACF conversion circuit 111 b operates in the continuous operating state.
  • the controller 114 controls the clamping capacitor C c of the half-bridge circuit 1110b to stop discharging based on the comparison result between the capacitance voltage V Cc of the clamping capacitor C c of the half-bridge circuit 1110b and the preset capacitance voltage value V Cc3 .
  • the detection unit 1141 of the controller 114 detects the capacitance voltage V Cc of the clamping capacitor C c of the half-bridge circuit 1110 b and determines that the capacitance voltage V Cc of the clamping capacitor C c of the half-bridge circuit 1110 b is less than or equal to the preset capacitance voltage. Value V Cc3 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn off the auxiliary power transistor QH .
  • the discharge loop formed by the clamping capacitor C c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor Q H of the half-bridge circuit 1110b is disconnected, and the clamping capacitor C c of the half-bridge circuit 1110b stops discharging.
  • the controller 114 can stop discharging through the clamping capacitor C c of the half-bridge circuit 1110 b, and can avoid the capacitance voltage V Cc of the clamping capacitor C c being too low and affecting the ACF conversion circuit 111 b to resume continuous operation, further improving the power supply mode.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases to greater than or equal to the fourth preset value V 42 .
  • the controller 114 controls the clamping capacitor C c of the half-bridge circuit 1110b to stop discharging based on the comparison result between the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and the fourth preset value V 42 .
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 and determines that the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 is less than or equal to the preset capacitor voltage value V Cc3 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn off the auxiliary power transistor QH .
  • the discharge loop formed by the clamping capacitor C c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor Q H of the half-bridge circuit 1110b is disconnected, and the clamping capacitor C c of the half-bridge circuit 1110b stops discharging.
  • the controller 114 can stop discharging through the clamping capacitor C c of the half-bridge circuit 1110b, which can prevent the output voltage V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller. 114 and the stability of the power module 11 and electronic equipment 10 in which it is located.
  • the voltage value of the output voltage V 5 of the power circuit 113 is increased to greater than or equal to the fifth preset value V 53 .
  • the controller 114 controls the clamping capacitor C c of the half-bridge circuit 1110 b to stop discharging based on the comparison result between the voltage value of the output voltage V 5 of the power supply circuit 113 and the fifth preset value V 53 .
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 5 of the power supply circuit 113 and determines that the voltage value of the output voltage V 5 of the power supply circuit 113 is greater than or equal to the fifth preset value V 53 .
  • the driving unit 1142 of the controller 114 sends the first control signal GL to turn off the auxiliary power transistor QH .
  • the discharge loop formed by the clamping capacitor C c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor Q H of the half-bridge circuit 1110b is disconnected, and the clamping capacitor C c of the half-bridge circuit 1110b stops discharging. Therefore, the controller 114 can stop discharging by controlling the clamping capacitor C c of the half-bridge circuit 1110 b to prevent the output voltage V 4 of the power supply circuit 113 from being too high and damaging the controller 114 , further improving the efficiency of the controller 114 and its location.
  • the controller 114 may control the clamping capacitor C c of the half-bridge circuit 1110 b to discharge again. The specific process is as described in the above embodiment and will not be described again.
  • the controller 114 will also control the ACF conversion circuit according to the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b
  • the operating status of 111b switches from the suspended working status to the continuous working status.
  • the controller 114 controls the ACF conversion circuit 111 b to operate in a suspended operating state, and accordingly the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b decreases.
  • the controller 114 controls the operating state of the ACF conversion circuit 111b to switch from the suspended operating state to the continuous operating state.
  • the controller 114 controls the ACF conversion The operating state of the circuit 111b is switched from the suspended operating state to the continuous operating state.
  • the voltage value of the output voltage V 2 of the ACF conversion circuit 111b drops to less than or equal to the rated output voltage V 20 .
  • the controller 114 controls the operating state of the ACF converting circuit 111b to switch from the suspended operating state to the continuous operating state based on the comparison result between the voltage value of the output voltage V 2 of the ACF converting circuit 111 b and the rated output voltage V 20 .
  • the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b and determines that the voltage value of the output voltage V 2 of the ACF conversion circuit 111 b is less than or equal to the rated output voltage V 20 .
  • the driving unit 1142 of the controller 114 periodically sends the first control signal GL and the second control signal GH , and controls the main power tube QL and the auxiliary power tube QH to be turned on and off periodically, so that the ACF conversion circuit 111b Restore continuous working status.
  • the first control signal GL and the second control signal GH sent by the controller 114 are recorded as G 7 , G 8 , G 9 . . .
  • the specific implementation of each control signal G 7 , G 8 , G 9 ... is the same as shown in Figure 25 and will not be described again.
  • the voltage value of the output voltage V2 of the ACF conversion circuit 111b returns to the rated output voltage V20
  • the voltage value of the output voltage V4 of the auxiliary winding circuit 112 returns to V40
  • the output voltage V of the power supply circuit 113 The voltage value of 5 returns to V 50 .
  • Figure 26 is a schematic diagram of an embodiment of the controller provided by the present application controlling the discharge of the clamp capacitor of the ACF conversion circuit.
  • the difference between Figure 26 and Figure 24 is that the controller 114 controls the clamp capacitor C c of the primary winding circuit 1111b in the ACF conversion circuit 111b to periodically discharge. Description will be given below with reference to Figure 22 and Figure 26 .
  • the controller 114 controls the auxiliary power transistor Q H in the half-bridge circuit 1110b to be turned on periodically, so that the clamping capacitor C c in the half-bridge circuit 1110b is discharged. Specifically, the controller 114 does not send the first control signal GL to the main power tube QL , so that the main power tube QL is turned off. Furthermore, the controller 114 periodically sends the second control signal GH to the auxiliary power transistor QH , so that the auxiliary power transistor QH is periodically turned on.
  • the auxiliary power transistor Q H of the half-bridge circuit 1110b When the auxiliary power transistor Q H of the half-bridge circuit 1110b is turned on, the primary winding 1111b, the clamping capacitor C c of the half-bridge circuit 1110b, and the auxiliary power transistor Q H of the half-bridge circuit 1110b can form a discharge loop. Correspondingly, the auxiliary power transistor Q H of the half-bridge circuit 1110b is turned on periodically, which can cause the clamping capacitor C c in the half-bridge circuit 1110b to be discharged periodically.
  • the controller 114 controls the period T1 during which the auxiliary power transistor Q H is periodically turned on, which may be preconfigured, or the controller 114 may be based on the capacitance voltage V Cc of the current clamping capacitor C c or The stored electrical energy is calculated. In one embodiment, when the voltage value of the capacitance voltage V Cc of the clamping capacitor C c is relatively high or more electric energy is stored, the period T1 can be set smaller. In an embodiment, the period T1 may also be the same as the period of the control signals G 1 , G 2 , G 3 . . . or G 4 , G 5 , G 6 . . . In the embodiment of the present application, the duration for which the controller 114 controls the auxiliary power transistor Q H to be turned on or off in each cycle may be the same or different.
  • Figure 27 is a schematic diagram of changes in the capacitance voltage of the clamp capacitor of the ACF conversion circuit provided by this application.
  • the clamping capacitor Cc is periodically discharged, and the capacitance voltage V Cc of the clamping capacitor Cc decreases stepwise from V Cc2 .
  • the capacitance voltage V Cc of the clamping capacitor C c decreases stepwise as the auxiliary power transistor Q H is periodically turned on.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 also shows a step-like increase
  • the voltage value of the output voltage V 5 of the power supply circuit 113 also shows a step-like increase.
  • the controller 114 controls the clamping capacitor C c in the ACF conversion circuit 111b to periodically discharge, which can cause the capacitance voltage V Cc of the clamping capacitor C c to decrease in a stepwise manner, avoiding excessive rapid decline that affects the operation of the ACF conversion circuit 111b. , thereby improving the stability of the power module 11.
  • the controller 114 controls the clamping capacitor C c in the ACF conversion circuit 111b to periodically discharge, which can increase the output voltage V 4 of the auxiliary winding circuit 112 and the output voltage V 5 of the power supply circuit 113 in a stepwise manner to avoid excessive voltage increase.
  • the circuit components may be damaged quickly, thereby improving the stability of the power module 11.
  • Figure 28 is a schematic diagram of another embodiment of the controller provided by the present application controlling the discharge of the clamp capacitor of the ACF conversion circuit.
  • the difference between Figure 28 and Figure 26 is that the controller 114 controls the auxiliary power tube Q H and the main power tube Q L in the primary winding circuit 1111b of the ACF conversion circuit 111b to periodically alternately conduct, so that the clamping capacitor C c periodically Discharge.
  • the controller 114 periodically controls the main power tube QL and the auxiliary power tube QH to turn on alternately, and controls the auxiliary power tube QH and the main power tube QL to not turn on at the same time. Specifically, the controller 114 periodically sends the second control signal GH to the auxiliary power tube QH and the first control signal GL to the main power tube QL in sequence, so that the auxiliary power tube QH and the main power tube Q L is turned on in sequence, and the auxiliary power tube Q H and the main power tube Q L are not turned on at the same time.
  • the controller 114 controls the auxiliary power transistor QH to turn on first and the main power transistor QL to turn on later.
  • the controller 114 controls the auxiliary power transistor QH to turn on and the main power transistor QL to turn off. Specifically, the controller 114 sends the second control signal GH to the auxiliary power tube QH and does not send the first control signal GL to the main power tube QL .
  • the clamping capacitor C c , the primary winding a and the auxiliary power tube Q H form a current loop, and the clamping capacitor C c discharges.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the controller 114 controls the auxiliary power transistor QH to turn off and the main power transistor QL to turn on. Specifically, the controller 114 does not send the second control signal GH to the auxiliary power tube QH and sends the first control signal GL to the main power tube QL .
  • the input voltage V 1 , primary winding a, and main power tube Q L form a loop.
  • the input voltage V 1 generates the primary winding voltage V 11 on both sides of the primary winding a.
  • the primary winding voltage V 11 is coupled through the transformer 1112b to generate the auxiliary winding voltage V 3 on the auxiliary winding c.
  • the voltage value of the output voltage V 4 of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V 5 of the power supply circuit 113 increases.
  • the controller 114 controls the clamping capacitor C c of the primary side winding circuit 1111b in the ACF conversion circuit 111b to periodically discharge, which can cause the capacitance voltage V Cc of the clamping capacitor C c to drop in a stepwise manner to avoid falling too fast and affecting the ACF.
  • the operation of the conversion circuit 111b thereby improves the stability of the power module 111.
  • the controller 114 controls the clamping capacitor C c of the primary winding circuit 1111b in the ACF conversion circuit 111b to periodically discharge, which can increase the output voltage V 4 of the auxiliary winding circuit 112 and the output voltage V 5 of the power supply circuit 113 in a stepwise manner. , to avoid damage to circuit components due to excessive lifting, thereby improving the stability of the power module 111.
  • the controller 114 in each cycle, can control the main power transistor Q L to turn on first and the auxiliary power transistor Q H to turn on later. In the embodiment of the present application, the controller 114 controls the main power transistor Q L and the auxiliary power transistor Q H to periodically conduct alternately.
  • the period T2 may be pre-configured, or the controller 114 may control the main power transistor Q L and the auxiliary power transistor Q H according to the current clamping capacitance C c
  • the capacitor voltage V Cc or stored electrical energy is calculated. In one embodiment, when the voltage value of the capacitance voltage V Cc of the clamping capacitor C c is relatively high or more electric energy is stored, the period T2 can be set smaller.
  • the period T2 may be the same as the period of the control signals G 1 , G 2 , G 3 . . . or the period of G 4 , G 5 , G 6 . . .
  • the controller 114 controls the conduction time of the main power transistor QL and the conduction time of the auxiliary power transistor QH , which may be the same or different.
  • the duty ratios of the first control signal GL and the second control signal GH sent by the controller 114 may be the same or different.
  • the controller 114 provided in the embodiment of the present application only needs to control the on or off of the main power transistor Q L and the auxiliary power transistor Q H in the ACF conversion circuit 111 b when the load level L of the power module 11 drops. Therefore, the controller 114 provided by the embodiment of the present application can not only improve the stability of the ACF conversion circuit 111b, power module 11, and electronic device 10 where it is located, but also has a simple configuration and is more suitable for use in various products.
  • This application also provides an electronic device, including the controller 114 provided in any embodiment of this application, or the power module 11 provided in any embodiment of this application.
  • the controller 114 as the execution subject may include a hardware structure. and/or software modules to implement the above functions in the form of hardware structures, software modules, or hardware structures plus software modules. Whether one of the above functions is performed as a hardware structure, a software module, or a hardware structure plus a software module depends on the specific application and design constraints of the technical solution. It should be noted that it should be understood that the division of each module of the above device is only a division of logical functions. In actual implementation, they can be fully or partially integrated into a physical entity, or they can also be physically separated.
  • modules can all be implemented in the form of software calling through processing components; they can also all be implemented in the form of hardware; some modules can also be implemented in the form of software calling through processing components, and some modules can be implemented in the form of hardware. It can be a separate processing element, or it can be integrated into a chip of the above-mentioned device. In addition, it can also be stored in the memory of the above-mentioned device in the form of program code, and called and executed by a certain processing element of the above-mentioned device. Determine the function of the module. The implementation of other modules is similar. In addition, all or part of these modules can be integrated together or implemented independently.
  • the processing element described here may be an integrated circuit with signal processing capabilities.
  • each step of the above method or each of the above modules can be completed by instructions in the form of hardware integrated logic circuits or software in the processor element.
  • the above modules may be one or more integrated circuits configured to implement the above methods, such as: one or more application specific integrated circuits (ASICs), or one or more microprocessors (digital signal processor, DSP), or one or more field programmable gate arrays (field programmable gate array, FPGA), etc.
  • ASICs application specific integrated circuits
  • DSP digital signal processor
  • FPGA field programmable gate array
  • the processing element can be a general-purpose processor, such as a central processing unit (Central Processing Unit, CPU) or other processors that can call the program code.
  • these modules can be integrated together and implemented in the form of a system-on-a-chip (SOC).
  • SOC system-on-a-chip
  • the steps performed by the controller 114 may be implemented in whole or in part by software, hardware, firmware, or any combination thereof.
  • software When implemented using software, it may be implemented in whole or in part in the form of a computer program product.
  • the computer program product includes one or more computer instructions.
  • the computer program instructions When the computer program instructions are loaded and executed on a computer, the processes or functions described in the embodiments of the present application are generated in whole or in part.
  • the computer may be a general-purpose computer, a special-purpose computer, a computer network, or other programmable device.
  • the computer instructions may be stored in or transmitted from one computer-readable storage medium to another, e.g., the computer instructions may be transferred from a website, computer, server, or data center Transmission to another website, computer, server or data center by wired (such as coaxial cable, optical fiber, digital subscriber line (DSL)) or wireless (such as infrared, wireless, microwave, etc.) means.
  • the computer-readable storage medium may be any available medium that can be accessed by a computer or a data storage device such as a server, data center, etc. that contains one or more available media integrated.
  • the available media may be magnetic media (eg, floppy disk, hard disk, tape), optical media (eg, DVD), or semiconductor media (eg, solid state disk (SSD)), etc.
  • This application also provides a computer-readable storage medium.
  • the computer-readable storage medium stores computer instructions. When the computer instructions are executed, they can be used to perform any method performed by the controller 114 in any of the foregoing embodiments of this application.
  • This embodiment of the present application also provides a chip that runs instructions, and the chip is used to execute any method executed by the controller 114 as mentioned above in this application.
  • An embodiment of the present application also provides a computer program product.
  • the program product includes a computer program.
  • the computer program is stored in a storage medium.
  • At least one processor can read the computer program from the storage medium.
  • the at least one processor can read the computer program from the storage medium.
  • When a processor executes the computer program it may implement any method executed by the controller 114 as described above in this application.
  • the aforementioned program can be stored in a computer-readable storage medium.
  • the steps including the above-mentioned method embodiments are executed; and the aforementioned storage media include: ROM, RAM, magnetic disks, optical disks and other media that can store program codes.

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Abstract

本申请提供一种非对称半桥变换电路的控制器、电源模组及电子设备，控制器可以在非对称半桥变换电路运行于暂停工作状态后，通过控制非对称半桥变换电路的谐振电容放电，使电源电路的输出电压的电压值高于控制器的低电压保护的预设电压值，从而避免了控制器因低电压保护而重启，并提高了非对称半桥变换电路所在的电源模组及电子设备的稳定性。并且，控制器在控制谐振电容放电时还不会增大非对称半桥变换电路的输出电压的波纹，也不会引入来自输入电源的噪声。

Description

非对称半桥变换电路的控制器、电源模组及电子设备
本申请要求于2022年04月11日提交中国专利局、申请号为202210376104.7、申请名称为“非对称半桥变换电路的控制器、电源模组及电子设备”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请涉及电源技术，尤其涉及一种非对称半桥(asymmetrical half-bridge，AHB)变换电路的控制器及其所在的电源模组、电子设备。
背景技术
现有电子设备或电源模组中通常包括非对称半桥(asymmetrical half-bridge，AHB)、有源钳位反激(active clamp flyback，ACF)等类型的直流变换电路和控制器。直流变换电路通常包括半桥电路、变压器及整流电路。变压器的原边绕组电路经过半桥电路接收输入电源的输入电压，副边绕组电路用于提供输出电压为负载供电。其中，变压器还包括辅助绕组电路，用于为控制器的电源电路供电。在电源模组启动时，控制器的电源电路一般由输入电源的输入电压供电。在电源模组运行时，变压器的辅助绕组电路为控制器的电源电路供电。因此，直流变换电路的运行状态会影响控制器的电源电路的供电稳定性，进而影响控制器所在电源模组、电子设备的稳定性。
发明内容
本申请提供一种非对称半桥变换电路的控制器、电源模组及电子设备，用于解决非对称半桥变换电路等直流变换电路的运行状态影响控制器的电源电路、控制器所在电源模组、电子设备的稳定性的技术问题。
以直流变换电路为非对称半桥变换电路作为示例，本申请第一方面提供一种非对称半桥变换电路的控制器，可用于控制非对称半桥变换电路的运行状态。其中，控制器控制非对称半桥变换电路运行于连续工作状态时，非对称半桥变换电路输出电压为额定输出电压。当控制器判断非对称半桥变换电路的输出电压高于第一预设值时，则控制非对称半桥变换电路运行于暂停工作状态。随后，在非对称半桥变换电路运行于暂停工作状态后，当控制器判断非对称半桥变换电路中的辅助绕组电路的输出电压小于或等于第二预设值，则控制非对称半桥变换电路的谐振电容放电。或者，在非对称半桥变换电路运行于暂停工作状态后，当控制器判断非对称半桥变换电路中的电源电路的输出电压小于或等于第三预设值，则控制非对称半桥变换电路的谐振电容放电。因此，本实施例提供的控制器在非对称半桥变换电路运行于暂停工作状态后，可以通过控制非对称半桥变换电路的谐振电容放电，使电源电路的输出电压的电压值高于控制器的低电压保护的预设电压值，从而避免了控制器 因低电压保护而重启，并提高了非对称半桥变换电路所在的电源模组及电子设备的稳定性。且本实施例提供的控制器在控制谐振电容放电时还不会增大非对称半桥变换电路的输出电压的波纹，也不会引入来自输入电源的噪声。
在本申请第一方面一实施例中，当控制器判断非对称半桥变换电路的输出电压小于或等于额定输出电压，则控制器控制非对称半桥变换电路从暂停工作状态切换为连续工作状态。因此，本实施例提供的控制器能够在非对称半桥变换电路的输出电压恢复正常后，及时控制非对称半桥变换电路恢复连续工作状态，进一步提高了非对称半桥变换电路所在的电源模组及电子设备的稳定性。
在本申请第一方面一实施例中，控制器具体通过控制非对称半桥变换电路中半桥变换电路的辅助功率管和主功率管都关断的方式，控制非对称半桥变换电路运行于暂停工作状态。因此，本实施例提供的控制器能够在其所在电源模组的负载水平发生跌落后，控制非对称半桥变换电路不再对接收到的输入电压进行处理并提供输出电压，避免了电源模组的的输出电压过高而损坏负载。
在本申请第一方面一实施例中，控制器控制非对称半桥变换电路的半桥电路中辅助功率管导通，使半桥电路中的谐振电容放电。可以使辅助绕组电路的输出电压、电源电路的输出电压得到较快的提升，更快地降低电源模组的的输出电压，尽可能减少电源模组向负载的输出电压大于第一预设值，更有效地保护负载。
在本申请第一方面一实施例中，控制器控制非对称半桥变换电路的半桥电路中辅助功率管周期性地导通，使半桥电路中的谐振电容放电。由于半桥电路中的谐振电容周期性地放电，可以使辅助绕组电路的输出电压、电源电路的输出电压阶梯式地提升，避免电压提升过快而损坏电路器件，从而提高了非对称半桥变换电路所在的电源模组及电子设备的稳定性。
在本申请第一方面一实施例中，控制器控制非对称半桥变换电路的半桥电路中辅助功率管和主功率管周期性地交替导通，使半桥电路中的谐振电容放电。其中，当控制器控制辅助功率管导通、主功率管截止时，谐振电容放电，控制器的电源电路的输出电压的电压值提升；当控制器控制辅助功率管截止、主功率管导通，输入电压在原边绕组两侧产生原边绕组电压。原边绕组电压通过变压器耦合，在辅助绕组上产生辅助绕组电压。相应地，辅助绕组电路的输出电压的电压值提升，控制器的电源电路的输出电压的电压值提升。辅助绕组电路的输出电压、电源电路的输出电压阶梯式地提升，避免提升过快而损坏电路器件，从而提高了非对称半桥变换电路所在的电源模组及电子设备的稳定性。
在上述各实施例中，在电源模组的负载水平发生跌落的场景中，控制器都可以控制谐振电容开始放电。并且控制器在控制谐振电容放电时，仅需要控制非对称半桥变换电路中的主功率管和辅助功率管的导通或者截止，使其配置简单从而更适用于各类产品使用。
在本申请第一方面一实施例中，控制器判断谐振电容的电容电压下降至小于或等于预设电容电压值，则控制谐振电容停止放电。因此，本实施例中的控制器可以避免谐振电容的电容电压过低而影响非对称半桥变换电路恢复连续工作状态，进一步提高了非对称半桥变换电路所在的电源模组及电子设备的稳定性。
在本申请第一方面一实施例中，控制器判断辅助绕组电路的输出电压的电压值提升至大于或等于第四预设值，则控制谐振电容停止放电。因此，本实施例中的控制器可以避免 辅助绕组电路的输出电压的电压过高而损坏电源电路及控制器，进一步提高了非对称半桥变换电路所在的电源模组及电子设备的稳定性。
在本申请第一方面一实施例中，控制器可以判断电源电路的输出电压的电压值提升至大于或等于第五预设值，则控制谐振电容停止放电。因此，本实施例中的控制器可以避免电源电路的输出电压的电压过高而损坏控制器，进一步提高了非对称半桥变换电路所在的电源模组及电子设备的稳定性。
在本申请第一方面一实施例中，控制器控制非对称半桥变换电路的半桥电路中辅助功率管和主功率管关断，使谐振电容停止放电。因此，本实施例中的控制器在电源模组的负载水平发生跌落的场景中，控制谐振电容停止放电仅需要控制非对称半桥变换电路中的主功率管和辅助功率管的导通或者截止，使其配置简单从而更适用于各类产品使用。
本申请第二方面提供一种电源模组，包括非对称半桥变换电路、辅助绕组电路、电源电路及控制器。其中，非对称半桥变换电路包括：半桥电路、变压器及整流电路。半桥电路包括主功率管、辅助功率管及谐振电容。
非对称半桥变换电路用于接收输入电压，并对输入电压进行电压变换处理后，向负载提供输出电压。辅助绕组电路用于为所述电源电路供电。电源电路用于为所述控制器供电。控制器可用于控制非对称半桥变换电路。
其中，控制器控制非对称半桥变换电路运行于连续工作状态时，非对称半桥变换电路输出电压为额定输出电压。当控制器判断对称半桥变换电路的输出电压高于第一预设值时，则控制非对称半桥变换电路运行于暂停工作状态。随后，在非对称半桥变换电路运行于暂停工作状态后，当控制器判断非对称半桥变换电路中的辅助绕组电路的输出电压小于或等于第二预设值，则控制非对称半桥变换电路的谐振电容放电。或者，在非对称半桥变换电路运行于暂停工作状态后，当控制器判断非对称半桥变换电路中的电源电路的输出电压小于或等于第三预设值，则控制非对称半桥变换电路的谐振电容放电。
因此，本实施例提供的电源模组中，控制器可以在非对称半桥变换电路运行于暂停工作状态后，通过控制非对称半桥变换电路的谐振电容放电，使电源电路的输出电压的电压值高于控制器的低电压保护的预设电压值，从而避免了控制器因低电压保护而重启，并提高了电源模组及其所在电子设备的稳定性。且本实施例提供的控制器在控制谐振电容放电时还不会增大非对称半桥变换电路的输出电压的波纹，也不会引入来自输入电源的噪声。
在本申请第二方面一实施例中，当控制器判断非对称半桥变换电路的输出电压小于或等于额定输出电压，则控制器控制非对称半桥变换电路从暂停工作状态切换为连续工作状态。因此，本实施例提供的电源模组中，控制器能够在非对称半桥变换电路的输出电压恢复正常后，及时控制非对称半桥变换电路恢复连续工作状态，进一步提高了电源模组及其所在电子设备的稳定性。
在本申请第二方面一实施例中，控制器具体通过控制非对称半桥变换电路中半桥变换电路的辅助功率管和主功率管都关断的方式，控制非对称半桥变换电路运行于暂停工作状态。因此，本实施例提供的电源模组中，控制器能够在其所在电源模组的负载水平发生跌落后，控制非对称半桥变换电路不再对接收到的输入电压进行处理并提供输出电压，避免了电源模组的的输出电压过高而损坏负载。
在本申请第二方面一实施例中，控制器控制非对称半桥变换电路的半桥电路中辅助功 率管导通，使半桥电路中的谐振电容放电。可以使辅助绕组电路的输出电压、电源电路的输出电压得到较快的提升，更快地降低电源模组的的输出电压，尽可能减少电源模组向负载的输出电压大于第一预设值，更有效地保护负载。
在本申请第二方面一实施例中，控制器控制非对称半桥变换电路的半桥电路中辅助功率管周期性地导通，使半桥电路中的谐振电容放电。由于半桥电路中的谐振电容周期性地放电，可以使辅助绕组电路的输出电压、电源电路的输出电压阶梯式地提升，避免电压提升过快而损坏电路器件，从而提高了电源模组及其所在电子设备的稳定性。
在本申请第二方面一实施例中，控制器控制非对称半桥变换电路的半桥电路中辅助功率管和主功率管周期性地交替导通，使半桥电路中的谐振电容放电。其中，当控制器控制辅助功率管导通、主功率管截止时，谐振电容放电，控制器的电源电路的输出电压的电压值提升；当控制器控制辅助功率管截止、主功率管导通，输入电压在原边绕组两侧产生原边绕组电压。原边绕组电压通过变压器耦合，在辅助绕组上产生辅助绕组电压。相应地，辅助绕组电路的输出电压的电压值提升，控制器的电源电路的输出电压的电压值提升。辅助绕组电路的输出电压、电源电路的输出电压阶梯式地提升，避免提升过快而损坏电路器件，从而提高了电源模组及其所在电子设备的稳定性。
在上述各实施例中，在电源模组的负载水平发生跌落的场景中，电源模组中的控制器都可以控制谐振电容开始放电。并且控制器在控制谐振电容放电时，仅需要控制非对称半桥变换电路中的主功率管和辅助功率管的导通或者截止，使其配置简单从而更适用于各类产品使用。
在本申请第二方面一实施例中，控制器判断谐振电容的电容电压下降至小于或等于预设电容电压值，则控制谐振电容停止放电。因此，本实施例中的控制器可以避免谐振电容的电容电压过低而影响非对称半桥变换电路恢复连续工作状态，进一步提高了电源模组及其所在的电子设备的稳定性。
在本申请第二方面一实施例中，控制器判断辅助绕组电路的输出电压的电压值提升至大于或等于第四预设值，则控制谐振电容停止放电。因此，本实施例中的控制器可以避免辅助绕组电路的输出电压的电压过高而损坏电源电路及控制器，进一步提高了电源模组及其所在电子设备的稳定性。
在本申请第二方面一实施例中，控制器可以判断电源电路的输出电压的电压值提升至大于或等于第五预设值，则控制谐振电容停止放电。因此，本实施例中的控制器可以避免电源电路的输出电压的电压过高而损坏控制器，进一步提高了电源模组及其所在电子设备的稳定性。
在本申请第二方面一实施例中，控制器控制非对称半桥变换电路的半桥电路中辅助功率管和主功率管关断，使谐振电容停止放电。因此，本实施例中电源模组在负载水平发生跌落的场景中，电源模组的控制器控制谐振电容停止放电仅需要控制非对称半桥变换电路中的主功率管和辅助功率管的导通或者截止，使其配置简单从而更适用于各类产品使用。
需要说明的是，上述各实施例中，以直流变换电路为非对称半桥变换电路作为示例，直流变换电路还可以是有源钳位反激变换等。
本申请第三方面提供一种电子设备，包括如本申请第一方面任一项所述的非对称半桥变换电路的控制器。
本申请第四方面提供一种电子设备，包括如本申请第二方面任一项所述的电源模组。
附图说明
图1为本申请提供的一种电子设备的示意图；
图2为本申请提供的一种电子设备的另一示意图；
图3为本申请实施例提供的一种电源模组的示意图；
图4为一种电源模组的示意图；
图5为图4的电源模组在负载水平发生跌落的场景中的电压波形示意图；
图6为现有的另一种控制器及其所在电源模组的示意图；
图7为本申请实施例提供的一种电源模组的示意图；
图8为本申请提供的控制器及其所在的电源模组在负载水平发生跌落的场景中的电压波形示意图；
图9为本申请提供的电源模组一种实施例的示意图；
图10为本申请提供的电源模组一种实施例的示意图；
图11为本申请提供的控制器及其所在的电源模组在负载水平发生跌落的场景中的电压波形示意图；
图12为本申请提供的电源模组一种实施例的示意图；
图13为本申请提供的控制器在电源模组的负载水平发生跌落的场景中的控制信号示意图；
图14为本申请实施例提供的控制器的控制信号的示意图；
图15为本申请提供的控制器控制AHB变换电路的谐振电容放电的一种实施例的示意图；
图16为本申请提供的AHB变换电路的谐振电容的电容电压的变化示意图；
图17为本申请提供的控制器控制AHB变换电路的谐振电容放电的另一种实施例的示意图；
图18为本申请提供的另一种AHB变换电路中半桥电路的示意图；
图19为本申请提供的另一种AHB变换电路中半桥电路的示意图；
图20为本申请提供的电源模组一种实施例的示意图；
图21为本申请提供的电源模组一种实施例的示意图；
图22为本申请提供的控制器及其所在的电源模组在负载水平发生跌落的场景中的电压波形示意图；
图23为本申请提供的电源模组一种实施例的示意图；
图24为本申请提供的控制器在电源模组的负载水平发生跌落的场景中的控制信号示意图；
图25为本申请实施例提供的控制器的控制信号的示意图；
图26为本申请提供的控制器控制ACF变换电路的钳位电容放电的一种实施例的示意图；
图27为本申请提供的ACF变换电路的钳位电容的电容电压的变化示意图；
图28为本申请提供的控制器控制ACF变换电路的钳位电容放电的另一种实施例的示意图。
具体实施方式
图1为本申请提供的一种电子设备的示意图。如图1所示，电子设备10包括电源模组11和负载12。其中，电源模组11接收输入电源13提供的输入电压V 1，并提供输出电压V 2为负载12供电。在一种实施例中，电子设备10可以包括多个电源模组11，多个电源模组11提供多个输出电压V 2为负载12供电。在一种实施例中，电子设备10可以包括多个负载12，电源模组11提供多个输出电压V 2分别为多个负载12供电。在一种实施例中，电子设备10可以包括多个负载12和多个电源模组11，多个电源模组11可以分别为多个负载12供电。在一种实施例中，电子设备10可以接收多个输入电源13的输出电压V 1。在一种实施例中，电子设备10可以包括一个或多个输入电源13。在一种实施例中，电子设备10可以是手机、电脑、平板或者家电等电子设备。在一种实施例中，负载12包括电子设备10的内部电路或电子设备10的外接电子设备。
图2为本申请提供的一种电子设备的另一示意图。如图2所示，电子设备10包括电源模组11。电源模组11接收输入电源13提供的输入电压V 1，并提供输出电压V 2为负载12供电。在一种实施例中，电子设备10中包括多个电源模组11，多个电源模组11可以提供多个输出电压V 2为负载12供电。在一种实施例中，电子设备10中电源模组11可以提供多个输出电压V 2分别为多个负载12供电。在一种实施例中，电子设备10可以包括多个电源模组11，多个电源模组11分别为多个负载12提供输出电压V 2。在一种实施例中，电子设备10可以接收多个输入电源13。在一种实施例中，电子设备10可以包括输入电源13。在一种实施例中，电子设备10可以是适配器、充电桩等设备。通常，适配器(adaptor)也可以被称为充电器(charger)、充电头、开关电源(switch power supply)或者功率变换器(power converter)等。在一种实施例中，负载12可以是手机、电脑、平板或者家电等电子设备。在一种实施例中，负载12可以是电子设备10的其它内部电路。
图3为本申请实施例提供的一种电源模组的示意图。如图3所示，电源模组11包括直流(direct current，DC)变换电路111、辅助绕组电路112、电源电路113和控制器114。直流变换电路111用于接收输入电源13提供的输入电压V 1，并向负载12提供输出电压V 2。另外，直流变换电路111经辅助绕组电路112为控制器114的电源电路113供电。其中，辅助绕组电路112与直流变换电路111耦合，在辅助绕组上产生辅助绕组电压V 3。辅助绕组电路112将辅助绕组电压V 3转换为输出电压V 4，并向电源电路113提供输出电压V 4。电源电路113将辅助绕组电路112的输出电压V 4转换为输出电压V 5，并向控制电路114提供输出电压V 5。控制器114用于控制直流变换电路111。在本申请实施例中，直流变换电路111可以包括非对称半桥(asymmetrical half-bridge，AHB)变换电路或有源钳位反激(active clamp flyback，ACF)变换电路。
图4为一种电源模组的示意图。如图4所示，电源模组11包括直流变换电路111、辅助绕组电路112、电源电路113和控制器114。直流变换电路111可以包括半桥电路1110、变压器1112和整流电路1114。其中，变压器1112包括原边绕组1111和副边绕组1113。 另外，变压器1112还包括辅助绕组电路112中的辅助绕组1121。副边绕组1113与原边绕组1111相耦合，辅助绕组1121与原边绕组1111相耦合。
半桥电路1110用于接收输入电源13提供的输入电压V 1，并根据控制器114的控制信号提供输出电压V 10。输入电压V 1和输出电压V 10可以是一个电压范围。半桥电路1110通常包括主功率管、辅助功率管及电容。根据主功率管、辅助功率管及电容的连接关系，直流变换电路111包括AHB变换电路和ACF变换电路。AHB变换电路的半桥电路1110中的电容为谐振电容C r。ACF变换电路的半桥电路1110中的电容为钳位电容C c。
变压器1112的原边绕组1111用于接收半桥电路1110的输出电压V 10，并在原边绕组1111上产生原边绕组电压V 11。经过变压器1112的副边绕组1113与变压器1112的原边绕组1111相耦合，副边绕组1113上产生副边绕组电压V 12。绕组电压V 11和副边绕组电压V 12可以是一个电压范围。
整流电路1114用于接收副边绕组1113上产生的副边绕组电压V 12，并转换为输出电压V 2。输出电压V 2可以是一个电压范围。
辅助绕组电路112用于为电源电路113供电。辅助绕组电路112的辅助绕组1121与变压器1112的原边绕组1111相耦合。原边绕组1112上的原边绕组电压V 11经过耦合，在辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电压V 3经辅助绕组电路112处理后，向电源电路113提供输出电压V 4。其中，辅助绕组电路112可以包括辅助绕组1121和整流模块1122。辅助绕组电压V 3和输出电压V 4可以是一个电压范围。
电源电路113用于为控制器114供电。电源电路113接收辅助绕组电路112的输出电压V 4，并向控制器114提供输出电压V 5。其中，电源电路113可以包括稳压电路。输出电压V 5可以是一个电压范围。
控制器114用于控制直流变换电路111的运行状态。控制器114可以向直流变换电路111的半桥电路1110发送控制信号G，从而控制直流变换电路111的运行状态。直流变化电路111的运行状态通常包括连续工作状态和暂停工作状态。连续工作状态也可以称为正常工作状态、控制器正常发波状态等。暂停工作状态也可以称为间歇工作状态、BURST工作状态、控制器间歇发波状态等。
电源模组11的负载12的负载水平发生跌落时，由于直流变换电路111中原边绕组1111的原边绕组电压V 11未发生变化，将导致直流变换电路111的输出电压V 2的电压值快速提升。相应地，控制器114需要调整直流变换电路111的运行状态，从而降低直流变换电路111的输出电压V 2，避免电源模组11的的输出电压V 2过高而损坏负载12。
图5为图4的电源模组在负载水平发生跌落的场景中的电压波形示意图。下文结合图4所示的电源模组11，详细说明负载12的负载水平L发生跌落对现有的控制器114及其所在的电源模组11的影响。
在t 1时刻之前，负载12的负载水平L为正常负载L 1。控制器114控制直流变换电路111处于连续工作状态，直流变换电路111的输出电压V 2的电压值为额定输出电压V 20。额定输出电压V 20为直流变换电路111在连续工作状态时的额定输出电压。额定输出电压V 20可以是一个电压范围。相应地，辅助绕组电路112的输出电压V 4的电压值为V 40。电压值V 40为辅助绕组电路112的额定输入电压。电压值V 40可以是一个电压范围电源电路113的输出电压V 5的电压值为V 50。电压值V 50为控制器114的额定输入电压。电压值V 50 可以是一个电压范围。
在t 1时刻，负载12的负载水平L从正常负载L 1跌落到轻负载L 2。
在t 1时刻之后，直流变换电路111的输出电压V 2的电压值将提升至大于额定输出电压V 20。在一种实施例中，控制器114控制直流变换电路111运行于连续工作状态。并且，控制器114减少半桥电路1111中主功率管和辅助功率管的导通频率或导通时长，使得原边绕组1111的原边绕组电压V 11的电压值下降。相应地，副边绕组电压V 13的电压值下降，可以降低直流变换电路111的输出电压V 2的电压值。由于辅助绕组电路112中的辅助绕组1121与原边绕组1111相耦合，辅助绕组电压V 3的电压值下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
但是，负载12的负载水平跌落影响较大，控制器114仅通过减少半桥电路1111中主功率管和辅助功率管的导通频率或导通时长，通常无法有效降低直流变换电路111的输出电压V 2的电压值。导致在t 1时刻之后，直流变换电路111的输出电压V 2的电压值将继续提升。
在t 1时刻之后的t 2时刻，直流变换电路111的输出电压V 2的电压值提升至大于或等于第一预设值V 21。变换电路111的输出电压V 2的电压值过高将损坏负载12。为了防止直流变换电路111的输出电压V 2的电压值继续提升，控制器114需要控制直流变换电路111运行于暂停工作状态。其中，将电压值V 21记为第一预设值，电压值V 21是直流变换电路111的最大输出电压。电压值V 21小于直流变换电路111的额定输出输出电压V 20，且小于直流变换电路111的过压保护电压。
在t 2时刻之后，直流变换电路111处于暂停工作状态，使得直流变换电路111中原边绕组电路1111的原边绕组电压V 11下降。相应地，直流变换电路111的输出电压V 2的电压值下降。由于辅助绕组1121与原边绕组1111相耦合，原边绕组1111的原边绕组电压V 11下降，会导致辅助绕组1121的辅助绕组电压V 3的电压值下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
如果电源电路113的输出电压V 5的电压值小于控制器114的欠压保护电压V 51，控制器114将因为低电压保护而重启。电压值V 51为控制器114的欠压保护电压。控制器114需要一段时间完成重启过程，从而导致这段时间内控制器14不能控制直流变压电路111的运行状态，进而影响控制器114所在电源模组11、电子设备10的稳定性。
在t 2时刻后的t 3时刻，电源电路113的输出电压V 5的电压值下降至小于或等第三预设值V 52。第三预设值V 52大于控制器114的欠压保护电压V 51且小于控制器114的额定输入电压V 50。当电源电路113的输出电压V 5的电压值小于或等于第三预设值V 52，控制器114控制直流变换电路111运行于连续工作状态。相应地，原边绕组电压V 11的电压值提升。原边绕组电压V 11的电压值提升，可以导致辅助绕组电压V 3的电压值提升。相应地，辅助绕组电路112的输出电压V 4的电压值提升。电源电路113的输出电压V 5的电压值提升。但是，原边绕组电压V 11的电压值提升，也会导致副边绕组电压V 12的电压值提升，从而使得直流变换电路111的输出电压V 2的电压值提升。
在t 3时刻之后的t 4时刻，直流变换电路111的输出电压V 2的电压值提升至大于或等于第二预定值V 21。此时，控制器114又需要控制直流变换电路111运行于暂停工作状态。直流变换电路111运行于暂停工作状态，可以使得原边绕组电压V 11的电压值下降。相应 地，直流变换电路111的输出电压V 2的电压值下降。但是，原边绕组电压V 11的电压值下降，还会导致辅助绕组电路112的输出电压V 4的电压值下降。相应地，电源电路113的输出电压V 5的电压值下降。
在t 4时刻之后的t 5时刻，电源电路113的输出电压V 5的电压值下降至小于或等第五预定值V 52。此时，控制器114又需要控制直流变换电路111运行于连续工作状态。相应地，辅助绕组电路112的输出电压V 4的电压值提升。电源电路113的输出电压V 5的电压值提升。但是，直流变换电路111运行于连续工作状态，又将使得直流变换电路111的输出电压V 2的电压值提升。
因此，现有的电源模块11中控制器114虽然可以避免因欠压保护而重启，但也会导致直流变换电路111的输出电压V 2的波纹较大。因此，现有的控制器114及其所在的电源模块11会导致直流变换电路111的输出电压V 2的波纹较大，从而影响电源模组11的稳定性。
图6为现有的另一种控制器及其所在电源模组的示意图。如图6所示，电源模组11中辅助绕组电路112通过开关K与输入电源13相连。负载12的负载水平L变化导致直流变换电路111的输出电压V 2的电压值提升后，控制器114控制直流变换电路111运行于暂停工作状态，且控制器114控制开关K导通。输入电源13经过开关K、辅助绕组电路112为电源电路113供电，从而避免控制器114因欠压保护而重启。但是，输入电源13的噪声也会通过开关K传递到电源模组11内部，影响电源模组11的电磁兼容性(EMC，electro magnetic compatibility)。
本申请提供了一种直流变换电路的控制器及其所在的电源模组、电子设备，可以解决现有技术中控制器及其所在电源模组、电子设备的稳定性问题、电磁兼容性问题、输出电压波纹增大等缺陷。下面以具体的实施例进行详细说明。下面具体的实施例可以相互结合，对于相同或相似的概念或过程可能在某些实施例不再赘述。
图7为本申请实施例提供的一种电源模组的示意图。如图7所示的电源模组11可应用在如图1或者图2所示的电子设备10中。如图7所示，电源模组11包括直流变换电路111、辅助绕组电路112、电源电路113和控制器114。直流变换电路111可以包括半桥电路1110、变压器1112和整流电路1114。其中，变压器1112包括原边绕组1111和副边绕组1113。另外，变压器1112还包括辅助绕组电路112中的辅助绕组1121。副边绕组1113与原边绕组1111相耦合，辅助绕组1121与原边绕组1111相耦合。
半桥电路1110用于接收输入电源13提供的输入电压V 1，并根据控制器114的控制信号向原边绕组1111提供输出电压V 10。半桥电路1110通常包括主功率管、辅助功率管及电容。根据主功率管、辅助功率管及电容的连接关系，本申请实施例中直流变换电路111包括AHB变换电路和ACF变换电路。在一种实施例中，直流变换电路111包括AHB变换电路，半桥电路1110中的电容为谐振电容C r。在一种实施例中，直流变换电路111包括ACF变换电路，半桥电路1110中的电容为钳位电容C c。在一种实施例中，主功率管和辅助功率管为金属氧化物半导体场效应晶体管(Metal-Oxide-Semiconductor Field-Effect Transistor，MOS)。在其它实施例中，主功率管和辅助功率管还可以为三极管或者绝缘栅双极型晶体管(Insulated Gate Bipolar Transistor，IGBT)等其它类型的晶体管。
变压器1112的原边绕组1111用于接收半桥电路1110的输出电压V 10，并产生原边绕 组电压V 11。变压器1112的副边绕组1113与变压器1112的原边绕组1111相耦合，副边绕组1113上产生副边绕组电压V 3。
整流电路1114用于接收副边绕组1113上的副边绕组电压V 3，并转换为输出电压V 2。
辅助绕组电路112用于为电源电路113供电。辅助绕组电路112的辅助绕组1121与变压器1112的原边绕组1111相耦合。原边绕组1112上的原边绕组电压V 11经过耦合，在辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电压V 3经辅助绕组电路112处理后，向电源电路113提供输出电压V 4。在一种实施例中，辅助绕组电路112包括辅助绕组1121和整流模块1122。
电源电路113用于为控制器114供电。电源电路113接收辅助绕组电路112的输出电压V 4，并向控制器114提供输出电压V 5。即，直流变换电路111经与其变压器1112的原边绕组1111耦合的辅助绕组电路112，为控制器114的电源电路113供电。一些实施例中，电源电路113包括稳压电路。
控制器114用于控制直流变换电路111的运行状态。控制器114还用于检测直流变换电路111的输出电压V 2、绕组电路112的输出电压V 4、电源电路113的输出电压V 5或半桥电路1110中电容的电容电压V c等多个电压值的变化。控制器114还用于根据上述一个或多个电压值的变化，控制直流变换电路111的运行状态。
在一种实施例中，控制114通过控制直流变换电路111中半桥电路1110的运行状态，从而控制直流变换电路111的运行状态。例如，控制器114可以控制半桥电路1110中主功率管及辅助功率管的导通及关断，从而控制半桥电路1110的运行状态。控制器114可以调整半桥电路1110中主功率管及辅助功率管的导通频率或导通时长，相应地调整半桥电路1110的输出电压V 10。相应地，半桥电路1110的输出电压V 10的变化，会导致原边绕组电压V 11变化。相应地，原边绕组电压V 11的变化可以导致副边绕组电压V 12和辅助绕组电压V 3变化。相应地，副边绕组电压V 12的变化可以导致直流变换电路111的输出电压V 2变化。相应地，辅助绕组电压V 3的变化可以导致辅助绕组电路112的输出电压V 4变化。相应地，辅助绕组电路112的输出电压V 4可以导致电源电113的输出电压V 5的变化。
如图7中F1方向所示，直流变换电路111可以提供输出电压V 2为负载12供电。其中，输入电压V 1经直流变换电路111的半桥电路1110、原边绕组1111、副边绕组1113及整流电路1114转换为输出电压V 2。
如图7中F2方向所示，直流变换电路111可以通过辅助绕组电路112为控制器114的电源电路113供电。其中，输入电压V 1经直流变换电路111的半桥电路1110处理后，可以在原边绕组1111产生原边绕组电压V 11。相应地，原边绕组电压V 11可以在变压器1112的辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电压V 3经辅助绕组电路1121处理后提供输出电压V 4，为控制器114的电源电路113供电。
图8为本申请提供的控制器及其所在的电源模组在负载水平发生跌落的场景中的电压波形示意图。下文结合图7和图8，说明本申请提供的控制器114及其所在的电源模组11在负载12的负载水平L发生跌落的场景中的运行过程。
在t 1时刻之前，负载12的负载水平L为正常负载L 1，控制器114控制直流变换电路111运行于连续工作状态，控制器114控制直流变换电路111的输出电压V 2的电压值为额 定输出电压V 20。辅助绕组电路112的输出电压V 4的电压值为V 40。电源电路113的输出电压V 5的电压值为V 50。半桥电路1111中电容的电容电压V c的电压值为V C1。V C1为直流转换电路111运行于连续工作状态时电容的电容电压。
在t 1时刻，负载12的负载水平L从正常负载L 1跌落到轻负载L 2。相应地，在t 1时刻之后，直流变换电路111的输出电压V 2的电压值将提升至大于额定输出电压V 20。
在一种实施例中，当直流转换电路111的输出电压V 2的电压值大于额定输出电压V 20，控制器114可以控制直流转换电路111运行于连续工作状态。并且，控制器114控制直流变换电路111降低输出电压V 2的电压值。即，控制器114根据直流变换电路111的输出电压V 2的电压值与额定输出电压V 20的比较结果，控制器114控制直流转换电路111运行于连续工作状态，控制器114控制直流变换电路111降低输出电压V 2的电压值。具体地，控制器114发送控制信号G控制半桥电路1110中主功率管和辅助功率管的运行状态，使得原边绕组电压V 11的电压值下降。在一种实施例中，控制器114可以降低控制信号G的发送频率，从而降低主功率管和辅助功率管的导通频率。在一种实施方式中，控制器114可以降低控制信号G的占空比，从而降低主功率管和辅助功率管的导通时长。在另一种实施例中，当直流转换电路111的输出电压V 2的电压值大于额定输出电压V 20，控制器114可以控制直流转换电路111运行于暂停工作状态，也能够降低输出电压V 2的电压值。但是，上述两种实施例都可能无法使得直流变换电路111的输出电压V 2的电压值有效下降，在t 1时刻之后直流变换电路111的输出电压V 2的电压值将继续提升。
同时，在t 1时刻之后，负载水平L的跌落导致直流变换电路111的输出电压V 2的电压值高于额定输出电压V 20。原边绕组电压V 11给半桥电路1110中的电容充电，半桥电路1110中电容的电容电压V c的电压值从V C1提升到V C2。V C2为半桥电路1110中电容的最大充电电压。
在t 1时刻之后的t 2时刻，直流变换电路111的输出电压V 2的电压值提升至第一预设值V 21。控制器114确定直流变换电路111的输出电压V 2的电压值大于或等于第一预设值V 21，控制器114控制直流变换电路111暂停工作。即，控制器114根据直流变换电路111的输出电压V 2的电压值与第一预设值V 21的比较结果，控制器114控制直流变换电路111运行于暂停工作状态。具体的，控制器114控制半桥电路1110中主功率管和辅助功率管都关断。在本申请实施例中，第一预设值V 21可以是直流变换电路111的峰值电压。直流变换电路111的峰值电压大于额定输出电压V 20，且小于直流变换电路111的过压保护电压。
在t 2时刻之后，控制器114控制直流变换电路111运行于暂停工作状态。相应地，半桥电路1110的输出电压V 10的电压值下降，使得原边绕组1111上的原边绕组电压V 11的电压值下降。原边绕组1111上的原边绕组电压V 11的电压值下降，会导致副边绕组1113上的副边绕组电压V 12下降。相应地，直流变换电路111的输出电压V 2的电压值下降。另外，原边绕组1111上的原边绕组电压V 11的电压值下降，会导致辅助绕组电压V 3的电压值下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在t 2时刻后的t 3时刻，辅助绕组电路112的输出电压V 4的电压值下降至小于或等于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降至小于或等于第三预设值V 52。其中，将电压值V 41记为第二预设值，电压值V 41大于电源电路113的最低输入电压、 且小于电源电路113的额定输入电压V 40。将电压值V 52记为第三预设值，电压值V 52大于控制器114的欠压保护电压V 51、且小于控制器114的额定输入电压V 50
在一种实施例中，控制器114确定辅助绕组电路112的输出电压V 4的电压值小于或等于第二预设值V 41，控制器114控制半桥电路1110中的电容放电。即，控制器114根据辅助绕组电路112的输出电压V 4的电压值与第二预设值V 41的比较结果，控制半桥电路1110中的电容放电。
在一种实施例中，控制器114确定电源电路113的输出电压V 5的电压值小于或等于第三预设值V 52，控制器114控制半桥电路1110中的电容放电。即，控制器114根据电源电路113的输出电压V 5的电压值与第三预设值V 52的比较结果，控制器114控制半桥电路1110中的电容放电。
在一种实施例中，控制器114控制半桥电路1110中辅助功率管导通，使得半桥电路1110的电容放电。半桥电路1110中辅助功率管通时，原边绕组1111及半桥电路1110的电容、辅助功率管可以形成放电回路。相应地，半桥电路1110中的电容放电，在原边绕组1111上产生原边绕组电压V 11。
在一种实施例中，控制器114控制半桥电路1110中辅助功率管周期性地导通，使得半桥电路1110的电容放电。半桥电路1110中辅助功率导通时，原边绕组1111、半桥电路1110的电容、半桥电路1110的辅助功率管可以形成放电回路。相应地，辅助功率管周期性地导通，可以使得半桥电路1110中的电容周期性地放电。
在一种实施例中，直流变换电路111包括AHB变换电路，控制器114控制AHB变换电路的半桥电路1110中的谐振电容放电。在一种实施例中，直流变换电路111包括ACF变换电路，控制器114控制ACF变换电路的半桥电路1110中的钳位电容放电。在一种实施例中，直流变换电路111的半桥电路1110中可以包括多个电容，控制器114控制半桥电路1110中的多个电容放电。
在t 3时刻之后，半桥电路1110中的电容的电容电压V c的电压值下降。半桥电路1110中的电容放电，使得原边绕组1111上的原边绕组电压V 11的电压值提升。相应地，原边绕组电压V 11的电压值提升，会导致辅助绕组电压V 3的电压值提升。相应地，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。因此，负载12的负载水平发生变化的场景中，电源电路113的输出电压V 5的电压值不会下降至低于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。
本申请实施例提供的控制器114通过控制直流变换电路111的原边绕组电路1111中电容放电，可以使得电源电路113的输出电压V 5的电压值高于控制器114的低电压保护的预设电压值V 51，从而避免了控制器114因低电压保护而重启。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
由于半桥电路1110中电容存储的能量有限，放电后在原边绕组1111上产生的原边绕组电压V 11的电压值较小。此时原边绕组1111上产生的原边绕组电压V 11小于副边绕组1113上的副边绕组电压V 12，不会导致直流变压电路111的输出电压V 2提升。因此，控制器114控制半桥电路1110中电容放电后，原边绕组1111上产生的原边绕组电压V 11仅用于提升辅助绕组电路112的输出电压V 4和电源电路113的输出电压V 5，如图7中F2方向所示。因此，本申请实施例提供的控制器114及其所在的电源模组111不仅可以避免控制 器114因欠压保护而重启，还可以避免增大直流变换电路111的输出电压V 2的波纹，可以提高控制器114其所在的电源模组11及电子设备10的稳定性。
而且，本申请实施例提供的控制器114通过控制直流变换电路111中的电容放电，不会引入来自输入电源13的噪声，可以避免噪声影响直流变换电路111及其所在的电源模组11、电子设备10的电磁兼容性。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
在本申请一种实施例中，在直流变换电路111的半桥电路1110中的电容开始放电后，控制器114还可以根据半桥电路1110中电容的电容电压V c的电压值、辅助绕组电路112的输出电压V 4的电压值或者电源电路113的输出电压V 5的电压值，控制半桥电路1110中的电容停止放电。
在一种实施例中，控制器114控制半桥电路1110的辅助功率管关断，原边绕组1111及半桥电路1110的电容、辅助功率管形成的放电回路断开。相应地，半桥电路1110中的电容停止放电。
在一种实施例中，直流变换电路111包括AHB变换电路，控制器114控制半桥电路1110中的谐振电容C r停止放电。在一种实施例中，直流变换电路111包括ACF变换电路，控制器114控制半桥电路1110中的钳位电容C c停止放电。在一种实施例中，直流变换电路111的半桥电路1110中还可以包括多个电容，控制器114控制半桥电路1110中的多个电容停止放电。
在第一种实施例中，在t 3时刻之后的t 4时刻，半桥电路1110中电容的电容电压V c下降至小于或等于预设电容电压值V C3。在一种实施例中，控制器114确定半桥电路1110中电容的电容电压V c下降至小于或等于预设电容电压值V C3，控制器114控制半桥电路1110中电容停止放电。在一种实施例中，预设电容电压值V C3可以大于或等于直流变换电路111运行在连续运行状态时半桥电路1110中电容的电容电压的电压值V C1。即，控制器114根据半桥电路1110中电容的电容电压V c与预设电容电压值V C3的比较结果，控制器114控制半桥电路1110中电容停止放电。因此，控制器114可以通过控制半桥电路1110中电容停止放电，避免电容电压过低影响直流变换电路111恢复连续工作状态，进一步提高了电源模组11及其所在的电子设备10的稳定性。
在第二种实施例中，在t 3时刻之后的t 4时刻，辅助绕组电路112的输出电压V 4的电压值提升至大于或等于第四预设值V 42。在一种实施例中，控制器114确定辅助绕组电路112的输出电压V 4的电压值大于或等于第四预设值V 42，控制器114控制半桥电路1110中电容停止放电。其中，将电压值V 42记为第四预设值，电压值V 42可以是电源电路113的最高输入电压。电压值V 42大于电源电路113的额定输入电压V 40，且小于电源电路113的过压保护电压。即，控制器114根据辅助绕组电路112的输出电压V 4的电压值与第四预设值V 42的比较结果，控制器114控制半桥电路1110中电容停止放电。因此，控制器114可以通过控制半桥电路1110中电容停止放电，可以避免辅助绕组电路112的输出电压V 4的电压过高而损坏电源电路113及控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在第三种实施例中，在t 3时刻之后的t 4时刻，电源电路113的输出电压V 5的电压值提升至大于或等于第五预设值V 53时。在一种实施例中，控制器114确定电源电路113的 输出电压V 5的电压值大于或等于第五预设值V 53，控制器114控制半桥电路1110中的电容停止放电。其中，将电压值V 53记为第五预设值，电压值V 53大于控制器114的额定输入电压V 50、且小于控制器114的过压保护电压。即，控制器114根据电源电路113的输出电压V 5的电压值与第五预设值V 53的比较结果，控制器114控制半桥电路1110中的电容停止放电。因此，控制器114可以通过控制半桥电路1110中的电容停止放电，避免电源电路113的输出电压V 4的电压过高而损坏控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在t 4时刻之后，半桥电路1110中的电容停止放电后，电容电压V c的电压值停止下降。相应地，原边绕组电压V 11的电压值下降，导致辅助绕组电压V 3下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在本申请一种实施例中，在t 4时刻之后，当辅助绕组电路112的输出电压V 4的电压值下降至小于或等于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降至小于或等于第三预设值V 52时，控制器114可以控制半桥电路1110的电容再次放电。具体过程如上述实施例中所述，不再重复说明。即，控制器114可以根据辅助绕组电路112的输出电压V 4的电压值与第二预设值V 41的比较结果，控制半桥电路1110的电容再次放电。或者，控制器114可以根据电源电路113的输出电压V 5的电压值与第三预设值V 52的比较结果，控制半桥电路1110的电容再次放电。
在本申请一种实施例中，在半桥电路1110中的电容开始放电后或停止放电后，控制器114还会根据直流变换电路111的输出电压V 2的电压值控制直流变换电路111的运行状态从暂停工作状态切换为连续工作状态。在t 2时刻之后，控制器114控制直流变换电路111运行于暂停工作状态，相应地直流变换电路111的输出电压V 2的电压值下降。在一种实施例中，在半桥电路1110中的电容开始放电后、停止放电前，直流变换电路111的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制直流变换电路111的的运行状态从暂停工作状态切换为连续工作状态。在一种实施例中，在半桥电路1110中的电容停止放电后，直流变换电路111的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制直流变换电路111的运行状态从暂停工作状态切换为连续工作状态。
在t 3时刻之后的t 5时刻，直流变换电路111的输出电压V 2的电压值下降至小于或等于额定输出电压V 20。控制器114确定直流变换电路111的输出电压V 2的电压值下降至小于或等于额定输出电压V 20，控制器114控制直流变换电路111的运行状态从暂停工作状态切换为连续工作状态。即，控制器114根据直流变换电路111的输出电压V 2的电压值与额定输出电压V 20的比较结果，控制器114控制直流变换电路111的运行状态从暂停工作状态切换为连续工作状态。也就是说，在t 2时刻之后、t 5时刻之前，控制器114控制直流变换电路111运行于暂停工作状态。在t 5时刻之后，控制器114控制直流变换电路111运行于连续工作状态。在t 5时刻之后，直流变换电路111的输出电压V 2的电压值提升至额定输出电压V 20，辅助绕组电路112的输出电压V 4的电压值提升至V 40，电源电路113的输出电压V 5的电压值提升至V 50。
在本申请一些实施例中，控制器114可以在半桥电路1110中的电容的电容电压的电压值下降至小于V C1前停止放电，可以使得直流变换电路111的运行状态可以更快地从暂停工作状态切换为连续工作状态，因此本申请实施例提供的控制114可以提高其所在的电 源模组11、电子设备10的性能。
图9为本申请提供的电源模组一种实施例的示意图。如图9所示的电源模组11可应用于如图1或者图2所示的电子设备10中。如图9所示的电源电源模组11包括AHB变换电路111a、辅助绕组电路112、电源电路113和控制器114。AHB变换电路111a用于接收输入电源13的输入电压V 1，并提供输出电压V 2为负载12供电。另外，AHB变换电路111a经辅助绕组电路112为控制器114的电源电路113供电。其中，辅助绕组电路112与AHB变换电路111a耦合，辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电路112将辅助绕组电压V 3转换为输出电压V 4，为电源电路113供电。电源电路113为控制电路114供电。控制器114用于控制AHB变换电路111a的运行状态。
图10为本申请提供的电源模组一种实施例的示意图。如图10所示，电源模组11包括AHB变换电路111a、辅助绕组电路112、电源电路113和控制器114。其中，电源模组11中AHB变换电路111a包括半桥电路1110a、变压器1112a和整流电路1114a。其中，变压器1112a包括原边绕组1111a和副边绕组1113a。另外，变压器1112a还包括辅助绕组电路112中的辅助绕组1121。副边绕组1113a与原边绕组1111a相耦合，辅助绕组1121与原边绕组1111a相耦合。
半桥电路1110a用于接收输入电源13提供的输入电压V 1，并根据控制器114的控制信号向原边绕组1111a提供输出电压V 10。半桥电路1110a通常包括主功率管、辅助功率管及谐振电容。
变压器1112a的原边绕组1111a用于接收半桥电路1110a的输出电压V 10，并产生原边绕组电压V 11。变压器1112a的副边绕组1113a与变压器1112a的原边绕组1111a相耦合，副边绕组1113a上产生副边绕组电压V 3。
整流电路1114a用于接收副边绕组1113a上的副边绕组电压V 3，并转换为输出电压V 2。
辅助绕组电路112用于为电源电路113供电。辅助绕组电路112的辅助绕组1121与变压器1112a的原边绕组1111a相耦合。原边绕组1112a上的原边绕组电压V 11经过耦合，在辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电压V 3经辅助绕组电路112处理后，向电源电路113提供输出电压V 4。其中，辅助绕组电路112可以包括辅助绕组1121和整流模块1122。
电源电路113用于为控制器114供电。电源电路113接收辅助绕组电路112的输出电压V 4，并向控制器114提供输出电压V 5。即，AHB变换电路111a经与其变压器1112a的原边绕组1111耦合的辅助绕组电路112，为控制器114的电源电路113供电。一些实施例中，电源电路113包括稳压电路。
控制器114用于控制AHB变换电路111a的运行状态。控制器114还用于检测AHB变换电路111a的输出电压V 2、辅助绕组电路112的输出电压V 4、电源电路113的输出电压V 5或半桥电路1110a中谐振电容C r的电容电压V Cr的电压值等多个电压值的变化。控制器114还用于根据上述一个或多个电压值的变化，控制AHB变换电路111a的运行状态。
在一种实施例中，控制114发送控制信号G控制AHB变换电路111a中半桥电路1110a的运行状态，从而控制AHB变换电路111a的运行状态。例如，AHB变换电路 111a的运行状态通常包括连续工作状态和暂停工作状态。连续工作状态也可以称为正常工作状态、控制器正常发波状态等。暂停工作状态也可以称为间歇工作状态、BURST工作状态、控制器间歇发波状态等。
在本申请实施例中，控制器114可以发送控制信号G控制半桥电路1110a中主功率管及辅助功率管的导通及关断。控制器114调整控制信号G的频率或占空比，可以控制半桥电路1110a中主功率管及辅助功率管的导通频率或导通时长，从而相应地调整半桥电路1110a的输出电压V 10。半桥电路1110a的输出电压V 10，会导致原边绕组电压V 11变化。相应地，原边绕组电压V 11变化可以导致副边绕组电压V 12和辅助绕组电压V 3变化。相应地，副边绕组电压V 12的变化可以导致AHB变换电路111a的输出电压V 2变化。相应地，辅助绕组电压V 3的变化可以导致辅助绕组电路112的输出电压V 4变化。相应地，辅助绕组电路112的输出电压V 4可以导致电源电113的输出电压V 5的变化。
如图10中F1方向所示，AHB变换电路111a可以提供输出电压V 2为负载12供电。其中，输入电压V 1经AHB变换电路111a中的半桥电路1110a、原边绕组1111a、副边绕组1113a及整流电路1114a转换为输出电压V 2。
如图10中F2方向所示，AHB变换电路111a可以通过辅助绕组电路112为控制器114的电源电路113供电。其中，输入电压V 1经AHB变换电路111a中的半桥电路1110a处理后，可以在原边绕组1111a产生原边绕组电压V 11。相应地，原边绕组电压V 11可以在变压器1112a的辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电压V 3经辅助绕组电路1121处理后提供输出电压V 4，为控制器114的电源电路113供电。
图11为本申请提供的控制器及其所在的电源模组在负载水平发生跌落的场景中的电压波形示意图。下文结合图10和图11，详细说明本申请提供的控制器114及其所在的电源模组11在负载12的负载水平L发生跌落的场景中的运行过程。
在t 1时刻之前，负载12的负载水平L为正常负载L 1，控制器114控制AHB变换电路111a运行于连续工作状态，控制器114控制AHB变换电路111a的输出电压V 2的电压值为额定输出电压V 20。辅助绕组电路112的输出电压V 4的电压值为V 40。电源电路113的输出电压V 5的电压值为V 50。半桥电路1111a中谐振电容C r的电容电压V Cr的电压值为V Cr1。V Cr1为AHB变换电路111a运行于连续工作状态时谐振电容C r的电容电压。
在t 1时刻，负载12的负载水平从正常负载L 1跌落到轻负载L 2。相应地，在t 1时刻之后，AHB变换电路111a的输出电压V 2的电压值提升至大于额定输出电压V 20。
在一种实施例中，当AHB变换电路111a的输出电压V 2的电压值大于额定输出电压V 20，控制器114可以控制AHB变换电路111a运行于连续工作状态。并且，控制器控制AHB变换电路111a降低输出电压V 2的电压值。即，控制器114根据AHB变换电路111a的输出电压V 2的电压值与额定输出电压V 20的比较结果，控制器114控制AHB变换电路111a运行于连续工作状态，控制器114控制AHB变换电路111a降低输出电压V 2的电压值。具体地，控制器114发送控制信号G控制半桥电路1110a中主功率管和辅助功率管的运行状态，使得原边绕组电压V 11的电压值下降。在一种实施例中，控制器114可以降低控制信号G的发送频率，从而降低主功率管和辅助功率管的导通频率。在一种实施方式中，控制器114可以降低控制信号G的占空比，从而降低主功率管和辅助功率管的导通时长。 在另一种实施例中，当AHB变换电路111a的输出电压V 2的电压值大于额定电压V 20，控制器114可以控制AHB变换电路111a运行于暂停工作状态，也能够降低输出电压V 2的电压值。但是，上述两种实施例都可能无法使得AHB变换电路111a的输出电压V 2的电压值有效下降，在t 1时刻之后AHB变换电路111a的输出电压V 2的电压值将继续提升。
同时，在t 1时刻之后，负载水平L的跌落导致AHB变换电路111a的输出电压V 2的电压值高于额定电压V 20。原边绕组电压V 11给半桥电路1110a中谐振电容C r充电，半桥电路1110a中谐振电容C r的电容电压V Cr的电压值从V Cr1提升到V Cr2。V Cr2为半桥电路1110a中谐振电容C r的最大充电电压。
在t 1时刻之后的t 2时刻，AHB变换电路111a的输出电压V 2的电压值提升至第一预设值V 21。控制器114确定AHB变换电路111a的输出电压V 2的电压值大于或等于第一预设值V 21，控制器114控制AHB变换电路111a暂停工作。即，控制器114根据AHB变换电路111a的输出电压V 2的电压值与第一预设值V 21的比较结果，控制器114控制AHB变换电路111a运行于暂停工作状态。具体的，控制器114控制半桥电路1110a中主功率管和辅助功率管都关断。在本申请实施例中，第一预设值V 21可以是AHB变换电路111a的峰值电压。AHB变换电路111a的峰值电压大于额定电压V 20，且小于AHB变换电路111a的过压保护电压。
在t 2时刻之后，控制器114控制AHB变换电路111a运行于暂停工作状态。相应地，AHB变换电路111a中原边绕组1111a上的原边绕组电压V 11的电压值下降，从而导致副边绕组电压V 12下降，并导致辅助绕组电压V 3下降。相应地，AHB变换电路111a的输出电压V 2的电压值下降，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在t 2时刻后的t 3时刻，辅助绕组电路112的输出电压V 4的电压值下降至小于或等于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降至小于或等于第三预设值V 52。此时，控制器114控制半桥电路1110a中的谐振电容C r放电。
在一种实施例中，控制器114确定辅助绕组电路112的输出电压V 4的电压值小于或等于第二预设值V 41，控制器114控制半桥电路1110a中的谐振电容C r放电。即，控制器114根据辅助绕组电路112的输出电压V 4的电压值与第二预设值V 41的比较结果，控制半桥电路1110a中的谐振电容C r放电。
在一种实施例中，控制器114确定电源电路113的输出电压V 5的电压值小于或等于第三预设值V 52，控制器114控制半桥电路1110a中的谐振电容C r放电。即，控制器114根据电源电路113的输出电压V 5的电压值与第三预设值V 52的比较结果，控制器114控制半桥电路1110a中的谐振电容C r放电。
在一种实施例中，控制器114控制半桥电路1110a中辅助功率管导通，使得半桥电路1110a中的谐振电容C r放电。原边绕组1111a、半桥电路1110a的谐振电容C r、半桥电路1110a的辅助功率管可以形成放电回路。相应地，半桥电路1110a的谐振电容C r放电，可以在原边绕组1111a上产生原边绕组电压V 11。
在一种实施例中，控制器114控制半桥电路1110a中辅助功率管周期性地导通，使得半桥电路1110a中的谐振电容C r放电。半桥电路1110a的辅助功率管导通时，原边绕组1111a及半桥电路1110a的谐振电容C r、半桥电路1110a的辅助功率管可以形成放电回路。 相应地，半桥电路1110a的辅助功率管周期性地导通，可以使得半桥电路1110a中的谐振电容C r周期性地放电。
在t 3时刻之后，半桥电路1110a中的谐振电容C r的电容电压V Cr的电压值下降。半桥电路1110a中的谐振电容C r放电，使得原边绕组1111a上的原边绕组电压V 11的电压值提升。相应地，原边绕组电压V 11的电压值提升，会导致辅助绕组电压V 3的电压值提升。相应地，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。因此，负载12的负载水平发生变化的场景中，电源电路113的输出电压V 5的电压值不会下降至低于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。
本申请实施例提供的控制器114通过控制AHB变换电路111a的半桥电路1110a中谐振电容C r放电，可以使得电源电路113的输出电压V 5的电压值高于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
由于AHB变换电路111a的半桥电路1110a中谐振电容C r存储的能量有限，放电后在原边绕组1111a上产生的原边绕组电压V 11的电压值较小。此时原边绕组1111a上产生的原边绕组电压V 11小于副边绕组1113上的副边绕组电压V 12，不会导致AHB变换电路111a的输出电压V 2提升。因此，控制器114控制半桥电路1110a中谐振电容C r放电后，原边绕组1111a上产生的原边绕组电压V 11仅用于提升辅助绕组电路112的输出电压V 4和电源电路113的输出电压V 5，如图10中F2方向所示。因此，本申请实施例提供的控制器114及其所在的电源模组111不仅可以避免控制器114因欠压保护而重启，还可以避免增大AHB变换电路111a的输出电压V 2的波纹，可以提高控制器114其所在的电源模组11及电子设备10的稳定性。
而且，本申请实施例提供的控制器114通过控制AHB变换电路111a的半桥电路1110a中谐振电容C r，不会引入来自输入电源13的噪声，可以避免噪声影响AHB变换电路111a及其所在的电源模组11、电子设备10的电磁兼容性。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
在本申请一种实施例中，在AHB变换电路111a的半桥电路1110a中谐振电容C r开始放电后，控制器114还可以根据半桥电路1110a中谐振电容C r的电容电压V Cr的电压值、辅助绕组电路112的输出电压V 4的电压值或者电源电路113的输出电压V 5的电压值，控制半桥电路1110a中谐振电容C r停止放电。在一种实施例中，控制器114控制半桥电路1110a中辅助功率管关断，原边绕组1111a、半桥电路1110a的谐振电容C r、半桥电路1110a的辅助功率管形成的放电回路断开。相应地，半桥电路1110a的谐振电容C r停止放电。
在第一种实施例中，在t 3时刻之后的t 4时刻，半桥电路1110a的谐振电容C r的电容电压V Cr下降至小于或等于预设电容电压值V Cr3。在一种实施例中，控制器114确定半桥电路1110a的谐振电容C r的电容电压V Cr下降至小于或等于预设电容电压值V Cr3，控制器114控制半桥电路1110a的谐振电容C r停止放电。在一种实施例中，预设电容电压值V Cr3可以大于或等于AHB变换电路111a运行在连续运行状态时半桥电路1110a的谐振电容C r的电容电压的电压值V Cr1。即，控制器114根据半桥电路1110a的谐振电容C r的电容电压V Cr与预设电容电压值V Cr3的比较结果，控制器114控制半桥电路1110a的谐振电容C r停止放 电。因此，控制器114可以通过半桥电路1110a的谐振电容C r停止放电，可以避免谐振电容C r的电容电压V Cr过低而影响AHB变换电路111a恢复连续工作状态，进一步提高了电源模组11及其所在的电子设备10的稳定性。
在第二种实施例中，在t 3时刻之后的t 4时刻，辅助绕组电路112的输出电压V 4的电压值提升至大于或等于第四预设值V 42。在一种实施例中，控制器114确定辅助绕组电路112的输出电压V 4的电压值大于或等于第四预设值V 42，控制器114控制半桥电路1110a的谐振电容C r停止放电。即，控制器114根据辅助绕组电路112的输出电压V 4的电压值与第四预设值V 42的比较结果，控制器114控制半桥电路1110a的谐振电容C r停止放电。因此，控制器114可以通过半桥电路1110a的谐振电容C r停止放电，可以避免辅助绕组电路112的输出电压V 4的电压过高而损坏电源电路113及控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在第三种实施例中，在t 3时刻之后的t 4时刻，电源电路113的输出电压V 5的电压值提升至大于或等于第五预设值V 53时。在一种实施例中，控制器114确定电源电路113的输出电压V 5的电压值大于或等于第五预设值V 53，控制器114控制半桥电路1110a的谐振电容C r停止放电。即，控制器114根据电源电路113的输出电压V 5的电压值与第五预设值V 53的比较结果，控制器114控制半桥电路1110a的谐振电容C r停止放电。因此，控制器114可以通过控制半桥电路1110a的谐振电容C r停止放电，避免电源电路113的输出电压V 4的电压过高而损坏控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在t 4时刻之后，半桥电路1110a的谐振电容Cr停止放电后，谐振电容C r的电容电压V Cr的电压值停止下降。相应地，原边绕组电压V 11的电压值下降，导致辅助绕组电压V 3下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在本申请一种实施例中，在t 4时刻之后，当辅助绕组电路112的输出电压V 4的电压值下降至小于或等于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降至小于或等于第三预设值V 52时，控制器114可以控制半桥电路1110a的谐振电容C r再次放电。具体过程如上述实施例中所述，不再重复说明。即，控制器114可以根据辅助绕组电路112的输出电压V 4的电压值与第二预设值V 41的比较结果，控制半桥电路1110a的谐振电容C r再次放电。或者，控制器114可以根据电源电路113的输出电压V 5的电压值与第三预设值V 52的比较结果，控制半桥电路1110a的谐振电容C r再次放电。
在本申请一种实施例中，在半桥电路1110a的谐振电容C r开始放电后或停止放电后，控制器114还会根据AHB变换电路111a的输出电压V 2的电压值控制AHB变换电路111a的运行状态从暂停工作状态切换为连续工作状态。在t 2时刻之后，控制器114控制AHB变换电路111a运行于暂停工作状态，相应地AHB变换电路111a的输出电压V 2的电压值下降。在一种实施例中，在半桥电路1110a的谐振电容C r开始放电后、停止放电前，AHB变换电路111a的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制AHB变换电路111a的运行状态从暂停工作状态切换为连续工作状态。在一种实施例中，在半桥电路1110a的谐振电容C r停止放电后，AHB 变换电路111a的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制AHB变换电路111a的运行状态从暂停工作状态切换为连续工作状态。
在t 3时刻之后的t 5时刻，AHB变换电路111a的输出电压V 2的电压值下降至小于或等于额定电压V 20。控制器114确定AHB变换电路111a的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制AHB变换电路111a的运行状态从暂停工作状态切换为连续工作状态。即，控制器114根据AHB变换电路111a的输出电压V 2的电压值与额定电压V 20的比较结果，控制AHB变换电路111a的运行状态从暂停工作状态切换为连续工作状态。在t 5时刻之后，AHB变换电路111a的输出电压V 2的电压值恢复至额定电压V 20，辅助绕组电路112的输出电压V 4的电压值恢复至V 40，电源电路113的输出电压V 5的电压值恢复至V 50。
图12为本申请提供的电源模组一种实施例的示意图。如图12示出了图10所示的电源模组11中部分电路的示意图。如图12所示，电源模组11包括AHB变换电路111a、辅助绕组电路112、电源电路113和控制器114。其中，AHB变换电路111a包括半桥电路1110a、变压器1112a和整流电路1114a。其中，变压器1112a包括原边绕组1111a和副边绕组1113a。另外，变压器1112a还包括辅助绕组电路112中的辅助绕组1121。副边绕组1113a与原边绕组1111a相耦合，辅助绕组1121与原边绕组1111a相耦合。
半桥电路1110a包括主功率管Q L、辅助功率管Q H及谐振电容C r。主功率管Q L、辅助功率管Q H及谐振电容C r形成非对称半桥拓扑。具体地，谐振电容C r的第一端连接原边绕组1111a的异名端，谐振电容C r的第二端连接辅助功率管Q H的漏极。辅助功率管Q H的源极连接原边绕组1111a的同名端和主功率管Q L的漏极。主功率管Q L的源极接地。在一种实施例中，主功率管Q L的栅极用于接收控制器114的第二控制信号G H。辅助功率管Q H的栅极用于接收控制器114的第一控制信号G L。
整流电路1114a包括电容C 1和二极管D 2。二极管D 2的阳极与副边绕组1113a的同名端连接。电容C 1的两端分别连接二极管D 2的阴极和副边绕组1113a的异名端。
辅助绕组电路112包括辅助绕组1121和整流模块1122。整流模块1122可以包括二极管D 1。其中，二极管D 1的阳极与辅助绕组1121的同名端连接，二极管D 1的阴极、辅助绕组1121的异名端与电源电路113连接。
电源电路113可以包括升压(BOOST)电路。在一种实施例中，电源电路113还可以是降压(BUCK)电路、升降压(BUCK-BOOST)电路等。在一种实施例中，电源电路113还可以是低压差线性稳压电路(low dropout regulator，LDO)等稳压电路。
控制器114包括检测单元1141和驱动单元1142。在一些实施例中，当驱动单元1142为芯片，电源电路113可以连接驱动单元1142的供电引脚。例如，供电引脚可以是图12中所示的标号为“V dd”的引脚。
检测单元1141用于检测AHB变换电路111a的输出电压V 2、辅助绕组电路112的输出电压V 4的电压值、电源电路113的输出电压V 5的电压值或AHB变换电路111a的半桥电路1110a中谐振电容C r的电容电压V Cr的电压值中的多种电压值的变化。驱动电路1142用于根据上述一个或多个电压值的变化，控制AHB变换电路111a的运行状态。
例如，检测单元1141可以通过连接图12中副边绕组电路1114a输出端的A点，检测AHB变换电路111a的输出电压V 2的电压值。检测单元1141可以通过连接图12中辅助绕 组电路112输出端的B点，检测辅助绕组电路112的输出电压V 4的电压值。检测单元1141可以通过连接图12中电源电路113输出端的C点，检测电源电路113的输出电压V 5的电压值。检测单元1141可以通过连接图12中谐振电容C r任一侧的D点，检测谐振电容C r的电容电压V Cr的电压值。
驱动单元1142用于控制AHB变换电路111a的运行状态。其中，驱动单元1142通过发出控制信号G L/G H控制主功率管Q L和辅助功率管Q H的导通和截止，从而控制AHB变换电路111a的运行状态。在一些实施例中，当驱动单元1142为芯片，图12中所示的驱动单元1142可以通过其标号为“G H”的引脚发出控制信号G H，可以通过其其标号为“G L”的引脚发出控制信号G L。图12中引脚的标号仅为示例，在实际应用中还可以使用驱动单元1142的其他标号的引脚实现图12中示出的引脚的功能。
驱动单元1142通过向主功率管Q L发送第一控制信号G L的方式控制主功率管Q L导通或截止。驱动单元1142通过向辅助功率管Q H发送第二控制信号G H的方式控制辅助功率管Q H导通或截止。在本申请实施例中，控制器114发送的第一控制信号G L、第二控制信号G H可以包括高电平信号或低电平信号等实现方式。在一种实施例中，主功率管Q L根据第一控制信号G L导通，辅助功率管Q H根据第二控制信号G H导通。在一种实施例中，主功率管Q L根据第一控制信号G L关断，辅助功率管Q H根据第二控制信号G H关断。
图13为本申请提供的控制器在电源模组的负载水平发生跌落的场景中的控制信号示意图。下文结合图11、图12和图13，说明本申请提供的控制器114及其所在的电源模组11在负载12的负载水平L发生跌落的场景中的运行过程。
在t1时刻之前，负载12的负载水平为正常负载L 1。控制器114控制AHB变换电路111a运行于连续工作状态，并控制AHB变换电路111a的输出电压V 2的电压值为额定电压V 20。此时，辅助绕组电路112的输出电压V 4的电压值为V 40。电源电路113的输出电压V 5的电压值为V 50。半桥电路1111a中谐振电容C r的电容电压V Cr的电压值为V Cr1。
图14为本申请实施例提供的控制器的控制信号的示意图。如图14所示，控制器114发送的控制信号G 1、G 2、G 3…中的每一个包括向主功率管Q L发送的第一控制信号G L或向辅助功率管Q H发送的第二控制信号G H。控制器114控制主功率管Q L和辅助功率管Q H周期性地交替导通和关断，半桥电路1110a可以在原边绕组1111a产生原边绕组电压V 11。原边绕组1111a上的原边绕组电压V 11经过耦合，可以在副边绕组1113a上产生副边绕组电压V 12，并可以在辅助绕组1121上产生辅助绕组电压V 3。相应地，整流电路1114a向负载12提供输出电压V 2，辅助绕组电路112向电源电路113提供输出电压V 4，电源电路113向控制器115的输出电压V 5为V 50。由于AHB变换电路111a向负载12的输出电压V 2的电压值稳定在额定电压V 20，半桥电路1110a中谐振电容C r的电压值V Cr稳定在V Cr1。
在t1时刻，负载12的负载水平从正常负载L 1跌落到轻负载L 2。在t1时刻之后，AHB变换电路111a的输出电压V 2的电压值提升至大于额定电压V 20。
在一种实施例中，控制器114根据AHB变换电路111a的输出电压V 2的电压值与额定电压V 20的比较结果，控制AHB变换电路111a运行于连续工作状态，控制器114控制AHB变换电路111a降低输出电压V 2的电压值。
具体地，控制器114的检测单元1141检测AHB变换电路111a的输出电压V 2并判断AHB变换电路111a的输出电压V 2大于额定电压V 20。相应地，控制器114控制AHB变 换电路111a运行于连续工作状态，控制器114降低第一控制信号G L和第二控制信号G H的发送频率，或者降低第一控制信号G L和第二控制信号G H的占空比。如图13所示，在t 1时刻之后控制器114发送的控制信号G 4、G 5、G 6的频率小于t 1时刻之前周期性发送的控制信号G 1、G 2、G 3的频率。相应地，主功率管Q L和辅助功率管Q H导通和关断的频率减少，使得AHB变换电路111a的输出电压V 2的电压值下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。但是，上述方式可能无法使得AHB变换电路111a的输出电压V 2的电压值有效下降，AHB变换电路111a的输出电压V 2的电压值将继续提升。
在t 1时刻之后，AHB变换电路111a的输出电压V 2的电压值高于额定电压V 20。此时，原边绕组电压V 11给半桥电路1110a中谐振电容C r充电，半桥电路1110a中谐振电容C r的电容电压V Cr的电压值从V Cr1提升到V Cr2。
在t 1时刻之后的t 2时刻，AHB变换电路111a的输出电压V 2的电压值提升至大于或等于第一预设值V 21。控制器114根据AHB变换电路111a的输出电压V 2的电压值与第一预设值V 21的比较结果，控制器114控制AHB变换电路111a运行于暂停工作状态。具体地，控制器114的检测单元1141检测AHB变换电路111a的输出电压V 2的电压值，并判断AHB变换电路111a的输出电压V 2的电压值大于或等于第一预设值V 21。相应地，控制器114的驱动单元1142停止发送第一控制信号G L和第二控制信号G H，从而控制AHB变换电路111a运行于暂停工作状态。相应地，AHB变换电路111a不会对其接收到的输入电压V 1进行处理，AHB变换电路111a的输出电压V 2降低。
在t 2时刻之后，控制器114控制AHB变换电路111a运行于暂停工作状态。相应地，AHB变换电路111a中原边绕组1111a上的原边绕组电压V 11的电压值下降，从而导致副边绕组电压V 12下降，并导致辅助绕组电压V 3下降。相应地，AHB变换电路111a的输出电压V 2的电压值下降，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在t 2时刻后的t 3时刻，辅助绕组电路112的输出电压V 4的电压值下降至低于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降至低于第三预设值V 52。此时，控制器114控制半桥电路1110a中的谐振电容C r放电。
在一种实施例中，控制器114的检测单元1141检测辅助绕组电路112的输出电压V 4的电压值，并判断辅助绕组电路112的输出电压V 4的电压值小于或等于第二预设值V 41。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H导通。此时，半桥电路1110a的谐振电容C r、原边绕组1111a和半桥电路1110a的功率管Q H形成放电回路，半桥电路1110a的谐振电容C r开始放电。
在一种实施例中，控制器114的检测单元1141检测电源电路113的输出电压V 5的电压值并判断电源电路113的输出电压V 5的电压值小于或等于第三预设值V 52。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H导通。此时，半桥电路1110a的谐振电容C r、原边绕组1111a和半桥电路1110a的功率管Q H形成放电回路，半桥电路1110a的谐振电容C r开始放电。
在t 3时刻之后，半桥电路1110a中的谐振电容C r的电容电压V Cr的电压值下降。半桥电路1110a中的谐振电容C r放电，使得原边绕组1111a上的原边绕组电压V 11的电压值提 升。相应地，辅助绕组电压V 3的电压值提升，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。因此，负载12的负载水平发生变化的场景中，电源电路113的输出电压V 5的电压值不会下降至低于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。
本申请实施例提供的控制器114通过控制AHB变换电路111a的半桥电路1110a中谐振电容C r放电，可以使得电源电路113的输出电压V 5的电压值高于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
由于AHB变换电路111a的半桥电路1110a中谐振电容C r存储的能量有限，放电后在原边绕组1111a上产生的原边绕组电压V 11的电压值较小。此时原边绕组1111a上产生的原边绕组电压V 11小于副边绕组1113上的副边绕组电压V 12，不会导致AHB变换电路111a的输出电压V 2提升。因此，控制器114控制半桥电路1110a中谐振电容C r放电后，原边绕组1111a上产生的原边绕组电压V 11仅用于提升辅助绕组电路112的输出电压V 4和电源电路113的输出电压V 5。因此，本申请实施例提供的控制器114及其所在的电源模组111不仅可以避免控制器114因欠压保护而重启，还可以避免增大AHB变换电路111a的输出电压V 2的波纹，可以提高控制器114其所在的电源模组11及电子设备10的稳定性。
而且，本申请实施例提供的控制器114通过控制AHB变换电路111a的半桥电路1110a中谐振电容C r，不会引入来自输入电源13的噪声，可以避免影响AHB变换电路111a及其所在的电源模组11、电子设备10的电磁兼容性。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
在本申请一种实施例中，控制器114还可以控制AHB变换电路111a的半桥电路1110a中的谐振电容C r停止放电。
在第一种实施例中，在t 3时刻之后的t 4时刻，半桥电路1110a的谐振电容C r的电容电压V Cr下降至小于或等于预设电容电压值V Cr3。在一种实施例中，预设电容电压值V Cr3可以大于或等于AHB变换电路111a运行在连续运行状态时半桥电路1110a的谐振电容C r的电容电压的电压值V Cr1。控制器114根据半桥电路1110a的谐振电容C r的电容电压V Cr与预设电容电压值V Cr3的比较结果，控制器114控制半桥电路1110a的谐振电容C r停止放电。具体地，控制器114的检测单元1141检测半桥电路1110a的谐振电容C r的电容电压V Cr并判断半桥电路1110a的谐振电容C r的电容电压V Cr小于或等于预设电容电压值V Cr3。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H关断。此时，半桥电路1110a的谐振电容C r、原边绕组1111a和半桥电路1110a的功率管Q H形成的放电回路断开，半桥电路1110a的谐振电容C r停止放电。
因此，控制器114可以通过半桥电路1110a的谐振电容C r停止放电，可以避免谐振电容C r的电容电压V Cr过低而影响AHB变换电路111a恢复连续工作状态，进一步提高了电源模组11及其所在的电子设备10的稳定性。
在第二种实施例中，在t 3时刻之后的t 4时刻，辅助绕组电路112的输出电压V 4的电压值提升至大于或等于第四预设值V 42。控制器114根据辅助绕组电路112的输出电压V 4的电压值与第四预设值V 42的比较结果，控制器114控制半桥电路1110a的谐振电容C r停止放电。具体地，控制器114的检测单元1141检测辅助绕组电路112的输出电压V 4的电 压值并判断辅助绕组电路112的输出电压V 4的电压值小于或等于预设电容电压值V Cr3。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H关断。此时，半桥电路1110a的谐振电容C r、原边绕组1111a和半桥电路1110a的功率管Q H形成的放电回路断开，半桥电路1110a的谐振电容C r停止放电。
因此，控制器114可以通过半桥电路1110a的谐振电容C r停止放电，可以避免辅助绕组电路112的输出电压V 4的电压过高而损坏电源电路113及控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在第三种实施例中，在t 3时刻之后的t 4时刻，电源电路113的输出电压V 5的电压值提升至大于或等于第五预设值V 53。控制器114根据电源电路113的输出电压V 5的电压值与第五预设值V 53的比较结果，控制器114控制半桥电路1110a的谐振电容C r停止放电。具体地，控制器114的检测单元1141检测电源电路113的输出电压V 5的电压值并判断电源电路113的输出电压V 5的电压值大于或等于第五预设值V 53。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H关断。此时，半桥电路1110a的谐振电容C r、原边绕组1111a和半桥电路1110a的功率管Q H形成的放电回路断开，半桥电路1110a的谐振电容C r停止放电。
因此，控制器114可以通过控制半桥电路1110a的谐振电容C r停止放电，避免电源电路113的输出电压V 4的电压过高而损坏控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在t 4时刻之后，半桥电路1110a的谐振电容C r停止放电后，谐振电容C r的电容电压V Cr的电压值停止下降。相应地，原边绕组电压V 11的电压值下降，导致辅助绕组电压V 3下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在本申请一种实施例中，在t 4时刻之后，当辅助绕组电路112的输出电压V 4的电压值下降至小于或等于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降至小于或等于第三预设值V 52时，控制器114可以控制半桥电路1110a的谐振电容C r再次放电。具体过程如上述实施例中所述，不再重复说明。
在本申请一种实施例中，在半桥电路1110a的谐振电容C r开始放电后或停止放电后，控制器114还会根据AHB变换电路111a的输出电压V 2的电压值控制AHB变换电路111a的运行状态从暂停工作状态切换为连续工作状态。在t 2时刻之后，控制器114控制AHB变换电路111a运行于暂停工作状态，相应地AHB变换电路111a的输出电压V 2的电压值下降。在一种实施例中，在半桥电路1110a的谐振电容C r开始放电后、停止放电前，AHB变换电路111a的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制AHB变换电路111a的运行状态从暂停工作状态切换为连续工作状态。在一种实施例中，在半桥电路1110a的谐振电容C r停止放电后，AHB变换电路111a的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制AHB变换电路111a的运行状态从暂停工作状态切换为连续工作状态。
在t 3时刻之后的t 5时刻，AHB变换电路111a的输出电压V 2的电压值下降至小于或等于额定输出电压V 20。控制器114根据AHB变换电路111a的输出电压V 2的电压值与额定输出电压V 20的比较结果，控制AHB变换电路111a的运行状态从暂停工作 状态切换为连续工作状态。具体地，控制器114的检测单元1141检测AHB变换电路111a的输出电压V 2的电压值并判断AHB变换电路111a的输出电压V 2的电压值小于或等于额定输出电压V 20。控制器114的驱动单元1142周期性地发送第一控制信号G L和第二控制信号G H，控制主功率管Q L和辅助功率管Q H周期性导通和关断，使得AHB变换电路111a恢复连续工作状态。此时，控制器114发送的第一控制信号G L和第二控制信号G H，记为G 7、G 8、G 9…。每个控制信号G 7、G 8、G 9…的具体实现方式与图14中所示相同，不再赘述。又例如，控制信号G 7、G 8、G 9…的周期也可以与控制信号G 1、G 2、G 3……的周期相同、或者与G 4、G 5、G 6……的周期相同等。在t 5时刻之后，AHB变换电路111a的输出电压V 2的电压值恢复至额定输出电压V 20，辅助绕组电路112的输出电压V 4的电压值恢复至V 40，电源电路113的输出电压V 5的电压值恢复至V 50。
图15为本申请提供的控制器控制AHB变换电路的谐振电容放电的一种实施例的示意图。图15与图13的区别在于，控制器114控制AHB变换电路111a中原边绕组电路1111a的谐振电容C r周期性地放电。下文结合图11和图15，进行说明。
在t 3时刻，控制器114控制半桥电路1110a中辅助功率管Q H周期性地导通，使得半桥电路1110a中的谐振电容C r放电。具体地，控制器114不向主功率管Q L发送第一控制信号G L，使得主功率管Q L关断。并且，控制器114周期性地向辅助功率管Q H发送第二控制信号G H，使得辅助功率管Q H周期性地导通。半桥电路1110a的辅助功率管Q H导通时，原边绕组1111a及半桥电路1110a的谐振电容C r、半桥电路1110a的辅助功率管Q H可以形成放电回路。相应地，半桥电路1110a的辅助功率管Q H周期性地导通，可以使得半桥电路1110a中的谐振电容C r周期性地放电。
在本申请实施例中，控制器114控制辅助功率管Q H周期性地导通的周期T1，可以是预先配置的，也可以是控制器114根据当前谐振电容C r的电容电压V Cr或存储电能计算得到。在一种实施例中，谐振电容C r的电容电压V Cr的电压值较高或存储电能较多时，周期T1可以设置的更小。在一种实施例中，周期T1也可以与控制信号G 1、G 2、G 3……或者G 4、G 5、G 6……的周期相同。在本申请实施例中，每个周期中控制器114控制控制辅助功率管Q H导通或关断的时长可以相同或不同。
图16为本申请提供的AHB变换电路的谐振电容的电容电压的变化示意图。如图16所示，谐振电容C r周期性地放电，谐振电容C r的电容电压V Cr从V Cr2阶梯式地下降。在t 3时刻到t 4时刻之间，谐振电容C r的电容电压V Cr随着辅助功率管Q H周期性导通呈现阶梯式的下降。相应地，辅助绕组电路112的输出电压V 4的电压值也呈现阶梯式的提升，电源电路113的输出电压V 5的电压值也呈现阶梯型的提升。
因此，控制器114控制AHB变换电路111a中谐振电容C r周期性地放电，可以使得谐振电容C r的电容电压V Cr阶梯式的下降，避免下降过快而影响AHB变换电路111a的运行，从而提高了电源模组11的稳定性。而且，控制器114控制AHB变换电路111a中谐振电容C r周期性地放电，可以使得辅助绕组电路112的输出电压V 4、电源电路113的输出电压V 5阶梯式地提升，避免电压提升过快而损坏电路器件，从而提高了电源模组11的稳定性。
图17为本申请提供的控制器控制AHB变换电路的谐振电容放电的另一种实施例的示 意图。图17与图15的区别在于，控制器114控制AHB变换电路111a中原边绕组电路1111a中辅助功率管Q H和主功率管Q L周期性地交替导通，使得谐振电容C r周期性地放电。
在t 3时刻，控制器114周期性地控制主功率管Q L和辅助功率管Q H交替导通，且控制辅助功率管Q H和主功率管Q L不同时导通。具体地，控制器114周期性地依次向辅助功率管Q H发送第二控制信号G H、向主功率管Q L发送的第一控制信号G L，使得辅助功率管Q H和主功率管Q L依次导通，且辅助功率管Q H和主功率管Q L不同时导通。半桥电路1110a的辅助功率管Q H导通时，原边绕组1111a及半桥电路1110a的谐振电容C r、半桥电路1110a的辅助功率管Q H可以形成放电回路。谐振电容C r的电容电压V Cr的变化，可以参考图16所示。
在一种实施例中，每个周期中控制器114控制辅助功率管Q H先导通、主功率管Q L后导通。
首先，控制器114控制辅助功率管Q H导通、主功率管Q L截止。具体地，控制器114向辅助功率管Q H发送第二控制信号G H、且不向主功率管Q L发送第一控制信号G L。相应地，谐振电容C r、原边绕组a和辅助功率管Q H形成电流回路，谐振电容C r放电。相应地，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。
然后，控制器114控制辅助功率管Q H截止、主功率管Q L导通。具体地，控制器114不向辅助功率管Q H发送第二控制信号G H、且向主功率管Q L发送第一控制信号G L。此时，输入电压V 1、原边绕组a、和主功率管Q L形成回路。相应地，输入电压V 1在原边绕组a两侧产生原边绕组电压V 11。原边绕组电压V 11通过变压器1112a耦合，在辅助绕组c上产生辅助绕组电压V 3。相应地，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。
因此，控制器114控制AHB变换电路111a中原边绕组电路1111a的谐振电容C r周期性地放电，可以使得谐振电容C r的电容电压V Cr阶梯式的下降，避免下降过快而影响AHB变换电路111a的运行，从而提高了电源模组111的稳定性。而且，控制器114控制AHB变换电路111a中原边绕组电路1111a的谐振电容C r周期性地放电，可以使得辅助绕组电路112的输出电压V 4、电源电路113的输出电压V 5阶梯式地提升，避免提升过快而损坏电路器件，从而提高了电源模组111的稳定性。
在一种实施例中，每个周期中控制器114可以控制主功率管Q L先导通、辅助功率管Q H后导通。在本申请实施例中，控制器114控制主功率管Q L和辅助功率管Q H周期性地交替导通的周期T2可以是预先配置的，也可以是控制器114根据当前谐振电容C r的电容电压V Cr或存储电能计算得到。在一种实施例中，谐振电容C r的电容电压V Cr的电压值较高或存储电能较多时，周期T2可以设置的更小。在一种实施例中，周期T2可以与控制信号G 1、G 2、G 3……的周期或者G 4、G 5、G 6……的周期相同。在本申请实施例中，每个周期中控制器114控制主功率管Q L导通的时长、控制辅助功率管Q H导通的时长可以相同或不同。在本申请实施例中，控制器114发送的第一控制信号G L和第二控制信号G H的占空比可以相同或者不同。
图18为本申请提供的另一种AHB变换电路中半桥电路的示意图。如图18所示，半 桥电路1110a1包括主功率管Q L、辅助功率管Q H及谐振电容C r。主功率管Q L的源极连接原边绕组1111a的异名端和辅助功率管Q H的漏极。辅助功率管Q H的源极连接谐振电容C r的第一端并接地。谐振电容C r的第二端连接原边绕组1111a的同名端。如图18所示的半桥电路1110a1可以替换图12中的半桥电路1110a，半桥电路1110a1的功能和控制逻辑与半桥电路1110a功能和控制逻辑相同。
图19为本申请提供的另一种AHB变换电路中半桥电路的示意图。如图19所示，半桥电路1110a2包括主功率管Q L、辅助功率管Q H及谐振电容C r。原边绕组1111a的同名端连接主功率管Q L的漏极和谐振电容C r的第一端。谐振电容C r的第二端连接辅助功率管Q H的源极。主功率管Q L的源极接地。辅助功率管Q H的漏极接地。如图19所示的半桥电路1110a2可以替换图12中的半桥电路1110a，半桥电路1110a2的功能和控制逻辑与半桥电路1110a功能和控制逻辑相同。
本申请实施例提供的控制器114在电源模组11的负载水平L发生跌落的场景中，仅需要控制AHB变换电路111a中的主功率管Q L和辅助功率管Q H的导通或者截止。因此，本申请实施例提供的控制器114不仅可以提高其所在的AHB变换电路111a、电源模组11、电子设备10的稳定性，而且控制器114的配置简单从而更适用于各类产品使用。
图20为本申请提供的电源模组一种实施例的示意图，如图20所示的电源模组11可以应用于如图1或者图2所示的电子设备10中。如图20所示，电源模组11包括ACF变换电路111b、辅助绕组电路112、电源电路113和控制器114。
ACF变换电路111b用于接收输入电源13的输入电压V 1，并提供输出电压V 2为负载12供电。另外，ACF变换电路111b经辅助绕组电路112为控制器114的电源电路113供电。其中，辅助绕组电路112与ACF变换电路111b耦合，辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电路112将辅助绕组电压V 3转换为输出电压V 4，为电源电路113供电。电源电路113为控制电路114供电。控制器114用于控制ACF变换电路111b的运行状态。
图21为本申请提供的电源模组一种实施例的示意图。如图21所示，电源模组11包括ACF变换电路111b、辅助绕组电路112、电源电路113和控制器114。其中，电源模组11中ACF变换电路111b包括半桥电路1110b、变压器1112b和整流电路1114b。其中，变压器1112b包括原边绕组1111b和副边绕组1113b。另外，变压器1112b还包括辅助绕组电路112中的辅助绕组1121。副边绕组1113b与原边绕组1111b相耦合，辅助绕组1121与原边绕组1111b相耦合。
半桥电路1110b用于接收输入电源13提供的输入电压V 1，并根据控制器114的控制信号向原边绕组1111b提供输出电压V 10。半桥电路1110b通常包括主功率管、辅助功率管及钳位电容。
变压器1112b的原边绕组1111b用于接收半桥电路1110b的输出电压V 10，并产生原边绕组电压V 11。变压器1112b的副边绕组1113b与变压器1112b的原边绕组1111b相耦合，副边绕组1113b上产生副边绕组电压V 3。
整流电路1114b用于接收副边绕组1113b上的副边绕组电压V 3，并转换为输出电压V 2。
辅助绕组电路112用于为电源电路113供电。辅助绕组电路112的辅助绕组1121与变压器1112b的原边绕组1111b相耦合。原边绕组1112b上的原边绕组电压V 11经过耦合， 在辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电压V 3经辅助绕组电路112处理后，向电源电路113提供输出电压V 4。其中，辅助绕组电路112可以包括辅助绕组1121和整流模块1122。
电源电路113用于为控制器114供电。电源电路113接收辅助绕组电路112的输出电压V 4，并向控制器114提供输出电压V 5。即，ACF变换电路111b经与其变压器1112b的原边绕组1111耦合的辅助绕组电路112，为控制器114的电源电路113供电。一些实施例中，电源电路113包括稳压电路。
控制器114用于控制ACF变换电路111b的运行状态。控制器114还用于检测ACF变换电路111b的输出电压V 2、辅助绕组电路112的输出电压V 4、电源电路113的输出电压V 5或半桥电路1110b中钳位电容C c的电容电压V Cc的电压值等多个电压值的变化。控制器114还用于根据上述一个或多个电压值的变化，控制ACF变换电路111b的运行状态。
在一种实施例中，控制114发送控制信号G控制ACF变换电路111b中半桥电路1110b的运行状态，从而控制ACF变换电路111b的运行状态。例如，ACF变换电路111b的运行状态通常包括连续工作状态和暂停工作状态。连续工作状态也可以称为正常工作状态、控制器正常发波状态等。暂停工作状态也可以称为间歇工作状态、BURST工作状态、控制器间歇发波状态等。
在本申请实施例中，控制器114可以发送控制信号G控制半桥电路1110b中主功率管及辅助功率管的导通及关断。控制器114调整控制信号G的频率或占空比，可以控制半桥电路1110b中主功率管及辅助功率管的导通频率或导通时长，从而相应地调整半桥电路1110b的输出电压V 10。半桥电路1110b的输出电压V 10，会导致原边绕组电压V 11变化。相应地，原边绕组电压V 11变化可以导致副边绕组电压V 12和辅助绕组电压V 3变化。相应地，副边绕组电压V 12的变化可以导致ACF变换电路111b的输出电压V 2变化。相应地，辅助绕组电压V 3的变化可以导致辅助绕组电路112的输出电压V 4变化。相应地，辅助绕组电路112的输出电压V 4可以导致电源电113的输出电压V 5的变化。
如图21中F1方向所示，ACF变换电路111b可以提供输出电压V 2为负载12供电。其中，输入电压V 1经ACF变换电路111b中的半桥电路1110b、原边绕组1111b、副边绕组1113b及整流电路1114b转换为输出电压V 2。
如图21中F2方向所示，ACF变换电路111b可以通过辅助绕组电路112为控制器114的电源电路113供电。其中，输入电压V 1经ACF变换电路111b中的半桥电路1110b处理后，可以在原边绕组1111b产生原边绕组电压V 11。相应地，原边绕组电压V 11可以在变压器1112b的辅助绕组1121上产生辅助绕组电压V 3。辅助绕组电压V 3经辅助绕组电路1121处理后提供输出电压V 4，为控制器114的电源电路113供电。
图22为本申请提供的控制器及其所在的电源模组在负载水平发生跌落的场景中的电压波形示意图。下文结合图22和图21，详细说明本申请提供的控制器114及其所在的电源模组11在负载12的负载水平L发生跌落的场景中的运行过程。
在t 1时刻之前，负载12的负载水平L为正常负载L 1，控制器114控制ACF变换电路111b运行于连续工作状态，控制器114控制ACF变换电路111b的输出电压V 2的电压值 为额定输出电压V 20。辅助绕组电路112的输出电压V 4的电压值为V 40。电源电路113的输出电压V 5的电压值为V 50。半桥电路1111b中钳位电容C c的电容电压V Cc的电压值为V Cc1。V Cc1为ACF变换电路111b运行于连续工作状态时钳位电容C c的电容电压。
在t 1时刻，负载12的负载水平从正常负载L 1跌落到轻负载L 2。相应地，在t 1时刻之后，ACF变换电路111b的输出电压V 2的电压值提升至大于额定输出电压V 20。
在一种实施例中，当ACF变换电路111b的输出电压V 2的电压值大于额定输出电压V 20，控制器114可以控制ACF变换电路111b运行于连续工作状态。并且，控制器控制ACF变换电路111b降低输出电压V 2的电压值。即，控制器114根据ACF变换电路111b的输出电压V 2的电压值与额定输出电压V 20的比较结果，控制器114控制ACF变换电路111b运行于连续工作状态，控制器114控制ACF变换电路111b降低输出电压V 2的电压值。具体地，控制器114发送控制信号G控制半桥电路1110b中主功率管和辅助功率管的运行状态，使得原边绕组电压V 11的电压值下降。在一种实施例中，控制器114可以降低控制信号G的发送频率，从而降低主功率管和辅助功率管的导通频率。在一种实施方式中，控制器114可以降低控制信号G的占空比，从而降低主功率管和辅助功率管的导通时长。在另一种实施例中，当ACF变换电路111b的输出电压V 2的电压值大于额定电压V 20，控制器114可以控制ACF变换电路111b运行于暂停工作状态，也能够降低输出电压V 2的电压值。但是，上述两种实施例都可能无法使得ACF变换电路111b的输出电压V 2的电压值有效下降，在t 1时刻之后ACF变换电路111b的输出电压V 2的电压值将继续提升。
同时，在t 1时刻之后，负载水平L的跌落导致ACF变换电路111b的输出电压V 2的电压值高于额定电压V 20。原边绕组电压V 11给半桥电路1110b中钳位电容C c充电，半桥电路1110b中钳位电容C c的电容电压V Cc的电压值从V Cc1提升到V Cc2。V Cc2为半桥电路1110b中钳位电容C c的最大充电电压。
在t 1时刻之后的t 2时刻，ACF变换电路111b的输出电压V 2的电压值提升至第一预设值V 21。控制器114确定ACF变换电路111b的输出电压V 2的电压值大于或等于第一预设值V 21，控制器114控制ACF变换电路111b暂停工作。即，控制器114根据ACF变换电路111b的输出电压V 2的电压值与第一预设值V 21的比较结果，控制器114控制ACF变换电路111b运行于暂停工作状态。具体的，控制器114控制半桥电路1110b中主功率管和辅助功率管都关断。在本申请实施例中，第一预设值V 21可以是ACF变换电路111b的峰值电压。ACF变换电路111b的峰值电压大于额定电压V 20，且小于ACF变换电路111b的过压保护电压。
在t 2时刻之后，控制器114控制ACF变换电路111b运行于暂停工作状态。相应地，ACF变换电路111b中原边绕组1111b上的原边绕组电压V 11的电压值下降，从而导致副边绕组电压V 12下降，并导致辅助绕组电压V 3下降。相应地，ACF变换电路111b的输出电压V 2的电压值下降，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在t 2时刻后的t 3时刻，辅助绕组电路112的输出电压V 4的电压值下降至小于或等于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降至小于或等于第三预设值V 52。此时，控制器114控制半桥电路1110b中的钳位电容C c放电。
在一种实施例中，控制器114确定辅助绕组电路112的输出电压V 4的电压值小于或等 于第二预设值V 41，控制器114控制半桥电路1110b中的钳位电容C c放电。即，控制器114根据辅助绕组电路112的输出电压V 4的电压值与第二预设值V 41的比较结果，控制半桥电路1110b中的钳位电容C c放电。
在一种实施例中，控制器114确定电源电路113的输出电压V 5的电压值小于或等于第三预设值V 52，控制器114控制半桥电路1110b中的钳位电容C c放电。即，控制器114根据电源电路113的输出电压V 5的电压值与第三预设值V 52的比较结果，控制器114控制半桥电路1110b中的钳位电容C c放电。
在一种实施例中，控制器114控制半桥电路1110b中辅助功率管导通，使得半桥电路1110b中的钳位电容C c放电。原边绕组1111b、半桥电路1110b的钳位电容C c、半桥电路1110b的辅助功率管可以形成放电回路。相应地，半桥电路1110b的钳位电容C c放电，可以在原边绕组1111b上产生原边绕组电压V 11。
在一种实施例中，控制器114控制半桥电路1110b中辅助功率管周期性地导通，使得半桥电路1110b中的钳位电容C c放电。半桥电路1110b的辅助功率管导通时，原边绕组1111b及半桥电路1110b的钳位电容C c、半桥电路1110b的辅助功率管可以形成放电回路。相应地，半桥电路1110b的辅助功率管周期性地导通，可以使得半桥电路1110b中的钳位电容C c周期性地放电。
在t 3时刻之后，半桥电路1110b中的钳位电容C c的电容电压V Cc的电压值下降。半桥电路1110b中的钳位电容C c放电，使得原边绕组1111b上的原边绕组电压V 11的电压值提升。相应地，原边绕组电压V 11的电压值提升，会导致辅助绕组电压V 3的电压值提升。相应地，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。因此，负载12的负载水平发生变化的场景中，电源电路113的输出电压V 5的电压值不会下降至低于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。
本申请实施例提供的控制器114通过控制ACF变换电路111b的半桥电路1110b中钳位电容C c放电，可以使得电源电路113的输出电压V 5的电压值高于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
由于ACF变换电路111b的半桥电路1110b中钳位电容C c存储的能量有限，放电后在原边绕组1111b上产生的原边绕组电压V 11的电压值较小。此时原边绕组1111b上产生的原边绕组电压V 11小于副边绕组1113上的副边绕组电压V 12，不会导致ACF变换电路111b的输出电压V 2提升。因此，控制器114控制半桥电路1110b中钳位电容C c放电后，原边绕组1111b上产生的原边绕组电压V 11仅用于提升辅助绕组电路112的输出电压V 4和电源电路113的输出电压V 5，如图21中F2方向所示。因此，本申请实施例提供的控制器114及其所在的电源模组111不仅可以避免控制器114因欠压保护而重启，还可以避免增大ACF变换电路111b的输出电压V 2的波纹，可以提高控制器114其所在的电源模组11及电子设备10的稳定性。
而且，本申请实施例提供的控制器114通过控制ACF变换电路111b的半桥电路1110b中钳位电容C c，不会引入来自输入电源13的噪声，可以避免噪声影响ACF变换电路111b及其所在的电源模组11、电子设备10的电磁兼容性。因此，本申请实施例提供的控制器 114可以提高其所在的电源模组11及电子设备10的稳定性。
在本申请一种实施例中，在ACF变换电路111b的半桥电路1110b中钳位电容C c开始放电后，控制器114还可以根据半桥电路1110b中钳位电容C c的电容电压V Cc的电压值、辅助绕组电路112的输出电压V 4的电压值或者电源电路113的输出电压V 5的电压值，控制半桥电路1110b中钳位电容C c停止放电。在一种实施例中，控制器114控制半桥电路1110b中辅助功率管关断，原边绕组1111b、半桥电路1110b的钳位电容C c、半桥电路1110b的辅助功率管形成的放电回路断开。相应地，半桥电路1110b的钳位电容C c停止放电。
在第一种实施例中，在t 3时刻之后的t 4时刻，半桥电路1110b的钳位电容C c的电容电压V Cc下降至小于或等于预设电容电压值V Cc3。在一种实施例中，控制器114确定半桥电路1110b的钳位电容C c的电容电压V Cc下降至小于或等于预设电容电压值V Cc3，控制器114控制半桥电路1110b的钳位电容C c停止放电。在一种实施例中，预设电容电压值V Cc3可以大于或等于ACF变换电路111b运行在连续运行状态时半桥电路1110b的钳位电容C c的电容电压的电压值V Cc1。即，控制器114根据半桥电路1110b的钳位电容C c的电容电压V Cc与预设电容电压值V Cc3的比较结果，控制器114控制半桥电路1110b的钳位电容C c停止放电。因此，控制器114可以通过半桥电路1110b的钳位电容C c停止放电，可以避免钳位电容C c的电容电压V Cc过低而影响ACF变换电路111b恢复连续工作状态，进一步提高了电源模组11及其所在的电子设备10的稳定性。
在第二种实施例中，在t 3时刻之后的t 4时刻，辅助绕组电路112的输出电压V 4的电压值提升至大于或等于第四预设值V 42。在一种实施例中，控制器114确定辅助绕组电路112的输出电压V 4的电压值大于或等于第四预设值V 42，控制器114控制半桥电路1110b的钳位电容C c停止放电。即，控制器114根据辅助绕组电路112的输出电压V 4的电压值与第四预设值V 42的比较结果，控制器114控制半桥电路1110b的钳位电容C c停止放电。因此，控制器114可以通过半桥电路1110b的钳位电容C c停止放电，可以避免辅助绕组电路112的输出电压V 4的电压过高而损坏电源电路113及控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在第三种实施例中，在t 3时刻之后的t 4时刻，电源电路113的输出电压V 5的电压值提升至大于或等于第五预设值V 53时。在一种实施例中，控制器114确定电源电路113的输出电压V 5的电压值大于或等于第五预设值V 53，控制器114控制半桥电路1110b的钳位电容C c停止放电。即，控制器114根据电源电路113的输出电压V 5的电压值与第五预设值V 53的比较结果，控制器114控制半桥电路1110b的钳位电容C c停止放电。因此，控制器114可以通过控制半桥电路1110b的钳位电容C c停止放电，避免电源电路113的输出电压V 4的电压过高而损坏控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在t 4时刻之后，半桥电路1110b的钳位电容C c停止放电后，钳位电容C c的电容电压V Cc的电压值停止下降。相应地，原边绕组电压V 11的电压值下降，导致辅助绕组电压V 3下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在本申请一种实施例中，在t 4时刻之后，当辅助绕组电路112的输出电压V 4的电压值下降至小于或等于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降 至小于或等于第三预设值V 52时，控制器114可以控制半桥电路1110b的钳位电容C c再次放电。具体过程如上述实施例中所述，不再重复说明。即，控制器114可以根据辅助绕组电路112的输出电压V 4的电压值与第二预设值V 41的比较结果，控制半桥电路1110b的钳位电容C c再次放电。或者，控制器114可以根据电源电路113的输出电压V 5的电压值与第三预设值V 52的比较结果，控制半桥电路1110b的钳位电容C c再次放电。
在本申请一种实施例中，在半桥电路1110b的钳位电容C c开始放电后或停止放电后，控制器114还会根据ACF变换电路111b的输出电压V 2的电压值控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。在t 2时刻之后，控制器114控制ACF变换电路111b运行于暂停工作状态，相应地ACF变换电路111b的输出电压V 2的电压值下降。在一种实施例中，在半桥电路1110b的钳位电容C c开始放电后、停止放电前，ACF变换电路111b的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。在一种实施例中，在半桥电路1110b的钳位电容C c停止放电后，ACF变换电路111b的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。
在t 3时刻之后的t 5时刻，ACF变换电路111b的输出电压V 2的电压值下降至小于或等于额定电压V 20。控制器114确定ACF变换电路111b的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。即，控制器114根据ACF变换电路111b的输出电压V 2的电压值与额定电压V 20的比较结果，控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。在t 5时刻之后，ACF变换电路111b的输出电压V 2的电压值恢复至额定电压V 20，辅助绕组电路112的输出电压V 4的电压值恢复至V 40，电源电路113的输出电压V 5的电压值恢复至V 50。
图23为本申请提供的电源模组一种实施例的示意图。如图23示出了图21所示的电源模组11中部分电路的示意图。如图23所示，电源模组11包括ACF变换电路111b、辅助绕组电路112、电源电路113和控制器114。其中，ACF变换电路111b包括半桥电路1110b、变压器1112b和整流电路1114b。其中，变压器1112b包括原边绕组1111b和副边绕组1113b。另外，变压器1112b还包括辅助绕组电路112中的辅助绕组1121。副边绕组1113b与原边绕组1111b相耦合，辅助绕组1121与原边绕组1111b相耦合。
半桥电路1110b包括主功率管Q L、辅助功率管Q H及钳位电容C c。主功率管Q L、辅助功率管Q H及钳位电容C c形成有源钳位反激半桥拓扑。具体地，钳位电容C c的第一端连接原边绕组1111b的异名端，钳位电容C c的第二端连接辅助功率管Q H的漏极。辅助功率管Q H的源极连接原边绕组1111b的同名端和主功率管Q L的漏极。主功率管Q L的源极接地。在一种实施例中，主功率管Q L的栅极用于接收控制器114的第二控制信号G H。辅助功率管Q H的栅极用于接收控制器114的第一控制信号G L。
整流电路1114b包括电容C 1和二极管D 2。二极管D 2的阳极与副边绕组1113b的同名端连接。电容C 1的两端分别连接二极管D 2的阴极和副边绕组1113b的异名端。
辅助绕组电路112包括辅助绕组1121和整流模块1122。整流模块1122可以包括二极 管D 1。其中，二极管D 1的阳极与辅助绕组1121的同名端连接，二极管D 1的阴极、辅助绕组1121的异名端与电源电路113连接。
电源电路113可以包括升压(BOOST)电路。在一种实施例中，电源电路113还可以是降压(BUCK)电路、升降压(BUCK-BOOST)电路等。在一种实施例中，电源电路113还可以是低压差线性稳压电路(low dropout regulator，LDO)等稳压电路。
控制器114包括检测单元1141和驱动单元1142。在一些实施例中，当驱动单元1142为芯片，电源电路113可以连接驱动单元1142的供电引脚。例如，供电引脚可以是图23中所示的标号为“V dd”的引脚。
检测单元1141用于检测ACF变换电路111b的输出电压V 2、辅助绕组电路112的输出电压V 4的电压值、电源电路113的输出电压V 5的电压值或ACF变换电路111b的半桥电路1110b中钳位电容C c的电容电压V Cc的电压值中的多种电压值的变化。驱动电路1142用于根据上述一个或多个电压值的变化，控制ACF变换电路111b的运行状态。
例如，检测单元1141可以通过连接图23中副边绕组电路1114b输出端的A点，检测ACF变换电路111b的输出电压V 2的电压值。检测单元1141可以通过连接图23中辅助绕组电路112输出端的B点，检测辅助绕组电路112的输出电压V 4的电压值。检测单元1141可以通过连接图23中电源电路113输出端的C点，检测电源电路113的输出电压V 5的电压值。检测单元1141可以通过连接图23中钳位电容C c任一侧的D点，检测钳位电容C c的电容电压V Cc的电压值。
驱动单元1142用于控制ACF变换电路111b的运行状态。其中，驱动单元1142通过发出控制信号G L/G H控制主功率管Q L和辅助功率管Q H的导通和截止，从而控制ACF变换电路111b的运行状态。在一些实施例中，当驱动单元1142为芯片，图23中所示的驱动单元1142可以通过其标号为“G H”的引脚发出控制信号G H，可以通过其其标号为“G L”的引脚发出控制信号G L。需要说明的是，图23中引脚的标号仅为示例，在实际应用中还可以使用驱动单元1142的其他标号的引脚实现图23中示出的引脚的功能。
驱动单元1142通过向主功率管Q L发送第一控制信号G L的方式控制主功率管Q L导通或截止。驱动单元1142通过向辅助功率管Q H发送第二控制信号G H的方式控制辅助功率管Q H导通或截止。在本申请实施例中，控制器114发送的第一控制信号G L、第二控制信号G H可以包括高电平信号或低电平信号等实现方式。在一种实施例中，主功率管Q L根据第一控制信号G L导通，辅助功率管Q H根据第二控制信号G H导通。在一种实施例中，主功率管Q L根据第一控制信号G L关断，辅助功率管Q H根据第二控制信号G H关断。
图24为本申请提供的控制器在电源模组的负载水平发生跌落的场景中的控制信号示意图。下文结合图22、图23和图24，说明本申请提供的控制器114及其所在的电源模组11在负载12的负载水平L发生跌落的场景中的运行过程。
在t1时刻之前，负载12的负载水平为正常负载L 1。控制器114控制ACF变换电路111b运行于连续工作状态，并控制ACF变换电路111b的输出电压V 2的电压值为额定电压V 20。此时，辅助绕组电路112的输出电压V 4的电压值为V 40。电源电路113的输出电压V 5的电压值为V 50。半桥电路1111b中钳位电容C c的电容电压V Cc的电压值为V Cc1。
图25为本申请实施例提供的控制器的控制信号的示意图。如图25所示，控制器114发送的控制信号G 1、G 2、G 3…中的每一个包括向主功率管Q L发送的第一控制信号G L或 向辅助功率管Q H发送的第二控制信号G H。控制器114控制主功率管Q L和辅助功率管Q H周期性地交替导通和关断，半桥电路1110b可以在原边绕组1111b产生原边绕组电压V 11。原边绕组1111b上的原边绕组电压V 11经过耦合，可以在副边绕组1113b上产生副边绕组电压V 12，并可以在辅助绕组1121上产生辅助绕组电压V 3。相应地，整流电路1114b向负载12提供输出电压V 2，辅助绕组电路112向电源电路113提供输出电压V 4，电源电路113向控制器115的输出电压V 5为V 50。由于ACF变换电路111b向负载12的输出电压V 2的电压值稳定在额定电压V 20，半桥电路1110b中钳位电容C c的电压值V Cc稳定在V Cc1。
在t1时刻，负载12的负载水平从正常负载L 1跌落到轻负载L 2。在t1时刻之后，ACF变换电路111b的输出电压V 2的电压值提升至大于额定电压V 20。
在一种实施例中，控制器114根据ACF变换电路111b的输出电压V 2的电压值与额定电压V 20的比较结果，控制ACF变换电路111b运行于连续工作状态，控制器114控制ACF变换电路111b降低输出电压V 2的电压值。
具体地，控制器114的检测单元1141检测ACF变换电路111b的输出电压V 2并判断ACF变换电路111b的输出电压V 2大于额定电压V 20。相应地，控制器114控制ACF变换电路111b运行于连续工作状态，控制器114降低第一控制信号G L和第二控制信号G H的发送频率，或者降低第一控制信号G L和第二控制信号G H的占空比。如图24所示，在t 1时刻之后控制器114发送的控制信号G 4、G 5、G 6的频率小于t 1时刻之前周期性发送的控制信号G 1、G 2、G 3的频率。相应地，主功率管Q L和辅助功率管Q H导通和关断的频率减少，使得ACF变换电路111b的输出电压V 2的电压值下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。但是，上述方式可能无法使得ACF变换电路111b的输出电压V 2的电压值有效下降，ACF变换电路111b的输出电压V 2的电压值将继续提升。
在t 1时刻之后，ACF变换电路111b的输出电压V 2的电压值高于额定电压V 20。此时，原边绕组电压V 11给半桥电路1110b中钳位电容C c充电，半桥电路1110b中钳位电容C c的电容电压V Cc的电压值从V Cc1提升到V Cc2。
在t 1时刻之后的t 2时刻，ACF变换电路111b的输出电压V 2的电压值提升至大于或等于第一预设值V 21。控制器114根据ACF变换电路111b的输出电压V 2的电压值与第一预设值V 21的比较结果，控制器114控制ACF变换电路111b运行于暂停工作状态。具体地，控制器114的检测单元1141检测ACF变换电路111b的输出电压V 2的电压值，并判断ACF变换电路111b的输出电压V 2的电压值大于或等于第一预设值V 21。相应地，控制器114的驱动单元1142停止发送第一控制信号G L和第二控制信号G H，从而控制ACF变换电路111b运行于暂停工作状态。相应地，ACF变换电路111b不会对其接收到的输入电压V 1进行处理，ACF变换电路111b的输出电压V 2降低。
在t 2时刻之后，控制器114控制ACF变换电路111b运行于暂停工作状态。相应地，ACF变换电路111b中原边绕组1111b上的原边绕组电压V 11的电压值下降，从而导致副边绕组电压V 12下降，并导致辅助绕组电压V 3下降。相应地，ACF变换电路111b的输出电压V 2的电压值下降，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在t 2时刻后的t 3时刻，辅助绕组电路112的输出电压V 4的电压值下降至低于第二预 设值V 41、或电源电路113的输出电压V 5的电压值下降至低于第三预设值V 52。此时，控制器114控制半桥电路1110b中的钳位电容C c放电。
在一种实施例中，控制器114的检测单元1141检测辅助绕组电路112的输出电压V 4的电压值，并判断辅助绕组电路112的输出电压V 4的电压值小于或等于第二预设值V 41。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H导通。此时，半桥电路1110b的钳位电容C c、原边绕组1111b和半桥电路1110b的功率管Q H形成放电回路，半桥电路1110b的钳位电容C c开始放电。
在一种实施例中，控制器114的检测单元1141检测电源电路113的输出电压V 5的电压值并判断电源电路113的输出电压V 5的电压值小于或等于第三预设值V 52。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H导通。此时，半桥电路1110b的钳位电容C c、原边绕组1111b和半桥电路1110b的功率管Q H形成放电回路，半桥电路1110b的钳位电容C c开始放电。
在t 3时刻之后，半桥电路1110b中的钳位电容C c的电容电压V Cc的电压值下降。半桥电路1110b中的钳位电容C c放电，使得原边绕组1111b上的原边绕组电压V 11的电压值提升。相应地，辅助绕组电压V 3的电压值提升，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。因此，负载12的负载水平发生变化的场景中，电源电路113的输出电压V 5的电压值不会下降至低于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。
本申请实施例提供的控制器114通过控制ACF变换电路111b的半桥电路1110b中钳位电容C c放电，可以使得电源电路113的输出电压V 5的电压值高于控制器114的欠压保护电压V 51，从而避免了控制器114因低电压保护而重启。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
由于ACF变换电路111b的半桥电路1110b中钳位电容C c存储的能量有限，放电后在原边绕组1111b上产生的原边绕组电压V 11的电压值较小。此时原边绕组1111b上产生的原边绕组电压V 11小于副边绕组1113上的副边绕组电压V 12，不会导致ACF变换电路111b的输出电压V 2提升。因此，控制器114控制半桥电路1110b中钳位电容C c放电后，原边绕组1111b上产生的原边绕组电压V 11仅用于提升辅助绕组电路112的输出电压V 4和电源电路113的输出电压V 5。因此，本申请实施例提供的控制器114及其所在的电源模组111不仅可以避免控制器114因欠压保护而重启，还可以避免增大ACF变换电路111b的输出电压V 2的波纹，可以提高控制器114其所在的电源模组11及电子设备10的稳定性。
而且，本申请实施例提供的控制器114通过控制ACF变换电路111b的半桥电路1110b中钳位电容C c，不会引入来自输入电源13的噪声，可以避免影响ACF变换电路111b及其所在的电源模组11、电子设备10的电磁兼容性。因此，本申请实施例提供的控制器114可以提高其所在的电源模组11及电子设备10的稳定性。
在本申请一种实施例中，控制器114还可以控制ACF变换电路111b的半桥电路1110b中的钳位电容C c停止放电。
在第一种实施例中，在t 3时刻之后的t 4时刻，半桥电路1110b的钳位电容C c的电容电压V Cc下降至小于或等于预设电容电压值V Cc3。在一种实施例中，预设电容电压值V Cc3可以大于或等于ACF变换电路111b运行在连续运行状态时半桥电路1110b的钳位电容C c 的电容电压的电压值V Cc。控制器114根据半桥电路1110b的钳位电容C c的电容电压V Cc与预设电容电压值V Cc3的比较结果，控制器114控制半桥电路1110b的钳位电容C c停止放电。具体地，控制器114的检测单元1141检测半桥电路1110b的钳位电容C c的电容电压V Cc并判断半桥电路1110b的钳位电容C c的电容电压V Cc小于或等于预设电容电压值V Cc3。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H关断。此时，半桥电路1110b的钳位电容C c、原边绕组1111b和半桥电路1110b的功率管Q H形成的放电回路断开，半桥电路1110b的钳位电容C c停止放电。
因此，控制器114可以通过半桥电路1110b的钳位电容C c停止放电，可以避免钳位电容C c的电容电压V Cc过低而影响ACF变换电路111b恢复连续工作状态，进一步提高了电源模组11及其所在的电子设备10的稳定性。
在第二种实施例中，在t 3时刻之后的t 4时刻，辅助绕组电路112的输出电压V 4的电压值提升至大于或等于第四预设值V 42。控制器114根据辅助绕组电路112的输出电压V 4的电压值与第四预设值V 42的比较结果，控制器114控制半桥电路1110b的钳位电容C c停止放电。具体地，控制器114的检测单元1141检测辅助绕组电路112的输出电压V 4的电压值并判断辅助绕组电路112的输出电压V 4的电压值小于或等于预设电容电压值V Cc3。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H关断。此时，半桥电路1110b的钳位电容C c、原边绕组1111b和半桥电路1110b的功率管Q H形成的放电回路断开，半桥电路1110b的钳位电容C c停止放电。
因此，控制器114可以通过半桥电路1110b的钳位电容C c停止放电，可以避免辅助绕组电路112的输出电压V 4的电压过高而损坏电源电路113及控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在第三种实施例中，在t 3时刻之后的t 4时刻，电源电路113的输出电压V 5的电压值提升至大于或等于第五预设值V 53。控制器114根据电源电路113的输出电压V 5的电压值与第五预设值V 53的比较结果，控制器114控制半桥电路1110b的钳位电容C c停止放电。具体地，控制器114的检测单元1141检测电源电路113的输出电压V 5的电压值并判断电源电路113的输出电压V 5的电压值大于或等于第五预设值V 53。控制器114的驱动单元1142发送第一控制信号G L使得辅助功率管Q H关断。此时，半桥电路1110b的钳位电容C c、原边绕组1111b和半桥电路1110b的功率管Q H形成的放电回路断开，半桥电路1110b的钳位电容C c停止放电。因此，控制器114可以通过控制半桥电路1110b的钳位电容C c停止放电，避免电源电路113的输出电压V 4的电压过高而损坏控制器114，进一步提高了控制器114及其所在的电源模组11、电子设备10的稳定性。
在t 4时刻之后，半桥电路1110b的钳位电容C c停止放电后，钳位电容C c的电容电压V Cc的电压值停止下降。相应地，原边绕组电压V 11的电压值下降，导致辅助绕组电压V 3下降。相应地，辅助绕组电路112的输出电压V 4的电压值下降，电源电路113的输出电压V 5的电压值下降。
在本申请一种实施例中，在t 4时刻之后，当辅助绕组电路112的输出电压V 4的电压值下降至小于或等于第二预设值V 41、或电源电路113的输出电压V 5的电压值下降至小于或等于第三预设值V 52时，控制器114可以控制半桥电路1110b的钳位电容C c再次放电。具体过程如上述实施例中所述，不再重复说明。
在本申请一种实施例中，在半桥电路1110b的钳位电容C c开始放电后或停止放电后，控制器114还会根据ACF变换电路111b的输出电压V 2的电压值控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。在t 2时刻之后，控制器114控制ACF变换电路111b运行于暂停工作状态，相应地ACF变换电路111b的输出电压V 2的电压值下降。在一种实施例中，在半桥电路1110b的钳位电容C c开始放电后、停止放电前，ACF变换电路111b的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。在一种实施例中，在半桥电路1110b的钳位电容C c停止放电后，ACF变换电路111b的输出电压V 2的电压值下降至小于或等于额定电压V 20，控制器114控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。
在t 3时刻之后的t 5时刻，ACF变换电路111b的输出电压V 2的电压值下降至小于或等于额定输出电压V 20。控制器114根据ACF变换电路111b的输出电压V 2的电压值与额定输出电压V 20的比较结果，控制ACF变换电路111b的运行状态从暂停工作状态切换为连续工作状态。具体地，控制器114的检测单元1141检测ACF变换电路111b的输出电压V 2的电压值并判断ACF变换电路111b的输出电压V 2的电压值小于或等于额定输出电压V 20。控制器114的驱动单元1142周期性地发送第一控制信号G L和第二控制信号G H，控制主功率管Q L和辅助功率管Q H周期性导通和关断，使得ACF变换电路111b恢复连续工作状态。此时，控制器114发送的第一控制信号G L和第二控制信号G H，记为G 7、G 8、G 9…。每个控制信号G 7、G 8、G 9…的具体实现方式与图25中所示相同，不再赘述。又例如，控制信号G 7、G 8、G 9…的周期也可以与控制信号G 1、G 2、G 3……的周期相同、或者与G 4、G 5、G 6……的周期相同等。在t 5时刻之后，ACF变换电路111b的输出电压V 2的电压值恢复至额定输出电压V 20，辅助绕组电路112的输出电压V 4的电压值恢复至V 40，电源电路113的输出电压V 5的电压值恢复至V 50。
图26为本申请提供的控制器控制ACF变换电路的钳位电容放电的一种实施例的示意图。图26与图24的区别在于，控制器114控制ACF变换电路111b中原边绕组电路1111b的钳位电容C c周期性地放电。下文结合图22和图26，进行说明。
在t 3时刻，控制器114控制半桥电路1110b中辅助功率管Q H周期性地导通，使得半桥电路1110b中的钳位电容C c放电。具体地，控制器114不向主功率管Q L发送第一控制信号G L，使得主功率管Q L关断。并且，控制器114周期性地向辅助功率管Q H发送第二控制信号G H，使得辅助功率管Q H周期性地导通。半桥电路1110b的辅助功率管Q H导通时，原边绕组1111b及半桥电路1110b的钳位电容C c、半桥电路1110b的辅助功率管Q H可以形成放电回路。相应地，半桥电路1110b的辅助功率管Q H周期性地导通，可以使得半桥电路1110b中的钳位电容C c周期性地放电。
在本申请实施例中，控制器114控制辅助功率管Q H周期性地导通的周期T1，可以是预先配置的，也可以是控制器114根据当前钳位电容C c的电容电压V Cc或存储电能计算得到。在一种实施例中，钳位电容C c的电容电压V Cc的电压值较高或存储电能较多时，周期T1可以设置的更小。在一种实施例中，周期T1也可以与控制信号G 1、G 2、G 3……或者G 4、G 5、G 6……的周期相同。在本申请实施例中，每个周期中控制器114控制控制辅助 功率管Q H导通或关断的时长可以相同或不同。
图27为本申请提供的ACF变换电路的钳位电容的电容电压的变化示意图。如图27所示，钳位电容C c周期性地放电，钳位电容C c的电容电压V Cc从V Cc2阶梯式地下降。在t 3时刻到t 4时刻之间，钳位电容C c的电容电压V Cc随着辅助功率管Q H周期性导通呈现阶梯式的下降。相应地，辅助绕组电路112的输出电压V 4的电压值也呈现阶梯式的提升，电源电路113的输出电压V 5的电压值也呈现阶梯型的提升。
因此，控制器114控制ACF变换电路111b中钳位电容C c周期性地放电，可以使得钳位电容C c的电容电压V Cc阶梯式的下降，避免下降过快而影响ACF变换电路111b的运行，从而提高了电源模组11的稳定性。而且，控制器114控制ACF变换电路111b中钳位电容C c周期性地放电，可以使得辅助绕组电路112的输出电压V 4、电源电路113的输出电压V 5阶梯式地提升，避免电压提升过快而损坏电路器件，从而提高了电源模组11的稳定性。
图28为本申请提供的控制器控制ACF变换电路的钳位电容放电的另一种实施例的示意图。图28与图26的区别在于，控制器114控制ACF变换电路111b中原边绕组电路1111b中辅助功率管Q H和主功率管Q L周期性地交替导通，使得钳位电容C c周期性地放电。
在t 3时刻，控制器114周期性地控制主功率管Q L和辅助功率管Q H交替导通，且控制辅助功率管Q H和主功率管Q L不同时导通。具体地，控制器114周期性地依次向辅助功率管Q H发送第二控制信号G H、向主功率管Q L发送的第一控制信号G L，使得辅助功率管Q H和主功率管Q L依次导通，且辅助功率管Q H和主功率管Q L不同时导通。半桥电路1110b的辅助功率管Q H导通时，原边绕组1111b及半桥电路1110b的钳位电容C c、半桥电路1110b的辅助功率管Q H可以形成放电回路。钳位电容C c的电容电压V Cc的变化，可以参考图27所示。
在一种实施例中，每个周期中控制器114控制辅助功率管Q H先导通、主功率管Q L后导通。
首先，控制器114控制辅助功率管Q H导通、主功率管Q L截止。具体地，控制器114向辅助功率管Q H发送第二控制信号G H、且不向主功率管Q L发送第一控制信号G L。相应地，钳位电容C c、原边绕组a和辅助功率管Q H形成电流回路，钳位电容C c放电。相应地，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。
然后，控制器114控制辅助功率管Q H截止、主功率管Q L导通。具体地，控制器114不向辅助功率管Q H发送第二控制信号G H、且向主功率管Q L发送第一控制信号G L。此时，输入电压V 1、原边绕组a、和主功率管Q L形成回路。相应地，输入电压V 1在原边绕组a两侧产生原边绕组电压V 11。原边绕组电压V 11通过变压器1112b耦合，在辅助绕组c上产生辅助绕组电压V 3。相应地，辅助绕组电路112的输出电压V 4的电压值提升，电源电路113的输出电压V 5的电压值提升。
因此，控制器114控制ACF变换电路111b中原边绕组电路1111b的钳位电容C c周期性地放电，可以使得钳位电容C c的电容电压V Cc阶梯式的下降，避免下降过快而影响ACF变换电路111b的运行，从而提高了电源模组111的稳定性。而且，控制器114控制ACF变换电路111b中原边绕组电路1111b的钳位电容C c周期性地放电，可以使得辅助绕组电 路112的输出电压V 4、电源电路113的输出电压V 5阶梯式地提升，避免提升过快而损坏电路器件，从而提高了电源模组111的稳定性。
在一种实施例中，每个周期中控制器114可以控制主功率管Q L先导通、辅助功率管Q H后导通。在本申请实施例中，控制器114控制主功率管Q L和辅助功率管Q H周期性地交替导通的周期T2可以是预先配置的，也可以是控制器114根据当前钳位电容C c的电容电压V Cc或存储电能计算得到。在一种实施例中，钳位电容C c的电容电压V Cc的电压值较高或存储电能较多时，周期T2可以设置的更小。在一种实施例中，周期T2可以与控制信号G 1、G 2、G 3……的周期或者G 4、G 5、G 6……的周期相同。在本申请实施例中，每个周期中控制器114控制主功率管Q L导通的时长、控制辅助功率管Q H导通的时长可以相同或不同。在本申请实施例中，控制器114发送的第一控制信号G L和第二控制信号G H的占空比可以相同或者不同。
本申请实施例提供的控制器114在电源模组11的负载水平L发生跌落的场景中，仅需要控制ACF变换电路111b中的主功率管Q L和辅助功率管Q H的导通或者截止。因此，本申请实施例提供的控制器114不仅可以提高其所在的ACF变换电路111b、电源模组11、电子设备10的稳定性，而且控制器114的配置简单从而更适用于各类产品使用。
本申请还提供一种电子设备，包括如本申请任一实施例中提供的控制器114，或者包括如本申请任一实施例中提供的电源模组11。
在前述实施例中，对本申请实施例提供的控制器114所执行的方法进行了介绍，而为了实现上述本申请实施例提供的方法中的各功能，作为执行主体的控制器114可以包括硬件结构和/或软件模块，以硬件结构、软件模块、或硬件结构加软件模块的形式来实现上述各功能。上述各功能中的某个功能以硬件结构、软件模块、还是硬件结构加软件模块的方式来执行，取决于技术方案的特定应用和设计约束条件。需要说明的是，应理解以上装置的各个模块的划分仅仅是一种逻辑功能的划分，实际实现时可以全部或部分集成到一个物理实体上，也可以物理上分开。且这些模块可以全部以软件通过处理元件调用的形式实现；也可以全部以硬件的形式实现；还可以部分模块通过处理元件调用软件的形式实现，部分模块通过硬件的形式实现。可以为单独设立的处理元件，也可以集成在上述装置的某一个芯片中实现，此外，也可以以程序代码的形式存储于上述装置的存储器中，由上述装置的某一个处理元件调用并执行以上确定模块的功能。其它模块的实现与之类似。此外这些模块全部或部分可以集成在一起，也可以独立实现。这里所述的处理元件可以是一种集成电路，具有信号的处理能力。在实现过程中，上述方法的各步骤或以上各个模块可以通过处理器元件中的硬件的集成逻辑电路或者软件形式的指令完成。例如，以上这些模块可以是被配置成实施以上方法的一个或多个集成电路，例如：一个或多个特定集成电路(application specific integrated circuit，ASIC)，或，一个或多个微处理器(digital signal processor，DSP)，或，一个或者多个现场可编程门阵列(field programmable gate array，FPGA)等。再如，当以上某个模块通过处理元件调度程序代码的形式实现时，该处理元件可以是通用处理器，例如中央处理器(central processing unit，CPU)或其它可以调用程序代码的处理器。再如，这些模块可以集成在一起，以片上系统(system-on-a-chip，SOC)的形式实现。
在上述实施例中，控制器114所执行的步骤可以全部或部分地通过软件、硬件、固件或者其任意组合来实现。当使用软件实现时，可以全部或部分地以计算机程序产品的形式 实现。所述计算机程序产品包括一个或多个计算机指令。在计算机上加载和执行所述计算机程序指令时，全部或部分地产生按照本申请实施例所述的流程或功能。所述计算机可以是通用计算机、专用计算机、计算机网络、或者其他可编程装置。所述计算机指令可以存储在计算机可读存储介质中，或者从一个计算机可读存储介质向另一个计算机可读存储介质传输，例如，所述计算机指令可以从一个网站站点、计算机、服务器或数据中心通过有线(例如同轴电缆、光纤、数字用户线(DSL))或无线(例如红外、无线、微波等)方式向另一个网站站点、计算机、服务器或数据中心进行传输。所述计算机可读存储介质可以是计算机能够存取的任何可用介质或者是包含一个或多个可用介质集成的服务器、数据中心等数据存储设备。所述可用介质可以是磁性介质，(例如，软盘、硬盘、磁带)、光介质(例如，DVD)、或者半导体介质(例如固态硬盘solid state disk(SSD))等。
本申请还提供一种计算机可读存储介质，计算机可读存储介质存储有计算机指令，计算机指令被执行时可用于执行如本申请前述实施例中任一由控制器114执行的方法。
本申请实施例还提供一种运行指令的芯片，所述芯片用于执行如本申请前述任一由控制器114执行的方法。
本申请实施例还提供一种计算机程序产品，所述程序产品包括计算机程序，所述计算机程序存储在存储介质中，至少一个处理器可以从所述存储介质读取所述计算机程序，所述至少一个处理器执行所述计算机程序时可实现如本申请前述任一由控制器114执行的方法。
本领域普通技术人员可以理解：实现上述实施例的全部或部分步骤可以通过程序指令相关的硬件来完成。前述的程序可以存储于一计算机可读取存储介质中。该程序在执行时，执行包括上述各方法实施例的步骤；而前述的存储介质包括：ROM、RAM、磁碟或者光盘等各种可以存储程序代码的介质。
本领域普通技术人员可以理解：为便于说明本申请技术方案，本申请实施例中通过功能模块进行分别描述，各个模块中的电路器件可能存在部分或全部重叠，不作为对本申请保护范围的限定。
最后应说明的是：以上各实施例仅用以说明本申请的技术方案，而非对其限制；尽管参照前述各实施例对本申请进行了详细的说明，本领域的普通技术人员应当理解：其依然可以对前述各实施例所记载的技术方案进行修改，或者对其中部分或者全部技术特征进行等同替换；而这些修改或者替换，并不使相应技术方案的本质脱离本申请各实施例技术方案的范围。

Claims (13)

  1. 一种用于非对称半桥变换电路的控制器，所述非对称半桥变换电路包括半桥电路、变压器及整流电路，所述半桥电路包括主功率管、辅助功率管及谐振电容，所述变压器包括原边绕组、副边绕组及辅助绕组电路，所述辅助绕组电路为所述控制器的电源电路供电，其特征在于，所述控制器用于：
    控制所述非对称半桥变换电路运行于连续工作状态，使得所述非对称半桥变换电路的输出电压为额定输出电压；
    判断所述非对称半桥变换电路的输出电压高于第一预设值，则控制所述非对称半桥变换电路运行于暂停工作状态；所述第一预设值小于所述非对称半桥变换电路的过压保护电压、大于所述非对称半桥变换电路的额定输出电压；
    判断所述辅助绕组电路的输出电压小于或等于第二预设值，则控制所述半桥电路的谐振电容放电；所述第二预设值小于所述电源电路的额定输入电压、大于所述电源电路的欠压保护电压；或者，
    判断所述电源电路的输出电压小于或等于第三预设值，则控制所述半桥电路的谐振电容放电；所述第三预设值小于所述控制器的额定输入电压、大于所述控制器的欠压保护电压。
  2. 根据权利要求1所述的控制器，其特征在于，所述控制器用于：
    判断非对称半桥变换电路的输出电压小于或等于额定输出电压，则控制所述非对称半桥变换电路从暂停工作状态切换为连续工作状态。
  3. 根据权利要求1-2任一项所述的控制器，其特征在于，所述控制器控制所述非对称半桥变换电路运行于暂停工作状态，包括：
    所述控制器控制所述半桥电路的所述辅助功率管和所述主功率管都关断。
  4. 根据权利要求1-3任一项所述的控制器，其特征在于，所述控制器控制所述谐振电容放电，包括：
    所述控制器控制所述半桥电路的所述辅助功率管导通、所述主功率管关断；或者，
    所述控制器控制所述半桥电路的所述辅助功率管周期性导通、所述主功率管关断；或者，
    所述控制器控制所述半桥电路的所述辅助功率管和所述主功率管周期性地交替导通和关断。
  5. 根据权利要求1-4任一项所述的控制器，其特征在于，所述控制器用于：
    判断所述谐振电容的电容电压小于或等于预设电容电压值，则控制所述谐振电容停止放电；所述预设电容电压值为所述非对称半桥变换电路运行于连续工作状态时所述谐振电容的电容电压的电压值；或者，
    判断所述辅助绕组电路的输出电压大于或等于第四预设值，则控制所述谐振电容停止放电；所述第四预设值小于所述电源电路的过压保护电压、大于所述电源电路的额定输入电压；或者，
    判断所述电源电路的输出电压大于或等于第五预设值，则控制所述谐振电容停止放电；所述第五预设值大于所述控制器的额定输入电压、小于所述控制器的过压保护电压。
  6. 根据权利要求5所述的控制器，其特征在于，所述控制器控制所述谐振电容停止 放电，包括：
    所述控制器控制所述半桥电路的所述辅助功率管关断。
  7. 一种电源模组，包括非对称半桥变换电路、辅助绕组电路、电源电路及控制器，其特征在于，包括：
    所述非对称半桥变换电路，用于接收输入电压，并对输入电压进行电压变换处理后，向负载提供输出电压；所述非对称半桥变换电路包括：半桥电路、变压器及整流电路，所述半桥电路包括主功率管、辅助功率管及谐振电容；
    所述辅助绕组电路，用于为所述电源电路供电；
    所述电源电路，用于为所述控制器供电；
    所述控制器，用于：
    控制所述非对称半桥变换电路运行于连续工作状态，所述非对称半桥变换电路的输出电压为额定输出电压；
    判断所述非对称半桥变换电路的输出电压高于第一预设值，则控制所述非对称半桥变换电路运行于暂停工作状态；所述第一预设值小于所述非对称半桥变换电路的过压保护电压、大于所述非对称半桥变换电路的额定输出电压；
    判断所述辅助绕组电路的输出电压小于或等于第二预设值，则控制所述半桥电路的谐振电容放电；所述第二预设值小于所述电源电路的额定输入电压、大于所述电源电路的欠压保护电压；或者，
    判断所述电源电路的输出电压小于或等于第三预设值，则控制所述半桥电路的谐振电容放电；所述第三预设值小于所述控制器的额定输入电压、大于所述控制器的欠压保护电压。
  8. 根据权利要求7所述的电源模组，其特征在于，所述控制器用于，
    判断非对称半桥变换电路的输出电压小于或等于额定输出电压，则控制所述非对称半桥变换电路从暂停工作状态切换为连续工作状态。
  9. 根据权利要求7-8任一项所述的电源模组，其特征在于，所述控制器控制所述非对称半桥变换电路运行于暂停工作状态，包括：
    所述控制器控制所述半桥电路的所述辅助功率管和所述主功率管都关断。
  10. 根据权利要求7-9任一项所述的电源模组，其特征在于，所述控制器控制所述谐振电容放电，包括：
    所述控制器控制所述半桥电路的所述辅助功率管导通、所述主功率管关断；或者，
    所述控制器控制所述半桥电路的所述辅助功率管周期性导通、所述主功率管关断；或者，
    所述控制器控制所述半桥电路的所述辅助功率管和所述主功率管周期性地交替导通和关断。
  11. 根据权利要求7-10任一项所述的电源模组，其特征在于，所述控制器用于：
    判断所述谐振电容的电容电压小于或等于预设电容电压值，则控制所述谐振电容停止放电；所述预设电容电压值为所述非对称半桥变换电路运行于连续工作状态时所述谐振电容的电容电压的电压值；或者，
    判断所述辅助绕组电路的输出电压大于或等于第四预设值，则控制所述谐振电容停止 放电；所述第四预设值小于所述电源电路的过压保护电压、大于所述电源电路的额定输入电压；或者，
    判断所述电源电路的输出电压大于或等于第五预设值，则控制所述谐振电容停止放电；所述第五预设值大于所述控制器的额定输入电压、小于所述控制器的过压保护电压。
  12. 根据权利要求11所述的电源模组，其特征在于，所述控制器控制所述谐振电容停止放电，包括：
    所述控制器控制所述半桥电路的所述辅助功率管关断。
  13. 一种电子设备，包括如权利要求1-6任一项所述的非对称半桥变换电路的控制器，或者，包括如权利要求7-12任一项所述的电源模组。
PCT/CN2022/140118 2022-04-11 2022-12-19 非对称半桥变换电路的控制器、电源模组及电子设备 WO2023197661A1 (zh)

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CN114759796A (zh) * 2022-04-11 2022-07-15 上海华为数字能源技术有限公司 有源钳位反激变换电路的控制器、电源模组及电子设备
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