WO2022170738A1 - 交错式功率变换器和超大功率宽范围恒功率变换器 - Google Patents

交错式功率变换器和超大功率宽范围恒功率变换器 Download PDF

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Publication number
WO2022170738A1
WO2022170738A1 PCT/CN2021/107786 CN2021107786W WO2022170738A1 WO 2022170738 A1 WO2022170738 A1 WO 2022170738A1 CN 2021107786 W CN2021107786 W CN 2021107786W WO 2022170738 A1 WO2022170738 A1 WO 2022170738A1
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Prior art keywords
network
transformer
rectifier
resonant
switch
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PCT/CN2021/107786
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English (en)
French (fr)
Inventor
刘慧�
邓礼宽
田高阳
柏建国
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深圳市优优绿能电气有限公司
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Priority claimed from CN202110183947.0A external-priority patent/CN112953228A/zh
Priority claimed from CN202110799527.5A external-priority patent/CN113541493B/zh
Application filed by 深圳市优优绿能电气有限公司 filed Critical 深圳市优优绿能电气有限公司
Publication of WO2022170738A1 publication Critical patent/WO2022170738A1/zh

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

Definitions

  • the present invention relates to the field of power supplies, and more particularly, to an interleaved power converter and an ultra-high-power wide-range constant power converter.
  • the charging power module is the core component of the DC charging pile, which is crucial to promoting the development of new energy vehicles.
  • the demand for DC fast charging has gradually increased the power requirements of the charging power module, from 7.5KW to 15kW, 20KW, and now 30KW, 40KW.
  • power tubes are usually connected in parallel to improve the output power, and staggered parallel connections are used to reduce the output ripple.
  • the power tubes are directly connected in parallel, which will bring about the problem of uneven current and reduce the reliability of the device. Improper selection of staggered parallel connection will cause uneven current flow due to the deviation of parameters.
  • the technical problem to be solved by the present invention is to provide an interleaved power converter and an ultra-high power wide-range constant power converter capable of realizing high power output and current sharing between resonant networks, aiming at the above-mentioned defects of the prior art. .
  • an interleaved power converter comprising: a first switching network, a second switching network, a third switching network, a first resonant network, a second resonant network, a third Three resonance network, transformer module and rectifier module;
  • First input terminals of the first switch network, the second switch network and the third switch network are connected to each other and receive an input voltage, the first switch network, the second switch network and the third switch network
  • the second input terminals of the switch network are also connected to each other, the output terminal of the first switch network is connected via the first resonant network, the output terminal of the second switch network is connected via the second resonant network, the third switch network
  • the output ends of the network are respectively connected to the primary windings of the transformer module through the third resonance network; the first ends of the secondary windings of the transformer module are connected to each other, and the second end is connected to the rectifier module;
  • the first resonant network, the second resonant network and the third resonant network operate alternately, and the rectifier module outputs an output voltage.
  • the invention also relates to an ultra-high-power wide-range constant power converter, comprising: a first switching network, a second switching network, a third switching network, a fourth switching network, a fifth switching network, a sixth switching network, a first resonant network network, second resonant network, third resonant network, fourth resonant network, fifth resonant network, sixth resonant network, transformer module, rectifier module, switch module and high and low voltage control module;
  • First inputs of the first, second, and third switch networks are connected to each other and receive a first input voltage, the fourth, fifth, and sixth transformer networks
  • the first input terminals of the transformer network are connected in parallel with each other to receive the second input voltage
  • the second input terminal of the first switching network is connected in series with the second input terminal of the fourth switching network
  • the second input terminal of the second switching network is connected in series.
  • the second input end of the fifth switch network is connected in series with the second input end of the fifth switch network
  • the second input end of the third switch network is connected in series with the second input end of the sixth switch network;
  • the output end of the first switch network passes through the first resonant network, the output end of the second switch network passes through the second resonant network, and the output end of the third switch network passes through the third resonant network , the output end of the fourth switch network passes through the fourth resonant network, the output end of the fifth switch network passes through the fifth resonance network, and the output end of the sixth switch network passes through the sixth resonance network
  • the network is respectively connected to each primary winding of the transformer module; one end of each secondary winding of the transformer module is connected to each other, and the other end is connected to the rectifier module; the first resonance network, the second resonance network and the the third resonant network is interleaved, the fourth transformer network, the fifth transformer network and the sixth transformer network are interleaved;
  • the rectifier module outputs the first output voltage and the second output voltage to the switch module respectively, and the high and low voltage control module controls the switching of switching devices in the switch module to realize the ultra-high power wide-range constant power converter. Ultra-high power and ultra-wide range of constant power output.
  • the staggered power converter and the ultra-high-power wide-range constant power converter implemented in the present invention can realize current sharing and high-power output without primary side coupling of the transformer module through the interleaving of the resonant network, and the ripple current of the input and output can be realized. can be significantly reduced.
  • each primary winding of the transformer module is connected to the switching network through the resonant network, and the secondary winding forms a star connection and is rectified by the rectifier module to generate two output voltages,
  • the two output voltages can be connected in series, in parallel or individually, and ultra-wide range of constant power output can be achieved.
  • it can realize ultra-wide range constant power charging that can cover 1000V ⁇ 250V high and low voltage electric vehicles, and can fast charge vehicles of different voltage levels.
  • first switch network and the fourth switch network are connected in series with each other, the second switch network and the fifth switch network are connected in series with each other, and the third switch network and the sixth switch network are connected in series with each other, so Switching devices do not need to be connected in parallel to achieve high-power output, and there is no reliability problem caused by paralleling switching devices.
  • Fig. 1 is the principle block diagram of the first preferred embodiment of the interleaved power converter of the present invention
  • Figures 2a-2d show circuit diagrams of a switching network according to a preferred embodiment of the present invention
  • Figures 3a-3d show circuit diagrams of a resonant network according to a preferred embodiment of the present invention
  • FIGS. 4a-4e show circuit diagrams of LLC series resonant units according to preferred embodiments of the present invention
  • FIG. 5a-5b show circuit diagrams of a rectifier network, a rectifier unit or a rectifier module according to a preferred embodiment of the present invention
  • Figures 6a-6c show circuit diagrams of a transformer network according to a preferred embodiment of the present invention.
  • FIG. 7 is a schematic block diagram of a second preferred embodiment of the interleaved power converter of the present invention.
  • FIG. 8 shows simulation results of the rectified current and output capacitor current of the interleaved power converter shown in FIG. 7;
  • FIG. 9 is a schematic block diagram of a third preferred embodiment of the interleaved power converter of the present invention.
  • Fig. 10 is the principle block diagram of the first preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • Fig. 11 is the principle block diagram of the second preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • Fig. 12 is the principle block diagram of the third preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • Fig. 13 is the principle block diagram of the fourth preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • Fig. 14 is the circuit diagram of the fifth preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • 15 is a circuit diagram of the sixth preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • Fig. 16 is the circuit diagram of the seventh preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • 17 is a circuit diagram of a seventh preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • One aspect of the present invention relates to an interleaved power converter comprising: a first switching network, a second switching network, a third switching network, a first resonant network, a second resonant network, a third resonant network, a transformer module, and a rectifier module; first input terminals of the first switch network, the second switch network and the third switch network are connected to each other and receive an input voltage, the first switch network, the second switch network and the The second input terminals of the third switching network are also connected to each other, the output terminal of the first switching network via the first resonant network, the output terminal of the second switching network via the second resonant network, the first resonant network
  • the output ends of the three-switch network are respectively connected to the primary windings of the transformer module through the third resonance network; the first ends of the secondary windings of the transformer module are connected to each other, and the second end is connected to the rectifier module;
  • Another aspect of the present invention relates to an ultra-high power wide-range constant power converter, comprising: a first switch network, a second switch network, a third switch network, a fourth switch network, a fifth switch network, a sixth switch network, a first resonant network, a second resonant network, a third resonant network, a fourth resonant network, a fifth resonant network, a sixth resonant network, a transformer module, a rectifier module, a switch module and a high and low voltage control module; the first switch network , the first input terminals of the second switch network and the third switch network are connected to each other and receive a first input voltage, the first input of the fourth transformer network, the fifth transformer network and the sixth transformer network The terminals are connected in parallel with each other to receive the second input voltage, the second input terminal of the first switch network is connected in series with the second input terminal of the fourth switch network, and the second input terminal of the second switch network is connected in series with the fifth input terminal.
  • the second input terminal of the switch network, the second input terminal of the third switch network is connected in series with the second input terminal of the sixth switch network;
  • the output terminal of the first switch network is connected through the first resonant network, the The output end of the second switch network passes through the second resonance network, the output end of the third switch network passes through the third resonance network, the output end of the fourth switch network passes through the fourth resonance network,
  • the output end of the fifth switch network is respectively connected to each primary winding of the transformer module via the fifth resonant network and the output end of the sixth switch network via the sixth resonant network;
  • One end of each secondary winding is connected to each other, and the other end is connected to the rectifier module;
  • the first resonant network, the second resonant network and the third resonant network operate alternately, the fourth transformer network, the third The five transformer network and the sixth transformer network operate alternately;
  • the rectifier module respectively outputs the first output voltage and the second output voltage to the switch module, and the high and low voltage control
  • the invention can realize current sharing and high power output without primary side coupling of the transformer module, and the input and output ripple currents can be greatly reduced.
  • each primary winding of the transformer module is connected to the switching network through the resonant network, and the secondary winding forms a star connection and is rectified by the rectifier module to generate two output voltages.
  • ultra-high power output can be achieved.
  • the two output voltages can be connected in series, in parallel or independently, which can achieve an ultra-wide range of constant power output, and can achieve an ultra-wide range that can cover 1000V ⁇ 250V high and low voltage electric vehicles.
  • Range constant power charging which can fast charge vehicles of different voltage levels.
  • the first switch network and the fourth switch network are connected in series with each other, the second switch network and the fifth switch network are connected in series with each other, and the third switch network and the sixth switch network are connected in series with each other, so Switching devices do not need to be connected in parallel to achieve high-power output, and there is no reliability problem caused by paralleling switching devices.
  • FIG. 1 is a functional block diagram of a first preferred embodiment of the interleaved power converter of the present invention.
  • the interleaved power converter of the present invention includes: a first switch network 110, a second switch network 120, a third switch network 130, a first resonant network 210, a second resonant network 220, a third resonant network Network 230 , transformer module 300 and rectifier module 400 .
  • the first input terminals of the first switch network 110, the second switch network 120 and the third switch network 130 are connected to each other and receive the input voltage Vin, the first switch network 110, the second switch network 130 120 and the second input of the third switching network 130 are likewise connected to each other.
  • the output end of the first switch network 110 passes through the first resonant network 210 and the output end of the second switch network 120 passes through the second resonant network 220 and the output end of the third switch network 130.
  • the third resonant network 230 is respectively connected to each primary winding of the transformer module 300 .
  • the first ends of the secondary windings of the transformer module 300 are connected to each other, and the second ends are connected to the rectifier module 400 .
  • the first resonant network 210 , the second resonant network 220 and the third resonant network 230 operate alternately, and the rectifier module 400 outputs an output voltage Vo.
  • the first switching network 110 , the second switching network 120 , and the third switching network 130 have the same structure, which may include a switching device full-bridge topology circuit, a switching device Symmetrical half-bridge topology circuit or switching device asymmetrical half-bridge topology circuit.
  • These switching device full-bridge topology circuits, switching device symmetrical half-bridge topology circuits or switching device asymmetric half-bridge topology circuits can be two-phase, as shown in Figures 2a-2c, or three-phase, as shown in Figure 2d .
  • the first resonant network 210, the second resonant network 220, and the third resonant network 230 respectively include an LC resonant unit, an LLC series resonant unit, an SRC series resonant unit, a PRC Parallel resonance unit and LCC series-parallel resonance unit.
  • the inductance Lr can be an LLC series resonance unit composed of an inductance Lr, an inductance Lm (equivalent inductance of the transformer module) and a capacitor Cr, or an SRC series resonance unit composed of an inductance Lr and a capacitor Cr; the inductance Lr and the capacitor Cr are composed
  • the PRC parallel resonant converter (the capacitor and the transformer are connected in parallel); the LCC series-parallel resonant converter composed of the inductor Lr, the capacitor Cr, and the capacitor Cpr are shown in Figures 3a-3d respectively.
  • the first resonant network 210 , the second resonant network 220 and the third resonant network 230 operate staggered with each other by 120 degrees. Of course, in other preferred embodiments of the present invention, other suitable staggered angles can also be selected.
  • the first resonant network 210, the second resonant network 220, and the third resonant network 230 may respectively adopt LLC series resonant units, which include series-connected inductors Lr, inductors
  • Lr series-connected inductors
  • the positions of Lm and capacitor Cr in series can be changed arbitrarily.
  • the capacitor Cr can be placed before the inductor Lr, or can be placed between the inductor Lr and the inductor Lm.
  • the inductance Lm can be the inductive inductance of the transformer module, or a separate inductance can be used.
  • the three elements of the inductor Lr, the inductor Lm and the capacitor Cr can also be split into multiple inductors or capacitors in series and parallel, and the series can be placed arbitrarily.
  • the inductance Lr When the inductance Lr is split into multiple inductances, it may be a single inductance or a mutual coupled inductance, as shown in Figures 4a-4e.
  • the rectifier module 400 includes at least one switching device rectifier bridge, such as a diode rectifier unit, a switch tube synchronous rectifier unit, etc., as shown in FIGS. 5a-5b.
  • switching device rectifier bridge such as a diode rectifier unit, a switch tube synchronous rectifier unit, etc.
  • the transformer module 300 includes a first transformer network, a second transformer network and a third transformer network.
  • Each transformer network may include one transformer or two transformers in series, such as shown in Figures 6a-6b.
  • the inductors Lma1 and Lma2 are connected in parallel with the primary windings of the transformers Ta1 and Ta2 respectively.
  • the inductors Lma1/Lma2 can be individually designed inductors or can be integrated in the transformer.
  • the inductors Lma1 and Lma2 are connected in series, and finally equivalent to the inductor Lm, as shown in Figure 6a-6b.
  • the inductor Lm can be integrated or the equivalent of the separately designed inductors Lma1 and Lma2, or can be the separately designed inductor Lm.
  • the connection manners of the transformers and the equivalent inductance Lm in the second transformer network and the third transformer network are similar.
  • each transformer network may also include multiple series-connected transformers, for example, four series-connected transformers, whose secondary sides are connected to form a star connection, as shown in FIG. 6c .
  • any suitable switch network, resonant network, transformer module, and rectifier module described anywhere in this application can be used for combination, so as to construct the ultra-high power wide-range constant power conversion of the present invention device.
  • the staggered power converter and the ultra-high-power wide-range constant power converter implemented in the present invention can realize current sharing and high-power output without primary side coupling of the transformer module through the interleaving of the resonant network, and the ripple current of the input and output can be realized. can be significantly reduced.
  • FIG. 7 is a functional block diagram of a second preferred embodiment of the interleaved power converter of the present invention.
  • the interleaved power converter of the present invention includes: a first switch network 110 , a second switch network 120 , a third switch network 130 , a first resonant network 210 , a second resonant network 220 , a third resonant network 230 , and a transformer module 300 and rectifier module 400.
  • the transformer module 300 includes the first transformer network, the second transformer network, and the third transformer network, and each transformer network includes a first transformer, namely, transformers T1-T3.
  • the rectifier module 400 includes a diode rectifier bridge composed of diodes D11-D16.
  • the first input terminals of the first switch network 110, the second switch network 120 and the third switch network 130 are connected to each other and receive the input voltage Vin, the first switch network 110, the second switch network 130 120 and the second input of the third switching network 130 are likewise connected to each other.
  • the output terminal of the first switching network 110 is connected to the primary winding of the transformer T1 via the first resonant network 210
  • the output terminal of the second switching network 120 is connected to the primary winding of the transformer T2 via the second resonant network 220 .
  • winding, the output end of the third switching network 130 is connected to the primary winding of the transformer T3 via the third resonant network 230 .
  • the first ends of the secondary windings of the transformer T1, the transformer T2 and the transformer T3 are respectively connected to the first input end, the second input end and the third input end of the diode rectifier bridge formed by the diodes D11-D16, so The second ends of the secondary windings of the transformer T1 , the transformer T2 and the transformer T3 are respectively connected to each other, that is, a Y-shaped connection is formed as shown in FIG. 7 .
  • the output end of the diode rectifier bridge formed by the diodes D11-D16 is connected to the output capacitor C to output the output voltage Vo.
  • the first resonant network 210, the second resonant network 220 and the third resonant network 230 operate 120 degrees staggered from each other, so the transformer T1, the transformer T2 and
  • the simulation results of the secondary rectified current of the transformer T3 and the ripple current of the output capacitor current are shown in Figure 8, where the upper part is the transformer T1, the transformer T2 and the transformer T3 (that is, three transformers). network), the three curves 4-1, 4-2, and 4-3 represent the secondary currents of the transformer T1, the transformer T2 and the transformer T3 respectively. It can be seen that the currents of the three-way transformers are staggered. 120 degrees.
  • the lower part of Figure 8 is the output current after rectification by the rectifier module, in which curve 4-4 represents the ripple current on the filter capacitor C, curve 4-6 represents the current flowing to the final sub-load, and curve 4-5 is the The sum of the transformer output current is also the sum of the load current and the capacitor ripple current.
  • the ratio of the ripple current in the output current is very small.
  • the ripple current is only 1.24A, accounting for about 8.2% of the total output current; the ripple current without interleaving operation accounts for about 48%; 1/6 of the staggered scheme. Therefore, by implementing the interleaved power converter of the present invention, through the interleaving of the resonant network, current sharing and high power output can be realized without the primary side coupling of the transformer module, and the input and output ripple currents can be greatly reduced, which is beneficial to Reduce the size and cost of the filter.
  • any suitable switch network, resonant network, transformer module, and rectifier module described anywhere in this application can be used in combination to construct the interleaved power converter of the present invention.
  • FIG. 9 is a functional block diagram of a third preferred embodiment of the interleaved power converter of the present invention.
  • the interleaved power converter of the present invention includes: a first switching network 110, a second switching network 120, a third switching network 130, a first resonant network 210, a second resonant network 220, a third resonant network Network 230 , transformer module 300 and rectifier module 400 .
  • the transformer module 300 includes the first transformer network, the second transformer network and the third transformer network.
  • the first transformer network, the second transformer network, and the third transformer network respectively include first transformers Ta1-Tc1 and second transformers Ta2-Tc2 connected in series with primary windings.
  • the rectifier module 400 includes a first rectifier network and a second rectifier network.
  • the first rectifier network and the second rectifier network respectively include diode rectifier bridges composed of diodes D11-D16.
  • FIG. 9 The structure and principle of the embodiment shown in FIG. 9 are similar to those of FIG. 8 , and the difference mainly lies in the design of the transformer module 300 and the rectifier module 400 , which are only further described as follows.
  • the first end of the primary winding of the first transformer Ta1 is connected to the first end of the first resonant network 210
  • the second end of the primary winding is connected to the primary side of the second transformer Ta2
  • the first end of the winding and the second end of the primary winding of the second transformer Ta2 are connected to the second end of the first resonant network 210 .
  • the first end of the secondary winding of the first transformer Ta1 is connected to the first input end of the first diode rectifier bridge formed by diodes D11-D16, and the second end of the secondary winding is connected to the secondary side of the first transformer Tb1.
  • the first end of the secondary winding of the second transformer Ta2 is connected to the first input end of the second diode rectifier bridge formed by diodes D11-D16, and the second end of the secondary winding is connected to the secondary side of the second transformer Tb2.
  • the first end of the primary winding of the first transformer Tb1 is connected to the first end of the second resonant network 220, and the second end of the primary winding is connected to the second end of the primary winding of the second transformer Tb2.
  • One end, the second end of the primary winding of the second transformer Tb2 is connected to the second end of the second resonant network 220 .
  • the first end of the secondary winding of the first transformer Tb1 is connected to the second input end of the first diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the second transformer Tb2 is connected to the second input end of the second diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the primary winding of the first transformer Tb1 is connected to the first end of the third resonant network 230
  • the second end of the primary winding is connected to the first end of the primary winding of the second transformer Tb2
  • the second end of the primary winding of the second transformer Tb2 is connected to the second end of the third resonant network 230 .
  • the first end of the secondary winding of the first transformer Tb1 is connected to the second input end of the first diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the second transformer Tb2 is connected to the second input end of the second diode rectifier bridge formed by the diodes D11-D16.
  • the output ends of the first diode rectifier bridge formed by diodes D11-D16 and the second diode rectifier bridge formed by diodes D11-D16 are connected to both ends of the output capacitors C11 and C12 in parallel to output the output voltage Vo.
  • the first switching network 110 , the second switching network 120 , the third switching network 130 , the first resonant network 210 , and the second resonant network 220 can be constructed using any of the aforementioned switching networks and resonant networks. , the third resonant network 230 .
  • the invention can realize current sharing and high power output without primary side coupling of the transformer module, and the input and output ripple currents can be greatly reduced. Further, the use of multiple transformer secondary side coupling can achieve the purpose of high power output.
  • the power of the charging power module has gradually increased, from 7.5KW, to 15kW, 20KW, and now 30KW, 40KW.
  • the constant power range of the charging power module has gradually expanded, from 600V ⁇ 750V, 375V ⁇ 500V constant power range, to 500V ⁇ 1000V, 300V ⁇ 500V constant power, and 300V ⁇ 1000V constant power .
  • FIG. 10 is a schematic block diagram of the first preferred embodiment of the ultra-high-power wide-range constant power converter of the present invention.
  • the ultra-high power wide-range constant power converter includes: a first switch network 110 , a second switch network 120 , a third switch network 130 , a fourth switch network 140 , a fifth switch network 150 , a sixth switch network 150 , and a sixth switch network Switching network 160, first resonant network 210, second resonant network 220, third resonant network 230, fourth resonant network 240, fifth resonant network 250, sixth resonant network 260, transformer module 300, rectifier module 400, switch module 500 and the high and low voltage control module 600.
  • the input capacitors C1 and C2 are connected in series, and the voltages at both ends are Uin respectively.
  • the anode of the input capacitor C1 is connected to the first input terminals of the first switch network 110 , the second switch network 120 and the third switch network 130 respectively to receive the first input voltage Uin, and the cathode is connected to the anode of the input capacitor C2 .
  • the second input terminal of the first switch network 110 is connected in series with the first input terminal of the fourth switch network 140
  • the second input terminal of the second switch network 120 is connected in series with the first input terminal of the fifth switch network 150
  • the third switch network 130 The second input terminal is connected in series with the first input terminal of the sixth switch network 160 .
  • the cathodes of the input capacitor C2 are respectively connected to the second input terminals of the fourth switch network 140 , the fifth switch network 150 and the sixth switch network 160 to receive the second input voltage Uin.
  • the first switch network 110 and the fourth switch network 140 are connected in series with each other
  • the second switch network 120 and the fifth switch network 150 are connected in series with each other
  • the third switch network 130 and the sixth switch network are connected in series with each other.
  • the switch networks 160 are connected in series with each other.
  • the output terminal of the first switching network 110 passes through the first resonant network 210
  • the output terminal of the second switching network 120 passes through the second resonant network and the third switching network 130
  • the output end of the third resonant network 230 passes through the third resonant network 230
  • the output end of the fourth switch network 140 passes through the fourth resonant network 240
  • the output end of the fifth switch network 150 passes through the fifth resonant network 250
  • the output ends of the sixth switching network 160 are respectively connected to the primary windings of the transformer module 300 via the sixth resonant network 260 .
  • each secondary winding of the transformer module 300 is connected to each other to form a star connection, and the other end is connected to the rectifier module 400 .
  • the first output terminal of the rectifier module 400 is connected to the anode of the output capacitor C3 and the first terminal of the switch module 500, and the second output terminal is connected to the cathode of the output capacitor C3 and the second terminal of the switch module 500 to output the first output voltage to Switch module 500 .
  • the third output terminal of the rectifier module 400 is connected to the anode of the output capacitor C4 and the third terminal of the switch module 500, and the second output terminal is connected to the cathode of the output capacitor C4 and the fourth terminal of the switch module 500 to output the second output voltage to Switch module 500 .
  • the switch module 500 includes a first switch device K1, a second switch device K2 and a third switch device K3.
  • the first switch device K1 is connected between the second end and the fourth end of the switch module 500
  • the third switch device K3 is connected between the third end and the first end of the switch module 500
  • the second switching device K2 is connected between the second terminal and the third terminal of the switching module 500 .
  • the high and low voltage control module 600 controls the switching devices in the switch module 500 to switch, and then outputs the first output voltage and the second output voltage output by the rectifier module 400 in parallel, in series or separately to achieve the ultra-high power and wide range
  • the super power and super wide range of constant power of the constant power converter are output to the load R0.
  • the first switching device K1 , the second switching device K2 and the third switching device K3 may be switches, relays, contactors and other devices that can be turned on and off.
  • the output capacitors C3 and C4 constitute the output filter circuit of the ultra-high power wide-range constant power converter.
  • filter modules can also be used, such as an inductor-capacitor filter module and the like.
  • any suitable switch network, resonant network, transformer module, and rectifier module described anywhere in this application can be used for combination, so as to construct the ultra-high power wide-range constant power conversion of the present invention device.
  • any known control methods and steps can be used to control the switch module 500 through the high and low voltage control module 600, or any known control method can be used to control the first-sixth switch network, the first - The sixth resonance network, the transformer module, and the rectifier module are modulated.
  • the first switch network 110 , the second switch network 120 , and the third switch network 130 operate interleaved
  • the fourth switch network 140 , the fifth switch network 150 , and the sixth switch network 160 Staggered operation the staggered angle can be selected as 120 degrees, which can further greatly reduce the input and output ripple current, thereby reducing the size and cost of the filter.
  • the staggered power converter shown in Figure 1-9 please refer to the staggered power converter shown in Figure 1-9. The description will not be repeated here.
  • the switching network is connected through the resonant network, the secondary winding forms a star connection and is rectified by the rectifier module to generate two output voltages.
  • the switching device switching of the two output voltages can connect two output voltages in series, in parallel or independently, which can achieve a wide range of constant power output, and can achieve a wide range of constant power charging that can cover 1000V ⁇ 250V high and low voltage electric vehicles, and can charge different voltages. Cars of the same level are fast charged. And the first switch network and the fourth switch network are connected in series with each other, the second switch network and the fifth switch network are connected in series with each other, and the third switch network and the sixth switch network are connected in series with each other, so Switching devices do not need to be connected in parallel to achieve high-power output, and there is no reliability problem caused by paralleling switching devices. Therefore, various types of switching devices can be used, especially low-cost silicon switching devices can be used.
  • FIG. 11 is a schematic block diagram of the second preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • the ultra-high power wide-range constant power converter includes: a first switch network 110 , a second switch network 120 , a third switch network 130 , a fourth switch network 140 , and a fifth switch network 150, sixth switching network 160, first resonant network 210, second resonant network 220, third resonant network 230, fourth resonant network 240, fifth resonant network 250, sixth resonant network 260, transformer module 300, rectifier Module 400 , switch module 500 and high and low voltage control module 600 .
  • the transformer module 300 includes a first transformer network 310 , a second transformer network 320 , a third transformer network 330 , a fourth transformer network 340 , a fifth transformer network 350 , and a sixth transformer network 360 .
  • the rectifier module 400 includes a first rectifier network 410 and a second rectifier network 420 .
  • the input capacitors C1 and C2 are connected in series, and the voltages at both ends are Uin respectively.
  • the anode of the input capacitor C1 is connected to the first input terminals of the first switch network 110 , the second switch network 120 and the third switch network 130 respectively, and the cathode is connected to the anode of the input capacitor C2 .
  • the cathodes of the input capacitor C2 are respectively connected to the second input terminals of the fourth switch network 140 , the fifth switch network 150 and the sixth switch network 160 .
  • the first input terminal of 150 and the first input terminal of the sixth switch network 160 are connected to each other.
  • the first switch network 110 and the fourth switch network 140 are connected in series with each other
  • the second switch network 120 and the fifth switch network 150 are connected in series with each other
  • the third switch network 130 and the sixth switch network are connected in series with each other.
  • the switch networks 160 are connected in series with each other.
  • the first switch network 110 is connected to the first transformer network 310 via the first resonant network 210
  • the second switch network 120 is connected to the first transformer network 310 via the second resonant network 220
  • Two transformer networks 320 the third switch network 130 is connected to the third transformer network 330 via the third resonant network 230
  • the fourth switch network 140 is connected to the fourth transformer via the fourth resonant network 240 network 340
  • the fifth switch network 150 is connected to the fifth transformer network 350 via the fifth resonant network 250
  • the sixth switch network 160 is connected to the sixth transformer network 360 via the sixth resonant network 260 .
  • the primary winding of the first transformer network 310 is connected to the first resonant network 210, the first end of the secondary winding is connected to the first rectifier network 410, and the primary winding of the second transformer network 320 is connected to the The second resonant network 220 and the first end of the secondary winding are connected to the first rectifier network 410 , the primary winding of the third transformer network 330 is connected to the third resonant network 230 and the first end of the secondary winding is connected The first rectifier network 410, the primary winding of the fourth transformer network 340 is connected to the fourth resonant network 240, the first end of the secondary winding is connected to the second rectifier network 420, and the fifth transformer network
  • the primary winding of 350 is connected to the second resonant network 220, the first end of the secondary winding is connected to the second rectifier network 420, and the primary winding of the sixth transformer network 360 is connected to the sixth resonant network 260, The first end of the secondary winding is connected to
  • the second ends of the secondary windings of the first transformer network 310, the second transformer network 320, and the third transformer network 330 are connected to each other; the fourth transformer network 340, the fifth transformer network 350, The second ends of the secondary windings of the sixth transformer network 360 are connected to each other.
  • the first transformer network 310, the second transformer network 320, and the third transformer network 330 may respectively include a first transformer, and the primary windings of the first transformers are respectively The first resonant network 210 , the second resonant network 220 or the third resonant network 230 , and the first ends of the secondary windings are connected to the first rectifier network 410 and the second ends of the secondary windings are connected to each other. connect.
  • the fourth transformer network 340, the fifth transformer network 350, and the sixth transformer network 360 respectively include second transformers, and the primary windings of the second transformers are connected to the fourth resonant network 240, the The fifth resonant network 250 or the sixth resonant network 260 and the first ends of the secondary windings are all connected to the second rectifier network 420, and the second ends of the secondary windings are connected to each other.
  • the high and low voltage control module 600 controls the switching of the switching devices in the switching module 500 to enable the first rectifier network 410 and the second rectifier network 420 to perform voltage output in parallel, in series or independently.
  • any suitable switching network, resonant network, transformer network, and rectifier network described anywhere in this application can be used for combination, so as to construct the ultra-high power wide-range constant power conversion of the present invention device.
  • the primary windings of the transformer module are respectively connected to the switching network through the resonant network, the secondary windings form a star connection, and are rectified by the rectifier module to generate two output voltages.
  • the two output voltages can be connected in series, in parallel or independently, which can achieve an ultra-wide range of constant power output, which can cover 1000V ⁇ 250V high and low voltage electric power.
  • the ultra-wide range constant power charging of the car can fast charge the car of different voltage levels.
  • first switch network and the fourth switch network are connected in series with each other, the second switch network and the fifth switch network are connected in series with each other, and the third switch network and the sixth switch network are connected in series with each other, so Switching devices do not need to be connected in parallel to achieve high-power output, and there is no reliability problem caused by paralleling switching devices. Therefore, various types of switching devices can be used, especially low-cost silicon switching devices can be used.
  • the ultra-high power wide-range constant power converter includes: a first switching network 110 , a second switching network 120 , a third switching network 130 , a fourth switching network 140 , a fifth switching network 150 , a sixth switching network 150 , and a sixth switching network 130 .
  • Switching network 160 first resonant network 210, second resonant network 220, third resonant network 230, fourth resonant network 240, fifth resonant network 250, sixth resonant network 260, first transformer network 310, second transformer network 320 , the third transformer network 330 , the fourth transformer network 340 , the fifth transformer network 350 , the sixth transformer network 360 , the first rectifier network 410 , the second rectifier network 420 , the switch module 500 and the high and low voltage control module 600 .
  • the first switching network 110 and the fourth switching network 140 respectively include a switching device full-bridge topology composed of switching devices S1-S4.
  • the second switching network 120 and the fourth switching network The five switch networks 150 respectively include a full-bridge topology of switching devices composed of switching devices S5-S8, and the third switching network 130 and the sixth switching network 160 include a full-bridge topology of switching devices composed of switching devices S9-S12.
  • the first resonant network 210 , the second resonant network 220 , the third resonant network 230 , the fourth resonant network 240 , the fifth resonant network 250 , and the sixth resonant network 260 respectively include an LC series resonance formed by a capacitor Cm and an inductor Lr in series. unit.
  • the first transformer network 310 , the second transformer network 320 , the third transformer network 330 , the fourth transformer network 340 , the fifth transformer network 350 , and the sixth transformer network 360 each include one transformer, and only transformers Ta1-Tc1 are marked for simplicity.
  • the first rectifier network 410 includes a diode rectifier bridge composed of diodes D11-D16.
  • the second rectifier network 420 includes a diode rectifier bridge formed by diodes D21-D26.
  • the ultra-high-power wide-range constant power converter of the present invention has an upper and lower combined structure. Therefore, only its upper circuit is further explained as follows.
  • the first end of the primary winding of the transformer Ta1 is connected to the first output end of the switching device full-bridge topology formed by the switching devices S1-S4 through the capacitor Cm and the inductance Lr connected in series, and the second end of the primary winding
  • the second output end of the switching device full-bridge topology formed by the switching devices S1-S4 is connected, and the first end of the secondary winding is connected to the first input end of the diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the primary winding of the transformer Tb1 is connected to the first output end of the switching device full-bridge topology formed by the switching devices S5-S8 through the capacitor Cm and the inductance Lr connected in series, and the second end of the primary winding is connected to the switching device.
  • the second output end of the switching device full-bridge topology composed of S5-S8 and the first end of the secondary winding are connected to the second input end of the diode rectifier bridge composed of diodes D11-D16, and the first end of the primary winding of the transformer Tc1 is
  • the capacitor Cm and the inductance Lr connected in series are connected to the first output end of the full bridge topology of the switching device formed by the switching devices S9-S12, and the second end of the primary winding is connected to the second output of the full bridge topology of the switching device formed by the switching devices S9-S12
  • the first end of the end and the secondary winding is connected to the third input end of the diode rectifier bridge formed by the diodes D11-D16.
  • the diodes D11-D16, the switching devices S1-S12, and K1-K3 can be silicon switching devices or silicon carbide switching devices. For cost savings, silicon switching devices are preferably used.
  • the primary windings of the transformer are independently connected to the bridge switch network of each phase, and the secondary windings are connected to each other, and are then connected in parallel through full-bridge rectification to achieve high-power output.
  • the ultra-wide range constant power output can be realized, which can realize the ultra-wide range constant power charging that can cover 1000V ⁇ 250V high and low voltage electric vehicles, and can be used for different voltage levels. Fast charge the car.
  • the switching devices of the primary winding and the secondary winding of the transformer (such as switching devices S1-S12, D1-D16 and K1-K3).
  • High-power output can be achieved without parallel connection, and there is no reliability problem of parallel connection of switching devices.
  • the three-phase interleaved operation is realized, so that the current ripple of the primary side and the secondary side busbar is greatly reduced, thereby reducing the volume of the primary side and the secondary side filter.
  • especially low-cost silicon switching devices can be used, and an ultra-wide range of constant power output can be achieved.
  • the rectifier network of the preferred embodiment shown in FIG. 14 includes a small number of rectifier bridges, which is especially suitable for the case of ultra-wide output, but the output power is not required to be so large. Of course, when the output power requirements are higher, the number of rectifier bridges and transformers can be appropriate.
  • FIG. 12 is a schematic block diagram of the third preferred embodiment of the ultra-high-power wide-range constant power converter of the present invention.
  • the embodiment shown in FIG. 12 is similar to the embodiment shown in FIG. 11 , the difference is that the first transformer network 310 , the second transformer network 320 , the third transformer network 330 , the fourth transformer network 340 , and the fifth transformer network 350 , the configuration of the sixth transformer network 360 , the first rectifier network 410 , and the second rectifier network 420 .
  • the first transformer network 310 , the second transformer network 320 and the third transformer network 330 respectively comprise first transformers Ta1 , Tb1 , Tc1 and The second transformers Ta2, Tb2, Tc2.
  • the fourth transformer network 340, the fifth transformer network 350, and the sixth transformer network 360 respectively comprise third transformers Ta3, Tb3, Tc3 and fourth transformers Ta4, Tb4, Tc4 connected in series with primary windings .
  • the first rectification network 410 includes a first rectification unit 411 and a second rectification unit 412
  • the second rectification network 420 includes a third rectification unit 413 and a fourth rectification unit 414 .
  • the first rectification unit 411, the second rectification unit 412, the third rectification unit 413 and the fourth rectification unit 414 may be constructed with reference to the embodiment shown in FIGS. 5a-5b.
  • the ultra-high-power wide-range constant power converter of the present invention has an upper and lower combined structure.
  • the first end of the primary winding of the first transformer Ta1 is connected to the first resonant network 210
  • the second end of the primary winding is connected to the first end of the primary winding of the second transformer Ta2
  • the terminals and the first terminals of the secondary windings are connected to the first rectifier unit 411
  • the second terminals of the secondary windings are connected to the second terminals of the secondary windings of the first transformers Tb1 and Tc1 .
  • the second end of the primary winding of the second transformer Ta2 is also connected to the first resonant network 210, the first end of the secondary winding is connected to the second rectifier unit 412, and the second end of the secondary winding is connected to the second rectifier unit 412.
  • the first end of the primary winding of the first transformer Tb1 is connected to the second resonant network 220
  • the second end of the primary winding is connected to the first end of the primary winding of the second transformer Tb2
  • the second end of the secondary winding is connected to the second resonant network 220.
  • the first end is connected to the first rectifying unit 411 .
  • the second end of the primary winding of the second transformer Tb2 is also connected to the second resonant network 220 , and the first end of the secondary winding is connected to the second rectifier unit 412 .
  • the first end of the primary winding of the first transformer Tc1 is connected to the third resonant network 230, the second end of the primary winding is connected to the first end of the primary winding of the second transformer Tc2, and the second end of the secondary winding is connected to the second transformer Tc2.
  • the first end is connected to the first rectifying unit 411 .
  • the second end of the primary winding of the second transformer Tc2 is also connected to the third resonant network 230 , and the first end of the secondary winding is connected to the second rectifier unit 412 .
  • the first end of the primary winding of the third transformer Ta3 is connected to the fourth resonant network 240 , and the second end of the primary winding is connected to the first end and the secondary winding of the fourth transformer Ta4
  • the first end of the side winding is connected to the third rectifier unit 413, and the second end of the secondary side winding is connected to the second ends of the secondary side windings of the third transformers Tb3 and Tc3.
  • the second end of the primary winding of the fourth transformer Ta4 is also connected to the fourth resonant network 240, the first end of the secondary winding is connected to the fourth rectifier unit 414, and the second end of the secondary winding is connected to the fourth rectifier unit 414.
  • the first end of the primary winding of the third transformer Tb3 is connected to the fifth resonant network 250, the second end of the primary winding is connected to the first end of the primary winding of the fourth transformer Tb4, and the second end of the primary winding of the fourth transformer Tb4.
  • the first end is connected to the third rectifying unit 413 .
  • the second end of the primary winding of the fourth transformer Tb4 is also connected to the fifth resonance network 250 , and the first end of the secondary winding is connected to the fourth rectifying unit 414 .
  • the first end of the primary winding of the third transformer Tc3 is connected to the sixth resonant network 260, the second end of the primary winding is connected to the first end of the primary winding of the fourth transformer Tc4, and the second end of the primary winding of the fourth transformer Tc4.
  • the first end is connected to the third rectifying unit 413 .
  • the second end of the primary winding of the fourth transformer Tc4 is also connected to the sixth resonant network 260 , and the first end of the secondary winding is connected to the fourth rectifying unit 414 .
  • the first rectification unit 411 and the second rectification unit 412 are connected in parallel, and the third rectification unit 413 and the fourth rectification unit 414 are connected in parallel.
  • the high and low voltage control module 600 controls the switching of the switching devices in the switching module 500 so that the first rectification network 410 and the third rectification network 410 formed by the first rectification unit 411 and the second rectification unit 412 and the third
  • the second rectification network 420 formed by the rectification unit 413 and the fourth rectification unit 414 is connected in parallel, in series or independently to output voltage.
  • any suitable switch network, resonant network, transformer network, and rectifier unit described anywhere in this application can be used for combination, so as to construct the ultra-high power wide-range constant power conversion of the present invention device.
  • the primary windings of the transformer module are respectively connected to the switching network through the resonant network, the secondary windings form a star connection, and are rectified by the rectifier module to generate two output voltages.
  • the two output voltages can be connected in series, in parallel or independently, which can achieve an ultra-wide range of constant power output, which can cover 1000V ⁇ 250V high and low voltage electric power.
  • the ultra-wide range constant power charging of the car can fast charge the car of different voltage levels.
  • first switch network and the fourth switch network are connected in series with each other, the second switch network and the fifth switch network are connected in series with each other, and the third switch network and the sixth switch network are connected in series with each other, so Switching devices do not need to be connected in parallel to achieve high-power output, and there is no reliability problem caused by paralleling switching devices. Therefore, various types of switching devices can be used, especially low-cost silicon switching devices can be used.
  • FIG. 15 is a circuit diagram of the sixth preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • the embodiment shown in FIG. 15 is similar to the embodiment shown in FIG. 14 , the difference is that the first transformer network 310 , the second transformer network 320 , the third transformer network 330 , the fourth transformer network 340 , and the fifth transformer network 350 , the configuration of the sixth transformer network 360 , the first rectifier network 410 , and the second rectifier network 420 .
  • the preferred embodiment shown in FIG. 15 includes a larger number of rectifier bridges and transformers, which is more suitable for the situation of ultra-high power output.
  • the first transformer network 310, the second transformer network 320, and the third transformer network 330 respectively include first transformers Ta1, Tb1, Tc1 and second transformers Ta2, Tb2, Tc2.
  • the fourth transformer network 340, the fifth transformer network 350, and the sixth transformer network 360 respectively comprise third transformers Ta3, Tb3, Tc3 and fourth transformers Ta4, Tb4, Tc4 connected in series with primary windings .
  • the first rectification network 410 includes a first rectification unit 411 and a second rectification unit 412
  • the second rectification network 420 includes a third rectification unit 413 and a fourth rectification unit 414 .
  • the first rectifier unit 411 and the second rectifier unit 412 respectively include a diode rectifier bridge composed of diodes D11-D16.
  • the third rectifier unit 413 and the fourth rectifier unit 414 also respectively include a diode rectifier bridge composed of diodes D21-D26.
  • each resonant network includes two LC series resonant cells.
  • the ultra-high-power wide-range constant power converter of the present invention has an upper and lower combined structure. Therefore, only the upper circuit is further described as follows, and the connection relationship of the lower circuit is similar to FIG. 15 .
  • the first end of the primary winding of the first transformer Ta1 is connected to the first output end and the primary side of the switching device full-bridge topology formed by the switching devices S1-S4 through the capacitor Cr and the inductance Lr connected in series.
  • the second end of the winding is connected to the first end of the primary winding of the second transformer Ta2, and the first end of the secondary winding is connected to the first input end and the secondary side of the first diode rectifier bridge formed by diodes D11-D16.
  • the second ends of the windings are connected to the second ends of the secondary windings of the first transformers Tb1 and Tc1.
  • the second end of the primary winding of the second transformer Ta2 is also connected to the second output end of the full-bridge topology of the switching device formed by the switching devices S1-S4 through the capacitor Cr and the inductance Lr connected in series, and the first end of the secondary winding is connected.
  • the first input end and the second end of the secondary winding of the second diode rectifier bridge formed by the diodes D11-D16 are connected to the second ends of the secondary windings of the second transformers Tb2 and Tc2.
  • the first end of the primary winding of the first transformer Tb1 is connected to the first output end of the switching device full-bridge topology formed by the switching devices S5-S8 through the capacitor Cm and the inductance Lr connected in series, and the second end of the primary winding is connected to the other end.
  • the first end of the primary winding and the first end of the secondary winding of the second transformer Tb2 are connected to the second input end of the first diode rectifier bridge formed by the diodes D11-D16.
  • the second end of the primary winding of the second transformer Tb2 is connected to the second output end of the switching device full-bridge topology formed by the switching devices S5-S8 through the capacitor Cm and the inductance Lr connected in series, and the first end of the secondary winding is connected to the second output end of the switching device full-bridge topology.
  • the first end of the primary winding of the first transformer Tc1 is also connected to the first output end of the switching device full-bridge topology formed by the switching devices S9-S12 through the capacitor Cr and the inductance Lr connected in series, and the second end of the primary winding is connected.
  • the first end of the primary winding and the first end of the secondary winding of the second transformer Tc2 are connected to the third input end of the first diode rectifier bridge formed by the diodes D11-D16.
  • the second end of the primary winding of the second transformer Tc2 is also connected to the second output end of the switching device full-bridge topology formed by the series-connected capacitor Cr and the inductor Lr connected to the switching devices S9-S12, and the first end of the secondary winding.
  • the third input terminal of the second diode rectifier bridge formed by the diodes D11-D16 is connected.
  • the diodes D11-D16, the switching devices S1-S12, and K1-K3 can be silicon switching devices or silicon carbide switching devices. For cost savings, silicon switching devices are preferably used.
  • the primary winding of the transformer is composed of two combined three-phase LLC resonant conversion networks connected in series, the primary winding of the transformer is independently connected to each phase bridge switch network, and the secondary windings of the three-phase transformer are connected to form a
  • the stars are connected, and then connected in parallel through three-phase rectification to achieve high power output.
  • the control switches K1 ⁇ K3 by the high and low voltage mode controller, the ultra-wide range constant power output can be realized, which can realize the ultra-wide range constant power charging that can cover 1000V ⁇ 250V high and low voltage electric vehicles, and can charge different voltage levels. car to fast charge.
  • the switching devices of the primary winding and the secondary winding of the transformer (such as switching devices S1-S12, D1-D16 and K1-K3). High-power output can be achieved without parallel connection, and there is no reliability problem of parallel connection of switching devices.
  • the three-phase interleaved operation is realized, so that the current ripple of the primary side and the secondary side busbar is greatly reduced, thereby reducing the volume of the primary side and the secondary side filter.
  • especially low-cost silicon switching devices can be used, and an ultra-wide range of constant power output can be achieved.
  • FIG. 13 is a schematic block diagram of the fourth preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • the ultra-high-power wide-range constant power converter includes: a first switching network 110 , a second switching network 120 , a third switching network 130 , a fourth switching network 140 , a fifth switching network 150 , a sixth switching network 150 , and a sixth switching network 130 .
  • Switching network 160 first resonant network 210, second resonant network 220, third resonant network 230, fourth resonant network 240, fifth resonant network 250, sixth resonant network 260, transformer module 300, rectifier module 400, switch module 500 and the high and low voltage control module 600.
  • the transformer module 300 includes a first transformer network 310 , a second transformer network 320 and a third transformer network 330
  • the rectifier module 400 includes a first rectifier network 410 , a second rectifier network 420 , and a third rectifier network 430 and fourth rectifier network 440 .
  • the primary winding of the first transformer network 310 is connected to the first switching network 110 and the second switching network 120 via the first resonant network 210 and the second resonant network 220 respectively.
  • the second transformer The primary winding of the network 320 is connected to the third switching network 130 and the fourth switching network 140 via the third resonant network 230 and the fourth resonant network 240 respectively.
  • the primary side of the third transformer network 330 The windings connect the fifth switching network 150 and the sixth switching network 160 via the fifth resonant network 250 and the sixth resonant network 260, respectively.
  • the secondary windings of the first transformer network 310 are respectively connected to the first rectifier network 410 , the second rectifier network 420 , the third rectifier network 430 and the fourth rectifier network 440 .
  • the side windings are respectively connected to the first rectifier network 410 , the second rectifier network 420 , the third rectifier network 430 and the fourth rectifier network 440 , and the secondary side windings of the third transformer network 330 are respectively connected to the third rectifier network 430 .
  • a rectifier network 410 , the second rectifier network 420 , the third rectifier network 430 and the fourth rectifier network 440 are respectively connected to the third rectifier network 430 .
  • the secondary windings of the first transformer network 310 , the second transformer network 320 and the third transformer network 330 are alternately connected to each other, such as star connection or delta connection.
  • the first rectifier network 410 and the second rectifier network 420 are connected in parallel with each other, and the third rectifier network 430 and the fourth rectifier network 440 are connected in parallel with each other.
  • the high and low voltage control module 600 controls the switching of the switching devices in the switch module 500 to control the parallel connection of the first rectifier network 410 and the second rectifier network 420 and the parallel connection of the third rectifier network 430 and all of them.
  • the fourth rectifier network 440 further performs voltage output in parallel, in series or independently.
  • any suitable switch network, resonant network, transformer network, and rectifier network described anywhere in this application are combined to construct the ultra-high power wide-range constant power converter of the present invention.
  • high-voltage silicon carbide switching devices can be used, which can reduce the number of switching devices and also achieve ultra-high power wide-range constant power. output.
  • the ultra-high-power wide-range constant power converter includes: a first switching network 110 , a second switching network 120 , a third switching network 130 , a fourth switching network 140 , a fifth switching network 150 , a sixth switching network 150 , and a sixth switching network 130 .
  • Switching network 160 first resonant network 210, second resonant network 220, third resonant network 230, fourth resonant network 240, fifth resonant network 250, sixth resonant network 260, transformer module 300, rectifier module 400, switch module 500 and the high and low voltage control module 600.
  • the transformer module 300 includes a first transformer network 310, a second transformer network 320 and a third transformer network 330
  • the rectifier module 400 includes a first rectifier network 410, a second rectifier network 420, a third rectifier network 430 and a fourth rectifier network Rectification network 440
  • the first transformer network 310, the second transformer network 320, and the third transformer network 330 respectively include first transformers T11-T31, second transformers T12-T32, third transformers T13-T33 and Fourth transformer T14-T34.
  • the first end of the primary winding of the first transformer T11 is connected to the output end of the switching device half-bridge topology formed by the switching devices S1-S2 through the capacitor Cr and the inductance Lr connected in series, and the second end of the primary winding is connected to the first The first end of the primary winding of the second transformer T12, the second end of the primary winding of the second transformer T12 is connected to the first end of the primary winding of the third transformer T13, and the primary winding of the third transformer T13
  • the second end of the side winding is connected to the first end of the primary side winding of the fourth transformer T14, and the second end of the primary side winding of the fourth transformer T14 is connected to the switching devices S3-S4 through the capacitor Cr and the inductor Lr connected in series
  • the output end of the half-bridge topology of the switching device formed, the first end of the secondary winding of the first transformer T11 is connected to the first input end of the first diode rectifier bridge formed by the diodes D11-D
  • the two ends are connected to the second ends of the secondary windings of the first transformers T21 and T31.
  • the first end of the secondary winding of the second transformer T12 is connected to the first input end of the second diode rectifier bridge formed by diodes D11-D16, and the second end of the secondary winding is connected to the secondary of the second transformers T22 and T32. the second end of the side winding.
  • the first end of the secondary winding of the third transformer T13 is connected to the first input end of the third diode rectifier bridge formed by diodes D11-D16, and the second end of the secondary winding is connected to the third transformers T23 and T33. the second end of the side winding.
  • the first end of the secondary winding of the fourth transformer T14 is connected to the first input end of the fourth diode rectifier bridge formed by diodes D11-D16, and the second end of the secondary winding is connected to the secondary ends of the fourth transformers T24 and T34. the second end of the side winding.
  • the first end of the primary winding of the first transformer T21 is connected to the output end of the switching device half-bridge topology formed by the switching devices S5-S6 through the capacitor Cr and the inductance Lr connected in series, and the second end of the primary winding is connected.
  • the first end of the primary winding of the second transformer T22, the second end of the primary winding of the second transformer T22 is connected to the first end of the primary winding of the third transformer T23, and the third transformer
  • the second end of the primary winding of T23 is connected to the first end of the primary winding of the fourth transformer T24, and the second end of the primary winding of the fourth transformer T24 is connected to the switching device through the capacitor Cr and the inductor Lr connected in series
  • the output end of the switching device half-bridge topology constituted by S7-S8, the first end of the secondary winding of the first transformer T21 is connected to the second input end of the first diode rectifier bridge constituted by diodes D11-D16.
  • the first end of the secondary winding of the second transformer T22 is connected to the second input end of the second diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the third transformer T23 is connected to the second input end of the third diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the fourth transformer T24 is connected to the second input end of the fourth diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the primary winding of the first transformer T31 is connected to the output end of the switching device half-bridge topology formed by the switching devices S9-S10 through the capacitor Cr and the inductance Lr connected in series, and the second end of the primary winding is connected.
  • the first end of the primary winding of the second transformer T32, the second end of the primary winding of the second transformer T32 is connected to the first end of the primary winding of the third transformer T33, and the third transformer
  • the second end of the primary winding of T33 is connected to the first end of the primary winding of the fourth transformer T34, and the second end of the primary winding of the fourth transformer T34 is connected to the switching device through the capacitor Cr and the inductor Lr connected in series
  • the output end of the switching device half-bridge topology formed by S11-S12, the first end of the secondary winding of the first transformer T31 is connected to the third input end of the first diode rectifier bridge formed by diodes D11-D16.
  • the first end of the secondary winding of the second transformer T32 is connected to the third input end of the second diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the third transformer T33 is connected to the third input end of the third diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the fourth transformer T34 is connected to the third input end of the fourth diode rectifier bridge formed by the diodes D11-D16.
  • the diodes D11-D16, the switching devices S1-S12, and K1-K3 can be silicon carbide switching devices.
  • FIG. 17 is a circuit diagram of a seventh preferred embodiment of the ultra-high power wide-range constant power converter of the present invention.
  • the embodiment shown in FIG. 17 is similar to the embodiment shown in FIG. 16 , except that the first switch network 110 , the second switch network 120 , the third switch network 130 , the fourth switch network 140 , the fifth switch network 150 , the Setting of the sixth switch network 160 .
  • the first switch network 110 , the second switch network 120 , the third switch network 130 , the fourth switch network 140 , the fifth switch network 150 , and the sixth switch network 160 respectively use three power switches. Flat switching device full-bridge topology.
  • the first end of the primary winding of the first transformer T11 is connected to the output end and the primary side of the first three-level switching device full-bridge topology formed by the switching devices S11-S14 and D11-D12 through the capacitor Cr and the inductor Lr connected in series.
  • the second end of the winding is connected to the first end of the primary winding of the second transformer T12, and the second end of the primary winding of the second transformer T12 is connected to the first end of the primary winding of the third transformer T13 , the second end of the primary winding of the third transformer T13 is connected to the first end of the primary winding of the fourth transformer T14, and the second end of the primary winding of the fourth transformer T14 is connected to the capacitor Cr in series
  • the output end of the second three-level switching device full-bridge topology composed of switching devices S21-S24 and D21-D22 is connected to the inductor Lr, and the first end of the secondary winding of the first transformer T11 is connected to the diode D11-D16.
  • the first input end of the first diode rectifier bridge and the second end of the secondary winding are connected to the second ends of the secondary windings of the first transformers T21 and T31.
  • the first end of the secondary winding of the second transformer T12 is connected to the first input end of the second diode rectifier bridge formed by diodes D11-D16, and the second end of the secondary winding is connected to the secondary of the second transformers T22 and T32. the second end of the side winding.
  • the first end of the secondary winding of the third transformer T13 is connected to the first input end of the third diode rectifier bridge formed by diodes D11-D16, and the second end of the secondary winding is connected to the third transformers T23 and T33. the second end of the side winding.
  • the first end of the secondary winding of the fourth transformer T14 is connected to the first input end of the fourth diode rectifier bridge formed by diodes D11-D16, and the second end of the secondary winding is connected to the secondary ends of the fourth transformers T24 and T34. the second end of the side winding.
  • the first end of the primary winding of the first transformer T21 is connected to the output end of the full-bridge topology of the third three-level switching device through the capacitor Cr and the inductor Lr in series, and the second end of the primary winding is connected to the The first end of the primary winding of the second transformer T22, the second end of the primary winding of the second transformer T22 is connected to the first end of the primary winding of the third transformer T23, the third transformer T23
  • the second end of the primary winding is connected to the first end of the primary winding of the fourth transformer T24, and the second end of the primary winding of the fourth transformer T24 is connected to the fourth and third electrical circuits through the capacitor Cr and the inductor Lr connected in series.
  • the output end of the full-bridge topology of the flat switching device the first end of the secondary winding of the first transformer T21 is connected to the second input end of the first diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the second transformer T22 is connected to the second input end of the second diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the third transformer T23 is connected to the second input end of the third diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the fourth transformer T24 is connected to the second input end of the fourth diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the primary winding of the first transformer T31 is connected to the output end of the full-bridge topology of the fifth three-level switching device through the capacitor Cr and the inductor Lr in series, and the second end of the primary winding is connected to the The first end of the primary winding of the second transformer T32, the second end of the primary winding of the second transformer T32 is connected to the first end of the primary winding of the third transformer T33, the third transformer T33
  • the second end of the primary winding is connected to the first end of the primary winding of the fourth transformer T34, and the second end of the primary winding of the fourth transformer T34 is connected to the sixth and third electrical circuits through the capacitor Cr and the inductor Lr connected in series.
  • the first end of the secondary winding of the first transformer T31 is connected to the third input end of the first diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the second transformer T32 is connected to the third input end of the second diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the third transformer T33 is connected to the third input end of the third diode rectifier bridge formed by the diodes D11-D16.
  • the first end of the secondary winding of the fourth transformer T34 is connected to the third input end of the fourth diode rectifier bridge formed by the diodes D11-D16.
  • the diodes D11-D16 and the switching devices K1-K3 can be silicon carbide switching devices, and the switching devices S21-S24 and D21-D22 can be silicon switching devices.
  • the primary windings of the transformer module are respectively connected to the switching network through the resonant network, the secondary windings form a star connection, and are rectified by the rectifier module to generate two output voltages.
  • the two output voltages can be connected in series, in parallel or independently, which can achieve an ultra-wide range of constant power output, which can cover 1000V ⁇ 250V high and low voltage electric power.
  • the ultra-wide range constant power charging of the car can fast charge the car of different voltage levels.
  • first switch network and the fourth switch network are connected in series with each other, the second switch network and the fifth switch network are connected in series with each other, and the third switch network and the sixth switch network are connected in series with each other, so Switching devices do not need to be connected in parallel to achieve high-power output, and there is no reliability problem caused by paralleling switching devices. Therefore, various types of switching devices can be used, especially low-cost silicon switching devices can be used.
  • high-voltage silicon carbide switching devices can be used, which can reduce the number of switching devices and also achieve ultra-high power wide-range constant power. output.

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Abstract

一种交错式功率变换器和超大功率宽范围恒功率变换器，交错式功率变换器包括：第一-第三开关网络（110、120、130）、第一-第三谐振网络（210、220、230）、变压器模块（300）和整流模块（400）。第一-第三开关网络（110、120、130）的第一输入端彼此连接并接收输入电压（Vin），第一-第三开关网络（110、120、130）的第二输入端同样彼此连接。第一开关网络（110）经第一谐振网络（210）、第二开关网络（120）经第二谐振网络（220）、第三开关网络（130）经第三谐振网络（230）分别连接变压器模块（300）的各个原边绕组；变压器模块（300）的各个副边绕组的第一端彼此连接、第二端连接整流模块（400）。第一-第三谐振网络（210、220、230）交错运行，整流模块（400）输出输出电压（Vo）。通过谐振网络的交错，无需变压器模块（300）的原边耦合即可实现均流和大功率输出，并且输入和输出的纹波电流都能得到大幅减少。

Description

交错式功率变换器和超大功率宽范围恒功率变换器 技术领域
本发明涉及电源领域，更具体地说，涉及一种交错式功率变换器和超大功率宽范围恒功率变换器。
 背景技术
充电电源模块是直流充电桩的核心部件，对推动新能源汽车发展至关重要。直流快充的需求，对充电电源模块的功率要求逐渐增大，从7.5KW，到15kW，20KW，以及现在的30KW、40KW。在大功率充电模块中，通常采用功率管并联来提高输出功率，同时采用交错并联来减小输出纹波。但是功率管直接并联，会带来不均流的问题，降低器件可靠性。交错并联选择不当，因为参数的偏差，也会存在不均流的问题。
 技术问题
本发明要解决的技术问题在于，针对现有技术的上述缺陷，提供一种能够实现大功率输出并且能够实现谐振网络之间的均流的交错式功率变换器和超大功率宽范围恒功率变换器。
 技术解决方案
本发明解决其技术问题所采用的技术方案是：构造一种交错式功率变换器，包括：第一开关网络、第二开关网络、第三开关网络、第一谐振网络、第二谐振网络、第三谐振网络、变压器模块和整流模块；
所述第一开关网络、所述第二开关网络和所述第三开关网络的第一输入端彼此连接并接收输入电压，所述第一开关网络、所述第二开关网络和所述第三开关网络的第二输入端同样彼此连接，所述第一开关网络的输出端经所述第一谐振网络、所述第二开关网络的输出端经所述第二谐振网络、所述第三开关网络的输出端经所述第三谐振网络分别连接所述变压器模块的各个原边绕组；所述变压器模块的各个副边绕组的第一端彼此连接、第二端连接所述整流模块；
所述第一谐振网络、所述第二谐振网络和所述第三谐振网络交错运行，所述整流模块输出输出电压。
本发明还涉及一种超大功率宽范围恒功率变换器，包括：第一开关网络、第二开关网络、第三开关网络、第四开关网络、第五开关网络、第六开关网络、第一谐振网络、第二谐振网络、第三谐振网络、第四谐振网络、第五谐振网络、第六谐振网络、变压器模块、整流模块、开关模块和高低压控制模块；
所述第一开关网络、所述第二开关网络和所述第三开关网络的第一输入端彼此连接并接收第一输入电压，所述第四变压器网络、所述第五变压器网络和第六变压器网络的第一输入端彼此并联以接收第二输入电压，所述第一开关网络的第二输入端串联所述第四开关网络的第二输入端，所述第二开关网络的第二输入端串联所述第五开关网络的第二输入端，所述第三开关网络的第二输入端串联所述第六开关网络的第二输入端；
所述第一开关网络的输出端经所述第一谐振网络、所述第二开关网络的输出端经所述第二谐振网络、所述第三开关网络的输出端经所述第三谐振网络、所述第四开关网络的输出端经所述第四谐振网络、所述第五开关网络的输出端经所述第五谐振网络、所述第六开关网络的输出端经所述第六谐振网络分别连接所述变压器模块的各个原边绕组；所述变压器模块的各个副边绕组的一端彼此连接、另一端连接所述整流模块；所述第一谐振网络、所述第二谐振网络和所述第三谐振网络交错运行，所述第四变压器网络、所述第五变压器网络和第六变压器网络交错运行；
所述整流模块分别输出第一输出电压和第二输出电压到所述开关模块，所述高低压控制模块控制所述开关模块中的开关器件切换以实现所述超大功率宽范围恒功率变换器的超大功率和超宽范围的恒功率输出。
 有益效果
实施本发明的交错式功率变换器和超大功率宽范围恒功率变换器，通过谐振网络的交错，无需变压器模块的原边耦合即可实现均流和大功率输出，并且输入和输出的纹波电流都能得到大幅减少。
进一步地，实施本发明的超大功率宽范围恒功率变换器，变压器模块的各个原边绕组分别经谐振网络连接开关网络、副边绕组形成星形连接并经整流模块整流后产生两个输出电压，通过并联这两个输出电压可以实现超大功率输出，而同时通过高低压控制模块控制开关模块中的开关器件切换可以将两个输出电压串联、并联或者单独输出，可以实现超宽范围的恒功率输出，能够实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。并且所述第一开关网络和所述第四开关网络彼此串联，所述第二开关网络和所述第五开关网络彼此串联，所述第三开关网络和所述第六开关网络彼此串联，因此开关器件不需要并联就能够实现大功率的输出，没有开关器件并联导致的可靠性问题。
 附图说明
下面将结合附图及实施例对本发明作进一步说明，附图中：
图1是本发明的交错式功率变换器的第一优选实施例的原理框图；
图2a-2d示出了根据本发明的优选实施例的开关网络的电路图；
图3a-3d示出了根据本发明的优选实施例的谐振网络的电路图；
图4a-4e示出了根据本发明的优选实施例的LLC串联谐振单元的电路图；
图5a-5b示出了根据本发明的优选实施例的整流网络、整流单元或者整流模块的电路图；
图6a-6c示出了根据本发明的优选实施例的变压器网络的电路图；
图7是本发明的交错式功率变换器的第二优选实施例的原理框图；
图8示出了图7所示的交错式功率变换器的整流电流和输出电容电流的仿真结果；
图9是本发明的交错式功率变换器的第三优选实施例的原理框图；
图10是本发明的超大功率宽范围恒功率变换器的第一优选实施例的原理框图；
图11是本发明的超大功率宽范围恒功率变换器的第二优选实施例的原理框图；
图12是本发明的超大功率宽范围恒功率变换器的第三优选实施例的原理框图；
图13是本发明的超大功率宽范围恒功率变换器的第四优选实施例的原理框图；
图14是本发明的超大功率宽范围恒功率变换器的第五优选实施例的电路图；
图15是本发明的超大功率宽范围恒功率变换器的第六优选实施例的电路图；
图16是本发明的超大功率宽范围恒功率变换器的第七优选实施例的电路图；
图17是本发明的超大功率宽范围恒功率变换器的第七优选实施例的电路图。
 本发明的最佳实施方式
为了使本发明的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本发明进行进一步详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本发明，并不用于限定本发明。
本发明的一个方面涉及一种交错式功率变换器，包括：第一开关网络、第二开关网络、第三开关网络、第一谐振网络、第二谐振网络、第三谐振网络、变压器模块和整流模块；所述第一开关网络、所述第二开关网络和所述第三开关网络的第一输入端彼此连接并接收输入电压，所述第一开关网络、所述第二开关网络和所述第三开关网络的第二输入端同样彼此连接，所述第一开关网络的输出端经所述第一谐振网络、所述第二开关网络的输出端经所述第二谐振网络、所述第三开关网络的输出端经所述第三谐振网络分别连接所述变压器模块的各个原边绕组；所述变压器模块的各个副边绕组的第一端彼此连接、第二端连接所述整流模块；所述第一谐振网络、所述第二谐振网络和所述第三谐振网络交错运行，所述整流模块输出输出电压。本发明通过谐振网络的交错，无需变压器模块的原边耦合即可实现均流和大功率输出，并且输入和输出的纹波电流都能得到大幅减少。
本发明的另一个方面涉及一种超大功率宽范围恒功率变换器，包括：第一开关网络、第二开关网络、第三开关网络、第四开关网络、第五开关网络、第六开关网络、第一谐振网络、第二谐振网络、第三谐振网络、第四谐振网络、第五谐振网络、第六谐振网络、变压器模块、整流模块、开关模块和高低压控制模块；所述第一开关网络、所述第二开关网络和所述第三开关网络的第一输入端彼此连接并接收第一输入电压，所述第四变压器网络、所述第五变压器网络和第六变压器网络的第一输入端彼此并联以接收第二输入电压，所述第一开关网络的第二输入端串联所述第四开关网络的第二输入端，所述第二开关网络的第二输入端串联所述第五开关网络的第二输入端，所述第三开关网络的第二输入端串联所述第六开关网络的第二输入端；所述第一开关网络的输出端经所述第一谐振网络、所述第二开关网络的输出端经所述第二谐振网络、所述第三开关网络的输出端经所述第三谐振网络、所述第四开关网络的输出端经所述第四谐振网络、所述第五开关网络的输出端经所述第五谐振网络、所述第六开关网络的输出端经所述第六谐振网络分别连接所述变压器模块的各个原边绕组；所述变压器模块的各个副边绕组的一端彼此连接、另一端连接所述整流模块；所述第一谐振网络、所述第二谐振网络和所述第三谐振网络交错运行，所述第四变压器网络、所述第五变压器网络和第六变压器网络交错运行；所述整流模块分别输出第一输出电压和第二输出电压到所述开关模块，所述高低压控制模块控制所述开关模块中的开关器件切换以实现所述超大功率宽范围恒功率变换器的超大功率和超宽范围的恒功率输出。
本发明通过谐振网络的交错，无需变压器模块的原边耦合即可实现均流和大功率输出，并且输入和输出的纹波电流都能得到大幅减少。并且变压器模块的各个原边绕组分别经谐振网络连接开关网络、副边绕组形成星形连接并经整流模块整流后产生两个输出电压，通过并联这两个输出电压可以实现超大功率输出，而同时通过高低压控制模块控制开关模块中的开关器件切换可以将两个输出电压串联、并联或者单独输出，可以实现超宽范围的恒功率输出，能够实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。并且所述第一开关网络和所述第四开关网络彼此串联，所述第二开关网络和所述第五开关网络彼此串联，所述第三开关网络和所述第六开关网络彼此串联，因此开关器件不需要并联就能够实现大功率的输出，没有开关器件并联导致的可靠性问题。
图1是本发明的交错式功率变换器的第一优选实施例的原理框图。如图1所示，本发明的交错式功率变换器，包括：第一开关网络110、第二开关网络120、第三开关网络130、第一谐振网络210、第二谐振网络220、第三谐振网络230、变压器模块300和整流模块400。所述第一开关网络110、所述第二开关网络120和所述第三开关网络130的第一输入端彼此连接并接收输入电压Vin，所述第一开关网络110、所述第二开关网络120和所述第三开关网络130的第二输入端同样彼此连接。所述第一开关网络110的输出端经所述第一谐振网络210、所述第二开关网络120的输出端经所述第二谐振网络220、所述第三开关网络130的输出端经所述第三谐振网络230分别连接所述变压器模块300的各个原边绕组。所述变压器模块300的各个副边绕组的第一端彼此连接、第二端连接所述整流模块400。所述第一谐振网络210、所述第二谐振网络220和所述第三谐振网络230交错运行，所述整流模块400输出输出电压Vo。
在本发明的一个优选实施例中，所述第一开关网络110、所述第二开关网络120、所述第三开关网络130为相同的结构，其可以包括开关器件全桥拓扑电路、开关器件对称半桥拓扑电路或开关器件不对称半桥拓扑电路。这些开关器件全桥拓扑电路、开关器件对称半桥拓扑电路或开关器件不对称半桥拓扑电路可以是两相的，如图2a-2c所示，也可以是三相的，如图2d所示。
在本发明的一个优选实施例中，所述第一谐振网络210、所述第二谐振网络220、所述第三谐振网络230分别包括LC谐振单元、LLC串联谐振单元、SRC串联谐振单元、PRC并联谐振单元和LCC串并联谐振单元。例如其可以是由电感Lr、电感Lm(变压器模块的等效电感) 和电容Cr组成的LLC串联谐振单元，也可以是由电感Lr、电容Cr组成的SRC串联谐振单元；电感Lr、电容Cr组成的PRC并联谐振变换器（电容和变压器并联）；电感Lr，电容Cr，电容Cpr组成的LCC串并联谐振变换器，分别如图3a-3d所示。在本发明的一个优选实施例中，所述第一谐振网络210、所述第二谐振网络220和所述第三谐振网络230彼此120度交错运行。当然，在本发明的其他优选实施例中，还可以选择其他适合的交错角度。
在本发明的一个优选实施例中，所述第一谐振网络210、所述第二谐振网络220、所述第三谐振网络230可以分别采用LLC串联谐振单元，其包括串联连接的电感Lr、电感Lm和电容Cr，相互串联的位置可以任意变换，电容Cr可以放置到电感Lr前，也可以放置在电感Lr和电感Lm之间。电感Lm可以采用变压器模块的感应电感，也可以采用单独的电感。电感Lr、电感Lm和电容Cr三个元件也可以分别拆分成多个电感或电容串并联，并任意摆放串联的位置。电感Lr拆分成多个电感时，可以是单独的电感，也可以是相互耦合电感，如图4a-4e所示。
在本发明的一个优选实施例中，所述整流模块400包括至少一个开关器件整流桥, 例如二极管整流单元、开关管同步整流单元等等，如图5a-5b所示。
在本发明的一个优选实施例中，所述变压器模块300包括第一变压器网络、第二变压器网络和第三变压器网络。每个变压器网络可以包括一个变压器或者两个串联的变压器，例如图6a-6b所示。以第一变压器网络为例，电感Lma1、Lma2分别和变压器Ta1、Ta2的原边绕组并联，这里电感Lma1/Lma2可以是单独设计的电感，也可以集成设计在变压器里。电感Lma1和 Lma2串联，最终等效为电感Lm，如图6a-6b所示。电感Lm可以集成或者单独设计的电感Lma1、Lma2的等效，也可是单独设计的电感Lm。同样地，所述第二变压器网络、所述第三变压器网络中变压器和等效电感Lm的连接方式类似。又例如，每个变压器网络也可以包括多个串联的变压器，例如4个串联的变压器，其副边连接成星星连接如图6c所示。
在本发明的各个优选实施例中，可以采用本申请全文中任何位置所描述的任何适合的开关网络、谐振网络、变压器模块、整流模块进行组合，从而构建本发明的超大功率宽范围恒功率变换器。
实施本发明的交错式功率变换器和超大功率宽范围恒功率变换器，通过谐振网络的交错，无需变压器模块的原边耦合即可实现均流和大功率输出，并且输入和输出的纹波电流都能得到大幅减少。
图7是本发明的交错式功率变换器的第二优选实施例的原理框图。本发明的交错式功率变换器，包括：第一开关网络110、第二开关网络120、第三开关网络130、第一谐振网络210、第二谐振网络220、第三谐振网络230、变压器模块300和整流模块400。在本优选实施例中，所述变压器模块300包括所述第一变压器网络、第二变压器网络和第三变压器网络，每个变压器网络分别包括一个第一变压器，即变压器T1-T3。所述整流模块400包括二极管D11-D16构成的二极管整流桥。
所述第一开关网络110、所述第二开关网络120和所述第三开关网络130的第一输入端彼此连接并接收输入电压Vin，所述第一开关网络110、所述第二开关网络120和所述第三开关网络130的第二输入端同样彼此连接。所述第一开关网络110的输出端经所述第一谐振网络210连接变压器T1的原边绕组，所述第二开关网络120的输出端经所述第二谐振网络220连接变压器T2的原边绕组，所述第三开关网络130的输出端经所述第三谐振网络230连接变压器T3的原边绕组。所述变压器T1、所述变压器T2和所述变压器T3的副边绕组的第一端分别连接二极管D11-D16构成的二极管整流桥的第一输入端、第二输入端和第三输入端，所述变压器T1、所述变压器T2和所述变压器T3的副边绕组的第二端分别彼此连接，即如图7所示形成Y形连接。二极管D11-D16构成的二极管整流桥的输出端连接输出电容C以输出输出电压Vo。
在本发明的一个优选实施例中，所述第一谐振网络210、所述第二谐振网络220和所述第三谐振网络230彼此120度交错运行，因此所述变压器T1、所述变压器T2和所述变压器T3的副边整流电流及输出电容电流的纹波电流的仿真结果如图8所示，其中上半部分是所述变压器T1、所述变压器T2和所述变压器T3（即三个变压器网络）的各自输出电流，三条曲线4-1、4-2、4-3是分别表示所述变压器T1、所述变压器T2和所述变压器T3的副边电流，可见三路变压器的电流是交错120度的。图8的下半部分是整流模块整流后后输出电流，其中曲线4-4表示的滤波电容C上的纹波电流，曲线4-6表示的是流向最终分负载的电流，曲线4-5是变压器输出电流之和，也是负载电流和电容纹波电流之和。
由于三路变压器T1-T3（即第一-第三变压器网络）输出电流彼此交错，此消彼涨，输出电流中纹波电流占比已经很小。如示例中输出电流15.1A时纹波电流只有1.24A，约占总输出电流的8.2%；而不交错运行的纹波电流占比约为48%；交错运行后，纹波电流大幅下降到了不交错方案的1/6。因此，实施本发明的交错式功率变换器，通过谐振网络的交错，无需变压器模块的原边耦合即可实现均流和大功率输出，并且输入和输出的纹波电流都能得到大幅减少有利于减小滤波器的体积和成本。
在本发明的进一步的优选实施例中，可以采用本申请全文中任何位置所描述的任何适合的开关网络、谐振网络、变压器模块、整流模块进行组合，从而构建本发明的交错式功率变换器。
图9是本发明的交错式功率变换器的第三优选实施例的原理框图。如图9所示，本发明的交错式功率变换器，包括：第一开关网络110、第二开关网络120、第三开关网络130、第一谐振网络210、第二谐振网络220、第三谐振网络230、变压器模块300和整流模块400。在本优选实施例中，所述变压器模块300包括所述第一变压器网络、第二变压器网络和第三变压器网络。所述第一变压器网络、所述第二变压器网络、所述第三变压器网络分别包括原边绕组串联的第一变压器Ta1-Tc1和第二变压器Ta2-Tc2。所述整流模块400包括第一整流网络和第二整流网络。所述第一整流网络和第二整流网络分别包括二极管D11-D16构成的二极管整流桥。
图9所示实施例的构造和原理与图8类似，其区别主要在于变压器模块300和整流模块400的设计，在此仅对其进一步说明如下。如图9所示，所述第一变压器Ta1的原边绕组的第一端连接所述第一谐振网络210的第一端、原边绕组的第二端连接所述第二变压器Ta2的原边绕组的第一端，所述第二变压器Ta2的原边绕组的第二端连接所述第一谐振网络210的第二端。所述第一变压器Ta1的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第一输入端，副边绕组的第二端连接所述第一变压器Tb1的副边绕组的第二端和所述第一变压器Tc1的副边绕组的第二端。所述第二变压器Ta2的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第一输入端，副边绕组的第二端连接所述第二变压器Tb2的副边绕组的第二端和所述第二变压器Tc2的副边绕组的第二端。
类似地，所述第一变压器Tb1的原边绕组的第一端连接所述第二谐振网络220的第一端、原边绕组的第二端连接所述第二变压器Tb2的原边绕组的第一端，所述第二变压器Tb2的原边绕组的第二端连接所述第二谐振网络220的第二端。所述第一变压器Tb1的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第二输入端。所述第二变压器Tb2的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第二输入端。所述第一变压器Tb1的原边绕组的第一端连接所述第三谐振网络230的第一端、原边绕组的第二端连接所述第二变压器Tb2的原边绕组的第一端，所述第二变压器Tb2的原边绕组的第二端连接所述第三谐振网络230的第二端。所述第一变压器Tb1的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第二输入端。所述第二变压器Tb2的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第二输入端。二极管D11-D16构成的第一二极管整流桥和二极管D11-D16构成的第二二极管整流桥的输出端连接输出电容C11和C12的两端以并联并输出所述输出电压Vo。
在本发明的优选实施例中，可以采用任何前述开关网络、谐振网络构建所述第一开关网络110、第二开关网络120、第三开关网络130、第一谐振网络210、第二谐振网络220、第三谐振网络230。
本发明通过谐振网络的交错，无需变压器模块的原边耦合即可实现均流和大功率输出，并且输入和输出的纹波电流都能得到大幅减少。进一步的，采用多个变压器副边耦合，可以达到大功率输出目的。
由于直流快充的需求，对充电电源模块的功率和宽范围的恒功率要求越来越高。一方面，充电电源模块的功率逐渐增大，从7.5KW，到15kW，20KW，以及现在的30KW、40KW。另一方面，针对不同类型的车，充电电源模块的恒功率范围也逐渐扩大，从600V~750V、375V~500V恒功率范围，到500V~1000V，300V~500V恒功率，以及300V~1000V恒功率。通过将本发明的前述交错式功率变换器的进行组合，可以实现超宽范围的恒功率输出的超大功率宽范围恒功率变换器。因此本发明的另一个方面公开了一种超大功率宽范围恒功率变换器。
图10是本发明的超大功率宽范围恒功率变换器的第一优选实施例的原理框图。如图10所示，所述超大功率宽范围恒功率变换器包括：第一开关网络110、第二开关网络120、第三开关网络130、第四开关网络140、第五开关网络150、第六开关网络160、第一谐振网络210、第二谐振网络220、第三谐振网络230、第四谐振网络240、第五谐振网络250、第六谐振网络260、变压器模块300、整流模块400、开关模块500和高低压控制模块600。
如图10所示，输入电容C1和C2串联，其两端电压分别为Uin。输入电容C1的阳极分别连接第一开关网络110、第二开关网络120、第三开关网络130的第一输入端以接收第一输入电压Uin，阴极连接输入电容C2的阳极。第一开关网络110的第二输入端串联第四开关网络140的第一输入端，第二开关网络120的第二输入端串联第五开关网络150的第一输入端，第三开关网络130的第二输入端串联第六开关网络160的第一输入端。所述输入电容C2的阴极分别连接所述第四开关网络140、第五开关网络150、第六开关网络160的第二输入端以接收第二输入电压Uin。这样，所述第一开关网络110和所述第四开关网络140彼此串联，所述第二开关网络120和所述第五开关网络150彼此串联，所述第三开关网络130和所述第六开关网络160彼此串联。
如图10所示，所述第一开关网络110的输出端经所述第一谐振网络210、所述第二开关网络120的输出端经所述第二谐振网络、所述第三开关网络130的输出端经所述第三谐振网络230、所述第四开关网络140的输出端经所述第四谐振网络240、所述第五开关网络150的输出端经所述第五谐振网络250、所述第六开关网络160的输出端经所述第六谐振网络260分别连接所述变压器模块300的各个原边绕组。所述变压器模块300的各个副边绕组的一端彼此连接以形成星星连接、另一端连接所述整流模块400。所述整流模块400的第一输出端连接输出电容C3的阳极和开关模块500的第一端、第二输出端连接输出电容C3的阴极和开关模块500的第二端以输出第一输出电压到开关模块500。所述整流模块400的第三输出端连接输出电容C4的阳极和开关模块500的第三端、第二输出端连接输出电容C4的阴极和开关模块500的第四端以输出第二输出电压到开关模块500。所述开关模块500包括第一开关器件K1、第二开关器件K2和第三开关器件K3。所述第一开关器件K1连接在所述开关模块500的第二端和第四端之间，所述第三开关器件K3连接在所述开关模块500的第三端和第一端之间，所述第二开关器件K2连接在所述开关模块500的第二端和第三端之间。所述高低压控制模块600控制所述开关模块500中的开关器件进行切换，进而将整流模块400输出的第一输出电压和第二输出电压并联、串联或者单独输出以实现所述超大功率宽范围恒功率变换器的超大功率和超宽范围的恒功率输出到负载R0。
在本发明的一个优选实施例中，所述第一开关器件K1、第二开关器件K2和第三开关器件K3可以是开关管，继电器，接触器等可以实现导通和关断的器件。所述输出电容C3和C4构成所述超大功率宽范围恒功率变换器的输出滤波电路。当然，也可以采用其他滤波模块，例如电感电容滤波模块等等。
在本发明的各个优选实施例中，可以采用本申请全文中任何位置所描述的任何适合的开关网络、谐振网络、变压器模块、整流模块进行组合，从而构建本发明的超大功率宽范围恒功率变换器。
在本发明中，可以采用任何已知的控制方法和步骤通过所述高低压控制模块600控制所述开关模块500，也可以采用任何已知的控制方法对第一-第六开关网络、第一-第六谐振网络、变压器模块、整流模块进行调制。在本发明的优选实施例中，所述第一开关网络110、第二开关网络120、第三开关网络130交错运行，所述第四开关网络140、第五开关网络150、第六开关网络160交错运行，其交错角度可以选择120度进而可以进一步大幅减小输入和输出的纹波电流，进而减小滤波器的体积和成本，具体原理可以参照图1-9所示的交错式功率变换器的描述，在此就不再累述了。
在本发明中，通过谐振网络的交错，无需变压器模块的原边耦合即可实现均流和大功率输出，并且输入和输出的纹波电流都能得到大幅减少；变压器模块的各个原边绕组分别经谐振网络连接开关网络、副边绕组形成星形连接并经整流模块整流后产生两个输出电压，通过并联这两个输出电压可以实现超大功率输出，而同时通过高低压控制模块控制开关模块中的开关器件切换可以将两个输出电压串联、并联或者单独输出，可以实现超宽范围的恒功率输出，能够实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。并且所述第一开关网络和所述第四开关网络彼此串联，所述第二开关网络和所述第五开关网络彼此串联，所述第三开关网络和所述第六开关网络彼此串联，因此开关器件不需要并联就能够实现大功率的输出，没有开关器件并联导致的可靠性问题。因此，可以采用各种类型的开关器件，尤其是可以采用低成本的硅开关器件。
图11是本发明的超大功率宽范围恒功率变换器的第二优选实施例的原理框图。在图11所示的优选实施例中，所述超大功率宽范围恒功率变换器包括：第一开关网络110、第二开关网络120、第三开关网络130、第四开关网络140、第五开关网络150、第六开关网络160、第一谐振网络210、第二谐振网络220、第三谐振网络230、第四谐振网络240、第五谐振网络250、第六谐振网络260、变压器模块300、整流模块400、开关模块500和高低压控制模块600。
在本优选实施例中，所述变压器模块300包括第一变压器网络310、第二变压器网络320、第三变压器网络330、第四变压器网络340、第五变压器网络350、第六变压器网络360。所述整流模块400包括第一整流网络410和第二整流网络420。
如图11所示，输入电容C1和C2串联，其两端电压分别为Uin。输入电容C1的阳极分别连接第一开关网络110、第二开关网络120、第三开关网络130的第一输入端，阴极连接输入电容C2的阳极。所述输入电容C2的阴极分别连接所述第四开关网络140、第五开关网络150、第六开关网络160的第二输入端。第一开关网络110的第二输入端、第二开关网络120的第二输入端、第三开关网络130的第二输入端、第四开关网络140的第一输入端、所述第五开关网络150的第一输入端、所述第六开关网络160的第一输入端彼此连接。这样，所述第一开关网络110和所述第四开关网络140彼此串联，所述第二开关网络120和所述第五开关网络150彼此串联，所述第三开关网络130和所述第六开关网络160彼此串联。
进一步如图11所示，所述第一开关网络110经所述第一谐振网络210连接所述第一变压器网络310，所述第二开关网络120经所述第二谐振网络220连接所述第二变压器网络320，所述第三开关网络130经所述第三谐振网络230连接所述第三变压器网络330，所述第四开关网络140经所述第四谐振网络240连接所述第四变压器网络340，所述第五开关网络150经所述第五谐振网络250连接所述第五变压器网络350，所述第六开关网络160经所述第六谐振网络260连接所述第六变压器网络360。所述第一变压器网络310的原边绕组连接所述第一谐振网络210、副边绕组的第一端连接所述第一整流网络410，所述第二变压器网络320的原边绕组连接所述第二谐振网络220、副边绕组的第一端连接所述第一整流网络410，所述第三变压器网络330的原边绕组连接所述第三谐振网络230、副边绕组的第一端连接所述第一整流网络410，所述第四变压器网络340的原边绕组连接所述第四谐振网络240、副边绕组的第一端连接所述第二整流网络420，所述第五变压器网络350的原边绕组连接所述第二谐振网络220、副边绕组的第一端连接所述第二整流网络420，所述第六变压器网络360的原边绕组连接所述第六谐振网络260、副边绕组的第一端连接所述第二整流网络420。所述第一变压器网络310、所述第二变压器网络320、所述第三变压器网络330的副边绕组的第二端彼此连接；所述第四变压器网络340、所述第五变压器网络350、所述第六变压器网络360的副边绕组的第二端彼此连接。
在本发明的一个优选实施例中，所述第一变压器网络310、所述第二变压器网络320、所述第三变压器网络330可以分别包括第一变压器，所述第一变压器的原边绕组分别连接所述第一谐振网络210、所述第二谐振网络220或所述第三谐振网络230、副边绕组的第一端均连接所述第一整流网络410、副边绕组的第二端彼此连接。所述第四变压器网络340、所述第五变压器网络350、所述第六变压器网络360分别包括第二变压器，所述第二变压器的原边绕组分别连接所述第四谐振网络240、所述第五谐振网络250或所述第六谐振网络260、副边绕组的第一端均连接所述第二整流网络420、副边绕组的第二端彼此连接。所述高低压控制模块600控制所述开关模块500中的开关器件的切换可以使得所述第一整流网络410和第二整流网络420并联、串联或者单独进行电压输出。
在本发明的各个优选实施例中，可以采用本申请全文中任何位置所描述的任何适合的开关网络、谐振网络、变压器网络、整流网络进行组合，从而构建本发明的超大功率宽范围恒功率变换器。
在本发明中，变压器模块的各个原边绕组分别经谐振网络连接开关网络、副边绕组形成星形连接并经整流模块整流后产生两个输出电压，通过并联这两个输出电压可以实现超大功率输出，而同时通过高低压控制模块控制开关模块中的开关器件切换可以将两个输出电压串联、并联或者单独输出，可以实现超宽范围的恒功率输出，能够实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。并且所述第一开关网络和所述第四开关网络彼此串联，所述第二开关网络和所述第五开关网络彼此串联，所述第三开关网络和所述第六开关网络彼此串联，因此开关器件不需要并联就能够实现大功率的输出，没有开关器件并联导致的可靠性问题。因此，可以采用各种类型的开关器件，尤其是可以采用低成本的硅开关器件。
图14是本发明的超大功率宽范围恒功率变换器的第五优选实施例的电路图。如图14所示，所述超大功率宽范围恒功率变换器包括：第一开关网络110、第二开关网络120、第三开关网络130、第四开关网络140、第五开关网络150、第六开关网络160、第一谐振网络210、第二谐振网络220、第三谐振网络230、第四谐振网络240、第五谐振网络250、第六谐振网络260、第一变压器网络310、第二变压器网络320、第三变压器网络330、第四变压器网络340、第五变压器网络350、第六变压器网络360、第一整流网络410、第二整流网络420、开关模块500和高低压控制模块600。
在图14所示优选实施例中，所述第一开关网络110和第四开关网络140分别包括开关器件S1-S4构成的开关器件全桥拓扑，类似地，所述第二开关网络120和第五开关网络150分别包括开关器件S5-S8构成的开关器件全桥拓扑，所述第三开关网络130和第六开关网络160包括开关器件S9-S12构成的开关器件全桥拓扑。所述第一谐振网络210、第二谐振网络220、第三谐振网络230、第四谐振网络240、第五谐振网络250、第六谐振网络260分别包括电容Cm和电感Lr串联构成的LC串联谐振单元。所述第一变压器网络310、第二变压器网络320、第三变压器网络330、第四变压器网络340、第五变压器网络350、第六变压器网络360分别包括一个变压器，为了简化仅标注变压器Ta1-Tc1。第一整流网络410包括二极管D11-D16构成的二极管整流桥。同样地，第二整流网络420包括二极管D21-D26构成的二极管整流桥。
在本实施例中，本发明的超大功率宽范围恒功率变换器为上下两个组合式结构。因此，仅对其上部电路进一步说明如下。如图14所示，变压器Ta1的原边绕组的第一端经串联的电容Cm和电感Lr连接开关器件S1-S4构成的开关器件全桥拓扑的第一输出端、原边绕组的第二端连接开关器件S1-S4构成的开关器件全桥拓扑的第二输出端、副边绕组的第一端连接二极管D11-D16构成的二极管整流桥的第一输入端。类似地，变压器Tb1的原边绕组的第一端经串联的电容Cm和电感Lr连接开关器件S5-S8构成的开关器件全桥拓扑的第一输出端、原边绕组的第二端连接开关器件S5-S8构成的开关器件全桥拓扑的第二输出端、副边绕组的第一端连接二极管D11-D16构成的二极管整流桥的第二输入端，变压器Tc1的原边绕组的第一端经串联的电容Cm和电感Lr连接开关器件S9-S12构成的开关器件全桥拓扑的第一输出端、原边绕组的第二端连接开关器件S9-S12构成的开关器件全桥拓扑的第二输出端、副边绕组的第一端连接二极管D11-D16构成的二极管整流桥的第三输入端。
在本发明的优选实施例中，所述二极管D11-D16、开关器件S1-S12、K1-K3可以采用硅开关器件或者碳化硅开关器件。为了节省成本，优选采用硅开关器件。
在本优选实施例中，变压器的原边绕组分别独立连接每相桥式开关网络，副边绕组彼此连接，再通过全桥整流进行并联实现大功率输出。同时，通过高低压模式控制器对控制开关K1~K3的切换，实现超宽范围恒功率输出，能够实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。并且变压器原边绕组和副边绕组的开关器件（例如开关器件S1-S12，D1-D16以及K1-K3）。不需要并联，就实现大功率的输出，没有开关器件并联的可靠性问题。此外，通过控制开关器件的工作，实现三相交错工作，使得原边和副边母线电流纹波大大减小，从而减小原边和副边滤波器的体积。依靠上述电路的拓扑的连接控制，尤其可以采用低成本的硅开关器件，可以实现超宽范围的恒功率输出。
此外，图14所示的优选实施例的整流网络包括的整流桥数量较少，尤其适合超宽范围输出，但输出功率不要求那么大的情况。当然，针对输出功率要求更高时，可以适当整流桥和变压器的数量。
图12是本发明的超大功率宽范围恒功率变换器的第三优选实施例的原理框图。图12所示实施例与图11所示的实施例类似，其区别在于，所述第一变压器网络310、第二变压器网络320、第三变压器网络330、第四变压器网络340、第五变压器网络350、第六变压器网络360、第一整流网络410、第二整流网络420的设置。
在图12所示的优选实施例中，所述第一变压器网络310、所述第二变压器网络320、所述第三变压器网络330分别包括原边绕组串联的第一变压器Ta1、Tb1、Tc1和第二变压器Ta2、Tb2、Tc2。类似地，所述第四变压器网络340、所述第五变压器网络350、所述第六变压器网络360分别包括原边绕组串联的第三变压器Ta3、Tb3、Tc3和第四变压器Ta4、Tb4、Tc4。所述第一整流网络410包括第一整流单元411和第二整流单元412，所述第二整流网络420包括第三整流单元413和第四整流单元414。在此。第一整流单元411、第二整流单元412、第三整流单元413和第四整流单元414可以参照图5a-5b所示实施例构造。
在本实施例中，在本实施例中，本发明的超大功率宽范围恒功率变换器为上下两个组合式结构。如图12所示，所述第一变压器Ta1的原边绕组的第一端连接所述第一谐振网络210、原边绕组的第二端连接所述第二变压器Ta2的原边绕组的第一端、副边绕组的第一端连接所述第一整流单元411、副边绕组的第二端连接第一变压器Tb1和Tc1的副边绕组的第二端。所述第二变压器Ta2的原边绕组的第二端同样连接所述第一谐振网络210、副边绕组的第一端连接所述第二整流单元412、副边绕组的第二端连接第二变压器Tb2和Tc2的副边绕组的第二端。所述第一变压器Tb1的原边绕组的第一端连接所述第二谐振网络220、原边绕组的第二端连接所述第二变压器Tb2的原边绕组的第一端、副边绕组的第一端连接所述第一整流单元411。所述第二变压器Tb2的原边绕组的第二端同样连接所述第二谐振网络220、副边绕组的第一端连接所述第二整流单元412。所述第一变压器Tc1的原边绕组的第一端连接所述第三谐振网络230、原边绕组的第二端连接所述第二变压器Tc2的原边绕组的第一端、副边绕组的第一端连接所述第一整流单元411。所述第二变压器Tc2的原边绕组的第二端同样连接所述第三谐振网络230、副边绕组的第一端连接所述第二整流单元412。
类似地，所述第三变压器Ta3的原边绕组的第一端连接所述第四谐振网络240、原边绕组的第二端连接所述第四变压器Ta4的原边绕组的第一端、副边绕组的第一端连接所述第三整流单元413、副边绕组的第二端连接第三变压器Tb3和Tc3的副边绕组的第二端。所述第四变压器Ta4的原边绕组的第二端同样连接所述第四谐振网络240、副边绕组的第一端连接所述第四整流单元414、副边绕组的第二端连接第四变压器Tb4和Tc4的副边绕组的第二端。所述第三变压器Tb3的原边绕组的第一端连接所述第五谐振网络250、原边绕组的第二端连接所述第四变压器Tb4的原边绕组的第一端、副边绕组的第一端连接所述第三整流单元413。所述第四变压器Tb4的原边绕组的第二端同样连接所述第五谐振网络250、副边绕组的第一端连接所述第四整流单元414。所述第三变压器Tc3的原边绕组的第一端连接所述第六谐振网络260、原边绕组的第二端连接所述第四变压器Tc4的原边绕组的第一端、副边绕组的第一端连接所述第三整流单元413。所述第四变压器Tc4的原边绕组的第二端同样连接所述第六谐振网络260、副边绕组的第一端连接所述第四整流单元414。所述第一整流单元411和所述第二整流单元412并联，所述第三整流单元413和所述第四整流单元414并联。
所述高低压控制模块600控制所述开关模块500中的开关器件的切换可以使得所述第一整流单元411和所述第二整流单元412构成的所述第一整流网络410和所述第三整流单元413和所述第四整流单元414构成的第二整流网络420并联、串联或者单独进行电压输出。
在本发明的各个优选实施例中，可以采用本申请全文中任何位置所描述的任何适合的开关网络、谐振网络、变压器网络、整流单元进行组合，从而构建本发明的超大功率宽范围恒功率变换器。
在本发明中，变压器模块的各个原边绕组分别经谐振网络连接开关网络、副边绕组形成星形连接并经整流模块整流后产生两个输出电压，通过并联这两个输出电压可以实现超大功率输出，而同时通过高低压控制模块控制开关模块中的开关器件切换可以将两个输出电压串联、并联或者单独输出，可以实现超宽范围的恒功率输出，能够实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。并且所述第一开关网络和所述第四开关网络彼此串联，所述第二开关网络和所述第五开关网络彼此串联，所述第三开关网络和所述第六开关网络彼此串联，因此开关器件不需要并联就能够实现大功率的输出，没有开关器件并联导致的可靠性问题。因此，可以采用各种类型的开关器件，尤其是可以采用低成本的硅开关器件。
图15是本发明的超大功率宽范围恒功率变换器的第六优选实施例的电路图。图15所示实施例与图14所示的实施例类似，其区别在于，所述第一变压器网络310、第二变压器网络320、第三变压器网络330、第四变压器网络340、第五变压器网络350、第六变压器网络360、第一整流网络410、第二整流网络420的设置。图15所示的优选实施例包括更多数量的整流桥和变压器，更加适合超大功率输出的情况。
如图15所示，所述第一变压器网络310、所述第二变压器网络320、所述第三变压器网络330分别包括原边绕组串联的第一变压器Ta1、Tb1、Tc1和第二变压器Ta2、Tb2、Tc2。类似地，所述第四变压器网络340、所述第五变压器网络350、所述第六变压器网络360分别包括原边绕组串联的第三变压器Ta3、Tb3、Tc3和第四变压器Ta4、Tb4、Tc4。所述第一整流网络410包括第一整流单元411和第二整流单元412，所述第二整流网络420包括第三整流单元413和第四整流单元414。在此。第一整流单元411、第二整流单元412分别包括二极管D11-D16构成的一个二极管整流桥。第三整流单元413和第四整流单元414同样分别包括二极管D21-D26构成的一个二极管整流桥。在本优选实施例中，每个谐振网络包括两个LC串联谐振单元。
在本实施例中，本发明的超大功率宽范围恒功率变换器为上下两个组合式结构。因此，仅对其上部电路进一步说明如下，其下部电路连接关系类似参见图15。进一步如图15所示，所述第一变压器Ta1的原边绕组的第一端经串联的电容Cr和电感Lr连接开关器件S1-S4构成的开关器件全桥拓扑的第一输出端、原边绕组的第二端连接所述第二变压器Ta2的原边绕组的第一端、副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第一输入端、副边绕组的第二端连接第一变压器Tb1和Tc1的副边绕组的第二端。所述第二变压器Ta2的原边绕组的第二端同样经串联的电容Cr和电感Lr连接开关器件S1-S4构成的开关器件全桥拓扑的第二输出端、副边绕组的第一端连接所述二极管D11-D16构成的第二二极管整流桥的第一输入端、副边绕组的第二端连接第二变压器Tb2和Tc2的副边绕组的第二端。所述第一变压器Tb1的原边绕组的第一端经串联的电容Cm和电感Lr连接开关器件S5-S8构成的开关器件全桥拓扑的第一输出端、原边绕组的第二端连接所述第二变压器Tb2的原边绕组的第一端、副边绕组的第一端连接所述二极管D11-D16构成的第一二极管整流桥的第二输入端。所述第二变压器Tb2的原边绕组的第二端经串联的电容Cm和电感Lr连接开关器件S5-S8构成的开关器件全桥拓扑的第二输出端、副边绕组的第一端连接所述二极管D11-D16构成的第二二极管整流桥的第二输入端。所述第一变压器Tc1的原边绕组的第一端同样经串联的电容Cr和电感Lr连接开关器件S9-S12构成的开关器件全桥拓扑的第一输出端、原边绕组的第二端连接所述第二变压器Tc2的原边绕组的第一端、副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第三输入端。所述第二变压器Tc2的原边绕组的第二端同样连接经串联的电容Cr和电感Lr连接开关器件S9-S12构成的开关器件全桥拓扑的第二输出端、副边绕组的第一端连接所述二极管D11-D16构成的第二二极管整流桥的第三输入端。
在本发明的优选实施例中，所述二极管D11-D16、开关器件S1-S12、K1-K3可以采用硅开关器件或者碳化硅开关器件。为了节省成本，优选采用硅开关器件。
在本优选实施例中，变压器的原边绕组由两个组合式三相LLC谐振变换网络串联构成，变压器的原边绕组分别独立连接每相桥式开关网络，三相的变压器副边绕组连接成星星连接，再通过三相整流并联，实现大功率输出。同时，通过高低压模式控制器对控制开关K1~K3的切换，实现超宽范围恒功率输出，，能够实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。并且变压器原边绕组和副边绕组的开关器件（例如开关器件S1-S12，D1-D16以及K1-K3）。不需要并联，就实现大功率的输出，没有开关器件并联的可靠性问题。此外，通过控制开关器件的工作，实现三相交错工作，使得原边和副边母线电流纹波大大减小，从而减小原边和副边滤波器的体积。依靠上述电路的拓扑的连接控制，尤其可以采用低成本的硅开关器件，可以实现超宽范围的恒功率输出。
图13是本发明的超大功率宽范围恒功率变换器的第四优选实施例的原理框图。如图13所示，所述超大功率宽范围恒功率变换器包括：第一开关网络110、第二开关网络120、第三开关网络130、第四开关网络140、第五开关网络150、第六开关网络160、第一谐振网络210、第二谐振网络220、第三谐振网络230、第四谐振网络240、第五谐振网络250、第六谐振网络260、变压器模块300、整流模块400、开关模块500和高低压控制模块600。
如图13所示，所述变压器模块300包括第一变压器网络310、第二变压器网络320和第三变压器网络330，所述整流模块400包括第一整流网络410、第二整流网络420、第三整流网络430和第四整流网络440。
所述第一变压器网络310的原边绕组分别经所述第一谐振网络210和所述第二谐振网络220连接所述第一开关网络110和所述第二开关网络120，所述第二变压器网络320的原边绕组分别经所述第三谐振网络230和所述第四谐振网络240连接所述第三开关网络130和所述第四开关网络140，所述第三变压器网络330的原边绕组分别经所述第五谐振网络250和所述第六谐振网络260连接所述第五开关网络150和所述第六开关网络160。
第一变压器网络310的副边绕组分别连接所述第一整流网络410、所述第二整流网络420、所述第三整流网络430和所述第四整流网络440，第二变压器网络320的副边绕组分别连接所述第一整流网络410、所述第二整流网络420、所述第三整流网络430和所述第四整流网络440，第三变压器网络330的副边绕组分别连接所述第一整流网络410、所述第二整流网络420、所述第三整流网络430和所述第四整流网络440。所述第一变压器网络310、第二变压器网络320和第三变压器网络330的副边绕组彼此交错连接，例如可以是星星连接或者三角连接。所述第一整流网络410和所述第二整流网络420彼此并联，所述第三整流网络430和所述第四整流网络440彼此并联。
所述高低压控制模块600控制所述开关模块500中的开关器件的切换可以控制并联的所述第一整流网络410和所述第二整流网络420与并联的所述第三整流网络430和所述第四整流网络440进一步并联、串联或者单独进行电压输出。
在此，采用本申请全文中任何位置所描述的任何适合的开关网络、谐振网络、变压器网络、整流网络进行组合，从而构建本发明的超大功率宽范围恒功率变换器。在本优选实施例中，采用本发明的超大功率宽范围恒功率变换器的电路设计，可以采用高压碳化硅开关器件，这样可以减少在开关器件的数量的同时同样达到超大功率宽范围恒功率的输出。
图16是本发明的超大功率宽范围恒功率变换器的第七优选实施例的电路图。如图16所示，所述超大功率宽范围恒功率变换器包括：第一开关网络110、第二开关网络120、第三开关网络130、第四开关网络140、第五开关网络150、第六开关网络160、第一谐振网络210、第二谐振网络220、第三谐振网络230、第四谐振网络240、第五谐振网络250、第六谐振网络260、变压器模块300、整流模块400、开关模块500和高低压控制模块600。所述变压器模块300包括第一变压器网络310、第二变压器网络320和第三变压器网络330，所述整流模块400包括第一整流网络410、第二整流网络420、第三整流网络430和第四整流网络440。所述第一变压器网络310、所述第二变压器网络320和所述第三变压器网络330分别包括原边串联的第一变压器T11-T31、第二变压器T12-T32、第三变压器T13-T33和第四变压器T14-T34。
所述第一变压器T11的原边绕组的第一端经串联的电容Cr和电感Lr连接开关器件S1-S2构成的开关器件半桥拓扑的输出端、原边绕组的第二端连接所述第二变压器T12的原边绕组的第一端，所述第二变压器T12的原边绕组的第二端连接所述第三变压器T13的原边绕组的第一端，所述第三变压器T13的原边绕组的第二端连接所述第四变压器T14的原边绕组的第一端，所述第四变压器T14的原边绕组的第二端经串联的电容Cr和电感Lr连接开关器件S3-S4构成的开关器件半桥拓扑的输出端，所述第一变压器T11的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第一输入端、副边绕组的第二端连接第一变压器T21和T31的副边绕组的第二端。所述第二变压器T12的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第一输入端、副边绕组的第二端连接第二变压器T22和T32的副边绕组的第二端。所述第三变压器T13的副边绕组的第一端连接二极管D11-D16构成的第三二极管整流桥的第一输入端、副边绕组的第二端连接第三变压器T23和T33的副边绕组的第二端。所述第四变压器T14的副边绕组的第一端连接二极管D11-D16构成的第四二极管整流桥的第一输入端、副边绕组的第二端连接第四变压器T24和T34的副边绕组的第二端。
类似地，所述第一变压器T21的原边绕组的第一端经串联的电容Cr和电感Lr连接开关器件S5-S6构成的开关器件半桥拓扑的输出端、原边绕组的第二端连接所述第二变压器T22的原边绕组的第一端，所述第二变压器T22的原边绕组的第二端连接所述第三变压器T23的原边绕组的第一端，所述第三变压器T23的原边绕组的第二端连接所述第四变压器T24的原边绕组的第一端，所述第四变压器T24的原边绕组的第二端经串联的电容Cr和电感Lr连接开关器件S7-S8构成的开关器件半桥拓扑的输出端，所述第一变压器T21的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第二输入端。所述第二变压器T22的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第二输入端。所述第三变压器T23的副边绕组的第一端连接二极管D11-D16构成的第三二极管整流桥的第二输入端。所述第四变压器T24的副边绕组的第一端连接二极管D11-D16构成的第四二极管整流桥的第二输入端。
类似地，所述第一变压器T31的原边绕组的第一端经串联的电容Cr和电感Lr连接开关器件S9-S10构成的开关器件半桥拓扑的输出端、原边绕组的第二端连接所述第二变压器T32的原边绕组的第一端，所述第二变压器T32的原边绕组的第二端连接所述第三变压器T33的原边绕组的第一端，所述第三变压器T33的原边绕组的第二端连接所述第四变压器T34的原边绕组的第一端，所述第四变压器T34的原边绕组的第二端经串联的电容Cr和电感Lr连接开关器件S11-S12构成的开关器件半桥拓扑的输出端，所述第一变压器T31的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第三输入端。所述第二变压器T32的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第三输入端。所述第三变压器T33的副边绕组的第一端连接二极管D11-D16构成的第三二极管整流桥的第三输入端。所述第四变压器T34的副边绕组的第一端连接二极管D11-D16构成的第四二极管整流桥的第三输入端。在本优选实施例中，所述二极管D11-D16、开关器件S1-S12、K1-K3可以采用碳化硅开关器件。
图17是本发明的超大功率宽范围恒功率变换器的第七优选实施例的电路图。图17所示实施例与图16所示的实施例类似，其区别在于，第一开关网络110、第二开关网络120、第三开关网络130、第四开关网络140、第五开关网络150、第六开关网络160的设置。在图17所示的优选实施例中，第一开关网络110、第二开关网络120、第三开关网络130、第四开关网络140、第五开关网络150、第六开关网络160分别采用三电平开关器件全桥拓扑。
所述第一变压器T11的原边绕组的第一端经串联的电容Cr和电感Lr连接开关器件S11-S14和D11-D12构成的第一三电平开关器件全桥拓扑的输出端、原边绕组的第二端连接所述第二变压器T12的原边绕组的第一端，所述第二变压器T12的原边绕组的第二端连接所述第三变压器T13的原边绕组的第一端，所述第三变压器T13的原边绕组的第二端连接所述第四变压器T14的原边绕组的第一端，所述第四变压器T14的原边绕组的第二端经串联的电容Cr和电感Lr连接开关器件S21-S24和D21-D22构成的第二三电平开关器件全桥拓扑的输出端，所述第一变压器T11的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第一输入端、副边绕组的第二端连接第一变压器T21和T31的副边绕组的第二端。所述第二变压器T12的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第一输入端、副边绕组的第二端连接第二变压器T22和T32的副边绕组的第二端。所述第三变压器T13的副边绕组的第一端连接二极管D11-D16构成的第三二极管整流桥的第一输入端、副边绕组的第二端连接第三变压器T23和T33的副边绕组的第二端。所述第四变压器T14的副边绕组的第一端连接二极管D11-D16构成的第四二极管整流桥的第一输入端、副边绕组的第二端连接第四变压器T24和T34的副边绕组的第二端。
类似地，所述第一变压器T21的原边绕组的第一端经串联的电容Cr和电感Lr连接第三三电平开关器件全桥拓扑的输出端、原边绕组的第二端连接所述第二变压器T22的原边绕组的第一端，所述第二变压器T22的原边绕组的第二端连接所述第三变压器T23的原边绕组的第一端，所述第三变压器T23的原边绕组的第二端连接所述第四变压器T24的原边绕组的第一端，所述第四变压器T24的原边绕组的第二端经串联的电容Cr和电感Lr连接第四三电平开关器件全桥拓扑的输出端，所述第一变压器T21的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第二输入端。所述第二变压器T22的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第二输入端。所述第三变压器T23的副边绕组的第一端连接二极管D11-D16构成的第三二极管整流桥的第二输入端。所述第四变压器T24的副边绕组的第一端连接二极管D11-D16构成的第四二极管整流桥的第二输入端。
类似地，所述第一变压器T31的原边绕组的第一端经串联的电容Cr和电感Lr连接第五三电平开关器件全桥拓扑的输出端、原边绕组的第二端连接所述第二变压器T32的原边绕组的第一端，所述第二变压器T32的原边绕组的第二端连接所述第三变压器T33的原边绕组的第一端，所述第三变压器T33的原边绕组的第二端连接所述第四变压器T34的原边绕组的第一端，所述第四变压器T34的原边绕组的第二端经串联的电容Cr和电感Lr连接第六三电平开关器件全桥拓扑的输出端，所述第一变压器T31的副边绕组的第一端连接二极管D11-D16构成的第一二极管整流桥的第三输入端。所述第二变压器T32的副边绕组的第一端连接二极管D11-D16构成的第二二极管整流桥的第三输入端。所述第三变压器T33的副边绕组的第一端连接二极管D11-D16构成的第三二极管整流桥的第三输入端。所述第四变压器T34的副边绕组的第一端连接二极管D11-D16构成的第四二极管整流桥的第三输入端。在本优选实施例中，所述二极管D11-D16、开关器件K1-K3可以采用碳化硅开关器件，而开关器件S21-S24和D21-D22可以采用硅开关器件。
在本发明中，变压器模块的各个原边绕组分别经谐振网络连接开关网络、副边绕组形成星形连接并经整流模块整流后产生两个输出电压，通过并联这两个输出电压可以实现超大功率输出，而同时通过高低压控制模块控制开关模块中的开关器件切换可以将两个输出电压串联、并联或者单独输出，可以实现超宽范围的恒功率输出，能够实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。并且所述第一开关网络和所述第四开关网络彼此串联，所述第二开关网络和所述第五开关网络彼此串联，所述第三开关网络和所述第六开关网络彼此串联，因此开关器件不需要并联就能够实现大功率的输出，没有开关器件并联导致的可靠性问题。因此，可以采用各种类型的开关器件，尤其是可以采用低成本的硅开关器件。
在本优选实施例中，采用本发明的超大功率宽范围恒功率变换器的电路设计，可以采用高压碳化硅开关器件，这样可以减少在开关器件的数量的同时同样达到超大功率宽范围恒功率的输出。
虽然本发明是通过具体实施例进行说明的，本领域技术人员应当明白，在不脱离本发明范围的情况下，还可以对本发明进行各种变换及等同替代。另外，针对特定情形或材料，可以对本发明做各种修改，而不脱离本发明的范围。因此，本发明不局限于所公开的具体实施例，而应当包括落入本发明权利要求范围内的全部实施方式。
以上所述仅为本发明的较佳实施例而已，并不用以限制本发明，凡在本发明的精神和原则之内所作的任何修改、等同替换和改进等，均应包含在本发明的保护范围之内。

Claims (15)

  1. 一种交错式功率变换器，其特征在于，包括：第一开关网络、第二开关网络、第三开关网络、第一谐振网络、第二谐振网络、第三谐振网络、变压器模块和整流模块；
    所述第一开关网络、所述第二开关网络和所述第三开关网络的第一输入端彼此连接并接收输入电压，所述第一开关网络、所述第二开关网络和所述第三开关网络的第二输入端同样彼此连接，所述第一开关网络的输出端经所述第一谐振网络、所述第二开关网络的输出端经所述第二谐振网络、所述第三开关网络的输出端经所述第三谐振网络分别连接所述变压器模块的各个原边绕组；所述变压器模块的各个副边绕组的第一端彼此连接、第二端连接所述整流模块；
    所述第一谐振网络、所述第二谐振网络和所述第三谐振网络交错运行，所述整流模块输出输出电压。
  2. 根据权利要求1所述的交错式功率变换器，其特征在于，所述第一开关网络、所述第二开关网络和所述第三开关网络分别包括开关器件全桥拓扑电路、开关器件对称半桥拓扑电路或开关器件不对称半桥拓扑电路。
  3. 根据权利要求1所述的交错式功率变换器，其特征在于，所述第一谐振网络、所述第二谐振网络和所述第三谐振网络分别包括LC谐振单元、LLC串联谐振单元、SRC串联谐振单元、PRC并联谐振单元和LCC串并联谐振单元。
  4. 根据权利要求1所述的交错式功率变换器，其特征在于，所述第一谐振网络、所述第二谐振网络和所述第三谐振网络彼此120度交错运行。
  5. 根据权利要求1所述的交错式功率变换器，其特征在于，所述变压器模块包括第一变压器网络、第二变压器网络和第三变压器网络；所述整流模块包括至少一个开关器件整流桥。
  6. 根据权利要求5所述的交错式功率变换器，其特征在于，所述第一变压器网络、第二变压器网络和第三变压器网络分别包括第一变压器，所述第一变压器的原边绕组分别连接所述第一谐振网络、所述第二谐振网络或所述第三谐振网络、副边绕组的第一端均连接所述整流模块、副边绕组的第二端彼此连接。
  7. 根据权利要求5所述的交错式功率变换器，其特征在于，所述第一变压器网络、所述第二变压器网络、所述第三变压器网络分别包括原边绕组串联的第一变压器和第二变压器，所述整流模块包括第一整流网络和第二整流网络；所述第一变压器的原边绕组的第一端分别连接所述第一谐振网络、所述第二谐振网络或所述第三谐振网络、原边绕组的第二端连接所述第二变压器的原边绕组的第一端，所述第二变压器的原边绕组的第二端同样分别连接所述第一谐振网络、所述第二谐振网络或所述第三谐振网络，所述第一变压器的副边绕组的第一端分别连接所述第一整流网络、副边绕组的第二端彼此连接，所述第二变压器的副边绕组的第一端分别连接所述第二整流网络、副边绕组的第二端彼此连接；所述第一整流网络和所述第二整流网络分别包括至少一个开关器件整流桥；所述第一整流网络和所述第二整流网络并联以输出所述输出电压。
  8. 一种超大功率宽范围恒功率变换器，其特征在于，包括：第一开关网络、第二开关网络、第三开关网络、第四开关网络、第五开关网络、第六开关网络、第一谐振网络、第二谐振网络、第三谐振网络、第四谐振网络、第五谐振网络、第六谐振网络、变压器模块、整流模块、开关模块和高低压控制模块；
    所述第一开关网络、所述第二开关网络和所述第三开关网络的第一输入端彼此连接并接收第一输入电压，所述第四变压器网络、所述第五变压器网络和第六变压器网络的第一输入端彼此并联以接收第二输入电压，所述第一开关网络的第二输入端串联所述第四开关网络的第二输入端，所述第二开关网络的第二输入端串联所述第五开关网络的第二输入端，所述第三开关网络的第二输入端串联所述第六开关网络的第二输入端；
    所述第一开关网络的输出端经所述第一谐振网络、所述第二开关网络的输出端经所述第二谐振网络、所述第三开关网络的输出端经所述第三谐振网络、所述第四开关网络的输出端经所述第四谐振网络、所述第五开关网络的输出端经所述第五谐振网络、所述第六开关网络的输出端经所述第六谐振网络分别连接所述变压器模块的各个原边绕组；所述变压器模块的各个副边绕组的一端彼此连接、另一端连接所述整流模块；所述第一谐振网络、所述第二谐振网络和所述第三谐振网络交错运行，所述第四变压器网络、所述第五变压器网络和第六变压器网络交错运行；
    所述整流模块分别输出第一输出电压和第二输出电压到所述开关模块，所述高低压控制模块控制所述开关模块中的开关器件切换以实现所述超大功率宽范围恒功率变换器的超大功率和超宽范围的恒功率输出。
  9. 根据权利要求8所述的超大功率宽范围恒功率变换器，其特征在于，所述变压器模块包括第一变压器网络、第二变压器网络、第三变压器网络、第四变压器网络、第五变压器网络、第六变压器网络，所述整流模块包括第一整流网络和第二整流网络；
    所述第一变压器网络的原边绕组连接所述第一谐振网络、副边绕组的第一端连接所述第一整流网络，所述第二变压器网络的原边绕组连接所述第二谐振网络、副边绕组的第一端连接所述第一整流网络，所述第三变压器网络的原边绕组连接所述第三谐振网络、副边绕组的第一端连接所述第一整流网络，所述第四变压器网络的原边绕组连接所述第四谐振网络、副边绕组的第一端连接所述第二整流网络，所述第五变压器网络的原边绕组连接所述第二谐振网络、副边绕组的第一端连接所述第二整流网络，所述第六变压器网络的原边绕组连接所述第六谐振网络、副边绕组的第一端连接所述第二整流网络；所述第一变压器网络、所述第二变压器网络、所述第三变压器网络的副边绕组的第二端彼此连接；所述第四变压器网络、所述第五变压器网络、所述第六变压器网络的副边绕组的第二端彼此连接。
  10. 根据权利要求9所述的超大功率宽范围恒功率变换器，其特征在于，所述第一变压器网络、所述第二变压器网络、所述第三变压器网络分别包括第一变压器，所述第一变压器的原边绕组分别连接所述第一谐振网络、所述第二谐振网络或所述第三谐振网络、副边绕组的第一端均连接所述第一整流网络、副边绕组的第二端彼此连接；
    所述第四变压器网络、所述第五变压器网络、所述第六变压器网络分别包括第二变压器，所述第二变压器的原边绕组分别连接所述第四谐振网络、所述第五谐振网络或所述第六谐振网络、副边绕组的第一端均连接所述第二整流网络、副边绕组的第二端彼此连接。
  11. 根据权利要求9所述的超大功率宽范围恒功率变换器，其特征在于，所述第一变压器网络、所述第二变压器网络、所述第三变压器网络分别包括原边绕组串联的第一变压器和第二变压器，所述第四变压器网络、所述第五变压器网络、所述第六变压器网络分别包括原边绕组串联的第三变压器和第四变压器，所述第一整流网络包括第一整流单元和第二整流单元，所述第二整流网络包括第三整流单元和第四整流单元；
    所述第一变压器的原边绕组的第一端分别连接所述第一谐振网络、所述第二谐振网络或所述第三谐振网络、原边绕组的第二端连接所述第二变压器的原边绕组的第一端，所述第二变压器的原边绕组的第二端同样分别连接所述第一谐振网络、所述第二谐振网络或所述第三谐振网络，所述第一变压器的副边绕组的第一端分别连接所述第一整流单元、副边绕组的第二端彼此连接，所述第二变压器的副边绕组的第一端分别连接所述第二整流单元、副边绕组的第二端彼此连接；
    所述第三变压器的原边绕组的第一端分别连接所述第四谐振网络、所述第五谐振网络或所述第六谐振网络、原边绕组的第二端连接所述第四变压器的原边绕组的第一端，所述第四变压器的原边绕组的第二端同样分别连接所述第四谐振网络、所述第五谐振网络或所述第六谐振网络，所述第三变压器的副边绕组的第一端分别连接所述第三整流单元、副边绕组的第二端彼此连接，所述第四变压器的副边绕组的第一端分别连接所述第四整流单元、副边绕组的第二端彼此连接；
    所述第一整流单元和所述第二整流单元并联，所述第三整流单元和所述第四整流单元并联。
  12. 根据权利要求11所述的超大功率宽范围恒功率变换器，其特征在于，所述第一开关网络、所述第二开关网络、所述第三开关网络、所述第四开关网络、所述第五开关网络、所述第六开关网络分别包括开关器件全桥拓扑电路、开关器件对称半桥拓扑电路或开关器件不对称半桥拓扑电路；所述第一整流单元、所述第二整流单元、所述第三整流单元和所述第四整流单元分别包括开关器件整流桥。
  13. 根据权利要求8所述的超大功率宽范围恒功率变换器，其特征在于，所述变压器模块包括第一变压器网络、第二变压器网络和第三变压器网络，所述整流模块包括第一整流网络、第二整流网络、第三整流网络和第四整流网络；
    所述第一变压器网络的原边绕组分别经所述第一谐振网络和所述第二谐振网络连接所述第一开关网络和所述第二开关网络，所述第二变压器网络的原边绕组分别经所述第三谐振网络和所述第四谐振网络连接所述第三开关网络和所述第四开关网络，所述第三变压器网络的原边绕组分别经所述第五谐振网络和所述第六谐振网络连接所述第五开关网络和所述第六开关网络；
    所述第一变压器网络的副边绕组的第一端分别连接所述第一整流网络、所述第二整流网络、所述第三整流网络和所述第四整流网络，第二变压器网络的副边绕组的第一端分别连接所述第一整流网络、所述第二整流网络、所述第三整流网络和所述第四整流网络，第三变压器网络的副边绕组的第一端分别连接所述第一整流网络、所述第二整流网络、所述第三整流网络和所述第四整流网络；所述第一变压器网络的副边绕组的第二端、所述第二变压器网络的副边绕组的第二端和所述第三变压器网络的副边绕组的第二端彼此连接。
  14. 根据权利要求13所述的超大功率宽范围恒功率变换器，其特征在于，所述第一变压器网络、所述第二变压器网络和所述第三变压器网络分别包括原边串联的第一变压器、第二变压器、第三变压器和第四变压器，所述第一变压器的原边绕组的第一端经所述第一谐振网络连接所述第一开关网络、经所述第二谐振网络连接所述第二开关网络并经所述第三谐振网络连接所述第三开关网络；所述第一变压器的原边绕组的第二端连接所述第二变压器的原边绕组的第一端，所述第二变压器的原边绕组的第二端连接所述第三变压器的原边绕组的第一端，所述第三变压器的原边绕组的第二端连接所述第四变压器的原边绕组的第一端，所述第四变压器的原边绕组的第二端经所述第四谐振网络连接所述第四开关网络、经所述第五谐振网络连接所述第五开关网络并经所述第六谐振网络连接所述第六开关网络；
    所述第一变压器的副边绕组的第一端分别连接所述第一整流网络、所述第一变压器的副边绕组的第二端彼此连接，所述第二变压器的副边绕组的第一端分别连接所述第二整流网络、所述第二变压器的副边绕组的第二端彼此连接，所述第三变压器的副边绕组的第一端分别连接所述第三整流网络、所述第三变压器的副边绕组的第二端彼此连接，所述第四变压器的副边绕组的第一端分别连接所述第四整流网络、所述第四变压器的副边绕组的第二端彼此连接；
    所述第一整流网络和所述第二整流网络彼此并联，所述第三整流网络和所述第四整流网络彼此并联。
  15. 根据权利要求13所述的超大功率宽范围恒功率变换器，其特征在于，所述第一开关网络、所述第二开关网络、所述第三开关网络、所述第四开关网络、所述第五开关网络、所述第六开关网络分别包括至少两个并联的开关器件；所述第一整流网络、所述第二整流网络、所述第三整流网络和所述第四整流网络分别包括开关器件整流桥，所述开关器件包括碳化硅开关器件；所述第一谐振网络、所述第二谐振网络、所述第三谐振网络、所述第四谐振网络、所述第五谐振网络和所述第六谐振网络分别包括LC谐振单元、LLC串联谐振单元、SRC串联谐振单元、PRC并联谐振单元和LCC串并联谐振单元。
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