WO2022133793A1 - 一种充电系统和汽车 - Google Patents

一种充电系统和汽车 Download PDF

Info

Publication number
WO2022133793A1
WO2022133793A1 PCT/CN2020/138586 CN2020138586W WO2022133793A1 WO 2022133793 A1 WO2022133793 A1 WO 2022133793A1 CN 2020138586 W CN2020138586 W CN 2020138586W WO 2022133793 A1 WO2022133793 A1 WO 2022133793A1
Authority
WO
WIPO (PCT)
Prior art keywords
switch tube
bridge circuit
switch
duration
side bridge
Prior art date
Application number
PCT/CN2020/138586
Other languages
English (en)
French (fr)
Inventor
杨帅
赵德琦
吴壬华
Original Assignee
深圳欣锐科技股份有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 深圳欣锐科技股份有限公司 filed Critical 深圳欣锐科技股份有限公司
Priority to EP20966372.3A priority Critical patent/EP4239827A4/en
Priority to CN202080008185.4A priority patent/CN113330672B/zh
Priority to PCT/CN2020/138586 priority patent/WO2022133793A1/zh
Publication of WO2022133793A1 publication Critical patent/WO2022133793A1/zh
Priority to US18/327,111 priority patent/US20230307928A1/en

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584—Bidirectional converters
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/10—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by the energy transfer between the charging station and the vehicle
    • B60L53/12—Inductive energy transfer
    • B60L53/122—Circuits or methods for driving the primary coil, e.g. supplying electric power to the coil
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/60—Monitoring or controlling charging stations
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/0029—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries with safety or protection devices or circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/0068—Battery or charger load switching, e.g. concurrent charging and load supply
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/02—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries for charging batteries from ac mains by converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33561—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having more than one ouput with independent control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33571—Half-bridge at primary side of an isolation transformer
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L2210/00—Converter types
    • B60L2210/10—DC to DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2310/00—The network for supplying or distributing electric power characterised by its spatial reach or by the load
    • H02J2310/40—The network being an on-board power network, i.e. within a vehicle
    • H02J2310/48—The network being an on-board power network, i.e. within a vehicle for electric vehicles [EV] or hybrid vehicles [HEV]
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/80—Technologies aiming to reduce greenhouse gasses emissions common to all road transportation technologies
    • Y02T10/92—Energy efficient charging or discharging systems for batteries, ultracapacitors, supercapacitors or double-layer capacitors specially adapted for vehicles

Definitions

  • the present application relates to the field of electrical technology, and in particular, to a charging system and an automobile.
  • the power source of new energy vehicles is mainly the power battery.
  • the power battery In order to maintain the battery life, the power battery needs to be regularly charged through the charging system.
  • the charging system includes a primary side circuit and two secondary side circuits.
  • the charging system with bidirectional charging function has multiple working modes, one of which is the direct current to direct current (DC-DC) mode, that is, the power of the DC power supply connected to one of the secondary circuits, from One of the secondary circuits passes to the other secondary circuit, and finally supplies the DC operating equipment connected to the other secondary circuit.
  • DC-DC direct current to direct current
  • the closed-loop control only involves two secondary circuits. At this time, the primary circuit is unloaded and no closed-loop control is formed.
  • the power supplied by a secondary circuit will also be transferred to the primary circuit through the transformer. Then, since the closed-loop control does not involve the primary circuit, devices such as switches and capacitors in the primary circuit will be damaged by the transmitted power or high voltage.
  • the purpose of this application is to provide a charging system and a vehicle, which solve the problem of damage to devices such as switching tubes and high-voltage electrolytic capacitors in the primary circuit.
  • a first aspect of the present application provides a charging system, including: a primary side bridge circuit, a transformer, a first secondary side bridge circuit and a second secondary side bridge circuit; the primary side bridge circuit is connected to the primary winding of the transformer, and the first Both a secondary side bridge circuit and the second secondary side bridge circuit are connected to the secondary windings of the transformer; when power is transferred from the first secondary side bridge circuit to the second secondary side bridge circuit, the primary side bridge circuit After the switch tube of the circuit is turned on for the duration Td, the switch tube of the first secondary-side bridge circuit starts to be turned on.
  • symmetric pulse width modulation PWM is used to control the primary side bridge circuit
  • asymmetric PWM is used to control the first secondary side bridge circuit
  • the first secondary-side bridge circuit includes a first half-bridge circuit and a second half-bridge circuit connected in parallel; the first half-bridge circuit includes a first switch tube and a second switch tube, and the second half-bridge circuit includes a third half-bridge circuit.
  • the switch tube and the fourth switch tube; the first switch tube and the fourth switch tube are diagonally distributed, and the second switch tube and the third switch tube are diagonally distributed;
  • asymmetric PWM is used to control the first secondary side bridge circuit Including: when the first switch tube and the fourth switch tube are used to form a loop, the first switch tube and the fourth switch tube start to conduct at the same time, and the conduction duration T1 of the first switch tube is greater than the conduction duration of the fourth switch tube.
  • T2 in the case of using the second switch tube and the fourth switch tube to form a loop, the second switch tube and the third switch tube start to conduct at the same time, and the conduction time T1 of the third switch tube is greater than the conduction time of the second switch tube.
  • the use of asymmetric PWM to control the first secondary-side bridge circuit further includes: when the fourth switch tube is turned off for a duration of T12, and the first switch tube is turned on for a duration of T12, the second switch tube and the third switch tube are turned on.
  • using asymmetric PWM to control the first secondary-side bridge circuit further includes: after the first switch tube is turned off for a length of time TD, the second switch tube and the third switch tube start to conduct at the same time; After the expiration time TD, enter the next working cycle.
  • the conduction duration T2 of the second switch transistor and the fourth switch transistor is adjustable; and when the conduction duration T2 increases, the output voltage range of the first secondary-side bridge circuit increases.
  • the range of the on-time Td of the switching tube of the primary-side bridge circuit is: 300 nanoseconds ⁇ Td ⁇ 500 nanoseconds.
  • the primary-side bridge circuit includes a third half-bridge circuit and a fourth half-bridge circuit in parallel;
  • the third half-bridge circuit includes a fifth switch tube and a sixth switch tube, and the fourth half-bridge circuit includes a seventh switch tube and the eighth switch tube;
  • the fifth switch tube and the eighth switch tube are diagonally distributed, and the sixth switch tube and the seventh switch tube are diagonally distributed;
  • using symmetrical PWM to control the primary side bridge circuit includes: using the fifth switch tube When the switch tube and the eighth switch tube form a loop, the conduction duration T4 of the fifth switch tube is equal to the conduction duration T4 of the eighth switch tube; in the case of using the sixth switch tube and the seventh switch tube to form a loop, the first The conduction period T3 of the seven switches is equal to the conduction period T3 of the sixth switch.
  • the sixth switch tube and the seventh switch tube are turned on synchronously for a duration T3 and then turned off; after the sixth switch tube and the seventh switch tube are turned off for a duration T0, the fifth switch tube and the eighth switch tube are turned off.
  • the transistors are turned on synchronously for a duration of T4, and the fifth switch tube and the eighth switch tube are turned off for a duration of T0, and then enter the next working cycle TS.
  • a second aspect of the present application provides an automobile, including the charging system of any one of the first aspect of the present application.
  • the switch tube of the primary side circuit is set to be turned on ahead of the switch tube of the secondary side circuit, so as to reduce the power transmitted to the primary side circuit in the DC-DC working mode, and avoid the switching tube and high-voltage electrolysis of the primary side circuit. Damage to capacitors and other devices.
  • FIG. 1 is a circuit diagram of a charging system provided by an embodiment of the present application.
  • FIG. 2 is a sequence diagram of a charging system provided by an embodiment of the present application.
  • FIG. 3 is a current and voltage timing diagram of a first secondary side bridge circuit provided by an embodiment of the present application.
  • FIG. 4 is a current and voltage timing diagram of a primary-side bridge circuit provided by an embodiment of the present application.
  • FIG. 5 is a schematic diagram of a current flow of a charging system provided by an embodiment of the present application.
  • FIG. 6 is a schematic diagram of a current flow of a charging system provided by an embodiment of the present application.
  • FIG. 7 is a schematic diagram of a current flow of a charging system provided by an embodiment of the present application.
  • FIG. 8 is a schematic diagram of a current flow of a charging system provided by an embodiment of the present application.
  • the circuit of the charging system includes a primary side bridge circuit, a transformer, a first secondary side bridge circuit and a second secondary side bridge circuit .
  • the primary bridge circuit is connected to the primary winding of the transformer, and the first secondary bridge circuit and the second secondary bridge circuit are both connected to the secondary winding of the transformer.
  • the secondary winding includes a first secondary winding and a second secondary winding, wherein the second secondary bridge circuit is connected with the first secondary winding, and the second secondary bridge circuit is connected with the second secondary winding.
  • the first secondary-side bridge circuit includes a first half-bridge circuit and a second half-bridge circuit connected in parallel; the first half-bridge circuit includes a first switch transistor Q1 and a second switch transistor Q2, and the second half-bridge circuit includes a first half-bridge circuit.
  • the three switch tubes Q3 and the fourth switch tube Q4; the first switch tube Q1 and the fourth switch tube Q4 are arranged diagonally, and the second switch tube Q2 and the third switch tube Q3 are arranged diagonally.
  • the first secondary bridge circuit also includes a first capacitor C1 and a second capacitor C2, the first capacitor C1 is connected in parallel with the second half-bridge circuit, one end of the second capacitor C2 is connected to one end of the first secondary winding, and the other end is connected to between the third switch tube Q3 and the fourth switch tube Q4; the other end of the first secondary winding is connected between the first switch tube Q1 and the second switch tube Q2.
  • the primary-side bridge circuit includes a third half-bridge circuit and a fourth half-bridge circuit in parallel; the third half-bridge circuit includes a fifth switch Q5 and a sixth switch Q6, and the fourth half-bridge circuit includes a seventh switch Q7 and The eighth switch tube Q8; the fifth switch tube Q5 and the eighth switch tube Q8 are arranged diagonally, and the sixth switch tube Q6 and the seventh switch tube Q7 are arranged diagonally.
  • the primary-side bridge circuit further includes a third capacitor C3, a fourth capacitor C4 and a first inductor L1.
  • the third capacitor C3 is connected in parallel with the third half-bridge circuit; one end of the first inductor L1 is connected between the seventh switch Q7 and the eighth switch Q8, and the other end of the first inductor L1 is connected to one end of the primary winding; One end of the fourth capacitor C4 is connected between the fifth switch transistor Q5 and the eighth switch transistor Q8, and the other end of the fourth capacitor C4 is connected to the other end of the primary winding.
  • the second secondary-side bridge circuit includes a ninth switch Q9, a tenth switch Q10, a first diode D1, a second diode D2, a third inductor L3, a fifth capacitor C5 and a resistor R.
  • One end of the first diode D1 is connected to one end of the second secondary winding, the other end of the first diode D1 is connected to one end of the ninth switch Q9; one end of the second diode D2 is connected to the second The other end of the secondary winding is connected, and the other end of the second diode D2 is also connected to one end of the ninth switch tube Q9; the other end of the ninth switch tube Q9 is respectively connected to one end of the third inductor L3 and the tenth switch tube Q10
  • the other end of the third inductor L3 is connected to one end of the fifth capacitor C5 and one end of the resistor R respectively; the other end of the tenth switch Q10, the other end of the fifth capacitor C5 and the other end of the
  • the second inductance L2 shown in the figure is the leakage inductance of the transformer.
  • the leakage inductance of the transformer does not actually have a physical entity, and the second inductance L2 in the figure is only for illustration.
  • the circuit of the charging system has five operating modes:
  • the first type the power is inverted from the primary side bridge circuit into an AC square wave, and then transferred to the first secondary side bridge circuit through the transformer to charge the power battery of the car.
  • the second type The power is inverted from the primary side bridge circuit to an AC square wave, and then transferred to the first secondary side bridge circuit through the transformer to charge the power battery of the car. At the same time, it is also transmitted to the second secondary side bridge circuit through the transformer, and is regulated by the step-down circuit to charge the battery of the car.
  • the third type the power is inverted from the first secondary side bridge circuit to an AC square wave, and then transferred to the primary side bridge circuit through the transformer, and the electric energy of the power battery is supplied to the external load of the outside car.
  • the fourth type The power is inverted from the first secondary side bridge circuit to an AC square wave, and then transferred to the primary side bridge circuit through the transformer to provide the electric energy of the power battery to the external load of the external vehicle. At the same time, it is also transmitted to the second secondary side bridge circuit through the transformer, and is regulated by the step-down circuit to charge the battery of the car.
  • the fifth type the power is inverted from the first secondary side bridge circuit into an AC square wave, and then transferred to the second secondary side bridge circuit through the transformer, and then regulated by the step-down circuit to charge the battery of the car.
  • the fifth operating mode described above is also referred to as a direct current to direct current (DC-DC) mode.
  • DC-DC direct current to direct current
  • the power battery is connected to both ends of the first secondary side bridge circuit as the input power supply, and at this time, the diagonally distributed switch tubes of the first secondary side bridge circuit are controlled to be turned on at the same time. , so that the first secondary-side bridge circuit can be controlled to output a square wave voltage.
  • the square wave voltage will be transmitted to the secondary winding of the transformer connected to the first secondary bridge circuit.
  • the transformer will be connected to the primary bridge circuit and the second secondary bridge circuit. A proportional voltage is output on the primary and secondary windings, and the output voltages of the different windings are constrained by the turns ratio of the transformer's windings.
  • the square wave voltage output by the first secondary-side bridge circuit is not only transmitted to the second secondary-side bridge circuit, but also transmitted to the primary-side bridge circuit.
  • the voltage transmitted to the primary bridge circuit is rectified by the body diode of the primary bridge circuit, and then filtered by the third capacitor C3, which will form a stable high-voltage direct current across the third capacitor C3 of the primary bridge circuit.
  • the high voltage direct current may damage the third capacitor C3.
  • the primary bridge circuit is also connected with a capacitor-inductance LC resonant circuit in series, when the primary bridge circuit is completely unloaded, the voltage applied to the third capacitor C3 under the action of the resonant circuit will exceed the voltage of the primary winding of the transformer. Voltage. At this time, the voltage applied to the third capacitor C3 may damage circuit devices connected to the primary-side bridge circuit.
  • the third capacitor C3 may be a high-voltage aluminum electrolytic capacitor.
  • the charging system provided by the present application aims to solve the problem that the voltage applied to the primary bridge circuit damages circuit devices when the primary bridge circuit is no-loaded.
  • the charging system provided by the present application includes a primary bridge circuit, a transformer, a first secondary bridge circuit and a second secondary bridge circuit.
  • the primary bridge circuit is connected to the primary winding of the transformer, and the first secondary bridge circuit and the second secondary bridge circuit are both connected to the secondary winding of the transformer.
  • the switch tube of the primary side bridge circuit When the power is transferred from the first secondary side bridge circuit to the second secondary side bridge circuit, after the switch tube of the primary side bridge circuit is turned on for the duration Td, the switch tube of the first secondary side bridge circuit starts to be turned on .
  • the switch tube of the first secondary side bridge circuit After the switch tube of the primary side bridge circuit is turned on for a length of Td, the switch tube of the first secondary side bridge circuit starts to be turned on. That is, the time when the switch tube of the primary side bridge circuit starts to be turned on is ahead of the time when the switch tube of the first secondary side bridge type circuit starts to turn on, and the lead on time period is equal to the turn on time length Td.
  • the switch tube of the first secondary side bridge circuit can utilize the current to realize zero-voltage switching operation.
  • the lead-on duration Td is adjustable, and the longer the lead-on duration Td is, the greater the current flowing from the primary-side bridge circuit into the first secondary-side bridge circuit. Then, when the circuit works in a steady state, the voltage applied to the third capacitor C3 of the primary bridge circuit will decrease, and the voltage applied to the device connected to the primary bridge circuit will decrease. This can reduce the damage to the third capacitor C3 when the primary-side bridge circuit is no-load, and reduce the damage to the device connected to the primary-side bridge circuit.
  • the current flowing from the primary bridge circuit into the first secondary bridge circuit during the lead-on period of the switch of the primary bridge circuit can also assist the switch of the first secondary bridge circuit to achieve zero When the voltage is turned on, it can also supply power to the load of the first secondary side bridge circuit.
  • the switch tube of the primary side bridge circuit After the switch tube of the primary side bridge circuit is turned on for a length of Td, the switch tube of the first secondary side bridge circuit starts to be turned on. At this time, after the switch tube of the primary side bridge circuit and the switch tube of the first secondary side bridge circuit are both in a conducting state, the circuit enters a stable working state.
  • symmetric pulse width modulation PWM
  • asymmetric PWM is used to control the first secondary side bridge circuit.
  • Asymmetric PWM is used to control the switch tube of the first secondary side bridge circuit.
  • the first secondary-side bridge circuit includes a first half-bridge circuit and a second half-bridge circuit connected in parallel; the first half-bridge circuit includes a first switch transistor Q1 and a second switch transistor Q2, and the second half-bridge circuit includes a first half-bridge circuit
  • the three switch tubes Q3 and the fourth switch tube Q4; the first switch tube Q1 and the fourth switch tube Q4 are arranged diagonally, and the second switch tube Q2 and the third switch tube Q3 are arranged diagonally.
  • asymmetric PWM to control the first secondary-side bridge circuit includes:
  • the first switch transistor Q1 and the fourth switch transistor Q4 In the case of using the first switch transistor Q1 and the fourth switch transistor Q4 to form a loop, the first switch transistor Q1 and the fourth switch transistor Q4 start to conduct at the same time, and the on-time T1 of the first switch transistor Q1 is longer than the fourth switch transistor Q4 In the case of using the second switch tube Q2 and the fourth switch tube Q4 to form a loop, the second switch tube Q2 and the third switch tube Q3 start to conduct at the same time, and the third switch tube Q3 is turned on for the duration T1. It is greater than the conduction period T2 of the second switch transistor Q2.
  • asymmetric PWM as the name implies, that is, the conduction durations of the two diagonally distributed switches are different, so the width of the output voltage of the first secondary-side bridge circuit becomes controllable.
  • the first secondary-side bridge circuit forms a loop only when the two diagonally-distributed switch tubes are turned on at the same time, thereby outputting a voltage. Therefore, the conduction durations of the two diagonally-distributed switches are different, so the time for the first secondary bridge circuit to form a loop is determined by the switch with the shorter conduction duration among the two diagonally-distributed switches. .
  • the time for the first secondary-side bridge circuit to form a loop is the same as the on-time T2 of the second switch Q2 and the fourth switch Q4; the time for the first secondary-side bridge circuit to form a loop determines its output voltage , and since the on-time of the switch is determined by the duty cycle, as long as the duty cycle of the second switch Q2 and the fourth switch Q4 is determined, the output voltage of the first secondary-side bridge circuit can be determined. , thereby making the output voltage of the first secondary-side bridge circuit controllable.
  • the output voltage of the first secondary-side bridge circuit in the DC-DC mode can be regulated.
  • the control method of symmetric PWM that is, the time difference of the conduction time of the first switch Q1 and the fourth switch Q4, and the conduction time of the second switch Q2 and the fourth switch Q4, so that the first switch Q2 and the fourth switch Q4 have a time difference.
  • the Q1 to the fourth switching transistors Q4 are simultaneously in the off state at the time duration T12, so that zero-voltage switching of the first switching transistors Q1 to the fourth switching transistors Q4 is realized.
  • the on-time T2 of the second switch Q2 and the fourth switch Q4 is adjustable; and when the on-time T2 increases, the output voltage range of the first secondary-side bridge circuit increases. Since the on-time of the switch is determined by the duty ratio, the on-time T2 is adjustable, that is, the duty ratio of the second switch Q2 and the fourth switch Q4 is adjustable. By adjusting the duty ratio of the second switch Q2 and the fourth switch Q4, the output voltage of the first secondary-side bridge circuit can be adjusted, and after adjusting the duty cycle, the longer the on-time T2, the higher the output voltage. large; the shorter the on-time T2, the smaller the output voltage. Therefore, the output voltage regulation of the first secondary-side bridge circuit in the DC-DC working mode can be better realized.
  • the duty cycle of the output voltage of the first secondary-side bridge circuit can be controlled more precisely.
  • the output voltage of the first secondary-side bridge circuit is applied to the second secondary-side bridge circuit through the transformer. After rectification and filtering, the DC voltage output of the second secondary side bridge circuit can be stabilized, and the low-voltage battery of the electric vehicle can be charged to meet the driving needs.
  • the first switch tube Q1 and the fourth switch tube Q4 start to be turned on at the same time, and the first switch tube Q1 starts to turn off after the turn-on period T1,
  • the fourth switch transistor Q4 is turned off after the on-time duration T2.
  • the first switch tube Q1 continues to be turned on for a duration of T12.
  • the second switch tube Q2 and the third switch tube Q3 are also turned off, that is, the fourth switch tube Q4 is turned off for a duration of T12 at the same time.
  • the second switch transistor Q2 and the third switch transistor Q3 are turned off.
  • the second switch transistor Q2 and the fourth switch transistor Q4 start to conduct at the same time, the third switch transistor Q3 starts to turn off after the on-time duration T1, and the second switch transistor Q3 turns off.
  • the tube Q2 turns off after the conduction time T2.
  • the third switch tube Q3 continues to be turned on for the duration T12.
  • the first switch tube Q1 and the fourth switch tube Q4 are also turned off, that is, the second switch tube Q2 is turned off for the duration T12.
  • the third switch transistor Q3 is turned on for a duration of T12
  • the first switch transistor Q1 and the fourth switch transistor Q4 are turned off.
  • the first switch transistor Q1 and the fourth switch transistor Q4 In the case of using the first switch transistor Q1 and the fourth switch transistor Q4 to form a loop, that is, in the first half cycle, within the time difference T12, the first switch transistor Q1 is still in the conducting state, that is, after the fourth switch transistor Q4 is turned off , the first switch transistor Q1 will continue to maintain the on state, and the on-time duration of continuing to maintain the on state is T12 .
  • the second switch Q2 and the third switch Q3 are in the off state; that is, only the first switch is present at this time. Q1 is on.
  • the current of the first secondary bridge circuit will flow through the body diode of the third switch Q3 and the body diode of the first switch Q1, and then form a new closed-loop current path. Then, in the working state where the body diode of the first switch transistor Q1 and the body diode of the third switch transistor Q3 are turned on to form a loop, the current flowing out of the transformer can only flow out in one direction, and is connected in series with the parasitic parasitics of the first secondary side bridge circuit. The current of the inductor decreases, because the third switch transistor Q3 is still in an off state, so the current cannot be increased, so the circulating current of the transformer decreases.
  • the second switch Q2 and the third switch Q3 start to be turned on at the same time, and the turn-on duration T1 of the third switch Q3 is greater than the turn-on duration T2 of the second switch Q2.
  • the third switch transistor Q3 is still in the on state, that is, after the second switch transistor Q2 is turned off, the third switch transistor Q3 will continue to maintain the on state, and the on-time duration of maintaining the on state is T12 .
  • the first switch tube Q1 and the fourth switch tube Q4 are in the off state; that is, only the third switch tube is present at this time. Q3 is on. Then, in the working state of using the second switch tube Q2 and the third switch tube Q3 to form a loop, the circulating current of the secondary winding connected to the transformer and the first secondary bridge circuit can also be reduced.
  • the current of the primary-side bridge circuit decreases, the voltage to the third capacitor C3 in the primary-side bridge circuit decreases, thereby reducing the probability of damage to the devices connected to the primary-side bridge circuit. Referring to FIG. 4, it can be seen that when both the first switch Q1 and the third switch Q3 are not turned on, the voltage on the winding of the transformer is the free oscillation waveform in T12.
  • using asymmetric PWM to control the first secondary-side bridge circuit also includes: after the first switch Q1 is turned off for a duration TD, the second switch Q2 and the third switch Q3 start to conduct at the same time; After the three-switch Q3 is cut off for a length of TD, it enters the next working cycle. Because the fourth switch transistor Q4 is already in the off state before the first switch transistor Q1 starts to be off, and the second switch transistor Q2 and the third switch transistor Q3 are also in the off state during the time period when the first switch transistor Q1 is off for the duration TD .
  • the first switch transistor Q1 to the fourth switch transistor Q4 are all in the off state, that is, the first switch transistor Q1 and the fourth switch transistor Q4 are all in the zero voltage state.
  • the control method of the lead-on of the switch of the primary-side bridge circuit allows a relatively large current to flow from the primary-side bridge circuit into the first secondary-side bridge during the lead-on time period Td. After the current flows into the first secondary side bridge circuit, the switch tube of the first secondary side bridge circuit is turned on by the current.
  • the first switch transistor Q1 and the fourth switch transistor Q4 can implement a zero voltage switch (ZVS).
  • ZVS zero voltage switch
  • the value of TD can be: 300 nanoseconds.
  • the conduction duration Td of the switch tube of the primary bridge circuit is adjustable; and when the duration Td increases, the voltage across the high voltage electrolytic capacitor of the primary bridge circuit decreases.
  • the range of the on-delay Td of the switch tube of the primary-side bridge circuit is: 300 ns ⁇ Td ⁇ 500 ns, and the Td is limited to between 300 ns and 500 ns, which can be
  • the first switch transistor Q1 and the fourth switch transistor Q4 can achieve a full range of ZVS; the full range here refers to the full output load range of the DCDC working mode, such as the working area where the output current is from 0% to 100%.
  • the adjustable Td can also achieve a better balance on the loss of the primary bridge circuit.
  • the primary-side bridge circuit includes a third half-bridge circuit and a fourth half-bridge circuit in parallel; the third half-bridge circuit includes a fifth switch Q5 and a sixth switch Q6, and the fourth half-bridge circuit includes a seventh switch The tube Q7 and the eighth switch tube Q8; the fifth switch tube Q5 and the eighth switch tube Q8 are arranged diagonally, and the sixth switch tube Q6 and the seventh switch tube Q7 are arranged diagonally.
  • Using symmetrical PWM to control the primary-side bridge circuit includes: when the fifth switch Q5 and the eighth switch Q8 are used to form a loop, the conduction time T4 of the fifth switch Q5 is equal to the conduction of the eighth switch Q8 Duration T4; when the sixth switch transistor Q6 and the seventh switch transistor Q7 are used to form a loop, the conduction duration T3 of the seventh switch transistor Q7 is equal to the conduction duration T3 of the sixth switch transistor Q6.
  • the sixth switch tube Q6 and the seventh switch tube Q7 are turned on synchronously for a duration T3, and then turn off; after the sixth switch tube Q6 and the seventh switch tube Q7 turn off for a duration T0, the fifth switch tube Q5 turns off.
  • the fifth switch Q5 and the eighth switch Q8 are turned off for a duration T0 and then enter the next working cycle TS.
  • the working sequence of the first secondary side bridge circuit can be as follows: within one working cycle TS, the first switch transistor Q1 and the fourth switch transistor Q4 start to conduct at the same time. On, the first switch Q1 is turned on for a duration of T1 and then turned off, and the fourth switch Q4 is turned on for a duration of T2 and then turned off; after the first switch Q1 is turned off for a length of TD, the second switch Q2 and the third switch Q3 start to conduct at the same time.
  • the second switch Q2 is turned on for a duration of T2 and then ends, the third switch Q3 is turned on for a duration of T1 and then ends; after the third switch Q3 is turned off for a duration of TD, it enters the next working cycle TS.
  • FIG. 5 to 8 show several schematic diagrams of current flow, wherein the current flow shown in FIG. 5 corresponds to the first switch Q1 , the fourth switch Q4 , the sixth switch Q6 and the seventh switch in FIG. 2 .
  • the first secondary side bridge circuit transmits power to the primary side bridge circuit and the second secondary side bridge circuit respectively.
  • the current flow shown in FIG. 6 corresponds to the time period T12 in FIG. 2 , only the first switch transistor Q1 is in the conducting state. At this time, the remaining second switch transistors Q2, third switch transistors Q3, and fourth switch transistors Q4 and the fifth switch transistor Q5 to the eighth switch transistor Q8 are all turned off. After the fourth switch transistor Q4 is turned off, the current of the first secondary side bridge circuit will flow through the second switch transistor Q2 and the third switch transistor Q3 to form a new closed-loop current path.
  • the first inductance L1 of the primary bridge circuit has a current flowing in the previous state. At this time, the current will charge the parasitic capacitance of the seventh switch Q7 and the parasitic capacitance of the eighth switch Q8, and the current will also flow.
  • a new closed-loop current path is formed through the body diode of the sixth switch Q6 and the body diode of the seventh switch Q7, and at the same time, it resonates with the parasitic capacitances of the four switches in the primary bridge circuit
  • the current flow shown in FIG. 7 corresponds to the Td-TD time period in FIG. 2 , the fifth switch Q5 and the eighth switch Q8 in the primary bridge circuit are turned on, and the first secondary bridge circuit in the first The switch tube Q1 is turned on.
  • the fifth switch Q5 and the eighth switch Q8 are turned on in advance for the time period Td.
  • a relatively large current will flow into the bridge arms of the third switch Q3 and the fourth switch Q4, which are the first auxiliary The ZVS implementation of the side bridge circuit provides sufficient current.
  • the current flow shown in FIG. 8 corresponds to the schematic diagram of the current flow when the second switch Q2, the third switch Q3, the fifth switch Q5 and the eighth switch Q8 are turned on at the same time in FIG. 2, that is, the circuit steady state operation.
  • the first secondary side bridge circuit transmits power to the primary side bridge circuit and the second secondary side bridge circuit respectively.
  • the primary-side bridge circuit is commutated, from negative current to positive current.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Transportation (AREA)
  • Mechanical Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

一种充电系统和汽车，充电系统包括原边桥式电路、变压器(T)、第一副边桥式电路和第二副边桥式电路；原边桥式电路和变压器(T)的初级绕组连接，第一副边桥式电路和第二副边桥式电路均和变压器(T)的次级绕组连接；在功率从第一副边桥式电路传递到第二副边桥式电路的情况下，原边桥式电路的开关管(Q5-Q8)导通时长Td之后，第一副边桥式电路的开关管(Q1-Q4)开始导通。通过设置原边电路的开关管(Q5-Q8)超前一个副边电路的开关管(Q1-Q4)导通，从而在DC-DC工作模式下，降低传递至原边电路的功率，避免对原边电路的开关管(Q5-Q8)和高压电解电容(C3)等器件造成损伤。

Description

一种充电系统和汽车 技术领域
本申请涉及电气技术领域，尤其涉及一种充电系统和汽车。
背景技术
新能源汽车的动力来源主要是动力电池，为保持续航能力，动力电池需要通过充电系统定期充电。
目前，采用的充电系统多具有双向充电功能，该充电系统包括原边电路和两个副边电路。具有双向充电功能的充电系统具有多种工作模式，其中一种工作模式为直流-直流(direct current to direct current，DC-DC)模式，也即和其中一个副边电路连接直流电源的功率，从其中一个副边电路传递至另一个副边电路，并最终供给和另一个副边电路连接的直流工作设备。由于在DC-DC模式下，闭环控制仅涉及两个副边电路，此时原边电路空载且没有形成闭环控制，另外，一个副边电路供给的功率也会经过变压器传递至原边电路，那么由于闭环控制不涉及原边电路，原边电路的开关管和电容等器件会被传递过来的功率或高电压损伤。
发明内容
本申请的目的在于提供一种充电系统和汽车，解决原边电路的开关管和高压电解电容等器件被损伤的问题。
本申请第一方面提供一种充电系统，包括：原边桥式电路、变压器、第一副边桥式电路和第二副边桥式电路；原边桥式电路和变压器的初级绕组连接，第一副边桥式电路和第二副边桥式电路均和变压器的次级绕组连接；在功率从第一副边桥式电路传递到第二副边桥式电路的情况下，原边桥式电路的开关管导通时长Td之后，第一副边桥式电路的开关管开始导通。
可选的，采用对称脉冲宽度调制PWM对原边桥式电路进行控制，采用不对称PWM对第一副边桥式电路进行控制。
可选的，第一副边桥式电路包括并联的第一半桥电路和第二半桥电路；第一半桥电路包括第一开关管和第二开关管，第二半桥电路包括第三开关管和第 四开关管；第一开关管和第四开关管成对角分布，第二开关管和第三开关管成对角分布；采用不对称PWM对第一副边桥式电路进行控制包括：利用第一开关管和第四开关管形成回路的情况下，第一开关管和第四开关管同时开始导通，第一开关管的导通时长T1大于第四开关管的导通时长T2；利用第二开关管和第四开关管形成回路的情况下，第二开关管和第三开关管同时开始导通，第三开关管的导通时长T1大于第二开关管的导通时长T2。
可选的，采用不对称PWM对第一副边桥式电路进行控制还包括：第四开关管截止时长T12的同时，第一开关管导通时长T12的情况下，第二开关管和第三开关管截止；在第二开关管截止时长T12的同时，第三开关管导通时长T12的情况下，第一开关管和第四开关管截止；其中时长T1、时长T2和时长T12满足以下关系：T12＝T1-T2。
可选的，采用不对称PWM对第一副边桥式电路进行控制还包括：在第一开关管截止时长TD后，第二开关管和第三开关管同时开始导通；在第三开关管截止时长TD后，进入下一个工作周期。
可选的，第二开关管和第四开关管的导通时长T2可调；且在导通时长T2增大的情况下，第一副边桥式电路的输出电压的范围增大。
可选的，原边桥式电路的开关管的导通时长Td的范围为：300纳秒≥Td≥500纳秒。
可选的，原边桥式电路包括并联的第三半桥电路和第四半桥电路；第三半桥电路包括第五开关管和第六开关管，第四半桥电路包括第七开关管和第八开关管；第五开关管和第八开关管成对角分布，第六开关管和第七开关管成对角分布；采用对称PWM对原边桥式电路进行控制包括：利用第五开关管和第八开关管形成回路的情况下，第五开关管的导通时长T4等于第八开关管的导通时长T4；利用第六开关管和第七开关管形成回路的情况下，第七开关管的导通时长T3等于第六开关管的导通时长T3。
可选的，在一个工作周期TS内，第六开关管和第七开关管同步导通时长T3后截止；第六开关管和第七开关管截止时长T0后，第五开关管和第八开关管同步导通时长T4后截止，第五开关管和第八开关管截止时长T0后，进入下一个工作周期TS。
本申请第二方面提供一种汽车，包括本申请第一方面任一项的充电系统。
本申请通过设置原边电路的开关管超前一个副边电路的开关管导通，从而在DC-DC工作模式下，降低传递至原边电路的功率，避免对原边电路的开关管和高压电解电容等器件造成损伤。
附图说明
为了更清楚地说明本申请的技术方案，下面将对实施方式中所需要使用的附图作简单地介绍。
图1是本申请实施例提供的充电系统的电路图；
图2是本申请实施例提供的充电系统的时序图；
图3是本申请实施例提供的第一副边桥式电路的电流和电压时序图；
图4是本申请实施例提供的原边桥式电路的电流和电压时序图；
图5是本申请实施例提供的充电系统的一种电流流向示意图；
图6是本申请实施例提供的充电系统的一种电流流向示意图；
图7是本申请实施例提供的充电系统的一种电流流向示意图；
图8是本申请实施例提供的充电系统的一种电流流向示意图。
附图标记说明：
Q1-第一开关管，Q2-第二开关管，Q3-第三开关管，Q4-第四开关管，Q5-第五开关管，Q6-第六开关管，Q7-第七开关管，Q8-第八开关管，Q9-第九开关管，Q10-第十开关管，C1-第一电容，C2-第二电容，C3-第三电容，C4-第四电容，C5-第五电容，L1-第一电感，L2-第二电感，L3-第三电感，D1-第一二极管，D2-第二二极管，R-电阻。
具体实施方式
下面将结合本申请实施例中的附图，对本申请实施例中的技术方案进行清楚、完整地描述。
以下先介绍本申请实施例提供的充电系统的电路结构，如图1所示，该充电系统的电路包括原边桥式电路、变压器、第一副边桥式电路和第二副边桥式 电路。
其中，原边桥式电路和变压器的初级绕组连接，第一副边桥式电路和第二副边桥式电路均和变压器的次级绕组连接。次级绕组包括第一次级绕组和第二次级绕组，其中第二副边桥式电路和第一次级绕组连接，第二副边桥式电路和第二次级绕组连接。
详细地，第一副边桥式电路包括并联的第一半桥电路和第二半桥电路；第一半桥电路包括第一开关管Q1和第二开关管Q2，第二半桥电路包括第三开关管Q3和第四开关管Q4；第一开关管Q1和第四开关管Q4成对角分布，第二开关管Q2和第三开关管Q3成对角分布。第一副边桥式电路还包括第一电容C1和第二电容C2，第一电容C1和第二半桥电路并联，第二电容C2的一端和第一次级绕组的一端连接，另一端连接在第三开关管Q3和第四开关管Q4之间；第一次级绕组的另一端连接在第一开关管Q1和第二开关管Q2之间。
原边桥式电路包括并联的第三半桥电路和第四半桥电路；第三半桥电路包括第五开关管Q5和第六开关管Q6，第四半桥电路包括第七开关管Q7和第八开关管Q8；第五开关管Q5和第八开关管Q8成对角分布，第六开关管Q6和第七开关管Q7成对角分布。原边桥式电路还包括第三电容C3、第四电容C4和第一电感L1。其中，第三电容C3和第三半桥电路并联；第一电感L1的一端连接在第七开关管Q7和第八开关管Q8之间，第一电感L1的另一端和初级绕组的一端连接；第四电容C4的一端连接在第五开关管Q5和第八开关管Q8之间，第四电容C4的另一端和初级绕组的另一端连接。
第二副边桥式电路包括第九开关管Q9、第十开关管Q10、第一二极管D1、第二二极管D2、第三电感L3、第五电容C5和电阻R。其中，第一二极管D1的一端和第二次级绕组的一端连接，第一二极管D1的另一端和第九开关管Q9的一端连接；第二二极管D2的一端和第二次级绕组的另一端连接，第二二极管D2的另一端也和第九开关管Q9的一端连接；第九开关管Q9的另一端分别和第三电感L3的一端以及第十开关管Q10的一端连接；第三电感L3的另一端分别和第五电容C5的一端和电阻R一端连接；第十开关管Q10的另一端、第五电容C5的另一端和电阻R的另一端分别和第二次级绕组的中部连接。
另外，图中示出的第二电感L2为变压器的漏感。当然，变压器的漏感实际中并无物理实体，图中第二电感L2仅做示意用。
一般情况下，该充电系统的电路具有五种工作模式：
第一种：功率从原边桥式电路逆变成交流方波，然后经过变压器传递到第一副边桥式电路，为汽车的动力电池充电。
第二种：功率从原边桥式电路逆变为交流方波，然后经过变压器传递到第一副边桥式电路，为汽车的动力电池充电。同时还经过变压器传递到第二副边桥式电路，经过降压电路稳压后为汽车的蓄电池充电。
第三种：功率从第一副边桥式电路逆变为交流方波，然后经过变压器传递到原边桥式电路，将动力电池的电能提供给外车的外部负载。
第四种：功率从第一副边桥式电路逆变为交流方波，然后经过变压器传递到原边桥式电路，将动力电池的电能提供给外车的外部负载。同时还经过变压器传递到第二副边桥式电路，经过降压电路稳压后为汽车的蓄电池充电。
第五种：功率从第一副边桥式电路逆变成交流方波，然后经过变压器传递到第二副边桥式电路，经过降压电路稳压后为汽车的蓄电池充电。
上述第五种工作模式也称为直流-直流(direct current to direct current，DC-DC)模式。
在电路以DC-DC模式工作的情况下，动力电池连接在第一副边桥式电路的两端作为输入电源，此时控制第一副边桥式电路成对角分布的开关管同时导通，由此可以控制第一副边桥式电路输出方波电压。该方波电压会传输至和第一副边桥式电路连接的变压器的次级绕组上，根据变压器的电磁感应原理，变压器会在和原边桥式电路和第二副边桥式电路连接的初级绕组和次级绕组上输出成比例的电压，不同绕组的输出电压受到变压器的绕组的线圈匝数比约束。
也即，第一副边桥式电路输出的方波电压，不仅会传递至第二副边桥式电路，还会传递至原边桥式电路。而传递至原边桥式电路的电压经过原边桥式电路的体二极管的整流，再通第三电容C3滤波，会在原边桥式电路的第三电容C3两端形成稳定的高压直流电，该高压直流电可能会损伤第三电容C3。同时，由于原边桥式电路还串联有电容电感LC谐振电路，在原边桥式电路完全空载 的情况下，在谐振电路作用下加在第三电容C3上的电压将超过变压器的初级绕组的电压。此时，加在第三电容C3上的电压可能会损坏与原边桥式电路连接的电路器件。该第三电容C3可以为高压铝电解电容。
请同时参考图1和图2，本申请提供的充电系统致力于解决原边桥式电路空载时，加在原边桥式电路的电压损伤电路器件的问题。
具体地，本申请提供的充电系统，包括原边桥式电路、变压器、第一副边桥式电路和第二副边桥式电路。其中，原边桥式电路和变压器的初级绕组连接，第一副边桥式电路和第二副边桥式电路均和变压器的次级绕组连接。
在功率从第一副边桥式电路传递到第二副边桥式电路的情况下，原边桥式电路的开关管导通时长Td之后，第一副边桥式电路的开关管开始导通。
原边桥式电路的开关管导通时长Td之后，第一副边桥式电路的开关管开始导通。也即，原边桥式电路的开关管开始导通的时间超前第一副边桥式电路的开关管开始导通的时间，并且超前导通时长等于导通时长Td。
原边桥式电路的开关管超前导通的控制方式，使得在该超前导通的时间段内，有较大的电流从原边桥式电路流入第一副边桥式电路，该电流流入第一副边桥式电路后，第一副边桥式电路的开关管可以利用该电流实现零电压开关工作。
本领域技术人员可以理解的是，超前导通时长Td可调，并且超前导通时长Td越大，从原边桥式电路流入第一副边桥式电路的电流越大。那么，在电路进入稳态工作的情况下，加在原边桥式电路的第三电容C3的电压会降低，加在和原边桥式电路连接的器件上的电压会降低。由此可以降低原边桥式电路空载时，对第三电容C3的损伤，以及降低对和原边桥式电路连接的器件的损伤。
另外，在原边桥式电路的开关管超前导通时间段内，从原边桥式电路流入第一副边桥式电路中的电流，还可以辅助第一副边桥式电路的开关管实现零电压开通，也能为第一副边桥式电路的负载供电。
原边桥式电路的开关管导通时长Td之后，第一副边桥式电路的开关管开始导通。此时，原边桥式电路的开关管和第一副边桥式电路的开关管均处于导通状态后，那么电路进入稳定工作状态。
进一步地，请继续参考图2，采用对称脉冲宽度调制(pulse width modulation，PWM)对原边桥式电路进行控制，采用不对称PWM对第一副边桥式电路进行控制。采用不对称PWM对第一副边桥式电路的开关管进行控制，结合上述原边桥式电路的开关管超前导通的设计，可以实现第一副边桥式电路的开关管整个负载范围中零电压开关，拓宽了零电压开关的工作范围。
具体地，第一副边桥式电路包括并联的第一半桥电路和第二半桥电路；第一半桥电路包括第一开关管Q1和第二开关管Q2，第二半桥电路包括第三开关管Q3和第四开关管Q4；第一开关管Q1和第四开关管Q4成对角分布，第二开关管Q2和第三开关管Q3成对角分布。
请继续参考图2，采用不对称PWM对第一副边桥式电路进行控制包括：
利用第一开关管Q1和第四开关管Q4形成回路的情况下，第一开关管Q1和第四开关管Q4同时开始导通，第一开关管Q1的导通时长T1大于第四开关管Q4的导通时长T2；利用第二开关管Q2和第四开关管Q4形成回路的情况下，第二开关管Q2和第三开关管Q3同时开始导通，第三开关管Q3的导通时长T1大于第二开关管Q2的导通时长T2。
采用不对称PWM，顾名思义，也就是成对角分布的两个开关管的导通时长不同，那么第一副边桥式电路的输出电压的宽度则变得可控。具体地，由于对角分布的两个开关管同时导通的情况下，第一副边桥式电路才会形成一个回路，从而输出电压。因此，成对角分布的两个开关管导通时长不相同，那么第一副边桥式电路形成回路的时间，由成对角分布的两个开关管中导通时长较短的开关管决定。具体地，第一副边桥式电路形成回路的时间，与第二开关管Q2和第四开关管Q4的导通时长T2相同；第一副边桥式电路形成回路的时间决定其输出电压大小，而由于开关管的导通时长由占空比决定，因此，只要确定第二开关管Q2和第四开关管Q4的占空比，则可以确定第一副边桥式电路的输出电压的大小，由此使得第一副边桥式电路的输出电压可控。
从上可见，本实施例通过对第一副边桥式电路采用不对称PWM进行控制的方式，实现DC-DC模式下第一副边桥式电路的输出电压稳压的同时，还可以通过不对称PWM的控制方式，也即第一开关管Q1和第四开关管Q4的导通时长有时差，第二开关管Q2和第四开关管Q4的导通时长有时差，从而使 得第一开关管Q1至第四开关管Q4在时长T12处同时处于截止状态，实现了第一开关管Q1至第四开关管Q4零电压开关。
进一步地，第二开关管Q2和第四开关管Q4的导通时长T2可调；且在导通时长T2增大的情况下，第一副边桥式电路的输出电压的范围增大。由于开关管的导通时长由占空比决定，因此，导通时长T2可调，也即第二开关管Q2和第四开关管Q4的占空比可调。通过调整第二开关管Q2和第四开关管Q4的占空比，就可以调整第一副边桥式电路的输出电压，并且，调整占空比后，导通时长T2越长，输出电压越大；导通时长T2越短，输出电压越小。由此可以更好的实现DC-DC工作模式下，第一副边桥式电路的输出电压稳压。也即，可以更加精确的控制第一副边桥式电路的输出电压的占空比的大小，第一副边桥式电路的输出电压经过变压器加在第二副边桥式电路，该电压经过整流和滤波后，能稳定第二副边桥式电路的直流电压输出，为电动汽车的低压蓄电池充电，满足行车需要。
进一步地，利用第一开关管Q1和第四开关管Q4形成回路的情况下，第一开关管Q1和第四开关管Q4同时开始导通，第一开关管Q1导通时长T1后开始截止，第四开关管Q4导通时长T2后开始截止。在第四开关管Q4截止后，第一开关管Q1继续导通时长T12，此时，第二开关管Q2和第三开关管Q3也截止，也即，第四开关管Q4截止时长T12的同时，第一开关管Q1导通时长T12的情况下，第二开关管Q2和第三开关管Q3截止。
利用第二开关管Q2和第四开关管Q4形成回路的情况下，第二开关管Q2和第三开关管Q3同时开始导通，第三开关管Q3导通时长T1后开始截止，第二开关管Q2导通时长T2后开始截止。在第二开关管Q2截止后，第三开关管Q3继续导通时长T12，此时，第一开关管Q1和第四开关管Q4也截止，也即，在第二开关管Q2截止时长T12的同时，第三开关管Q3导通时长T12的情况下，第一开关管Q1和第四开关管Q4截止。其中时长T1、时长T2和时长T12满足以下关系：T12＝T1-T2。
上述已经提及，第一开关管Q1和第四开关管Q4同时开始导通，第一开关管Q1的导通时长T1大于第四开关管Q4的导通时长T2。由此可知，第四开关管Q4会先于第一开关管Q1开始截止，也就是说第一开关管Q1和第四 开关管Q4的截止具有时间差，该时间差为T12＝T1-T2。利用第一开关管Q1和第四开关管Q4形成回路的情况下，也即在前半周期内，在时间差T12内，第一开关管Q1还是处于导通状态，也即第四开关管Q4截止后，第一开关管Q1会继续维持导通状态，并且继续维持导通状态的导通时长为T12。在第四开关管Q4截止，并且第一开关管Q1继续维持导通状态的这段时间内，第二开关管Q2和第三开关管Q3处于截止状态；也即此时仅有第一开关管Q1处于导通状态。
在控制第四开关管Q4截止后，此时第一副边桥式电路的电流会流经第三开关管Q3的体二极管和第一开关管Q1的体二极管，然后形成新的闭环电流路径。那么在利用第一开关管Q1的体二极管和第三开关管Q3的体二极管导通形成回路的工作状态下，流出变压器的电流仅能单向流出，串联在第一副边桥式电路的寄生电感的电流下降，因为第三开关管Q3还处于关闭状态，所以该电流不能增大，因此变压器的环流电流降低。
参考图3可见，在控制第四开关管Q4截止后，环流电流降低，则传递至原边桥式电路的电流降低，那么对原边桥式电路中的第三电容C3的损伤会较小，对和原边桥式电路连接的器件的损伤也较小。环流电流降低，则原边桥式电路的开关管和高压电解电容的电压降低，再加上原边桥式电路超前于第一副边桥式电路导通Td的原因，在该超前的时间段内，会有电流从第三电容C3流出。从一个工作周期的角度来讲，因为原边桥式电路的第三电容C3中的电荷在Td时间段流出，所以在降低环流和原边桥式电路超前第一副边桥式电路TD时间综合作用下，可以降低原边高压电解电容器的电压。
同样的道理，第二开关管Q2和第三开关管Q3同时开始导通，第三开关管Q3的导通时长T1大于第二开关管Q2的导通时长T2。由此可知，第二开关管Q2会先于第三开关管Q3开始截止，也就是说，第二开关管Q2和第三开关管Q3的截止具有时间差，该时间差也为T12＝T1-T2。在时间差T12内，第三开关管Q3还是处于导通状态，也即第二开关管Q2截止后，第三开关管Q3会继续维持导通状态，并且继续维持导通状态的导通时长为T12。在第二开关管Q2截止，并且第三开关管Q3继续维持导通状态的这段时间内，第一开关管Q1和第四开关管Q4处于截止状态；也即此时仅有第三开关管Q3处 于导通状态。那么在利用第二开关管Q2和第三开关管Q3形成回路的工作状态下，也可以降低变压器和第一副边桥式电路连接的次级绕组的环流电流，该环流电流降低，则传递至原边桥式电路的电流降低，那么对原边桥式电路中的第三电容C3的电压会降低，从而降低原边桥式电路连接的器件产生被损伤的机率。参考图4可见，在第一开关管Q1和第三开关管Q3两者都没有导通时，变压器的绕组上的电压为T12里面的自由振荡的波形。
更进一步地，采用不对称PWM对第一副边桥式电路进行控制还包括：在第一开关管Q1截止时长TD后，第二开关管Q2和第三开关管Q3同时开始导通；在第三开关管Q3截止时长TD后，进入下一个工作周期。由于第四开关管Q4在第一开关管Q1开始截止之前已经处于截止状态，而第二开关管Q2和第三开关管Q3在第一开关管Q1截止时长TD的时间段内，也处于截止状态。那么也就是说，在TD时间段内，第一开关管Q1至第四开关管Q4全部处于截止状态，也即第一开关管Q1和第四开关管Q4全部处于零电压状态。而上述已经提及，原边桥式电路的开关管超前导通的控制方式，使得在该超前导通的时间段Td内，有较大的电流从原边桥式电路流入第一副边桥式电路，该电流流入第一副边桥式电路后，第一副边桥式电路的开关管利用该电流导通。结合第一开关管Q1和第四开关管Q4全部处于零电压状态的情况，此时第一开关管Q1和第四开关管Q4可以实现零电压开关(zero voltage switch，ZVS)。可选的，TD的取值可以为：300纳秒。
可选地，原边桥式电路的开关管的导通时长Td可调；且在时长Td增大的情况下，原边桥式电路的高压电解电容两端的电压降低。在一种实施方式中，原边桥式电路的开关管导通延时时长Td的范围为：300纳秒≥Td≥500纳秒，将Td限制在300纳秒至500纳秒之间，可以使得第一开关管Q1和第四开关管Q4实现全范围的ZVS；此处的全范围是指DCDC工作模式的全输出负载范围，如输出电流从0％到100％的工作区域。另外，Td可调还可以在原边桥式电路的损耗上达到一种较好的平衡。
进一步地，原边桥式电路包括并联的第三半桥电路和第四半桥电路；第三半桥电路包括第五开关管Q5和第六开关管Q6，第四半桥电路包括第七开关管Q7和第八开关管Q8；第五开关管Q5和第八开关管Q8成对角分布，第六 开关管Q6和第七开关管Q7成对角分布。
采用对称PWM对原边桥式电路进行控制包括：利用第五开关管Q5和第八开关管Q8形成回路的情况下，第五开关管Q5的导通时长T4等于第八开关管Q8的导通时长T4；利用第六开关管Q6和第七开关管Q7形成回路的情况下，第七开关管Q7的导通时长T3等于第六开关管Q6的导通时长T3。
进一步地，在一个工作周期TS内，第六开关管Q6和第七开关管Q7同步导通时长T3后截止；第六开关管Q6和第七开关管Q7截止时长T0后，第五开关管Q5和第八开关管Q8同步导通时长T4后截止，第五开关管Q5和第八开关管Q8截止时长T0后，进入下一个工作周期TS。
结合上述第一副边桥式电路的控制方法，可知，对于第一副边桥式电路的工作时序可以为：在一个工作周期TS内，第一开关管Q1和第四开关管Q4同时开始导通，第一开关管Q1导通时长T1后截止，第四开关管Q4导通时长T2后截止；第一开关管Q1截止时长TD后，第二开关管Q2和第三开关管Q3同时开始导通，第二开关管Q2导通时长T2后截止，第三开关管Q3导通时长T1后截止；第三开关管Q3截止时长TD后，进入下一个工作周期TS。
图5至图8示出了几种电流流向示意图，其中图5中示出的电流流向对应图2中，第一开关管Q1、第四开关管Q4、第六开关管Q6和第七开关管Q7同时导通情况下的电流流向示意图，也即电路的稳态工作情况。此时，第一副边桥式电路分别向原边桥式电路和第二副边桥式电路传递功率。
图6中示出的电流流向对应图2中T12时间段内，仅有第一开关管Q1处于导通状态，此时，其余的第二开关管Q2、第三开关管Q3、第四开关管Q4以及第五开关管Q5至第八开关管Q8均截止。第一副边桥式电路的电流在第四开关管Q4截止后，会流经第二开关管Q2和第三开关管Q3形成新的闭环电流路径。原边桥式电路的第一电感L1因在上一个状态里流过电流，此时该电流会向第七开关管Q7的寄生电容和第八开关管Q8的寄生电容充电，该电流还会流过第六开关管Q6的体二极管和第七开关管Q7的体二极管形成新的闭环电流路径，同时和原边桥式电路中的四个开关管的寄生电容进行谐振。
图7中示出的的电流流向对应图2中Td-TD时间段内，原边桥式电路中第五开关管Q5和第八开关管Q8导通，第一副边桥式电路中第一开关管Q1 导通。第五开关管Q5和第八开关管Q8超前导通了时间段Td，在该段时间段内，会有较大电流流入第三开关管Q3和第四开关管Q4桥臂，为第一副边桥式电路的ZVS实现提供了足够的电流。
图8中示出的电流流向对应图2中，第二开关管Q2、第三开关管Q3、第五开关管Q5和第八开关管Q8同时导通情况下的电流流向示意图，也即电路的稳态工作情况。此时，第一副边桥式电路分别向原边桥式电路和第二副边桥式电路传递功率。此时，原边桥式电路进行了换相，从负向电流换为正向电流。
以上对本申请实施例进行了详细介绍，本文中应用了具体个例对本申请的原理及实施方式进行了阐述，以上实施例的说明只是用于帮助理解本申请的方法及其核心思想。

Claims (10)

  1. 一种充电系统，其特征在于，包括：原边桥式电路、变压器、第一副边桥式电路和第二副边桥式电路；
    所述原边桥式电路和所述变压器的初级绕组连接，所述第一副边桥式电路和所述第二副边桥式电路均和所述变压器的次级绕组连接；
    在功率从所述第一副边桥式电路传递到所述第二副边桥式电路的情况下，所述原边桥式电路的开关管导通时长Td之后，所述第一副边桥式电路的开关管开始导通。
  2. 根据权利要求1所述的充电系统，其特征在于，采用对称脉冲宽度调制PWM对所述原边桥式电路进行控制，采用不对称PWM对所述第一副边桥式电路进行控制。
  3. 根据权利要求2所述的充电系统，其特征在于，所述第一副边桥式电路包括并联的第一半桥电路和第二半桥电路；所述第一半桥电路包括第一开关管和第二开关管，所述第二半桥电路包括第三开关管和第四开关管；所述第一开关管和所述第四开关管成对角分布，所述第二开关管和所述第三开关管成对角分布；
    所述采用不对称PWM对所述第一副边桥式电路进行控制包括：
    利用所述第一开关管和所述第四开关管形成回路的情况下，所述第一开关管和所述第四开关管同时开始导通，所述第一开关管的导通时长T1大于所述第四开关管的导通时长T2；利用所述第二开关管和所述第四开关管形成回路的情况下，所述第二开关管和所述第三开关管同时开始导通，所述第三开关管的导通时长T1大于所述第二开关管的导通时长T2。
  4. 根据权利要求3所述的充电系统，其特征在于，所述采用不对称PWM对所述第一副边桥式电路进行控制还包括：
    所述第四开关管截止时长T12的同时，所述第一开关管导通时长T12的情况下，所述第二开关管和所述第三开关管截止；在所述第二开关管截止时长T12的同时，所述第三开关管导通时长T12的情况下，所述第一开关管和所述第四开关管截止；
    其中时长T1、时长T2和时长T12满足以下关系：
    T12＝T1-T2。
  5. 根据权利要求4所述的充电系统，其特征在于，采用不对称PWM对所述第一副边桥式电路进行控制还包括：
    在所述第一开关管截止时长TD后，所述第二开关管和所述第三开关管同时开始导通；在所述第三开关管截止时长TD后，进入下一个工作周期。
  6. 根据权利要求3至5中任一项所述的充电系统，其特征在于，所述第二开关管和所述第四开关管的导通时长T2可调；且在所述导通时长T2增大的情况下，所述第一副边桥式电路的输出电压的范围增大。
  7. 根据权利要求1至6中任一项所述的充电系统，其特征在于，所述原边桥式电路的开关管的导通时长Td的范围为：300纳秒≥Td≥500纳秒。
  8. 根据权利要求1至7中任一项所述的充电系统，其特征在于，所述原边桥式电路包括并联的第三半桥电路和第四半桥电路；所述第三半桥电路包括第五开关管和第六开关管，所述第四半桥电路包括第七开关管和第八开关管；所述第五开关管和所述第八开关管成对角分布，所述第六开关管和所述第七开关管成对角分布；
    采用对称PWM对所述原边桥式电路进行控制包括：
    利用所述第五开关管和所述第八开关管形成回路的情况下，所述第五开关管的导通时长T4等于所述第八开关管的导通时长T4；利用所述第六开关管和所述第七开关管形成回路的情况下，所述第七开关管的导通时长T3等于所述第六开关管的导通时长T3。
  9. 根据权利要求8所述的充电系统，其特征在于，在一个工作周期TS内，所述第六开关管和所述第七开关管同步导通时长T3后截止；所述第六开关管和所述第七开关管截止时长T0后，所述第五开关管和所述第八开关管同步导通时长T4后截止，所述第五开关管和所述第八开关管截止时长T0后，进入下一个工作周期TS。
  10. 一种汽车，其特征在于，包括权利要求1至9中任一项所述的充电系统。
PCT/CN2020/138586 2020-12-23 2020-12-23 一种充电系统和汽车 WO2022133793A1 (zh)

Priority Applications (4)

Application Number Priority Date Filing Date Title
EP20966372.3A EP4239827A4 (en) 2020-12-23 2020-12-23 CHARGING SYSTEM AND VEHICLE
CN202080008185.4A CN113330672B (zh) 2020-12-23 2020-12-23 一种充电系统和汽车
PCT/CN2020/138586 WO2022133793A1 (zh) 2020-12-23 2020-12-23 一种充电系统和汽车
US18/327,111 US20230307928A1 (en) 2020-12-23 2023-06-01 Charging system, charging method, and vehicle

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/CN2020/138586 WO2022133793A1 (zh) 2020-12-23 2020-12-23 一种充电系统和汽车

Related Child Applications (1)

Application Number Title Priority Date Filing Date
US18/327,111 Continuation US20230307928A1 (en) 2020-12-23 2023-06-01 Charging system, charging method, and vehicle

Publications (1)

Publication Number Publication Date
WO2022133793A1 true WO2022133793A1 (zh) 2022-06-30

Family

ID=77413321

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2020/138586 WO2022133793A1 (zh) 2020-12-23 2020-12-23 一种充电系统和汽车

Country Status (4)

Country Link
US (1) US20230307928A1 (zh)
EP (1) EP4239827A4 (zh)
CN (1) CN113330672B (zh)
WO (1) WO2022133793A1 (zh)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2024068075A1 (de) * 2022-09-27 2024-04-04 Robert Bosch Gmbh Gleichspannungswandler, elektrofahrzeug und verfahren zum betreiben eines gleichspannungswandlers

Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106936184A (zh) * 2017-03-14 2017-07-07 深圳威迈斯电源有限公司 一种车载充电机和dcdc的集成电路
CN110040028A (zh) * 2019-04-15 2019-07-23 创驱（上海）新能源科技有限公司 一种车载充电机和dcdc转换装置的集成控制电路
CN110289667A (zh) * 2019-08-05 2019-09-27 苏州博沃创新能源科技有限公司 大功率集成式车载充电机与车载dc/dc电路及控制方法
CN210669899U (zh) * 2019-10-24 2020-06-02 深圳市高斯宝电气技术有限公司 一种集成车载dc/dc转换器的车载双向充电机电路
KR20200061672A (ko) * 2018-11-26 2020-06-03 대우전자부품(주) 전기자동차용 배터리 통합 충전 제어 장치
CN111251916A (zh) * 2019-09-23 2020-06-09 华为技术有限公司 一种双输出端口充电电路
CN210970721U (zh) * 2019-08-28 2020-07-10 比亚迪股份有限公司 电动汽车及其车载充电机
CN111404387A (zh) * 2020-03-30 2020-07-10 上海电气集团股份有限公司 车载充电机和车载dc/dc的集成电路、电动汽车

Family Cites Families (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5808879A (en) * 1996-12-26 1998-09-15 Philips Electronics North America Corporatin Half-bridge zero-voltage-switched PWM flyback DC/DC converter
CN102299631A (zh) * 2011-08-30 2011-12-28 南京邮电大学 一种全桥软开关直流变换器
CN205666757U (zh) * 2016-05-19 2016-10-26 山东大学 基于三端口全桥dc/dc变换器的零功率电流控制系统及储能系统
CN207156960U (zh) * 2017-07-11 2018-03-30 深圳市永联科技股份有限公司 一种集成dc/dc转换器的车载充电机主电路及其控制环路
CN107623365A (zh) * 2017-09-30 2018-01-23 深圳威迈斯电源有限公司 一种带逆变功能的三端口充电机
TWI664790B (zh) * 2017-12-22 2019-07-01 財團法人工業技術研究院 分散式單級車載充電裝置及其方法
CN110198862A (zh) * 2018-09-18 2019-09-03 深圳欣锐科技股份有限公司 集成车载充电机电路及制造方法、集成车载充电机
CN209389954U (zh) * 2019-01-30 2019-09-13 广州工程技术职业学院 三电平半桥型变换器
WO2020215279A1 (zh) * 2019-04-25 2020-10-29 深圳欣锐科技股份有限公司 过压保护控制电路及相关设备
WO2021002875A1 (en) * 2019-07-03 2021-01-07 Rompower Technology Holdings, Llc Self-adjusting current injection technology
CN111555638A (zh) * 2020-04-07 2020-08-18 华为技术有限公司 一种电源变换器、充电机、充电系统及方法

Patent Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106936184A (zh) * 2017-03-14 2017-07-07 深圳威迈斯电源有限公司 一种车载充电机和dcdc的集成电路
KR20200061672A (ko) * 2018-11-26 2020-06-03 대우전자부품(주) 전기자동차용 배터리 통합 충전 제어 장치
CN110040028A (zh) * 2019-04-15 2019-07-23 创驱（上海）新能源科技有限公司 一种车载充电机和dcdc转换装置的集成控制电路
CN110289667A (zh) * 2019-08-05 2019-09-27 苏州博沃创新能源科技有限公司 大功率集成式车载充电机与车载dc/dc电路及控制方法
CN210970721U (zh) * 2019-08-28 2020-07-10 比亚迪股份有限公司 电动汽车及其车载充电机
CN111251916A (zh) * 2019-09-23 2020-06-09 华为技术有限公司 一种双输出端口充电电路
CN210669899U (zh) * 2019-10-24 2020-06-02 深圳市高斯宝电气技术有限公司 一种集成车载dc/dc转换器的车载双向充电机电路
CN111404387A (zh) * 2020-03-30 2020-07-10 上海电气集团股份有限公司 车载充电机和车载dc/dc的集成电路、电动汽车

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See also references of EP4239827A4 *

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2024068075A1 (de) * 2022-09-27 2024-04-04 Robert Bosch Gmbh Gleichspannungswandler, elektrofahrzeug und verfahren zum betreiben eines gleichspannungswandlers

Also Published As

Publication number Publication date
CN113330672A (zh) 2021-08-31
CN113330672B (zh) 2022-09-09
EP4239827A1 (en) 2023-09-06
US20230307928A1 (en) 2023-09-28
EP4239827A4 (en) 2024-01-17

Similar Documents

Publication Publication Date Title
WO2021077757A1 (zh) 一种变拓扑llc谐振变换器的宽增益控制方法
WO2021103415A1 (zh) 一种基于倍压整流电路的高增益准谐振dc-dc变换器
CN108028605B (zh) 具有保持操作的转换器
WO2021042773A1 (zh) 一种llc谐振变换器及控制方法
US7557546B2 (en) Unidirectional DC-DC converter
Fathy et al. A novel quasi-resonant snubber-assisted ZCS-PWM DC-DC converter with high frequency link
Wu et al. Soft-switching bidirectional isolated full-bridge converter with active and passive snubbers
EP0415923B2 (en) High efficiency converter
US5991171A (en) DC-to-DC converters
JP5397024B2 (ja) スイッチング電源装置、スイッチング電源制御回路およびスイッチング電源装置の制御方法
WO2020248472A1 (zh) 不对称半桥变换器及控制方法
JP2003324956A (ja) 直列共振型ブリッジインバータ回路の制御方法及び直列共振型ブリッジインバータ回路
KR20180004675A (ko) 보조 lc 공진 회로를 갖는 양방향 컨버터 및 그 구동 방법
KR100732612B1 (ko) 하이브리드 자동차용 고효율 강압형 직류-직류 컨버터
WO2022133793A1 (zh) 一种充电系统和汽车
US20150009716A1 (en) Power conversion device and method for driving same
Zhang et al. LLC resonant DC/DC converter with current-driven synchronized voltage-doubler rectifier
Shimada et al. Two novel control methods expanding input-output operating range for a bi-directional isolated DC-DC converter with active clamp circuit
WO2023010233A1 (zh) 一种变换器及变换器的控制方法
JP4093116B2 (ja) 力率改善コンバータ
TWM597537U (zh) Llc諧振轉換器
Yin et al. A new ZVS-PWM current-fed full-bridge converter with full soft-switching load range
JP7024137B2 (ja) 直流電圧変換回路およびスイッチング電源装置
CN216216540U (zh) 一种用于电动汽车充电器的pwm控制串联谐振变换器
Xuewei et al. Novel interleaved bidirectional snubberless naturally clamped zero current commutated soft-switching current-fed full-bridge voltage doubler for fuel cell vehicles

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 20966372

Country of ref document: EP

Kind code of ref document: A1

ENP Entry into the national phase

Ref document number: 2020966372

Country of ref document: EP

Effective date: 20230601

NENP Non-entry into the national phase

Ref country code: DE