WO2021227813A1

WO2021227813A1 - Antenna apparatus and electronic device

Info

Publication number: WO2021227813A1
Application number: PCT/CN2021/088923
Authority: WO
Inventors: 张帅; 雍征东
Original assignee: 西安电子科技大学; Oppo广东移动通信有限公司
Priority date: 2020-05-12
Filing date: 2021-04-22
Publication date: 2021-11-18

Abstract

The present application provides an antenna apparatus and an electronic device. The antenna apparatus comprises: multiple antenna units arranged at intervals, multiple decoupling networks, a decoupling transmission line, and a grounding layer. The multiple decoupling networks correspond one-to-one to the multiple antenna units. Each decoupling network comprises a closed-loop structure, and a first transmission line and a second transmission line connected to the closed-loop structure. The closed-loop structure is provided with a first output port and a second output port. The first transmission line is used for being connected to a radio frequency chip. One end of the second transmission line is connected to the first output port, and the other end is connected to the corresponding antenna unit. The decoupling transmission line is connected between the second output ports of adjacent decoupling networks. The grounding layer and the multiple decoupling networks are stacked at intervals. A slot is formed in the grounding layer, and at least a part of the slot overlaps the closed-loop structures. The electronic device comprises the antenna apparatus.

Description

Antenna device and electronic equipment

【Technical Field】

This application relates to the field of antenna decoupling technology, and in particular to an antenna device, an electronic device having the antenna device, and a decoupling method for the antenna device.

【Background technique】

Antennas can efficiently transmit and receive electromagnetic waves and are an indispensable part of wireless communication systems. However, with the advancement of science and technology, it is difficult for a single antenna to meet the ever-increasing performance requirements. In order to improve the poor directivity and low radiation gain of a single antenna unit, several antennas with the same radiation characteristics can be arranged according to a certain geometric structure to form an array antenna, thereby enhancing the antenna's radiation performance and generating more flexible directions Figure to meet the needs of different scenarios.

[Summary of the invention]

An aspect of the present application provides an antenna device including: a plurality of antenna units arranged at intervals, a plurality of decoupling networks, a decoupling transmission line, and a ground layer. Wherein, a plurality of decoupling networks corresponds to the plurality of antenna units one-to-one, and each of the decoupling networks includes a closed-loop structure and a first transmission line and a second transmission line connected to the closed-loop structure; the closed-loop structure There are a first output port and a second output port, the first transmission line is used to connect with the radio frequency chip, one end of the second transmission line is connected to the first output port, and the other end is connected to the corresponding antenna unit; decoupling The transmission line is connected between the second output ports of adjacent decoupling networks; the ground layer is overlapped with the plurality of decoupling networks at intervals, the ground layer is provided with slots, and at least a part of the slots is connected to the The closed loop structure overlaps.

Another aspect of the present application provides an electronic device including a housing, a display screen assembly, a radio frequency chip, and an antenna device. Wherein, the display screen assembly is connected to the housing and forms an accommodating space with the housing; the radio frequency chip is arranged in the accommodating space; and the antenna device is at least partially arranged in the accommodating space. The antenna device includes a plurality of antenna units arranged at intervals, a plurality of decoupling networks, a decoupling transmission line and a ground layer. Wherein, a plurality of decoupling networks corresponds to the plurality of antenna units one-to-one, and each of the decoupling networks includes a closed-loop structure and a first transmission line and a second transmission line connected to the closed-loop structure; the closed-loop structure There are a first output port and a second output port, the first transmission line is used to connect with the radio frequency chip, one end of the second transmission line is connected to the first output port, and the other end is connected to the corresponding antenna unit; decoupling The transmission line is connected between the second output ports of adjacent decoupling networks; the ground layer is overlapped with the plurality of decoupling networks at intervals, the ground layer is provided with slots, and at least a part of the slots is connected to the The closed loop structure overlaps.

The antenna device of the present application introduces the concept of a decoupling network under the antenna unit, without changing the structure of the array antenna unit, and only needs to configure the length of the decoupling transmission line and the S parameters of the three-port network to accurately define the antenna unit. The degree of coupling between the antenna elements can reduce the mutual coupling between the antenna elements, expand the scanning angle, and increase the scanning gain. Further, the power division ratio of the directional power divider can be calculated according to the magnitude of the isolation before decoupling, and then the characteristic impedance of each branch of the power divider can be determined according to the formula, and then the width of the transmission line corresponding to the characteristic impedance can be calculated, so that Make a power divider. Based on this method, the isolation of the multi-antenna system can be improved. In addition, the decoupling network of the present application includes a closed-loop structure. The closed-loop structure has first and second output ports. Slots are provided on the antenna floor, and at least a part of the slots overlap the closed-loop structure, so that the power divider can be The interference effects between the first output port and the second output port are equal in magnitude and inverted and cancel each other out, so that the first and second output ports will no longer affect each other, thus significantly improving the two main components of the power splitter. Isolation between two output ports. In addition, there is no need to provide an isolation resistor between the two output ports of the main body of the power splitter of the present application, which can reduce the insertion loss.

【Explanation of the drawings】

In order to more clearly describe the technical solutions in the embodiments of the present application, the following will briefly introduce the drawings that need to be used in the description of the embodiments. Obviously, the drawings in the following description are only some embodiments of the present application. For those of ordinary skill in the art, without creative work, other drawings can be obtained based on these drawings, among which:

FIG. 1 is a schematic structural diagram of an electronic device according to an embodiment of the present application;

2 is a schematic diagram of the decoupling principle of the array antenna according to an embodiment of the present application;

FIG. 3 is a schematic structural diagram of an array antenna according to an embodiment of the present application;

4 is a schematic flowchart of a decoupling method for an array antenna according to an embodiment of the present application;

FIG. 5 is a schematic structural diagram of an electronic device according to an embodiment of the present application;

Fig. 6 is a bottom view of the antenna device according to an embodiment of the present application;

FIG. 7 is a schematic diagram of the layered structure of two antenna units of the antenna device according to an embodiment of the present application;

FIG. 8 is a schematic diagram of an antenna device according to another embodiment of the present application;

FIG. 9 is a top view of an antenna device according to another embodiment of the present application;

Fig. 10 is a front view of the two antenna units in Fig. 9, in which the substrate of the antenna device is omitted;

FIG. 11 is a three-dimensional schematic diagram of an antenna unit in FIG. 9, in which the substrate of the antenna device is omitted;

Figure 12 shows the isolation comparison curve of the antenna unit before and after connecting the decoupling network;

Figure 13 shows the reflection parameter curve of an isolated antenna unit before decoupling;

Figure 14 shows the reflection parameter curve of the antenna unit after decoupling;

Figure 15 shows the comparison curve of the gain sweep of the antenna device before and after the decoupling network is connected, when the beam is scanned to 0°;

Figure 16 shows the comparison curve of the gain sweep of the antenna device when the beam is scanned to 45° before and after connecting the decoupling network;

Figure 17 shows the comparison curve of the gain sweep of the antenna device when the beam is scanned to 50° before and after connecting the decoupling network;

Figure 18 shows the transmission coefficient curve of the decoupling network; and

Figure 19 shows the reflection parameters of the decoupling network.

【Detailed ways】

The following will clearly and completely describe the technical solutions in the embodiments of the present application in conjunction with the drawings in the embodiments of the present application. Obviously, the described embodiments are only a part of the embodiments of the present application, rather than all the embodiments. Based on the embodiments in this application, all other embodiments obtained by those of ordinary skill in the art without creative work shall fall within the protection scope of this application.

The reference to "embodiments" herein means that a specific feature, structure, or characteristic described in conjunction with the embodiments may be included in at least one embodiment of the present application. The appearance of the phrase in various places in the specification does not necessarily refer to the same embodiment, nor is it an independent or alternative embodiment mutually exclusive with other embodiments. Those skilled in the art clearly and implicitly understand that the embodiments described herein can be combined with other embodiments.

Array antennas, especially small-pitch array antennas, have the problem of strong mutual coupling. The mutual coupling between the antenna elements affects the matching characteristics and spatial radiation characteristics of the antenna elements and their arrays to a large extent, and the specific manifestations are as follows.

(1) Pattern: The distribution of the current on the antenna changes under the action of mutual coupling, causing part of the radiated energy to be further coupled to other antenna elements, part of the coupling energy is absorbed by the terminal load and consumed, and the other part of the energy will be Radiate again. Therefore, the antenna pattern will be distorted. The termination load mentioned here is a parameter equivalent to the back end of the antenna feed; when drawing the equivalent circuit, the entire back end of the antenna feed can be replaced by a resistor, which can be called a termination load .

(2) Input impedance: Affected by mutual coupling, the input impedance of the antenna unit in the array will change, and is different from the input impedance of the antenna unit in an isolated environment, so the matching situation of the antenna unit in each array is different and the matching characteristics will be affected .

(3) Gain: There is heat loss and reflection loss caused by impedance mismatch in the antenna unit, so that the radiation power of the antenna is smaller than the transmission power, and the reflection coefficient will change under the action of mutual coupling, so the gain of the antenna affected.

In related technologies, the following five methods are usually used to solve the influence of mutual coupling effects on the antenna unit's pattern, input impedance, gain and other characteristics: DGS-Defected Ground Structure (DGS-Defected Ground Structure) decoupling method, neutralization line Method (NLT-Neutralization Line Technique) decoupling method, band-stop filter decoupling method, electromagnetic band gap structure (EBG, Electromagnetic Band Gap) decoupling method, metamaterial decoupling method (MDT, Metamaterial Decoupling Technique).

However, the above methods are all researches on the method of eliminating coupling between antenna elements, and the coupling effect between antennas cannot be precisely defined and controlled.

This application provides an electronic device. The array antenna of the electronic device can customize the coupling effect between the antennas, and realize the control of the radiation pattern of the antenna unit through the design of the coupling effect, such as widening the scanning angle and improving the scanning Gain, eliminate scanning blind spots, etc.

The electronic device may be a mobile phone, a tablet computer, a PDA (Personal Digital Assistant), a POS (Point of Sales, sales terminal), a car computer, a CPE (Customer Premise Equipment, customer front equipment) and other terminal devices. The following uses a mobile phone as an example to introduce this application.

As shown in Figure 1, the mobile phone 100 may include: an RF (Radio Frequency) circuit 101, a memory 102, a central processing unit (CPU) 103, a peripheral interface 104, an audio circuit 105, a speaker 106, and power management The chip 107, an input/output (I/O) subsystem 108, a touch screen 109, other input/control devices 110, and an external port 111 communicate through one or more communication buses or signal lines 112.

It should be understood that the illustrated mobile phone is only an example of an electronic device, and the mobile phone 100 may have more or fewer components than those shown in the figure, may combine two or more components, or may have Different component configurations. The various components shown in the figure may be implemented in hardware, software, or a combination of hardware and software including one or more signal processing and/or application specific integrated circuits.

The following describes the components of the mobile phone in detail with reference to Figure 1:

The RF circuit 101 is mainly used to establish communication between the mobile phone and the wireless network (ie, the network side), and realize the data reception and transmission between the mobile phone and the wireless network. For example, sending and receiving short messages, emails, etc. Specifically, the RF circuit 101 receives and transmits RF signals, which are also called electromagnetic signals. The RF circuit 101 converts electrical signals into electromagnetic signals or converts electromagnetic signals into electrical signals, and communicates with communication networks and other equipment through the electromagnetic signals. To communicate. The RF circuit 101 may include known circuits for performing these functions, including but not limited to an antenna system with an antenna array, an RF transceiver, one or more amplifiers, a tuner, one or more oscillators, digital signal processing Device, CODEC (COder-DECoder, codec) chipset, subscriber identity module (Subscriber Identity Module, SIM), etc.

The memory 102 can be accessed by the CPU 103, the peripheral interface 104, etc. The memory 102 can include a high-speed random access memory, and can also include a non-volatile memory, such as one or more disk storage devices, flash memory devices, or other volatile Sexual solid-state storage devices.

The central processing unit 103 executes various functional applications and data processing of the electronic device by running software programs and modules stored in the memory 102.

The peripheral interface 104 can connect the input and output peripherals of the device to the CPU 103 and the memory 102.

The I/O subsystem 108 can connect the input and output peripherals on the device, such as the touch screen 109 and other input/control devices 110, to the peripheral interface 104. The I/O subsystem 108 may include a display controller 1081 and one or more input controllers 1082 for controlling other input/control devices 110. Among them, one or more input controllers 1082 receive electrical signals from other input/control devices 110 or send electrical signals to other input/control devices 110, and other input/control devices 110 may include physical buttons (press buttons, rocker buttons, etc.) ), dial, slide switch, joystick, click wheel. It is worth noting that the input controller 1082 can be connected to any of the following: a keyboard, an infrared port, a USB interface, and a pointing device such as a mouse.

The touch screen 109 is an input interface and an output interface between the user terminal and the user, and displays visual output to the user. The visual output may include graphics, text, icons, videos, and the like.

The display controller 1081 in the I/O subsystem 108 receives electrical signals from the touch screen 109 or sends electrical signals to the touch screen 109. The touch screen 109 detects the contact on the touch screen, and the display controller 1081 converts the detected contact into interaction with the user interface object displayed on the touch screen 109, that is, realizes human-computer interaction. The user interface object displayed on the touch screen 109 can be running The icon of the game, the icon of connecting to the corresponding network, etc. It is worth noting that the device may also include an optical mouse, which is a touch-sensitive surface that does not display visual output, or is an extension of the touch-sensitive surface formed by a touch screen.

The audio circuit 105 is mainly used to receive audio data from the peripheral interface 104, convert the audio data into an electric signal, and send the electric signal to the speaker 106.

The speaker 106 is used to restore the voice signal received by the mobile phone 100 from the wireless network through the RF circuit 101 into sound and play the sound to the user.

The power management chip 107 is used to perform power supply and power management for the hardware connected to the CPU 103, the I/O subsystem 108 and the peripheral interface 104.

The following describes the array antenna in the antenna system of the RF circuit 101 of the electronic device. The array antenna usually includes a plurality of closely-arranged antenna units, and in at least two adjacent antenna units, each antenna unit is connected to the feed through a matching network. In the description of this application, "a plurality of" means at least two, such as two, three, etc., unless otherwise specifically defined.

In this embodiment, two

adjacent antenna units

10 and 20 are used as examples to introduce the present application, where the antenna unit 10 may be referred to as the first antenna unit 10, and the antenna unit 20 may be referred to as the second antenna unit 20. As shown in FIG. 2, the antenna unit 10 and the antenna unit 20 are adjacent to each other. The radiation characteristics of the antenna unit 10 and the antenna unit 20 may be the same or different. The antenna unit 10 can receive the excitation current from the feed (radio frequency transceiver) of the electronic device, and after amplifying, filtering, matching and tuning, the antenna unit 10 is excited to resonate at the corresponding frequency, thereby generating an electromagnetic wave signal of the corresponding frequency, which is the same frequency as the free space. The electromagnetic wave signal coupling realizes signal transmission; the antenna unit 10 can also resonate with the antenna unit of the corresponding frequency under the excitation of the excitation signal to couple the electromagnetic wave signal of the same frequency from the free space, thereby forming an induced current on the antenna unit 10, and the induced current is filtered , After amplifying, enter the radio frequency transceiver.

The array antenna also includes a decoupling structure. Among them, the decoupling structure includes a decoupling network and a decoupling transmission line connected to the decoupling network. Specifically, the decoupling networks corresponding to two

adjacent antenna units

10 and 20 are connected to each other, wherein the antenna unit 10 corresponds to the first decoupling network 30, and the antenna unit 20 corresponds to the second decoupling network 30. '. Both the first decoupling network 30 and the second decoupling network 30' are three-port networks. The first decoupling network 30 has an input port (a ₁ , b ₁ _{) connected to the feed, an output port (a 2} , b ₂ ) connected to the antenna unit 10, and a decoupling port used to connect to the second decoupling network 30 ′ (a ₃ ,b ₃ ). Second decoupling network 30 'having an input port (a connector feeds' _{_1,} b' _1), an output port connected to the antenna unit (a 20 is the _{_'2,} b' ₂₎ and means for connecting the first decoupling network 30 Decoupling port (a' ₃ ,b' ₃ ). _{_{Wherein, a 1, a 2, a}} 3, a '1, a' 2 , and a _'3 is the incident voltage wave _{_{amplitude, b 1, b 2, b}} 3, b' 1, b '2 and b' ₃ is reflected The amplitude of the voltage wave. It is worth mentioning that the “input port” and “output port” in the embodiment of the present application are only named from the angle of the antenna unit 10 transmitting signals. It is understandable that the antenna unit 10 can also receive signals. In this case, the aforementioned "output port" can be used as an input port, and the aforementioned "input port" can be used as an output port, that is, the "input port" and "output port" in this application. The naming does not limit the attributes of the port. The transmission line of length d ₁ in FIG. 2 forms an output port (a ₂ , b ₂ ), and has an impedance Z ₂ . A transmission line of length d ₂ forming the output port _{_{(a '2, b' 2}} ), and having an impedance Z _2. Among them, d ₁ and d ₂ can be equal. Decoupling of length d of the transmission line ₅ is connected to a first port coupled to the decoupling network 30 (a _{_3,} b ₃₎ and the second decoupling network 30 'is coupled to port _{_{(a' 3, b '3}} ), and an impedance Z ₃ . Among them, the first decoupling network 30 and the decoupling transmission line-shaped success divider are used to distribute _{the power input from the input ports (a 1} , b ₁ ) of the first decoupling network 30 to the power divider according to the power division ratio of the power divider. The first antenna unit 10 and the decoupling transmission line. Second decoupling network 30 'is coupled to the transmission line and the success splitter to decoupling from the second network 30' the input port _{_{(a '1, b' 1}} ) is assigned to a second power input in accordance with the predetermined ratio The antenna unit 30 and the decoupling transmission line 33 cancel the mutual coupling between the two

antenna units

10 and 20.

It should be pointed out that the _{transmission line with a length of d 1} in Figure 2 also shows a transmission line with impedance Z ₂ , but these two transmission lines correspond to the same wire in physical objects; similarly, the transmission line _{with a length of d 2} , The decoupling transmission line of length d ₅ should also be understood in the same way.

As shown in FIG. 3, it is a schematic diagram of a decoupling structure for an array antenna according to an embodiment of the present application, in which at least a first decoupling network 30, a second decoupling network 30', and a decoupling transmission line 33 connected therebetween can be formed This application is used for the decoupling structure of the array antenna. In addition, the decoupling structure and the array antenna connected to it can also form the antenna device of the present application.

The following takes the first decoupling network 30 corresponding to the antenna unit 10 and the second decoupling network 30' corresponding to the antenna unit 20 in FIG. The first decoupling network 30 is the same.

Specifically, the first decoupling network 30 is a three-port network. In some embodiments, the three-port network includes a closed loop structure 34 and a first transmission line 31 and a second transmission line 32 connected to the closed loop structure 34. The closed loop structure 34 is provided with a first output port and a second output port. The first transmission line 31 is used to connect to the feed source 40. One end of the second transmission line 32 is connected to the first output port, and the other end is connected to the corresponding antenna unit 10.

The closed-loop structure 34 may be a power divider, including a first branch 341, a second branch 342, and a microstrip connection line 343. The first end of the first branch 341 and the first end of the second branch 342 are connected to the same end of the first transmission line 31, and the second end of the first branch 341 forms a first output port. The second end of the second branch 342 forms a second output port. Among them, the second output port is the decoupling port of the first decoupling network 30. The lengths of the first branch 341 and the second branch 342 are equal, or the length difference between the first branch 341 and the second branch 342 is equal to the wavelength, so that the phases of the two output ports of the power splitter can be kept the same. The microstrip connection line 343 is connected between the first output port and the second output port to form a closed structure, so that the confluence of the two signals is equal in amplitude and inverted to achieve superposition and cancellation, that is, at the confluence of the two signals , The distance traveled by the two signals is double the wavelength. The first branch 341, the second branch 342, and the microstrip connecting line 343 are connected end to end in turn to form a closed shape. The closed shape power divider is matched with the slot opened on the ground layer of the antenna unit 10, and it is a closed structure 34 The interference between the first output port and the second output port affects the same amplitude and reverse, and then cancels each other, thereby improving the isolation between the first output port and the second output port of the enclosed structure 34. In some embodiments, the first branch 341, the second branch 342, and the microstrip connecting line 343 are all arc-shaped, and then surround a circular ring. In some other embodiments, the first branch 341, the second branch 342 and the microstrip connecting line 343 may also be enclosed in an elliptical ring or a polygon. In some embodiments, the closed-loop structure 34 may have an axisymmetric pattern.

The first end of the first transmission line 31 is connected to the first ends of the first branch 341 and the second branch 342, and the second end of the first transmission line 31 forms an input port of the first decoupling network 30. The first end of the second transmission line 32 is connected to the second end of the first branch 341 (ie, the first output port of the closed loop structure 34 ), and the second end of the second transmission line 32 forms the output port of the first decoupling network 30. It is pointed out here that the first end and the second end of a certain transmission line mentioned in the text refer to the two opposite ends of the transmission line.

The second decoupling network 30' may also be a three-port network, including a closed loop structure 34' and a first transmission line 31' and a second transmission line 32' connected to the closed loop structure 34'.

The closed-loop structure 34' can also be a power divider, including a first branch 341', a second branch 342', and a microstrip connection line 343'. The first end of the first branch 341' and the first end of the second branch 342' are connected to the same end of the first transmission line 31', and the second end of the first branch 341' forms a first output port. The second end of the second branch 342' forms a second output port. The microstrip connection line 343' is connected between the first output port and the second output port to form a closed structure, so that the confluence of the two signals is equal in amplitude and inverted, so as to realize superposition and cancellation, that is, when the two signals are converged At this point, the distance traveled by the two signals is twice the wavelength.

The first end of the first transmission line 31' is connected to the first ends of the first branch 341' and the second branch 342', and the second end of the first transmission line 31' forms the input port of the second decoupling network 30'. The first end of the second transmission line 32' is connected to the second end of the first branch 341' (that is, the first output port of the closed loop structure 34'), and the second end of the second transmission line 32' forms a second decoupling network 30 'The output port. It is pointed out here that the first end and the second end of a certain transmission line mentioned in the text refer to the two opposite ends of the transmission line.

The first end of the decoupling transmission line 33 is connected to the decoupling port (ie, the second output port) of the first decoupling network 30, and the second end of the decoupling transmission line 33 is connected to the decoupling port of the second decoupling network 30' (Ie, the second output port), thereby connecting the first decoupling network 30 and the second decoupling network 30' together.

The terms "first", "second", and "third" in this application are only used for descriptive purposes, and cannot be understood as indicating or implying relative importance or implicitly indicating the number of indicated technical features. Thus, the features defined with “first”, “second”, and “third” may explicitly or implicitly include at least one of the features.

The following describes the current trend of the first decoupling network 30: the current flows from the feed source 40 from the first end of the first transmission line 31 (ie, the input port of the first decoupling network 30) into the first transmission line 31, The second end of the transmission line 31 is divided into two paths to flow to the first branch 341 and the second branch 342 according to the power division ratio. The current entering the first branch 341 flows from the first output port of the enclosed structure 34 into the second transmission line 32, and from the second end of the second transmission line 32 (ie, the output port of the first decoupling network 30) through the antenna unit 10 The feed port enters the antenna unit 10. The current entering the second branch 342 flows into the decoupling transmission line 33 from the second output port of the enclosed structure 34, thereby realizing the decoupling effect. The foregoing embodiment is only described from the aspect of power distribution performed by the power divider. It is understandable that the power divider of the foregoing embodiment can be used for power synthesis, and its current trend is not repeated here.

The decoupling transmission line 33 in the embodiment of the present application is used to transmit signals to cancel the mutual coupling between the two

antenna units

10 and 20. The degree of coupling between the two

antenna units

10 and 20 can be determined by the scattering parameters (i.e., S parameters) of the first decoupling network 30 and the second decoupling network 30' and the length of the decoupling transmission line 33. For example, if the coupling degree between the two

antenna units

10 and 20 is required to reach the preset coupling degree D, the S parameter of the three-port network and the length of the decoupling transmission line 33 can be configured so that the distance between the

antenna units

10 and 20 is The coupling degree satisfies the preset coupling degree D.

It is easy to understand that when the first decoupling network 30 and the second decoupling network 30' adopt the same structure, their S parameters are also the same. Therefore, when the first decoupling network 30 and the second decoupling network 30' are the same, the degree of coupling between the two antenna units 10, 20 is comparable to that of the three-port network (the first decoupling network 30 or the second decoupling network 30'). The relationship between the S parameter of the net 30') and the length of the decoupling transmission line can be obtained in the following way:

The [S] matrix of the decoupling network is:

Among them, S ₁₁ , S ₂₂ , S ₃₃ are the reflection coefficients of the three ports when the three-port network exists alone; S ₁₂ is the power directly fed from the input port to the output port; S ₁₃ is the power fed from the input port to the decoupling port Power; S ₂₃ is the power fed from the decoupling port to the output port.

S ₁₁ , S ₂₂ , S ₃₃ and S _{23 can be} designed as 0, so that the S parameter matrix is:

At Ⅱ reference surface in FIG. 2, the three-port to port coupling network connection length d ₅ of decoupling the transmission line, S-parameters of the relationship six-port network composed of two three-port network is:

Among them, k is the wave number, e is the natural constant, and j is the sign of the imaginary number.

Write the matrix in formula (3) into block matrix form:

Rewrite formula (5) into the form of equations:

The formula (4) is abbreviated as:

[a ₂ ]=[Γ]·[b ₂ ] (7)

Substituting formula (7) into formula (6), we can get:

From the formula ② in formula (8), we can get:

[b ₂ ]={E-[S ₂₂ ][Γ]} ^-1 [S ₂₁ ][a ₁ ] (9)

Among them, E represents the identity matrix.

Substituting formula (9) into formula (8), formula ① can be obtained:

[b ₁ ]=[S ₁₁ ][a ₁ ]+[S ₁₂ ][Γ]{E-[S ₂₂ ][Γ]} ^-1 [S ₂₁ ][a ₁ ] (10)

From equation (10), it can be seen that the S-parameter matrix of the four-port network (1, 2, 1', 2') formed after two three-port networks are connected by a decoupling transmission line is:

S _Four-port =[S ₁₁ ]+[S ₁₂ ][Γ]{E-[S ₂₂ ][Γ]} ^-1 [S ₂₁ ] (11)

It is pointed out here that the four ports of the four-port network here refer to the four external ports (a ₁ ,b ₁ ), (a ₂ ,b ₂ ), (a' ₁ ,b' ₁ ) and (a' ₂ ,b' ₂ ).

Substituting the block matrix planned by equation (3) and equation (5) into equation (11), the new S-parameter matrix of the four-port network can be obtained as:

Adjust the port sequence of the four-port network to 1→1′→2→2′, then the formula (12) becomes:

Rewrite formula (13) into the form of a block matrix:

Suppose the S parameter matrix of the binary antenna array formed by the two antenna elements is:

In the formula (15), S _'12 is the intensity of two yuan initial isolation of the antenna, i.e., the intensity of two adjacent antenna element isolation when decoupling network is not connected between the 10 and the 20; S' _11, S _'21 and S' _22, respectively two adjacent antenna input reflection coefficient when the unit is not decoupling network connection between 10 and 20, the forward transmission coefficient (gain) and output reflection coefficients.

After the two three-port networks are connected together by a decoupling transmission line, the four-port network formed is connected with the two

antenna units

10 and 20 to form a two-port (1, 1') network. The S parameter matrix of the two-port network is:

[S]=[S ₁₁ ]+[S ₁₂ ][S _array ]{E-[S ₂₂ ][S _array ]} ^-1 [S ₂₁ ] (16)

It is pointed out here that the two ports of the two-port network here refer to the connection between the two three-port networks and the two

antenna units

10 and 20 respectively, and the remaining two are used to connect to the feeder. Ports (a ₁ ,b ₁ ) and (a' ₁ ,b' ₁ ).

Substituting the block matrix defined by equation (13) and equation (14) into equation (16), we can get:

It can be seen from formula (17) that

Wherein, S _'12 initial isolation of the intensity, i.e., two adjacent antenna elements 30 of the first and the second decoupling network 30 is not connected between the decoupling network 10 and 20' when the strength of the isolation.

It can be seen that by designing the length d _{5 of the} decoupling transmission line 33 and the S parameter of the three-port network, the degree of coupling between the antennas can be accurately defined. That is, when the required degree of coupling is preset, the above formula can be expressed as:

Therefore, the length d5 of the decoupling transmission line 33 and the S parameter of the three-port network can be configured so that the coupling degree between the

antenna units

10 and 20 meets the preset coupling degree.

In some embodiments, the first decoupling network 30 and the decoupling transmission line 33 can form a splitter. The second decoupling network 30' and the decoupling transmission line 33 can also form a splitter. In this case, the coupling degree between the two

antenna units

10 and 20 can be set to zero by configuring the length of the decoupling transmission line 33 and the power division ratio of the power divider.

The length of the decoupling transmission line 33 and the power division ratio of the power divider can be determined by the initial isolation between the two

antenna units

10 and 20, where the initial isolation is when the decoupling network is not connected between the two antenna units. The isolation. That is, in some embodiments, the power division ratio between the two

antenna elements

10 and 20 may be configured according to the initial isolation degree and the length of the decoupling transmission line 33 to zero the coupling degree between the two

antenna elements

10 and 20.

Specifically, the power division ratio of the power divider can be determined by the strength of the initial isolation between the two antenna elements (ie, S′ ₁₂ ). The length of the decoupling transmission line 33 can then be determined by the phase (φ′ ₁₂ ) of the initial isolation between the two

antenna elements

10 and 20.

For example, when a decoupling network is required to completely cancel the mutual coupling between the two

antenna units

10 and 20, the default coupling degree is set to 0, then

From equation (18), we can see:

in,

It is the power division ratio of the power divider, therefore, the S parameter of the decoupling network can be determined according to the power division ratio.

From equation (19), we can see that if

And φ ₁₂ =φ ₁₃ , then

It can be seen that the power division ratio of the power divider is configured to satisfy the relationship of formula (21) with the strength of the initial isolation of the two

antenna units

10 and 20, and the length of the decoupling transmission line 33 is configured to be equal to two The phases of the initial isolation of the two

antenna units

10 and 20 satisfy the relationship of formula (21), so that the coupling degree between the two

antenna units

10 and 20 can be set to zero.

Specifically, the intensity of the initial isolation S _'12 and the phase φ' ₁₂ are known, the relationship between wave number k and the wavelength λ are known, and therefore, wavelength λ represents the wavenumber k, and substituting into equation (21), can be Get the calculation formula of _{d 5:}

_{Therefore, after calculating the power division ratio of the power divider and the length d 5 of the} decoupling transmission line 33, a power divider with this power division ratio and a decoupling transmission line 33 with this length can be designed to achieve zero coupling. .

In some embodiments, the power division ratio of the power divider is related to the characteristic impedance of the first transmission line 31, the first branch 341 and the second branch 342. It can be seen from the above embodiment that the power division ratio of the power divider can be obtained according to the strength of the initial isolation. Therefore, the obtained power division ratio and the characteristic impedance of the first transmission line 31 can be used to determine the first branch 341 and the second branch. 342 characteristic impedance. Therefore, the characteristic impedance of the first branch 341 and the second branch 342 can be determined according to the characteristic impedance of the first transmission line 31 and the strength of the initial isolation.

Specifically, the first branch 341 of the characteristic impedance Z ₂ and the first characteristic transmission line impedance Z ₁ 31 and the power divider ratio (the intensity of the initial isolation of S _'12) satisfy the following relation:

Z ₂ =(1+|S' ₁₂ |)ⅹZ ₁ (23)

The second branch 342 of the characteristic impedance Z ₃ and the first transmission line characteristic impedance Z ₁ 31 and power splitter ratio (i.e., the intensity of the initial isolation of S _'12) satisfy the following relation:

Therefore, it can be seen from the above that the required power divider ratio of the power divider can be obtained through the preset coupling degree, and then the required characteristic impedance Z ₂ of the first branch 341 and the second branch 342 can be obtained according to the power ratio. the characteristic impedance Z _3, arranged so that the decoupling network first branch 341 and second branch 342, such that the characteristic impedance of the first branch 341 to meet the desired characteristic impedance Z _2, and a second branch satisfies the characteristic impedance of 342 The required characteristic impedance Z ₃ .

In some embodiments, the line width of the transmission line can be configured to make the characteristic impedance of the transmission line meet the requirements, that is, the line width of the first branch 341 is determined according to the characteristic impedance of the first branch 341. The line width of the second branch 342 is determined according to the characteristic impedance of the second branch 342. _{For example, after the characteristic impedance Z 2 of the} first branch 341 is obtained according to the above-mentioned relational expression, the line width of the first branch 341 can be configured such that its characteristic impedance satisfies the characteristic impedance Z ₂ . For example, after determining the required thickness of the first branch 341, the relative dielectric constant of the PCB board, and the thickness of the dielectric layer, according to the relationship between the characteristic impedance and the line width and the required characteristic impedance Z ₂ , that is The line width of the first branch 341 can be calculated. Therefore, the line width of the first branch 341 is configured according to the calculation result, thereby obtaining the first branch 341 _{having the above-mentioned characteristic impedance Z 2.}

Similarly, the line width of the second branch 342 can be configured to make the second branch 342 meet the above-mentioned required characteristic impedance Z ₃ . The line width of the second branch 342 can be calculated according to the relationship between the characteristic impedance and the line width and the required characteristic impedance Z ₃ . Therefore, the line width of the second branch 342 is configured according to the calculation result, thereby obtaining the second branch 342 _{having the above-mentioned characteristic impedance Z 3.}

In some embodiments, the input impedances of the feed ports of the

antenna units

10 and 20 are matched with 50Ω. Therefore, the second transmission line 32 is configured as three transmission lines with a length of 1/4λ, that is, the length of the second transmission line 32 is Configured to 3/4λ to match its impedance to 50Ω.

In combination with the above decoupling structure, this application also proposes a decoupling method for an antenna device, which may be the antenna device of any of the above embodiments. FIG. 7 is a schematic flowchart of a decoupling method for an antenna device according to an embodiment of the application.

As shown in FIG. 4, the decoupling method may mainly include the following operations S101-S105.

Operation S101: Obtain the strength of the initial isolation between the first antenna unit and the second antenna unit; where the initial isolation is that the first antenna unit and the second antenna unit are not connected to the first decoupling network and the second decoupling network The degree of isolation at the time.

Operation S102: Determine the power division ratio of the power divider according to the strength of the initial isolation.

Operation S103: distribute the power fed into the first decoupling network to the first antenna unit and the decoupling transmission line according to the power division ratio.

In some embodiments, the decoupling method further includes the following operations: obtaining the phase of the initial isolation; and determining the length of the decoupling transmission line according to the phase of the initial isolation.

In some embodiments, the degree of coupling between the first antenna unit and the second antenna unit is determined according to the length of the decoupled transmission line and the scattering parameters of the first three-port network and the second three-port network.

In some embodiments, the degree of coupling between the first antenna unit and the second antenna unit is determined according to the following relationship:

Wherein, S _'12 degrees of the intensity of the initial isolation between the first antenna element and second antenna elements, the initial isolation of a first antenna element and second antenna elements are not the first and second three-port three-port network connection Isolation in the network; S ₁₂ and S ₁₃ are the scattering parameters of the first three-port network; d ₅ is the length of the decoupling transmission line; k is the wave number, e is the natural constant, and j is the sign of the imaginary number.

In some embodiments, the length of the decoupling transmission line is set according to the phase of the initial isolation of the first antenna unit and the second antenna unit.

In some embodiments, the power division ratio of the power divider and the length of the decoupling transmission line are determined according to the aforementioned relationship (21). In some embodiments, the characteristic impedances of the first branch and the second branch are determined according to the characteristic impedance of the first transmission line and the strength of the initial isolation.

In some embodiments, the characteristic impedance of the first branch is determined according to the aforementioned relationship (23).

In some embodiments, the characteristic impedance of the second branch is determined according to the aforementioned relationship (24).

In some embodiments, the line width of the first branch is calculated according to the characteristic impedance of the first branch, and the line width of the second branch is calculated according to the characteristic impedance of the second branch.

In some embodiments, the length of the decoupling transmission line is determined according to the aforementioned relationship (22).

It is easy to understand that the relevant content described in the decoupling principle part of this application can be applied to the decoupling method, and will not be repeated here.

In some embodiments, the electronic device of the present application may be a mobile phone 100a as shown in FIG. Wherein, an accommodating space is formed between the housing 41 and the display screen assembly 50. Other electronic components of the mobile phone, such as the main board, battery, and antenna device 60, are all arranged in the accommodating space.

Specifically, the housing 41 may be made of plastic, glass, ceramic, fiber composite material, metal (for example, stainless steel, aluminum, etc.), or other suitable materials. The housing 41 shown in FIG. 5 is substantially rectangular with rounded corners. Of course, the housing 41 can also have other shapes, such as a circular shape, an oblong shape, an oval shape, and so on.

The display assembly 50 includes a display cover 51 and a display module 52. The display module 52 is attached to the inner surface of the display cover 51. The housing 41 is connected to the display cover 51 of the display assembly 50. Among them, the display cover 51 may be made of glass; the display module 52 may be an OLED flexible display structure, which may specifically include a substrate, a display panel (Panel), and auxiliary material layers, etc., in addition, the display module 52 and the display cover Structures such as a polarizing film can also be sandwiched between 51, and the detailed laminated structure of the display module 52 is not limited here.

The antenna device 60 may be completely contained in the housing 41, or may be embedded in the housing 41, and a part of the antenna device 60 may be exposed on the outer surface of the housing 41.

In some embodiments, the antenna device 60 may include a plurality of antenna units arranged at intervals, a plurality of decoupling networks, and a decoupling transmission line. The multiple decoupling networks correspond to the multiple antenna units one-to-one, and the decoupling transmission lines are connected between adjacent decoupling networks. Wherein, the decoupling network may be the decoupling network of any of the above embodiments.

In some embodiments, the multiple antenna elements of the antenna device 60 may be a four-element linear array as shown in FIG. 6, that is, there are four

antenna elements

10a, 20a, 10b, and 20b arranged in a straight line.

Specifically, with reference to FIG. 7, the antenna device 60 includes a first substrate 61, a second substrate 62, a third substrate 63, and a radio frequency chip 64 that are sequentially stacked in layers, and a plurality of antenna units formed on the first substrate 61 ( FIG. 8 only shows two

antenna elements

10a, 20a), and a plurality of metal layers 661-668 (among them, the metal layer 665 is the ground layer 665) formed on the first substrate 61 and the third substrate 63, pass through the first substrate 61 and the third substrate 63. The multiple feeders in the third substrate 63 and the second substrate 62 and the multiple decoupling networks (for example, the first decoupling network 30 and the second decoupling network 30') arranged in the third substrate 63 and connected to them Decoupling transmission line 33a between. Among them, multiple feeders, multiple decoupling networks, and multiple antenna units are in one-to-one correspondence. In this embodiment, the antenna unit 10a, the first decoupling network 30 and the corresponding feeder are introduced. The feeder is used to connect the corresponding antenna unit 10 a, the decoupling network 30 and the radio frequency chip 64. The decoupling transmission line 33a is used to connect the first decoupling network 30 and the second decoupling network 30' corresponding to the

adjacent antenna units

10a and 20a together to cancel the coupling between the

antenna units

10a and 20a. It can be grounded properly, and the antenna device 60 may also include other signal transmission lines.

The

antenna units

10a, 20a are used to send and receive radio frequency signals. As shown in Fig. 7, the two

antenna units

10a, 20a are spaced apart from each other. The

antenna units

10a, 20a are double-layer patch antennas, including

surface radiating plates

11a, 21a and

inner radiating plates

12a, 22a that are isolated from each other and correspond to each other one-to-one.

The first substrate 61 includes a first outer surface 611 and a first inner surface 612 that are oppositely disposed. The surface

layer radiating sheets

11 a and 21 a are arranged on the first outer surface 611, and the inner

layer radiating sheets

12 a and 22 a are arranged on the first inner surface 612. The

inner radiating fins

12a, 22a and the

surface radiating fins

11a, 21a are isolated by the first substrate 61, so that the

surface radiating fins

11a, 21a and the

inner radiating fins

12a, 22a are separated by a certain distance, so as to meet the performance of the antenna frequency band Require. The vertical projections of the

surface radiating sheets

11a, 21a and the

inner radiating sheets

12a, 22a on the first substrate 61 at least partially overlap.

The first substrate 61 may be made of thermosetting resin such as epoxy resin, thermoplastic resin such as polyimide resin, reinforcing material including glass fiber (or glass cloth, or glass fabric) and/or inorganic filler, and thermosetting resin and thermoplastic resin. Resin insulating materials (for example, prepreg, ABF (Ajinomoto Build-up Film), photosensitive dielectric (PID), etc.) are made. However, the material of the first substrate 61 is not limited to this. That is, a glass plate or a ceramic plate can also be used as the material of the first substrate 61. Optionally, liquid crystal polymer (LCP) with low dielectric loss can also be used as the material of the first substrate 61 to reduce signal loss.

In some embodiments, the first substrate 61 may be a prepreg. As shown in FIG. 7, the first substrate 61 includes three stacked prepregs. Among the three-layer prepregs of the first substrate 61,

metal layers

662 and 663 are respectively provided between adjacent prepregs. The first outer surface of the first substrate 61 is further provided with a metal layer 661, and the metal layer 661 is located on the same layer as the

surface radiation sheets

11a, 21a and insulated from each other. The first inner surface 612 of the first substrate 61 is provided with a metal layer 664, and the metal layer 664 is located on the same layer as the

inner radiating sheets

12a, 22a and insulated from each other. The metal layers 661, 662, 663, and 664 may be made of conductive materials such as metallic copper, aluminum, silver, tin, gold, nickel, lead, titanium, or their alloys. In this embodiment, the metal layers 661, 662, 663, and 664 are all copper layers.

The arrangement of the metal layer 661 reduces the difference between the copper spreading rate of the first outer surface 611 of the first substrate 61 and the copper spreading rate of other prepreg surfaces of the first substrate 61. During the manufacturing process of the first substrate 61, the copper spreading rate The reduction of the difference can reduce the generation of bubbles, thereby improving the manufacturing yield of the first substrate 61. In the same way, the arrangement of the metal layer 664 also reduces the difference between the copper spreading rate of the first inner surface 612 of the first substrate 61 and the copper spreading rate of other prepreg surfaces of the first substrate 61, so as to reduce the manufacturing process of the first substrate 61. The air bubbles are generated, thereby improving the manufacturing yield of the first substrate 61.

The first substrate 61 is also provided with grounding vias 613 penetrating through the first inner surface 612 and the first outer surface 611 to connect

different metal layers

661, 662, 663 and 664 to each other and further to the ground layer 665. Specifically, the conductive material may be completely filled in the ground via 613, or the conductive material may be formed along the wall of the ground via 613 to form a conductive layer. Among them, the conductive material may be copper, aluminum, silver, tin, gold, nickel, lead, titanium, or their alloys. The ground via 613 may have a cylindrical shape, an hourglass shape, a cone shape, or the like.

The second substrate 62 includes a first side surface 621 and a second side surface 622, wherein the first side surface 621 is stacked on the first inner surface 612 of the first substrate 61. The second substrate 62 may be the core layer of a PCB board, and is made of materials such as polyimide, polyethylene terephthalate, and polyethylene naphthalate. The second substrate 62 is provided with a ground via 623 and a feeder via 624 penetrating through the first side surface 621 and the second side surface 622.

The ground layer 665 is sandwiched between the second substrate 62 and the third substrate 63. The ground layer 665 is provided with a feeder via 665a. Referring to FIG. 6, a slot 665 b is also provided on the ground layer 665, and at least a part of the slot 665 b overlaps the closed loop structure 34. In some embodiments, the slot 665b may be enclosed in an axisymmetric pattern. The symmetry axis of the slot 665b overlaps the symmetry axis of the closed loop structure 34. In some embodiments, the slot 665b may be enclosed in a closed shape. In other embodiments, the slot 665b may include a closed-loop groove 665d and a strip-shaped groove 665c extending from the closed-loop groove 665d, and at least a part of the strip-shaped groove 665c overlaps the closed-loop structure 34. Wherein, at least a part of the strip groove 665c overlaps the microstrip connection line 343, and the microstrip connection line 343 is symmetrically arranged with respect to the strip groove 665c. The closed-loop structure 34 and the closed-loop groove 665d are both symmetrical with respect to the line where the strip-shaped groove 665c is located. The closed-loop groove 665d may have a closed shape such as a circular ring, an elliptical ring, a polygon, or a serpentine shape. Specifically, when the strip groove 665c is excited, the center surface of the strip groove 665c is opposite to an electric wall, and the end of the strip groove 665c is the closed loop groove 665d. When the signal enters the closed loop groove 665d from the strip groove 665c, it is divided into two paths of equal size. , Signals of opposite phase. At the position on the other side of the closed loop groove 665d opposite to the strip groove 665c, the two signals cancel each other out. In some embodiments, the length of the strip-shaped groove 665c may be 1/4λ, which is more favorable for adjusting the network matching characteristics.

The third substrate 63 includes a second outer surface 631 and a second inner surface 632 opposite to each other. The second inner surface 632 of the third substrate 63 is stacked on the second side surface 622 of the second substrate 62, and the ground layer 665 is sandwiched between the second side surface 622 and the second inner surface 632.

The formation material of the third substrate 63 may be the same as the material of the first substrate 61. In some embodiments, the third substrate 63 may be a prepreg and has a multilayer structure. As shown in FIG. 7, the third substrate 63 includes a three-layer prepreg. Among the three-layer prepregs of the third substrate 63,

metal layers

666 and 667 are provided between adjacent prepregs, which serve as feeder network and control line wiring layers, respectively. A metal layer 668 is provided on the second outer surface 631 of the third substrate 63, and the metal layer 668 and the radio frequency chip 64 are welded together. Among them, the metal layers 666, 667, and 668 may be made of conductive materials such as metallic copper, aluminum, silver, tin, gold, nickel, lead, titanium, or their alloys. In this embodiment, the metal layers 666, 667, and 668 are all copper layers.

The third substrate 63 is provided with wiring vias. The wiring via includes a ground via 633 to connect the

different metal layers

666, 667, and 668 to each other and further to the ground layer 665. The wiring vias also include a feeder via 634 for the feeder to pass through, and a signal via 635 for the control line to pass through. Similar to the ground via 613 on the first substrate 61, the wiring via on the third substrate 63 can be completely filled with conductive material, or a conductive layer can be formed on the wall of the hole. The shape of the various wiring vias can be cylindrical, hourglass, or cone-shaped.

The radio frequency chip 64 is disposed on the side of the third substrate 63 away from the first substrate 61, which is equivalent to the feed sources of the foregoing embodiment, such as the first feed source 40 and the second feed source 40'. When there are multiple feed sources, the multiple feed sources can be the same or different.

The feeder line includes a first feeder line 65 and a second feeder line 67. The decoupling networks 30, 30' are respectively connected between the corresponding first feeder 65 and the second feeder 67. One end of the first feeder 65 is arranged on a side of the third substrate 63 away from the second substrate 62 to connect to the radio frequency chip 64, and the other end extends into the third substrate 63, that is, passes through the feeder via 634 of the third substrate 63. Connected to the decoupling network 30. A part of the second feeder 67 is disposed in the third substrate 67 to connect to the decoupling network 30, and the other part penetrates the second substrate, that is, passes through the feeder via 624 of the second substrate 62 to connect the corresponding antenna unit 10a. Therefore, the radio frequency chip 64, the first feeder line 65, the decoupling network 30, the second feeder line 67, and the antenna unit 10 are connected in sequence to realize signal transmission between the antenna unit 10 and the radio frequency chip 64. The feeder is insulated from each metal layer, such as the metal layers 666, 667, 668 and the ground layer 665 in this embodiment.

In addition, other signal transmission lines are provided on the third substrate 63, such as a control line 68 and a power line 69. As shown in FIG. 7, the power cord 69 is disposed on the second outer surface 631 of the third substrate 63 and soldered on the radio frequency chip 64. The control line 68 is arranged between the prepreg of the third substrate 63 close to the radio frequency chip 64 and the adjacent prepreg, and passes through the signal via 635 on the prepreg to connect to the radio frequency chip 64.

In addition, the third substrate 63 is also used to carry multiple decoupling networks and decoupling transmission lines 33a, and the decoupling network may be the decoupling network of any of the foregoing embodiments. The first decoupling network 30 is connected between the corresponding first antenna unit 10 a and the radio frequency chip 64. The second decoupling network 30' is connected between the corresponding second antenna unit 20a and the radio frequency chip 64. The two ends of the decoupling transmission line 33a are respectively connected to the decoupling ports of the first decoupling network 30a and the second decoupling network 30a'. The first decoupling network 30 is a three-port network, including a closed loop structure 34, a first transmission line 31a, and a second transmission line 32a. After the two three-port networks are connected to the decoupling transmission line 33a, the distance between the two

antenna units

10a, 20a can be reduced Coupling. For example, after the signal from the radio frequency chip 64 is input to the first transmission line 31a through the first feeder 65, a part of it enters the second transmission line 32a through the first branch 341, and then is transmitted to the inner layer of the antenna unit 10a through the second feeder 67 for radiation. The other part of the sheet 12a enters the decoupling transmission line 33a through the second branch 342, and then is transmitted to the adjacent antenna unit 20a, thereby canceling the coupling between the two

antenna units

10a, 20a.

In some embodiments, the strip groove 665c opened on the ground layer 665 extends between the first output port and the second output port of the closed loop structure 34, and the first output port and the second output port are opposite to the strip groove 665c. symmetry. In addition, the microstrip connection line 343 is arranged in a circular arc shape, and the microstrip connection line 343 is symmetrical with respect to the strip groove 665c. Thereby, the interference effects between the first output port and the second output port of the power divider main body 34 can be inverted and cancel each other in equal amplitude, so that the first output port and the second output port will no longer affect each other. Therefore, the isolation between the two output ports of the main body of the power splitter can be significantly improved.

The degree of coupling between the two antenna elements 10a, 20a can be defined by the scattering parameters of the decoupling network and the length of the decoupling transmission line 33a. Specifically, as in the foregoing embodiment of the array antenna, the length d5 of the decoupling transmission line 33a of the decoupling network of the antenna device 60 in this embodiment, the S parameter of the decoupling network and the preset coupling degree satisfy the following relationship:

In some embodiments, the length of the decoupling transmission line 33a in the decoupling network and the power division ratio of the power divider are configured to zero the coupling degree between the two

antenna units

10a, 20a.

In some embodiments, the length of the decoupling transmission line 33a and the power division ratio of the power divider are configured according to the initial isolation between the two

antenna units

10a, 20a. Specifically, the power division ratio of the power divider is configured according to the strength of the initial isolation, and the length of the decoupling transmission line 33a is configured according to the phase of the initial isolation. For example, the relationship between the power division ratio of the power divider and the strength of the initial isolation, and the relationship between the length of the decoupling transmission line 33a and the phase of the initial isolation satisfy the aforementioned relational expressions (21) and (22).

In some embodiments, the power division ratio of the power divider can be specifically realized by configuring the characteristic impedance of the first branch 341 and the second branch 342. A first branch 341, for example, characteristic impedance Z ₂ of the first transmission line 31a and the characteristic impedance Z ₁ power divider ratio (initial isolation strength S _'12) satisfies the above relation (23) as well. The second branch 342 characteristic impedance Z ₃ 31a and the first transmission line characteristic impedance Z ₁ and the power dividing ratio (i.e. the initial isolation strength S _'12) satisfies the above relation (24).

As described in the foregoing antenna array embodiment, the characteristic impedance of the transmission line can be configured to meet the requirements by configuring the line width of the transmission line. For example, the line width of the first branch 341 is configured such that the first branch 341 meets the aforementioned required characteristic impedance Z ₂ . The line width of the second branch 342 is configured such that the second branch 342 meets the aforementioned required characteristic impedance Z ₃ .

The first decoupling network 30 and the decoupling transmission line 33 may be arranged on a layer of the third substrate 63, for example, the third substrate 63 is on the prepreg near the radio frequency chip 64 or on the prepreg in the middle. The first decoupling network 30 and the decoupling transmission line 33 shown in FIG. 7 are arranged on the prepreg with the third substrate 63 in the middle, that is, the same layer as the metal layer 666. The first decoupling network 30 and the ground layer 665 are separated by a part of the third substrate 63 (ie, the prepreg close to the second substrate). The closed-loop structure 34 of the first decoupling network 30, the first transmission line 31a, the second transmission line 32a, and the decoupling transmission line 33 all extend on this layer and form a pattern. In some embodiments, the length may be formed on the layer where the metal layer 666 satisfies the desired decoupling length d of the transmission line 33a _5. When will be appreciated, the linear distance between adjacent antenna elements corresponding to the feeder is less than d _5, decoupling the transmission line pattern 33a may be formed bent to meet the desired length (Figure 6). In some other embodiments, the decoupling transmission line 33a may also be in a curved pattern. The first decoupling network 30 and the second decoupling network 30' of the present application are located on different layers from the

surface radiating sheets

11a, 21a and the

inner radiating sheets

12a, 22a. As shown in FIG. 7, the decoupling transmission line 33 a is disposed under the

antenna units

10 a and 20 a, for example, in the third substrate 63. The first decoupling network 30 and the second decoupling network 30' shown in FIG. 7 and the decoupling transmission line 33 connected between them are located on the same layer as the metal layer 666, that is, they are arranged on the third substrate 63 closest to the ground. Between the prepreg of layer 665 and its adjacent prepreg. Understandably, in some other embodiments, the first decoupling network 30 and the second decoupling network 30' and the decoupling transmission line 33 connected between them may also be the same layer as the

metal layer

667 or 668.

The decoupling transmission line 33a can also be distributed in different layers, for example, a part of the decoupling transmission line 33a is distributed in the layer where the metal layer 666 is located, and the other part is distributed in the layer where the metal layer 667 is located through via holes; or, a part of the decoupling transmission line 33a It is distributed in the layer where the metal layer 666 is located, one part is distributed in the layer where the metal layer 667 is located through the via hole, and the other part is distributed in the layer where the metal layer 668 is located through the via hole.

In some embodiments, the characteristic impedance may gradually change along the direction from the second branch 342 to the middle position of the decoupling transmission line 33a. The change of the characteristic impedance of the transmission line can be realized by the change of the line width of the transmission line. In some embodiments, the line width gradually changes from the second branch 342 to the middle position of the decoupling transmission line 33a. In some embodiments, the line width of the decoupling transmission line 33a changes step by step from the second branch 342 to the middle position of the decoupling transmission line 33a. For example, the decoupling transmission line 33a shown in FIG. 6 includes a first section 331a, a second section 332a, and a third section 333a that are sequentially connected, wherein the width of each section may be uniform. The width of the first section 331a and the third section 333a are the same. The width of the second branch 342 is smaller than the width of the first section 331a. The width of the first section 331a is smaller than the width of the second section 332a. The width of the second branch 342 of the adjacent decoupling network is smaller than the width of the third section 333a. The width of the third section 333a is smaller than the width of the second section 332a. Therefore, from the second branch 342 to the first section 331a to the second section 332a, and from the second branch 342 to the third section 333a to the second section 332a, the characteristic impedance changes step by step until the characteristic of the second section 332a The impedance reaches 50Ω. Through the multi-stage impedance transformation, the appropriate characteristic impedance of the second branch 342 and the decoupling transmission line 33a can achieve full matching at multiple frequency points. Increasing the number of matching nodes will increase the frequency points where matching occurs and the bandwidth. Widen. Among them, the characteristic impedance of the second branch 342 can be calculated according to the power division ratio of the power divider, as shown in the above relation (24), its width can be calculated from the characteristic impedance; the characteristic impedance of the second section 332a is 50Ω, Its width can also be calculated from the characteristic impedance; the characteristic impedance of the first segment 331a and the third segment 333a can be equal to the square root of the product of the characteristic impedance of the first branch 342 and the second segment 332a, and the width can be calculated according to this The characteristic impedance is calculated. Of course, in some other embodiments, the width of the decoupling transmission line 33a can also be changed in three, four or more levels. It is understandable that the width of the decoupling transmission line 33a can be continuously changed.

In some embodiments,

stubs

334a and 335a (as shown in FIG. 6) may be further provided on the decoupling transmission line 33a, and the

stubs

334a and 335a are provided in the third section 333a to adjust the transmission characteristics of the decoupling network.

The length of the second transmission line 32a may be 3/4λ. In the embodiment shown in FIG. 6, the second transmission line 32 a forms a pattern that is bent or bent in a direction away from the decoupling transmission line 33 on the layer where the decoupling transmission line 33 is located.

The two

antenna units

10a and 20a, the first decoupling network 30 and the second decoupling network 30', and the decoupling transmission line 3 have been introduced above. However, it is easy to understand that the decoupling structure of the present application can also be provided for the

antenna units

20a and 10b, or the decoupling structure of the present application can also be provided for the

antenna units

10b and 20b (as shown in FIG. 6). For example, a third decoupling network 35 and a fourth decoupling network 35' and a decoupling transmission line 33a connected between the third decoupling network 35 and the fourth decoupling network 35' can be provided for the

antenna units

10b and 20a. '. The third decoupling network 35 may be the same as or similar to the aforementioned first decoupling network 30, and the fourth decoupling network 35' may be the same or similar to the aforementioned second decoupling network 30'. The third decoupling transmission line 33a' may be the same as or similar to the aforementioned decoupling transmission line 33a.

When more than three antenna units as shown in FIG. 6 are used, these decoupling networks and decoupling transmission lines can also be distributed in different layers. For example, the first decoupling network 30 and the second decoupling network 30' and the decoupling transmission line 33a connected between them can be distributed on the layer where the metal layer 666 shown in FIG. 7 is located, and the third decoupling network 35 and the The four decoupling network 35' and the decoupling transmission line 33a' connected between the third decoupling network 35 and the fourth decoupling network 35' may be distributed on the layer where the metal layer 667 shown in FIG. 7 is located.

Refer to FIG. 8, which is a schematic diagram of an antenna device according to another embodiment of the present application. In the antenna device 60 of this embodiment, for example, the top portion of the middle frame 42 of the mobile phone can be divided into two sections by the slot 44, and the two sections can be used as the first antenna 10a and the second antenna 20a, respectively. The middle frame 42 may be provided with a circuit board 43 on which the first decoupling network 30 and the second decoupling network 30' and the decoupling transmission line 33 (see FIG. 3) described in the present application may be arranged. The first feed source 40 and the second feed source 40' can be connected to the circuit board 43, which in turn is connected to the first antenna 10a and the second antenna 20a. The slit 44 can usually be arranged non-centrally, for example, arranged close to the left side or the right side of the middle frame 42.

Referring to FIG. 9, FIG. 10, and FIG. 11, FIG. 9 is a top view of an antenna device according to another embodiment of the present application. 10 is a front view of the two antenna units in FIG. 9, and FIG. 11 is a three-dimensional schematic diagram of one antenna unit in FIG. The antenna device includes a patch array 710, a ground layer 720, a grounding portion 730, a feeding portion 740, and a decoupling network. Wherein, the decoupling network may be the decoupling network of any of the above embodiments. For example, the first decoupling network 30 and the second decoupling network 30' are shown in the figure. The patch array 710 and the ground layer 720 are separated by a substrate (not shown). The ground layer 720 and the decoupling network 750 are separated by a substrate (not shown). The grounding portion 730 is electrically connected to the patch array 710 and the ground layer 720; the power feeding portion 740 includes a first power feeding member 741 and a second power feeding member 742 that are cross-insulated. The power feeding member 741 and the second power feeding member 742 are respectively used for feeding current signals to excite the patch array 720 and the ground feeding portion 730 to resonate in a corresponding frequency band. Specifically, the first power feeder 741 and the second power feeder 742 are respectively used to feed different current signals, which can excite the patch array 720 and the grounding portion 730 to resonate in different frequency bands. , Which can achieve dual-frequency dual-polarization. The first power feeder 741 and the second power feeder 742 feed the same current signal, which can excite the patch array 720 and the grounding portion 730 to resonate in the same frequency band, thereby enhancing the signal strength .

In some embodiments, the patch array 710 includes a first radiator 711, a second radiator 712, a third radiator 713, and a fourth radiator 714 that are arranged at intervals from each other. The first radiator 711, the second radiator 712, the third radiator 713, and the fourth radiator 714 are all metal patches, and the patch array 710 has a mirror-symmetric structure and forms a mesh structure. Cross-arranged first radiator 711, second radiator 712, third radiator 713, and fourth radiator 714 form a cross gap.

The power feeding part 740 is arranged corresponding to the gap between the first radiator 711, the second radiator 712, the third radiator 713 and the fourth radiator 714. The power feeder 740 transmits current to the first radiator 711, the second radiator 712, the third radiator 713, and the fourth radiator 714 by coupling and feeding, so that the The first radiator 711, the second radiator 712, the third radiator 713, and the fourth radiator 714 generate resonance. At this time, when the current signal on the feeding part 740 is coupled to the first radiator 711, the second radiator 712, the third radiator 713, and the fourth radiator 714, the current can be The flow directions on the radiator 712, the third radiator 713, and the fourth radiator 714 are relatively uniform, thereby making the radiation performance of the antenna device relatively stable.

The first power feeder 741 is at least partially arranged to face one gap in the patch array 710, and the second power feeder 742 is at least partially arranged to face another gap in the patch array 710. The first power feeder 741 is used to feed a first current signal, and the first current signal is coupled to the patch array 710 to excite the patch array 710 to resonate in a first frequency band. The current signal is coupled to the ground feeding part 730 to excite the ground feeding part 730 to resonate in a second frequency band. The first frequency band may be the same as the second frequency band or different from the second frequency band. The second power feeder 742 is used to feed a second current signal, and the second current signal is coupled to the patch array 710 to excite the patch array 710 to resonate in a third frequency band, and the second current signal The current signal is coupled to the ground feeding portion 730 to excite the ground feeding portion 730 to resonate in a fourth frequency band, and the third frequency band may be the same as the fourth frequency band or different from the fourth frequency band. The first power feeder 741 and the second power feeder 742 are arranged to be cross-insulated. When the first power feeder 741 and the second power feeder 742 remain orthogonal, the direction of the current on the first power feeder 741 The direction of the current on the second feeder 742 remains orthogonal. At this time, the antenna device has dual polarization characteristics.

The grounding portion 730 includes a first grounding member 731 and a second grounding member 732, the first grounding member 731 is electrically connected to the first radiator 711 and the ground layer 720, and the second grounding member 731 is electrically connected to the first radiator 711 and the ground layer 720. The member 732 is electrically connected to the first radiator 711 and the ground layer 720. The grounding portion 730 further includes a third grounding member 733 and a third grounding member 734. The third grounding member 733 is electrically connected to the second radiator 712 and the ground layer 720. The four-fed ground member 734 is electrically connected to the second radiator 712 and the ground layer 720. It can be understood that a ground feeder is also connected between the third radiator 713 and the ground layer 720, and a ground feeder is also connected between the fourth radiator 714 and the ground layer 720. The specific structure is similar to that of the first radiator 711 and the ground layer 720. The structure of the ground feeder between the grounding layers 720 is similar, and will not be repeated here. The above-mentioned radiator may be called an electric dipole, and the feed part may be called a magnetic dipole. In some embodiments, the antenna device may include a plurality of electric dipoles, a magnetic dipole corresponding to the plurality of electric dipoles one-to-one, and a first substrate, a second substrate, and a third substrate. A plurality of electric dipoles are arranged on the surface of the first substrate away from the second substrate and are spaced apart from each other. A plurality of magnetic dipoles are arranged in the second substrate and the first substrate, and connected between the ground layer and the corresponding electric dipoles. The decoupling network is arranged in the third substrate and spaced from the ground layer. The antenna unit of this embodiment may include a patch array 710, a grounding portion 730, and a power feeding portion 740.

It is easy to understand that the decoupling network of the present application can be applied to various types of antenna units, and is not limited to the types of antenna units in the foregoing embodiments.

In this embodiment, the decoupling design of the four-element linear array as shown in FIG. 9 is taken as an example, and the center operating frequency of the four-element linear array is 28 GHz. It is pointed out here that according to the 3GPP TS 38.101 protocol, the frequency between 24.25 GHz and 52.6 GHz is usually called millimeter wave (mm Wave); therefore, the decoupling structure proposed in this application can be a millimeter wave array antenna Decoupling structure. Figure 12 shows the isolation comparison curve of the antenna unit before and after connecting the decoupling network. It can be seen from Figure 12 that after connecting the decoupling network, the isolation between the antenna elements increases at 26.2GHz～33GHz and 37.4GHz～39.6GHz, which realizes broadband mutual coupling suppression and dual-band mutual coupling suppression.

Figure 13 shows the reflection parameter curve of an isolated antenna unit before decoupling. It can be seen from Fig. 13 that the -6dB working bandwidth of the antenna unit in the decoupling front array is 24.4GHz～31.3GHz and 35GHz～40.1GHz. Figure 14 shows the reflection parameter curve of the antenna unit after decoupling. It can be seen from Figure 14 that the -6dB working bandwidth of the antenna unit in the decoupling array is 24.1GHz～29.7GHz and 35.7GHz～45.0GHz. Therefore, the dual-band matching is improved.

Figures 15-17 are the comparison curves of the gain sweep frequency of the antenna device when the beam is scanned to 0°, 45° and 50° before and after the decoupling network is connected. It can be seen from Fig. 15 that when the beam is pointed at 0°, in the frequency range of 27 GHz to 29 GHz, the gain after decoupling is improved compared with that before decoupling. In the frequency ranges of 24.25GHz～27GHz, 29GHz～29.6GHz, and 37GHz～40GHz, the gain loss after decoupling is all less than 0.5dB. As shown in Figure 16, when the beam is pointed at 45°, in the frequency range of 24GHz～29.8GHz and 37GHz～41GHz, the gain after decoupling is improved compared with that before decoupling. Among them, when the frequency is 24.5GHz, the gain increase is the largest , An increase of 1.34dB. As shown in Figure 17, when the beam is pointed at 50°, in the frequency range of 24GHz～30GHz and 37GHz～41GHz, the gain after decoupling is improved compared with that before decoupling, and the maximum gain increase is 1.55dB at 24.5GHz. Therefore, after connecting the decoupling network, when scanning to 0°, 45°, and 50°, the gain is improved, and the radiation ability of the array antenna is significantly improved.

Please refer to Figure 18, which shows the transmission coefficient curve of the decoupling network. It can be seen from Figure 18 that the transmission performance of the decoupling network in the dual frequency bands is improved, and the insertion loss is less than 0.7dB in the frequency ranges of 24.5GHz～29.6GHz and 37GHz～40GHz. Referring to Figure 19, the reflection parameters of the decoupling network are shown. It can be seen from Fig. 19 that the matching performance of the decoupling network in the dual frequency band is improved, and the frequency range of the working bandwidth of -10dB is 23.6GHz～30.3GHz and 36.7GHz～40.4GHz. Therefore, the present application improves the transmission performance and matching performance of the dual frequency band of the decoupling network by adopting the design of ring cancellation.

In summary, the antenna device of the present application introduces the concept of a decoupling network under the antenna unit, and there is no need to change the structure of the array antenna unit. Only the length of the decoupling transmission line and the S parameters of the three-port network need to be configured. Accurately define the coupling degree between the antenna elements, which can reduce the mutual coupling between the antenna elements, expand the scanning angle, and increase the scanning gain. Further, the power division ratio of the directional power divider can be calculated according to the magnitude of the isolation before decoupling, and then the characteristic impedance of each branch of the power divider can be determined according to the formula, and then the width of the transmission line corresponding to the characteristic impedance can be calculated, so that Make a power divider. Based on this method, the isolation of the multi-antenna system can be improved.

In addition, the decoupling network of the present application includes a closed-loop structure. The closed-loop structure has first and second output ports. Slots are provided on the antenna floor, and at least a part of the slots overlap the closed-loop structure, so that the power divider can be The interference effects between the first output port and the second output port are equal in magnitude and inverted and cancel each other out, so that the first and second output ports will no longer affect each other, thus significantly improving the two main components of the power splitter. Isolation between two output ports. In addition, there is no need to provide an isolation resistor between the two output ports of the main body of the power splitter of the present application, which can reduce the insertion loss.

The above are only examples of this application, and do not limit the scope of this application. Any equivalent structure or equivalent process transformation made using the content of the description and drawings of this application, or directly or indirectly applied to other related technologies In the same way, all fields are included in the scope of patent protection of this application.

Claims

An antenna device, characterized in that it comprises:

Multiple antenna units arranged at intervals;

A plurality of decoupling networks correspond to the plurality of antenna units one-to-one, and each of the decoupling networks includes a closed-loop structure and a first transmission line and a second transmission line connected to the closed-loop structure; on the closed-loop structure A first output port and a second output port are provided, the first transmission line is used to connect with a radio frequency chip, one end of the second transmission line is connected to the first output port, and the other end is connected to a corresponding antenna unit;

The decoupling transmission line is connected between the second output ports of adjacent decoupling networks;

The ground layer is overlapped with the plurality of decoupling networks at intervals, the ground layer is provided with a slot, and at least a part of the slot overlaps the closed loop structure.
The antenna device according to claim 1, wherein the slot is enclosed in an axially symmetrical pattern; the closed-loop structure is an axially symmetrical pattern; and the symmetry axis of the slot overlaps with the symmetry axis of the closed-loop structure.
The antenna device according to claim 1, wherein the slot is enclosed in a closed shape.
The antenna device according to claim 1, wherein the closed-loop structure comprises a first branch, a second branch and a microstrip connection line;

The first end of the first branch and the first end of the second branch are connected to the same end of the first transmission line; the second end of the first branch forms the first output port; The second ends of the two branches form the second output port;

The microstrip connection line is connected between the first output port and the second output port.
The antenna device according to claim 4, wherein the first branch, the second branch and the microstrip connecting line are enclosed in a circular ring, an elliptical ring, or a polygon.
The antenna device according to claim 4, wherein the lengths of the first branch and the second branch are equal; or, the length difference between the first branch and the second branch is equal to the wavelength.
The antenna device according to claim 4, wherein the slot comprises a closed-loop groove and a strip-shaped groove extending from the closed-loop groove, and at least a part of the strip-shaped groove overlaps the closed-loop structure.
8. The antenna device according to claim 7, wherein at least a part of the strip-shaped groove overlaps the microstrip connection line, and the microstrip connection line is symmetrically arranged with respect to the strip-shaped groove; the closed loop Both the structure and the closed-loop groove are symmetrical with respect to the line where the strip-shaped groove is located.
The antenna device according to claim 7, wherein the closed-loop groove has a circular ring shape, an elliptical ring shape, or a polygonal shape.
4. The antenna device according to claim 4, wherein the characteristic impedance changes stepwise from the second branch to the middle position of the decoupling transmission line.
The antenna device according to claim 4, wherein the isolation degree when the adjacent antenna unit is not connected to the decoupling network is defined as the initial isolation degree;

The first branch, the second branch and the microstrip connection linear success divider;

The power division ratio of the power divider and the strength of the initial isolation, and the length of the decoupling transmission line and the phase of the initial isolation satisfy the following relationship:

Wherein, S'12 is the strength of the initial isolation; S12 and S13 are the scattering parameters of the decoupling network;
Said power divider ratio; φ '12 are the phase of initial isolation; d5 of decoupling the transmission line length, k is the wave number.
The antenna device according to claim 11, wherein the characteristic impedance of the first branch, the characteristic impedance of the first transmission line, and the strength of the initial isolation satisfy the following relationship:

Z2=(1+|S’12|)ⅹZ1;

Wherein, Z1 is the characteristic impedance of the first transmission line, and Z2 is the characteristic impedance of the first branch.
The antenna device according to claim 11, wherein the characteristic impedance of the second branch, the characteristic impedance of the first transmission line, and the strength of the initial isolation satisfy the following relationship:

Wherein, Z1 is the characteristic impedance of the first transmission line, and Z3 is the characteristic impedance of the second branch.
The antenna device according to claim 1, further comprising a first substrate, a second substrate, and a third substrate that are stacked in sequence;

The multiple antenna units are arranged on the first substrate;

The ground layer is disposed between the second substrate and the third substrate;

The plurality of decoupling networks are arranged in the third substrate; the plurality of decoupling networks and the ground layer are separated by a part of the third substrate.
The antenna device according to claim 14, wherein the third substrate has a multilayer structure, and the decoupling transmission line is arranged on a layer of the third substrate; the plurality of decoupling networks are connected to the The same layer of the decoupling transmission line.
The antenna device according to claim 14, wherein each antenna unit comprises:

A plurality of electric dipoles are arranged on the surface of the first substrate away from the second substrate, the plurality of electric dipoles are spaced apart from each other; and

A plurality of magnetic dipoles correspond to the plurality of electric dipoles one-to-one, and the plurality of magnetic dipoles are arranged in the second substrate and the first substrate and connected to the ground layer And the corresponding electric dipole.
The antenna device according to claim 1, wherein the degree of coupling between the adjacent antenna units is determined according to the length of the decoupling transmission line and the scattering parameter of the decoupling network corresponding to the antenna unit.
The antenna device according to claim 1, wherein the coupling degree between the adjacent antenna elements and the length of the decoupling transmission line and the corresponding scattering parameter of the decoupling network satisfy the following relationship :

Wherein, S'12 is the strength of the initial isolation between the adjacent antenna units, and the initial isolation is the isolation when the adjacent antenna units are not connected to the decoupling network; S12, S13 Is the scattering parameter of the decoupling network; d5 is the length of the decoupling transmission line, k is the wave number, e is the natural constant, and j is the symbol of the imaginary number.
An electronic device, characterized in that it comprises:

case,

The display screen assembly is connected to the housing and forms an accommodation space with the housing;

The radio frequency chip is arranged in the accommodating space; and

The antenna device is at least partially arranged in the accommodating space, and the antenna device includes:

Multiple antenna units arranged at intervals;

A plurality of decoupling networks correspond to the plurality of antenna units one-to-one, and each of the decoupling networks includes a closed-loop structure and a first transmission line and a second transmission line connected to the closed-loop structure; on the closed-loop structure A first output port and a second output port are provided, the first transmission line is used to connect with a radio frequency chip, one end of the second transmission line is connected to the first output port, and the other end is connected to a corresponding antenna unit;

The decoupling transmission line is connected between the second output ports of adjacent decoupling networks;

The ground layer is overlapped with the plurality of decoupling networks at intervals, the ground layer is provided with a slot, and at least a part of the slot overlaps the closed loop structure.
The electronic device according to claim 19, wherein the antenna device further comprises a first substrate, a second substrate, and a third substrate that are stacked in sequence;

The multiple antenna units are arranged on the first substrate;

The ground layer is disposed between the second substrate and the third substrate;

The plurality of decoupling networks are arranged in the third substrate; the plurality of decoupling networks and the ground layer are separated by a part of the third substrate;

The radio frequency chip is arranged on a side of the third substrate away from the second substrate.