WO2021227808A1 - 天线装置、电子设备和用于天线装置的去耦方法 - Google Patents

天线装置、电子设备和用于天线装置的去耦方法 Download PDF

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Publication number
WO2021227808A1
WO2021227808A1 PCT/CN2021/088836 CN2021088836W WO2021227808A1 WO 2021227808 A1 WO2021227808 A1 WO 2021227808A1 CN 2021088836 W CN2021088836 W CN 2021088836W WO 2021227808 A1 WO2021227808 A1 WO 2021227808A1
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WIPO (PCT)
Prior art keywords
decoupling
transmission line
network
antenna
port
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PCT/CN2021/088836
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English (en)
French (fr)
Inventor
张帅
刘雨果
雍征东
Original Assignee
西安电子科技大学
Oppo广东移动通信有限公司
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Priority claimed from CN202010398727.5A external-priority patent/CN113659337B/zh
Application filed by 西安电子科技大学, Oppo广东移动通信有限公司 filed Critical 西安电子科技大学
Publication of WO2021227808A1 publication Critical patent/WO2021227808A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/18—Means for stabilising antennas on an unstable platform
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/242—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use
    • H01Q1/243—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use with built-in antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/28—Combinations of substantially independent non-interacting antenna units or systems

Definitions

  • This application relates to the field of antenna decoupling technology, and in particular to an antenna device, electronic equipment, and a decoupling method for the antenna device.
  • Antennas can efficiently transmit and receive electromagnetic waves and are an indispensable part of wireless communication systems.
  • several antenna elements with the same radiation characteristics can be arranged according to a certain geometric structure to form an array antenna, thereby enhancing the radiation performance of the array antenna and producing a more flexible Directional map to meet the needs of different scenarios.
  • an antenna device which includes: a first antenna unit and a second antenna unit arranged adjacently; a first decoupling network, the first decoupling network having an input port, an output port, and a first connection Port and a second connection port; the output port is connected to the first antenna unit, the input port is used to connect the first feed source; a second decoupling network, the second decoupling network has an input port, an output port , The first connection port and the second connection port; the output port of the second decoupling network is connected to the second antenna unit, and the input port of the second decoupling network is used to connect a second feed source; A coupling transmission line, the first decoupling transmission line connecting the first connection port of the first decoupling network and the first connection port of the second decoupling network; a second decoupling transmission line, the second decoupling transmission line The second connection port of the first decoupling network is connected to the second connection port of the second decoupling network.
  • a phase shifter is provided in at least one of the first decoupling network having
  • the present application also provides an electronic device, which includes: a housing; a display screen assembly connected to the housing and forming an accommodating space with the housing; and a feed source arranged in the housing And the antenna device is at least partially arranged in the accommodating space.
  • the antenna device includes: a plurality of antenna units; a plurality of decoupling networks corresponding to the plurality of antenna units one-to-one, wherein each decoupling network has an input port, an output port, a first connection port, and a second connection port.
  • Connection port the output port is connected to the corresponding antenna unit, the input port is connected to the feed; a first decoupling transmission line, the first decoupling transmission line is connected to the adjacent decoupling network Between a connection port; a second decoupling transmission line, the second decoupling transmission line is connected between adjacent second connection ports of the decoupling network.
  • a phase shifter is provided in at least one of the first decoupling transmission line and the second decoupling transmission line.
  • the present application also provides a decoupling method for an antenna device, the antenna device comprising: a first antenna unit and a second antenna unit arranged adjacently; a first decoupling network, the first antenna unit
  • the decoupling network has an input port, an output port, a first connection port, and a second connection port; the output port is connected to the first antenna unit, and the input port is used to connect the first feed;
  • the second decoupling network has an input port, an output port, a first connection port, and a second connection port; the output port of the second decoupling network is connected to the second antenna unit, and the second decoupling network is The input port is used to connect a second feed source; a first decoupling transmission line that connects the first connection port of the first decoupling network and the first connection port of the second decoupling network; And a second decoupling transmission line, which connects the second connection port of the first decoupling network and the second connection port of the second decoupling network; wherein, the
  • phase shifter is provided in at least one of the first decoupling transmission line and the second decoupling transmission line, the phase shifter is changed and the decoupling transmission lines connected to the phase shifter are adjusted
  • the phase accumulation can change the degree of coupling between antenna elements and realize the adjustable decoupling between antenna elements. Based on these methods, the isolation between the antenna device and the electronic equipment can be flexibly improved.
  • FIG. 1 is a schematic diagram of the structure of an electronic device according to an embodiment of the present application.
  • FIG. 2 is a schematic diagram of a decoupling principle for an array antenna according to an embodiment of the present application
  • FIG. 3 is a schematic diagram of the first decoupling structure for an array antenna according to an embodiment of the present application
  • FIG. 4 is a schematic structural diagram of a first decoupling network according to an embodiment of the present application.
  • FIG. 5 is a schematic structural diagram of a second decoupling network according to an embodiment of the present application.
  • Fig. 6 is a schematic diagram of a second decoupling structure for an array antenna according to an embodiment of the present application.
  • FIG. 7 is a schematic diagram of a third decoupling structure for an array antenna according to an embodiment of the present application.
  • FIG. 8 is a schematic diagram of a fourth decoupling structure for an array antenna according to an embodiment of the present application.
  • FIG. 9 is a schematic flowchart of a decoupling method for an array antenna according to an embodiment of the present application.
  • FIG. 10 is a schematic diagram of a three-dimensional structure of an electronic device according to an embodiment of the present application.
  • FIG. 11 is a perspective view of the antenna device according to an embodiment of the present application.
  • FIG. 12 is a top view of the antenna device of FIG. 11;
  • FIG. 13 is a bottom view of the antenna device of FIG. 11;
  • FIG. 14 is a partial schematic diagram of the antenna device of FIG. 13, which shows the arrangement of the first decoupling network and the second decoupling network of the antenna device and the first decoupling transmission line and the second decoupling transmission line connected between them;
  • FIG. 15 is a schematic diagram of a layered structure of an antenna device according to an embodiment of the present application, in which two antenna units are shown;
  • FIG. 16 is a schematic diagram of an antenna device according to another embodiment of the present application.
  • Array antennas especially small-pitch array antennas, have the problem of strong mutual coupling.
  • the mutual coupling between the antenna elements affects the matching characteristics and spatial radiation characteristics of the antenna elements and their arrays to a large extent, and the specific manifestations are as follows.
  • Pattern The distribution of the current on the antenna unit changes under the action of mutual coupling, causing part of the radiated energy to be further coupled to other antenna units, part of the coupling energy is absorbed and consumed by the terminal load, and the other part of the energy is Will radiate again. Therefore, the pattern of the antenna unit will be distorted.
  • the termination load mentioned here is a parameter equivalent to the back end of the antenna feed; when drawing the equivalent circuit, the entire back end of the antenna feed can be replaced by a resistor, which can be called a termination load .
  • Input impedance Affected by mutual coupling, the input impedance of the antenna unit in the array will change, and is different from the input impedance of the antenna unit in an isolated environment, so the matching situation of the antenna unit in each array is different and the matching characteristics will be affected .
  • DGS-Defected Ground Structure DGS-Defected Ground Structure
  • NLT-Neutralization Line Technique neutralization line Method
  • band-stop filter decoupling method electromagnetic band gap structure
  • ECG Electromagnetic Band Gap
  • MDT Metamaterial Decoupling Technique
  • the array antenna of the electronic device can customize the coupling effect between the antenna elements, and realize the control of the radiation pattern of the antenna element through the design of the coupling effect, such as widening the scanning angle and improving Scan gain, eliminate scan blind area, etc.
  • the electronic device may be a mobile phone, a tablet computer, a PDA (Personal Digital Assistant), a POS (Point of Sales, sales terminal), a car computer, a CPE (Customer Premise Equipment, customer front equipment) and other terminal devices.
  • PDA Personal Digital Assistant
  • POS Point of Sales, sales terminal
  • car computer a CPE (Customer Premise Equipment, customer front equipment) and other terminal devices.
  • CPE Customer Premise Equipment, customer front equipment
  • the mobile phone 100 may include: an RF (Radio Frequency) circuit 101, a memory 102, a central processing unit (CPU) 103, a peripheral interface 104, an audio circuit 105, a speaker 106, and power management
  • the chip 107, an input/output (I/O) subsystem 108, a touch screen 109, other input/control devices 110, and an external port 111 communicate through one or more communication buses or signal lines 112.
  • the illustrated mobile phone is only an example of an electronic device, and the mobile phone 100 may have more or fewer components than those shown in the figure, may combine two or more components, or may have Different component configurations.
  • the various components shown in the figure may be implemented in hardware, software, or a combination of hardware and software including one or more signal processing and/or application specific integrated circuits.
  • the radio frequency (RF) circuit 101 is mainly used to establish communication between the mobile phone and the wireless network (ie, the network side), so as to realize the data reception and transmission between the mobile phone and the wireless network. For example, sending and receiving short messages, emails, etc. Specifically, the RF circuit 101 receives and transmits RF signals, which are also called electromagnetic signals. The RF circuit 101 converts electrical signals into electromagnetic signals or converts electromagnetic signals into electrical signals, and communicates with communication networks and other equipment through the electromagnetic signals. To communicate.
  • the RF circuit 101 may include known circuits for performing these functions, including but not limited to an antenna system with an antenna array, an RF transceiver, one or more amplifiers, a tuner, one or more oscillators, digital signal processing Device, CODEC (COder-DECoder, codec) chipset, subscriber identity module (Subscriber Identity Module, SIM), etc.
  • CODEC COder-DECoder, codec
  • SIM Subscriber Identity Module
  • the memory 102 can be accessed by the CPU 103, the peripheral interface 104, etc.
  • the memory 102 can include a high-speed random access memory, and can also include a non-volatile memory, such as one or more disk storage devices, flash memory devices, or other easy-to-use devices. Destroy solid-state storage devices.
  • the central processing unit 103 executes various functional applications and data processing of the electronic device by running software programs and modules stored in the memory 102.
  • the peripheral interface 104 can connect the input and output peripherals of the device to the CPU 103 and the memory 102.
  • the I/O subsystem 108 can connect the input and output peripherals on the device, such as the touch screen 109 and other input/control devices 110, to the peripheral interface 104.
  • the I/O subsystem 108 may include a display controller 1081 and one or more input controllers 1082 for controlling other input/control devices 110.
  • one or more input controllers 1082 receive electrical signals from other input/control devices 110 or send electrical signals to other input/control devices 110, and other input/control devices 110 may include physical buttons (press buttons, rocker buttons, etc.) ), dial, slide switch, joystick, click wheel.
  • the input controller 1082 can be connected to any of the following: a keyboard, an infrared port, a USB interface, and a pointing device such as a mouse.
  • the touch screen 109 is an input interface and an output interface between the user terminal and the user, and displays visual output to the user.
  • the visual output may include graphics, text, icons, videos, and the like.
  • the display controller 1081 in the I/O subsystem 108 receives electrical signals from the touch screen 109 or sends electrical signals to the touch screen 109.
  • the touch screen 109 detects the contact on the touch screen, and the display controller 1081 converts the detected contact into interaction with the user interface object displayed on the touch screen 109, that is, realizes human-computer interaction.
  • the user interface object displayed on the touch screen 109 can be running The icon of the game, the icon of connecting to the corresponding network, etc.
  • the device may also include an optical mouse, which is a touch-sensitive surface that does not display visual output, or is an extension of the touch-sensitive surface formed by a touch screen.
  • the audio circuit 105 is mainly used to receive audio data from the peripheral interface 104, convert the audio data into an electric signal, and send the electric signal to the speaker 106.
  • the speaker 106 is used to restore the voice signal received by the mobile phone 100 from the wireless network through the RF circuit 101 into sound and play the sound to the user.
  • the power management chip 107 is used to perform power supply and power management for the hardware connected to the CPU 103, the I/O subsystem 108, and the peripheral interface 104.
  • the array antenna in the antenna system of the RF circuit 101 of the electronic device.
  • the array antenna usually includes a plurality of closely arranged antenna elements. In at least two adjacent antenna units, each antenna unit is connected to the feed through a decoupling network.
  • a plurality of means at least two, such as two, three, etc., unless otherwise specifically defined.
  • FIG. 2 it is a schematic diagram of a decoupling principle for an array antenna according to an embodiment of the present application.
  • the array antenna includes adjacent antenna elements 10 and antenna elements 20.
  • the radiation characteristics of the antenna unit 10 and the antenna unit 20 may be the same or different.
  • the antenna unit 10 can receive the excitation current from the feed (radio frequency transceiver) of the electronic device, and after amplifying, filtering, matching and tuning, the antenna unit 10 is excited to resonate at the corresponding frequency, thereby generating an electromagnetic wave signal of the corresponding frequency, which is the same frequency as the free space.
  • Electromagnetic wave signal coupling realizes signal transmission.
  • the antenna unit 10 can also resonate with the antenna unit of the corresponding frequency under the excitation of the excitation signal to couple electromagnetic wave signals of the same frequency from free space, thereby forming an induced current on the antenna unit 10, and the induced current enters the radio frequency transceiver after being filtered and amplified. .
  • the decoupling networks corresponding to two adjacent antenna units 10 and 20 are connected to each other, wherein the antenna unit 10 corresponds to the first decoupling network 31, and the antenna unit 20 corresponds to the second decoupling network 31'.
  • Both the first decoupling network 31 and the second decoupling network 31' are four-port networks.
  • the first decoupling network 31 has an input port (a 1 , b 1 ) connected to the feed, an output port (a 2 , b 2 ) connected to the antenna unit 10, and a first connection for connecting the second decoupling network 31' Ports (a 3 , b 3 ) and second connection ports (a 4 , b 4 ).
  • Second decoupling network 31 ' having an input port (a connector feeds' 1, b' 1), an output port connected to the antenna unit (a 20 is the '2, b' 2) and means for connecting the first decoupling network 31 a first connection port (a '3, b' 3 ) and a second connection port (a '4, b' 4 ).
  • Length d of the transmission line 1 may form an output port (a 2, b 2), and having a characteristic impedance Z 0; length of a transmission line d 2 may form an output port (a '2, b' 2 ), and having a characteristic impedance Z 0 .
  • the first connection port (a' length d 3 of the first transmission line is connected to a first coupling decoupling network 31 is connected to a first port (a 3, b 3) and the second decoupling network 31 3, b '3 ), and has a characteristic impedance Z 3 ;
  • a second decoupling transmission line with a length of d 4 is connected to the second connection port (a 4 , b 4 ) of the first decoupling network 31 and the second connection of the second decoupling network 31 ′ port (a '4, b' 4 ), and having a characteristic impedance Z 4.
  • a 1, a 2, a '1, a' 2, a 3, a 4, a '3, a' 4 is the incident voltage wave amplitude
  • b 1, b 2, b '1, b' 2, b 3, b 4, b '3 , b' 4 is reflected voltage wave amplitude.
  • the “input port” and “output port” in the embodiment of the present application are only named from the angle of the antenna unit 10 transmitting signals. It is understandable that the antenna unit 10 can also receive signals.
  • the aforementioned "output port” can be used as an input port
  • the aforementioned "input port” can be used as an output port, that is, the "input port” and "output port” in this application.
  • the naming does not limit the attributes of the port.
  • the side of the transmission line with length d 1 in Fig. 2 also shows a transmission line with characteristic impedance Z 0 , but these two transmission lines correspond to the same wire in physical objects; similarly, the length is d 2
  • the characteristic impedance Z 3 and the characteristic impedance Z 4 can be set equal to the characteristic impedance Z 0.
  • the characteristic impedance Z 0 is usually set in advance, for example, set to 50 ⁇ .
  • FIG. 3 it is a schematic diagram of the first decoupling structure for an array antenna according to an embodiment of the present application, in which at least a first decoupling network 31, a second decoupling network 31', and a first decoupling network connected therebetween are
  • the coupling transmission line 33 and the second decoupling transmission line 34 can form the decoupling structure for the array antenna of the present application.
  • the decoupling structure and the array antenna connected to it can also form the antenna device of the present application.
  • first decoupling network 31 corresponding to the antenna unit 10 in FIGS. 3 and 4
  • second decoupling network 31' corresponding to the antenna unit 20 may be the same as the first decoupling network 31 corresponding to the antenna unit 10.
  • the first decoupling network 31 is a four-port network.
  • the four-port network is a directional coupler, which may include a directional coupler main body 310 and four transmission lines extending from the directional coupler main body 310.
  • the four transmission lines include a first transmission line 311, a second transmission line 312, a third transmission line 313, and a fourth transmission line 314.
  • the first connection port (a 3 , b 3 ) of the directional coupler can be a coupling port or an isolated port; accordingly, the second connection port (a 4 , b 4 ) of the directional coupler can be an isolated port or Coupling port.
  • the directional coupler body 310 may include a fifth transmission line 315, a sixth transmission line 316, a seventh transmission line 317, and an eighth transmission line 318.
  • the fifth transmission line 315, the sixth transmission line 316, the seventh transmission line 317, and the eighth transmission line 318 are sequentially connected end to end to form a polygon to form a loop.
  • the first end of the first transmission line 311 is connected to the first end of the fifth transmission line 315, and the second end of the first transmission line 311 forms an input port connected to the feed source 40.
  • the first end of the second transmission line 312 is connected to the second end of the fifth transmission line 315, and the second end of the second transmission line 312 forms an output port connected to the antenna unit 10.
  • the first end of the third transmission line 313 is connected to the first end of the seventh transmission line 317, and the second end of the third transmission line 313 forms a first connection port connected to the first end of the first decoupling transmission line 33.
  • the first end of the fourth transmission line 314 is connected to the second end of the seventh transmission line 317, and the second end of the fourth transmission line 314 forms a second connection port connected to the first end of the second decoupling transmission line 34. It is pointed out here that the first end and the second end of a certain transmission line mentioned in the text refer to the two opposite ends of the transmission line.
  • the third transmission line 313 and the fourth transmission line 314 can be designed to have a shorter length.
  • the length of the third transmission line 313 and the fourth transmission line 314 can only be connected to the first decoupling transmission line 33 and the second decoupling transmission line 34. There is no longer a redundant length. This can reduce the influence on the length design of the first decoupling transmission line 33 and the second decoupling transmission line 34.
  • the characteristic impedance of the fifth transmission line 315 and the seventh transmission line 317 may be designed as Z 1
  • the characteristic impedance of the sixth transmission line 316 and the eighth transmission line 318 may be designed as Z 2
  • the lengths of the fifth transmission line 315, the sixth transmission line 316, the seventh transmission line 317, and the eighth transmission line 318 can all be set to (1/4) ⁇ , where ⁇ is the wavelength.
  • the second decoupling network 31' corresponding to the antenna unit 20 may be the same as the first decoupling network 31 described above.
  • the second decoupling network 31' is a four-port network.
  • the four-port network is a directional coupler, which may include a directional coupler main body 310' and four transmission lines extending from the directional coupler main body 310'.
  • the four transmission lines include a first transmission line 311', a second transmission line 312', a third transmission line 313', and a fourth transmission line 314'.
  • first connection port of the directional coupler (a '3, b' 3 ) may be coupled isolation port or ports; Accordingly, the second connection port of the directional coupler (a '4, b' 4 ) may be It is an isolated port or a coupled port.
  • the directional coupler body 310' may include a fifth transmission line 315', a sixth transmission line 316', a seventh transmission line 317', and an eighth transmission line 318'.
  • the fifth transmission line 315', the sixth transmission line 316', the seventh transmission line 317' and the eighth transmission line 318' are sequentially connected end to end to form a loop.
  • the first end of the first transmission line 311' is connected to the first end of the fifth transmission line 315', and the second end of the first transmission line 311' forms an input port connected to the feed source 40'.
  • the first end of the second transmission line 312' is connected to the second end of the fifth transmission line 315', and the second end of the second transmission line 312' forms an output port connected to the antenna unit 20.
  • the first end of the third transmission line 313' is connected to the first end of the seventh transmission line 317', and the second end of the third transmission line 313' forms a first connection port connected to the second end of the first decoupling transmission line 33.
  • the first end of the fourth transmission line 314' is connected to the second end of the seventh transmission line 317', and the second end of the fourth transmission line 314' forms a second connection port connected to the second end of the second decoupling transmission line 34.
  • the feed source 40 and the feed source 40' may be the same feed source.
  • the third transmission line 313' and the fourth transmission line 314' can be designed to have a shorter length.
  • the length of the third transmission line 313' and the fourth transmission line 314' can only be the same as the first decoupling transmission line 33 and the second decoupling transmission line 34. Just connect, and no longer have redundant length. This can reduce the influence on the length design of the first decoupling transmission line 33 and the second decoupling transmission line 34.
  • the characteristic impedance of the fifth transmission line 315 ′ and the seventh transmission line 317 ′ may be designed as Z 1
  • the characteristic impedance of the sixth transmission line 316 ′ and the eighth transmission line 318 ′ may be designed as Z 2
  • the lengths of the fifth transmission line 315', the sixth transmission line 316', the seventh transmission line 317', and the eighth transmission line 318' can all be set to (1/4) ⁇ .
  • the first decoupling transmission line 33 and the second decoupling transmission line 34 are both connected between the first decoupling network 31 and the second decoupling network 31'.
  • the first end of the first decoupling transmission line 33 is connected to the first connection port of the first decoupling network 31, that is, to the second end of the third transmission line 313; the second end of the first decoupling transmission line 33 is connected to The first connection port of the second decoupling network 31' is connected to the second end of the third transmission line 313'.
  • the first end of the second decoupling transmission line 34 is connected to the second connection port of the first decoupling network 31, that is, to the second end of the fourth transmission line 314; the second end of the second decoupling transmission line 34 is connected to the The second connection port of the second decoupling network 31' is connected to the second end of the fourth transmission line 314'.
  • the first transmission line 311, the second transmission line 312, the third transmission line 313, the fourth transmission line 314, the first transmission line 311', the second transmission line 312', the third transmission line 313', and the fourth transmission line 314 The characteristic impedance of the first decoupling transmission line 33 and the second decoupling transmission line 34 can be designed as Z 0 .
  • the length of the first decoupling transmission line 33 can be set to d 3
  • the length of the second decoupling transmission line 34 can be set to d 4 .
  • the first decoupling transmission line 33 and the second decoupling transmission line 34 are used to transmit signals to cancel the mutual coupling between the two antenna units 10 and 20.
  • the coupling degree D1 between the two antenna units 10 and 20 can be determined by the scattering parameters (ie, S parameters) of the first decoupling network 31 and the second decoupling network 31', and the first decoupling transmission line 33 and the second decoupling network 31'.
  • the lengths d 3 and d 4 of the decoupling transmission line 34 are defined.
  • the coupling degree D1 between the two antenna units 10 and 20 is required to reach the preset coupling degree, the S parameter of the four-port network and the length d 3 of the first decoupling transmission line 33 and the second decoupling transmission line 34 can be combined. , d 4 configured to cause the degree of coupling between the antenna elements 10,20 D1 satisfies the preset degree of coupling. It is pointed out here that the coupling degree D1 between the two antenna elements 10 and 20 is inversely proportional to the isolation degree between the two antenna elements 10 and 20; that is, the degree of isolation between the two antenna elements 10 and 20 The higher the value, the lower the coupling degree D1 between the two antenna elements 10 and 20.
  • the coupling degree D1 between the two antenna units 10 and 20 is the same as the S parameter of the first decoupling network 31 and the first decoupling network 31.
  • the relationship between the lengths d 3 and d 4 of the transmission line 33 and the second decoupling transmission line 34 can be obtained in the following manner.
  • the S parameter matrix S 0 of the first decoupling network 31 is:
  • S 12 , S 13 , and S 31 are three of the S parameters when the first decoupling network 31 is a four-port network. Specifically, these three S parameters are mutual coupling coefficients, which can also be called coupling coefficients.
  • the first connection port and the second connection port of the first decoupling network 31 are respectively connected to the first decoupling transmission line of length d 3 and d 4 33 and the second decoupling transmission line 34, so the S parameter matrix S of the first decoupling network 31 can be calculated by the S parameter in formula (1):
  • e is a natural constant
  • j is the sign of an imaginary number
  • k is the wave number
  • S 31 in formula (1) is equal to S 13 in formula (2).
  • the first decoupling network 31 and the second decoupling network 31' form an eight-port network before they are connected, and the relational formula of the S parameter is:
  • a1-a' 4 is the amplitude of the incident voltage wave
  • b1-b' 4 is the amplitude of the reflected voltage wave.
  • S 11 , S 22 , and S 21 are three S parameters of the four-port network, S 11 is the reflection coefficient, and S 21 is the mutual coupling coefficient.
  • formula (4) can be abbreviated as:
  • E represents the identity matrix
  • the four ports of the new four-port network here refer to the four external ports (a 1 , b 1 ), (a 2 ,b 2 ), (a' 1 ,b' 1 ) and (a' 2 ,b' 2 ).
  • S '12 is the initial isolation of the amplitude, i.e., two adjacent antenna elements 10 and 20 are not connected between the decoupled intensity during the isolation network; S' 11, S '21, and S '22 port input reflection coefficient (a 1, b 1) is not connected between the decoupling networks 10 and 20 of two adjacent antenna elements, respectively, and output isolation port (a 2, b 2) of the reflector coefficient.
  • the S parameter matrix [S] of the two-port network is:
  • the two ports of the two-port network here means that after the new four-port network is connected to the antenna units 10 and 20, there are only two remaining ports (a 1 , b 1 ) and ( a '1, b' 1) .
  • the lengths d 3 and d 4 of the first decoupling transmission line 33 and the second decoupling transmission line 34 and the S parameter of the four-port network can be configured so that the coupling degree D1 between the antenna units 10 and 20 meets the preset coupling degree .
  • S 1 ′ 2 can be expressed by the S parameter of the four-port network:
  • ⁇ s 12 represents the phase of the parameter S 12 of the four-port network
  • ⁇ s 13 represents the phase of the parameter S 13 of the four-port network.
  • the coupling degree D of the coupler can be calculated as follows:
  • the lengths d 3 and d 4 of the first decoupling transmission line 33 and the second decoupling transmission line 34 are respectively:
  • ⁇ 21 is the phase of the isolation before decoupling
  • the corresponding value of Pi is ⁇ , for example, 3.14
  • S 1 ′ 2 is the amplitude of the isolation before decoupling.
  • D can be calculated desired degree of coupling of the directional coupler according to S '12; also possible to calculate the length of the transmission line 33 is coupled to a first and second decoupling the transmission line 34 and d 3 of d 4 according to ⁇ 21.
  • the required directional coupler can also meet the following structural parameters:
  • the characteristic impedance Z 0 of the first transmission line 311, the second transmission line 312, the third transmission line 313, the fourth transmission line 314, the first decoupling transmission line 33 and the second decoupling transmission line 34 is usually preset, for example, set Into 50 ⁇ ; h can be the impedance conversion factor. Therefore, according to the coupling degree D of the directional coupler calculated by equation (22), and then according to equations (24) and (25), the characteristic impedance of each branch of the directional coupler as shown in Figure 4 can be determined, and It is: a fifth transmission line 315 characteristic of the transmission line 317 and the seventh impedance Z 1, a transmission line 316 and the characteristics of the sixth and eighth transmission line 318 impedance Z 2. Furthermore, the line width of the transmission line corresponding to the characteristic impedance can be calculated in order to fabricate a directional coupler. Based on this method, the isolation of the multi-antenna system can be improved.
  • the characteristic impedance of the transmission line can meet the requirements by configuring the line width of the transmission line. For example, after obtaining the characteristic impedance Z 0 of the first transmission line 311, the second transmission line 312, the third transmission line 313, the fourth transmission line 314, the first decoupling transmission line 33, and the second decoupling transmission line 34 according to the above relationship, these The line width of the transmission line is configured such that its characteristic impedance satisfies the aforementioned characteristic impedance Z 0 . For example, determine the required thickness of the first transmission line 311, the second transmission line 312, the third transmission line 313, the fourth transmission line 314, the first decoupling transmission line 33 and the second decoupling transmission line 34, and the relative dielectric of the PCB board.
  • the line width of these transmission lines can be calculated. Therefore, according to the calculation result, the line widths of the first transmission line 311, the second transmission line 312, the third transmission line 313, the fourth transmission line 314, the first decoupling transmission line 33, and the second decoupling transmission line 34 are configured to obtain the above-mentioned characteristics.
  • the line widths of the fifth transmission line 315 and the seventh transmission line 317 can be configured to satisfy the aforementioned required characteristic impedance Z 1 .
  • the line width of the sixth transmission line 316 and the eighth transmission line 318 can be calculated according to the relationship between the characteristic impedance and the line width and the required characteristic impedance Z 2 .
  • the seventh configuration 315 and the sixth transmission line 317 and transmission line width eighth transmission line 318 according to a fifth transmission line 316 so as to obtain the above-mentioned plurality of transmission lines having a characteristic impedance of Z 1 and Z 2.
  • the aforementioned four-port network may also be other forms of directional couplers, such as coupled line directional couplers, miniaturized directional couplers, and broadband directional couplers.
  • FIG. 6 is a schematic diagram of a second decoupling structure for an array antenna according to an embodiment of the present application.
  • the decoupling structure in this embodiment is basically the same as the decoupling structure of the embodiment shown in FIG. 3 to FIG.
  • the first connection ports (for example, coupling ports) of the two decoupling networks 31 ′ are connected to the first phase shifter 333 through the third decoupling transmission line 331 and the fourth decoupling transmission line 332. That is, in FIG. 6, the first decoupling transmission line 33 in FIG. 3 is replaced with the third decoupling transmission line 331, the first phase shifter 333, and the fourth decoupling transmission line 332 that are connected in sequence.
  • the first connection port (for example, the coupling port) of the first decoupling network 31 and the first connection port (for example, the coupling port) of the second decoupling network 31' pass through sequentially
  • the connected third decoupling transmission line 331, the first phase shifter 333, and the fourth decoupling transmission line 332 are connected.
  • the phase shifter described in this article is a device that can adjust the phase of a signal, and its function is to shift the phase of the signal by an angle.
  • the first phase shifter 333 is an active phase shifter. It is pointed out here that the basic principle of the active phase shifter described in this article is to use the method of polar modulation to decompose the input signal into two orthogonal vectors, and then perform a weighted summation by changing the magnitude of the branch vector To change the phase of the output signal.
  • the phase of the first phase shifter 333 is P1.
  • the phase P1 can be adjusted so that the sum of the phase accumulation of P1 and the third decoupling transmission line 331 and the fourth decoupling transmission line 332 is approximately equal to an integer multiple of 2 ⁇ minus ⁇ 21 , which can also make P1 and the second decoupling transmission line 34
  • the sum of the phase accumulation of the third decoupling transmission line 331 and the fourth decoupling transmission line 332 is equal to an integer multiple of 2 ⁇ .
  • ⁇ 21 is the phase of isolation before decoupling.
  • the phase of the second decoupling transmission line 34 can also be designed to be approximately equal to an integer multiple of 2 ⁇ plus ⁇ 21 .
  • the coupling between the antenna units 10 and 20 can be changed.
  • the degree D1 that is, the isolation degree is changed
  • the decoupling between the antenna units 10 and 20 can be adjusted, for example, the decoupling frequency and the decoupling amplitude of the antenna units 10 and 20 can be adjusted. Based on this method, the isolation of the array antenna can be flexibly improved.
  • FIG. 7 is a schematic diagram of a third decoupling structure for an array antenna according to an embodiment of the present application.
  • the decoupling structure in this embodiment is basically the same as the decoupling structure of the embodiment shown in FIG. 3 to FIG.
  • the second connection ports (for example, isolation ports) of the two decoupling networks 31 ′ are connected to the second phase shifter 343 through the fifth decoupling transmission line 341 and the sixth decoupling transmission line 342. That is, in FIG. 7, the second decoupling transmission line 34 in FIG. 3 is replaced with the fifth decoupling transmission line 341, the second phase shifter 343, and the sixth decoupling transmission line 342 that are connected in sequence.
  • FIG. 7 is a schematic diagram of a third decoupling structure for an array antenna according to an embodiment of the present application.
  • the decoupling structure in this embodiment is basically the same as the decoupling structure of the embodiment shown in FIG. 3 to FIG.
  • the second connection ports (for example, isolation ports) of the two decoupling networks 31 ′ are connected
  • the second connection port (for example, the isolation port) of the first decoupling network 31 and the second connection port (for example, the isolation port) of the second decoupling network 31' pass through sequentially
  • the connected fifth decoupling transmission line 341, the second phase shifter 343, and the sixth decoupling transmission line 342 are connected.
  • the second phase shifter 343 is an active phase shifter.
  • the phase of the second phase shifter 343 is P2.
  • the phase P2 can be adjusted so that the sum of the phase accumulation of P2 and the fifth decoupling transmission line 341 and the sixth decoupling transmission line 342 is approximately equal to an integer multiple of 2 ⁇ plus ⁇ 21 , which can also make P2 and the first decoupling transmission line 33,
  • the sum of the phase accumulations of the fifth decoupling transmission line 341 and the sixth decoupling transmission line 342 is equal to an integer multiple of 2 ⁇ .
  • the phase of the first decoupling transmission line 33 can also be designed to be approximately equal to an integer multiple of 2 ⁇ minus ⁇ 21 .
  • the coupling between the antenna units 10 and 20 can be changed.
  • the degree D1 that is, the isolation degree is changed
  • the decoupling between the antenna units 10 and 20 can be adjusted, for example, the decoupling frequency and the decoupling amplitude of the antenna units 10 and 20 can be adjusted. Based on this method, the isolation of the array antenna can also be flexibly improved.
  • FIG. 8 is a schematic diagram of a third decoupling structure for an array antenna according to an embodiment of the present application.
  • the decoupling structure in this embodiment is basically the same as the decoupling structure of the embodiment shown in FIG. 3 to FIG.
  • the first connection port (for example, the coupling port) of the second decoupling network 31' is connected to the first phase shifter 333 through the third decoupling transmission line 331 and the fourth decoupling transmission line 332;
  • the second connection port (for example, the isolation port) and the second connection port (for example, the isolation port) of the second decoupling network 31' are connected to the second mobile through the fifth decoupling transmission line 341 and the sixth decoupling transmission line 342.
  • the first decoupling transmission line 33 in FIG. 3 is replaced by the third decoupling transmission line 331, the first phase shifter 333, and the fourth decoupling transmission line 332 that are connected in sequence;
  • the fifth decoupling transmission line 341, the second phase shifter 343, and the sixth decoupling transmission line 342 replace the second decoupling transmission line 34 in FIG. 3.
  • the first connection port (for example, the coupling port) of the first decoupling network 31 and the first connection port (for example, the coupling port) of the second decoupling network 31' pass through sequentially The connected third decoupling transmission line 331, the first phase shifter 333, and the fourth decoupling transmission line 332 are connected; the second connection port (for example, the isolation port) of the first decoupling network 31 and the second decoupling network 31'
  • the second connection port (for example, the isolation port) is connected through the fifth decoupling transmission line 341, the second phase shifter 343, and the sixth decoupling transmission line 342 that are connected in sequence.
  • the first phase shifter 333 and the second phase shifter 343 are both active phase shifters.
  • the phase of the first phase shifter 333 is P1, and the phase of the second phase shifter 343 is P2.
  • the phases P1 and P2 can be adjusted so that the sum of the phase accumulation of P1 and the third decoupling transmission line 331 and the fourth decoupling transmission line 332 is approximately equal to an integer multiple of 2 ⁇ minus ⁇ 21 , so that P2 and the fifth decoupling transmission line 341
  • the sum of the phase accumulations of the sixth decoupling transmission line 342 and the sixth decoupling transmission line 342 is approximately equal to an integer multiple of 2 ⁇ plus ⁇ 21 , so that P1, P2 and the third decoupling transmission line 331, the fourth decoupling transmission line 332, the fifth decoupling transmission line 341, and the sixth decoupling transmission line 341
  • the sum of the phase accumulation of the decoupled transmission line 342 is equal to an integer multiple of 2 ⁇ .
  • phase accumulation of the transmission line 342 can change the coupling D1 between the antenna units 10 and 20 (that is, change the isolation), and realize the adjustment of the decoupling between the antenna units 10 and 20, for example, to realize the decoupling of the antenna units 10 and 20.
  • the frequency of the coupling and the amplitude of the decoupling are adjustable. Based on this method, the isolation of the array antenna can be improved more flexibly.
  • FIG. 9 is a schematic flow chart of the decoupling method for an antenna device according to an embodiment of this application.
  • the decoupling method may mainly include the following operations S101-S102.
  • Operation S101 Provide an antenna device, the antenna device comprising: a first antenna unit and a second antenna unit arranged adjacently; a first decoupling network, the first decoupling network having an input port, an output port, and a first connection Port and a second connection port; the output port is connected to the first antenna unit, the input port is used to connect the first feed source; a second decoupling network, the second decoupling network has an input port, an output port , The first connection port and the second connection port; the output port of the second decoupling network is connected to the second antenna unit, and the input port of the second decoupling network is used to connect a second feed; A coupling transmission line, the first decoupling transmission line connecting the first connection port of the first decoupling network and the first connection port of the second decoupling network; and a second decoupling transmission line, the second decoupling The transmission line connects the second connection port of the first decoupling network and the second connection port of the second decoupling network; wherein at least one of the first decoup
  • Operation S102 adjusting the degree of coupling between the first antenna unit and the second antenna unit by adjusting the phase of the phase shifter.
  • the descriptions related to the first phase shifter 333 and/or the second phase shifter 343 in the present application can be applied to the operation S102, and details are not described herein again.
  • the decoupling method may further include the following operations: according to the phase accumulation of the decoupling transmission line where the phase shifter is located and the first antenna unit and the second antenna unit are not connected to the The phase of the isolation between the first decoupling network and the second decoupling network is used to adjust the phase of the phase shifter.
  • the decoupling method may further include the following operation: adjusting the phase of the phase shifter according to the phase accumulation of the first decoupling transmission line and the second decoupling transmission line.
  • the decoupling method may further include the following operations: designing the phase shifter as an active phase shifter.
  • the decoupling method may further include the following operations: setting the first connection port as one of a coupling port and an isolation port, and setting the second connection port as one of the isolation port and the coupling port another.
  • the decoupling method may further include the following operations: disposing the phase shifter in the first decoupling transmission line, and the first decoupling transmission line includes a third decoupling transmission line connected in sequence, The phase shifter and the fourth decoupling transmission line.
  • the decoupling method may further include the following operations: adjusting the phase of the first phase shifter so that the phase of the first phase shifter is the same as the third decoupling transmission line and the fourth decoupling transmission line.
  • the sum of the phase accumulation of the decoupling transmission line is approximately equal to an integer multiple of 2 ⁇ minus ⁇ 21 , where ⁇ 21 is that the first decoupling network and the second decoupling network are not connected between the first antenna unit and the second antenna unit.
  • the phase of the isolation in the coupling network may further include the following operations: adjusting the phase of the first phase shifter so that the phase of the first phase shifter is the same as the third decoupling transmission line and the fourth decoupling transmission line.
  • the sum of the phase accumulation of the decoupling transmission line is approximately equal to an integer multiple of 2 ⁇ minus ⁇ 21 , where ⁇ 21 is that the first decoupling network and the second decoupling network are not connected between the first antenna unit and the second antenna unit.
  • the decoupling method may further include the following operations: adjusting the phase of the first phase shifter so that the phase of the first phase shifter is related to the second decoupling transmission line and the third decoupling The sum of the phase accumulation of the transmission line and the fourth decoupling transmission line is equal to an integer multiple of 2 ⁇ .
  • the decoupling method may further include the following operations: further disposing a second phase shifter in the second decoupling transmission line, so that the second decoupling transmission line includes a fifth decoupling transmission line connected in sequence , The second phase shifter and the sixth decoupling transmission line.
  • the decoupling method may further include the following operations: adjusting the phase of the first phase shifter so that the phase of the first phase shifter is equal to that of the third decoupling transmission line and the fourth decoupling transmission line.
  • the sum of phase accumulation is approximately equal to an integer multiple of 2 ⁇ minus ⁇ 21 , where ⁇ 21 is when the first decoupling network and the second decoupling network are not connected between the first antenna unit and the second antenna unit The phase of isolation.
  • the decoupling method may further include the following operations: adjusting the phase of the second phase shifter so that the phase of the second phase shifter is equal to that of the fifth decoupling transmission line and the sixth decoupling transmission line.
  • the sum of phase accumulation is equal to an integer multiple of 2 ⁇ plus ⁇ 21 , where ⁇ 21 is the isolation between the first antenna unit and the second antenna unit when the first decoupling network and the second decoupling network are not connected Degree phase.
  • the decoupling method may further include the following operations: adjusting the phase of the first phase shifter and the phase of the second phase shifter so that the phase of the first phase shifter and the phase of the second phase shifter The sum of the phase of the second phase shifter and the phase accumulation of the third decoupling transmission line, the fourth decoupling transmission line, the fifth decoupling transmission line, and the sixth decoupling transmission line is equal to an integer multiple of 2 ⁇ .
  • the decoupling method may further include the following operations: setting the first decoupling network and the second decoupling network to have the same scattering parameter.
  • the decoupling method may further include the following operations: according to the isolation between the first antenna unit and the second antenna unit when the first decoupling network and the second decoupling network are not connected The strength of the degree to determine the degree of coupling of the first decoupling network.
  • the decoupling method may further include the following operations: defining the coupling degree of the first decoupling network as D, defining that the first antenna unit and the second antenna unit are not connected to the The strength of the isolation between the first decoupling network and the second decoupling network is S′ 12 , and these parameters satisfy the relationship defined by the above formula (22).
  • the electronic device of the present application may be a mobile phone 100a as shown in FIG. Wherein, an accommodating space is formed between the housing 41 and the display screen assembly 50. Other electronic components of the mobile phone, such as the main board, battery, and antenna device 60, are all arranged in the accommodating space.
  • the housing 41 may be made of plastic, glass, ceramic, fiber composite material, metal (for example, stainless steel, aluminum, etc.), or other suitable materials.
  • the housing 41 shown in FIG. 10 is substantially rectangular with rounded corners.
  • the housing 41 can also have other shapes, such as a circular shape, an oblong shape, an oval shape, and so on.
  • the display assembly 50 includes a display cover 51 and a display module 52.
  • the display module 52 is attached to the inner surface of the display cover 51.
  • the housing 41 is connected to the display cover 51 of the display assembly 50.
  • the display cover 51 may be made of glass;
  • the display module 52 may be an OLED flexible display structure, which may specifically include a substrate, a display panel (Panel), and auxiliary material layers, etc., in addition, the display module 52 and the display cover Structures such as a polarizing film can also be sandwiched between 51, and the detailed laminated structure of the display module 52 is not limited here.
  • the antenna device 60 may be completely contained in the housing 41, or may be embedded in the housing 41, and a part of the antenna device 60 may be exposed on the outer surface of the housing 41.
  • the antenna device 60 may include a plurality of antenna elements.
  • the antenna module 60 shown in FIGS. 11 to 15 is a four-element linear array, that is, has four antenna elements 10a, 20a, 10b, and 20b arranged in a straight line. Specifically, with reference to FIG.
  • the antenna device 60 includes a first substrate 61, a second substrate 62, a third substrate 63, and a radio frequency chip 64 that are sequentially stacked in layers, and a plurality of antenna units formed on the first substrate 61 ( 15 only shows two antenna elements 10a, 20a), a plurality of metal layers 661-668 (among them, the metal layer 665 is the ground layer 665) formed on the first substrate 61 and the third substrate 63, and pass through the first substrate 61 and the third substrate 63.
  • the feeder lines in the three substrates 63 and the second substrate 62, the first decoupling network 31 and the second decoupling network 31' provided on the third substrate 63, and the first decoupling transmission line 33 and the second decoupling network connected between them Decoupling transmission line 34.
  • the feeder has a one-to-one correspondence with the antenna units 10a, 20a, and is used to connect the corresponding antenna units 10a, 20a with the radio frequency chip 64, respectively.
  • the first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling transmission line 34 connected between them are used to connect the feeders corresponding to the adjacent antenna units 10a, 20a Together, they are used to cancel the coupling between the antenna elements 10a and 20a.
  • the first decoupling transmission line 33 and the second decoupling transmission line 34 may both be in the same plane layer, for example, arranged in the third substrate 63; in addition, the first decoupling transmission line 33 and the second decoupling transmission line 34 may be The arrangement is bent to meet the length design. It can be grounded properly, and the antenna device 60 may also include other signal transmission lines.
  • the antenna units 10a, 20a are used to send and receive radio frequency signals. As shown in FIG. 15, the two antenna units 10a and 20a are spaced apart from each other.
  • the antenna units 10a, 20a are double-layer patch antennas, including surface radiating plates 11a, 21a and inner radiating plates 12a, 22a that are isolated from each other and correspond to each other one-to-one.
  • the first substrate 61 includes a first outer surface 611 and a first inner surface 612 that are oppositely disposed.
  • the surface layer radiating sheets 11 a and 21 a are arranged on the first outer surface 611, and the inner layer radiating sheets 12 a and 22 a are arranged on the first inner surface 612.
  • the inner radiating fins 12a, 22a and the surface radiating fins 11a, 21a are isolated by the first substrate 61, so that the surface radiating fins 11a, 21a and the inner radiating fins 12a, 22a are separated by a certain distance, so as to meet the performance of the antenna frequency band Require.
  • the vertical projections of the surface radiating sheets 11a, 21a and the inner radiating sheets 12a, 22a on the first substrate 61 at least partially overlap.
  • the first substrate 61 may be made of thermosetting resin such as epoxy resin, thermoplastic resin such as polyimide resin, reinforcing material including glass fiber (or glass cloth, or glass fabric) and/or inorganic filler, and thermosetting resin and thermoplastic resin.
  • Resin insulating materials for example, prepreg, ABF (Ajinomoto Build-up Film), photosensitive dielectric (PID), etc.
  • the material of the first substrate 61 is not limited to this. That is, a glass plate or a ceramic plate can also be used as the material of the first substrate 61.
  • liquid crystal polymer (LCP) with low dielectric loss can also be used as the material of the first substrate 61 to reduce signal loss.
  • the first substrate 61 may be a prepreg. As shown in FIG. 15, the first substrate 61 includes three stacked prepregs. Among the three-layer prepregs of the first substrate 61, metal layers 662 and 663 are respectively provided between adjacent prepregs. The first outer surface of the first substrate 61 is further provided with a metal layer 661, and the metal layer 661 is located on the same layer as the surface radiation sheets 11a, 21a and insulated from each other. The first inner surface 612 of the first substrate 61 is provided with a metal layer 664, which is located on the same layer as the inner radiating sheets 12a, 22a and insulated from each other.
  • the metal layers 661, 662, 663, and 664 may be made of conductive materials such as metallic copper, aluminum, silver, tin, gold, nickel, lead, titanium, or their alloys. In this embodiment, the metal layers 661, 662, 663, and 664 are all copper layers.
  • the arrangement of the metal layer 661 reduces the difference between the copper spreading rate of the first outer surface 611 of the first substrate 61 and the copper spreading rate of other prepreg surfaces of the first substrate 61. During the manufacturing process of the first substrate 61, the copper spreading rate The reduction of the difference can reduce the generation of bubbles, thereby improving the manufacturing yield of the first substrate 61.
  • the arrangement of the metal layer 664 also reduces the difference between the copper spreading rate of the first inner surface 612 of the first substrate 61 and the copper spreading rate of other prepreg surfaces of the first substrate 61, so as to reduce the manufacturing process of the first substrate 61. The air bubbles are generated, thereby improving the manufacturing yield of the first substrate 61.
  • the first substrate 61 is also provided with grounding vias 613 penetrating through the first inner surface 612 and the first outer surface 611 to connect different metal layers 661, 662, 663 and 664 to each other and further to the ground layer 665.
  • the conductive material may be completely filled in the ground via 613, or the conductive material may be formed along the wall of the ground via 613 to form a conductive layer.
  • the conductive material may be copper, aluminum, silver, tin, gold, nickel, lead, titanium, or their alloys.
  • the ground via 613 may have a cylindrical shape, an hourglass shape, a cone shape, or the like.
  • the second substrate 62 includes a first side surface 621 and a second side surface 622, wherein the first side surface 621 is stacked on the first inner surface 612 of the first substrate 61.
  • the second substrate 62 may be the core layer of a PCB board, and is made of materials such as polyimide, polyethylene terephthalate, and polyethylene naphthalate.
  • the second substrate 62 is provided with a ground via 623 and a feeder via 624 penetrating through the first side surface 621 and the second side surface 622.
  • the ground layer 665 is sandwiched between the second substrate 62 and the third substrate 63.
  • the ground layer 665 is provided with a feeder via 665a.
  • the third substrate 63 includes a second outer surface 631 and a second inner surface 632 opposite to each other.
  • the second inner surface 632 of the third substrate 63 is stacked on the second side surface 622 of the second substrate 62, and the ground layer 665 is sandwiched between the second side surface 622 and the second inner surface 632.
  • the formation material of the third substrate 63 may be the same as the material of the first substrate 61.
  • the third substrate 63 may be a prepreg.
  • the third substrate 63 includes a three-layer prepreg.
  • metal layers 666 and 667 are provided between adjacent prepregs, which serve as feeder network and control line wiring layers, respectively.
  • a metal layer 668 is provided on the second outer surface 631 of the third substrate 63, and the metal layer 668 and the radio frequency chip 64 are welded together.
  • the metal layers 666, 667, and 668 may be made of conductive materials such as metallic copper, aluminum, silver, tin, gold, nickel, lead, titanium, or their alloys. In this embodiment, the metal layers 666, 667, and 668 are all copper layers.
  • the third substrate 63 is provided with wiring vias.
  • the wiring via includes a ground via 633 to connect the different metal layers 666, 667, and 668 to each other and further to the ground layer 665.
  • the wiring vias also include a feeder via 634 for the feeder to pass through, and a signal via 635 for the control line to pass through. Similar to the ground via 613 on the first substrate 61, the wiring via on the third substrate 63 can be completely filled with conductive material, or a conductive layer can be formed on the wall of the hole.
  • the shape of the various wiring vias can be cylindrical, hourglass, or cone-shaped.
  • the feeder line includes a first feeder line 31a and a second feeder line 32a connected by a decoupling network.
  • the first feed line 31a is connected to the radio frequency chip 64, and the second feed line 32a is connected to the inner radiating sheets 12a, 22a.
  • the feeder is insulated from each metal layer, such as the metal layers 666, 667, 668 and the ground layer in this embodiment. It is pointed out here that the first feeder line 31a in FIG. 15 may be connected to the first transmission line 311 in FIG. 3, and the second feeder line 32a may be connected to the second transmission line 312 in FIG. 3.
  • signal transmission lines are provided on the third substrate 63, such as a control line 68 and a power line 69.
  • the power cord 69 is disposed on the second outer surface 631 of the third substrate 63 and soldered on the radio frequency chip 64.
  • the control line 68 is arranged between the prepreg of the third substrate 63 close to the radio frequency chip 64 and the adjacent prepreg, and passes through the signal via 635 on the prepreg layer to connect to the radio frequency chip 64.
  • the third substrate 63 is also used to carry the first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling transmission line 34 connected between them.
  • the first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling transmission line 34 connected between them are connected to the adjacent antennas 10a, 20a.
  • the first decoupling network 31 is connected to the connection of the first feeder 31a and the second feeder 32a corresponding to one antenna unit 10a; specifically, the first transmission line 311 (see FIG.
  • the second decoupling network 31' is connected to the junction of the first feeder line 31a and the second feeder line 32a corresponding to the adjacent antenna unit 20a; that is, the first transmission line 311' of the second decoupling network 31' (See FIG. 5) It is connected to the first feeder 31a corresponding to the antenna unit 20a, and the second transmission line 312' of the second decoupling network 31' is connected to the second feeder 32a corresponding to the antenna unit 20a.
  • first decoupling network 31 and the second decoupling network 31' are arranged between two adjacent antenna units of the antenna device, and the first decoupling transmission line 33 and the second decoupling transmission line 34 are in the first decoupling network 31 and the second decoupling network 31' are connected, so after the signal sent from the radio frequency chip 64 passes through the first feeder 31a, a part of it is transmitted to the inner radiating sheet of the antenna unit through the first decoupling network 31 and the second feeder 32a 12a, the other part is transmitted to the second decoupling network 31' through the first decoupling network 31 and the first decoupling transmission line 33 and the second decoupling transmission line 34 to reach the adjacent antenna unit 20a, thereby canceling the two to a certain extent.
  • the degree of coupling between the two antenna units 10 and 20 can be determined by the S parameters of the first decoupling network 31 and the second decoupling network 31' and the lengths of the first decoupling transmission line 33 and the second decoupling transmission line 34. definition. Specifically, as in the above-mentioned embodiment of the array antenna, the lengths d 3 and d 4 of the first decoupling transmission line 33 and the second decoupling transmission line 34 of the antenna device 60 of this embodiment, the S parameters of the first decoupling network 31, And the preset coupling degree satisfies the following relationship:
  • the lengths d 3 and d 4 of the first decoupling transmission line 33 and the second decoupling transmission line 34 and the S parameter of the first decoupling network 31 can be configured to make the distance between the two antenna units 10 and 20
  • the coupling degree D1 is set to zero.
  • the initial isolation degree S12' between the two antenna elements 10 and 20 is calculated.
  • the coupling degree D of the directional coupler refer to the aforementioned formula (22) for details.
  • FIG. 14 it is a partial schematic diagram of the antenna device of FIG. 13, mainly showing the first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling network connected between them.
  • the arrangement of the transmission line of the second decoupling network 31' can be the same as the bending arrangement of the transmission line in the first decoupling network 31.
  • the lengths d 3 and d 4 of the first decoupling transmission line 33 and the second decoupling transmission line 34 can also be calculated according to the phase ⁇ 21 of the isolation before decoupling. For details, refer to the aforementioned formula (23).
  • the characteristic impedance of each branch of the directional coupler can be determined, namely: the first transmission line 311, the second transmission line 312, the third transmission line 313, and the fourth transmission line 311.
  • Z 2 refer to the aforementioned formulas (24) and (25) for details.
  • the line width of the transmission line corresponding to the characteristic impedance can be calculated in order to fabricate a directional coupler.
  • the characteristic impedance of the transmission line can be configured to meet the requirements by configuring the line width of the transmission line.
  • a first transmission line 311, second transmission line 312, the third transmission line 313, a fourth transmission line 314, transmission line 33 is coupled to the first and the second decoupling the transmission line 34 is configured so that the line width of the impedance characteristic satisfies the characteristic impedance Z 0 .
  • the line widths of the fifth transmission line 315 and the seventh transmission line 317 are configured such that their characteristic impedance satisfies the aforementioned characteristic impedance Z 1 .
  • the line widths of the sixth transmission line 316 and the eighth transmission line 318 are configured such that their characteristic impedance satisfies the aforementioned characteristic impedance Z 2 .
  • the length of the first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling transmission line connected between them can be formed on the layer where the metal layer 666 is located. 34. It is understandable that when the linear distance between the feed lines corresponding to the adjacent antenna units 10a, 20a is small, the first decoupling transmission line 33 and the second decoupling transmission line 34 can form a bent pattern to meet the length requirement ( As shown in Figure 13 and Figure 14). In some other embodiments, the first decoupling transmission line 33 may also be in a curved pattern, as long as the length requirement is met.
  • the first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling transmission line 34 connected between them are located at the surface radiating plates 11a, 21a and the inner radiating plates 12a, 22a. Different layers. As shown in FIG. 15, the first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling transmission line 34 connected between them are arranged under the antenna units 10a, 20a, For example, in the third substrate 63.
  • first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling transmission line 34 connected between them may also be connected to the metal layer. 667 or 668 on the same floor.
  • the antenna units 20a and 10b and the antenna units 10b and 20b can also be provided with the decoupling structure of the present application in the same way.
  • a third decoupling network 35 and a fourth decoupling network 35' and a third decoupling network connected between the third decoupling network 35 and the fourth decoupling network 35' can be provided for the antenna units 20a and 10b.
  • the transmission line 33' and the fourth decoupling transmission line 34'; the third decoupling network 35 can be the same as or similar to the above-mentioned first decoupling network 31, and the fourth decoupling network 35' can be the above-mentioned second decoupling network
  • the network 31' is the same or similar; the third decoupling transmission line 33' can be the same as or similar to the aforementioned first decoupling transmission line 33, and the fourth decoupling transmission line 34' can be the same or similar to the aforementioned second decoupling transmission line 34. similar.
  • the second decoupling network 31' and the third decoupling network 35 can share part of the transmission line, for example, the first transmission line 311', the second transmission line 312', and the fifth transmission line of the second decoupling network 31'. 315' (see Figure 5).
  • these decoupling networks and decoupling transmission lines can also be distributed in different layers.
  • the first decoupling network 31 and the second decoupling network 31' and the first decoupling transmission line 33 and the second decoupling transmission line 34 connected between them can be distributed on the layer where the metal layer 666 shown in FIG. 15 is located.
  • the third decoupling network 35 and the fourth decoupling network 35' and the third decoupling transmission line 33' and the fourth decoupling transmission line 34' connected between the third decoupling network 35 and the fourth decoupling network 35' It can be distributed in the layer where the metal layer 667 shown in FIG. 15 is located.
  • FIG. 16 is a schematic diagram of an antenna device according to another embodiment of the present application.
  • the top portion of the middle frame 42 of the mobile phone can be divided into two sections by the slot 44, and the two sections can be used as the first antenna 10a and the second antenna 20a, respectively.
  • the middle frame 42 can be provided with a circuit board 43.
  • the first decoupling network 31 and the second decoupling network 31', as well as the first decoupling transmission line 33 and the second decoupling transmission line 34 (see FIG. 3) described above in this application can be It is arranged on the circuit board 43.
  • the feed source 40 and the feed source 40' can be connected to the circuit board 43, which in turn is connected to the first antenna 10a and the second antenna 20a.
  • the slit 44 can usually be arranged non-centrally, for example, arranged close to the left side or the right side of the middle frame 42.
  • the center operating frequency of the four-element linear array is 28 GHz. It is pointed out here that according to the 3GPP TS 38.101 protocol, the frequency between 24.25 GHz and 52.6 GHz is usually called millimeter wave (mm Wave); therefore, the decoupling structure proposed in this application can be a millimeter wave array antenna Decoupling structure.
  • the antenna device of the present application introduces the concept of a decoupling network under the antenna unit, and there is no need to change the structure of the array antenna unit, and only the length d 3 of the first decoupling transmission line 33 and the second decoupling transmission line 34 is required.
  • the coupling degree D1 between the antenna units 10 and 20 can be adjusted, that is, the mutual coupling between the antenna units can be reduced, the scanning angle can be expanded, and the scanning gain can be improved.
  • the coupling degree D of the directional coupler can be calculated according to the magnitude of the isolation before decoupling, and then the characteristic impedance of each branch of the directional coupler can be determined according to the formula, and then the line width of the transmission line corresponding to the characteristic impedance can be calculated.
  • Produced a directional coupler Based on this method, the isolation of the multi-antenna system can be improved.
  • the phase shifter is used in the decoupling structure, the phase of the first phase shifter 333 and/or the second phase shifter 343 is changed, and the phase shifter is adjusted to the first phase shifter 333 and/or the second phase shifter.
  • phase accumulation of these decoupling transmission lines connected to the phase converter 343 can also change the coupling degree D1 between the antenna units 10 and 20, so that the decoupling between the antenna units 10 and 20 can be adjusted. Based on these methods, the isolation of the array antenna can be flexibly improved.

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Abstract

本申请提供一种天线装置、电子设备和用于天线装置的去耦方法。该天线装置包括：第一天线单元和第二天线单元；第一去耦网络和第二去耦网络，均具有输入端口、输出端口、第一连接端口和第二连接端口；第一去耦网络的输出端口连接第一天线单元，第一去耦网络的输入端口用于连接第一馈源；第二去耦网络的输出端口连接第二天线单元，第二去耦网络的输入端口用于连接第二馈源；第一去耦传输线，连接第一去耦网络的第一连接端口与第二去耦网络的第一连接端口；第二去耦传输线，连接第一去耦网络的第二连接端口与第二去耦网络的第二连接端口。第一去耦传输线和该第二去耦传输线的至少一个中设置有移相器。本申请可灵活地提高多天线系统的隔离度。

Description

天线装置、电子设备和用于天线装置的去耦方法 【技术领域】
本申请涉及天线去耦技术领域，具体涉及一种天线装置、电子设备和用于天线装置的去耦方法。
【背景技术】
天线可以高效地发射与接收电磁波，是无线通信系统中不可或缺的重要组成部分。然而，随着科学技术的进步，单个天线难以满足日益增高的性能需求。为了解决单个天线的方向性较差和辐射增益较低等问题，可将若干个辐射特性相同的天线单元按照一定的几何结构排列起来组成阵列天线，从而增强阵列天线的辐射性能，产生较为灵活的方向图，以满足不同场景的需求。
【发明内容】
本申请一个方面提供一种天线装置，其包括：相邻设置的第一天线单元和第二天线单元；第一去耦网络，所述第一去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述输出端口连接所述第一天线单元，所述输入端口用于连接第一馈源；第二去耦网络，所述第二去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述第二去耦网络的输出端口连接所述第二天线单元，所述第二去耦网络的输入端口用于连接第二馈源；第一去耦传输线，所述第一去耦传输线连接所述第一去耦网络的第一连接端口与所述第二去耦网络的第一连接端口；第二去耦传输线，所述第二去耦传输线连接所述第一去耦网络的第二连接端口与所述第二去耦网络的第二连接端口。所述第一去耦传输线和所述第二去耦传输线的至少一个中设置有移相器。
在另一方面，本申请还提供一种电子设备，其包括：壳体；显示屏组件，与所述壳体连接，并与所述壳体形成容置空间；馈源，设置在所述容置空间内；以及天线装置，至少部分设置在所述容置空间内。所述天线装置包括：多个天线单元；多个去耦网络，与所述多个天线单元一一对应，其中，每个去耦网络均具有输入端口、输出端口、第一连接端口和第二连接端口；所述输出端口与对应的天线单元连接，所述输入端口与所述馈源连接；第一去耦传输线，所述第一去耦传输线连接在相邻的所述去耦网络的第一连接端口之间；第二去耦传输线，所述第二去耦传输线连接在相邻的所述去耦网络的第二连接端口之间。所述第一去耦传输线和所述第二去耦传输线的至少一个中设置有移相器。
在又一方面，本申请还提供一种用于天线装置的去耦方法，所述天线装置包括：相邻设置的第一天线单元和第二天线单元；第一去耦网络，所述第一去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述输出端口连接所述第一天线单元，所述输入端口用于连接第一馈源；第二去耦网络，所述第二去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述第二去耦网络的输出端口连接所述第二天线单元，所述第二去耦网络的输入端口用于连接第二馈源；第一去耦传输线，所述第一去耦传输线连接所述第一去耦网络的第一连接端口与所述第二去耦网络的第一连接端口；以及第二去耦传输线，所述第二去耦传输线连接所述第一去耦网络的第二连接端口与所述第二去耦网络的第二连接端口；其中，所述第一去耦传输线和所述第二去耦传输线的至少一个中设置有移相器；所述去耦方法包括：通过调整所述移相器的相位来调整所述第一天线单元和第二天线单元之间的耦合度。
本申请由于在所述第一去耦传输线和所述第二去耦传输线的至少一个中设置有移相器，因此通过改变移相器的相位，以及调节与移相器连接的这些去耦传输线的相位积累，可改变天线单元之间的耦合度，实现天线单元之间去耦的可调化。基于这些方法，可以灵活地提高天线装置和电子设备的隔离度。
【附图说明】
为了更清楚地说明本申请实施例中的技术方案，下面将对实施例描述中所需要使用的附图作简单地介绍。显而易见地，下面描述中的附图仅仅是本申请的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其他的附图，其中：
图1是本申请实施例的电子设备的结构示意图；
图2是本申请实施例的用于阵列天线的去耦原理示意图；
图3是本申请实施例的第一种用于阵列天线的去耦结构示意图；
图4是本申请实施例的第一去耦网络的结构示意图；
图5是本申请实施例的第二去耦网络的结构示意图；
图6是本申请实施例的第二种用于阵列天线的去耦结构示意图；
图7是本申请实施例的第三种用于阵列天线的去耦结构示意图；
图8是本申请实施例的第四种用于阵列天线的去耦结构示意图；
图9是本申请实施例的用于阵列天线的去耦方法的流程示意图；
图10是本申请实施例的电子设备的立体结构示意图。
图11是本申请实施例的天线装置的立体视图；
图12是图11的天线装置的俯视图；
图13是图11的天线装置的仰视图；
图14是图13的天线装置的局部示意图，其显示了天线装置的第一去耦网络和第二去耦网络以及连接在他们之间的第一去耦传输线和第二去耦传输线的布置；
图15是本申请实施例的天线装置的层状结构示意图，其中显示了两个天线单元；
图16是本申请另一实施例的天线装置的示意图。
【具体实施方式】
下面将结合本申请实施例中的附图，对本申请实施例中的技术方案进行清楚、完整地描述。显然，所描述的实施例仅是本申请的一部分实施例，而不是全部的实施例。基于本申请中的实施例，本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其他实施例，都属于本申请保护的范围。
在本文中提及“实施例”意味着，结合实施例描述的特定特征、结构或特性可以包含在本申请的至少一个实施例中。在说明书中的各个位置出现该短语并不一定均是指相同的实施例，也不是与其他实施例互斥的独立的或备选的实施例。本领域技术人员显式地和隐式地理解的是，本文所描述的实施例可以与其他实施例相结合。
阵列天线，尤其是小间距阵列天线，存在着互耦较强的问题。天线单元间的互耦在很大程度上影响天线单元及其阵列的匹配特性和空间辐射特性，具体表现为以下几点。
(1)方向图：天线单元上的电流在互耦作用下其分布发生了改变，导致部分辐射能量进一步耦合到其他天线单元，其中一部分耦合能量被端接负载吸收而消耗，而另一部分能量又会再次辐射。所以，天线单元的方向图会发生畸变。此处所述的端接负载是天线馈源后端等效出来的一个参数；在画等效电路时，可将天线馈源的整个后端用一个电阻来代替，并可称为端接负载。
(2)输入阻抗：受到互耦影响，阵列中天线单元的输入阻抗会发生改变，并与孤立环境中天线单元的输入阻抗不同，因此各阵列中天线单元的匹配情况不同并且匹配特性会受到影响。
(3)增益：在天线单元中存在热损耗以及特性阻抗不匹配引起的反射损耗等，从而使得天线单元的辐射功率比发射功率要小，反射系数在互耦的作用下会发生变化，故天线单元的增益受到影响。
在相关技术中，解决互耦效应对天线单元的方向图、输入阻抗、增益等特性的影响方面，通常采用以下五种方法：缺陷地结构(DGS-Defected Ground Structure)去耦法、中和线法(NLT-Neutralization Line Technique)去耦法、带阻滤波去耦法、电磁带隙结构(EBG,Electromagnetic Band Gap)去耦法、超材料去耦法(MDT,Metamaterial Decoupling Technique)。
然而，上述方法都是针对天线单元间耦合消除方法的研究，未能对天线单元间耦合效应进行精确定义与控制。
本申请提供了一种电子设备，该电子设备的阵列天线可以对天线单元间的耦合效应进行自定义，并通过耦合效应的设计实现对天线单元的辐射方向图的控制，例如拓宽扫描角、提升扫描增益、消除扫描盲区等。
该电子设备可以是手机、平板电脑、PDA(Personal Digital Assistant，个人数字助理)、POS(Point of Sales，销售终端)、车载电脑、CPE(Customer Premise Equipment，客户前置设备)等终端设备。以下以手机作为示例对本申请进行介绍。
如图1所示，手机100可以包括：RF(Radio Frequency，射频)电路101、存储器102、中央处理器(Central Processing Unit，CPU)103、外设接口104、音频电路105、扬声器106、电源管理芯片107、输入/输出(I/O)子系统108、触摸屏109、其他输入/控制设备110以及外部端口111，这些部件通过一个或多个通信总线或信号线112来通信。
应该理解的是，图示手机仅仅是电子设备的一个范例，并且手机100可以具有比图中所示出的更多的或者更少的部件，可以组合两个或更多的部件，或者可以具有不同的部件配置。图中所示出的各种部件可以在包括一个或多个信号处理和/或专用集成电路在内的硬件、软件、或硬件和软件的组合中实现。
下面结合图1对手机100的各个构成部件进行具体的介绍。
射频(RF)电路101主要用于建立手机与无线网络(即网络侧)的通信，实现手机与无线网络的数据接收和发送。例如收发短信息、电子邮件等。具体地，RF电路101接收并发送RF信号，RF信号也称为电磁信号，RF电路101将电信号转换为电磁信号或将电磁信号转换为电信号，并且通过该电磁信号与通信网络以及其他设备进行通信。RF电路101可以包括用于执行这些功能的已知电路，其包括但不限于具有天线阵列的天线系统、RF收发机、一个或多个放大器、调谐器、一个或多个振荡器、数字信号处理器、CODEC(COder-DECoder，编译码器)芯片组、用户标识模块(Subscriber Identity Module，SIM)等等。
存储器102可以被CPU 103、外设接口104等访问，所述存储器102可以包括高速随机存取存储器，还可以包括非易失性存储器，例如一个或多个磁盘存储器件、闪存器件、或其他易失性固态存储器件。
中央处理器103通过运行存储在存储器102的软件程序以及模块，从而执行电子设备的各种功能应用以及数据处理。
外设接口104可以将设备的输入和输出外设连接到CPU 103和存储器102。
I/O子系统108可以将设备上的输入输出外设，例如触摸屏109和其他输入/控制设备110，连接到外设接口104。I/O子系统108可以包括显示控制器1081和用于控制其他输入/控制设备110的一个或多个输入控制器1082。其中，一个或多个输入控制器1082从其他输入/控制设备110接收电信号或者向其他输入/控制设备110发送电信号，其他输入/控制设备110可以包括物理按钮(按压按钮、摇臂按钮等)、拨号盘、滑动开关、操纵杆、点击滚轮。值得说明的是，输入控制器1082可以与以下任一个连接：键盘、红外端口、USB接口以及诸如鼠标的指示设备。
触摸屏109是用户终端与用户之间的输入接口和输出接口，将可视输出显示给用户，可视输出可以包括图形、文本、图标、视频等。
I/O子系统108中的显示控制器1081从触摸屏109接收电信号或者向触摸屏109发送电信号。触摸屏109检测触摸屏上的接触，显示控制器1081将检测到的接触转换为与显示在触摸屏109上的用户界面对象的交互，即实现人机交互，显示在触摸屏109上的用户界面对象可以是运行游戏的图标、联网到相应网络的图标等。值得说明的是，设备还可以包括光鼠，光鼠是不显示可视输出的触摸敏感表面，或者是由触摸屏形成的触摸敏感表面的延伸。
音频电路105主要用于从外设接口104接收音频数据，将该音频数据转换为电信号，并且将该电信号发送给扬声器106。
扬声器106用于将手机100通过RF电路101从无线网络接收的语音信号，还原为声音并向用户播放该声音。
电源管理芯片107用于为CPU 103、I/O子系统108及外设接口104所连接的硬件进行供电及电源管理。
以下针对该电子设备的RF电路101的天线系统中的阵列天线进行介绍。该阵列天线通常包括多个紧密布置的天线单元。在至少两个相邻的天线单元中，每个天线单元与馈源之间均通过去耦网络连接。本申请的描述中，“多个”的含义是至少两个，例如两个，三个等，除非另有明确具体的限定。
本实施例以两个相邻的天线单元10和20作为示例来对本申请进行介绍。如图2所示，其是本申请实施例的用于阵列天线的去耦原理示意图，该阵列天线包括相邻的天线单元10和天线单元20。天线单元10和天线单元20的辐射特性可以相同也可以不同。天线单元10可以从电子设备的馈源(射频收发器)接收激励电流，经放大、滤波、匹配调谐后激励天线单元10谐振于对应频率，从而产生对应频率的电磁波信号，与自由空间相同频率的电磁波信号耦合实现信号发射。天线单元10还可以在激励信号的激励下谐振于对应频率的天线单元耦合来自自由空间相同频率的电磁波信号，从而在天线单元10上形成感应电流，该感应电流经滤波、放大后进入射频收发器。
相邻的两个天线单元10和20所对应的去耦网络之间相互连接，其中天线单元10对应的是第一去耦网络31，天线单元20对应的是第二去耦网络31’。第一去耦网络31和第二去耦网络31’均为四端口网络。第一去耦网络31具有连接馈源的输入端口(a 1,b 1)、连接天线单元10的输出端口(a 2,b 2)以及用于连接第二去耦网络31’的第一连接端口(a 3,b 3)和第二连接端口(a 4,b 4)。第二去耦网络31’具有连接馈源的输入端口(a’ 1,b’ 1)、连接天线单元20的输出端口(a’ 2,b’ 2)以及用于连接第一去耦网络31的第一连接端口(a’ 3,b’ 3)和第二连接端口(a’ 4,b’ 4)。长度为d 1的传输线可形成输出端口(a 2,b 2)，并且具有特性阻抗Z 0；长度为d 2的传输线可形成输出端口(a’ 2,b’ 2)，并且具有特性阻抗Z 0。长度为d 3的第一去耦传输线连接第一去耦网络31的第一连接端口(a 3,b 3)与第二去耦网络31’的第一连接端口(a’ 3,b’ 3)，并且具有特性阻抗Z 3；长度为d 4的第二去耦传输线连接第一去耦网络31的第二连接端口(a 4,b 4)与第二去耦网络31’的第二连接端口(a’ 4,b’ 4)，并且具有特性阻抗Z 4。另外，a 1，a 2，a’ 1，a’ 2，a 3，a 4，a’ 3，a’ 4是入射电压波振幅，b 1，b 2，b’ 1，b’ 2，b 3，b 4，b’ 3，b’ 4是反射电压波振幅。值得一提的是，本申请实施例中的“输入端口”和“输出端口”均只是从天线单元10发射信号的角度进行命名。可以理解地，天线单元10还可以接收信号，此时，上述“输出端口”可以作为输入端口，上述“输入端口”则可以作为输出端口，即，本申请的“输入端口”和“输出端口”的命名并不对端口的属性构成限定。还需要指出的是，图2中长度为d 1的传输线一侧还显示了具有特性阻抗Z 0的传输线，但这两条传输线在实物上对应的是同一条导线；同样地，长度为d 2的传输线、长度为d 3的第一去耦传输线和长度为d 4的第二去耦传输线也应如此理解。特性阻抗Z 3、特性阻抗Z 4可设置成与特性阻抗Z 0相等。另外，该特性阻抗Z 0通常是预先设定的，例如设定成50Ω。
如图3所示，其是本申请实施例的第一种用于阵列天线的去耦结构示意图，其中至少第一去耦网络31、第二去耦网络31’以及连接在其间的第一去耦传输线33和第二去耦传输线34可组成本申请用于阵列天线的去耦结构。另外，该去耦结构和与之连接的阵列天线也可形成本申请的天线装置。
下文对图3和图4中天线单元10对应的第一去耦网络31的示例进行具体介绍。可以理解的是，天线单元20对应的第二去耦网络31’可以与天线单元10对应的第一去耦网络31相同。
具体地，如图3和图4所示，第一去耦网络31为四端口网络。在一实施例中，该四端口网络为定向耦合器，其可包括定向耦合器主体310和从该定向耦合器主体310伸出的四条传输线。这四条传输线包括第一传输线311、第二传输线312、第三传输线313和第四传输线314。另外，该定向耦合器的第一连接端口(a 3,b 3)可为耦合端口或隔离端口；相应地，该定向耦合器的第二连接端口(a 4,b 4)可为隔离端口或耦合端口。
该定向耦合器主体310可包括第五传输线315、第六传输线316、第七传输线317和第八传输线318。该第五传输线315、第六传输线316、第七传输线317和第八传输线318首尾顺次连接成多边形，以形成一回路。
其中，第一传输线311的第一端与第五传输线315的第一端连接，第一传输线311的第二端形成与馈源40连接的输入端口。第二传输线312的第一端与第五传输线315的第二端连接，第二传输线312的第二端形成与天线单元10连接的输出端口。第三传输线313的第一端与第七传输线317的第一端连接，第三传输线313的第二端形成与第一去耦传输线33的第一端连接的第一连接端口。第四传输线314的第一端与第七传输线317的第二端连接，第四传输线314的第二端形成与第二去耦传输线34的第一端连接的第二连接端口。在此指出，文中所述的某一传输线的第一端和第二端指的是该传输线的两个相对末端。
第三传输线313和第四传输线314可设计成具有较短长度，例如，第三传输线313和第四传输线314的长度仅能与第一去耦传输线33和第二去耦传输线34连接即可，而不再具有冗余长度。这可降低对第一去耦传输线33和第二去耦传输线34的长度设计的影响。
第五传输线315和第七传输线317的特性阻抗可设计为Z 1，第六传输线316和第八传输线318的特性阻抗可设计为Z 2。另外，第五传输线315、第六传输线316、第七传输线317和第八传输线318的长度均可设置为(1/4)λ，其中λ为波长。
如图3和图5所示，天线单元20对应的第二去耦网络31’可以与上述的第一去耦网络31相同。具体而言，第二去耦网络31’为四端口网络。在一实施例中，该四端口网络为定向耦合器，其可包括定向耦合器主体310’和从该定向耦合器主体310’伸出的四条传输线。这四条传输线包括第一传输线311’、第二传输线312’、第三传输线313’和第四传输线314’。另外，该定向耦合器的第一连接端口(a’ 3,b’ 3)可为耦合端口或隔离端口；相应地，该定向耦合器的第二连接端口(a’ 4,b’ 4)可为隔离端口或耦合端口。
该定向耦合器主体310’可包括第五传输线315’、第六传输线316’、第七传输线317’和第八传输线318’。该第五传输线315’、第六传输线316’、第七传输线317’和第八传输线318’首尾顺次连接，以形成一回路。
其中，第一传输线311’的第一端与第五传输线315’的第一端连接，第一传输线311’的第二端形成与馈源40’连接的输入端口。第二传输线312’的第一端与第五传输线315’的第二端连接，第二传输线312’的第二端形成与天线单元20连接的输出端口。第三传输线313’的第一端与第七传输线317’的第一端连接，第三传输线313’的第二端形成与第一去耦传输线33的第二端连接的第一连接端口。第四传输线314’的第一端与第七传输线317’的第二端连接，第四传输线314’的第二端形成与第二去耦传输线34的第二端连接的第二连接端口。馈源40和馈源40’可是同一个馈源。
第三传输线313’和第四传输线314’可设计成具有较短长度，例如，第三传输线313’和第四传输线314’的长度仅能与第一去耦传输线33和第二去耦传输线34连接即可，而不再具有冗余长度。这可降低对第一去耦传输线33和第二去耦传输线34的长度设计的影响。
第五传输线315’和第七传输线317’的特性阻抗可设计为Z 1，第六传输线316’和第八传输线318’的特性阻抗可设计为Z 2。另外，第五传输线315’、第六传输线316’、第七传输线317’和第八传输线318’的长度均可设置为(1/4)λ。
再结合图3所示，第一去耦传输线33和第二去耦传输线34均连接在第一去耦网络31和第二去耦网络31’之间。具体而言，第一去耦传输线33的第一端连接第一去耦网络31的第一连接端口，也就是连接第三传输线313的第二端；第一去耦传输线33的第二端连接第二去耦网络31’的第一连接端口，也就是连接第三传输线313’的第二端。类似地，第二去耦传输线34的第一端连接第一去耦网络31的第二连接端口，也就是连接第四传输线314的第二端；第二去耦传输线34的第二端连接第二去耦网络31’的第二连接端口，也就是连接第四传输线314’的第二端。
在图3至图5中，第一传输线311、第二传输线312、第三传输线313、第四传输线314、第一传输线311’、第二传输线312’、第三传输线313’、第四传输线314’、第一去耦传输线33和第二去耦传输线34的特性阻抗可设计为Z 0。另外，第一去耦传输线33的长度可设为d 3，第二去耦传输线34的长度可设为d 4。
在此指出，本申请中的术语“第一”、“第二”、“第三”仅用于描述目的，而不能理解为指示或暗示相对重要性或者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”、“第三”的特征可以明示或者隐含地包括至少一个该特征。
第一去耦传输线33和第二去耦传输线34用于传输信号以抵消两个天线单元10、20之间的互耦。其中，两个天线单元10、20之间的耦合度D1可以通过第一去耦网络31和第二去耦网络31’的散射参数(即，S参数)以及第一去耦传输线33与第二去耦传输线34的长度d 3和d 4来进行定义。例如，如果要求两个天线单元10、20之间的耦合度D1达到预设耦合度，则可以将四端口网络的S参数和第一去耦传输线33与第二去耦传输线34的长度d 3，d 4配置为使天线单元10、20之间的耦合度D1满足预设的耦合度。在此指出，两个天线单元10、20之间的耦合度D1与两个天线单元10、20之间的隔离度成反比关系；也就是说，两个天线单元10、20之间的隔离度越高，则两个天线单元10、20之间的耦合度D1越低。
容易明白的是，当第一去耦网络31和第二去耦网络31’采用相同的结构时，他们的S参数也是相同的。从而，在第一去耦网络31和第二去耦网络31’相同的情况下，两个天线单元10、20之间的耦合度D1与第一去耦网络31的S参数以及第一去耦传输线33与第二去耦传输线34的长度d 3，d 4之间的关系可以通过以下方式获得。
第一去耦网络31的S参数的矩阵S 0为：
Figure PCTCN2021088836-appb-000001
其中，S 12、S 13、S 31是第一去耦网络31为四端口网络时的其中三个S参数，具体而言，这三个S参数均是互耦系数，又可称耦合系数。
在参考面Ⅲ处(该参考面Ⅲ可通过数学推导选定)，第一去耦网络31的第一连接端口和第二连接端口分别连接了长度为d 3和d 4的第一去耦传输线33和第二去耦传输线34，故第一去耦网络31的S参数的矩阵S可由式(1)中的S参数演算得到：
Figure PCTCN2021088836-appb-000002
其中，e为自然常数，j为虚数的表示符号，k为波数，且式(1)中的S 31等于式(2)中的S 13。
第一去耦网络31与第二去耦网络31’未连接前组成一个八端口网络，其S参数的关系式为：
Figure PCTCN2021088836-appb-000003
式(3)中，a1-a’ 4是入射电压波振幅，b1-b’ 4是反射电压波振幅。
其中：
Figure PCTCN2021088836-appb-000004
将式(3)中的矩阵写为分块矩阵形式：
Figure PCTCN2021088836-appb-000005
其中，S 11、S 22、S 21是四端口网络的其中三个S参数，且S 11是反射系数，S 21是互耦系数。
写成方程组形式：
Figure PCTCN2021088836-appb-000006
由式(6)可将式(4)简写为：
[a 2]＝[Γ]·[b 2]    (7)
将式(7)代入式(6)可知：
Figure PCTCN2021088836-appb-000007
由式(8)中第②式可得：
[b 2]＝{E-[S 22][Γ]} -1[S 21][a 1]     (9)
式(9)中，E代表单位矩阵。
将式(9)代入式(8)中第①式可得：
[b 1]＝[S 11][a 1]+[S 12][Γ]{E-[S 22][Γ]} -1[S 21][a 1]     (10)
由式(10)可得到，第一去耦网络31和第二去耦网络31’之间通过第一去耦传输线33和第二去耦传输线34连接后形成的新的四端口网络(1、2、1’、2’)的S参数的矩阵S Four-port为：
S Four-port＝[S 11]+[S 12][Γ]{E-[S 22][Γ]} -1[S 21]      (11)
在此指出，这里的新的四端口网络的四个端口是指第一去耦网络31和第二去耦网络31’连接后，组成的整体对外的四个端口(a 1,b 1)、(a 2,b 2)、(a’ 1,b’ 1)和(a’ 2,b’ 2)。
将式(3)和式(5)所规划的分块矩阵代入式(11)，即可得到该新的四端口网络的新的S参数的矩阵S Four-port为：
Figure PCTCN2021088836-appb-000008
通过数字运算，可得该新的四端口网络的S参数的矩阵S Four-port为：
Figure PCTCN2021088836-appb-000009
将该新的四端口网络的端口顺序调整为1→1'→2→2'，则式(13)变为：
Figure PCTCN2021088836-appb-000010
将式(14)改写成分块矩阵的形式：
Figure PCTCN2021088836-appb-000011
设该两个天线单元10和20形成的二元天线的S参数的矩阵S array为：
Figure PCTCN2021088836-appb-000012
式(16)中，S’ 12为初始隔离度的幅度，即，两个相邻的天线单元10和20之间未连接去耦网络时的隔离度的强度；S’ 11、S’ 21和S’ 22分别为两个相邻的天线单元10和20之间未连接去耦网络时输入端口(a 1,b 1)的反射系数、隔离度和输出端口(a 2,b 2)的反射系数。
第一去耦网络31和第二去耦网络31’之间通过第一去耦传输线33和第二去耦传输线34连接在一起后，形成的新的四端口网络再与两个天线单元10和20连接后，组建成一个二端口网络。该二端口网络的S参数的矩阵[S]为：
[S]＝[S 11]+[S 12][S array]{E-[S 22][S array]} -1[S 21]     (17)
在此指出，这里的二端口网络的二端口是指该新的四端口网络连接了天线单元10和20之后，只剩下的两个与馈源连接的端口(a 1,b 1)和(a’ 1,b’ 1)。
将式(14)与式(15)所定义的分块矩阵代入式(17)，可得：
Figure PCTCN2021088836-appb-000013
由式(18)可知，通过设计第一去耦传输线33和第二去耦传输线34的长度d 3与d 4，以及四端口网络的S参数，即可精确定义天线单元间的耦合度D1。也即，当预设好所需的耦合度后，上式可表示为：
Figure PCTCN2021088836-appb-000014
因此，可以将第一去耦传输线33和第二去耦传输线34的长度d 3与d 4和四端口网络的S参数配置为使天线单元10、20之间的耦合度D1满足预设耦合度。
举例而言，当需要去耦网络将两个天线单元10、20之间的互耦完全抵消时，令预设耦合度为0，则：
Figure PCTCN2021088836-appb-000015
进一步地，在令预设耦合度为0的情况下，可将S 1' 2用四端口网络的S参数表示：
Figure PCTCN2021088836-appb-000016
令四端口网络(例如，前述的耦合器)的耦合系数S 13＝D，则
Figure PCTCN2021088836-appb-000017
代入上式可得：
Figure PCTCN2021088836-appb-000018
令k(d 3+d 4)＝2π，
Figure PCTCN2021088836-appb-000019
其中，φs 12代表四端口网络的参数S 12的相位，φs 13代表四端口网络的参数S 13的相位。
进而，可算得耦合器的耦合度D，如下：
Figure PCTCN2021088836-appb-000020
并且，第一去耦传输线33和第二去耦传输线34的长度d 3与d 4分别为：
Figure PCTCN2021088836-appb-000021
其中，φ 21为去耦前隔离度的相位，Pi对应的数值为π，例如为3.14，S 1' 2为去耦前隔离度的幅度。
由此可知，能够根据S’ 12计算出所需定向耦合器的耦合度D；还能够根据φ 21计算出第一去耦传输线33和第二去耦传输线34的长度d 3与d 4。其中，所述第一去耦传输线33的长度d 3和所述第二去耦传输线34的长度d 4之和为波长的整数倍。
另外，在令预设耦合度为0的情况下，所需定向耦合器还可满足以下结构参数：
Figure PCTCN2021088836-appb-000022
Figure PCTCN2021088836-appb-000023
其中，第一传输线311、第二传输线312、第三传输线313、第四传输线314、第一去耦传输线33和第二去耦传输线34的特性阻抗Z 0通常是预先设定的，例如设定成50Ω；h可为阻抗变换因子。因此，依据由式(22)计算出的定向耦合器的耦合度D，再依据式(24)和式(25)，就能够确定如图4所示的定向耦合器各枝节的特性阻抗，也就是：第五传输线315和第七传输线317的特性阻抗Z 1，以及第六传输线316和第八传输线318的特性阻抗Z 2。进而，能够计算出对应特性阻抗的传输线的线宽，以便制作出定向耦合器。基于此方法，可以提高多天线系统的隔离度。
一些实施例中，可以通过配置传输线的线宽来使传输线的特性阻抗满足要求。例如，按照上述关系式获得第一传输线311、第二传输线312、第三传输线313、第四传输线314、第一去耦传输线33和第二去耦传输线34的特性阻抗Z 0之后，可以将这些传输线的线宽配置为使其特性阻抗满足上述特性阻抗Z 0。举 例而言，确定所需的第一传输线311、第二传输线312、第三传输线313、第四传输线314、第一去耦传输线33和第二去耦传输线34的厚度、PCB板材的相对介电常数以及介质层厚度等因素后，根据特性阻抗和线宽之间的关系以及所需的特性阻抗Z 0，即可计算出这些传输线的线宽。因此，根据该计算结果来配置第一传输线311、第二传输线312、第三传输线313、第四传输线314、第一去耦传输线33和第二去耦传输线34的线宽，从而获得具有上述特性阻抗Z 0的多个传输线。
类似地，可以通过配置第五传输线315和第七传输线317的线宽来使他们满足上述所需的特性阻抗Z 1。第六传输线316和第八传输线318的线宽则可以根据特性阻抗和线宽之间的关系以及所需的特性阻抗Z 2来计算。因此，根据该计算结果来配置第五传输线315和第七传输线317以及第六传输线316和第八传输线318的线宽，从而获得具有上述特性阻抗Z 1和Z 2的多个传输线。
可以理解地，上述四端口网络还可以是其他形式的定向耦合器，例如耦合线定向耦合器、小型化定向耦合器，宽带化定向耦合器。
参见图6，其是本申请实施例的第二种用于阵列天线的去耦结构示意图。此实施例中的去耦结构与图3至图5所示实施例的去耦结构基本相同，不同之处在于：在第一去耦网络31的第一连接端口(例如，耦合端口)和第二去耦网络31’的第一连接端口(例如，耦合端口)之间通过第三去耦传输线331和第四去耦传输线332连接了第一移相器333。也就是说，在图6中，用依次连接的第三去耦传输线331、第一移相器333和第四去耦传输线332代替了图3中的第一去耦传输线33。从而，在图6所示的实施例中，第一去耦网络31的第一连接端口(例如，耦合端口)和第二去耦网络31’的第一连接端口(例如，耦合端口)通过依次连接的第三去耦传输线331、第一移相器333和第四去耦传输线332实现连接。在此指出，本文中所述的移相器是能够对信号的相位进行调整的一种装置，其作用是将信号的相位移动一个角度。
在一实施例中，该第一移相器333为有源移相器。在此指出，本文中所述的有源移相器的基本原理是采用极性调制的方法，将输入信号分解为两路正交矢量，通过改变分路矢量幅度大小再进行加权求和，从而来改变输出信号的相位。
在一实施例中，该第一移相器333的相位为P1。并且，可调节该相位P1，使得P1与第三去耦传输线331和第四去耦传输线332的相位积累之和约等于2π的整数倍减去φ 21，还可使得P1与第二去耦传输线34、第三去耦传输线331和第四去耦传输线332的相位积累之和等于2π的整数倍。如前所述，φ 21为去耦前隔离度的相位。另外，还可将第二去耦传输线34的相位设计为约等于2π的整数倍加上φ 21。
从而，通过改变第一移相器333的相位，以及调节第二去耦传输线34、第三去耦传输线331和第四去耦传输线332的相位积累，可改变天线单元10、20之间的耦合度D1(也就是改变隔离度)，实现天线单元10、20之间去耦的可调化，例如实现天线单元10、20去耦的频率可调和去耦幅度可调。基于此方法，可以灵活地提高阵列天线的隔离度。
参见图7，其是本申请实施例的第三种用于阵列天线的去耦结构示意图。此实施例中的去耦结构与图3至图5所示实施例的去耦结构基本相同，不同之处在于：在第一去耦网络31的第二连接端口(例如，隔离端口)和第二去耦网络31’的第二连接端口(例如，隔离端口)之间通过第五去耦传输线341和第六去耦传输线342连接了第二移相器343。也就是说，在图7中，用依次连接的第五去耦传输线341、第二移相器343和第六去耦传输线342代替了图3中的第二去耦传输线34。从而，在图7所示的实施例中，第一去耦网络31的第二连接端口(例如，隔离端口)和第二去耦网络31’的第二连接端口(例如，隔离端口)通过依次连接的第五去耦传输线341、第二移相器343和第六去耦传输线342实现连接。
在一实施例中，该第二移相器343为有源移相器。
在一实施例中，该第二移相器343的相位为P2。并且，可调节该相位P2，使得P2与第五去耦传输线341和第六去耦传输线342的相位积累之和约等于2π的整数倍加上φ 21，还可使得P2与第一去耦传输线33、第五去耦传输线341和第六去耦传输线342的相位积累之和等于2π的整数倍。另外，还可将第一去耦传输线33的相位设计为约等于2π的整数倍减去φ 21。
从而，通过改变第二移相器343的相位，以及调节第一去耦传输线33、第五去耦传输线341和第六去耦传输线342的相位积累，可改变天线单元10、20之间的耦合度D1(也就是改变隔离度)，实现天线单元10、20之间去耦的可调化，例如实现天线单元10、20去耦的频率可调和去耦幅度可调。基于此方法，也可以灵活地提高阵列天线的隔离度。
参见图8，其是本申请实施例的第三种用于阵列天线的去耦结构示意图。此实施例中的去耦结构与图3至图5所示实施例的去耦结构基本相同，不同之处在于：在第一去耦网络31的第一连接端口(例如，耦合端口)和第二去耦网络31’的第一连接端口(例如，耦合端口)之间通过第三去耦传输线331和第四去耦传输线332连接了第一移相器333；在第一去耦网络31的第二连接端口(例如，隔离端口)和第二去耦网络31’的第二连接端口(例如，隔离端口)之间通过第五去耦传输线341和第六去耦传输线342连接了第二移相器343。
也就是说，在图8中，用依次连接的第三去耦传输线331、第一移相器333和第四去耦传输线332代替了图3中的第一去耦传输线33；并且用依次连接的第五去耦传输线341、第二移相器343和第六去耦传输线342代替了图3中的第二去耦传输线34。从而，在图8所示的实施例中，第一去耦网络31的第一连接端口(例如，耦合端口)和第二去耦网络31’的第一连接端口(例如，耦合端口)通过依次连接的第三去耦传输线331、第一移相器333和第四去耦传输线332实现连接；第一去耦网络31的第二连接端口(例如，隔离端口)和第二去耦网络31’的第二连接端口(例如，隔离端口)通过依次连接的第五去耦传输线341、第二移相器343和第六去耦传输线342实现连接。
在一实施例中，该第一移相器333和该第二移相器343均为有源移相器。
在一实施例中，该第一移相器333的相位为P1，该第二移相器343的相位为P2。并且，可调节该相位P1和P2，使得P1与第三去耦传输线331和第四去耦传输线332的相位积累之和约等于2π的整数倍减去φ 21，使得P2与第五去耦传输线341和第六去耦传输线342的相位积累之和约等于2π的整数倍加上φ 21，进而使得P1、P2与第三去耦传输线331、第四去耦传输线332、第五去耦传输线341和第六去耦传输线342的相位积累之和等于2π的整数倍。
从而，通过改变第一移相器333和第二移相器343的相位P1、P2，以及调节第三去耦传输线331、第四去耦传输线332、第五去耦传输线341和第六去耦传输线342的相位积累，可改变天线单元10、20之间的耦合度D1(也就是改变隔离度)，实现天线单元10、20之间去耦的可调化，例如实现天线单元10、20去耦的频率可调和去耦幅度可调。基于此方法，可以更灵活地提高阵列天线的隔离度。
结合上述用于阵列天线的去耦结构，本申请还提出了一种用于天线装置的去耦方法，图9为本申请实施例的用于天线装置的去耦方法的流程示意图。
如图9所示，该去耦方法主要可包括以下操作S101-S102。
操作S101：提供天线装置，所述天线装置包括：相邻设置的第一天线单元和第二天线单元；第一去耦网络，所述第一去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述输出端口连接所述第一天线单元，所述输入端口用于连接第一馈源；第二去耦网络，所述第二去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述第二去耦网络的输出端口连接所述第二天线单元，所述第二去耦网络的输入端口用于连接第二馈源；第一去耦传输线，所述第一去耦传输线连接所述第一去耦网络的第一连接端口与所述第二去耦网络的第一连接端口；以及第二去耦传输线，所述第二去耦传输线连接所述第一去耦网络的第二连接端口与所述第二去耦网络的第二连接端口；其中，所述第一去耦传输线和所述第二去耦传输线的至少一个中设置有移相器。
结合图2至图8所示，本申请中与天线装置相关的描述均可适用于该操作S101，在此不再赘述。
操作S102：通过调整所述移相器的相位来调整所述第一天线单元和第二天线单元之间的耦合度。
结合图2至图8所示，本申请中与第一移相器333和/或第二移相器343相关的描述均可适用于该操作S102，在此不再赘述。
在一实施例中，该去耦方法还可包括以下操作：根据所述移相器所在的去耦传输线的相位积累以及所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的相位来调节所述移相器的相位。
在一实施例中，该去耦方法还可包括以下操作：根据所述第一去耦传输线和所述第二去耦传输线的相位积累来调节所述移相器的相位。
在一实施例中，该去耦方法还可包括以下操作：将所述移相器设计为有源移相器。
在一实施例中，该去耦方法还可包括以下操作：将所述第一连接端口设置为耦合端口和隔离端口中的一个，将所述第二连接端口设置为隔离端口和耦合端口中的另一个。
在一实施例中，该去耦方法还可包括以下操作：在所述第一去耦传输线中设置所述移相器，所述第一去耦传输线包括依次连接的第三去耦传输线、所述移相器和第四去耦传输线。
在一实施例中，该去耦方法还可包括以下操作：调节所述第一移相器的相位，使得所述第一移相器的相位与所述第三去耦传输线和所述第四去耦传输线的相位积累之和约等于2π的整数倍减去φ 21，其中φ 21为所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的相位。
在一实施例中，该去耦方法还可包括以下操作：调节所述第一移相器的相位，使得所述第一移相器的相位与所述第二去耦传输线、第三去耦传输线和第四去耦传输线的相位积累之和等于2π的整数倍。
在一实施例中，该去耦方法还可包括以下操作：还在所述第二去耦传输线中设置第二移相器，使得所述第二去耦传输线包括依次连接的第五去耦传输线、所述第二移相器和第六去耦传输线。
在一实施例中，该去耦方法还可包括以下操作：调节所述第一移相器的相位，使得所述第一移相器的相位与第三去耦传输线和第四去耦传输线的相位积累之和约等于2π的整数倍减去φ 21，其中φ 21为所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的相位。
在一实施例中，该去耦方法还可包括以下操作：调节所述第二移相器的相位，使得所述第二移相器的相位与第五去耦传输线和第六去耦传输线的相位积累之和等于2π的整数倍加上φ 21，其中φ 21为所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的相位。
在一实施例中，该去耦方法还可包括以下操作：调节所述第一移相器的相位和所述第二移相器的相位，使得所述第一移相器的相位、所述第二移相器的相位与第三去耦传输线、第四去耦传输线、第五去耦传输线和第六去耦传输线的相位积累之和等于2π的整数倍。
在一实施例中，该去耦方法还可包括以下操作：将所述第一去耦网络和所述第二去耦网络设置成具有相同的散射参数。
在一实施例中，该去耦方法还可包括以下操作：根据所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的强度来确定所述第一去耦网络的耦合度。
在一实施例中，该去耦方法还可包括以下操作：定义所述第一去耦网络的耦合度为D，定义所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的强度为S’ 12，这些参数之间满足上述式(22)所限定的关系。
容易明白的是，本申请中在去耦原理部分所描述的相关内容均可适用于该去耦方法，在此不再赘述。
在一些实施例中，本申请的电子设备可以是如图10所示的手机100a，该手机100a包括但不限于以下结构：壳体41以及与壳体41连接的显示屏组件50。其中，壳体41和显示屏组件50之间形成容置空间。手机的其他电子元器件，例如，主板、电池和天线装置60等均设置在容置空间内。
具体而言，壳体41可以由塑料、玻璃、陶瓷、纤维复合材料、金属(例如，不锈钢，铝等)或者其他合适的材料制成。图10所示的壳体41大体为具有圆角的矩形。当然，壳体41也可以具有其他形状，例如圆形，长圆形和椭圆形等。
显示屏组件50包括显示屏盖板51以及显示模组52。显示模组52贴设于显示屏盖板51的内表面。壳体41与显示屏组件50的显示屏盖板51连接。其中，显示屏盖板51可以为玻璃材质；显示模组52可以为OLED柔性显示屏结构，具体可以包括基板、显示面板(Panel)以及辅料层等，另外，显示模组52与显示屏盖板51之间还可以夹设偏光膜片等结构，关于显示模组52的详细层叠结构此处不做限定。
天线装置60可以完全收容在壳体41内部，或者，也可以嵌设在壳体41上，并且，天线装置60的一部分可暴露在壳体41外表面上。
天线装置60可以包括多个天线单元，例如，图11至图15所示的天线模60为四元直线阵，即，具有四个沿直线排列的天线单元10a、20a、10b和20b。具体地，结合图15，该天线装置60包括依次叠层设置的第一基板61、第二基板62、第三基板63和射频芯片64，以及形成在第一基板61上的多个天线单元(图15仅示出两个天线单元10a、20a)，形成在第一基板61和第三基板63上的多个金属层661-668(其中，金属层665为接地层665)、穿设在第三基板63和第二基板62内的馈线以及设置在第三基板63上的第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34。其中，馈线与天线单元10a、20a一一对应，分别用于将对应的天线单元10a、20a与射频芯片64连接。第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34则用于将相邻的天线单元10a、20a对应的馈线连接在一起，用以抵消天线单元10a、20a之间的耦合。所述第一去耦传输线33和第二去耦传输线34可均在同一平面层内，例如设置在第三基板63内；另外，所述第一去耦传输线33和第二去耦传输线34可呈弯折布置，以满足长度设计。可以理接地，天线装置60还可以包括其他信号传输线。
天线单元10a、20a用于收发射频信号。如图15所示，两个天线单元10a、20a相互间隔设置。天线单元10a、20a为双层贴片天线，包括相互隔离且一一对应的表层辐射片11a、21a和内层辐射片12a、22a。
第一基板61包括相对设置的第一外表面611和第一内表面612。表层辐射片11a、21a设置在第一外表面611，内层辐射片12a、22a设置在第一内表面612。通过第一基板61将内层辐射片12a、22a和表层辐射片11a、21a隔离，使得表层辐射片11a、21a和内层辐射片12a、22a之间间隔一定的距离，从而满足天线频段的性能要求。表层辐射片11a、21a和内层辐射片12a、22a在第一基板61的垂直投影至少部分重合。
第一基板61可以由诸如环氧树脂的热固性树脂、诸如聚酰亚胺树脂的热塑性树脂、包括诸如玻璃纤维(或玻璃布，或玻璃织物)和/或无机填料的增强材料以及热固性树脂和热塑性树脂的绝缘材料(例如，半固化片、ABF(Ajinomoto Build-up Film)、感光电介质(PID)等)制成。然而，第一基板61的材料不限于此。也就是说，玻璃板或陶瓷板也可用作第一基板61的材料。可选地，具有低的介电损耗的液晶聚合物(LCP)也可用作第一基板61的材料，以减小信号损耗。
在一些实施例中，第一基板61可以是半固化片，如图15所示，第一基板61包括叠设的三层半固化片。第一基板61的三层半固化片中，相邻的半固化片之间分别设有金属层662和663。第一基板61的第一外表面还设有金属层661，该金属层661与表层辐射片11a、21a位于同一层，且相互绝缘。第一基板61 的第一内表面612设有金属层664，该金属层664与内层辐射片12a、22a位于同一层，且相互绝缘。金属层661、662、663和664可以由金属铜、铝、银、锡、金、镍、铅、钛或他们的合金等导电材料制成。本实施例中，金属层661、662、663和664均为铜层。
金属层661的设置使得第一基板61的第一外表面611的铺铜率与第一基板61的其他半固化片的表面的铺铜率差异减少，在第一基板61制造的过程中，铺铜率差异减少能够减少气泡的产生，从而提升第一基板61的制造良率。同理，金属层664的设置也使得第一基板61的第一内表面612的铺铜率与第一基板61的其他半固化片的表面的铺铜率差异减少，以减少第一基板61制造过程中气泡的产生，从而提升第一基板61的制造良率。
第一基板61上还设有贯穿第一内表面612和第一外表面611接地过孔613，以使不同的金属层661、662、663和664彼此连接，并进一步连接到接地层665。具体地，可以将导电材料完全填充接地过孔613，或者可以将导电材料沿着接地过孔613的孔壁形成导电层。其中，导电材料可以是铜、铝、银、锡、金、镍、铅、钛或他们的合金等。接地过孔613可以具有圆柱状、沙漏状或者锥体状等。
第二基板62包括第一侧表面621和第二侧表面622，其中，第一侧表面621叠设在第一基板61的第一内表面612上。第二基板62可以为PCB板的核层，由聚酰亚胺、聚对苯二甲酸乙二醇酯、聚萘二甲酸乙二醇酯等材料制成。第二基板62上设有贯穿第一侧表面621和第二侧表面622的接地过孔623和馈线过孔624。
接地层665夹设在第二基板62和第三基板63之间。接地层665上开设有馈线过孔665a。
第三基板63包括相对设置的第二外表面631和第二内表面632。第三基板63的第二内表面632叠设于第二基板62的第二侧表面622，接地层665夹设在第二侧表面622和第二内表面632之间。
第三基板63的形成材料可以与第一基板61的材料相同。在一些实施例中，第三基板63可以是半固化片，如图15所示，第三基板63包括三层半固化片。第三基板63的三层半固化片中，相邻的半固化片之间设有金属层666和667，分别作为馈电网络和控制线布线层。第三基板63的第二外表面631上设有金属层668，金属层668与射频芯片64焊接在一起。其中，金属层666、667和668可以由金属铜、铝、银、锡、金、镍、铅、钛或他们的合金等导电材料制成。本实施例中，金属层666、667和668均为铜层。
第三基板63上开设有布线过孔。布线过孔包括接地过孔633，以使不同的金属层666、667和668彼此连接，并进一步连接到接地层665。布线过孔还包括供馈线穿过的馈线过孔634和供控制线穿过的信号过孔635等。与第一基板61上的接地过孔613类似，第三基板63上的布线过孔内可以完全填充导电材料，也可以在孔壁上形成导电层。各种布线过孔的形状可以是圆柱状、沙漏状或者锥体状。
一馈线的一端连接在射频芯片64上，另一端穿入第三基板63的馈线过孔634而与第一去耦网络31。另一馈线的一端连接第一去耦网络31，另一端穿入接地层665的馈线过孔665a以及第二基板62的馈线过孔624而与内层辐射片12a、22a连接，以在天线单元10a、20a和射频芯片64之间传输信号。具体地，馈线包括通过去耦网络连接的第一馈线31a和第二馈线32a。其中，第一馈线31a与射频芯片64连接，第二馈线32a则与内层辐射片12a、22a连接。馈线与各金属层，例如本实施例的金属层666、667、668以及接地层相互绝缘。在此指出，图15中的第一馈线31a可连接图3中的第一传输线311，并且第二馈线32a可连接图3中的第二传输线312。
此外，第三基板63上还设有其他信号传输线，例如控制线68和电源线69等。如图15所示，电源线69设置在第三基板63的第二外表面631上，并焊接在射频芯片64上。控制线68设置在第三基板63靠近射频芯片64的半固化片和与其相邻的半固化片之间，并穿过半固化层上的信号过孔635而与射频芯片64连接。
此外，第三基板63还用于承载第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34。如图15所示，第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34连接在相邻的天线10a、20a所对应的馈线之间。第一去耦网络31连接在一个天线单元10a对应的第一馈线31a和第二馈线32a的连接处；具体地，第一去耦网络31的第一传输线311(参见图3)与第一馈线31a连接，第一去耦网络31的第二传输线312与第二馈线32a连接。类似地，第二去耦网络31’连接在相邻的天线单元20a所对应的第一馈线31a和第二馈线32a的连接处；也就是，第二去耦网络31’的第一传输线311’(参见图5)与天线单元20a所对应的第一馈线31a连接，第二去耦网络31’的第二传输线312’与天线单元20a所对应的第二馈线32a连接。
由于在天线装置的两个相邻天线单元之间设置了第一去耦网络31和第二去耦网络31’，并且第一去耦传输线33和第二去耦传输线34在第一去耦网络31和第二去耦网络31’之间连接，因此从射频芯片64发出的信号经过第一馈线31a之后，一部分经第一去耦网络31以及第二馈线32a传输至天线单元的内层辐射片12a，另一部分经第一去耦网络31以及第一去耦传输线33和第二去耦传输线34传输至第二去耦网络31’以到达相邻的天线单元20a，从而在一定程度上抵消两个天线单元10a、20a之间的耦合。
两个天线单元10、20之间的耦合度可以通过该第一去耦网络31和第二去耦网络31’的S参数和第一去耦传输线33与第二去耦传输线34的长度来进行定义。具体地，如上述阵列天线的实施例，本实施例的天线装置60的第一去耦传输线33和第二去耦传输线34的长度d 3与d 4，第一去耦网络31的S参数，以及预设耦合度满足以下关系：
Figure PCTCN2021088836-appb-000024
一些实施例中，可以将第一去耦传输线33和第二去耦传输线34的长度d 3与d 4和第一去耦网络31的S参数配置为使两个天线单元10、20之间的耦合度D1置零。
进一步地，在一些实施例中，在将两个天线单元10、20之间的耦合度D1置零的情况下，再根据两个天线单元10、20之间的初始隔离度S12’计算出所需定向耦合器的耦合度D，具体参见前述的公式(22)。
如图14所示，其是图13的天线装置的局部示意图，主要显示了第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34的布置。在此实施例中，第一去耦传输线33和第二去耦传输线34呈不同的弯折布置，其中第一去耦传输线33的长度d 3包括多个弯折段，也就是d 3＝L1*2+L2*2+L3。第二去耦传输线34的长度d 4包括多个弯折段，也就是d 4＝L4*2+L5*2+L6。
进一步地，d 3与d 4相加的结果可近似等于两倍的波长，即2*λ＝2*6.45mm＝12.9mm。
由于第二去耦网络31’可以第一去耦网络31相同，因此第二去耦网络31’的传输线的布置可与第一去耦网络31中的传输线的弯折布置相同。
一些实施例中，还能够根据去耦前隔离度的相位φ 21计算出第一去耦传输线33和第二去耦传输线34的长度d 3与d 4，具体参见前述的公式(23)。
一些实施例中，根据所计算出的定向耦合器的耦合度D，就能够确定定向耦合器各枝节的特性阻抗，也就是：第一传输线311、第二传输线312、第三传输线313、第四传输线314、第一去耦传输线33和第二去耦传输线34的特性阻抗Z 0，第五传输线315和第七传输线317的特性阻抗Z 1，以及第六传输线316和第八传输线318的特性阻抗Z 2，具体参见前述的公式(24)和(25)。进而，能够计算出对应特性阻抗的传输线的线宽，以便制作出定向耦合器。
如上述天线阵列的实施例所述，可以通过配置传输线的线宽来使传输线的特性阻抗满足要求。例如，第一传输线311、第二传输线312、第三传输线313、第四传输线314、第一去耦传输线33和第二去耦传输线34的线宽配置为使其特性阻抗满足上述特性阻抗Z 0。第五传输线315和第七传输线317的线宽配置为使其特性阻抗满足上述特性阻抗Z 1。第六传输线316和第八传输线318的线宽配置为使其特性阻抗满足上述特性阻抗Z 2。
因此，可以在金属层666所在层上形成长度满足上述所需长度第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34。可以理解地，相邻的天线单元10a、20a所对应的馈线之间的直线距离较小时，第一去耦传输线33和第二去耦传输线34可以形成弯折的图案，以满足长度的要求(如图13和图14所示)。在其他一些实施例中，第一去耦传输线33也可以呈弯曲的图案，只要满足长度要求即可。
第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34与表层辐射片11a、21a和内层辐射片12a、22a位于不同的层。如图15所示，第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34设置在天线单元10a、20a的下方，例如第三基板63内。图15所示的第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34与金属层666位于同一层，即，设置在第三基板63的最靠近接地层665的半固化片及其相邻的半固化片之间。可以理解地，在其他一些实施例中，第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34也可以与金属层667或者668同层。
以上针对两个天线单元10a和20a、第一去耦网络31和第二去耦网络31’以及第一去耦传输线33与第二去耦传输线34进行了介绍。然而，容易理解的是，如图13所示，还可以为天线单元20a和10b以及天线单元10b和20b同样地设置本申请的去耦结构。举例而言，可为天线单元20a和10b设置第三去耦网络35和第四去耦网络35’以及连接在第三去耦网络35和第四去耦网络35’之间的第三去耦传输线33’与第四去耦传输线34’；该第三去耦网络35可与上述的第一去耦网络31相同或相类似，该第四去耦网络35’可与上述的第二去耦网络31’相同或相类似；第三去耦传输线33’可与上述的第一去耦传输线33相同或相类似，第四去耦传输线34’可与上述的第二去耦传输线34相同或相类似。另外，所述第二去耦网络31’和所述第三去耦网络35可共用部分传输线，例如共用第二去耦网络31’的第一传输线311’、第二传输线312’和第五传输线315’(参见图5)。
当采用如图13所示的三个以上的天线单元时，这些去耦网络和去耦传输线也可以分布在不同的层。例如，第一去耦网络31和第二去耦网络31’以及连接在他们之间的第一去耦传输线33和第二去耦传输线34可分布在图15所示的金属层666所在层，而第三去耦网络35和第四去耦网络35’以及连接在第三去耦网络35和第四去耦网络35’之间的第三去耦传输线33’与第四去耦传输线34’可分布在图15所示的金属层667所在层。
参见图16，其是本申请另一实施例的天线装置的示意图。在此实施例的天线装置60中，可将例如手机的中框42的顶端部分通过缝隙44分割为两段，这两段可分别作为第一天线10a和第二天线20a。该中框42中可设置一电路板43，本申请上述的第一去耦网络31和第二去耦网络31’以及第一去耦传输线33与第二去耦传输线34(参见图3)可布置在该电路板43上。馈源40和馈源40’可与该电路板43连接，该电路板43又与该第一天线10a和第二天线20a连接。缝隙44通常可非居中设置，例如靠近中框42的左侧或右侧设置。
在本申请以如图11至图13所示的四元直线阵进行去耦设计的示例中，该四元直线阵的中心工作频率为28GHz。在此指出，根据3GPP TS 38.101协议的规定，处在24.25GHz至52.6GHz之间的频率通常称为毫米波(mm Wave)；因此，本申请提出的去耦结构可为一种毫米波阵列天线去耦结构。
综上所述，本申请的天线装置，在天线单元下方引入去耦网络的概念，无需改变阵列天线单元的结构，只需对第一去耦传输线33和第二去耦传输线34的长度d 3与d 4以及四端口网络的S参数进行配置，即可调节天线单元10、20之间的耦合度D1，即能降低天线单元间的互耦，拓展扫描角，提升扫描增益。另外，还能依据去耦前隔离度的幅度计算出的定向耦合器的耦合度D，再依据公式确定定向耦合器各枝节的特性阻抗，进而能够计算出对应特性阻抗的传输线的线宽，以便制作出定向耦合器。基于此方法，可以提高多天线系统的隔离度。再者，当在去耦结构中采用移相器时，通过改变第一移相器333和/或第二移相器343的相位，以及调节与第一移相器333和/或第二移相器343连接的这些去耦传输线的相位积累，也可改变天线单元10、20之间的耦合度D1，实现天线单元10、20之间去耦的可调化。基于这些方法，都可以灵活地提高阵列天线的隔离度。
以上所述仅为本申请的实施例，并非因此限制本申请的专利范围，凡是利用本申请说明书及附图内容所作的等效结构或等效流程变换，或直接或间接运用在其他相关的技术领域，均同理包括在本申请的专利保护范围内。

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  1. 一种天线装置，其特征在于，包括：
    相邻设置的第一天线单元和第二天线单元；
    第一去耦网络，所述第一去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述输出端口连接所述第一天线单元，所述输入端口用于连接第一馈源；
    第二去耦网络，所述第二去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述第二去耦网络的输出端口连接所述第二天线单元，所述第二去耦网络的输入端口用于连接第二馈源；
    第一去耦传输线，所述第一去耦传输线连接所述第一去耦网络的第一连接端口与所述第二去耦网络的第一连接端口；以及
    第二去耦传输线，所述第二去耦传输线连接所述第一去耦网络的第二连接端口与所述第二去耦网络的第二连接端口；
    其中，所述第一去耦传输线和所述第二去耦传输线的至少一个中设置有移相器。
  2. 根据权利要求1所述的天线装置，其特征在于：
    所述移相器为有源移相器；和/或
    所述第一连接端口为耦合端口和隔离端口中的一个，所述第二连接端口为隔离端口和耦合端口中的另一个。
  3. 根据权利要求1所述的天线装置，其特征在于：
    所述移相器设置在所述第一去耦传输线中，所述第一去耦传输线包括依次连接的第三去耦传输线、所述移相器和第四去耦传输线。
  4. 根据权利要求3所述的天线装置，其特征在于：
    所述移相器的相位与所述第三去耦传输线和所述第四去耦传输线的相位积累之和等于2π的整数倍减去φ 21，其中φ 21为所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的相位。
  5. 根据权利要求3所述的天线装置，其特征在于：
    所述移相器的相位与所述第二去耦传输线、第三去耦传输线和第四去耦传输线的相位积累之和等于2π的整数倍。
  6. 根据权利要求3所述的天线装置，其特征在于：
    还在所述第二去耦传输线中设置另一移相器，所述第二去耦传输线包括依次连接的第五去耦传输线、所述另一移相器和第六去耦传输线。
  7. 根据权利要求6所述的天线装置，其特征在于：
    所述移相器的相位与第三去耦传输线和第四去耦传输线的相位积累之和等于2π的整数倍减去φ 21，其中φ 21为所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的相位。
  8. 根据权利要求6所述的天线装置，其特征在于：
    所述另一移相器的相位与第五去耦传输线和第六去耦传输线的相位积累之和等于2π的整数倍加上φ 21，其中φ 21为所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的相位。
  9. 根据权利要求6所述的天线装置，其特征在于：
    所述移相器的相位P1和所述另一移相器的相位P2与所述第三去耦传输线、第四去耦传输线、第五去耦传输线和第六去耦传输线的相位积累之和等于2π的整数倍。
  10. 根据权利要求1所述的天线装置，其特征在于：
    所述第一去耦网络和所述第二去耦网络具有相同的散射参数。
  11. 根据权利要求10所述的天线装置，其特征在于：
    所述第一去耦网络的耦合度根据所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的强度来确定。
  12. 根据权利要求11所述的天线装置，其特征在于：
    定义所述第一去耦网络的耦合度为D，定义所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的强度为S’ 12，这些参数之间满足以下关系：
    Figure PCTCN2021088836-appb-100001
  13. 根据权利要求1所述的天线装置，其特征在于：
    所述第一天线单元和第二天线单元具有相同的辐射特性。
  14. 一种电子设备，其特征在于，包括：
    壳体；
    显示屏组件，与所述壳体连接，并与所述壳体形成容置空间；
    馈源，设置在所述容置空间内；以及
    天线装置，至少部分设置在所述容置空间内，所述天线装置包括：
    多个天线单元；
    多个去耦网络，与所述多个天线单元一一对应，其中，每个去耦网络均具有输入端口、输出端口、第一连接端口和第二连接端口；所述输出端口与对应的天线单元连接，所述输入端口与所述馈源连接；
    第一去耦传输线，所述第一去耦传输线连接在相邻的所述去耦网络的第一连接端口之间；以及
    第二去耦传输线，所述第二去耦传输线连接在相邻的所述去耦网络的第二连接端口之间；
    其中，所述第一去耦传输线和所述第二去耦传输线的至少一个中设置有移相器。
  15. 根据权利要求14所述的电子设备，其特征在于，所述馈源包括多个馈源，所述多个馈源与所述多个去耦网络一一对应，每一所述输入端口与对应的馈源连接。
  16. 根据权利要求14所述的电子设备，其特征在于，所述馈源为射频芯片。
  17. 根据权利要求16所述的电子设备，其特征在于，所述天线装置包括依次叠层设置的第一基板、第二基板和第三基板；所述多个天线单元设置在所述第一基板上；所述第一去耦传输线和所述第二去耦传输线设置在所述第三基板内；所述射频芯片设置在所述第三基板远离所述第二基板的一侧。
  18. 一种用于天线装置的去耦方法，其特征在于，所述天线装置包括：相邻设置的第一天线单元和第二天线单元；第一去耦网络，所述第一去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述输出端口连接所述第一天线单元，所述输入端口用于连接第一馈源；第二去耦网络，所述第二去耦网络具有输入端口、输出端口、第一连接端口和第二连接端口；所述第二去耦网络的输出端口连接所述第二天线单元，所述第二去耦网络的输入端口用于连接第二馈源；第一去耦传输线，所述第一去耦传输线连接所述第一去耦网络的第一连接端口与所述第二去耦网络的第一连接端口；以及第二去耦传输线，所述第二去耦传输线连接所述第一去耦网络的第二连接端口与所述第二去耦网络的第二连接端口；其中，所述第一去耦传输线和所述第二去耦传输线的至少一个中设置有移相器；所述去耦方法包括：
    通过调整所述移相器的相位来调整所述第一天线单元和第二天线单元之间的耦合度。
  19. 根据权利要求18所述的去耦方法，其特征在于：
    根据所述移相器所在的去耦传输线的相位积累以及所述第一天线单元和所述第二天线单元之间未连接所述第一去耦网络与第二去耦网络时的隔离度的相位来调节所述移相器的相位。
  20. 根据权利要求18所述的去耦方法，其特征在于：
    根据所述第一去耦传输线和所述第二去耦传输线的相位积累来调节所述移相器的相位。
PCT/CN2021/088836 2020-05-12 2021-04-22 天线装置、电子设备和用于天线装置的去耦方法 WO2021227808A1 (zh)

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