WO2021027823A1 - 一种无线充电发射装置，发射方法及无线充电系统 - Google Patents

一种无线充电发射装置，发射方法及无线充电系统 Download PDF

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Publication number
WO2021027823A1
WO2021027823A1 PCT/CN2020/108554 CN2020108554W WO2021027823A1 WO 2021027823 A1 WO2021027823 A1 WO 2021027823A1 CN 2020108554 W CN2020108554 W CN 2020108554W WO 2021027823 A1 WO2021027823 A1 WO 2021027823A1
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Prior art keywords
leading
bridge arm
circuit
controllable
lagging
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PCT/CN2020/108554
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English (en)
French (fr)
Inventor
毛云鹤
刘彦丁
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华为技术有限公司
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Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Priority to EP20853277.0A priority Critical patent/EP4009487A4/en
Publication of WO2021027823A1 publication Critical patent/WO2021027823A1/zh
Priority to US17/669,718 priority patent/US20220166257A1/en

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    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/10—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by the energy transfer between the charging station and the vehicle
    • B60L53/12—Inductive energy transfer
    • B60L53/122—Circuits or methods for driving the primary coil, e.g. supplying electric power to the coil
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/10—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by the energy transfer between the charging station and the vehicle
    • B60L53/12—Inductive energy transfer
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/60—Monitoring or controlling charging stations
    • B60L53/66—Data transfer between charging stations and vehicles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/20—Circuit arrangements or systems for wireless supply or distribution of electric power using microwaves or radio frequency waves
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L2210/00—Converter types
    • B60L2210/10—DC to DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2310/00—The network for supplying or distributing electric power characterised by its spatial reach or by the load
    • H02J2310/40—The network being an on-board power network, i.e. within a vehicle
    • H02J2310/48—The network being an on-board power network, i.e. within a vehicle for electric vehicles [EV] or hybrid vehicles [HEV]
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/80—Circuit arrangements or systems for wireless supply or distribution of electric power involving the exchange of data, concerning supply or distribution of electric power, between transmitting devices and receiving devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/02—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries for charging batteries from ac mains by converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

Definitions

  • the present invention relates to the field of power electronics technology, in particular to a wireless charging transmitting device, a transmitting method and a wireless charging system.
  • Electric vehicles With the intensification of energy shortages and environmental pollution in modern society, electric vehicles as new energy vehicles have received extensive attention from all walks of life. Electric vehicles use on-board power battery packs as energy sources to drive vehicles. However, most of the existing electric vehicles are limited by the capacity of the power battery pack, and the driving range is short. At the same time, the power battery pack of the electric vehicle has a longer charging time and there are fewer charging stations. Therefore, the electric vehicle has not yet been widely used and popularized.
  • the charging methods of electric vehicles currently include contact charging and wireless charging, and wireless charging has become the development direction of electric vehicles in the future due to its convenience, no sparks and electric shock.
  • FIG. 1 is a schematic diagram of a wireless charging system.
  • the wireless charging system includes a wireless charging transmitting device and a wireless charging receiving device.
  • the wireless charging transmitting device is located at the transmitting end, and the wireless charging receiving device is located at the receiving end.
  • the transmitting end includes: an inverter H1, a transmitting end compensation circuit 100 and a transmitting coil Ct;
  • the inverter H1 includes controllable switch tubes S1-S4, and the inverter H1 is used to invert the direct current output by the direct current power supply into alternating current.
  • S1, S2 are lagging bridge arms
  • S3, S4 are leading bridge arms
  • the voltage phase of the leading bridge arm is ahead of the voltage phase of the lagging bridge arm in the same period.
  • the transmitting coil Ct is used to transmit the alternating current output from the inverter H1 in the form of an alternating magnetic field.
  • the receiving end includes: receiving coil Cr, receiving end compensation circuit 200 and rectifier H2.
  • the rectifier H2 includes controllable switch tubes Q1-Q4.
  • the receiving coil Cr is used to receive the electromagnetic energy emitted by the transmitting coil Ct in the form of an alternating magnetic field.
  • the rectifier H2 is used to rectify the alternating current output by the receiving coil Cr into direct current and output it to the load.
  • the controller 300 at the receiving end and the controller 400 at the transmitting end perform wireless communication.
  • the reflected impedance reflected from the receiving end of the wireless charging system to the transmitting end may be resistive-capacitive, resulting in a certain degree of resistive-capacitive output impedance.
  • the controllable switch in H1 implements zero voltage switching (ZVS, Zero Voltage Switching) in order to reduce the power consumption of the controllable switch during operation.
  • ZVS Zero Voltage Switching
  • the input voltage of H1 can be adjusted to enable H1 to achieve ZVS under all operating conditions.
  • adjusting the input voltage of H1 requires an additional DC conversion circuit at the input end of H1, which will increase the volume and cost of the wireless charging transmitter.
  • the output voltage of H1 can also be adjusted by adjusting the phase shift of H1.
  • the controllable switch tube can realize ZVS under various output voltages of H1, and once the controllable switch tube loses ZVS, the switching loss of H1 will be relatively large or even damaged.
  • the present application provides a wireless charging transmitting device, and the transmitting method is a wireless charging system.
  • the controller controls the turn-on or turn-off of the controllable inductance branch switch, and adjusts the size of the inductive current flowing into the leading and lagging bridge arms of the impedance adjustment circuit, so that the leading and lagging bridge arms can be controlled by the switch
  • the tube realizes zero-voltage switching, reduces the loss of the controllable switching tube, and improves the efficiency of wireless charging while improving its interoperability, that is, compatibility.
  • an embodiment of the present application provides a wireless charging and transmitting device, including: an inverter circuit, a compensation circuit, a transmitting coil, an impedance adjusting circuit, and a controller.
  • the inverter circuit is used to convert input direct current into alternating current.
  • the inverter circuit includes a leading bridge arm and a lagging bridge arm, wherein the voltage phase of the leading bridge arm leads the voltage phase of the lagging bridge arm in the same period, and the leading bridge arm and the lagging bridge arm are respectively Including controllable switch tube.
  • the compensation circuit is used to compensate the alternating current and send it to the transmitting coil.
  • the transmitting coil is used to transmit the alternating current output by the compensation circuit in the form of an alternating magnetic field.
  • the impedance adjusting circuit includes a leading bridge arm impedance adjusting circuit and a lagging bridge arm impedance adjusting circuit.
  • the first end of the leading bridge arm impedance adjustment circuit is connected to the controllable switch tube of the leading bridge arm.
  • the first end of the lagging bridge arm impedance adjustment circuit is connected to the controllable switch tube of the lagging bridge arm.
  • the leading arm impedance adjusting circuit and the lagging arm impedance adjusting circuit respectively include inductance branches, the inductive branches include at least one controllable inductance branch, and each of the controllable inductance branches includes at least one inductance. And at least one switch.
  • the controller adjusts the magnitude of the inductive current flowing into the lead arm by controlling the on or off of the switch of the controllable inductance branch in the lead arm impedance adjustment circuit, so that the The controllable switch tube of the leading bridge arm realizes zero-voltage switching; by controlling the on or off of the switch of the controllable inductance branch in the lagging bridge arm impedance adjustment circuit, the magnitude of the inductive current flowing into the lagging bridge arm is controlled.
  • the adjustment is performed so that the controllable switch tube of the lagging bridge arm realizes zero voltage switching.
  • the inductance branches of the leading arm impedance adjustment circuit and the lagging arm impedance adjustment circuit further include at least one fixed inductance branch, and the fixed inductance branch
  • the circuit includes at least one inductor.
  • the fixed inductance branch is not controlled by the switch and can directly inject inductive current into the leading and lagging bridge arms. Therefore, through the reasonable selection and matching of the controllable inductance branch and the fixed inductance branch, zero can be achieved in the controllable switch tube.
  • the voltage switch can construct a reasonable current gradient for the inductive current injected into the leading and lagging bridge arms.
  • the controllable switching tubes of the leading bridge arm and the lagging bridge arm each include two upper and lower switching tubes
  • the leading bridge arm impedance adjusting circuit is first
  • the first end of the lagging bridge arm impedance adjustment circuit is connected to the midpoint of the two upper and lower switching transistors of the lagging bridge arm, so
  • the second ends of the leading bridge arm impedance adjusting circuit and the lagging bridge arm impedance adjusting circuit are respectively connected to one of the positive bus bar, the negative bus bar or the midpoint of the bus bar of the power supply.
  • the impedance adjusting circuit further includes at least one DC blocking capacitor, and the second ends of the leading arm impedance adjusting circuit and the lagging arm impedance adjusting circuit respectively pass
  • the DC blocking capacitor is connected to one of the positive bus bar, the negative bus bar or the midpoint of the bus bar of the power supply.
  • the DC blocking capacitor can filter out the direct current component in the impedance adjustment circuit, reduce the increase in the effective value of the current in the leading and lagging bridge arms, thereby reducing the conduction loss and switching loss of the controllable switch tubes in the leading and lagging bridge arms .
  • the impedance adjusting circuit further includes at least one first dc blocking capacitor and at least one second dc blocking capacitor, the leading arm impedance adjusting circuit and the lagging bridge
  • the second end of the arm impedance adjustment circuit is connected to the positive bus of the power supply through the at least one first DC blocking capacitor, and is connected to the negative bus of the power supply through the at least one second DC blocking capacitor.
  • the first and second DC blocking capacitors can filter out the DC component in the impedance adjustment circuit, reduce the increase in the effective value of the current in the lead and lag arms, and thereby reduce the conduction of the controllable switch in the lead and lag arms. Conduction loss and switching loss.
  • the impedance adjustment circuit further includes at least one first DC blocking capacitor, at least one second DC blocking capacitor, and at least one third DC blocking capacitor, and the leading bridge arm
  • the second end of the impedance adjusting circuit and the lagging arm impedance adjusting circuit are respectively connected to the first end of the at least one first DC blocking capacitor, and the second end of the at least one first DC blocking capacitor passes through the at least one
  • a second DC blocking capacitor is connected to the positive bus of the power supply, and the second end of the at least one first DC blocking capacitor is connected to the negative bus of the power supply through the at least one third DC blocking capacitor.
  • the first, second, and third DC blocking capacitors can filter out the DC component in the impedance adjustment circuit, reduce the increase in the effective value of the current in the lead and lag arms, thereby reducing the controllable switches in the lead and lag arms The conduction loss and switching loss of the tube.
  • the leading bridge arm impedance adjustment circuit further includes at least one DC blocking capacitor, and the inductive branch of the leading bridge arm impedance adjustment circuit passes through the at least one DC blocking capacitor Connect with one of the positive bus, negative bus or the midpoint of the power supply.
  • the DC blocking capacitor can filter out the direct current components in the impedance adjustment circuit, reduce the increase in the effective value of the current in the leading and lagging bridge arms, and thereby reduce the conduction loss and switching loss of the controllable switch in the leading bridge arm.
  • the lead arm impedance adjustment circuit further includes at least one first DC blocking capacitor and at least one second DC blocking capacitor, and the inductance of the lead arm impedance adjustment circuit
  • the branch is connected to the positive bus of the power supply through the at least one first DC blocking capacitor, and is connected to the negative bus of the power supply through the at least one second DC blocking capacitor.
  • the first and second DC blocking capacitors can filter out the DC component in the impedance adjustment circuit, reduce the increase in the effective value of the current in the leading and lagging bridge arms, thereby reducing the conduction loss of the controllable switch in the leading bridge arm And the switching loss.
  • the leading bridge arm impedance adjustment circuit further includes at least one first DC blocking capacitor, at least one second DC blocking capacitor, and at least one third DC blocking capacitor.
  • the inductance branch of the leading arm impedance adjustment circuit is connected to the positive bus of the power supply through the at least one first DC blocking capacitor and the at least one second DC blocking capacitor, and the inductance branch of the leading arm impedance adjustment circuit
  • the at least one first DC blocking capacitor and the at least one third DC blocking capacitor are connected to the negative bus of the power supply.
  • the first, second, and third DC blocking capacitors can filter out the DC component in the impedance adjustment circuit, reduce the increase in the effective value of the current in the lead arm, and thereby reduce the controllable switch in the lead and lag arm. Conduction loss and switching loss.
  • the compensation circuit includes LCC, or LCL.
  • the lead arm impedance adjustment circuit further includes at least one diode clamp circuit, and the controllable inductance branch of the lead arm impedance adjustment circuit is connected to the The at least one diode clamping circuit of the leading arm impedance adjusting circuit is connected, the diode clamping circuit of the leading arm impedance adjusting circuit includes a first diode and a second diode, and the leading arm impedance adjusting The connection points of the inductance and the switch in the controllable inductance branch of the circuit are respectively connected to the anode of the first diode and the cathode of the second diode. Two diodes are used to form a diode clamp circuit.
  • the switch of the inductance branch of the leading arm impedance adjustment circuit with the diode clamp circuit When the switch of the inductance branch of the leading arm impedance adjustment circuit with the diode clamp circuit is turned off, it can provide the inductance in the inductance branch of the lead arm impedance adjustment circuit.
  • the freewheeling path can maintain the voltage of the common terminal of the inductor and the switch in the inductance branch of the leading arm impedance adjustment circuit to be stable within a safe range, and has the function of protecting the circuit.
  • the lagging bridge arm impedance adjustment circuit further includes at least one diode clamp circuit, and the controllable inductance branch of the lagging bridge arm impedance adjustment circuit and the The at least one diode clamping circuit of the lagging bridge arm impedance adjusting circuit is connected, the diode clamping circuit of the lagging bridge arm impedance adjusting circuit includes a third diode and a fourth diode, and the lagging bridge arm impedance adjusting The connection points of the inductance and the switch in the controllable inductance branch of the circuit are respectively connected to the anode of the third diode and the cathode of the fourth diode.
  • Two diodes are used to form a diode clamping circuit.
  • the switch of the inductance branch of the lagging arm impedance adjustment circuit with the diode clamping circuit is turned off, the inductance in the inductance branch of the lagging arm impedance adjustment circuit can be provided
  • the freewheeling path can maintain the voltage of the common terminal of the inductor and the switch in the inductance branch of the lagging arm impedance adjustment circuit within a safe range, and has the function of protecting the circuit.
  • the controller is configured to obtain the current flowing into the compensation circuit; according to the current flowing into the compensation circuit, control the leading bridge arm of the wireless charging transmitter
  • the switch of the controllable inductance branch in the impedance adjusting circuit is turned on or off to change the current flowing out of the lead bridge arm of the wireless charging transmitter, so that the controllable switch tube of the lead bridge arm realizes zero voltage switching.
  • the controller is configured to obtain the difference between the current flowing into the compensation circuit and a preset current, and control the impedance adjustment circuit in the lead arm according to the difference Turn on or turn off the switch in the inductor branch. Regardless of whether there is a closed inductor branch, the current flowing into the compensation circuit can be obtained based on the difference between the current flowing into the compensation circuit and the preset current, and the on-off condition of the inductor branch can be controlled according to the difference.
  • the controller is used to obtain that the controllable switching tube of the leading bridge arm flows from the midpoint of the leading bridge arm from the time when the controllable switching tube of the leading arm is turned off to the turning-on time.
  • the current of the compensation circuit is used to obtain that the controllable switching tube of the leading bridge arm flows from the midpoint of the leading bridge arm from the time when the controllable switching tube of the leading arm is turned off to the turning-on time.
  • the controller is configured to control the current flowing out of the leading bridge arm from the time when the controllable switch of the leading bridge arm is turned off to the actual turning time
  • the current in the inductance branch of the leading bridge arm impedance adjustment circuit obtains the current flowing into the compensation circuit.
  • the current flowing into the compensation circuit can be obtained indirectly through the current of the leading bridge arm and the current of the leading bridge arm impedance adjusting circuit inductance branch.
  • the turn-off time is the time corresponding to the controllable switching tube from turning on to turning off; the turning-on time is the time corresponding to the turning off of the controllable switching tube to turning on.
  • the actual turn-off time and the actual turn-on time of the switch tube may be one delay time longer than the signal at the turn-off time and the turn-on time sent by the controller. Therefore, in the embodiment of the present application, the period from the off time to the on time is the longest period from the off time to the on time including the signal delay time.
  • an embodiment of the present application provides a method for controlling a wireless charging transmitter device.
  • the method includes: obtaining a current flowing into a compensation circuit of the wireless charging transmitter device; and controlling the wireless charging device according to the current flowing into the compensation circuit.
  • the switch of the controllable inductance branch in the lead arm impedance adjustment circuit of the transmitting device is turned on or off to change the current flowing out of the lead arm of the wireless charging and transmitting device, so that the controllable switch of the lead arm Realize zero voltage switching.
  • the controller can control the on and off of the switches in each inductance branch, and then adjust the impedance adjustment circuit to show different inductance sizes to change the magnitude of the inductive current injected into the leading bridge arm, thereby
  • the controllable switch tube of the leading bridge arm realizes ZVS. Since the controller can control the inductance branch to be connected, it can also control the inductive branch to be disconnected, that is, according to the actual operation of the inverter circuit to control whether the inductive branch is connected or not, in some working conditions, the leading arm of the inverter circuit ZVS can be achieved by itself, so there is no need to connect to any inductive branch.
  • the controller can control all the inductive branches to disconnect, so as to avoid additional power consumption caused by the inductive branch access; in some working conditions, in order to ensure the The interoperability of the charging receiving device also realizes the ZVS of the inverter circuit leading the bridge arm of the controllable switch, and the leading bridge arm impedance adjustment circuit can also be directly connected to the fixed inductance branch. Therefore, the control method is flexible to control, and for different working conditions, ZVS can be realized when it needs to be connected.
  • the leading bridge arm does not need to be connected to the inductive branch
  • the controllable inductive branch is controlled to be disconnected, thereby reducing power consumption.
  • the process of switching the inductive branch by the controller does not affect the power transmission of the wireless charging transmitter, which improves the stability and reliability of the wireless charging transmitter.
  • the difference between the current flowing into the compensation circuit and the preset current is obtained, and the inductance branch in the leading arm impedance adjustment circuit is controlled according to the difference The on or off of the switch. Regardless of whether there is a closed inductor branch, the current flowing into the compensation circuit can be directly obtained, and the current flowing into the compensation circuit is differentiated from the preset current, and the on-off condition of the inductor branch is controlled according to the difference.
  • controllable switch tube of the leading bridge arm flows into the compensation from the midpoint of the controllable switch tube of the leading bridge arm during the period from the turn-off time to the actual turn-on time.
  • the current of the circuit is not limited to the first aspect.
  • the current flowing out of the leading bridge arm during the period from the off time to the on time and the impedance of the leading bridge arm The current in the inductance branch of the circuit is adjusted to obtain the current flowing into the compensation circuit.
  • the current flowing into the compensation circuit can be obtained indirectly through the current of the leading bridge arm and the current of the leading bridge arm impedance adjusting circuit inductance branch.
  • the turn-off time is the time corresponding to the controllable switching tube from turning on to turning off;
  • the turning-on time is the time corresponding to the turning off of the controllable switching tube to turning on.
  • the actual turn-off time and the actual turn-on time of the switch tube will be one delay time longer than the signal of the turn-off time and the turn-on time sent by the controller. Therefore, in the embodiment of the present application, the period from the off time to the on time is the longest period from the off time to the on time including the signal delay time.
  • an embodiment of the present application provides a wireless charging system, including a wireless charging receiving device and a wireless charging transmitting device provided by any implementation manner described in the first aspect; the wireless charging receiving device is used to receive the wireless charging The alternating magnetic field emitted by the transmitting device converts the alternating magnetic field into direct current and provides it to the electric equipment. Since the wireless charging system includes the wireless charging transmitting device described above, the switching loss of the wireless charging transmitting device is reduced, the efficiency of wireless charging transmitting is improved, and the stability and reliability of the wireless charging transmitting device are improved.
  • an embodiment of the present application provides an electrical equipment, including power consumption components, a battery, and a wireless charging receiving device; the wireless charging receiving device is used to receive the alternating magnetic field emitted by the above wireless charging transmitting device; wireless charging The receiving device is used to convert the alternating magnetic field into direct current to charge the battery; the battery is used to supply power to the consuming components.
  • the electrical equipment may be an electric vehicle, wherein the wireless charging receiving device may be located on the electric vehicle, and the wireless charging transmitting device may be located on the ground.
  • the electric equipment can be charged using the wireless charging transmitter provided by any of the implementations described in the first aspect described above, the electric equipment has high stability and safety during the wireless charging process.
  • FIG. 1 is a schematic diagram of a wireless charging system provided by the prior art
  • Figure 2a is a schematic diagram of a wireless charging system for electric vehicles provided by an embodiment of the application.
  • Figure 2b is a schematic diagram of the structure of the electric vehicle wireless charging system provided in Figure 2a;
  • FIG. 2c is a schematic diagram of a wireless charging and transmitting device provided by Embodiment 1 of the device of this application;
  • Fig. 3a is a circuit diagram of the lead and lag arm impedance adjustment circuits of the wireless charging and transmitting device according to the second embodiment of the application device respectively including an inductance branch;
  • Fig. 3b is a schematic diagram of the waveform relationship when the phase shift angle corresponding to Fig. 3a is larger;
  • FIG. 3c is a schematic diagram of the waveform relationship of the leading bridge arm when the phase shift angle is small corresponding to FIG. 3a;
  • 3d is a schematic diagram of the waveform relationship of the lagging bridge arm when the phase shift angle is small corresponding to FIG. 3a;
  • 3e is a graph showing the relationship between the current I 1a in the leading arm and the phase shift angle when the leading and lagging arm impedance adjustment circuit provided in the second embodiment of the application includes an inductance branch;
  • FIG. 4 is a circuit diagram of the leading and lagging bridge arm impedance adjustment circuits provided by the third embodiment of the application, respectively, including two inductance branches;
  • Fig. 5a is a circuit diagram of the leading and lagging bridge arm impedance adjustment circuits provided in the fourth embodiment of the application, respectively, including a controllable inductance branch and a fixed inductance branch;
  • 5b is a circuit diagram of the leading and lagging bridge arm impedance adjustment circuits provided in the fourth embodiment of the application, respectively, including two controllable inductance branches and one fixed inductance branch;
  • FIG. 6a is a circuit diagram of a leading and lagging bridge arm impedance adjustment circuit provided in the fifth embodiment of the application, each including a controllable inductance branch and a diode clamp circuit on the controllable inductance branch;
  • FIG. 6b is a circuit diagram of the impedance adjusting circuit including two controllable inductance branches and a diode clamping circuit exists on the first controllable inductance branch;
  • Fig. 6c is a circuit diagram of the impedance adjusting circuit including two controllable inductance branches and a diode clamp circuit is present on the second controllable inductance branch;
  • Fig. 6d is a circuit diagram of the impedance adjusting circuit including two controllable inductance branches, and each controllable inductance branch has a diode clamp circuit;
  • Fig. 6e is a circuit diagram of the impedance adjusting circuit including two controllable inductance branches and one fixed inductance branch, and each inductance branch has a diode clamp circuit;
  • FIG. 7a is a circuit diagram of an impedance adjusting circuit provided by a sixth embodiment of the application, wherein the first end of the impedance adjustment circuit is connected to the midpoint of the DC bus of the DC power source;
  • FIG. 7b is a circuit diagram of another wireless charging and transmitting device provided by Embodiment 6 of the device of this application.
  • FIG. 7c is a circuit diagram of still another wireless charging and transmitting device provided by Embodiment 6 of the device of this application.
  • FIG. 7d is a circuit diagram of yet another wireless charging and transmitting device provided by Embodiment 6 of the device of this application;
  • FIG. 7e is a circuit diagram of another wireless charging and transmitting device provided by Embodiment 6 of the device of this application.
  • FIG. 7f is a circuit diagram of yet another wireless charging and transmitting device provided by Embodiment 6 of the device of this application.
  • FIG. 7g is a circuit diagram of the leading or lagging bridge arm impedance adjustment circuit provided by the sixth embodiment of the application device including a DC blocking capacitor;
  • FIG. 7h is a circuit diagram of the leading or lagging bridge arm impedance adjustment circuit provided by the sixth embodiment of the application device including two DC blocking capacitors;
  • FIG. 7i is a circuit diagram of the leading or lagging bridge arm impedance adjustment circuit provided by the sixth embodiment of the device of this application including three DC blocking capacitors;
  • FIG. 8 is a flowchart of a wireless charging control method provided by an embodiment of the application.
  • FIG. 9 is a schematic diagram of a wireless charging system provided by an embodiment of the application.
  • FIG. 10 is a schematic diagram of an electric device provided by an embodiment of the application.
  • FIG. 2a is a schematic diagram of an electric vehicle wireless charging system provided by an embodiment of the application.
  • the wireless charging system may at least include: an electric car 1000 and a wireless charging station 1001.
  • the electric vehicle 1000 may include a wireless charging receiving device 1000a
  • the wireless charging station 1001 may include a wireless charging transmitting device 1001a.
  • the charging process of the wireless charging system is to perform non-contact charging through the wireless charging receiving device 1000a located in the electric vehicle 1000 and the wireless charging transmitting device 1001a located in the wireless charging station 1001 working together.
  • the wireless charging station 1001 may specifically be a fixed wireless charging station, a fixed wireless charging parking space, or a wireless charging road.
  • the wireless charging transmitting device 1001a can be set on the ground or buried under the ground ( Figure 2a shows the situation when the wireless charging transmitting device 1001a is buried under the ground), and can wirelessly charge the electric vehicle 1000 located above it.
  • the wireless charging receiving device 1000a may be integrated at the bottom of the electric vehicle 1000.
  • the electric vehicle 1000 When the electric vehicle 1000 enters the wireless charging range of the wireless charging transmitter 1001a, the electric vehicle 1000 can be charged in a wireless charging mode.
  • the power receiving antenna and the rectifier circuit of the wireless charging receiving device 1000a can be integrated or separated. When separated, the rectifier in the rectifier circuit is usually placed in the car.
  • the power transmitting antenna and the inverter of the wireless charging transmitting device 1001a can be integrated or separated.
  • the non-contact charging can be wireless energy by the wireless charging receiving device 1000a and the wireless charging transmitting device 1001a through the electric field or magnetic field coupling.
  • the transmission may specifically be electric field induction, magnetic induction, magnetic resonance, or wireless radiation, which is not specifically limited in the embodiment of the present application.
  • the electric vehicle 1000 and the wireless charging station 1001 can also be charged in two directions, that is, the wireless charging station 1001 charges the electric vehicle 1000 through the power supply, or the electric vehicle 1000 discharges to the power supply.
  • Figure 2b is a schematic structural diagram of the electric vehicle wireless charging system provided in Figure 2a.
  • the wireless charging and transmitting device 1001a shown in FIG. 2b includes: a transmission conversion module 1001a1, a power transmission antenna 1001a2, a transmission control module 1001a3, a communication module 1001a4, an authentication management module 1001a5, and a storage module 1001a6.
  • the wireless charging receiving device 1000a includes: a power receiving antenna 1000a2, a receiving control module 1000a3, a receiving conversion module 1000a1, a vehicle communication module 1000a4, an energy storage management module 1000a5, and an energy storage module 1000a6.
  • the receiving transformation module 1000a1 can be connected to the energy storage module 1000a6 through the energy storage management module 1000a5, and the received energy is used to charge the energy storage module 1000a6, and further used for driving the electric vehicle.
  • the energy storage management module 1000a5 and the energy storage module 1000a6 may be located inside the wireless charging receiving device 1000a or outside the wireless charging receiving device 1000a, which is not specifically limited in the embodiment of the present application.
  • the transmission conversion module 1001a1 can be connected to an external power source to convert AC or DC power obtained from the external power supply into high-frequency AC power.
  • the transmission conversion module 1001a1 at least includes a power factor correction unit and an inverter;
  • the transmission conversion module 1001a1 at least includes an inverter.
  • the power factor correction unit is used to make the phase of the input current of the wireless charging system consistent with the phase of the grid voltage, reduce the harmonic content of the wireless charging system, and increase the power factor value to reduce the pollution of the wireless charging system to the grid and improve reliability
  • the power factor correction unit can also be used to increase or decrease the output voltage of the power factor correction unit according to the needs of the subsequent stage.
  • the inverter is used to convert the voltage output by the power factor correction unit into a high frequency AC voltage and then act on the power transmitting antenna 1001a2.
  • the high frequency AC voltage can improve the transmission efficiency and transmission distance.
  • Figure 2b takes the wireless charging transmitter device 1001a externally connected to an external power supply as an example. It can be understood that the power supply may also be a power supply inside the wireless charging transmitter device 1001a.
  • the power transmitting antenna 1001a2 is used to transmit the alternating current output from the transmitting conversion module 1001a1 in the form of an alternating magnetic field.
  • the transmission control module 1001a3 can control the voltage, current and frequency conversion parameter adjustments of the transmission conversion module 1001a1 according to the actual wireless charging transmission power requirements to control the voltage and current output adjustments of the high-frequency alternating current in the power transmission antenna 1001a2.
  • the communication module 1001a4 and the vehicle communication module 1000a4 are used to implement wireless communication between the wireless charging transmitter device 1001a and the wireless charging receiver device 1000a, including power control information, fault protection information, switch machine information, interactive authentication information, etc.
  • the wireless charging transmitting device 1001a can receive information such as the attribute information, charging request and interactive authentication information of the electric vehicle sent by the wireless charging receiving device 1000a; on the other hand, the wireless charging transmitting device 1001a can also send to the wireless charging receiving device 1000a Wireless charging transmission control information, interactive authentication information, wireless charging historical data information, etc.
  • the above-mentioned wireless communication methods may include, but are not limited to, Bluetooth, wireless broadband (WIreless-Fidelity, WiFi), Zigbee, Radio Frequency Identification (RFID), and Long Range , Lora) wireless technology, near field communication technology (Near Field Communication, NFC) any one or a combination of multiple.
  • the communication module 1001a4 can also communicate with the smart terminal of the user of the electric vehicle, and the user can realize remote authentication and user information transmission through the communication function.
  • the authentication management module 1001a5 is used for interactive authentication and authority management between the wireless charging transmitter 1001a and the electric vehicle in the wireless charging system.
  • the storage module 1001a6 is used to store the charging process data, interactive authentication data (such as interactive authentication information), and permission management data (such as permission management information) of the wireless charging transmitter 1001a, among which the interactive authentication data and permission management data can be factory settings It can also be set by the user, which is not specifically limited in the embodiment of the present application.
  • the power receiving antenna 1000a2 is used to receive the electromagnetic energy emitted by the power transmitting antenna 1001a2 in the form of an alternating magnetic field.
  • the structural combinations of the power transmitting antenna 1001a2 and the power receiving antenna 1000a2 in the wireless charging system include SS type, PP type, SP type, PS type, LCL-LCL type, LCL-P type, etc.
  • the embodiments of this application are There are no specific restrictions.
  • the wireless charging transmitting device 1001a and the wireless charging receiving device 1000a in the wireless charging system may also include both a power receiving antenna and a power transmitting antenna, which may be independent or Integrated.
  • the receiving conversion module 1000a1 is used to convert the electromagnetic energy received by the power receiving antenna 1000a2 into the DC voltage and DC current required for charging the energy storage module 1000a6.
  • the receiving conversion module 1000a1 at least includes a compensation circuit and a rectifier, where the rectifier converts the high-frequency resonance current and voltage received by the power receiving antenna into a direct current voltage and a direct current.
  • the receiving control module 1000a3 can control the voltage, current, and frequency conversion parameter adjustment of the receiving conversion module 1000a1 according to the actual wireless charging receiving power demand.
  • the inverter of the wireless charging and transmitting device 1001a includes an inverter circuit and a compensation circuit, wherein the inverter circuit is used to invert the DC power output by the DC power supply into AC power.
  • the controllable switch in the inverter circuit of the wireless charging transmitter implement ZVS, so as to reduce the power consumption of the controllable switch during operation.
  • the input voltage of the inverter can be adjusted to keep the phase shift angle unchanged, so that the inverter can achieve ZVS under all working conditions.
  • adjusting the input voltage of the inverter requires an additional DC conversion circuit at the input end of the inverter, which will increase the volume and cost of the wireless charging transmitter.
  • the output voltage of the inverter can be adjusted by adjusting the inverter phase shift, but for the leading and lagging bridge arms, it cannot be guaranteed that the inverter can achieve zero voltage switching under various output voltages (different phase shift angles).
  • the reflected impedance from the receiving end to the transmitting end is resistive and capacitive, it is more difficult to ensure that the controllable switch tube realizes ZVS, and once the controllable switch tube loses zero voltage switching, the switching loss of the inverter will be relatively large. Even damaged.
  • the present application provides a wireless charging transmitter device, which includes an impedance adjusting circuit and a controller, wherein the impedance adjusting circuit includes a leading arm impedance adjusting circuit and a lagging arm impedance adjusting circuit,
  • the leading arm impedance adjusting circuit and the lagging arm impedance adjusting circuit respectively include an inductance branch, each inductive branch includes at least one controllable inductance branch, and each controllable inductance branch includes at least one inductor and at least one Switch, all inductive branches are connected in parallel or in series.
  • the first ends of the leading and lagging bridge arm impedance adjustment circuits are respectively connected to the leading and lagging bridge arms, and the first ends of the leading and lagging bridge arm impedance adjustment circuits are respectively connected to the output port of the DC power supply, using the leading and lagging bridge arm impedance adjustment circuits as Inductive current is injected into the leading and lagging bridge arms to increase the inductive current component of the leading and lagging bridge arms.
  • the controller is used to control the turn-on or turn-off of the switch in the inductor branch to change the current flowing out of the lead and lag bridge arms, that is, the controller controls the injection of the lead and lag bridge by controlling the number of conductive branches
  • the current of the arm is large, so that the controllable switch tube of the leading and lagging bridge arm realizes zero voltage switching.
  • the process of switching the inductor branch by the controller does not need to interrupt wireless charging
  • the power transmission of the transmitter improves the stability and reliability of the wireless charging transmitter.
  • the controllable switch tube realizes zero voltage switching
  • the controllable switch tube realizes ZVS.
  • FIG. 2c is a schematic diagram of a wireless charging and transmitting device according to Embodiment 1 of the device of this application.
  • the wireless charging transmitter provided by the embodiments of the present application is located at the transmitter, and is used to convert the direct current input from the DC power supply into an alternating magnetic field and send it to the wireless charging receiver.
  • the wireless charging transmitter can be applied to the field of electric vehicles.
  • the car is charged, and the wireless charging receiver can be located on the electric car.
  • the device includes: an inverter circuit 201, a transmitting coil 202, an impedance adjusting circuit 203, a controller 204, and a compensation circuit 206.
  • the inverter circuit 201 inverts the DC power output by the DC power supply into AC power.
  • the inverter circuit 201 includes a leading bridge arm and a lagging bridge arm, wherein the voltage phase of the leading bridge arm leads the voltage phase of the lagging bridge arm in the same period.
  • the compensation circuit 206 compensates the alternating current output from the inverter circuit 201 and sends it to the transmitting coil 202.
  • the inverter circuit 201 includes controllable switching tubes S1-S4 as an example.
  • the bridge arms including the controllable switching tubes S3 and S4 are the leading bridge arms, and the bridge arms including the controllable switching tubes S1 and S2 are the lagging bridges. arm.
  • the transmitting coil 202 transmits alternating current in the form of an alternating magnetic field.
  • the impedance adjusting circuit 203 includes a leading arm impedance adjusting circuit and a lagging arm impedance adjusting circuit.
  • the leading arm impedance adjusting circuit and the lagging arm impedance adjusting circuit respectively include at least one inductance branch, wherein the inductive branch includes a controllable inductor.
  • each fixed inductance branch includes at least one inductance without switch control, wherein each inductance branch of the bridge arm impedance adjustment circuit is advanced
  • the circuits are connected in parallel or series with each other, and the inductance branches of the lagging bridge arm impedance adjustment circuit are also connected in parallel or series with each other.
  • the first ends of the leading and lagging bridge arm impedance adjustment circuits are respectively connected to the midpoints of the leading and lagging bridge arms.
  • the second ends of the leading and lagging bridge arm impedance adjusting circuits are respectively connected to the output ports of the DC power supply 205, namely the midpoint B between the controllable switch tubes S1 and S2 and the midpoint A between S3 and S4 in FIG. 2c.
  • the controller 204 can control the on or off of the switches in the inductance branch to change the current flowing out of the leading and lagging bridge arms, so that the controllable switches of the leading and lagging bridge arms realize ZVS.
  • controller provided in this application is equivalent to the emission control module 1001a3 in FIG. 2b.
  • the phase relationship between the midpoint current flowing out of the leading and lagging bridge arms and the leading and lagging bridge arm voltages of the inverter circuit 201 will be changed, thereby changing the leading and lagging bridge arm loads.
  • the reactance when the reflected impedance from the receiving end to the transmitting end may be resistive-capacitive, the reactance of the equivalent output impedance of the transmitting end may also change, which in turn also changes the reactance of the leading and lagging bridge arm loads.
  • the controllable switches S1-S4 cannot achieve ZVS.
  • This application injects suitable inductive currents into the leading or lagging bridge arms through the inductance branch to make the lead or lagging
  • the current phase in the bridge arm keeps lagging behind the phase of the inverter circuit 201 leading or lagging the output voltage of the bridge arm.
  • the number of inductance branches included in the lead and lag arm impedance adjustment circuit can continue to be expanded to more, so that the controllable switches of the lead and lag arms can achieve ZVS under different phase shift angles.
  • the controller to control the on and off of the switch in each controllable inductance branch, change the number of controllable inductance branches connected (including 0), and then change the inductive current injected by the impedance adjustment circuit for the lead and lag arms the size of.
  • the inductance of the inductance in each controllable and fixed inductance branch can be established.
  • the matching between the current and the phase shift angle is more accurate, avoiding that when the controllable switch of the leading or lagging bridge arm has achieved ZVS, the current in the leading or lagging bridge arm increases too much and aggravating the controllable switch on the leading or lagging bridge arm The conduction loss and switching loss of the tube.
  • the inductance values of the inductances in each inductance branch may be equal or unequal, and can be specifically set according to needs, which is not specifically limited in this application.
  • the switch types in each controllable inductance branch can be the same or different.
  • the switch type may be any one of the following: relay, circuit breaker, contactor, insulated gate bipolar transistor (IGBT) or metal oxide semiconductor field effect transistor (MOS) tube.
  • Each controllable inductance branch may include multiple inductors in parallel or in series, and the connection relationship between the inductor and the switch may also be in parallel or in series.
  • the wireless charging transmitter provided in the embodiment of the application adds an impedance adjustment circuit and a controller.
  • the impedance adjustment circuit includes a lead arm impedance adjustment circuit and a lag arm impedance adjustment circuit.
  • the lead arm impedance adjustment circuit and the lag arm impedance adjustment circuit respectively include at least one inductance branch,
  • the inductance branch includes a controllable inductance branch and a fixed inductance branch.
  • Each controllable inductance branch includes at least one inductance and at least one switch.
  • Each fixed inductance branch includes at least one inductance without switch control.
  • the fixed inductance branches and controllable inductance branches of the bridge arm impedance adjustment circuit are connected in parallel or series with each other, and the fixed inductance branches and the controllable inductance branches of the lagging bridge arm impedance adjustment circuit are also connected in parallel or series.
  • the first ends of the leading and lagging bridge arm impedance adjusting circuits are respectively connected to the midpoints of the leading and lagging bridge arms, and the second ends of the leading and lagging bridge arm impedance adjusting circuits are respectively connected to the output port of the DC power supply 205.
  • the controller is used to control the turn-on or turn-off of the switch in the controllable inductance branch to change the current flowing out of the leading and lagging bridge arms, that is, the controller controls the injection by controlling the number of controllable inductance branches that are turned on
  • the current magnitudes of the leading and lagging bridge arms enable the controllable switch tubes of the leading and lagging bridge arms to realize ZVS.
  • the controller controls the leading or lagging bridge arm impedance adjustment circuit to connect to the leading or lagging bridge arm.
  • the controller can control the on and off of the switches in each controllable inductance branch to realize the difference in inductance presented by the leading or lagging bridge arm impedance adjustment circuit.
  • the inductance of the leading or lagging bridge arm impedance adjustment circuit is different, and the inductive current injected into the leading or lagging bridge arm is different.
  • the process of the controller switching the controllable inductance branch does not affect the power transmission of the wireless charging and transmitting device, and the stability and reliability of the wireless charging and transmitting device are improved.
  • the following takes the lead and lag arm impedance adjustment circuit including at least one controllable inductance branch as an example to introduce the working principle.
  • the controller can control the closing and opening of the leading arm impedance adjustment circuit according to the controllable switch of the leading arm.
  • the current flowing into the compensation circuit or the current flowing out of the leading arm is controlled to turn on or off the switch in the leading arm impedance adjustment circuit.
  • the turn-off time is the time corresponding to the controllable switching tube from turning on to turning off; the turning-on time is the time corresponding to the turning off of the controllable switching tube to turning on.
  • the actual turn-off time and the actual turn-on time of the switch tube will be one delay time longer than the signal of the turn-off time and the turn-on time sent by the controller. Therefore, in the embodiment of the present application, the period from the off time to the on time is the longest period from the off time to the on time including the signal delay time.
  • the controller controls the on or off of the switch in the leading impedance adjustment circuit according to the current flowing into the compensation circuit or the current flowing out of the leading bridge arm according to the time when the controllable switch tube of the leading arm is turned off.
  • the lagging arm impedance adjustment circuit includes at least one controllable inductance branch.
  • the working principle is similar to that of the leading arm impedance adjustment circuit.
  • the controller flows into or out of the compensation circuit according to the time when the controllable switch of the lagging arm is turned off.
  • the current of the lagging bridge arm controls the on or off of the switch in the lagging bridge arm impedance adjustment circuit.
  • FIG. 3a is a circuit diagram of an impedance adjusting circuit provided in the second embodiment of the application, including a leading and lagging bridge arm impedance adjusting circuit, and the leading and lagging bridge arm impedance adjusting circuits each include a controllable inductance branch.
  • the circuit provided in this embodiment also includes a current detection circuit 208.
  • the current detection circuit 208 is used to detect the current flowing into the compensation circuit or the current flowing out of the leading and lagging bridge arms when the controllable switch tubes of the leading and lagging bridge arms are turned off, and detecting the controllability of the leading and lagging bridge arms.
  • the current flowing into the compensation circuit or the current flowing out of the leading and lagging bridge arms when the switch is turned off is sent to the controller.
  • inverter circuit 201 The description of the inverter circuit 201, the transmitting coil 202, the DC power supply 205 and the compensation circuit 206 can be found in the preceding text.
  • the direction of the current flowing out of the leading or lagging bridge arm is taken as the positive direction, and the positive direction of the voltage is shown in the figure. Repeat.
  • the current flowing into the compensation circuit is equal to the current flowing out of the leading or lagging bridge arm. Therefore, the current detection circuit 208 is used below. Detect the current flowing into the compensation circuit as an example.
  • the inductance branch of the leading arm impedance adjustment circuit 203 includes an inductor La and a switch Ka connected in series, the first end of the inductor La is connected to the output port M of the DC power supply 205, and the second end of the inductor La is connected through the switch Ka
  • the midpoint A of the leading bridge arm is connected between the controllable switches S3 and S4, because at this time, the leading bridge arm impedance adjustment branch includes only one inductive branch.
  • the controller is not shown in Figure 3a. The controller controls the on or off of the switch Ka in the inductive branch.
  • the controller controls whether the inductor branch injects an inductive current I Lb into the leading bridge arm by controlling the on and off of the inductor branch switch.
  • the turn-off current in the lagging bridge arm in Figure 3a is I 1b
  • the current in the inductor branch is I Lb
  • the current flowing into the compensation circuit 206 is I 2b
  • I 2b is also the output current of the inverter circuit 201
  • I 1b I Lb +I 2b (2)
  • the controller controls whether the inductive branch injects an inductive current I Lb into the lagging bridge arm by controlling the on and off of the inductive branch switch.
  • the turn-off current of the leading or lagging bridge arm can make the controllable switch tube of the leading or lagging bridge arm realize ZVS. set to a preset maximum current I 0 (I 0 ⁇ 0) , be appreciated that the preset current can be appropriately adjusted according to actual needs, for example, may be selected smaller than I 0 I 0 but relatively close to a current The value is the preset current, and the preset current can also be adjusted according to the capacitor voltage of the compensation circuit.
  • the current detection circuit 208 detects that the current flowing into the compensation circuit when the controllable switch tube of the leading arm is turned off is I 3 , it can be understood that when none of the inductance branches are turned on, the current I 3 and the current flowing out of the leading arm are When the current is equal, the controller compares I 3 with the preset current I 0. When I 3 >I 0 , the controllable switch tube of the leading bridge arm cannot achieve ZVS, and the controller controls the inductance branch to be turned on, and the inductance branch moves forward The midpoint of the bridge arm injects an inductive current so that the controllable switch tube of the lagging bridge arm realizes ZVS.
  • the controllable switch tube of the leading bridge arm has been able to realize ZVS, and the controller turns off the inductive branch to reduce power consumption.
  • the current detection circuit 208 detects the current flowing into the compensation circuit when the lagging bridge arm controllable switch is turned off and compares it with the preset current I 0 , and the controller controls whether the inductor branch needs to be turned on to achieve ZVS.
  • the on-off of the inductor branch can also be controlled according to the phase shift angle.
  • the controller searches for the corresponding relationship between the phase shift angle and the current flowing out of the leading or lagging bridge arm at the time when the controllable switch tube of the lagging bridge arm is turned off according to the output power; different output powers correspond to different corresponding relations; the correspondence found by searching The relationship obtains the phase shift angle interval in which the current phase shift angle of the inverter circuit is located, and controls the on or off of the switch in the controllable inductor branch according to the phase shift angle interval. Different phase shift angle intervals correspond to different numbers of inductors. Branch road.
  • the current flowing out of the leading or lagging bridge arm is equal to the absolute value I 2 of the current flowing into the compensation circuit.
  • the phase shift angle of the inverter circuit under different output powers and the current flowing out of the leading or lagging bridge arm at the time when the controllable switching tube of the leading and lagging bridge arms are turned off are established in advance. That is, the corresponding relationship is the corresponding relationship between the phase shift angle of the inverter circuit under different output powers and the current I 2 flowing into the compensation circuit, and different output powers correspond to different corresponding relationships.
  • the turn-off currents of the leading and lagging bridge arms are used to represent the currents flowing out of the leading and lagging bridge arms at the time when the controllable switch tubes of the leading and lagging bridge arms are turned off.
  • the corresponding relationship can be achieved by using curves or tables.
  • different output powers correspond to different curves.
  • the curve is a two-dimensional curve of the phase shift angle and the turn-off current of the leading or lagging bridge arm, that is, the two-dimensional curve characterization
  • the corresponding relationship between the phase shift angle and the turn-off current of the lagging bridge arm is described.
  • the output power of the inverter circuit 201 does not consider the transmission efficiency between the wireless charging transmitter and the wireless charging receiving device, the output power of the inverter circuit 201 is equivalent to the output power of the wireless charging receiving device Generally, the transmission efficiency is less than 100%, and there is a certain conversion relationship between the output power of the inverter circuit and the output power of the wireless charging receiving device. Therefore, it can also be understood that the controller controls the on or off of the switch in the inductive branch according to the current phase shift angle of the inverter circuit 201 and the output power of the wireless charging receiving device. Among them, the output power of the wireless charging receiving device is the output power of the wireless charging system.
  • the on-off of the inductor branch can be controlled according to the phase shift angle.
  • the phase of the current I 2 flowing into the compensation circuit 206 (that is, the output current of the inverter circuit 201) has lags behind the leading arm output voltage U of the inverter circuit 201. 1 (the voltage of the midpoint of the leading bridge arm relative to the negative bus).
  • the controllable switches S3 and S4 can already achieve ZVS.
  • the phase of the current I 2 flowing into the compensation circuit 206 (that is, the output current of the inverter circuit 201) has lagged behind the output voltage U 2 of the lagging arm of the inverter circuit 201 (the midpoint of the lagging arm is relative to the voltage of the negative bus ), when the current I 1b in the lagging bridge arm is the current I 2 flowing into the compensation circuit 206, the controllable switches S1 and S2 can already achieve ZVS.
  • the controller controls the lead and lag arm inductance branches. switch K a, K b is turned off, the inductor branch I La inductive current is not injected to the lagging leg, I Lb, bring the power consumption in order to avoid inductance access.
  • the controller controls the switch K b of the inductive branch to close, so that the inductive branch injects the inductive current I Lb into the lagging bridge arm.
  • the inductive current I Lb is superimposed with the current I 2b flowing into the compensation circuit 206 to arm current hysteresis lags the phase lagging leg of the inverter circuit 201 outputs the phase voltage U 2, so that the controllable switches S1 and S2 of the lagging leg achieve ZVS.
  • the maximum value that can be reached by the turn-off current in the leading bridge arm when the controllable switch tube on the leading bridge arm realizes ZVS can be set as the preset current I 0 , and different output powers of the inverter circuit 201 correspond to different preset currents I 0 .
  • a two-dimensional graph on each phase shifting angle ⁇ 0 corresponding to the predetermined current I 0 to the phase shifting angle ⁇ 0 is a preset angle, it is divided into two phase-shift angle interval, i.e., are greater than a preset
  • FIG. 3e is a graph of the relationship between I 1a and the phase shift angle when the impedance adjusting branch provided in the second embodiment of the application includes an inductance branch.
  • I 2a is equal to I 1a , which is equal to I 2 .
  • the inverter circuit is at different output powers.
  • the turn-off current of the leading arm can make the controllable switch tube of the leading arm to achieve ZVS as the maximum value.
  • I 0 (I 0 ⁇ 0) provided current I 0 (I 0 ⁇ 0) , be appreciated that the preset current can be appropriately adjusted according to actual needs, for example, may be selected with less than a certain current I 0 I 0 but closer to the predetermined current value, The preset current can also be adjusted according to the capacitor voltage of the compensation circuit.
  • the phase shift angle corresponding to the preset current I 0 is the preset angle ⁇ 0 , then the interval of the phase shift angle smaller than ⁇ 0 is the first phase shift angle interval, and the interval of the phase shift angle greater than ⁇ 0 is the second phase shift angle Interval.
  • the controllable switch tube of the lagging bridge arm cannot achieve ZVS, and the controller needs to control the inductor support.
  • the circuit is connected, and an inductive current is injected into the midpoint of the leading bridge arm.
  • the controllable switch tube of the leading bridge arm has been able to achieve ZVS, and the inductor can be turned off Branch to reduce power consumption.
  • the on-off state of the inductance branch of the lagging bridge arm can be controlled through the graph of the relationship between the current I 1b in the lagging bridge arm and the angle of the shift term, so as to ensure that the controllable switch tube of the lagging bridge arm realizes ZVS.
  • this application does not specifically limit the number of inductive branches of the leading or lagging bridge arm impedance adjustment circuit 203. It can be selected and set according to actual needs and hardware reference and cost. The greater the number of inductive branches , The more the inductance value appears, the more accurate the matching corresponding to the phase shift angle.
  • the controller controls the on-off state of the switch in each inductance branch, and can adjust the size of the inductive current injected by the impedance adjustment circuit to the leading or lagging bridge arm, so that the controllable switch tube of the lagging bridge arm can be realized under different phase shift angles. ZVS.
  • each inductor branch of the leading or lagging bridge arm impedance adjusting circuit 203 may be connected in parallel.
  • Each inductor branch is not limited to one inductor L, and multiple inductors can be connected in parallel or in series.
  • the size of the inductance on each branch can be the same or different, and the presented inductance values are richer, and the matching of the corresponding shift angle is more accurate.
  • Fig. 4 is a circuit diagram when the lead or lag arm impedance adjustment circuit of the wireless charging transmitter device includes two inductance branches.
  • inverter circuit 201 the transmitting coil 202, the DC power supply 205 and the compensation circuit 206 in the circuit can be referred to the foregoing, and will not be repeated here.
  • the leading arm impedance adjustment circuit 403 includes a first inductance branch and a second inductance branch.
  • the first inductance branch includes a first inductor L1a and a first switch K1a connected in series.
  • the first end of L1a is connected to the output port of the DC power supply.
  • the second end of M, L1a is connected to the midpoint A of the leading bridge arm through K1a;
  • the second inductance branch includes a second inductor L2a and a second switch K2a connected in series, and the first end of L2a is connected to the output port M, L2a of the DC power supply.
  • the second end of is connected to the midpoint of the leading bridge arm through K2a; the inductance of the first inductor L1a and the second inductor L2a may be the same or different, which is not specifically limited in this application.
  • the controller controls the turning on or off of the first switch K1a and the second switch K2a according to the current of the leading bridge arm at the time when the controllable switch tube of the leading bridge arm (that is, the controllable switching tube S3 or S4) is turned off Off.
  • the turn-off time is the time corresponding to the controllable switching tube from turning on to turning off;
  • the turning-on time is the time corresponding to the turning off of the controllable switching tube to turning on.
  • the actual turn-off time and the actual turn-on time of the switch tube will be one delay time longer than the signal of the turn-off time and the turn-on time sent by the controller. Therefore, in the embodiment of the present application, the period from the off time to the on time is the longest period from the off time to the on time including the signal delay time.
  • the first inductance branch and the second inductance branch are connected in parallel to form an adjustment branch.
  • the first end of the leading arm impedance adjusting circuit is connected to the midpoint A of the leading arm, and the second end of the leading arm impedance adjusting circuit is connected to the DC power supply 205
  • the output port M is connected between the controllable switch tubes S3 and S4.
  • the turn-off current in the leading arm is I 1a
  • the current of the leading arm impedance adjusting circuit is I La
  • the three still satisfy the equation (1 ), that is, I 1a I La +I 2a
  • the current I La of the leading bridge arm impedance adjusting circuit is the sum of the currents passing through the two inductor branches.
  • the leading arm impedance adjustment circuit injects an inductive current I La into the leading arm, which in turn affects the reactance of the turn-off current I 1a in the leading arm.
  • the controller controls the on and off of each inductive branch switch and then controls the inductive branch to inject the magnitude of the inductive current I La into the leading bridge arm.
  • the turn-off current I 1a in the leading arm is equal to the current I 2a flowing into the compensation circuit, and the direction of the current flowing out of the leading arm is the positive direction.
  • the turn-off current of the leading bridge arm can make the controllable switch tube of the leading bridge arm realize the maximum value when ZVS is set to the preset Set current I 0 .
  • I 2a and I 1a are not equal, and the turned-on inductive branch will affect the magnitude of I 1a .
  • the maximum value that the controllable switch of the leading bridge arm can achieve when ZVS is achieved in the leading bridge arm is set as the threshold current I 4 , and
  • the threshold current I 4 is greater than the preset current I 0 because an inductive branch is turned on to inject an inductive current into the leading bridge arm.
  • the different output power, output voltage, receiving end matching network and offset position of the inverter circuit 201 correspond to different preset currents I 0 and threshold currents I 4 .
  • the circuit provided in this embodiment also includes a current detection circuit 406.
  • the current detection circuit 406 is used to detect the current flowing into the compensation circuit or the current flowing out of the leading bridge arm when the controllable switch tube of the leading arm is turned off, and flow the detected controllable switching tube of the leading arm into the compensation circuit at the turning off time.
  • the current or the current flowing out of the leading bridge arm is sent to the controller.
  • the current detection circuit 406 detects that the current flowing into the compensation circuit when the controllable switch of the lagging bridge arm is turned off is I 3 , and the current I 3 is equal to the current I 1a flowing out of the leading bridge arm.
  • the controller compares I 3 with the interval values of the current (I 0 and I 4 ), and I 3 falls into different intervals, correspondingly controlling the closing of different numbers of inductive branches.
  • the controller controls both the first inductive branch and the second inductive branch to be connected to the leading bridge arm.
  • I 4 > I 3 > I 0 the controllable switch tube of the leading bridge arm cannot achieve soft switching.
  • the controller only needs to control the first inductive branch or the second inductive branch. When any one of them is turned on, sufficient inductive current can be injected into the midpoint A of the leading bridge arm; when I 3 ⁇ I 0 , the controllable switch tube of the leading bridge arm can achieve ZVS, and the controller turns off the inductive branch To reduce power consumption.
  • the current detection circuit 406 can detect the current flowing out of the leading bridge arm when the controllable switch tube of the leading bridge arm is turned off and send the detection result to the controller.
  • the difference between the current flowing into the compensation circuit and the preset current is obtained, and the switch in the inductor branch is controlled to be turned on and off according to the difference.
  • the difference in the difference corresponds to closing a different number of inductor branches.
  • the current detection circuit 406 detects the current I 2b flowing into the compensation circuit when the controllable switch tube of the lagging arm is turned off and compares it with the preset current I 0 and the threshold current I 4 , and the controller controls whether the inductor branch needs to be turned on To achieve ZVS.
  • the inductive branch of the leading or lagging bridge arm impedance adjustment circuit of the wireless charging transmitter not only includes at least one controllable inductive branch, but also includes a fixed inductive branch.
  • the fixed inductive branch includes at least one Fixed inductance, no controllable switch control. The first end of the fixed inductance branch is connected to the port M of the DC power supply 205, and the second end of the fixed inductance branch is connected to the midpoint A or B of the leading or lagging bridge arm.
  • FIG. 5a is a circuit diagram when the leading arm impedance adjustment branch of the wireless charging transmitter includes a controllable inductance branch and a fixed inductance branch.
  • inverter circuit 201 the transmitting coil 202, the DC power supply 205 and the compensation circuit 206 in the circuit can be referred to the foregoing, and will not be repeated here.
  • the leading arm impedance adjustment circuit 503 includes a first controllable inductance branch and a first fixed inductance branch, wherein the first controllable inductance branch includes a first inductance L1a and a first switch K1a connected in series, and the first end of L1a is connected The output port M of the DC power supply, the second end of L1a is connected to the midpoint A of the leading bridge arm through K1a; the first fixed inductance branch includes the second inductor L2a, and the first end of L2a is connected to the output port M of the DC power supply.
  • the second end is connected to the midpoint A of the leading bridge arm; the inductances of the first inductor L1a and the second inductor L2a may be the same or different, which is not specifically limited in this application.
  • the size of the fixed inductance can be matched according to the characteristics of the load at the receiving end, even when the equivalent impedance of the receiving end is resistive-capacitive, the inductive current is injected into the leading arm through the fixed inductance branch, so that the switch tube of the leading arm realizes ZVS .
  • the specific value of the fixed inductance is related to the size of the load, and is not specifically limited in the embodiment of the present application.
  • the controller (not shown) controls the turn-on or turn-off of the first switch K1a according to the current of the leading bridge arm when the controllable switch tube of the leading bridge arm (that is, the controllable switching tube S3 or S4) is turned off.
  • the turn-off time is the time corresponding to the controllable switch tube from turning on to turning off.
  • the first controllable inductance branch and the first fixed inductance branch are connected in parallel to form the inductance branch of the leading arm impedance adjusting circuit.
  • the first end of the leading arm impedance adjusting circuit is connected to the midpoint of the leading arm, that is, connected to the controllable arm.
  • the second end is connected to the output port of the DC power supply 205.
  • the turn-off current in the leading arm is I 1a
  • the current in the leading arm impedance adjustment branch is I La
  • the three still satisfy the equation (1), that is, I 1a I La +I 2a
  • the current in the leading arm impedance adjustment circuit is I La which is the sum of the currents passing through the first controllable inductance branch and the first fixed inductance branch.
  • the leading arm impedance adjustment circuit injects an inductive current I La into the leading arm, which in turn affects the reactance of the turn-off current I 1a in the leading arm. Since the fixed inductance branch is not provided with a switch, the inductance in the fixed inductance branch continues to provide inductive current for the leading bridge arm. At this time, the controller controls the on and off of the first controllable inductance branch switch and then controls the controllable inductive branch to inject the magnitude of the inductive current I La into the leading bridge arm. When the controllable inductance branch is not connected, the fixed inductance branch is already turned on, I 2a and I 1 are not equal, and the fixed inductance branch will affect the magnitude of I 1 .
  • this figure is a circuit diagram of a leading bridge arm impedance adjustment circuit provided in the fourth embodiment of the application, which includes a controllable inductance branch and a fixed inductance branch.
  • the circuit provided in this embodiment also includes a current detection circuit 506.
  • the current detection circuit 506 is used to detect the current flowing into the compensation circuit or the current flowing out of the leading bridge arm when the controllable switch tube of the leading arm is turned off, and flow the detected controllable switching tube of the leading arm into the compensation circuit at the turning off time. The current or the current flowing out of the leading bridge arm is sent to the controller.
  • the current detection circuit 506 detects that the current flowing into the compensation circuit at the time when the controllable switch tube of the leading bridge arm is turned off is I 5 , because there is a fixed inductance branch
  • the current I of is fixed
  • the current I 5 is smaller than the current I 1a flowing out of the leading arm.
  • the controller compares the fixed I 5 +I with the preset current I 0 , and I 5 falls into a different interval, correspondingly controlling a different number of inductive branches to close.
  • the controllable switch tube of the leading bridge arm cannot achieve soft switching and requires a larger inductive current.
  • the controller controls the controllable inductance branch to be turned on. At this time, the controller only needs to control the first An inductive branch can be turned on to inject enough inductive current into the midpoint of the leading arm; when I 5 +I is fixed ⁇ I 0 , the controllable switch tube of the leading arm can achieve ZVS, and the controller turns off the inductor Branch to reduce power consumption.
  • the lagging arm impedance adjustment branch can include a controllable inductance branch and a fixed inductance branch.
  • the current detection circuit 306 detects the current flowing into the compensation circuit at the time when the controllable switch tube of the lagging arm is turned off and compares it with the preset current I 0. The controller controls whether the controllable inductance branch needs to be turned on to achieve ZVS.
  • leading and lagging bridge arm impedance adjustment branches can also be at least one controllable inductance branch and at least one fixed inductance branch.
  • the fixed inductance branch does not need to exist in both the leading and lagging bridge arm impedance adjustment circuits.
  • This embodiment is different from the second embodiment in that the leading or lagging bridge arm impedance adjustment circuit of this embodiment includes at least one fixed inductor and is not controlled by a controllable switch.
  • the described embodiment is suitable for when the equivalent impedance of the receiving end is likely to be RC, the included fixed capacitor branch can automatically increase the inductive current flowing out of the leading or lagging bridge arm without the control of the controller.
  • the controllable switch tubes of the leading and lagging bridge arms can still achieve ZVS.
  • this application does not specifically limit the number of inductive branches of the leading or lagging bridge arm impedance adjustment circuit 203. It can be selected and set according to actual needs and hardware reference and cost. The greater the number of inductive branches , The more the inductance value appears, the more accurate the matching corresponding to the phase shift angle.
  • the controller controls the on-off state of the switch in each inductance branch, and can adjust the size of the inductive current injected by the impedance adjustment circuit to the leading or lagging bridge arm, so that the controllable switch tube of the lagging bridge arm can be realized under different phase shift angles. ZVS. As shown in Fig.
  • the leading or lagging bridge arm impedance adjustment circuit includes two controllable inductance branches and a fixed inductance branch, wherein the fixed inductance branch does not need to exist in both the leading and lagging bridge arm impedance adjustment circuits.
  • each inductor branch of the leading or lagging bridge arm impedance adjusting circuits 503 and 504 may be connected in parallel.
  • Each inductor branch is not limited to one inductor L, and multiple inductors can be connected in parallel or in series.
  • the size of the inductance on each branch can be the same or different, and the presented inductance values are richer, and the matching of the corresponding shift angle is more accurate.
  • the at least one inductor branch of the wireless charging and transmitting device provided in the embodiment of the present application further includes a first diode and a second diode, wherein the anode of the first diode is connected to the common terminal of the inductor and the switch in the inductor branch ,
  • the cathode of the first diode is connected to the positive DC bus at the output of the DC power supply;
  • the cathode of the second diode is connected to the common terminal of the inductor and the switch in the inductor branch, and the anode of the second diode is connected to the negative DC at the output of the DC power supply
  • the bus bar, the first diode and the second diode form a diode clamp circuit, which will be described in detail below with reference to the drawings.
  • Fig. 6a is a circuit diagram in which the inductance branches of the leading and lagging bridge arm impedance adjustment circuits each include a controllable inductance branch and a diode clamp circuit exists on the controllable inductance branch.
  • inverter circuit 201 the transmitting coil 202, the DC power supply 205, the compensation circuit 206, and the controller (not shown in FIG. 6a) can refer to the first embodiment of the device, which will not be repeated here.
  • the leading arm impedance adjustment circuit 603 includes a controllable inductance branch.
  • the controllable inductance branch includes a series-connected inductor L1a and a switch K1a.
  • the controllable inductance branch also includes a first diode D1a and a second diode D2a.
  • the cathode of the first diode D1a is connected to the positive DC bus of the DC power supply 205
  • the cathode of the second diode D2a is connected to the inductor L1a and the switch
  • the common terminal of K1a and the anode of the second diode D2a are connected to the negative DC bus of the DC power supply 205.
  • the controller controls the switch K1a from closed to open, the current inductor current is positive, and when the switch K1a is located on the right side of the inductor L1a, the first diode D1a is turned off, and the second diode D2a is turned on.
  • the second diode D2a provides a freewheeling path for the inductor L1a; when the switch K1a is on the left side of the inductor L1a, the first diode D1a is turned on, the second diode D2a is turned off, and the second diode is turned on D2a provides a freewheeling path for the inductor L1a.
  • the diode clamp circuit can also stabilize the voltage U C of the common terminal C of the inductor L1a and the switch K1a within a safe range.
  • the first diode D1a and the second diode D2a as silicon tubes as an example.
  • the conduction voltage drop of the tube is 0.7V
  • the positive DC bus voltage of the DC power supply 205 is U E
  • the negative DC bus voltage of the DC power supply 205 is U D.
  • the lagging arm impedance adjustment circuit may include at least one controllable inductance branch and also includes a first diode and a second diode, wherein the anode of the first diode is connected to the inductor and the switch in the inductance branch.
  • the cathode of the first diode is connected to the positive DC bus of the output terminal of the DC power supply; the cathode of the second diode is connected to the common terminal of the inductor and the switch in the inductor branch, and the anode of the second diode is connected to the output terminal of the DC power supply.
  • the negative DC bus, the first diode and the second diode form a diode clamp circuit, as shown in Figure 6a.
  • the above-mentioned diode clamping circuit may also be added to at least one of the controllable inductance branches, so that when each includes the above-mentioned diode clamp When the switch of the inductance branch of the bit circuit is turned off, it can provide a freewheeling path for the inductance on the controllable inductance branch, and it can also limit the voltage peak value of each controllable inductance branch to a safe range, improving the circuit Reliability and stability.
  • the inductance branch of the impedance adjusting circuit includes at least two controllable inductance branches: a first controllable inductance branch and a second controllable inductance branch as an example.
  • FIG. 6b is a circuit diagram when the leading or lagging arm impedance adjustment circuit includes two controllable inductance branches and a diode clamp circuit exists on the first inductance branch.
  • inverter circuit 201 the transmitting coil 202, the DC power supply 205, the compensation circuit 206, and the controller (not shown in FIG. 6b) can be found in the first embodiment of the device, which will not be repeated here.
  • the leading or lagging bridge arm impedance adjustment circuit 603 or 604 includes two controllable inductance branches, where the first controllable inductance branch includes a first inductor L1 and a first switch K1 connected in series, and the first end is connected to the leading or lagging bridge arm.
  • the middle point A or B is connected, the second end of the first controllable inductance branch is connected to the output terminal M of the DC power supply 205, and further includes a first diode D3 and a second diode D4, wherein the first diode
  • the anode of the tube D3 is connected to the common terminal of the first inductor L1 and the first switch K1 in the first inductance branch, the cathode of the first diode D3 is connected to the positive DC bus E of the DC power supply 205, and the cathode of the second diode D4
  • the common terminal of the first inductor L1 and the first switch K1 in the first inductor branch is connected, and the anode of the second diode D4 is connected to the negative DC bus D of the DC power supply 205.
  • the second inductor branch includes a second inductor L2 and a second switch K2 connected in series.
  • the diode clamping circuit includes the first diode D3 and the second diode D4, please refer to the related introduction of the corresponding part of the circuit shown in FIG. 6a, which will not be repeated here.
  • Fig. 6c is a circuit diagram of the leading or lagging bridge arm impedance adjustment circuit including two controllable inductance branches and a diode clamp circuit on the second controllable inductance branch.
  • the second controllable inductance branch of the circuit shown in Fig. 6c includes a first diode D5 and a second diode D6, wherein the first diode D5
  • the anode of the second inductance branch is connected to the common terminal of the second inductor L2 and the second switch K2
  • the cathode of the first diode D5 is connected to the positive DC bus E of the DC power supply 205
  • the cathode of the second diode D6 is connected to the first
  • the common terminal of the second inductor L2 and the second switch K2 in the two controllable inductor branches, and the anode of the second diode D6 is connected to the negative DC bus D of the DC power supply 205.
  • the first end of the second controllable inductance branch is connected to the leading or lagging bridge arm midpoint A or B, the second end is connected to the output terminal M of the DC power supply 205, and the second controllable inductance branch is connected to the first controllable
  • the inductance branches are connected in parallel.
  • the diode clamping circuit includes the first diode D5 and the second diode D6, please refer to the related introduction of the corresponding part of the circuit shown in FIG. 6a, which will not be repeated here.
  • FIG. 6d is a circuit diagram of the leading or lagging arm impedance adjustment circuit including two controllable inductance branches and each controllable inductance branch has a diode clamp circuit.
  • the first controllable inductance branch of the circuit shown in Figure 6d includes a first inductor L1 and a first switch K1 connected in series, and also includes a first diode D3 and a second diode D4, wherein the first diode D3
  • the anode is connected to the common terminal of the first inductor L1 and the first switch K1
  • the cathode of the first diode D3 is connected to the positive DC bus E of the DC power supply 205
  • the cathode of the second diode D4 is connected to the first inductor L1 and the first switch
  • the common terminal of K1, the anode of the second diode D4 is connected to the negative DC bus D of the DC power supply 205.
  • the second controllable inductance branch includes a second inductor L2 and a second switch K2 connected in series, and also includes a first diode D5 and a second diode D6, wherein the anode of the first diode D5 is connected to the second inductor L2 And the common terminal of the second switch K2, the cathode of the first diode D5 is connected to the positive DC bus E of the DC power supply 205, the cathode of the second diode D6 is connected to the common terminal of the second inductor L2 and the second switch K2, The anodes of the two diodes D6 are connected to the negative DC bus D of the DC power supply 205.
  • the first end of the first controllable inductance branch is connected to the leading or lagging bridge arm midpoint A or B, the second end is connected to the output terminal M of the DC power supply 205, and the second controllable inductance branch is connected to the first controllable
  • the inductance branches are connected in parallel.
  • the diode clamping circuit formed by the first diode D3 and the second diode D4 acts on the first inductive branch
  • the diode clamping circuit formed by the first diode D5 and the second diode D6 acts on the second
  • At least one controllable inductance branch in the leading or lagging bridge arm impedance adjustment circuit includes a first diode and a second diode, and two diodes are used to form a diode clamping circuit,
  • the switch of the inductance branch with the diode clamp circuit is turned off, it can provide a freewheeling path for the inductance in the controllable inductance branch, and can maintain the voltage stability of the common terminal of the inductance and the switch in the controllable inductance branch In the safety range, it has the function of protecting the circuit.
  • the leading or lagging bridge arm impedance adjustment circuit of this embodiment may also include at least one fixed inductance branch, as shown in FIG.
  • the figure is a circuit diagram in which the leading or lagging arm impedance adjustment circuit includes two controllable inductance branches and a fixed inductance branch, and each controllable inductance branch has a diode clamp circuit.
  • the inductance branch of the leading or lagging bridge arm impedance adjustment circuit includes at least two controllable inductance branches: the first controllable inductance branch and the second controllable inductance branch are connected in parallel
  • the first controllable inductance branch includes a first inductance and a first switch in series
  • the second controllable inductance branch includes a second inductance and a second switch in series.
  • This embodiment specifically introduces the connection relationship between the impedance adjustment circuit and the output end of the DC power supply, that is, the connection relationship between the second end of the leading and lagging arm impedance adjustment circuit and the output end of the DC power supply.
  • FIG. 7a is a circuit diagram when the second end of the lead and lag arm impedance adjustment circuit is connected to the midpoint of the DC bus of the DC power supply.
  • inverter circuit 201 the transmitting coil 202, the DC power supply 205, the compensation circuit 206, and the controller (not shown in FIG. 7a) can refer to the first embodiment of the device, which will not be repeated here.
  • the leading and lagging bridge arm impedance adjustment circuits 703 and 704 each include a first controllable inductance branch and a second controllable inductance branch.
  • the two controllable inductance branches are connected in parallel to form a leading and lagging bridge arm impedance adjustment circuit.
  • the second end of the bridge arm impedance adjustment circuit is directly connected to the midpoint of the DC bus at the output end of the DC power supply.
  • the impedance adjusting circuit may also include a first DC blocking capacitor, and the second ends of the leading and lagging bridge arm impedance adjusting circuits are respectively connected to the DC bus midpoint of the output terminal of the power supply through the first DC blocking capacitor, see FIG. 7b.
  • the phase of the current in the leading and lagging bridge arms needs to lag the phase of the output voltage of the inverter circuit 201, using The inductance branch injects appropriate inductive currents into the leading and lagging bridge arms, so that the phase of the current in the leading and lagging bridge arms is kept lagging the phase of the output voltage of the leading and lagging bridge arms of the inverter circuit 201. But at the same time, the direct current component in the inductance branch will also be injected into the leading and lagging bridge arms.
  • the wireless charging transmitter provided by the embodiment of the application introduces the first DC blocking capacitor in the leading and lagging bridge arm impedance adjustment circuit, and connects the second end of the leading and lagging bridge arm impedance adjusting circuit through the first DC blocking capacitor.
  • the midpoint of the DC bus bar is used to filter out the direct current components in the impedance adjustment circuit of the leading and lagging bridge arms, reducing the increase in the effective value of the current in the leading and lagging bridge arms, thereby reducing the controllable switching tube in the leading and lagging bridge arms. Conduction loss and switching loss.
  • the second end of the leading and lagging bridge arm impedance adjustment circuit can also be connected to the positive DC bus at the output end of the DC power supply.
  • the impedance adjustment circuit also includes a second DC blocking capacitor, and the second ends of the impedance adjustment circuit pass through the second DC blocking capacitor respectively.
  • the capacitor is connected to the positive DC bus at the output end of the power supply, see Figure 7c.
  • the wireless charging transmitter provided by the embodiment of the present application adds a second DC blocking capacitor to the impedance adjustment circuit, and connects the second end of the impedance adjustment circuit to the positive DC bus of the output terminal of the DC power supply through the second DC blocking capacitor, which can filter out
  • the direct current component in the impedance adjustment circuit reduces the increase in the effective value of the current in the leading and lagging bridge arms, and reduces the conduction loss and switching loss of the controllable switch in the leading and lagging bridge arms.
  • the second end of the impedance adjustment circuit can also be connected to the negative DC bus of the output end of the DC power supply.
  • the impedance adjustment circuit also includes a third blocking capacitor. The second end of the impedance adjustment circuit is connected to the output terminal of the power supply through the third blocking capacitor. Negative DC bus, thereby filtering out the DC component in the regulating branch, reducing the increase in the effective value of the current in the leading arm, and reducing the conduction loss and switching loss of the controllable switch in the leading arm. See Figure 7d.
  • the impedance adjustment circuit includes a second DC blocking capacitor and a third DC blocking capacitor.
  • the second end of the impedance adjustment circuit is respectively connected to the positive DC bus of the power output terminal through the second DC blocking capacitor, and the second end of the impedance adjustment circuit is also The negative DC bus at the output end of the power supply is connected through the third DC blocking capacitor respectively, so that the impedance adjustment circuit can be connected to the DC power supply without a DC bus, and it can also filter out the DC components in the impedance adjustment circuit and reduce the lead and lag in the bridge arm.
  • the increase in the effective value of the current reduces the conduction loss and switching loss of the controllable switch in the leading and lagging bridge arms. See Figure 7e.
  • the impedance adjusting circuit also includes a first blocking capacitor, a second blocking capacitor, and a third blocking capacitor.
  • the second end of the impedance adjusting circuit is connected to the second blocking capacitor and the third blocking capacitor through the first blocking capacitor.
  • the first end of the capacitor is connected, the second end of the second DC blocking capacitor is connected to the positive DC bus of the power supply output end, and the second end of the third DC blocking capacitor is connected to the negative DC bus of the power output end, which can filter out the regulation branch.
  • the direct current component also reduces the equivalent series resistance loss, reduces the increase in the effective value of the current in the lead and lag arms, and reduces the conduction loss and switching loss of the controllable switch in the lead and lag arms. See Figure 7f.
  • the impedance adjustment circuit is connected to the power supply through at least one DC blocking capacitor, that is, the second ends of the leading and lagging bridge arm impedance adjustment circuits are respectively connected to the power supply through at least one DC blocking capacitor.
  • leading bridge arm impedance adjusting circuit may include at least one DC blocking capacitor, and the second end of the leading bridge arm impedance adjusting circuit is connected to the power supply through at least one DC blocking capacitor.
  • the specific connection method is shown in Figure 7g. -7i shown.
  • the lagging bridge arm impedance adjustment circuit may include at least one DC blocking capacitor, and the second end of the lagging bridge arm impedance adjustment circuit is connected to the power supply through at least one DC blocking capacitor.
  • the specific connection mode is shown in Figure 7g. -7i shown.
  • leading and lagging bridge arm impedance adjustment circuits may each include at least one DC blocking capacitor, and the second end of the leading and lagging bridge arm impedance adjusting circuit is respectively connected to the power supply through at least one DC blocking capacitor.
  • the connection method is shown in Figure 7g-7i.
  • first diode and a second diode can also be added to at least one inductance branch to form a diode clamping circuit.
  • first diode and a second diode can also be added to at least one inductance branch to form a diode clamping circuit.
  • leading or lagging bridge arm impedance adjustment circuit in this embodiment includes at least one controllable inductance branch, and is not limited to two controllable inductance branches, and there may be more than or equal to one controllable inductance branch.
  • leading or lagging bridge arm impedance adjustment circuit includes at least one fixed inductance branch.
  • the impedance adjusting circuit includes the following two inductance branches: the first inductance branch and the second inductance branch as an example to specifically introduce the method of determining the inductance of the inductance in the inductance branch. It is understandable that this method It can be applied to the circuit scenario when the impedance adjustment circuit includes more parallel inductance branches.
  • FIG. 4 is a circuit diagram of a wireless charging transmitter.
  • inverter circuit 201 the transmitting coil 202, the impedance adjusting circuit 803, the DC power supply 205, and the controller (not shown in FIG. 4) can be found in the relevant introduction of the corresponding part of the circuit shown in FIG. 4, which will not be repeated here. .
  • the following is an analysis of the turn-off process of the leading bridge arm S4.
  • the method of analyzing the turn-off process of the leading bridge arm S3 and the lagging bridge arm S1-S2 is similar, so we will not repeat it.
  • the inductor current remains constant during the switching process and the current flowing out of the leading bridge arm remains constant during the switching process.
  • the junction capacitance C oss of the controllable switch, the bus voltage U bus , the leading bridge arm The dead time ⁇ t dead can be obtained when the controllable switch tube of the leading bridge arm realizes ZVS.
  • the S4 output current of the inverter circuit 201 is turned off.
  • the leading bridge arm can also achieve ZVS.
  • I Lmax 34.133A
  • the leading bridge arm can also achieve ZVS.
  • I Lmax 35A as an example to illustrate the inductance determination process.
  • the switching period T SW of the switching tube on the inverter circuit 201, the bus voltage U bus , the peak current that the inductance branch needs to inject into the leading arm is I Lmax and the maximum inductance L MAX of the regulating branch is related to the following, the leading arm voltage
  • the AC component of the voltage applied to the inductor is a square wave voltage with a switching period T SW and an amplitude of U bus /2.
  • the waveform of the inductor current is a positive and negative symmetrical triangular wave. Therefore, according to the relationship between the inductor current and voltage, The formula (6) can be obtained:
  • L MAX is the inductance value of the first inductance L1a and the second inductance L2a in parallel.
  • the inductances of the first inductor L1a and the second inductor L2a can be both 53.8 ⁇ H.
  • the peak current injected into the leading bridge arm by the adjusting branch is 17.5A.
  • the peak current injected into the leading bridge arm by the regulating branch is 35A.
  • the adjustment branch only fixedly includes the above two inductive branches, although the controllable switch tube of the leading bridge arm can achieve ZVS, it will cause the effective value of the inductive current injected into the leading bridge arm by the adjustment branch to be too large, thereby increasing The switching loss of the controllable switch on the leading bridge arm is reduced.
  • the number of parallel inductive branches in the branch can be adjusted, and the amount of current injected into the leading arm can be controlled by controlling the number of inductive branches that are turned on, so that the leading arm impedance adjustment branch can inject into the leading arm of the leading arm.
  • the inductor current matches the actual requirement.
  • the embodiment of the present application also provides a method for controlling the wireless charging and transmitting device, which is applied to the wireless charging and transmitting device described in the above embodiments, and the wireless charging and transmitting device includes: an inverter circuit, a transmitting coil, an impedance adjusting circuit, and a controller.
  • the inverter circuit is used to invert the direct current output by the direct current power supply into alternating current.
  • the inverter circuit includes a leading bridge arm and a lagging bridge arm, wherein the voltage phase of the leading bridge arm leads the lagging bridge in the same period The voltage phase of the arm.
  • the transmitting coil is used to receive alternating current and generate an alternating magnetic field.
  • the leading and lagging bridge arm impedance adjustment circuits respectively include at least one controllable inductance branch or fixed inductance branch.
  • Each controllable inductance branch includes at least one inductance and a switch.
  • the fixed inductance branch includes at least one inductance.
  • the inductance branches are connected in parallel or in series, the fixed inductance branch is in parallel with the controllable inductance branch, the second end of the lead and lag arm impedance adjustment circuit is connected to the output port of the DC power supply, and the second end of the lead and lag arm impedance adjustment circuit The terminal is connected to the midpoint of the lagging bridge arm.
  • wireless charging transmitting device please refer to the above-mentioned embodiment of the wireless charging transmitting device, which will not be repeated here.
  • control method of the wireless charging transmitter includes the following steps:
  • the method for controlling the wireless charging transmitter includes obtaining the current flowing into the compensation circuit of the wireless charging transmitter, specifically:
  • the turn-off time is the time corresponding to the controllable switching tube from turning on to turning off;
  • the turning-on time is the time corresponding to the turning off of the controllable switching tube to turning on.
  • the actual turn-off time and the actual turn-on time of the switch tube will be one delay time longer than the signal of the turn-off time and the turn-on time sent by the controller. Therefore, in the embodiment of the present application, the period from the off time to the on time is the longest period from the off time to the on time including the signal delay time.
  • the on or off of the switch in the inductance branch of the leading arm impedance adjustment circuit is controlled.
  • the difference between the current flowing into the compensation circuit by the controllable switch tube of the leading bridge arm and the preset current is obtained, and the switch in the controllable inductance branch is controlled to be turned on and off according to the difference.
  • control method of the wireless charging transmitter provided in the embodiment of the present application is also applicable to the hysteresis bridge arm, which will not be repeated here.
  • the controller is used to control the turn-on or turn-off of the inductor branch switch in the lead and lag arm impedance adjustment circuit to change the current flowing out of the lead and lag arm, by controlling the lead
  • the number of inductance branches that are connected controls the magnitude of the current injected into the leading and lagging bridge arms, so that the controllable switch tubes of the leading and lagging bridge arms realize ZVS.
  • the controller controls the inductance branch to connect to the leading or lagging bridge arm.
  • the controller can control the on and off of the switches in each controllable inductance branch to realize the leading and lagging bridge arm impedance adjustment circuit
  • the size of the inductance presented is different, and the inductance of the inductance branch is different, and the inductive current injected into the leading and lagging bridge arms is different.
  • the process of the controller switching the inductance branch does not affect the power transmission of the wireless charging transmitter, which improves the stability and reliability of the wireless charging transmitter.
  • an embodiment of the present application also provides a wireless charging system, which is described in detail below with reference to the accompanying drawings.
  • FIG. 9 is a schematic diagram of a wireless charging system provided by an embodiment of the application.
  • the system includes: a wireless charging receiving device 200 and a wireless charging receiving device 2000.
  • the wireless charging and transmitting device 200 may be any one of the above-mentioned device embodiments.
  • the wireless charging and transmitting device 200 includes at least: an inverter circuit 201, a transmitting coil 202, an impedance adjusting circuit 203, and a controller 204.
  • the wireless charging receiving device 2000 is configured to receive the alternating magnetic field emitted by the wireless charging transmitting device, and convert the alternating magnetic field into direct current to provide electrical equipment, which specifically includes: a coil 2001, a rectifier 2002, and electrical equipment 2003.
  • the inverter circuit 201 inverts the DC power output by the DC power supply 205 into AC power.
  • the inverter circuit 201 includes a leading bridge arm and a lagging bridge arm. The voltage phase of the leading bridge arm is ahead of the voltage phase of the lagging bridge arm.
  • the transmitting coil 202 transmits alternating current in the form of an alternating magnetic field.
  • the impedance adjusting circuit 203 includes a leading arm impedance adjusting circuit and a lagging arm impedance adjusting circuit.
  • the leading arm impedance adjusting circuit and the lagging arm impedance adjusting circuit respectively include at least one inductance branch, wherein the inductive branch includes a controllable inductor.
  • the inductance branches of the lagging bridge arm impedance adjusting circuit are also connected in parallel or series with each other.
  • the first end of the leading and lagging bridge arm impedance adjusting circuit is connected to the output port of the DC power supply 205, the leading and lagging bridges.
  • the second end of the arm impedance adjusting circuit is respectively connected to the midpoints of the leading and lagging bridge arms.
  • the controller 204 can control the on or off of the switches in the inductance branch to change the current flowing out of the leading and lagging bridge arms, so that the controllable switches of the leading and lagging bridge arms realize ZVS.
  • the receiving coil 2001 receives the electromagnetic energy emitted by the transmitting coil 202 in the form of an alternating magnetic field.
  • the rectifier 2002 rectifies the AC power output by the receiving coil 2001 into DC power and outputs it to the electrical equipment.
  • the wireless charging transmitter of the wireless charging system adds a leading and lagging bridge arm impedance adjustment circuit and a controller, wherein the leading and lagging bridge arm impedance adjustment circuits respectively include at least one controllable inductor branch and at least one fixed inductor Branch, each controllable inductance branch includes at least one inductor and one switch, each fixed inductance branch includes at least one inductance without switch control, all controllable inductance branches are connected in parallel or in series with each other, the fixed inductor After the branch is connected in parallel with the controllable inductance branch, the impedance adjustment circuit of the leading and lagging bridge arms is formed.
  • the leading and lagging bridge arm impedance adjustment circuits respectively include at least one controllable inductor branch and at least one fixed inductor Branch
  • each controllable inductance branch includes at least one inductor and one switch
  • each fixed inductance branch includes at least one inductance without switch control
  • all controllable inductance branches are connected in parallel or in
  • the first end of the impedance adjusting circuit of the leading and lagging bridge arms is connected to the output port of the DC power supply, the leading and lagging bridge arms
  • the second end of the impedance adjusting circuit is respectively connected to the midpoints of the leading and lagging bridge arms, and when needed, inductive current can be injected into the leading and lagging bridge arms to increase the inductive current components of the leading and lagging bridge arms.
  • the inverter circuit itself can realize the ZVS of the controllable switching tube.
  • the wireless charging transmitter controls the number of inductive branches connected to the leading or lagging bridge arm by injecting inductive current into the leading or lagging bridge arm so that the lead and lagging bridge arm of the wireless charging transmitter can be switched on and off. Pipe to achieve ZVS.
  • the turn-off time is the time corresponding to the controllable switch from turning on to the turn-off;
  • the turning-on time is the time corresponding to the controllable switch from turning off to being turned on.
  • the actual turn-off time and the actual turn-on time of the switch tube will be one delay time longer than the signal of the turn-off time and the turn-on time sent by the controller. Therefore, in the embodiment of the present application, the period from the off time to the on time is the longest period from the off time to the on time including the signal delay time.
  • the controller can control the inductance branch to be connected when the switch of the inductance branch is closed according to the difference between the current flowing into the compensation circuit and the preset current Leading or lagging the midpoint of the bridge arm, and then controlling the injection of inductive current to the leading or lagging bridge arm.
  • the controller can according to the difference between the sum of the current flowing into the compensation circuit and the current of the fixed inductance branch and the preset current, When the switch controlling the controllable inductance branch is closed, the controllable inductance branch is connected to the midpoint of the leading or lagging bridge arm, thereby controlling the injection of inductive current into the leading or lagging bridge arm.
  • the inductance branch includes a controllable inductance branch and a fixed inductance branch, and the controller is always out according to the viewpoint of the controllable switch of the leading and lagging bridge arms.
  • the currents of the leading and lagging bridge arms and the current number of closed inductance branches of the leading and lagging bridge arm impedance adjustment circuit and the number of fixed inductance branches are fixed to obtain the current leading and lagging bridge arm impedance adjustment circuit inductance branches.
  • the different on-off combinations of the switches in each inductance branch can be controlled to realize the size of the inductance presented by the impedance adjustment circuit.
  • the inductance of the impedance adjustment circuit is different, then it will lead or lag
  • the magnitude of the inductive current injected by the bridge arm is different.
  • the controller can control the on and off of the switches in each inductance branch to achieve the inductance of the impedance adjustment circuit. In this way, the size of the inductive current injected into the leading and lagging bridge arms is controlled, so that the injected inductor current can just make up the difference, avoiding too much inductance connected and increasing power consumption.
  • the process of the controller switching the inductive branch does not affect the power transmission of the wireless charging transmitter, and the stability and reliability of the wireless charging transmitter are improved.
  • the impedance adjustment circuit may also include at least one DC blocking capacitor connected to the output terminal of the power supply, which can filter out the DC component in the adjustment branch, reduce the loss of equivalent series resistance, and reduce the current in the lagging bridge arm.
  • the increase in the effective value reduces the conduction loss and switching loss of the controllable switch in the leading and lagging bridge arms.
  • At least one controllable inductance branch includes a first diode and a second diode to form a diode clamping circuit.
  • an embodiment of the present application also provides an electrical device, which is described in detail below with reference to the accompanying drawings.
  • FIG. 10 is a schematic diagram of an electrical equipment provided by an embodiment of the application.
  • the electrical equipment 2100 includes a power consumption element 2101, a battery 2102, and a wireless charging receiving device 2000.
  • the wireless charging receiving device 2000 is used to receive the alternating magnetic field emitted by the wireless charging transmitting device 200, and is also used to convert the alternating magnetic field into direct current to charge the battery 2102.
  • the battery 2102 is used to supply power to the power consumption element 2101.
  • the electrical equipment may be an electric vehicle as shown in Figure 2a.
  • the electrical equipment uses the wireless charging transmitter provided in this application for wireless charging, because the wireless charging transmitter can achieve ZVS under different currents flowing into the compensation circuit, and at the same time
  • the inductive current injected into the lead or lagging bridge arm can be adjusted online (charged) to adapt to different coupling coefficients, output voltages, output currents, and target power conditions, avoiding interruption of the power transmission of the wireless charging transmitter when adjusting the injected inductive current, and improving usage The stability and safety of electric equipment during wireless charging.
  • At least one (item) refers to one or more, and “multiple” refers to two or more.
  • “And/or” is used to describe the association relationship of associated objects, indicating that there can be three types of relationships, for example, “A and/or B” can mean: only A, only B, and both A and B , Where A and B can be singular or plural.
  • the character “/” generally indicates that the associated objects are in an “or” relationship.
  • the following at least one item (a)” or similar expressions refers to any combination of these items, including any combination of a single item (a) or plural items (a).
  • At least one (a) of a, b or c can mean: a, b, c, "a and b", “a and c", “b and c", or "a and b and c" ", where a, b, and c can be single or multiple.

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  • Engineering & Computer Science (AREA)
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  • Computer Networks & Wireless Communication (AREA)
  • Charge And Discharge Circuits For Batteries Or The Like (AREA)

Abstract

一种无线充电发射装置、发射方法及无线充电系统。发射装置包括：补偿电路（206）、逆变电路（201）、发射线圈（202）、阻抗调节电路（203）和控制器（204）。所述阻抗调节电路（203）包括超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路分别包括电感支路，所述电感支路包括至少一个可控电感支路，每个所述可控电感支路包括至少一个电感和至少一个开关。通过控制器（204）控制可控电感支路开关的导通或关断，对阻抗调节电路（203）注入超前桥臂和滞后桥臂的感性电流的大小进行调节，以使超前桥臂和滞后桥臂的可控开关管实现零电压开关，提高无线充电系统的效率和互操作性。

Description

一种无线充电发射装置，发射方法及无线充电系统 技术领域
本发明涉及电力电子技术领域，尤其涉及一种无线充电发射装置、发射方法及无线充电系统。
背景技术
随着现代社会能源短缺和环境污染问题的加剧，电动汽车作为新能源汽车受到了各界的广泛关注。电动汽车是以车载动力电池组为能源来驱动车辆行驶。但现有电动汽车大多受到动力电池组容量的限制，行驶里程较短，同时电动汽车的动力电池组充电时间较长，而且充电站较少，因此导致电动汽车还没有大范围应用和普及。
电动汽车的充电方式目前包括接触式充电和无线充电，而无线充电方式由于使用方便，无火花以及触电危险，因此无线充电成为未来电动汽车的发展方向。
下面结合附图1介绍无线充电系统的工作原理。
参见图1，该图为一种无线充电系统的示意图。
无线充电系统包括无线充电发射装置和无线充电接收装置。
其中，无线充电发射装置位于发射端，无线充电接收装置位于接收端。
发射端包括：逆变器H1、发射端补偿电路100和发射线圈Ct；
逆变器H1包括可控开关管S1-S4，逆变器H1用于将直流电源输出的直流电逆变为交流电。其中S1，S2为滞后桥臂，S3，S4为超前桥臂，其中同一个周期内超前桥臂的电压相位超前于滞后桥臂的电压相位。
发射线圈Ct，用于将逆变器H1输出的交流电以交变磁场的形式进行发射。
接收端包括：接收线圈Cr、接收端补偿电路200和整流器H2。
整流器H2包括可控开关管Q1-Q4。
接收线圈Cr，用于以交变磁场的形式接收发射线圈Ct发射的电磁能量。
整流器H2，用于将接收线圈Cr输出的交流电整流为直流电输出给负载。
其中，接收端的控制器300与发射端的控制器400进行无线通讯。
由于不同的无线充电标准，不同的车型等，导致无线充电系统的接收端所反射到发射端的反射阻抗有可能为阻容性，进而导致其等效输出阻抗呈现一定的阻容性。
目前，为了提高无线充电的互操作性和充电效率，希望H1中的可控开关管实现零电压开关(ZVS，Zero Voltage Switching)以此来降低可控开关管工作时的功耗。具体可以通过调节H1的输入电压使H1在所有工况下实现ZVS。但是，调节H1的输入电压需要在H1的输入端额外增加直流变换电路，这样将会增加无线充电发射装置的体积和成本。另外，通过调节H1移相也可以实现H1的输出电压的调节。但是，不能保证在H1的各种输出电压下可控开关管都可以实现ZVS，而可控开关管一旦失去ZVS就会导致H1的开关损耗比较大，甚至损坏。
发明内容
为了解决现有技术中存在的以上技术问题，本申请提供了一种无线充电发射装置， 发射方法即无线充电系统。通过控制器控制可控电感支路开关的导通或关断，对阻抗调节电路流入超前桥臂和滞后桥臂的感性电流的大小进行调节，以使超前桥臂和滞后桥臂的可控开关管实现零电压开关，降低可控开关管损耗，提高无线充电的效率的同时提高其互操作性，即兼容性。
以下从多个方面介绍本申请，容易理解的是，该以下多个方面的实现方式可互相参考。
第一方面，本申请实施例提供一种无线充电发射装置，包括：逆变电路，补偿电路，发射线圈，阻抗调节电路，和控制器。所述逆变电路，用于将输入直流电转变为交流电。所述逆变电路包括超前桥臂和滞后桥臂，其中同一个周期内所述超前桥臂的电压相位超前于所述滞后桥臂的电压相位，所述超前桥臂和所述滞后桥臂分别包括可控开关管。所述补偿电路，用于将所述交流电进行补偿后发送给所述发射线圈。所述发射线圈，用于将所述补偿电路输出的交流电通过交变磁场形式进行发射。所述阻抗调节电路包括超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路。所述超前桥臂阻抗调节电路第一端连接所述超前桥臂的可控开关管。所述滞后桥臂阻抗调节电路第一端连接所述滞后桥臂的可控开关管。所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路分别包括电感支路，所述电感支路包括至少一个可控电感支路，每个所述可控电感支路包括至少一个电感和至少一个开关。所述控制器，通过控制所述超前桥臂阻抗调节电路中所述可控电感支路的开关的导通或关断，对流入所述超前桥臂的感性电流的大小进行调节，使所述超前桥臂的可控开关管实现零电压开关；通过控制所述滞后桥臂阻抗调节电路中所述可控电感支路的开关的导通或关断，对流入滞后桥臂的感性电流的大小进行调节，使所述滞后桥臂的可控开关管实现零电压开关。可见，通过对超前和滞后桥臂阻抗调节电路中电感支路的电流大小的调节，确保超前桥臂和滞后桥臂的可控开关管可以实现零电压开关，不但降低了可控开关管的损耗，而且提高了无线充电发射装置的充电的效率及兼容性。
根据第一方面，在一种可能的实现方式中，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的电感支路还分别包括至少一个固定电感支路，所述固定电感支路包括至少一个电感。固定电感支路不受开关的控制，可以直接为超前和滞后桥臂注入感性电流，因此，通过对可控电感支路和固定电感支路的合理选择和搭配，可以在可控开关管实现零电压开关的同时能够为注入超前和滞后桥臂的感性电流构建合理的电流梯度。
根据第一方面，在一种可能的实现方式中，所述超前桥臂和所述滞后桥臂的可控开关管各包括两个上、下开关管，所述超前桥臂阻抗调节电路第一端连接所述超前桥臂的两个上、下开关管的中点；所述滞后桥臂阻抗调节电路的第一端连接所述滞后桥臂的两个上、下开关管的中点，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的第二端分别与电源的正母线、负母线或母线中点中的一个相连接。
根据第一方面，在一种可能的实现方式中，所述阻抗调节电路还包括至少一个隔直电容，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的第二端分别通过所述隔直电容与电源的正母线、负母线或母线中点中的一个相连接。所述隔直电容可以滤除阻抗调节电路中的直流电成分，减小超前和滞后桥臂中的电流有效值增加量，进而降低超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。
根据第一方面，在一种可能的实现方式中，所述阻抗调节电路还包括至少一个第一隔直电容和至少一个第二隔直电容，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的第二端分别通过所述至少一个第一隔直电容与电源的正母线相连接，通过所述至少一个第二隔直电容与电源的负母线相连接。所述第一，第二隔直电容可以滤除阻抗 调节电路中的直流电成分，减小超前和滞后桥臂中的电流有效值增加量，进而降低超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。
根据第一方面，在一种可能的实现方式中，所述阻抗调节电路还包括至少一个第一隔直电容、至少一个第二隔直电容和至少一个第三隔直电容，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的第二端分别与所述至少一个第一隔直电容的第一端相连，所述至少一个第一隔直电容的第二端通过所述至少一个第二隔直电容与电源的正母线相连接，所述至少一个第一隔直电容的第二端通过所述至少一个第三隔直电容与电源的负母线相连接。所述第一，第二，第三隔直电容可以滤除阻抗调节电路中的直流电成分，减小超前和滞后桥臂中的电流有效值增加量，进而降低超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。
根据第一方面，在一种可能的实现方式中，所述超前桥臂阻抗调节电路还包括至少一个隔直电容，所述超前桥臂阻抗调节电路的电感支路通过所述至少一个隔直电容与电源的正母线、负母线或母线中点中的一个相连接。所述隔直电容可以滤除阻抗调节电路中的直流电成分，减小超前和滞后桥臂中的电流有效值增加量，进而降低超前桥臂中可控开关管的导通损耗以及开关损耗。
根据第一方面，在一种可能的实现方式中，所述超前桥臂阻抗调节电路还包括至少一个第一隔直电容和至少一个第二隔直电容，所述超前桥臂阻抗调节电路的电感支路通过所述至少一个第一隔直电容与电源的正母线相连接，通过所述至少一个第二隔直电容与电源的负母线相连接。所述第一，第二隔直电容可以滤除阻抗调节电路中的直流电成分，减小超前和滞后桥臂中的电流有效值增加量，进而降低超前桥臂中可控开关管的导通损耗以及开关损耗。
根据第一方面，在一种可能的实现方式中，所述超前桥臂阻抗调节电路还包括至少一个第一隔直电容、至少一个第二隔直电容和至少一个第三隔直电容，所述超前桥臂阻抗调节电路的电感支路通过所述至少一个第一隔直电容、所述至少一个第二隔直电容与电源的正母线相连接，所述超前桥臂阻抗调节电路的电感支路通过所述至少一个第一隔直电容、所述至少一个第三隔直电容与电源的负母线相连接。所述第一，第二，第三隔直电容可以滤除阻抗调节电路中的直流电成分，减小超前桥臂中的电流有效值增加量，进而降低超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。
根据第一方面，在一种可能的实现方式中，所述补偿电路包括LCC，或LCL。
根据第一方面，在一种可能的实现方式中，所述超前桥臂阻抗调节电路还包括至少一个二极管箝位电路，所述超前桥臂阻抗调节电路的所述可控电感支路与所述超前桥臂阻抗调节电路的所述至少一个二极管箝位电路相连，所述超前桥臂阻抗调节电路的二极管箝位电路包括第一二极管和第二二极管，所述超前桥臂阻抗调节电路的可控电感支路中的电感和开关的连接点与所述第一二极管的阳极、所述第二二极管的阴极分别连接。利用两个二极管形成二极管箝位电路，当具有二极管箝位电路的超前桥臂阻抗调节电路的电感支路的开关断开时，能够为该超前桥臂阻抗调节电路的电感支路中的电感提供续流通路，并且能够维持该超前桥臂阻抗调节电路的电感支路中电感和开关的公共端的电压稳定在安全范围内，具有保护电路的作用。
根据第一方面，在一种可能的实现方式中，所述滞后桥臂阻抗调节电路还包括至少一个二极管箝位电路，所述滞后桥臂阻抗调节电路的所述可控电感支路与所述滞后桥臂阻抗调节电路的所述至少一个二极管箝位电路相连，所述滞后桥臂阻抗调节电路的二极 管箝位电路包括第三二极管和第四二极管，所述滞后桥臂阻抗调节电路的可控电感支路中的电感和开关的连接点与所述第三二极管的阳极、所述第四二极管的阴极分别连接。利用两个二极管形成二极管箝位电路，当具有二极管箝位电路的滞后桥臂阻抗调节电路的电感支路的开关断开时，能够为该滞后桥臂阻抗调节电路的电感支路中的电感提供续流通路，并且能够维持该滞后桥臂阻抗调节电路的电感支路中电感和开关的公共端的电压稳定在安全范围内，具有保护电路的作用。
根据第一方面，在一种可能的实现方式中，所述控制器用于获得流入所述补偿电路的电流；根据所述流入所述补偿电路的电流，控制所述无线充电发射装置的超前桥臂阻抗调节电路中可控电感支路的开关的导通或关断来改变流出所述无线充电发射装置的超前桥臂的电流，使所述超前桥臂的可控开关管实现零电压开关。以上介绍的根据补偿电路的电流直接控制电感支路通断的情况，节省了预先的仿真过程，而是控制器直接获取通过电流检测电路进行电流检测得到的补偿电路的电流，准确性更符合实际产品且更具有时效性。
根据第一方面，在一种可能的实现方式中，所述控制器用于获得流入所述补偿电路的电流与预设电流的差值，根据所述差值控制所述超前桥臂阻抗调节电路中的电感支路中开关的导通或关断。无论是否已经存在闭合的电感支路时，可以根据获取流入补偿电路的电流，将流入补偿电路的电流与预设电流做差，根据差值来控制电感支路的通断情况。
根据第一方面，在一种可能的实现方式中，所述控制器用于获得超前桥臂的可控开关管关断时刻到开通时刻期间内由所述超前桥臂可控开关管的中点流入所述补偿电路的电流。
根据第一方面，在一种可能的实现方式中，所述控制器用于根据所述超前桥臂的可控开关管关断时刻到实际开通时刻期间内流出所述超前桥臂的电流、以及所述超前桥臂阻抗调节电路电感支路的电流，获得流入所述补偿电路的电流。当已经存在闭合的电感支路时，可以通过超前桥臂的电流及超前桥臂阻抗调节电路电感支路的电流来间接获取流入补偿电路的电流。
关断时刻为可控开关管从导通到关断所对应的时刻；开通时刻为可控开关管从关断到导通所对应的时刻。其中，实际操作中，开关管实际关断时刻和实际开通时刻可能会比控制器所发出关断时刻和开通时刻的信号多一个延迟时间。因此，本申请实施例从关断时刻到开通时刻的期间为包括信号延迟时间在内的从关断时刻到开通时刻的最长期间。
以上介绍的根据补偿电路电流直接控制超前桥臂阻抗调节电路的电感支路通断的实现方式，同样也适用于根据补偿电路电流对滞后桥臂阻抗调节电路的电感支路通断进行控制。
第二方面，本申请实施例提供一种无线充电发射装置的控制方法包括：获得流入所述无线充电发射装置的补偿电路的电流；根据所述流入所述补偿电路的电流，控制所述无线充电发射装置的超前桥臂阻抗调节电路中可控电感支路的开关的导通或关断来改变流出所述无线充电发射装置的超前桥臂的电流，使所述超前桥臂的可控开关管实现零电压开关。本申请实施例中通过增加电感支路，控制器可以控制各个电感支路中开关的通断，进而调节阻抗调节电路呈现出不同的电感大小，来改变向超前桥臂注入的感性电流大小，从而使超前桥臂的可控开关管实现ZVS。由于控制器可以控制电感支路接入，也可以控制电感支路断开，即根据逆变电路实际运行时的需要来控制电感支路是否接入， 有些工况，逆变电路的超前桥臂自身可以实现ZVS，因此不需求接入任何电感支路，此时控制器可以控制所有电感支路断开，从而避免电感支路接入造成额外功耗；有些工况，为了确保与各种无线充电接收装置的互操作性的同时实现逆变电路超前桥臂可控开关管的ZVS，超前桥臂阻抗调节电路中也可直接接入固定电感支路。因此，该控制方式控制灵活，针对不同的工况，可以在需要接入时实现ZVS，在超前桥臂不需要接入电感支路时，控制可控电感支路断开，从而降低功耗。并且控制器切换电感支路的过程不影响无线充电发射装置的功率传输，提高了无线充电发射装置的稳定性与可靠性。
根据第二方面，在一种可能的实现方式中，获得流入所述补偿电路的电流与预设电流的差值，根据所述差值控制所述超前桥臂阻抗调节电路中的电感支路中开关的导通或关断。无论是否已经存在闭合的电感支路时，可以直接获取流入补偿电路的电流，将流入补偿电路的电流与预设电流做差，根据差值来控制电感支路的通断情况。
根据第二方面，在一种可能的实现方式中，获得超前桥臂的可控开关管从关断时刻到实际开通时刻期间内由所述超前桥臂可控开关管的中点流入所述补偿电路的电流。
根据第二方面，在一种可能的实现方式中，根据所述超前桥臂的可控开关管从关断时刻到开通时刻期间内流出所述超前桥臂的电流、以及所述超前桥臂阻抗调节电路电感支路的电流，获得流入所述补偿电路的电流。当已经存在闭合的电感支路时，可以通过超前桥臂的电流及超前桥臂阻抗调节电路电感支路的电流来间接获取流入补偿电路的电流。
关断时刻为可控开关管从导通到关断所对应的时刻；开通时刻为可控开关管从关断到导通所对应的时刻。其中，实际操作中，开关管实际关断时刻和实际开通时刻会比控制器所发出关断时刻和开通时刻的信号多一个延迟时间。因此，本申请实施例从关断时刻到开通时刻的期间为包括信号延迟时间在内的从关断时刻到开通时刻的最长期间。
以上介绍的根据补偿电路电流控制超前桥臂阻抗调节电路的电感支路通断的实现方式，同样也适用于根据补偿电路电流对滞后桥臂阻抗调节电路的电感支路通断进行控制。
第三方面，本申请实施例提供一种无线充电系统，包括无线充电接收装置和第一方面所述任一实现方式提供的无线充电发射装置；所述无线充电接收装置用于接收所述无线充电发射装置发射的交变磁场，并将所述交变磁场转换为直流电提供给用电设备。由于该无线充电系统包括了以上介绍的无线充电发射装置，降低了该无线充电发射装置的开关损耗，提升了无线充电发射的效率，提高了无线充电发射装置的稳定性与可靠性。
第四方面，本申请实施例提供了一种用电设备，包括耗电元件、电池以及无线充电接收装置；无线充电接收装置，用于接收以上的无线充电发射装置发射的交变磁场；无线充电接收装置用于将交变磁场转换为直流电为电池进行充电；电池用于为耗电元件供电。该用电设备可以为电动汽车，其中无线充电接收装置可以位于电动汽车上，无线充电发射装置可以位于地面。
由于该用电设备可以利用以上介绍的第一方面所述任一实现方式提供的无线充电发射装置进行充电，该用电设备在无线充电过程中的具有较高的稳定性与安全性。
附图说明
为了更清楚地说明本申请实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本申请中记载的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其它的附图。
图1为现有技术提供的一种无线充电系统的示意图；
图2a为本申请实施例提供的电动汽车无线充电系统示意图；
图2b为图2a提供的电动汽车无线充电系统的结构示意图；
图2c为本申请装置实施例一提供的一种无线充电发射装置的示意图；
图3a为本申请装置实施例二无线充电发射装置的超前和滞后桥臂阻抗调节电路分别包括一个电感支路的电路图；
图3b为图3a对应的移相角度较大时的波形关系示意图；
图3c为图3a对应的移相角度较小时的超前桥臂波形关系示意图；
图3d为图3a对应的移相角度较小时的滞后桥臂波形关系示意图；
图3e为本申请实施例二提供的超前和滞后桥臂阻抗调节电路包括一条电感支路时超前桥臂中的电流I 1a与移相角度的关系曲线图；
图4为本申请实施例三提供的超前和滞后桥臂阻抗调节电路分别包括两个电感支路的电路图；
图5a为本申请实施例四提供的超前和滞后桥臂阻抗调节电路分别包括一个可控电感支路和一个固定电感支路的电路图；
图5b为本申请实施例四提供的超前和滞后桥臂阻抗调节电路分别包括两个可控电感支路和一个固定电感支路的电路图；
图6a为本申请实施例五提供的一种超前和滞后桥臂阻抗调节电路分别包括一个可控电感支路且可控电感支路上存在二极管箝位电路的电路图；
图6b为阻抗调节电路包括两个可控电感支路且第一可控电感支路上存在二极管箝位电路的电路图；
图6c为阻抗调节电路包括两个可控电感支路且第二可控电感支路上存在二极管箝位电路的电路图；
图6d为阻抗调节电路包括两个可控电感支路且每个可控电感支路均存在二极管箝位电路的电路图；
图6e为阻抗调节电路包括两个可控电感支路和一个固定电感支路且每个电感支路均存在二极管箝位电路的电路图；
图7a为本申请实施例六提供的一种阻抗调节电路的第一端连接直流电源的直流母线中点的电路图；
图7b为本申请装置实施例六提供的另一种无线充电发射装置的电路图；
图7c为本申请装置实施例六提供的再一种无线充电发射装置的电路图；
图7d为本申请装置实施例六提供的又一种无线充电发射装置的电路图；
图7e为本申请装置实施例六提供的另一种无线充电发射装置的电路图；
图7f为本申请装置实施例六提供的又一种无线充电发射装置的电路图；
图7g为本申请装置实施例六提供的超前或滞后桥臂阻抗调节电路包括一个隔直电容的电路图；
图7h为本申请装置实施例六提供的超前或滞后桥臂阻抗调节电路包括两个隔直电容的电路图；
图7i为本申请装置实施例六提供的超前或滞后桥臂阻抗调节电路包括三个隔直电容的电路图；
图8为本申请实施例提供的一种无线充电的控制方法的流程图；
图9为本申请实施例提供的一种无线充电系统的示意图；
图10为本申请实施例提供的一种用电设备的示意图。
具体实施方式
为了使本领域技术人员更好地理解本申请实施例提供的技术方案，下面先介绍无线充电发射装置的应用场景。
参见图2a，该图为本申请实施例提供的电动汽车无线充电系统的示意图。
该无线充电系统至少可以包括：电动汽车1000和无线充电站1001。电动汽车1000可以包括无线充电接收装置1000a，无线充电站1001可以包括无线充电发射装置1001a。
目前，无线充电系统的充电过程是通过位于电动汽车1000中的无线充电接收装置1000a和位于无线充电站1001中的无线充电发射装置1001a共同工作，来进行非接触式充电。
无线充电站1001具体可以为固定无线充电站、固定无线充电停车位或无线充电道路等。无线充电发射装置1001a可以设置在地面上或者埋于地面下(图2a所示为无线充电发射装置1001a埋于地面之下时的情况)，可对位于其上方的电动汽车1000进行无线充电。
无线充电接收装置1000a可以集成在电动汽车1000的底部，当电动汽车1000进入无线充电发射装置1001a的无线充电范围时，即可通过无线充电方式对电动汽车1000进行充电。无线充电接收装置1000a的功率接收天线和整流电路可以集成在一起，也可以分离，分离时整流电路中的整流器通常放在车内。
无线充电发射装置1001a的功率发射天线和逆变器可以集成在一起，也可以分离，此外，非接触式充电可以是无线充电接收装置1000a和无线充电发射装置1001a通过电场或磁场耦合方式进行无线能量传输，具体可为电场感应、磁感应、磁共振或无线辐射方式，本申请实施例对此不做具体限制。进一步地，电动汽车1000和无线充电站1001还可以双向充电，即无线充电站1001通过供电电源向电动汽车1000充电，也可以由电动汽车1000向供电电源放电。
参见图2b，该图为图2a提供的电动汽车无线充电系统的结构示意图。
图2b示出的无线充电发射装置1001a包括：发射变换模块1001a1、功率发射天线1001a2、发射控制模块1001a3、通讯模块1001a4、认证管理模块1001a5和存储模块1001a6。
无线充电接收装置1000a包括：功率接收天线1000a2、接收控制模块1000a3、接收变换模块1000a1、车辆通讯模块1000a4、储能管理模块1000a5和储能模块1000a6。此外，接收变换模块1000a1可以通过储能管理模块1000a5和储能模块1000a6连接，将接收到的能量用于对储能模块1000a6充电，进一步用于电动汽车的驱动。需要说明的是，储能管理模块1000a5和储能模块1000a6可以位于无线充电接收装置1000a的内部，也可以位于无线充电接收装置1000a外部，本申请实施例对此不作具体限制。
发射变换模块1001a1可以与外部电源连接，将从外部电源中获取的交流电或直流电转换为高频交流电，当外部电源的输入为交流电时，发射变换模块1001a1至少包括功率因数校正单元和逆变器；当外部电源的输入为直流电时，发射变换模块1001a1至少包括逆变器。其中，功率因数校正单元用于使无线充电系统的输入电流相位与电网电压相位一致，减小无线充电系统的谐波含量，提高功率因数值，以减少无线充电系统对电网的污染，提高可靠性，功率因数校正单元还可用于根据后级需求，升高或者降低功率因数校正单元的输出电压。逆变器用于将功率因数校正单元输出的电压转换成高频交流电压后作用在功率发射天线1001a2上，高频交流电压可以提高发射效率及传输距离。图2b 以无线充电发射装置1001a外接外部电源为例，可以理解的是，电源还可以是处于无线充电发射装置1001a内部的电源。
功率发射天线1001a2用于将发射变换模块1001a1输出的交流电以交变磁场的形式进行发射。
发射控制模块1001a3可以根据实际无线充电的发射功率需求，控制发射变换模块1001a1的电压、电流和频率变换参数调节，以控制功率发射天线1001a2中高频交流电的电压和电流输出调节。
通讯模块1001a4和车辆通讯模块1000a4用于实现无线充电发射装置1001a和无线充电接收装置1000a之间的无线通讯，包括功率控制信息、故障保护信息、开关机信息、交互认证信息等。一方面，无线充电发射装置1001a可以接收无线充电接收装置1000a发送的电动汽车的属性信息、充电请求和交互认证信息等信息；另一方面，无线充电发射装置1001a还可向无线充电接收装置1000a发送无线充电发射控制信息、交互认证信息、无线充电历史数据信息等。具体地，上述无线通讯的方式可以包括但不仅限于蓝牙(Bluetooth)、无线宽带(WIreless-Fidelity，WiFi)、紫蜂协议(Zigbee)、射频识别技术(Radio Frequency Identification，RFID)、远程(Long Range，Lora)无线技术、近距离无线通信技术(Near Field Communication，NFC)中的任意一种或多种的组合。进一步地，通讯模块1001a4还可以与电动汽车的所属用户的智能终端进行通讯，所属用户通过通讯功能实现远程认证和用户信息传输。
认证管理模块1001a5用于无线充电系统中无线充电发射装置1001a与电动汽车的交互认证和权限管理。
存储模块1001a6用于存储无线充电发射装置1001a的充电过程数据、交互认证数据(例如交互认证信息)和权限管理数据(例如权限管理信息)等，其中，交互认证数据和权限管理数据可为出厂设置也可为用户自行设置的，本申请实施例对此不作具体限制。
功率接收天线1000a2，用于以交变磁场的形式接收功率发射天线1001a2发射的电磁能量。无线充电系统中的功率发射天线1001a2和功率接收天线1000a2的补偿电路的结构组合形式有S-S型、P-P型、S-P型、P-S型、LCL-LCL型、LCL-P型等，本申请实施例对此不作具体限制。另外，为了实现无线充电系统的双向充电功能，该无线充电系统中的无线充电发射装置1001a和无线充电接收装置1000a还可同时包含功率接收天线和功率发射天线，具体可为独立式，也可为集成式。
接收变换模块1000a1，用于把功率接收天线1000a2所接收的电磁能量转换成为储能模块1000a6充电所需要的直流电压和直流电流。接收变换模块1000a1至少包括补偿电路和整流器，其中整流器将功率接收天线所接收的高频谐振电流和电压转换成直流电压和直流电流。
接收控制模块1000a3能够根据实际无线充电的接收功率需求，控制接收变换模块1000a1的电压、电流和频率变换参数调节。
无线充电发射装置1001a的逆变器包括逆变电路和补偿电路，其中逆变电路用于将直流电源输出的直流电逆变为交流电。目前，为了提高无线充电的效率和互操作性，希望无线充电发射装置的逆变电路中的可控开关管实现ZVS，以此来降低可控开关管工作时的功耗。具体可以通过调节逆变器的输入电压，保持移相角度不变，从而使逆变器在所有工况下实现ZVS。但是，调节逆变器的输入电压需要在逆变器的输入端额外增加直流变换电路，这样将会增加无线充电发射装置的体积和成本。此外，通过调节逆变器移 相可以实现逆变器的输出电压的调节，但对于超前和滞后桥臂不能保证逆变器在各种输出电压(不同移相角度)下都可以实现零电压开关，尤其当接收端所反射到发射端的反射阻抗成阻容性时，更难保证可控开关管实现ZVS,而可控开关管一旦失去零电压开关就会导致逆变器的开关损耗比较大，甚至损坏。
为了解决现有技术存在的上述问题，本申请提供了一种无线充电发射装置，该装置包括阻抗调节电路和控制器，其中阻抗调节电路包括超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路，所述超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路分别包括一个电感支路，每个电感支路包括至少一个可控电感支路，每个可控电感支路包括至少一个电感和至少一个开关，所有电感支路相互并联或串联。超前和滞后桥臂阻抗调节电路的第一端分别连接超前和滞后桥臂，超前和滞后桥臂阻抗调节电路的第一端分别连接直流电源的输出端口，利用超前和滞后桥臂阻抗调节电路为超前和滞后桥臂注入感性电流，增大超前和滞后桥臂的感性电流成分。控制器用于控制电感支路中开关的导通或关断来改变流出所述超前和滞后桥臂的电流，即控制器，通过控制导通的电感支路的数目，进而控制注入超前和滞后桥臂的电流大小，从而使所述超前和滞后桥臂的可控开关管实现零电压开关。在保证超前和滞后桥臂的可控开关管可以实现零电压开关的前提下，避免因接入的电感数目过多导致功耗增加，同时，控制器切换电感支路的过程不需要中断无线充电发射装置的功率传输，提高了无线充电发射装置的稳定性与可靠性。本申请的以下说明中可控开关管实现零电压开关即可控开关管实现ZVS。
为了使本技术领域的人员更好地理解本发明方案，下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例仅是本发明一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有做出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。
装置实施例一：
参见图2c，该图为本申请装置实施例一提供的一种无线充电发射装置的示意图。
本申请实施例提供的无线充电发射装置位于发射端，用于将直流电源输入的直流电转换为交变磁场后发送给无线充电接收装置，无线充电发射装置可以应用于电动汽车领域，用于为电动汽车进行充电，而无线充电接收装置可以位于电动汽车上。
该装置包括：逆变电路201、发射线圈202、阻抗调节电路203、控制器204和补偿电路206。
逆变电路201将直流电源输出的直流电逆变为交流电，逆变电路201包括超前桥臂和滞后桥臂，其中，同一个周期内超前桥臂的电压相位超前于滞后桥臂的电压相位。
补偿电路206将逆变电路201输出的交流电进行补偿后发送给发射线圈202。
图2c中以逆变电路201包括可控开关管S1-S4为例，其中包括可控开关管S3和S4的桥臂为超前桥臂，包括可控开关管S1和S2的桥臂为滞后桥臂。
发射线圈202将交流电以交变磁场的形式进行发射。
阻抗调节电路203包括超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路，所述超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路分别包括至少一个电感支路，其中电感支路包括可控电感支路和固定电感支路，每个可控电感支路包括至少一个电感和至少一个开关，每个固定电感支路包括至少一个无开关控制的电感，其中超前桥臂阻抗调节电路的各电感支路之间相互并联或串联，滞后桥臂阻抗调节电路的各电感支路之间也相互并联或串联，超前和滞后桥臂阻抗调节电路的第一端分别连接超前和滞后桥臂的中点，超前和滞后桥臂阻抗调节电路的 第二端分别连接直流电源205的输出端口，即图2c中可控开关管S1和S2之间的中点B及S3和S4之间的中点A。通过将超前和滞后桥臂阻抗调节电路分别与超前和滞后桥臂的中点A，B连接，能够为超前和滞后桥臂注入感性电流，增大超前和滞后桥臂的感性电流成分。所述中点为两个上、下开关管的公共端。
控制器204可以控制电感支路中开关的导通或关断来改变流出所述超前和滞后桥臂的电流，以使超前和滞后桥臂的可控开关管实现ZVS。
可以理解的是，本申请提供的控制器相当于图2b中的发射控制模块1001a3。
使超前和滞后桥臂的可控开关管S1-S4实现ZVS，需要使流出超前和滞后桥臂中点的电流的相位滞后于逆变电路201的超前和滞后桥臂输出电压(超前和滞后桥臂中点相对于逆变器负母线的压差)的相位，即超前和滞后桥臂输出电压的负载呈现为感性。在调节逆变电路201的移相角度时，会改变流出超前和滞后桥臂的中点电流和逆变电路201的超前和滞后桥臂电压之间的相位关系，进而改变超前和滞后桥臂负载的电抗性。另外当接收端反射到发射端的反射阻抗可能为阻容性时，发射端的等效输出阻抗的电抗性也有可能改变，进而也会改变超前和滞后桥臂负载的电抗性。当超前和滞后桥臂由感性电路转变为容性电路时，可控开关管S1-S4不能实现ZVS，本申请通过电感支路向超前或滞后桥臂中注入合适的感性电流，以使超前或滞后桥臂中的电流相位保持滞后于逆变电路201的超前或滞后桥臂输出电压的相位。
可以理解的是，超前和滞后桥臂阻抗调节电路中包括的电感支路的数量可以继续拓展至更多，以使在不同移相角度下超前和滞后桥臂的可控开关可以实现ZVS。通过控制器控制每条可控电感支路中开关的通断，改变接通的可控电感支路的个数(包括0个)，进而改变阻抗调节电路为超前和滞后桥臂注入的感性电流的大小。进一步的，通过对每条可控和固定电感支路中电感的电感量进行合理选择，能够为注入超前或滞后桥臂的感性电流建立合理的电流梯度，使为超前或滞后桥臂注入的感性电流与移相角度的匹配更加精确，避免当超前或滞后桥臂的可控开关已经实现ZVS时，超前或滞后桥臂中的电流增大过多而加剧超前或滞后桥臂上的可控开关管的导通损耗和开关损耗。
其中，当电感支路为多个时，每个电感支路中电感的电感值可以相等，也可以不相等，具体可以根据需要来设置，本申请中不做具体限定。而且，每个可控电感支路中的开关类型可以相同，也可以不同。例如，开关类型可以为以下任意一种：继电器、断路器、接触器、绝缘栅双极型晶体管(Insulated Gate Bipolar Transistor，IGBT)或金属氧化物半导体场效应晶体管(Metal Oxide Semiconductor，MOS)管。每条可控电感支路可以包括多个电感并联或串联，电感与开关的连接关系也可为并联或者串联。
本申请实施例提供的无线充电发射装置添加了阻抗调节电路和控制器。阻抗调节电路包括超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路，所述超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路分别包括至少一个电感支路，
所述电感支路包括可控电感支路和固定电感支路，每个可控电感支路包括至少一个电感和至少一个开关，每个固定电感支路包括至少一个无开关控制的电感，其中超前桥臂阻抗调节电路的固定各电感支路和可控电感支路之间相互并联或串联，滞后桥臂阻抗调节电路的各固定电感支路和可控电感支路之间也相互并联或串联，超前和滞后桥臂阻抗调节电路的第一端分别连接超前和滞后桥臂的中点，超前和滞后桥臂阻抗调节电路的第二端分别连接直流电源205的输出端口。
控制器用于控制可控电感支路中开关的导通或关断来改变流出所述超前和滞后桥臂 的电流，即控制器，通过控制导通的可控电感支路的数目，进而控制注入超前和滞后桥臂的电流大小，从而使所述超前和滞后桥臂的可控开关管实现ZVS。在需要向超前或滞后桥臂注入感性电流时，控制器才控制超前或滞后桥臂阻抗调节电路接入超前或滞后桥臂。当超前和滞后桥臂阻抗调节电路包括多个可控电感支路时，控制器可以控制各个可控电感支路中开关通断以实现超前或滞后桥臂阻抗调节电路呈现的电感的大小不同，超前或滞后桥臂阻抗调节电路的电感大小不同，则向超前或滞后桥臂注入的感性电流大小不同。控制器切换可控电感支路的过程不影响无线充电发射装置的功率传输，提高了无线充电发射装置的稳定性与可靠性。
装置实施例二：
下面分别以超前和滞后桥臂阻抗调节电路包括至少一个可控电感支路为例介绍工作原理。
无论超前桥臂阻抗调节电路包括一个可控电感支路还是包括多个可控电感支路，控制器控制超前桥臂阻抗调节电路的闭合和断开可以通过控制器根据超前桥臂的可控开关管关断时刻流入补偿电路的电流或者流出超前桥臂的电流，控制超前桥臂阻抗调节电路中开关的导通或关断。所述关断时刻为可控开关管从导通到关断所对应的时刻；开通时刻为可控开关管从关断到导通所对应的时刻。其中，实际操作中，开关管实际关断时刻和实际开通时刻会比控制器所发出关断时刻和开通时刻的信号多一个延迟时间。因此，本申请实施例从关断时刻到开通时刻的期间为包括信号延迟时间在内的从关断时刻到开通时刻的最长期间。
可控电感支路均未接入时，流入补偿电路的电流与流出超前桥臂的电流相等。但是，当有电感支路接入时，则流入补偿电路的电流与流出超前桥臂的电流不相等。
控制器根据超前桥臂的可控开关管关断时刻流入补偿电路的电流或者流出超前桥臂的电流，控制超前阻抗调节电路中开关的导通或关断。
滞后桥臂阻抗调节电路包括至少一个可控电感支路的工作原理与超前桥臂阻抗调节电路的工作原理类似，控制器根据滞后桥臂的可控开关管关断时刻流入补偿电路的电流或者流出滞后桥臂的电流，控制滞后桥臂阻抗调节电路中开关的导通或关断。
参见图3a，该图为本申请实施例二提供的一种阻抗调节电路包括超前和滞后桥臂阻抗调节电路，所述超前和滞后桥臂阻抗调节电路分别包括一个可控电感支路的电路图。
本实施例提供的电路中还包括电流检测电路208。
该电流检测电路208用于检测超前和滞后桥臂的可控开关管关断时刻流入补偿电路的电流或者流出超前和滞后桥臂的电流，并将检测的所述超前和滞后桥臂的可控开关管关断时刻流入补偿电路的电流或者流出超前和滞后桥臂的电流发送给控制器。
其中逆变电路201、发射线圈202、直流电源205和补偿电路206的说明可参见前文，以电流流出超前或滞后桥臂的方向为正方向，电压的正方向如图所示，在此不再赘述。
由于超前或滞后桥臂阻抗调节电路分别仅包括一个电感支路且电感支路断开连接时，流入补偿电路的电流与流出超前或者滞后桥臂的电流大小相等，因此，下面以电流检测电路208检测流入补偿电路的电流为例进行介绍。
本实施例中，超前桥臂阻抗调节电路203的电感支路包括串联的电感La和开关Ka，电感La的第一端连接直流电源205的输出端口M，电感La的第二端通过开关Ka连接超前桥臂的中点A，即连接于可控开关管S3和S4之间，因为此时超前桥臂阻抗调节支路中仅包 括一条电感支路,图3a中并未示出控制器，控制器控制该电感支路中开关Ka的导通或关断。
图3a中超前桥臂中的关断电流为I 1a，电感支路中的电流为I La，流入补偿电路206的电流为I 2a，即I 2a为逆变电路201的输出电流，三者之间存在如下关系：
I 1a＝I La+I 2a    (1)
参见式(1)，当电感支路关断时，I La＝0，此时超前桥臂中的关断电流I 1a与流入补偿电路的电流I 2a相等。当电感支路导通时，电感支路为超前桥臂注入感性电流I La，可以影响超前桥臂中电流I 1a的成分。具体还可以参见图3b及图3c所示的波形关系示意图，图中θ a表示移相角度。所述移相角度是指超前桥臂的中点电压和滞后桥臂的中点电压之间的相位差。
此时控制器通过控制电感支路开关的通断进而控制电感支路是否向超前桥臂注入感性电流I Lb。
类似的，图3a中滞后桥臂中的关断电流为I 1b，电感支路中的电流为I Lb，流入补偿电路206的电流为I 2b，即I 2b也为逆变电路201的输出电流，三者之间存在如下关系：
I 1b＝I Lb+I 2b    (2)
参见式(2)，当电感支路关断时，I Lb＝0，此时滞后桥臂中的关断电流I 1b与流入补偿电路的电流I 2b相等。当电感支路导通时，电感支路为滞后桥臂注入感性电流I Lb，可以影响滞后桥臂中电流I 1b的成分。具体还可以参见图3b，图3c及图3d所示的波形关系示意图，图中θ b表示移相角度。
此时控制器通过控制电感支路开关的通断进而控制电感支路是否向滞后桥臂注入感性电流I Lb。
其中逆变电路201的输出电流I 2，I 2a＝-I 2b＝I 2     (3)
以电流流出超前或滞后桥臂的方向为正方向，预先确定逆变电路处于不同的输出功率下，超前或滞后桥臂的关断电流能够使超前或滞后桥臂的可控开关管实现ZVS时的最大值设置为预设电流I 0(I 0<0)，可以理解的是，预设电流也可以根据实际需要进行适当调整，例如可以选择小于I 0但与I 0较为接近的某一电流值为预设电流，也可以根据补偿电路的电容电压来调节预设电流。
当电流检测电路208检测超前桥臂的可控开关管关断时刻流入补偿电路的电流为I 3，可以理解的是，当电感支路均未接通时，电流I 3与流出超前桥臂的电流相等，控制器将I 3与预设电流I 0进行比较，当I 3>I 0时，超前桥臂的可控开关管不能实现ZVS，控制器控制电感支路接通，电感支路向超前桥臂的中点注入感性电流以使滞后桥臂的可控开关管实现ZVS。I 3<I 0时，超前桥臂的可控开关管已经能够实现ZVS，控制器关断该电感支路以降低功耗。类似的，电流检测电路208检测滞后桥臂可控开关管关断时刻流入补偿电路的电流并与预设电流I 0进行比较，控制器控制电感支路是否需要接通以实现ZVS。
另外，在逆变电路的输出功率确定的情况下，还可以根据移相角度来控制电感支路的通断。
控制器根据输出功率查找移相角度与滞后桥臂的可控开关管关断时刻流出超前或滞后桥臂的电流之间的对应关系；不同的输出功率对应不同的对应关系；通过查找出的对应关系获得逆变电路当前的移相角度位于的移相角度区间，根据移相角度区间控制可控电感支路中开关的导通或关断，不同的移相角度区间对应导通不同数目的电感支路。
电感支路未接通时，流出超前或滞后桥臂的电流与流入补偿电路的电流的绝对值I 2相 等。以电流流出超前或滞后桥臂的方向为正方向，预先建立逆变电路在不同输出功率下的移相角度与超前及滞后桥臂的可控开关管关断时刻流出超前或滞后桥臂的电流的对应关系，即该对应关系同时为逆变电路在不同输出功率下的移相角度与流入补偿电路的电流I 2的对应关系，不同的输出功率对应不同的对应关系。为了方便描述，下面以超前和滞后桥臂的关断电流分别代表超前和滞后桥臂的可控开关管关断时刻流出超前和滞后桥臂的电流。具体实现时，对应关系可以利用曲线或者表格来实现，例如不同的输出功率对应不同的曲线，该曲线为移相角度与超前或滞后桥臂的关断电流的二维曲线，即二维曲线表征了移相角度与滞后桥臂的关断电流的对应关系。
需要说明的是，逆变电路201的输出功率在不考虑无线充电发射装置与无线充电接收装置之间的传输效率的情况下，逆变电路201的输出功率等价于无线充电接收装置的输出功率，一般传输效率小于100％，逆变电路的输出功率与无线充电接收装置的输出功率之间存在一定的换算关系。因此，也可以理解为，控制器根据逆变电路201当前的移相角度和无线充电接收装置的输出功率，控制该电感支路中开关的导通或关断。其中，无线充电接收装置的输出功率即为无线充电系统的输出功率。
在逆变电路的输出功率确定的情况下，可以根据移相角度来控制电感支路的通断。
如图3b所示，具体为当移相角度较大时，流入补偿电路206的电流I 2(即逆变电路201的输出电流)的相位已经滞后于逆变电路201的超前桥臂输出电压U 1(超前桥臂中点相对于负母线的电压)的相位，当超前桥臂中的电流I 1a为流入补偿电路206的电流I 2时，可控开关管S3和S4已经可以实现ZVS。同样的，流入补偿电路206的电流I 2(即逆变电路201的输出电流)的相位已经滞后于逆变电路201的滞后桥臂输出电压U 2(滞后桥臂中点相对于负母线的电压)的相位，当滞后桥臂中的电流I 1b为流入补偿电路206的电流I 2时，可控开关管S1和S2已经可以实现ZVS，此时控制器控制超前和滞后桥臂电感支路的开关K a,K b断开，电感支路不向滞后桥臂注入感性电流I La,I Lb，以避免电感接入带来功耗。
如图3c所示，当移相角度较小时，流入补偿电路206的电流I 2的相位超前于逆变电路201的超前桥臂输出电压U 1的相位，超前桥臂的可控开关管S3和S4不能实现ZVS，此时控制器控制电感支路的开关K a闭合，使电感支路为超前桥臂注入感性电流I La，感性电流I La与流入补偿电路206的电流I 2a进行叠加，以使超前桥臂中电流的相位滞后于逆变电路201的超前桥臂输出电压U 1的相位，从而使超前桥臂的可控开关管S3和S4实现ZVS。
如图3d所示，当移相角度较小时，流入补偿电路206的电流I 2的相位超前于逆变电路201的滞后桥臂输出电压U 2的相位，滞后桥臂的可控开关管S1和S2不能实现ZVS，此时控制器控制电感支路的开关K b闭合，使电感支路为滞后桥臂注入感性电流I Lb，感性电流I Lb与流入补偿电路206的电流I 2b进行叠加，以使滞后桥臂中电流的相位滞后于逆变电路201的滞后桥臂输出电压U 2的相位，从而使滞后桥臂的可控开关管S1和S2实现ZVS。
可以预先将超前桥臂上的可控开关管实现ZVS时超前桥臂中关断电流能够达到的最大值设置为预设电流I 0，逆变电路201不同的输出功率对应不同的预设电流I 0。在每条二维曲线上分别预先获取预设电流I 0对应的移相角度θ 0，以该移相角度θ 0为预设角度， 划分为两个移相角度区间，即分别为大于预设角度θ 0的移相角度区间和小于等于预设角度θ 0的移相角度区间。
参见图3e，该图为本申请实施例二提供的阻抗调节支路包括一个电感支路时I 1a与移相角度的关系曲线图。
当电感支路未接通时，I 2a与I 1a相等,等于I 2。
以电流流出超前桥臂的方向为正方向，预先确定逆变电路处于不同的输出功率下，超前桥臂的关断电流能够使超前桥臂的可控开关管实现ZVS时的最大值设置为预设电流I 0(I 0<0)，可以理解的是，预设电流也可以根据实际需要进行适当调整，例如可以选择小于I 0但与I 0较为接近的某一电流值为预设电流，也可以根据补偿电路的电容电压来调节预设电流。
预设电流I 0对应的移相角度为预设角度θ 0，则小于θ 0的移相角度所在区间为第一移相角度区间，大于θ 0的移相角度所在区间为第二移相角度区间。
当逆变电路当前的移相角度位于第一移相角度区间内时，即当前的移相角度小于预设角度，此时滞后桥臂的可控开关管不能实现ZVS，需要控制器控制电感支路接通，向超前桥臂的中点注入感性电流。当逆变电路当前的移相角度位于第二移相角度区间内时，即当前的移相角度大于预设角度，此时超前桥臂的可控开关管已经能够实现ZVS，可以关断该电感支路以降低功耗。
类似的，可以通过滞后桥臂中的电流I 1b与移项角度的关系曲线图，来控制滞后桥臂电感支路的通断状态，以确保滞后桥臂的可控开关管实现ZVS。
另外，如上所述，本申请中不具体限制超前或滞后桥臂阻抗调节电路203的电感支路的数目，可以根据实际需要以及硬件的提及和成本来选择设置，电感支路的数目越多，对应呈现的电感值越多，对应于移相角度的匹配越精确。控制器控制每个电感支路中开关的通断状态，能够调整阻抗调节电路向超前或滞后桥臂注入的感性电流的大小，使滞后桥臂的可控开关管在不同的移相角度下实现ZVS。
其中，超前或者滞后桥臂阻抗调节电路203的每个电感支路的电感L和开关K可以是并联的关系。每个电感支路也不仅限于一个电感L,可以多个电感并联或串联。每个支路上的电感的大小可以相同或不同，所呈现的电感值丰富，对应的移项角度的匹配越精确。
装置实施例三：
参见图4，该图为无线充电发射装置的超前或者滞后桥臂阻抗调节电路各包括两个电感支路时的电路图。
电路中的逆变电路201、发射线圈202、直流电源205和补偿电路206的说明可参见前文，在此不再赘述。
超前桥臂阻抗调节电路403包括第一电感支路和第二电感支路，其中第一电感支路包括串联的第一电感L1a和第一开关K1a，L1a的第一端连接直流电源的输出端口M，L1a的第二端通过K1a连接超前桥臂的中点A；第二电感支路包括串联的第二电感L2a和第二开关K2a，L2a的第一端连接直流电源的输出端口M，L2a的第二端通过K2a连接超前桥臂的中点；第一电感L1a和第二电感L2a的电感量可以相同也可以不同，本申请对此不做具体限定。
控制器(未示出)根据超前桥臂的可控开关管(即可控开关管S3或S4)关断时刻超 前桥臂的电流，控制第一开关K1a和第二开关K2a的导通或关断。所述关断时刻为可控开关管从导通到关断所对应的时刻；开通时刻为可控开关管从关断到导通所对应的时刻。其中，实际操作中，开关管实际关断时刻和实际开通时刻会比控制器所发出关断时刻和开通时刻的信号多一个延迟时间。因此，本申请实施例从关断时刻到开通时刻的期间为包括信号延迟时间在内的从关断时刻到开通时刻的最长期间。
第一电感支路和第二电感支路并联形成调节支路，超前桥臂阻抗调节电路的第一端连接超前桥臂的中点A，超前桥臂阻抗调节电路的第二端连接直流电源205的输出端口M，即连接于可控开关管S3和S4之间。
图4中超前桥臂中的关断电流为I 1a，超前桥臂阻抗调节电路的电流为I La，逆变电路201的输出电流为I 2＝I 2a，三者之间仍满足式(1)，即I 1a＝I La+I 2a，其中超前桥臂阻抗调节电路的电流I La为通过两个电感支路的电流总和。
超前桥臂阻抗调节电路通过为超前桥臂注入感性电流I La，进而影响了超前桥臂中关断电流I 1a的电抗性。此时控制器控制每个电感支路开关的通断进而控制电感支路向超前桥臂注入感性电流I La的大小。
当所有电感支路均未接通时，超前桥臂中的关断电流I 1a与流入补偿电路的电流I 2a相等，同样以电流流出超前桥臂的方向为正方向
预先确定逆变电路处于不同的输出功率，输出电压，接收端匹配网络及偏移位置时，超前桥臂的关断电流能够使超前桥臂的可控开关管实现ZVS时的最大值设置为预设电流I 0。已经导通其中一条电感支路时，I 2a与I 1a不相等，并且导通的电感支路会影响I 1a大小。
当两条可控电感支路中的一条电感支路已经导通时，超前桥臂的可控开关管实现ZVS时超前桥臂中关断电流能够达到的最大值设置为阈值电流I 4，且阈值电流I 4大于预设电流I 0，因为一条电感支路导通向超前桥臂注入感性电流。逆变电路201不同的输出功率，输出电压，接收端匹配网络及偏移位置，对应不同的预设电流I 0和阈值电流I 4。
参见图4，本实施例提供的电路中还包括了电流检测电路406。该电流检测电路406用于检测超前桥臂的可控开关管关断时刻流入补偿电路的电流或者流出超前桥臂的电流，并将检测的超前桥臂的可控开关管关断时刻流入补偿电路的电流或者流出超前桥臂的电流发送给控制器。当所有电感支路均未接通时，电流检测电路406检测滞后桥臂的可控开关管关断时刻流入补偿电路的电流为I 3，电流I 3等于流出超前桥臂的电流I 1a。控制器将I 3与电流的区间值(I 0和I 4)进行比较，I 3落入不同的区间，对应控制不同数目的电感支路闭合。
当I 3>I 4时，超前桥臂的可控开关管不能实现ZVS且需要较大的感性电流，控制器控制第一电感支路和第二电感支路均接通，以向超前桥臂的中点A注入足够感性电流；I 4>I 3>I 0时，超前桥臂的可控开关管不能实现软开关，此时控制器只需控制第一电感支路或第二电感支路中的任意一个接通即可为超前桥臂中点A注入足够的感性电流；当I 3<I 0时，超前桥臂的可控开关管已经能够实现ZVS，控制器关断该电感支路以降低功耗。
当已有电感支路接通时，电流检测电路406可以检测超前桥臂的可控开关管关断时刻流出超前桥臂的电流并将检测结果发送给控制器，控制器首先根据超前桥臂的可控开关管关断时刻流出超前桥臂的电流与当前的电感支路的闭合数目以获得当前所述超前和滞后桥臂阻抗调节电路电感支路的电流，从而获得流入补偿电路的电流，然后获得流入补偿电路的电流与预设电流的差值，根据该差值控制电感支路中开关的导通和关断，差值不同对应闭合不同数目的电感支路。类似的，电流检测电路406检测滞后桥臂可控开关管关断时刻流入补偿电路的电流I 2b并与预设电流I 0和阈值电流I 4进行比较，控制器控制电 感支路是否需要接通以实现ZVS。
装置实施例四：
本申请实施例提供的无线充电发射装置的超前或者滞后桥臂阻抗调节电路的电感支路除了包含至少一个可控电感支路外，还包含固定电感支路，所述固定电感支路包括至少一个固定电感，无可控开关控制。所述固定电感支路的第一端连接直流电源205端口M，固定电感支路的第二端连接超前或滞后桥臂的中点A或B。
参见图5a，该图为无线充电发射装置的超前桥臂阻抗调节支路包括一个可控电感支路和一个固定电感支路时的电路图。
电路中的逆变电路201、发射线圈202、直流电源205和补偿电路206的说明可参见前文，在此不再赘述。
超前桥臂阻抗调节电路503包括第一可控电感支路和第一固定电感支路，其中第一可控电感支路包括串联的第一电感L1a和第一开关K1a，L1a的第一端连接直流电源的输出端口M，L1a的第二端通过K1a连接超前桥臂的中点A；第一固定电感支路包括第二电感L2a，L2a的第一端连接直流电源的输出端口M，L2的第二端连接超前桥臂的中点A；第一电感L1a和第二电感L2a的电感量可以相同也可以不同，本申请对此不做具体限定。所述固定电感的大小可以根据接收端负载的特性进行匹配，即使接收端的等效阻抗为阻容性时，通过固定电感支路向超前桥臂注入感性电流，而使超前桥臂的开关管实现ZVS。所述固定电感的具体取值，与负载大小有关，本申请实施例中不做具体限定。
控制器(未示出)根据超前桥臂的可控开关管(即可控开关管S3或S4)关断时刻超前桥臂的电流，控制第一开关K1a的导通或关断。所述关断时刻为可控开关管从导通到关断所对应的时刻。
第一可控电感支路和第一固定电感支路并联形成超前桥臂阻抗调节电路的电感支路，超前桥臂阻抗调节电路的第一端连接超前桥臂的中点，即连接于可控开关管S3和S4之间，第二端连接直流电源205的输出端口。
图5a中超前桥臂中的关断电流为I 1a，超前桥臂阻抗调节支路中的电流为I La，逆变电路201的输出电流为I 2＝I 2a，三者之间仍满足式(1)，即I 1a＝I La+I 2a，其中超前桥臂阻抗调节电路中的电流为I La为通过第一可控电感支路和第一固定电感支路的电流总和。
超前桥臂阻抗调节电路通过为超前桥臂注入感性电流I La，进而影响了超前桥臂中关断电流I 1a的电抗性。由于固定电感支路没有设置开关，所以固定电感支路中的电感持续为超前桥臂提供感性电流。此时控制器控制第一可控电感支路开关的通断进而控制可控电感支路向超前桥臂注入感性电流I La的大小。当可控电感支路未接通时，固定电感支路已经导通，I 2a与I 1不相等，且固定电感支路会影响I 1的大小。
参见图5a，该图为本申请实施例四提供的一种超前桥臂阻抗调节电路包括一个可控电感支路和一个固定电感支路的电路图。
本实施例提供的电路中还包括了电流检测电路506。该电流检测电路506用于检测超前桥臂的可控开关管关断时刻流入补偿电路的电流或者流出超前桥臂的电流，并将检测的超前桥臂的可控开关管关断时刻流入补偿电路的电流或者流出超前桥臂的电流发送给控制器。当仅固定电感支路接通而可控电感支路未接通时，电流检测电路506检测超前桥臂的可控开关管关断时刻流入补偿电路的电流为I 5，由于有固定电感支路的电流I 固定，电流I 5小于流出超前桥臂的电流I 1a。控制器将I 5+I 固定与预设电流I 0进行比较，I 5落入不同的区间， 对应控制不同数目的电感支路闭合。
当I 5+I 固定>I 0时，超前桥臂的可控开关管不能实现软开关且需要更大的感性电流，控制器控制可控电感支路接通，此时控制器只需控制第一电感支路接通即可为超前桥臂中点注入足够的感性电流；当I 5+I 固定<I 0时，超前桥臂的可控开关管已经能够实现ZVS，控制器关断该电感支路以降低功耗。
类似的，滞后桥臂阻抗调节支路可以包括一个可控电感支路和一个固定电感支路。电流检测电路306检测滞后桥臂可控开关管关断时刻流入补偿电路的电流并与预设电流I 0进行比较，控制器控制可控电感支路是否需要接通以实现ZVS。
其中，超前和滞后桥臂阻抗调节支路也可以至少一个可控电感支路和至少一个固定电感支路。所述固定电感支路不需要同时存在于超前和滞后桥臂阻抗调节电路中。
本实施例区别于实施例二于，本实施例的超前或者滞后桥臂阻抗调节电路包括至少一个固定电感，无可控开关控制。所述实施例适用于当接收端的等效阻抗有很大可能性为阻容性时，所包含的固定电容支路可以无需控制器支配，自动增加流出超前或者滞后桥臂的感性电流，以此来提高无线充电装置的互操作性，确保当接收端的等效阻抗为阻容性时，超前和滞后桥臂的可控开关管仍可实现ZVS。
另外，如上所述，本申请中不具体限制超前或滞后桥臂阻抗调节电路203的电感支路的数目，可以根据实际需要以及硬件的提及和成本来选择设置，电感支路的数目越多，对应呈现的电感值越多，对应于移相角度的匹配越精确。控制器控制每个电感支路中开关的通断状态，能够调整阻抗调节电路向超前或滞后桥臂注入的感性电流的大小，使滞后桥臂的可控开关管在不同的移相角度下实现ZVS。如图5b所示，为位于直流电源205端口M与超前或滞后桥臂中点A或B之间的超前或滞后的可控电感支路和固定电感支路连接结构。超前或滞后桥臂阻抗调节电路包括两个可控电感支路和一个固定电感支路，其中所述固定电感支路不需要同时存在于超前和滞后桥臂阻抗调节电路中。
其中，超前或者滞后桥臂阻抗调节电路503,504的每个电感支路的电感L和开关K可以是并联的关系。每个电感支路也不仅限于一个电感L,可以多个电感并联或串联。每个支路上的电感的大小可以相同或不同，所呈现的电感值丰富，对应的移项角度的匹配越精确。
装置实施例五：
本申请实施例提供的无线充电发射装置的至少一个电感支路还包括第一二极管和第二二极管，其中的第一二极管的阳极连接电感支路中电感和开关的公共端，第一二极管的阴极连接直流电源输出端的正直流母线；第二二极管的阴极连接电感支路中电感和开关的公共端，第二二极管的阳极连接直流电源输出端的负直流母线，第一二极管和第二二极管形成二极管箝位电路，下面结合附图具体说明。
首先以超前或滞后桥臂阻抗调节电路包括一个电感支路为例进行说明。
参见图6a，该图为超前和滞后桥臂阻抗调节电路的电感支路分别包括一个可控电感支路且可控电感支路上存在二极管箝位电路的电路图。
其中逆变电路201、发射线圈202、直流电源205、补偿电路206以及控制器(图6a中并未示出)的说明可参见装置实施例一，在此不再赘述。
超前桥臂阻抗调节电路603包括一个可控电感支路，该可控电感支路包括串联的电感L1a和开关K1a，可控电感支路还包括第一二极管D1a和第二二极管D2a，其中第一二极 管D1a的阳极连接电感L1a和开关K1a的公共端，第一二极管D1a的阴极连接直流电源205的正直流母线，第二二极管D2a的阴极连接电感L1a和开关K1a的公共端，第二二极管D2a的阳极连接直流电源205负直流母线。
以超前桥臂阻抗调节电路的电流I La流出超前桥臂中点的方向为正方向，当控制器控制开关K1a由闭合到断开，且当前电感电流为负时，第一二极管D1a导通，第二二极管D2a截止，导通的第一二极管D1a为电感L1a提供了续流通路。
当控制器控制开关K1a由闭合到断开，当前电感电流为正，且当开关K1a位于电感L1a的右侧时，第一二极管D1a截止，第二二极管D2a导通，导通的第二二极管D2a为电感L1a提供了续流通路；当开关K1a位于电感L1a的左侧,第一二极管D1a导通，第二二极管D2a截止，导通的第二二极管D2a为电感L1a提供了续流通路。
此外，二极管箝位电路还能够将电感L1a和开关K1a的公共端C的电压U C稳定在安全范围内，以第一二极管D1a和第二二极管D2a均为硅管为例，硅管的导通压降为0.7V，直流电源205的正直流母线电压为U E、直流电源205的负直流母线电压为U D，当U C-U E>0.7V时，第一二极管D1a导通，当U D-U C>0.7V时，第二二极管D2a导通，因此二极管箝位电路可以使电压U C满足：U D-0.7V<U C<U E+0.7V，即限制U C的电压峰值与直流电源205的正负直流母线间电压的差值小于二极管的导通压降，具有保护电路的作用。类似的，滞后桥臂阻抗调节电路可以包括至少一个可控电感支路还包括第一二极管和第二二极管，其中的第一二极管的阳极连接电感支路中电感和开关的公共端，第一二极管的阴极连接直流电源输出端的正直流母线；第二二极管的阴极连接电感支路中电感和开关的公共端，第二二极管的阳极连接直流电源输出端的负直流母线，第一二极管和第二二极管形成二极管箝位电路，如图6a所示。
由于阻抗调节电路的电感支路还可以包括并联在一起的多个可控电感支路，还可以为其中的至少一个可控电感支路增加上述二极管箝位电路，使得当每个包括上述二极管箝位电路的电感支路的开关断开时，能够为该可控电感支路上的电感提供续流通路，并且还能够限制每个可控电感支路上的电压峰值稳定在安全范围内，提高电路的可靠性与稳定性。
下面以阻抗调节电路的电感支路至少包括两个可控电感支路：第一可控电感支路和第二可控电感支路为例进行说明。
参见图6b，该图为超前或滞后桥臂阻抗调节电路包括两个可控电感支路且第一电感支路上存在二极管箝位电路时的电路图。
其中逆变电路201、发射线圈202、直流电源205、补偿电路206以及控制器(图6b中并未示出)的说明可参见装置实施例一，在此不再赘述。
超前或滞后桥臂阻抗调节电路603或604包括两个可控电感支路，其中第一可控电感支路包括串联的第一电感L1和第一开关K1，第一端与超前或滞后桥臂中点A或B连接，所述第一可控电感支路的第二端与直流电源205输出端M连接，还包括第一二极管D3和第二二极管D4，其中第一二极管D3的阳极连接第一电感支路中第一电感L1和第一开关K1的公共端，第一二极管D3的阴极连接直流电源205的正直流母线E，第二二极管D4的阴极连接第一电感支路中第一电感L1和第一开关K1的公共端，第二二极管D4的阳极连接直流电源205的负直流母线D。第二电感支路包括串联的第二电感L2和第二开关K2。
当二极管箝位电路包括第一二极管D3和第二二极管D4时的工作原理可参见图6a所示电路对应部分的相关介绍，在此不再赘述。
还可以参见图6c，该图为超前或滞后桥臂阻抗调节电路包括两个可控电感支路且第二可控电感支路上存在二极管箝位电路的电路图。
图6c所示电路与图6b所示电路的区别为：图6c所示电路的第二可控电感支路包括第一二极管D5和第二二极管D6，其中第一二极管D5的阳极连接第二电感支路中第二电感L2和第二开关K2的公共端，第一二极管D5的阴极连接直流电源205的正直流母线E，第二二极管D6的阴极连接第二可控电感支路中第二电感L2和第二开关K2的公共端，第二二极管D6的阳极连接直流电源205的负直流母线D。所述第二可控电感支路的第一端与超前或滞后桥臂中点A或B连接，第二端与直流电源205输出端M连接，第二可控电感支路与第一可控电感支路并联。
其中，当二极管箝位电路包括第一二极管D5和第二二极管D6时的工作原理可参见图6a所示电路对应部分的相关介绍，在此不再赘述。
参见图6d，该图为超前或滞后桥臂阻抗调节电路包括两个可控电感支路且每个可控电感支路均存在二极管箝位电路的电路图。
图6d所示电路的第一可控电感支路包括串联的第一电感L1和第一开关K1，还包括第一二极管D3和第二二极管D4，其中第一二极管D3的阳极连接第一电感L1和第一开关K1的公共端，第一二极管D3的阴极连接直流电源205的正直流母线E，第二二极管D4的阴极连接第一电感L1和第一开关K1的公共端，第二二极管D4的阳极连接直流电源205的负直流母线D.
第二可控电感支路包括串联的第二电感L2和第二开关K2，还包括第一二极管D5和第二二极管D6，其中第一二极管D5的阳极连接第二电感L2和第二开关K2的公共端，第一二极管D5的阴极连接直流电源205的正直流母线E，第二二极管D6的阴极连接第二电感L2和第二开关K2的公共端，第二二极管D6的阳极连接直流电源205的负直流母线D。所述第一可控电感支路的第一端与超前或滞后桥臂中点A或B连接，第二端与直流电源205输出端M连接，第二可控电感支路与第一可控电感支路并联。
第一二极管D3和第二二极管D4形成的二极管箝位电路作用于第一电感支路，第一二极管D5和第二二极管D6形成的二极管箝位电路作用于第二电感支路，工作原理可参见图6a所示电路对应部分的相关介绍，在此不再赘述。
本申请实施例提供的无线充电发射装置在超前或滞后桥臂阻抗调节电路中至少一个可控电感支路包括第一二极管和第二二极管，利用两个二极管形成二极管箝位电路，当具有二极管箝位电路的电感支路的开关断开时，能够为该可控电感支路中的电感提供续流通路，并且能够维持该可控电感支路中电感和开关的公共端的电压稳定在安全范围内，具有保护电路的作用。可以理解的是，本实施例超前或滞后桥臂阻抗调节电路中除了至少一个可控电感支路包括第一二极管和第二二极管，还可以包括至少一个固定电感支路，如图6e所示，该图为超前或滞后桥臂阻抗调节电路包括两个可控电感支路和一个固定电感支路，所述每个可控电感支路均存在二极管箝位电路的电路图。
为了便于说明，以下的装置实施例中均以超前或滞后桥臂阻抗调节电路的电感支路至少包括两个可控电感支路：第一可控电感支路和第二可控电感支路并联为例进行说明，其中第一可控电感支路包括串联的第一电感和第一开关，第二可控电感支路包括串联的 第二电感和第二开关，可以理解的是，当超前或滞后桥臂阻抗调节电路包括的可控电感支路和固定电感支路数量拓展至更多且各电感支路可串联也可以并联时，其工作原理与只包括两个并联可控电感支路时的工作原理相似。
装置实施例六：
本实施例具体介绍阻抗调节电路与直流电源输出端的连接关系，即超前和滞后桥臂阻抗调节电路第二端与直流电源输出端的连接关系，下面结合附图分别说明。
参见图7a，该图为超前和滞后桥臂阻抗调节电路的第二端连接直流电源的直流母线中点时的电路图。
其中逆变电路201、发射线圈202、直流电源205、补偿电路206以及控制器(图7a中并未示出)的说明可参见装置实施例一，在此不再赘述。
超前和滞后桥臂阻抗调节电路703和704各包括第一可控电感支路和第二可控电感支路，两个可控电感支路并联形成超前和滞后桥臂阻抗调节电路，超前和滞后桥臂阻抗调节电路第二端直接连接直流电源输出端的直流母线中点。
其中，阻抗调节电路还可以包括第一隔直电容，超前和滞后桥臂阻抗调节电路的第二端分别通过第一隔直电容连接电源输出端的直流母线中点，参见图7b。
参见装置实施例一中的说明，为使超前和滞后桥臂中的可控开关管实现ZVS，需要使超前和滞后桥臂中的电流的相位滞后于逆变电路201的输出电压的相位，利用电感支路向超前和滞后桥臂中注入合适的感性电流，使超前和滞后桥臂中的电流相位保持滞后于逆变电路201的超前和滞后桥臂输出电压的相位。但同时电感支路中的直流电成分也会被注入超前和滞后桥臂中，该直流电成分会使超前和滞后桥臂中电流的有效值增加，进而增加超前和滞后桥臂中可控开关管导通损耗以及开关损耗。因此本申请实施例提供的无线充电发射装置在超前和滞后桥臂阻抗调节电路中引入第一隔直电容，并使超前和滞后桥臂阻抗调节电路的第二端分别通过第一隔直电容连接直流母线的中点，以滤除超前和滞后桥臂阻抗调节电路中的直流电成分，减小超前和滞后桥臂中的电流有效值增加量，进而降低超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。
另外，超前和滞后桥臂阻抗调节电路的第二端也可以连接直流电源输出端的正直流母线，其阻抗调节电路还包括第二隔直电容，阻抗调节电路的第二端分别通过第二隔直电容连接电源输出端的正直流母线，参见图7c。本申请实施例提供的无线充电发射装置在阻抗调节电路中增加第二隔直电容，并使阻抗调节电路的第二端分别通过第二隔直电容连接直流电源输出端的正直流母线，能够滤除阻抗调节电路中的直流电成分，减小了超前和滞后桥臂中的电流有效值增加量，降低了超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。
另外，阻抗调节电路的第二端也可以连接直流电源输出端的负直流母线，其阻抗调节电路还包括第三隔直电容，阻抗调节电路的第二端分别通过第三隔直电容连接电源输出端的负直流母线，从而滤除调节支路中的直流电成分，减小了超前桥臂中的电流有效值增加量，降低了超前桥臂中可控开关管的导通损耗以及开关损耗。参见图7d。
另外，阻抗调节电路同时包括第二隔直电容和第三隔直电容，阻抗调节电路的第二端分别通过第二隔直电容连接电源输出端的正直流母线，且阻抗调节电路的第二端还分别通过第三隔直电容连接电源输出端的负直流母线，使阻抗调节电路可以与没有直流母线的直流电源连接，还能够滤除阻抗调节电路中的直流电成分，减小超前和滞后桥臂中的 电流有效值增加量，降低了超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。参见图7e。
另外，阻抗调节电路同时包括第一隔直电容，第二隔直电容和第三隔直电容，阻抗调节电路的第二端通过第一隔直电容分别与第二隔直电容和第三隔直电容的第一端连接，第二隔直电容的第二端与电源输出端的正直流母线连接，且第三隔直电容的第二端与电源输出端的负直流母线，能够滤除调节支路中的直流电成分，还降低等效串联电阻的损耗，减小超前和滞后桥臂中的电流有效值增加量，降低了超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。参见图7f。
如图7a-7f所示，阻抗调节电路通过至少一个隔直电容与电源连接，即超前和滞后桥臂阻抗调节电路的第二端分别通过至少一个隔直电容与电源相连。
可以理解的是，所述超前桥臂阻抗调节电路可以包括至少一个隔直电容，所述超前桥臂阻抗调节电路的第二端通过至少一个隔直电容与电源相连，具体的连接方式如图7g-7i所示。
可以理解的是，所述滞后桥臂阻抗调节电路可以包括至少一个隔直电容，所述滞后桥臂阻抗调节电路的第二端通过至少一个隔直电容与电源相连，具体的连接方式如图7g-7i所示。
可以理解的是，所述超前和滞后桥臂阻抗调节电路可以分别包括至少一个隔直电容，所述超前和滞后桥臂阻抗调节电路的第二端分别通过至少一个隔直电容与电源相连，具体的连接方式如图7g-7i所示。
可以理解的是，还可以在至少一个电感支路中增加第一二极管和第二二极管以形成二极管箝位电路，具体可以参见装置实施例二，在此不再赘述。
可以理解的是，本实施例中超前或滞后桥臂阻抗调节电路包括至少一个可控电感支路，不仅限于两个可控电感支路，也可以有大于等于一个可控电感支路。另外，超前或滞后桥臂阻抗调节电路包括至少一个固定电感支路。
为了使本领域技术人员更好地理解本申请提供的技术方案，下面具体介绍阻抗调节电路包括的电感大小的选取。本实施例以阻抗调节电路包括以下两个电感支路：第一电感支路和第二电感支路为例具体介绍了确定电感支路中电感的电感量的方法，可以理解的是，该方法可以拓展应用于阻抗调节电路包括更多个并联的电感支路时的电路场景。
参见图4，该图为无线充电发射装置的电路图。
其中逆变电路201、发射线圈202、阻抗调节电路803、直流电源205以及控制器(图4中并未示出)的说明可参见图4所示电路对应部分的相关介绍，在此不再赘述。
下面以超前桥臂S4关断过程进行分析，超前桥臂S3和滞后桥臂S1-S2关断过程分析的方法与之类似，因此不再赘述。理想工况下，电感电流在开关过程中保持恒定不变且流出超前桥臂的电流在开关过程中保持恒定不变，根据可控开关管的结电容C oss，母线电压U bus，超前桥臂的死区时间△t dead，可获取当超前桥臂的可控开关管实现ZVS时可以获取当超前桥臂的可控开关管实现ZVS前提下，逆变电路201的S4输出电流关断时刻所需要的负电流I 2的最小值为I 2min，考虑电流I 2min在死区时间△t dead内恒定，且电流I 2min对桥臂的两个可控开关管的结电容C oss分别进行充放电到母线电压Ubus和零，则可以获得公式4，具体如下：
Figure PCTCN2020108554-appb-000001
当C oss＝500pF，U bus＝640V，△t dead＝300ns时，可确定I 2min＝-2.133A。
预先将超前桥臂上的可控开关管实现ZVS时超前桥臂中关断电流能够达到的最大值 设置为I 1max＝32A：
结合式(1)，此时电感支路需要向超前桥臂注入的电流峰值为I Lmax需满足：
I Lmax>I 1max-I 2min      (5)
即当I Lmax>34.133A时，即使超前桥臂中关断电流达到最大值时，超前桥臂也可以实现ZVS，下面以I Lmax＝35A为例说明电感量的确定过程。
逆变电路201上开关管的开关周期T SW、母线电压U bus、电感支路需要向超前桥臂注入的电流峰值为I Lmax以及调节支路的最大电感量L MAX关系如下，超前桥臂电压中的交流分量加在电感的电压为一开关周期T SW，幅值为U bus/2的方波电压，电感电流的波形为一正负对称的三角波，因此根据电感的电流与电压的关系，可以获得公式(6)：
Figure PCTCN2020108554-appb-000002
当T SW＝1/85kHz时，通过式(6)可以确定此时L MAX＝26.9μH。
如果调节支路包括两条并联的电感支路，且每条电感支路包括一个电感，L MAX即为第一电感L1a和第二电感L2a并联后的电感值。
在一种可能的实现方式中，可以使第一电感L1a和第二电感L2a的电感量均为53.8μH，当接通一个电感支路时，调节支路向超前桥臂注入的电流峰值为17.5A，当接通两个电感支路时，调节支路向超前桥臂注入的电流峰值为35A。
当调节支路仅固定的包括以上两个电感支路时，虽然能够使超前桥臂的可控开关管实现ZVS，但会导致调节支路注入超前桥臂的感性电流有效值过大，进而增加了超前桥臂上可控开关管的开关损耗。为了避免上述问题，可以调节支路中并联电感支路的数量，通过控制导通的电感支路的数目控制注入超前桥臂的电流大小，从而使超前桥臂阻抗调节支路注入超前桥臂的电感电流与实际所需相匹配。
方法实施例：
本申请实施例还提供了一种无线充电发射装置的控制方法，应用于以上实施例介绍的无线充电发射装置，该无线充电发射装置包括：逆变电路、发射线圈、阻抗调节电路和控制器。其中，逆变电路用于将直流电源输出的直流电逆变为交流电，该逆变电路包括超前桥臂和滞后桥臂，其中同一个周期内所述超前桥臂的电压相位超前于所述滞后桥臂的电压相位。发射线圈用于接收交流电并产生交变磁场。超前和滞后桥臂阻抗调节电路分别包括至少一个可控电感支路或固定电感支路，每个可控电感支路包括至少一个电感和一个开关，固定电感支路包括至少一个电感，所有可控电感支路相互并联或串联，固定电感支路与可控电感支路并联，超前和滞后桥臂阻抗调节电路的第二端连接直流电源的输出端口，超前和滞后桥臂阻抗调节电路的第二端连接滞后桥臂的中点。
对于无线充电的发射装置的具体说明可参见上述的无线充电发射装置的实施例，在此不再赘述。
参见图8，无线充电发射装置的控制方法包括以下步骤：
S801：获得流入所述无线充电发射装置的补偿电路的电流；
S802:根据所述流入所述补偿电路的电流，控制所述无线充电发射装置的超前桥臂阻抗调节电路中可控电感支路的开关的导通或关断来改变流出所述无线充电发射装置的超前桥臂的电流，使所述超前桥臂的可控开关管实现零电压开关。
具体的，本申请实施例提供的无线充电发射装置的控制方法包括获得流入所述无线 充电发射装置的补偿电路的电流，具体为：
获得超前桥臂的可控开关管从关断时刻到开通时刻区间内由所述超前桥臂可控开关管的中点流入所述补偿电路的电流。
可选的，根据超前桥臂的可控开关管从关断时刻到开通时刻期间内流出所述超前桥臂的电流、以及所述超前桥臂阻抗调节电路电感支路的电流，获得流入所述补偿电路的电流。
可以理解的是，关断时刻为可控开关管从导通到关断所对应的时刻；开通时刻为可控开关管从关断到导通所对应的时刻。其中，实际操作中，开关管实际关断时刻和实际开通时刻会比控制器所发出关断时刻和开通时刻的信号多一个延迟时间。因此，本申请实施例从关断时刻到开通时刻的期间为包括信号延迟时间在内的从关断时刻到开通时刻的最长期间。
根据所述超前的可控开关管流入所述补偿电路的电流或者流出超前桥臂的电流，控制超前桥臂阻抗调节电路的电感支路中开关的导通或关断。
当控制器根据超前桥臂的可控开关管流入补偿电路的电流，控制电感支路中开关的导通或关断，具体为：
获得所述超前桥臂的可控开关管流入所述补偿电路的电流与预设电流的差值，根据所述差值控制所述可控电感支路中开关的导通和关断。
类似的，本申请实施例中所提供的无线充电发射装置的控制方法也适用于滞后桥臂，在此不再赘述。
可以参见图4所示的电路图，以流出超前和滞后桥臂的电流定义为正，S3关断的时刻为例分析，通过检测超前桥臂流出的电流，当超前桥臂流出的电流大于预设电流值(一般是一个小的负值)时，增加闭合的电感支路数目，即减小接入超前桥臂中点的电感值。类似的，通过检测超前桥臂流出的电流与预设电流值的差值，来控制滞后桥臂电感支路闭合的数目，以使滞后桥臂的可控开关管实现ZVS。
利用本申请提供的无线充电的控制方法，控制器用于控制超前和滞后桥臂阻抗调节电路中电感支路开关的导通或关断来改变流出所述超前和滞后桥臂的电流，通过控制导通的电感支路的数目，进而控制注入超前和滞后桥臂的电流大小，从而使所述超前和滞后桥臂的可控开关管实现ZVS。在需要向超前或滞后桥臂注入感性电流时，控制器才控制电感支路接入超前或滞后桥臂。当超前和滞后桥臂阻抗调节电路包括至少一个可控电感支路或至少一个固定电感支路时，控制器可以控制各个可控电感支路中开关通断以实现超前和滞后桥臂阻抗调节电路呈现的电感的大小不同，电感支路的电感大小不同，则向超前和滞后桥臂注入的感性电流大小不同。控制器切换电感支路的过程不影响无线充电发射装置的功率传输，提高了无线充电发射装置的稳定性与可靠性。
系统实施例：
基于上述实施例提供的无线充电的发射装置，本申请实施例还提供了一种无线充电系统，下面结合附图具体说明。
参见图9，该图为本申请实施例提供的一种无线充电系统的示意图。
该系统包括：无线充电接收装置200和无线充电接收装置2000。
其中，无线充电发射装置200可以为上述装置实施例提供的任一种，无线充电发射装置200至少包括：逆变电路201、发射线圈202、阻抗调节电路203和控制器204。
无线充电接收装置2000用于接收所述无线充电发射装置发射的交变磁场，并将所述交变磁场转换为直流电提供为用电设备，具体包括：线圈2001，整流器2002和用电设备2003。
逆变电路201将直流电源205输出的直流电逆变为交流电，逆变电路201包括超前桥臂和滞后桥臂，超前桥臂的电压相位超前于滞后桥臂的电压相位。
发射线圈202将交流电以交变磁场的形式进行发射。
阻抗调节电路203包括超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路，所述超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路分别包括至少一个电感支路，其中电感支路包括可控电感支路和固定电感支路，每个电感支路包括至少一个电感和至少一个开关，每个固定电感支路包括至少一个无开关控制的电感，其中超前桥臂阻抗调节电路的各电感支路之间相互并联或串联，滞后桥臂阻抗调节电路的各电感支路之间也相互并联或串联，超前和滞后桥臂阻抗调节电路的第一端分别连接直流电源205的输出端口，超前和滞后桥臂阻抗调节电路的第二端分别连接超前和滞后桥臂的中点。通过将超前和滞后桥臂阻抗调节电路分别与超前和滞后桥臂的中点连接，能够为超前和滞后桥臂注入感性电流，增大超前和滞后桥臂的感性电流成分。
控制器204可以控制电感支路中开关的导通或关断来改变流出所述超前和滞后桥臂的电流，以使超前和滞后桥臂的可控开关管实现ZVS。
接收线圈2001以交变磁场的形式接收发射线圈202发射的电磁能量。
整流器2002将接收线圈2001输出的交流电整流为直流电输出给用电设备。
该无线充电系统的无线充电发射装置添加了超前桥臂和滞后桥臂阻抗调节电路和控制器，其中超前桥臂和滞后桥臂阻抗调节电路分别包括至少一个可控电感支路和至少一个固定电感支路，每个可控电感支路包括至少一个电感和一个开关，每个固定电感支路包括至少一个无开关控制的电感，所有可控电感支路之间相互并联或串联，所述固定电感支路与可控电感支路并联后形成超前桥臂和滞后桥臂阻抗调节电路，超前桥臂和滞后桥臂阻抗调节电路的第一端连接直流电源的输出端口，超前桥臂和滞后桥臂阻抗调节电路的第二端分别连接超前和滞后桥臂的中点，在需要时可为超前和滞后桥臂注入感性电流，增大超前和滞后桥臂的感性电流成分。当超前或滞后桥臂的可控开关管关断时刻流入补偿电路的电流小于预设电流时，逆变电路自身可以实现可控开关管的ZVS，当超前或滞后桥臂的可控开关管关断时刻流入补偿电路的电流大于预设电流时，，逆变电路自身无法实现可控开关管的ZVS，因此，需要采取措施使其可控开关管实现ZVS。本申请实施例提供的无线充电发射装置是通过向超前或滞后桥臂注入感性电流，控制接入超前或滞后桥臂电感支路的数目以使无线充电发射装置的超前和滞后桥臂可控开关管实现ZVS。可以理解的是，所述关断时刻为可控开关管从导通到关断所对应的时刻；开通时刻为可控开关管从关断到导通所对应的时刻。其中，实际操作中，开关管实际关断时刻和实际开通时刻会比控制器所发出关断时刻和开通时刻的信号多一个延迟时间。因此，本申请实施例从关断时刻到开通时刻的期间为包括信号延迟时间在内的从关断时刻到开通时刻的最长期间。
当超前和滞后桥臂阻抗调节电路包括一个可控电感支路时，控制器可以根据流入补偿电路的电流与预设电流的差值，控制该电感支路的开关闭合时该电感支路接入超前或滞后桥臂的中点，进而控制向超前或滞后桥臂注入感性电流。当超前和滞后桥臂阻抗调节电路包括一个可控电感支路和至少一个固定电感支路时，控制器可以根据流入补偿电路的电流和固定电感支路电流之和与预设电流的差值，控制可控电感支路的开关闭合时所述可控电感支路接入超前或滞后桥臂的中点，进而控制向超前或滞后桥臂注入感性电流。
当超前和滞后桥臂阻抗调节电路包括多个电感支路时，所述电感支路包括可控电感支路和固定电感支路，控制器根据超前和滞后桥臂的可控开关管观点时刻流出超前和滞后桥臂的电流与当前的所述超前和滞后桥臂阻抗调节电路可控电感支路的闭合数目及固定电感支路的数目以获得当前所述超前和滞后桥臂阻抗调节电路电感支路的电流，从而获得流入所述补偿电路的电流，可以控制各个电感支路中开关的不同通断组合实现阻抗调节电路呈现的电感的大小，阻抗调节电路的电感大小不同，则向超前或滞后桥臂注入的感性电流大小不同。当流入所述补偿电路的电流和固定电感支路电流之和大于预设电流时，针对不同的差值，控制器可以通过控制各个电感支路中开关通断以实现阻抗调节电路呈现的电感的大小，进而控制向超前和滞后桥臂注入的感性电流大小，从而实现注入的电感电流刚好弥补差值，避免接入的电感量太大，而增加功耗。控制器切换电感支路的过程不影响无线充电发射装置的功率传输，提高了无线充电发射装置的稳定性与可靠性。
可以理解的是，阻抗调节电路还可以包括至少一个隔直电容与电源输出端连接，能够滤除调节支路中的直流电成分，还降低等效串联电阻的损耗，减小滞后桥臂中的电流有效值增加量，降低了超前和滞后桥臂中可控开关管的导通损耗以及开关损耗。
可以理解的是，至少一个可控电感支路中包括第一二极管和第二二极管以形成二极管箝位电路。
设备实施例：
基于上述实施例提供的无线充电发射装置以及控制方法，本申请实施例还提供了一种用电设备，下面结合附图具体说明。
参见图10，该图为本申请实施例提供的一种用电设备的示意图。
该用电设备2100包括：耗电元件2101、电池2102以及无线充电接收装置2000。
所述无线充电接收装置2000，用于接收无线充电发射装置200发射的交变磁场，还用于将所述交变磁场转换为直流电为所述电池2102进行充电。
所述电池2102，用于为所述耗电元件2101供电。
该用电设备可以为图2a所示的电动汽车，用电设备利用本申请提供的无线充电发射装置进行无线充电，由于该无线充电发射装置能够在不同的流入补偿电路的电流下实现ZVS，同时可以在线(带电)调节注入超前或者滞后桥臂感性电流以适应不同的耦合系数、输出电压、输出电流及目标功率等条件，避免在调节注入感性电流时中断无线充电发射装置的功率传输，提高用电设备在无线充电过程中的稳定性与安全性。
上述实施例中的“第一”和“第二”等词语仅是为了方便解释说明，并不构成对于本申请的限定。
应当理解，在本申请中，“至少一个(项)”是指一个或者多个，“多个”是指两个或两个以上。“和/或”，用于描述关联对象的关联关系，表示可以存在三种关系，例如，“A和/或B”可以表示：只存在A，只存在B以及同时存在A和B三种情况，其中A，B可以是单数或者复数。字符“/”一般表示前后关联对象是一种“或”的关系。“以下至少一项(个)”或其类似表达，是指这些项中的任意组合，包括单项(个)或复数项(个)的任意组合。例如，a，b或c中的至少一项(个)，可以表示：a，b，c，“a和b”，“a和c”，“b和c”，或“a和b和c”，其中a，b，c可以是单个，也可以是多个。

Claims (21)

  1. 一种无线充电发射装置，其特征在于，包括：逆变电路，补偿电路，发射线圈，阻抗调节电路，和控制器；
    所述逆变电路，用于将输入直流电转变为交流电，所述逆变电路包括超前桥臂和滞后桥臂，其中同一个周期内所述超前桥臂的电压相位超前于所述滞后桥臂的电压相位，所述超前桥臂和所述滞后桥臂分别包括可控开关管；
    所述补偿电路，用于将所述交流电进行补偿后发送给所述发射线圈；
    所述发射线圈，用于将所述补偿电路输出的交流电通过交变磁场形式进行发射；
    所述阻抗调节电路包括超前桥臂阻抗调节电路和滞后桥臂阻抗调节电路；
    所述超前桥臂阻抗调节电路第一端连接所述超前桥臂的可控开关管；
    所述滞后桥臂阻抗调节电路第一端连接所述滞后桥臂的可控开关管；
    所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路分别包括电感支路，所述电感支路包括至少一个可控电感支路，每个所述可控电感支路包括至少一个电感和至少一个开关；
    所述控制器，通过控制所述超前桥臂阻抗调节电路中所述可控电感支路的开关的导通或关断，对流入所述超前桥臂的感性电流的大小进行调节，使所述超前桥臂的可控开关管实现零电压开关；
    通过控制所述滞后桥臂阻抗调节电路中所述可控电感支路的开关的导通或关断，对流入滞后桥臂的感性电流的大小进行调节，使所述滞后桥臂的可控开关管实现零电压开关。
  2. 根据权利要求1所述的装置，其特征在于，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的电感支路还分别包括至少一个固定电感支路，所述固定电感支路包括至少一个电感。
  3. 根据权利要求1或2所述的装置，其特征在于，所述超前桥臂和所述滞后桥臂的可控开关管各包括两个上、下开关管，所述超前桥臂阻抗调节电路第一端连接所述超前桥臂的两个上、下开关管的中点；所述滞后桥臂阻抗调节电路的第一端连接所述滞后桥臂的两个上、下开关管的中点，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的第二端分别与电源的正母线、负母线或母线中点中的一个相连接。
  4. 根据权利要求3所述的装置，其特征在于，所述阻抗调节电路还包括至少一个隔直电容，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的第二端分别通过所述隔直电容与电源的正母线、负母线或母线中点中的一个相连接。
  5. 根据权利要求3所述的装置，其特征在于，所述阻抗调节电路还包括至少一个第一隔直电容和至少一个第二隔直电容，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的第二端分别通过所述至少一个第一隔直电容与电源的正母线相连接，通过所述至少一个第二隔直电容与电源的负母线相连接。
  6. 根据权利要求3所述的装置，其特征在于，所述阻抗调节电路还包括至少一个第一隔直电容、至少一个第二隔直电容和至少一个第三隔直电容，所述超前桥臂阻抗调节电路和所述滞后桥臂阻抗调节电路的第二端分别与所述至少一个第一隔直电容的第一端相连，所述至少一个第一隔直电容的第二端通过所述至少一个第二隔直电容与电源的正母线相连接，所述至少一个第一隔直电容的第二端通过所述至少一个第三隔直电容与电源的负母线相连接。
  7. 根据权利要求3所述的装置，其特征在于，所述超前桥臂阻抗调节电路还包括至少一个隔直电容，所述超前桥臂阻抗调节电路的电感支路通过所述至少一个隔直电容与电源的正母线、负母线或母线中点中的一个相连接。
  8. 根据权利要求3所述的装置，其特征在于，所述超前桥臂阻抗调节电路还包括至少一个第一隔直电容和至少一个第二隔直电容，所述超前桥臂阻抗调节电路的电感支路通过所述至少一个第一隔直电容与电源的正母线相连接，通过所述至少一个第二隔直电容与电源的负母线相连接。
  9. 根据权利要求3所述的装置，其特征在于，所述超前桥臂阻抗调节电路还包括至少一个第一隔直电容、至少一个第二隔直电容和至少一个第三隔直电容，所述超前桥臂阻抗调节电路的电感支路通过所述至少一个第一隔直电容、所述至少一个第二隔直电容与电源的正母线相连接，所述超前桥臂阻抗调节电路的电感支路通过所述至少一个第一隔直电容、所述至少一个第三隔直电容与电源的负母线相连接。
  10. 根据权利要求1-9任一项所述的装置，其特征在于，所述补偿电路包括LCC，或LCL。
  11. 根据权利要求1-10任一项所述的装置，其特征在于，所述超前桥臂阻抗调节电路还包括至少一个二极管箝位电路，所述超前桥臂阻抗调节电路的所述可控电感支路与所述超前桥臂阻抗调节电路的所述至少一个二极管箝位电路相连，所述超前桥臂阻抗调节电路的二极管箝位电路包括第一二极管和第二二极管，所述超前桥臂阻抗调节电路的可控电感支路中的电感和开关的连接点与所述第一二极管的阳极、所述第二二极管的阴极分别连接。
  12. 根据权利要求1-11任一项所述的装置，其特征在于，所述滞后桥臂阻抗调节电路还包括至少一个二极管箝位电路，所述滞后桥臂阻抗调节电路的所述可控电感支路与所述滞后桥臂阻抗调节电路的所述至少一个二极管箝位电路相连，所述滞后桥臂阻抗调节电路的二极管箝位电路包括第三二极管和第四二极管，所述滞后桥臂阻抗调节电路的可控电感支路中的电感和开关的连接点与所述第三二极管的阳极、所述第四二极管的阴极分别连接。
  13. 根据权利要求1-12任一项所述的装置，其特征在于，所述控制器用于获得流入 所述补偿电路的电流；根据所述流入所述补偿电路的电流，控制所述无线充电发射装置的超前桥臂阻抗调节电路中可控电感支路的开关的导通或关断来改变流出所述无线充电发射装置的超前桥臂的电流，使所述超前桥臂的可控开关管实现零电压开关。
  14. 根据权利要求13所述的装置，其特征在于，所述控制器用于：
    获得流入所述补偿电路的电流与预设电流的差值，根据所述差值控制所述超前桥臂阻抗调节电路中的电感支路中开关的导通或关断。
  15. 根据权利要求13或14所述的装置，其特征在于，所述控制器用于：
    获得超前桥臂的可控开关管关断时刻到实际开通时刻期间内由所述超前桥臂可控开关管的中点流入所述补偿电路的电流。
  16. 根据权利要求13或14所述的装置，其特征在于，所述控制器用于：
    根据所述超前桥臂的可控开关管关断时刻到实际开通时刻期间内流出所述超前桥臂的电流、以及所述超前桥臂阻抗调节电路电感支路的电流，获得流入所述补偿电路的电流。
  17. 一种无线充电发射装置的控制方法，其特征在于，所述方法包括：
    获得流入所述无线充电发射装置的补偿电路的电流；
    根据所述流入所述补偿电路的电流，控制所述无线充电发射装置的超前桥臂阻抗调节电路中可控电感支路的开关的导通或关断来改变流出所述无线充电发射装置的超前桥臂的电流，使所述超前桥臂的可控开关管实现零电压开关。
  18. 根据权利要求17所述的控制方法，其特征在于，所述方法包括：
    获得流入所述补偿电路的电流与预设电流的差值，根据所述差值控制所述超前桥臂阻抗调节电路中的电感支路中开关的导通或关断。
  19. 根据权利要求17或18所述的控制方法，其特征在于，所述方法包括：
    获得超前桥臂的可控开关管从关断时刻到实际开通时刻期间内由所述超前桥臂可控开关管的中点流入所述补偿电路的电流。
  20. 根据权利要求17或18所述的控制方法，其特征在于，所述方法包括：
    根据所述超前桥臂的可控开关管从关断时刻到开通时刻期间内流出所述超前桥臂的电流、以及所述超前桥臂阻抗调节电路电感支路的电流，获得流入所述补偿电路的电流。
  21. 一种无线充电系统，其特征在于，包括无线充电接收装置和如权利要求1-16任一项所述的无线充电发射装置；所述无线充电接收装置用于接收所述无线充电发射装置发射的交变磁场，并将所述交变磁场转换为直流电提供给用电设备。
PCT/CN2020/108554 2019-08-12 2020-08-12 一种无线充电发射装置，发射方法及无线充电系统 WO2021027823A1 (zh)

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