WO2020228402A1 - 一种滤波功分移相一体化的天线阵列馈电网络 - Google Patents

一种滤波功分移相一体化的天线阵列馈电网络 Download PDF

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Publication number
WO2020228402A1
WO2020228402A1 PCT/CN2020/078706 CN2020078706W WO2020228402A1 WO 2020228402 A1 WO2020228402 A1 WO 2020228402A1 CN 2020078706 W CN2020078706 W CN 2020078706W WO 2020228402 A1 WO2020228402 A1 WO 2020228402A1
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Prior art keywords
phase
shifting
filtering
antenna array
feed network
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PCT/CN2020/078706
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English (en)
French (fr)
Inventor
章秀银
詹万里
徐金旭
曹云飞
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South China University of Technology SCUT
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South China University of Technology SCUT
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Priority to US17/262,759 priority Critical patent/US11450951B2/en
Publication of WO2020228402A1 publication Critical patent/WO2020228402A1/zh
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H01Q21/0075—Stripline fed arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/32—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by mechanical means

Definitions

  • the antenna feed network is usually composed of passive components such as power splitters, phase shifters, and couplers. It is used in an antenna system with multiple radiating units to meet the amplitude distribution and phase distribution required by each radiating unit. In addition to the feed network, the antenna needs to be cascaded with a filter to filter out other unnecessary signals and avoid interference.
  • the power divider, phase shifter, and filter are all independently designed, and the power divider and phase shifter are cascaded to form a feed network, and then cascaded with the filter.
  • Such an approach will bring an inevitable cascade mismatch problem, resulting in an increase in the overall circuit insertion loss, performance degradation, and a larger circuit volume.
  • the antenna needs to take into account co-frequency interference and optimal coverage.
  • the amplitude distribution and phase distribution of each output of the feed network need to be optimized. Among them, the adjustment of the phase distribution is more important, in order to better meet the antenna beam
  • the phase distribution required for shaping electric downtilt, the feed network can flexibly adjust the phase difference of each output signal, which will have better applicability.
  • the present invention provides an antenna array feed network integrated with filtering power division and phase shifting, avoiding the problem of cascade mismatch between circuits with different functions in conventional designs, reducing circuit insertion loss and Volume, improve overall performance.
  • the phase modulation medium substrate by moving the position of the phase modulation medium substrate, the phase difference of the signal between the output ports can be conveniently controlled to meet the phase distribution requirements required by the antenna radiation unit.
  • An antenna array feed network integrated with filtering power division and phase shifting, including upper and lower metal floors, metal connection columns, coaxial feed ports, suspended dielectric substrates, suspended strip lines and two phase modulation dielectric substrates ;
  • the upper and lower metal floors are grounded by metal connecting posts, the suspended strip line is arranged on a suspended dielectric substrate, and the suspended dielectric substrate is placed horizontally between two phase modulating dielectric substrates.
  • the phase modulation medium substrate is placed horizontally between the upper and lower metal floors;
  • the suspended stripline includes a one-to-three filtering power dividing unit, two one-to-two unequal filtering power dividing units, two phase-shifting lines one and two phase-shifting lines two, the two phase modulation media
  • the substrate covers part of the one-to-three filter power dividing unit and two phase-shifting lines one and two phase-shifting lines two.
  • the two one-to-two unequal filtering power dividing units are symmetrically arranged on both sides of the one-to-three filtering power dividing unit, and three output terminals of the one-to-three filtering power dividing unit output equal amplitude and in-phase signals, wherein The two output terminals are respectively connected to the phase-shifting wires located on both sides, and the other output terminal is connected to the coaxial feed port;
  • the input end of the one-to-two filter power dividing unit is connected to the phase-shifting line 1, and the two output ends output in-phase unequal amplitude signals, which are respectively connected to the phase-shifting line two and the coaxial feed port.
  • the matching impedance of the three output ends of the one-to-three filter power dividing unit is 50 ohms.
  • the matching impedance of the input end of the one-to-two filter power dividing unit is the characteristic impedance corresponding to the phase-shifting line one without covering the phase-modulation medium substrate, and the matching impedance of the output end connected to the coaxial feed port is 50 ohms, and the other
  • the matching impedance of the output end is the characteristic impedance corresponding to the area of the phase-shifting line 2 not covering the substrate of the phase-modulating medium.
  • the two ends of the phase modulation dielectric substrate are provided with two spaced rectangular grooves, as a matching unit, by adjusting the width and spacing of the rectangular grooves, the phase shifting line 1 and the phase shifting line 2 are not covered or covered with the phase modulation dielectric substrate. It corresponds to the matching between the two characteristic impedances.
  • the line width of the phase shifting line 1 and the phase shifting line 2 is set to the width corresponding to the characteristic impedance of 50 ohms when being covered by the phase modulation dielectric substrate.
  • the one-to-three filtering power dividing unit implements the filtering function by four open-circuit branch loading structures
  • the one-to-two unequal filtering power dividing unit implements the filtering function by three open-circuit branch loading structures.
  • coaxial feed ports and metal connecting posts there are six coaxial feed ports and metal connecting posts, and the coaxial feed ports include coaxial lines, and the coaxial lines weld inner conductors on the circuit of the suspended dielectric substrate through the through holes of the metal connecting posts, The outer conductor is in contact with the metal connecting post to realize grounding.
  • the feed network realizes three functions of filtering, power division and phase shifting at the same time.
  • the three functional circuits of filtering, power division and phase shifting are integratedly designed. Compared with the conventional method of designing different functional circuits independently and then cascading, it avoids the problem of cascade mismatch and reduces circuit insertion loss. Improve the overall performance, while the circuit volume can be reduced.
  • phase modulation medium substrate By moving the position of the phase modulation medium substrate, the phase difference between the different output ports of the feed network can be conveniently controlled to meet the phase distribution requirements of the antenna beamforming ESC downtilt.
  • Figure 1 is a schematic diagram of the three-dimensional structure of the present invention.
  • FIG. 2 is a schematic diagram of the present invention
  • Figure 3 is a top view of the present invention.
  • Fig. 4a is a dimension drawing of a one-to-three filter power dividing unit of the feeder network of the present invention
  • Fig. 4b is a dimensioning drawing of the one-to-two unequal filtering power dividing unit of the feed network of the present invention
  • phase modulation dielectric substrate of the feed network of the present invention is a dimension drawing of the phase modulation dielectric substrate of the feed network of the present invention.
  • Figure 5 is a graph of frequency response characteristics of the feeder network of the present invention.
  • Figure 6a is the phase difference between the output signals of P3 and P5 when the phase modulation medium substrate of the feed network of the present invention moves to the right;
  • Figure 6b shows the phase difference between the output signals of P4 and P6 when the phase modulation medium substrate of the feed network of the present invention moves to the right.
  • an antenna array feed network integrated with filtering power division and phase shifting includes upper and lower metal floors 1, six metal connecting posts 2, coaxial feed ports 3, and suspended dielectric substrates 4, Suspended strip line 5 and two phase-modulating dielectric substrates 6; the structural dimensions of the two phase-modulating dielectric substrates are the same.
  • the upper and lower metal floors and the suspended dielectric substrates have the same center points. On a straight line.
  • FIG. 2 shows the principle block diagram of the integrated design of the feeder network of the present invention.
  • the conventionally designed feeder network is composed of individually designed filters, power dividers and phase shifters in cascade, and there is an inevitable cascade loss in the circuit.
  • the present invention integrates multiple devices into a single device to realize the original function, improves the overall performance of the circuit, and reduces the circuit volume at the same time.
  • the upper and lower metal floors realize common grounding through six metal connecting posts arranged between the two metal floors, the six metal connecting posts are arranged in a line, and the upper and lower metal floors are placed horizontally.
  • the implementation of the six coaxial feed ports P1-P6 is that the inner conductor of the coaxial line is welded to the circuit of the suspension dielectric substrate through the through hole of the metal connecting column, and the outer conductor is in contact with the metal connecting column to achieve grounding .
  • the two phase modulation medium substrates are placed horizontally between two layers of dielectric substrates, the suspension medium substrate is placed between the two phase modulation medium substrates, and the suspension strip line is printed on the suspension medium.
  • the suspended strip line is printed on the suspended dielectric substrate, and includes a one-to-three filter power dividing unit, two one-to-two unequal filtering power dividing units, two phase shifting lines, one or two shifting units.
  • Phase line two the one-to-three filtering power dividing unit is located in the middle position, and other circuits are symmetrically arranged on both sides of the one-to-three filtering power dividing unit, and the two phase modulation dielectric substrates cover the one-to-three filtering power dividing unit and Partial area of two phase-shift lines one and two phase-shift lines two.
  • Two spaced rectangular grooves are provided at both ends of the two phase modulation dielectric substrates, which are used to change the characteristic impedance of the suspended strip line in the corresponding area.
  • the strip line corresponding to the rectangular groove is a high impedance line.
  • the strip line in the corresponding area is a low impedance line, and the three partial strip lines form a step impedance structure.
  • the matching unit 9 the electrical length of each part of the step impedance structure is changed by adjusting the width and spacing of the two rectangular slots , To achieve the matching between the two characteristic impedances corresponding to the phase shifting line 1 and the phase shifting line 2 when the phase shifting line is not covered and the phase modulation dielectric substrate is covered.
  • the phase-modulating dielectric substrate by moving the phase-modulating dielectric substrate, the area covered by the dielectric substrate by the left and right phase shifting lines 1 and 2 is changed, thereby changing the equivalent electrical lengths of the left and right phase shifting lines 1 and 2 to achieve output Different phase difference between ports.
  • the one-to-three filter power divider unit 7 realizes the filter function through four open-circuit branch loading structures.
  • the input end is connected to the coaxial feed port P1.
  • the three outputs are equal in amplitude and in phase, and are matched to 50 ohms at the same time.
  • One of the outputs is connected to the same The shaft feed port P2, the other two outputs are connected to one end of the two phase shifting lines-lps1.
  • the filtering function of the one-to-two unequal filtering power division unit 8 realizes the filtering function through three open-circuit branch loading structures, the two outputs are in phase, and the power ratio is -1.6dB: -5.1dB, and its input is connected To the other end of the phase-shifting line 1, the matching impedance is the characteristic impedance corresponding to the phase-shifting line 1 without covering the phase-modulation dielectric substrate.
  • One output is connected to the coaxial feed port P4 or P6, and the matching impedance is 50 ohms.
  • the matching impedance is the corresponding characteristic impedance when the second phase shift line is not covered with the phase modulation dielectric substrate.
  • the characteristic impedance is the width corresponding to 50 ohms.
  • the working frequency of the feeder network of the present invention is 1.4-2.7GHz
  • the thickness of the plate used in the processing of the suspended dielectric substrate is 0.2mm
  • the relative dielectric constant is 3.38
  • the tangent loss is 0.0027
  • the phase modulation dielectric substrate is processed
  • the thickness of the board used is 3.048mm
  • the relative dielectric constant is 2.94
  • the tangent loss is 0.0012
  • the distance between the upper and lower metal floors is 6.4mm.
  • the dimensions of the feed network are shown in Figure 3 to Figure 4a and Figure 4b.
  • the specific parameters are as follows:
  • FIG. 5 it is a graph of the frequency response characteristic of the feed network of the present invention.
  • the output signal amplitudes of port P3 and port P5 are basically the same in the passband frequency range
  • the output signal amplitudes of port P4 and port P6 are basically the same
  • the output signal amplitude imbalance is less than 1.5dB, except for the power distribution part, the circuit
  • the insertion loss is not more than 1.6dB.
  • the suppression level is greater than 40dB.
  • the circuit has high sideband roll-off characteristics and out-of-band suppression capabilities, and good filtering performance.
  • FIG 6a it is the phase difference between the output signals of port P3 and port P5 when the feeder network phase modulation medium substrate of the present invention moves to the right (moving distance is recorded as dm), and Figure 6b is the output signal of port P4 and port P6.
  • the phase difference between the output signals of port P3 and port P5 fluctuates within the passband frequency range to [-77.3°, -174.3°]
  • port P4 The phase difference of the output signal from port P6 fluctuates within the passband frequency range of [-37.7°, -90.9°]. Since the port P1 to the port P4 and the port P6 only pass through the phase shift line 1, and the port P1 to the port P3 and the port P5 pass through the phase shift line 1 and the phase shift line 2, due to symmetry, when the phase modulation dielectric substrate moves , The phase difference between the output signals of the port P3 and the port P5 is twice the phase difference of the output signals of the port P4 and the port P6, and the result basically conforms to this rule.
  • the antenna array feed network with integrated filtering power division and phase shifting proposed by the present invention integrates multiple functions of filtering, power division and phase shifting. Among them, by moving the position of the phase modulation dielectric substrate, It can easily control the phase difference of the signal between the output ports.
  • the circuit of the invention has multiple performance advantages such as low loss, high integration, small size, etc., and is suitable for many radio frequency systems.

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Abstract

本发明公开了一种滤波功分移相一体化的天线阵列馈电网络，包括上、下层金属地板、金属连接柱、同轴馈电端口、悬置介质基板、悬置带状线和两个调相介质基板；所述上、下层金属地板通过金属连接柱实现共地，所述悬置带状线设置在悬置介质基板上，悬置介质基板水平放置在两块调相介质基板之间，所述两块调相介质基板水平放置在上下层金属地板之间；所述悬置带状线包括一分三滤波功分单元、两个一分二不等分滤波功分单元、两个移相线一及两个移相线二，所述两个调相介质基板覆盖一分三滤波功分单元及两个移相线一及两个移相线二的部分区域。本发明将滤波、功分和移相三种功能电路进行了一体化设计，避免了常规设计不同功能电路间级联失配的问题。

Description

一种滤波功分移相一体化的天线阵列馈电网络 技术领域
本发明涉及无线通信系统中的天线馈电网络领域，尤其涉及一种滤波功分移相一体化的天线阵列馈电网络。
背景技术
天线馈电网络通常由功分器、移相器以及耦合器等无源器件构成，应用于具有多个辐射单元的天线系统中，满足各个辐射单元馈电所需的幅度分布和相位分布。除了馈电网络，天线还需与滤波器级联，滤除其他不必要的信号，避免干扰。
常规设计中，功分器、移相器和滤波器等器件都是独立设计，再由功分器和移相器等器件级联组成馈电网络，然后与滤波器级联。这样的做法会带来不可避免的级联失配问题，导致整体电路插入损耗增大，性能有所恶化，同时电路体积也较大。另外，天线需要兼顾同频干扰和最佳覆盖，波束赋形时需要通过优化调整馈电网络各个输出的幅度分布和相位分布，其中，相位分布的调整更为重要，为了更好地满足天线波束赋形电调下倾所需的相位分布，馈电网络能够灵活调整各个输出信号的相位差，会具有更好的适用性。
发明内容
为了克服现有技术存在的缺点与不足，本发明提供一种滤波功分移相一体化的天线阵列馈电网络，避免常规设计不同功能电路间级联失配的问题，减小电路插损以及体积，提升整体性能。另外，通过移动调相介质基板的位置，能够方便地控制输出端口之间信号的相位差，满足天线辐射单元所需的相位分布要求。
本发明的目的能够通过以下技术方案实现：
一种滤波功分移相一体化的天线阵列馈电网络，包括上、下层金属地板、金属连接柱、同轴馈电端口、悬置介质基板、悬置带状线和两个调相介质基板；
所述上、下层金属地板通过金属连接柱实现共地，所述悬置带状线设置在悬置介质基板上，悬置介质基板水平放置在两块调相介质基板之间，所述两块调相介质基板水平放置在上下层金属地板之间；
所述悬置带状线包括一分三滤波功分单元、两个一分二不等分滤波功分单元、两个移相线一及两个移相线二，所述两个调相介质基板覆盖一分三滤波功分单元及两个移相线一及两个移相线二的部分区域。
所述两个一分二不等分滤波功分单元对称设置在一分三滤波功分单元的两侧，所述一分三滤波功分单元的三个输出端输出等幅同相信号，其中两个输出端分别与位于两侧的移相线一连接，另外一个输出端与同轴馈电端口连接；
所述一分二滤波功分单元的输入端与移相线一连接，两个输出端输出同相不等幅信号，分别与移相线二及同轴馈电端口连接。
所述一分三滤波功分单元三个输出端匹配阻抗为50欧姆。
所述一分二滤波功分单元的输入端匹配阻抗为移相线一未覆盖调相介质基板时所对应的特性阻抗，连接到同轴馈电端口的输出端匹配阻抗为50欧姆，另一个输出端匹配阻抗为移相线二未覆盖调相介质基板区域所对应的特性阻抗。
所述调相介质基板的两端设置两个间隔分布的矩形槽，作为匹配单元，通过调整矩形槽的宽度以及间距，实现移相线一和移相线二未覆盖以及覆盖调相介质基板时所对应两个特性阻抗之间的匹配。
所述移相线一及移相线二的线宽设置为被调相介质基板覆盖时，特性阻抗50欧姆所对应的宽度。
所述一分三滤波功分单元由四个开路枝节加载结构实现滤波功能；
所述一分二不等分滤波功分单元由三个开路枝节加载结构实现滤波功能。
所述一分二不等分滤波功分单元的输出端功率比值为-1.6dB:-5.1dB。
所述同轴馈电端口及金属连接柱有六个，所述同轴馈电端口包括同轴线，同轴线通过金属连接柱的通孔将内导体焊接在悬置介质基板的电路上，其外导体与金属连接柱接触实现接地。
该馈电网络同时实现滤波、功分和移相三种功能。
本发明的有益效果：
1、将滤波、功分和移相三种功能电路进行一体化设计，相较于常规设计不同功能电路独立设计再级联的方法，避免了级联失配的问题，减小电路插损，提升整体性能，同时电路体积得以减小。
2、通过移动调相介质基板的位置，能够方便地控制馈电网络不同输出端口间的相位差，满足天线波束赋形电调下倾所需的相位分布要求。
附图说明
图1是本发明的立体结构示意图；
图2为本发明的原理图；
图3为本发明的俯视图；
图4a为本发明馈电网络一分三滤波功分单元的尺寸标注图；
图4b为本发明馈电网络一分二不等分滤波功分单元的尺寸标注图；
图4c为本发明馈电网络调相介质基板的尺寸标注图；
图5为本发明馈电网络频率响应特性曲线图；
图6a为本发明馈电网络调相介质基板向右移动时P3和P5输出信号之间的相位差；
图6b为本发明馈电网络调相介质基板向右移动时P4和P6输出信号之间的相位差。
具体实施方式
下面结合实施例及附图，对本发明作进一步地详细说明，但本发明的实施方式不限于此。
实施例
如图1所示,一种滤波功分移相一体化的天线阵列馈电网络，包括上、下层金属地板1、六个金属连接柱2、同轴馈电端口3、悬置介质基板4、悬置带状线5和两个调相介质基板6；两个调相介质基板的结构尺寸相同，本实施例中上下层金属地板，悬置介质基板，两个调相介质基板的中心点均在一条竖直直线上。
如图2所示为本发明馈电网络一体化设计的原理框图，常规设计的馈电网络由单独设计的滤波器、功分器和移相器级联组成，电路存在不可避免的级联失配问题，本发明将多个器件进行一体化设计成单个器件实现原有功能，提升电路整体性能，同时减小电路体积。
所述上下层金属地板通过设置在两层金属地板之间的六个金属连接柱实现共地，六个金属连接柱一字型排列，上下层金属地板水平放置。
所述六个同轴馈电端口P1-P6的实现方式为，同轴线通过金属连接柱的通孔将内导体焊接在悬置介质基板的电路上，其外导体与金属连接柱接触实现接地。
如图3所示，所述两个调相介质基板，水平放置在两层介质基板之间，悬置介质基板放在两个调相介质基板之间，悬置带状线印刷在悬置介质基板上， 所述悬置带状线印刷在悬置介质基板上，包括一分三滤波功分单元、两个一分二不等分滤波功分单元、两个移相线一、两个移相线二，所述一分三滤波功分单元位于中间位置，其他电路对称设置在一分三滤波功分单元的两侧，所述两个调相介质基板覆盖一分三滤波功分单元及两个移相线一及两个移相线二的部分区域。
两个调相介质基板的两端设置有两个间隔分布的矩形槽，用于改变对应区域悬置带状线的特性阻抗，其中，矩形槽对应区域带状线为高阻抗线，两个槽之间对应区域带状线为低阻抗线，三个部分带状线形成阶跃阻抗结构，作为匹配单元9，通过调节两个矩形槽的宽度以及间距，改变阶跃阻抗结构各部分的电长度，实现移相线一和移相线二未覆盖以及覆盖调相介质基板时所对应两个特性阻抗之间的匹配。同时，通过移动调相介质基板，改变左右两边移相线一和移相线二被介质基板所覆盖的范围，从而改变左右两边移相线一和移相线二的等效电长度，实现输出端口间不同的相位差。
一分三滤波功分单元7通过四个开路枝节加载结构实现滤波功能，输入端与同轴馈电端口P1连接，三个输出等幅同相，同时都匹配到50欧姆，其中一个输出连接到同轴馈电端口P2，另外两个输出连接到两个移相线一lps1的一端。
如图3所示，一分二不等分滤波功分单元8的滤波功能通过三个开路枝节加载结构实现滤波功能，两个输出同相，功率比值为-1.6dB:-5.1dB，其输入连接到移相线一的另一端，匹配阻抗为移相线一未覆盖调相介质基板时所对应的特性阻抗，其输出一个连接到同轴馈电端口P4或P6，匹配阻抗为50欧姆，另一个连接到移相线二lps2一端，移相线二lps2的另一端连接同轴馈电端口P3或P5，匹配阻抗为移相线二未覆盖调相介质基板时所对应的特性阻抗。其中，移相线一和移相线二的线宽设置为覆盖调相介质基板时，特性阻抗为50欧姆所对应的宽度。
在本实施例中，本发明馈电网络的工作频率为1.4-2.7GHz，悬置介质基板加工采用的板材厚度为0.2mm，相对介电常数为3.38，正切损耗为0.0027，调相介质基板加工采用的板材厚度为3.048mm，相对介电常数为2.94，正切损耗为0.0012，上下层金属地板之间的距离为6.4mm，馈电网路对应的各项尺寸标注如图3至图4a、图4b、图4c所示，具体参数如下：
w 0＝4.3mm,w 1＝1.4mm,w 2＝0.9mm,w 3＝0.7mm,w 4＝2.3mm,w 5＝3.8mm,w 6＝4.8mm,w 7＝1.2mm,w 8＝3.0mm,w 9＝2.6mm,w 10＝2.2mm,w 11＝2.5mm,w 12＝8.4mm,w 13＝2mm,w 14＝3.5mm,w 15＝6.6mm,w 16＝7.6mm,w s1＝2.8mm, w s2＝1.1mm,w s3＝2.4mm,w s4＝3mm,w s5＝3.3mm,w s6＝2.4mm,w s7＝3.8mm,w p＝9.2mm,l 0＝7mm，l 1＝6.6mm，l 2＝9.8mm，l 3＝8.6mm，l 4＝13.8mm，l 5＝2.9mm，l 6＝16mm，l 7＝15.2mm，l 8＝18.2mm，l 9＝7.8mm，l 10＝10.8mm，l 11＝6mm，l 12＝13.1mm，l 13＝26.6mm，l 14＝23.5mm，l 15＝30.2mm，l 16＝22.6mm，l s1＝8.2mm，l s2＝11.1mm，l s3＝11.3mm，l s4＝11.8mm，l s5＝17.4mm，l s6＝20.6mm，l s7＝17.3mm，l p＝4mm，l ps1＝119mm，l ps2＝105mm,l x＝256.4mm，l x1＝18mm,l x2＝10.8mm,l x3＝7.1mm，l y＝51mm，l y1＝36.1mm。
如图5所示，为本发明馈电网络频率响应特性曲线图，通带1.4-2.7GHz范围内，S 11小于-20dB，表明输入端口匹配良好。由于本实施例中一分二不等分滤波功分单元的功率比值为-1.6dB:-5.1dB，理想情况下，各个输出端口间信号功率比值为，S 21:S 31:S 41:S 51:S 61＝-4.77dB:-9.87dB:-6.37dB:-9.87dB:-6.37dB。由图5可发现，通带频率范围内端口P3和端口P5输出信号幅度基本相等，端口P4和端口P6输出信号幅度基本相等，输出信号幅度不平衡度小于1.5dB，，除去功率分配部分，电路插入损耗不大于1.6dB。带外3.38-5GHz频率范围内，抑制水平大于40dB，电路具有较高的边带滚降特性和带外抑制能力，滤波性能良好。
如图6a所示，为本发明馈电网络调相介质基板向右移动时(移动距离记为dm)端口P3和端口P5输出信号之间的相位差，图6b则是端口P4和端口P6输出信号之间的相位差，可以看到，当调相介质基板未移动时(dm＝0mm)，工作频率1.4-2.7GHz范围内，端口P3和端口P5输出信号基本同相，端口P4和端口P6输出信号基本同相。移动距离dm越大，输出信号间的相位差越大，当dm＝20mm时，端口P3和端口P5输出信号相位差在通带频率范围内波动为[-77.3°，-174.3°]，端口P4和端口P6输出信号相位差在通带频率范围内波动为[-37.7°，-90.9°]。由于从端口P1到端口P4和端口P6只经过移相线一，而从端口P1到端口P3和端口P5则经过移相线一和移相线二，由于对称性，当调相介质基板移动时，端口P3和端口P5输出信号相位差为端口P4和端口P6输出信号相位差的两倍，结果基本符合这一规律。
综上所述，本发明所提出的一种滤波功分移相一体化的天线阵列馈电网络，集成了滤波、功分和移相多种功能，其中，通过移动调相介质基板的位置，能够方便地控制输出端口之间信号的相位差。本发明电路具有损耗低、集成度高、体积小等多种性能优点，适用于许多射频系统中。
上述实施例为本发明较佳的实施方式，但本发明的实施方式并不受所述实施例的限制，其他的任何未背离本发明的精神实质与原理下所作的改变、修饰、 替代、组合、简化，均应为等效的置换方式，都包含在本发明的保护范围之内。

Claims (10)

  1. 一种滤波功分移相一体化的天线阵列馈电网络，其特征在于，包括上、下层金属地板、金属连接柱、同轴馈电端口、悬置介质基板、悬置带状线和两个调相介质基板；
    所述上、下层金属地板通过金属连接柱实现共地，所述悬置带状线设置在悬置介质基板上，悬置介质基板水平放置在两个调相介质基板之间，所述两个调相介质基板水平放置在上下层金属地板之间；
    所述悬置带状线包括一分三滤波功分单元、两个一分二不等分滤波功分单元、两个移相线一及两个移相线二，所述两个调相介质基板覆盖一分三滤波功分单元及两个移相线一及两个移相线二的部分区域。
  2. 根据权利要求1所述的天线阵列馈电网络，其特征在于，所述两个一分二不等分滤波功分单元对称设置在一分三滤波功分单元的两侧，所述一分三滤波功分单元的三个输出端输出等幅同相信号，其中两个输出端分别与位于两侧的移相线一连接，另外一个输出端与同轴馈电端口连接；
    所述一分二滤波功分单元的输入端与移相线一连接，两个输出端输出同相不等幅信号，分别与移相线二及同轴馈电端口连接。
  3. 根据权利要求2所述的天线阵列馈电网络，其特征在于，所述一分三滤波功分单元三个输出端匹配阻抗为50欧姆。
  4. 根据权利要求2所述的天线阵列馈电网络，其特征在于，
    一分二滤波功分单元的输入端匹配阻抗为移相线一未覆盖调相介质基板时所对应的特性阻抗，连接到同轴馈电端口的输出端匹配阻抗为50欧姆，另一个输出端匹配阻抗为移相线二未覆盖调相介质基板区域所对应的特性阻抗。
  5. 根据权利要求1所述的天线阵列馈电网络，其特征在于，所述调相介质基板的两端设置两个间隔分布的矩形槽，作为匹配单元，通过调整矩形槽的宽度以及间距，实现移相线一和移相线二未覆盖以及覆盖调相介质基板时所对应两个特性阻抗之间的匹配。
  6. 根据权利要求1所述的天线阵列馈电网络，其特征在于，所述移相线一及移相线二的线宽设置为被调相介质基板覆盖时，特性阻抗50欧姆所对应的宽度。
  7. 根据权利要求1所述的天线阵列馈电网络，其特征在于，所述一分三滤波功分单元由四个开路枝节加载结构实现滤波功能；
    所述一分二不等分滤波功分单元由三个开路枝节加载结构实现滤波功能。
  8. 根据权利要求1所述的天线阵列馈电网络，其特征在于，所述一分二不等分滤波功分单元的输出端功率比值为-1.6dB:-5.1dB。
  9. 根据权利要求1所述的天线阵列馈电网络，其特征在于，所述同轴馈电端口及金属连接柱有六个，所述同轴馈电端口包括同轴线，同轴线通过金属连接柱的通孔将内导体焊接在悬置介质基板的电路上，其外导体与金属连接柱接触实现接地。
  10. 根据权利要求1所述的天线阵列馈电网络，其特征在于，该馈电网络同时实现滤波、功分和移相三种功能。
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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US11450951B2 (en) 2019-05-10 2022-09-20 South China University Of Technology Filtering, power-dividing and phase-shifting integrated antenna array feed network
CN116154430A (zh) * 2021-11-22 2023-05-23 华为技术有限公司 移相器、基站天线以及基站
CN116759779A (zh) * 2023-08-22 2023-09-15 安徽蓝讯通信科技有限公司 一种5g毫米波滤波功分模块

Families Citing this family (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112736378B (zh) * 2020-12-01 2021-12-14 武汉虹信科技发展有限责任公司 一种滤波移相器及天线
CN113328217A (zh) * 2021-06-11 2021-08-31 京信通信技术(广州)有限公司 功分与移相一体化组件及基站天线
CN113871822B (zh) * 2021-11-02 2022-08-09 江苏亨鑫科技有限公司 一种输出模式可调的移相器以及天线
CN114284723B (zh) * 2021-12-28 2025-05-16 武汉凡谷电子技术股份有限公司 天线模块
CN115117616B (zh) * 2022-08-25 2022-12-02 成都国恒空间技术工程股份有限公司 一种基于rgw结构的victs天线
CN116315745B (zh) * 2023-05-11 2023-08-01 合肥联宝信息技术有限公司 一种紧凑型电子设备的天线系统和笔记本电脑

Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20040252059A1 (en) * 2001-02-14 2004-12-16 Zaghloul Amir I. Wide-band modular mems phased array
CN105591183A (zh) * 2016-03-22 2016-05-18 南京理工大学 基于平行耦合结构的反相不等分功分器
CN106602280A (zh) * 2016-08-09 2017-04-26 广东通宇通讯股份有限公司 滤波馈电网络及基站天线
CN107369899A (zh) * 2017-07-18 2017-11-21 华南理工大学 基于多模谐振器滤波天线阵列
CN109378592A (zh) * 2018-11-15 2019-02-22 华南理工大学 一种具有稳定波束宽度和低副瓣的宽带天线阵列馈电网络
CN110112572A (zh) * 2019-05-10 2019-08-09 华南理工大学 一种滤波功分移相一体化的天线阵列馈电网络
CN209929493U (zh) * 2019-05-10 2020-01-10 华南理工大学 一种滤波功分移相一体化的天线阵列馈电网络

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7916083B2 (en) * 2008-05-01 2011-03-29 Emag Technologies, Inc. Vertically integrated electronically steered phased array and method for packaging
WO2016205995A1 (zh) * 2015-06-23 2016-12-29 华为技术有限公司 移相器和天线
CN208256903U (zh) * 2018-04-13 2018-12-18 广东通宇通讯股份有限公司 一种高增益并馈式全向阵列天线

Patent Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20040252059A1 (en) * 2001-02-14 2004-12-16 Zaghloul Amir I. Wide-band modular mems phased array
CN105591183A (zh) * 2016-03-22 2016-05-18 南京理工大学 基于平行耦合结构的反相不等分功分器
CN106602280A (zh) * 2016-08-09 2017-04-26 广东通宇通讯股份有限公司 滤波馈电网络及基站天线
CN107369899A (zh) * 2017-07-18 2017-11-21 华南理工大学 基于多模谐振器滤波天线阵列
CN109378592A (zh) * 2018-11-15 2019-02-22 华南理工大学 一种具有稳定波束宽度和低副瓣的宽带天线阵列馈电网络
CN110112572A (zh) * 2019-05-10 2019-08-09 华南理工大学 一种滤波功分移相一体化的天线阵列馈电网络
CN209929493U (zh) * 2019-05-10 2020-01-10 华南理工大学 一种滤波功分移相一体化的天线阵列馈电网络

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US11450951B2 (en) 2019-05-10 2022-09-20 South China University Of Technology Filtering, power-dividing and phase-shifting integrated antenna array feed network
CN116154430A (zh) * 2021-11-22 2023-05-23 华为技术有限公司 移相器、基站天线以及基站
CN116759779A (zh) * 2023-08-22 2023-09-15 安徽蓝讯通信科技有限公司 一种5g毫米波滤波功分模块
CN116759779B (zh) * 2023-08-22 2023-11-10 安徽蓝讯通信科技有限公司 一种5g毫米波滤波功分模块

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