WO2020100189A1 - Power feeding circuit - Google Patents

Abstract

In a power feeding circuit (1), a first 90-degree coupler (31) generates, on the basis of first and second propagation modes input from adjacent branch waveguides (13A, 13B) of a polarization demultiplexer (10), first and second composite signals. A second 90-degree coupler (32) generates, on the basis of third and fourth propagation modes input from other adjacent branch waveguides (13C, 13D) of the polarization demultiplexer (10), third and fourth composite signals. A first 180-degree coupler (51) generates, by compositing signal components with mutually opposite phases among combinations of signal components of the first composite signal and the third composite signal, a first circularly polarized wave signal. A second 180-degree coupler (52) generates, by compositing signal components with mutually opposite phases among combinations of signal components of the second composite signal and the fourth composite signal, a second circularly polarized wave signal orthogonal to the first circularly polarized wave signal.

Description

Power supply circuit

The present invention relates to a power supply circuit having a function of separating a plurality of polarized waves in a frequency band such as a VHF (Very High Frequency) band, a UHF (Ultra High Frequency) band, a microwave band and a millimeter wave band.

In the field of satellite broadcasting and satellite communication, in order to realize the tracking function, a power supply circuit having a polarization separation function for separating a plurality of different polarization modes from each other is used. For example, the receiving antenna of the base station receives the radio wave from the transmitting antenna of the artificial satellite, separates multiple types of polarization modes included in the received radio wave, and uses these polarization modes of the receiving antenna of the base station. It may have a tracking function of tracking the artificial satellite by electronically or mechanically controlling the pointing direction. On the contrary, the receiving antenna of the artificial satellite receives the radio wave from the transmitting antenna of the base station, separates the plural types of polarization modes included in the received radio wave, and uses these polarization modes to receive the antenna of the artificial satellite. It may have a tracking function of tracking the base station by electronically or mechanically controlling the pointing direction of the.

The following non-patent document 1 discloses a waveguide type power supply circuit for realizing a tracking function based on a monopulse tracking method. This power supply circuit includes a turnstile type junction having a coaxial horn structure and four rectangular waveguides, a plurality of magic T type couplers (magic-T junctions), It is equipped with a 90-degree phase shifter (90 ° phase shifter). According to Non-Patent Document 1, the coaxial horn structure includes an inner horn and an outer horn that are coaxially arranged, and a relatively high frequency band (X band) in the inner space of the inner horn. Signal can be propagated, and a signal in a relatively low frequency band (S band) can be propagated in the space between the inner horn and the outer horn. Further, a 90-degree phase shifter and a magic T-type coupler are used to separate a plurality of different polarization modes.

As described above, the power supply circuit disclosed in Non-Patent Document 1 uses a 90-degree phase shifter and a magic T-type coupler to separate a plurality of different polarization modes. At the center frequency in the used frequency band, the amount of phase shift in the 90-degree phase shifter is 90 degrees, so the isolation characteristic (polarization separation characteristic) is good. However, since the amount of phase shift depends on the frequency, it is not always possible to obtain the amount of phase shift of 90 degrees in the frequency region outside the center frequency. Therefore, the power supply circuit disclosed in Non-Patent Document 1 has a problem that it is difficult to obtain good isolation characteristics in a wide band.

Further, the power supply circuit disclosed in Non-Patent Document 1 has an asymmetric structure due to the presence of the 90-degree phase shifter, so that an unnecessary space is generated in the power supply circuit, which makes it difficult to reduce the circuit size. There are challenges.

In view of the above, an object of the present invention is to provide a power supply circuit that can realize good isolation characteristics in a wide band and downsizing of circuit size without using a 90-degree phase shifter. .

A power supply circuit according to an aspect of the present invention includes a plurality of tubular conductors arranged coaxially, and a conductor formed between any two tubular conductors of the plurality of tubular conductors. A polarization demultiplexer having first to fourth branch waveguides that branch symmetrically with respect to the central axis of the plurality of tubular conductors from the wave space and the first to fourth branch waveguides are adjacent to each other. The delayed wave obtained by delaying the phase of the second propagation mode by 90 degrees by inputting the first propagation mode and the second propagation mode output from the first and second branch waveguides, respectively, and A first composite signal is generated by superimposing the first propagation mode and at the same time, a delayed wave obtained by delaying the phase of the first propagation mode by 90 degrees and the second propagation mode are superposed. A first 90-degree coupler that generates a second combined signal by combining them, and a third 90-degree coupler output from the adjacent third and fourth branch waveguides of the first to fourth branch waveguides, respectively. A third combined signal is obtained by superimposing a delayed wave obtained by delaying the phase of the fourth propagation mode by 90 degrees with the propagation mode and the fourth propagation mode as inputs, and the third propagation mode. A second 90-degree coupler that generates a fourth combined signal by superimposing a delayed wave obtained by delaying the phase of the third propagation mode by 90 degrees at the same time as generating the fourth synthesized signal. And inputting the first combined signal and the third combined signal, the signal components having mutually opposite phases in the combination of the signal component of the first combined signal and the signal component of the third combined signal are input. A first 180-degree coupler that outputs a first circularly polarized wave signal from a first output terminal by combining, a second combined signal, and a fourth combined signal are input, and the second combined signal is input. A second circularly polarized signal that is orthogonal to the first circularly polarized signal by synthesizing signal components having opposite phases from each other in a combination of the signal component of the signal and the signal component of the fourth combined signal. And a second 180-degree coupler for outputting from the second output terminal.

The power supply circuit according to one aspect of the present invention can achieve good isolation characteristics in a wide band and miniaturization of circuit size without using a 90-degree phase shifter.

It is a figure which shows roughly the structure of the electric power feeding circuit 1 of Embodiment 1 which concerns on this invention. It is a figure which shows schematic structure of the polarization splitter of Embodiment 1. FIG. 6 is a schematic diagram for explaining the operation of the 90-degree coupler and the 180-degree coupler of the first embodiment. It is a figure for explaining a method of generating a right-handed circularly polarized signal. It is a figure for demonstrating the method of generating a left-handed circularly polarized signal. It is a figure for explaining a method of generating a coaxial TEM mode. It is a perspective view which shows the specific structural example of the electric power feeding circuit of Embodiment 2 which concerns on this invention. It is a top view of the electric power feeding circuit shown in FIG. FIG. 6 is a perspective view of a polarization splitter according to the second embodiment. FIG. 10 is a schematic view showing a cross-sectional structure taken along the line A1-A1 of the demultiplexer shown in FIG. 9. FIG. 7 is a perspective view showing a configuration of a waveguide including a bent waveguide according to the second embodiment. FIG. 7 is a perspective view of an H-plane cross coupler which constitutes the 90-degree coupler of the second embodiment. FIG. 9 is a perspective view of a magic T circuit that constitutes the 180-degree coupler of the second embodiment. 9 is a graph showing a calculation result of isolation characteristics of the power feeding circuit according to the second embodiment. It is a schematic sectional drawing of 10 A of demultiplexers of a triple cylinder structure. It is a figure which shows the structural example of a short slot coupler. It is a figure which shows the structural example of the hybrid coupler which has a branch line coupler and a twist waveguide. It is a figure which shows schematic structure of the polarization splitter and bending waveguide of Embodiment 3 which concerns on this invention. FIG. 19 is a top view of and the bending waveguide of the polarization splitter shown in FIG. 18. 7 is a graph showing the reflection characteristic of the power supply circuit according to the second embodiment. 9 is a graph showing a reflection characteristic of the power supply circuit according to the third embodiment. FIG. 7 is a diagram schematically showing a configuration of a power supply circuit according to a modified example of the first embodiment.

Hereinafter, various embodiments according to the present invention will be described in detail with reference to the drawings.

Embodiment 1.
1 is a diagram schematically showing a configuration of a power supply circuit 1 according to a first embodiment of the present invention. The feeding circuit 1 includes a coaxial TEM (Transverse Electric and Magnetic) mode, a left-hand circularly polarized signal included in a wideband signal input from an antenna input / output terminal 100 of a multi-frequency shared antenna (not shown) such as a horn antenna. And functions as a polarization separation circuit capable of separating a right-handed circularly polarized signal. Examples of the frequency band used by the power feeding circuit 1 include the VHF band, the UHF band, the microwave band, and the millimeter wave band.

As shown in FIG. 1, the feeding circuit 1 includes a polarization splitter 10 having an antenna-side terminal connected to an antenna input / output terminal 100, a 90-degree coupler (first and second 90-degree couplers) 31, 32, 180-degree couplers (first and second 180-degree couplers) 51 and 52, waveguides 21 and 22 coupling between the demultiplexer 10 and the 90-degree coupler 31, and the demultiplexer 10. And the 90-degree coupler 32, the waveguides 23 and 24, the 90-degree coupler 31 and the 180- degree couplers 51 and 52, and the 90-degree coupler 32 and the 180-degree coupler. The waveguides 43 and 44 for coupling between 51 and 52 are provided.

The demultiplexer 10 has a multi-cylinder structure. That is, the demultiplexer 10 includes two tubular conductors 11 and 12 arranged coaxially and a waveguide space formed between the tubular conductors 11 and 12, and It has four branching waveguides 13A, 13B, 13C and 13D which branch symmetrically with respect to the central axis of. The antenna-side terminal of the demultiplexer 10 includes an input / output end 10p of the inner waveguide space of the tubular conductor 11 and an input / output end 10q of the waveguide space formed between the tubular conductors 11 and 12. To be done. In the inner waveguide space of the cylindrical conductor 11, a signal in a relatively high frequency band (hereinafter referred to as “high frequency band”) such as the X band in the broadband signal input to the input / output terminal 10p is used as the waveguide mode. The waveguide space that is configured to propagate and is formed between the cylindrical conductors 11 and 12 has a relatively low frequency band (such as the S band) in the wideband signal input to the annular input / output terminal 10q ( Hereinafter, it will be referred to as a "low frequency band"). A specific structural example of such a demultiplexer 10 will be described later.

In addition, in the example of FIG. 1, the demultiplexer 10 has a double cylinder structure, but the invention is not limited to this. It has three or more tubular conductors arranged coaxially, and the branch waveguides 13A to 13D branch from the waveguide space formed between any two of these tubular conductors. Such a configuration may be adopted.

Referring to FIG. 1, the signal propagating in the inner waveguide space of the tubular conductor 11 is output from the high frequency band terminal (not shown) to the high frequency band polarization separation circuit 60. The high frequency band polarization separation circuit 60 separates the polarization signal input to the high frequency band terminal and outputs it from the input / output terminals 60a and 60b. In order to realize the tracking function, the high frequency band polarization separation circuit 60 includes a plurality of different types of polarization signals (for example, TM01 mode or TE21 mode, or a combination of these, which are included in the signal input to the high frequency band terminal. You may have the structure which isolate | separates each) separately. The configuration of such a high frequency band polarization separation circuit 60 can be configured using, for example, a waveguide structure, but is not particularly limited.

On the other hand, the signal propagated in the waveguide space formed between the cylindrical conductors 11 and 12 as a coaxial mode is input to the branch waveguides 13A, 13B, 13C and 13D. FIG. 2 is a diagram showing a schematic configuration of the polarization splitter 10. The wideband signal input to the input / output terminal 10q may include right-hand circular polarization, left-hand circular polarization, and coaxial TEM mode. The demultiplexer 10 converts the right-hand circularly polarized wave, the left-hand circularly polarized wave, and the coaxial TEM mode into the propagation modes of the branch waveguides 13A, 13B, 13C, and 13D according to the phase relationship shown in FIG.

Specifically, as shown in FIG. 2, when the phase state of the propagation mode of the branch waveguide 13A is used as a reference, that is, in the propagation mode of the branch waveguide 13A, a signal corresponding to right-handed circular polarization. The phase of the component is 0 °, the phase of the signal component corresponding to the left-hand circularly polarized wave is 0 °, and the phase of the signal component corresponding to the coaxial TEM mode is 0 °. At this time, the branching waveguide 13B propagates the signal component corresponding to the right-handed circularly polarized wave at a relative phase of −90 °, propagates the signal component corresponding to the left-handed circularly polarized wave at the relative phase of + 90 °, and the coaxial TEM mode. The signal component corresponding to is propagated with a relative phase of 0 °. The branching waveguide 13C propagates the signal component corresponding to the right-handed circularly polarized wave at a relative phase of −180 °, propagates the signal component corresponding to the left-handed circularly polarized wave at the relative phase of + 180 °, and enters the coaxial TEM mode. The corresponding signal components are propagated with a relative phase of 0 °. Further, the branching waveguide 13D propagates the signal component corresponding to the right-handed circularly polarized wave at a relative phase of -270 ° and the signal component corresponding to the left-handed circularly polarized wave at the relative phase of + 270 °, and sets the coaxial TEM mode. The corresponding signal components are propagated with a relative phase of 0 °. In this way, between adjacent branch waveguides among the branch waveguides 13A to 13D, the magnitude of the phase difference of the signal component corresponding to the right-handed circularly polarized wave is 90 °, which corresponds to the left-handed circularly polarized wave. The magnitude of the phase difference between the signal components is 90 °. Further, the phases of the signal components corresponding to the coaxial TEM mode are all 0 ° (in phase).

The 90-degree coupler 31 has four input / output terminals 31a, 31b, 31e, 31f. The 90-degree coupler 31 synthesizes the propagation modes input to the input / output terminals 31a and 31b from the input / output terminals 13a and 13b (ends of the branching waveguides 13A and 13B) of the polarization demultiplexer 10 to synthesize the first mode. A combined signal and a second combined signal are generated, the first combined signal is output from the input / output terminal 31e to the waveguide 41, and the second combined signal is output from the input / output terminal 31f to the waveguide 42. On the other hand, the 90-degree coupler 32 has four input / output terminals 32c, 32d, 32g, 32h. The 90-degree coupler 32 synthesizes the propagation modes input to the input / output terminals 31c and 31d from the input / output terminals 13c and 13d (ends of the branching waveguides 13C and 13D) of the polarization splitter 10 to synthesize the third mode. A combined signal and a fourth combined signal are generated, the third combined signal is output from the input / output terminal 32g to the waveguide 43, and the fourth combined signal is output from the input / output terminal 32h to the waveguide 44.

The 180 degree coupler 51 has four input / output terminals 51e, 51g, 51p and 51q. The 180-degree coupler 51 is a left-hand circularly polarized signal based on the first combined signal and the third combined signal input from the input / output terminals 31e and 32g of the 90- degree couplers 31 and 32 to the input / output terminals 51e and 51g, respectively. It is also possible to generate a coaxial TEM mode, output the left-handed circularly polarized signal to the outside from the input / output terminal 51q, and output the coaxial TEM mode to the outside from the input / output terminal 51p. On the other hand, the 180-degree coupler 52 has four input / output terminals 52f, 52h, 52p, 52q. The 180-degree coupler 52 is a right-handed circularly polarized wave based on the second combined signal and the fourth combined signal input from the input / output terminals 31f and 32h of the 90- degree couplers 31 and 32 to the input / output terminals 52f and 52h, respectively. It is possible to generate a signal and a coaxial TEM mode, output the right-handed circularly polarized wave signal to the outside from the input / output terminal 52q, and output the coaxial TEM mode to the outside from the input / output terminal 52p.

Next, the operations of the 90- degree couplers 31, 32 and the 180- degree couplers 51, 52 will be described in detail with reference to FIGS. 3 to 6. FIG. 3 is a schematic diagram for explaining the operation of the 90- degree couplers 31, 32 and the 180- degree couplers 51, 52. Now, the propagation mode of the phase θa input to the input / output terminal 31a of the 90 ° coupler 31 is represented by S (θa), and the propagation mode of the phase θb input to the input / output terminal 31b of the 90 ° coupler 31 is S (θb). ), The propagation mode of the phase θc input to the input / output terminal 32c of the 90-degree coupler 32 is represented by S (θc), and the propagation mode of the phase θd input to the input / output terminal 32d of the 90-degree coupler 32 is represented by S (θc). It is represented by (θd). For example, since the phase of the signal component corresponding to the right-hand circularly polarized wave in the propagation mode S (θa) input from the input / output terminal 13a to the input / output terminal 31a in FIG. The phase (relative phase) of the signal component corresponding to the right-handed circularly polarized wave in the input propagation mode S (θb) is −90 ° as shown in FIG.

FIG. 4 is a diagram for explaining a method for generating a right-handed circularly polarized signal, FIG. 5 is a diagram for explaining a method for producing a left-handed circularly polarized signal, and FIG. 6 is a coaxial diagram. It is a figure for explaining a method of generating a TEM mode. In FIG. 4, the symbol R (θ) represents the signal component of the phase θ corresponding to the right-handed circularly polarized wave in the propagation mode input to any of the input / output terminals 31a, 31b, 32c, 32d, and FIG. 6, the symbol L (θ) represents the signal component of the phase θ corresponding to the left-handed circularly polarized wave in the propagation mode input to any of the input / output terminals 31a, 31b, 32c, 32d, and in FIG. T (θ) represents the signal component of the phase θ corresponding to the coaxial TEM mode among the propagation modes input to any of the input / output terminals 31a, 31b, 32c, 32d.

As shown in FIG. 3, the 90-degree coupler 31 has a phase of only 90 degrees between the propagation mode S (θa) input to the input / output terminal 31a and the propagation mode S (θb) input to the input / output terminal 31b. It is configured to have a function of generating a combined signal S (θa) + S (θb-90 °) by superimposing (combining) the delayed wave S (θb-90 °) obtained by delaying, and this combining The signal S (θa) + S (θb−90 °) can be output to the waveguide 41 from the input / output terminal 31e as the first combined signal X ₁ (θe). At the same time, the 90-degree coupler 31 delays the phases of the propagation mode S (θb) input to the input / output terminal 31b and the propagation mode S (θa) input to the input / output terminal 31a by 90 degrees. It is configured to have a function of generating a combined signal S (θa-90 °) + S (θb) by superposing (combining) with the wave S (θa-90 °). ) + S (θb) can be output to the waveguide 42 from the input / output terminal 31f as the second combined signal X ₂ (θf). As will be described later, such a 90-degree coupler 31 can be composed of, for example, an H-plane cross coupler or a short slot coupler.

Further, as shown in FIG. 3, the 90-degree coupler 32 sets the phase of the propagation mode S (θc) input to the input / output terminal 32c and the phase of the propagation mode S (θd) input to the input / output terminal 32d to 90 degrees. It is configured to have a function of generating a composite signal S (θc) + S (θd-90 °) by superimposing (combining) the delayed wave S (θd-90 °) obtained by delaying by This combined signal S (θc) + S (θd−90 °) can be output to the waveguide 43 from the input / output terminal 32g as the third combined signal Y ₂ (θg). At the same time, the 90-degree coupler 32 delays the phase of the propagation mode S (θd) input to the input / output terminal 32d and the phase of the propagation mode S (θc) input to the input / output terminal 32c by 90 degrees. It is configured to have a function of generating a composite signal S (θd) + S (θc-90 °) by superimposing (combining) the wave S (θc-90 °), and this composite signal S (θd) + S (Θc−90 °) can be output to the waveguide 44 from the input / output terminal 32h as the fourth combined signal Y ₁ (θh). As will be described later, such a 90-degree coupler 32 can be composed of, for example, an H-plane cross coupler or a short slot coupler.

First, a method of generating a left-handed circularly polarized signal will be described. The 180-degree coupler 51 includes a signal component of the first combined signal X ₁ (θe) input to the input / output terminal 51e and a signal component of the third combined signal Y ₂ (θg) input to the input / output terminal 51g. Among the combinations of 1) and 2), there is a function of outputting a left-handed circularly polarized signal from the input / output terminal 51q to the outside by synthesizing signal components having opposite phases (signal components having a phase difference of 180 °). At this time, the left-handed circularly polarized signal is not output from the input / output terminal 51p. Such a 180-degree coupler 51 can be configured by, for example, a magic T circuit or a rat race circuit.

More specifically, consider a case where the signal components corresponding to the left-handed circularly polarized signal are input to the input / output terminals 31a, 31b, 32c, 32d according to the phase relationship shown in FIG. In this case, as shown in FIG. 5, the signal components L (0 °) and L (90 °) corresponding to the left-hand circularly polarized signals are input to the input / output terminals 31a and 31b, respectively. The 90-degree coupler 31 delays the phase of the signal component L (0 °) input to the input / output terminal 31a by 90 degrees, and the delayed wave L (-90 °) that is input to the input / output terminal 31b. The signal component L (90 °) is superimposed. At the time of this superposition, the delayed wave L (-90 °) and the signal component L (90 °) have the same amplitude and are in opposite phase to each other, so they are canceled out from each other. Therefore, the input / output terminal 31f does not output the signal component corresponding to the left-handed circularly polarized wave. At this time, the 90-degree coupler 31 inputs the delayed wave L (0 °) obtained by delaying the phase of the signal component L (90 °) input to the input / output terminal 31b by 90 degrees to the input / output terminal 31a. The generated signal component L (0 °) is superposed to generate a _first combined signal X ₁ (θe = 0 °), and the first combined signal X ₁ (0 °) is guided from the input / output terminal 31e. Output to the waveguide 41.

On the other hand, the 90-degree coupler 32 shown in FIG. 5 has a delayed wave L (90 °) obtained by delaying the phase of the signal component L (180 °) input to the input / output terminal 32c by 90 degrees, and The signal component L (270 °) input to the terminal 32d is superposed. At the time of this superposition, the delayed wave L (90 °) and the signal component L (270 °) have equal amplitudes and opposite phases to each other, and thus are cancelled. Therefore, the input / output terminal 32h does not output the signal component corresponding to the left-handed circularly polarized wave. At this time, the 90-degree coupler 32 inputs the delayed wave L (180 °) obtained by delaying the phase of the signal component L (270 °) input to the input / output terminal 32d by 90 degrees, and inputs the delayed wave L (180 °) to the input / output terminal 32c. The combined signal component L (180 °) is superimposed to generate a third combined signal Y ₂ (θg = 180 °), and the third combined signal Y ₂ (180 °) is guided from the input / output terminal 32g. Output to the waveguide 43.

Therefore, the 180-degree coupler 51 shown in FIG. 5 can combine the first combined signal X ₁ (0 °) and the third combined signal Y ₂ (180 °) having phases shifted from each other by 180 °. The left-handed circularly polarized signal can be output to the outside from the input / output terminal 51q. At this time, since the signal component corresponding to the left-hand circularly polarized wave is not input to the input / output terminals 52f and 52h of the 180-degree coupler 52, the 180-degree coupler 52 does not output the signal component corresponding to the left-hand circularly polarized wave.

Next, a method of generating a right-handed circularly polarized signal will be described. Referring to FIG. 3, the 180-degree coupler 52 includes a signal component of the second combined signal X ₂ (θf) input to the input / output terminal 52f and a fourth combined signal Y ₁ input to the input / output terminal 52h. Out of the combination with the signal component of (θh), the right-handed circularly polarized signal is output to the outside from the input / output terminal 52q by synthesizing the signal components having the opposite phases (the signal components having a phase difference of 180 °). Have a function. At this time, the right-handed circularly polarized signal is not output from the input / output terminal 52p. Such a 180-degree coupler 52 can be realized by, for example, a magic T circuit or a rat race circuit.

More specifically, consider a case where the signal component corresponding to the right-handed circularly polarized signal is input to the input / output terminals 31a, 31b, 32c, 32d according to the phase relationship shown in FIG. In this case, as shown in FIG. 4, the signal components R (0 °) and R (-90 °) corresponding to the right-hand circularly polarized signals are input to the input / output terminals 31a and 31b, respectively. The 90-degree coupler 31 delays the phase of the signal component R (-90 °) input to the input / output terminal 31b by 90 degrees and obtains a delayed wave R (-180 °), which is input to the input / output terminal 31a. The signal component L (0 °) is superimposed. At the time of this superposition, the delayed wave R (−180 °) and the signal component R (0 °) have equal amplitudes and opposite phases to each other, and therefore cancel each other. Therefore, the input / output terminal 31e does not output the signal component corresponding to the right-handed circularly polarized wave. At this time, the 90-degree coupler 31 delays the phase of the signal component R (0 °) input to the input / output terminal 31a by 90 degrees, and the delayed wave R (-90 °) and the input / output terminal 31b. The input signal component R (-90 °) is superposed to generate a _second combined signal X ₂ (θf = -90 °), and the second combined signal X ₂ (-90 °) is input / output. Output from the terminal 31f to the waveguide 42.

On the other hand, the 90-degree coupler 32 shown in FIG. 4 delays the phase of the signal component R (-270 °) input to the input / output terminal 32d by 90 degrees, and a delayed wave R (-360 °), The signal component R (−180 °) input to the input / output terminal 32c is superimposed. During this superposition, the delayed wave R (−360 °) and the signal component L (−180 °) have the same amplitude and are opposite in phase to each other, and therefore cancel each other. Therefore, the input / output terminal 32g does not output the signal component corresponding to the right-handed circularly polarized wave. At this time, the 90-degree coupler 32 delays the phase of the signal component R (-180 °) input to the input / output terminal 32c by 90 degrees and the delayed wave R (-270 °) and the input / output terminal 32d. The fourth combined signal Y ₁ (θg = −270 °) is generated by superimposing it on the signal component L (−270 °) that has been input to, and the fourth combined signal Y ₁ (−270 °) is input. Output from the output terminal 32h to the waveguide 44.

Therefore, the 180-degree coupler 52 shown in FIG. 4 synthesizes the second combined signal X ₂ (−90 °) and the fourth combined signal Y ₂ (−270 °), which have phases shifted from each other by 180 °. As a result, the right-handed circularly polarized wave signal can be output to the outside from the input / output terminal 52q. At this time, since the signal component corresponding to the right-hand circularly polarized wave is not input to the input / output terminals 51e and 51g of the 180-degree coupler 51, the 180-degree coupler 51 outputs the signal component corresponding to the right-hand circularly polarized wave. do not do.

Next, the method of generating the coaxial TEM mode will be described. The 180-degree coupler 51 has a function of outputting the coaxial TEM mode from the input / output terminal 51p to the outside by synthesizing the in-phase signal components input to the input / output terminals 51e and 51g. At this time, the coaxial TEM mode is not output from the input / output terminal 51q. Similarly, the 180-degree coupler 52 has a function of outputting the coaxial TEM mode from the input / output terminal 52p to the outside by synthesizing the in-phase signal components input to the input / output terminals 52f and 52h. At this time, the coaxial TEM mode is not output from the input / output terminal 52q.

More specifically, consider a case where signal components corresponding to the coaxial TEM mode are input to the input / output terminals 31a, 31b, 32c, 32d in accordance with the phase relationship shown in FIG. In this case, as shown in FIG. 6, since the input / output terminals 31a, 31b, 32c, and 32d are all input with the in-phase signal component T (0 °), the 90- degree couplers 31 and 32 are not connected. output terminals 31e, 31f, 32 g, from 32h, have the same phase, the first synthesized signal _{X 1} (.theta.e), the second composite signal _{X 2} (.theta.f), the third combined signal _{Y 2} ([theta] g) and the The composite signal Y ₁ (θh) of 4 can be output. Therefore, the 180-degree coupler 51 combines the first combined signal X ₁ (θe) and the third combined signal Y ₂ (θg), which have the same phase, in the coaxial TEM mode (first coaxial TEM mode). Is output from the input / output terminal 51p to the outside, and at the same time, the 180-degree coupler 52 combines the second combined signal X ₂ (θf) and the fourth combined signal Y ₁ (θh) having the same phase. The coaxial TEM mode (second coaxial TEM mode) is output from the input / output terminal 52p to the outside. At this time, the coaxial TEM mode is not output from the input / output terminals 51q and 52q.

As described above, the power feeding circuit 1 according to the first embodiment includes two coaxial TEM modes, a left-hand circularly polarized signal and a right-hand circularly polarized signal, which are included in the wideband signal input from the antenna input / output terminal 100. Can be separated. In the power supply circuit disclosed in Non-Patent Document 1, since a 90-degree phase shifter having frequency dependence is used, it is difficult to obtain good isolation characteristics in a wide band, and it is difficult to reduce the circuit size. There are challenges. On the other hand, the power feeding circuit 1 according to the first embodiment can separate the coaxial TEM mode, the left-hand circularly polarized signal, and the right-hand circularly polarized signal without using the 90-degree phase shifter, so that the broadband It is possible to realize a good isolation characteristic and a small circuit size.

Further, among the branching waveguides 13A to 13D of the demultiplexer 10, a set of spatially adjacent branching waveguides 13A and 13B and a set of spatially adjacent branching waveguides 13C and 13D are used for polarization. Since the wave separation is performed, there is an advantage that the circuit size of the feeding circuit 1 can be easily reduced. Furthermore, there is an advantage that the degree of freedom in selecting the arrangement of the 180- degree couplers 51 and 52 is large. For example, even if the 180- degree couplers 51 and 52 are arranged so as to intersect three-dimensionally, it is possible to obtain a configuration for performing polarization separation. Therefore, there is an advantage that the power feeding circuit 1 can be easily manufactured.

The power feeding circuit 1 can also generate a wideband signal based on the signals input to the input / output terminals 51p, 51q, 52p, 52q and output the wideband signal to a multi-frequency shared antenna (not shown). ..

Embodiment 2.
Next, a specific structure example of the power supply circuit 1 of the above-described first embodiment will be described below as a second embodiment. FIG. 7 is a perspective view showing a specific structural example of the power feeding circuit 1. The X axis, Y axis, and Z axis shown in FIG. 7 are assumed to be orthogonal to each other. Further, FIG. 8 is a top view of the power feeding circuit 1 of FIG. 7 when viewed from the Z-axis positive direction. The structure of the high frequency band circular polarization generator 60 shown in FIG. 1 is not shown.

The power supply circuit 1 shown in FIG. 7 is a 90-degree coupler (first and second 90-degree couplers) that is composed of a turn-style OMT (OrthoMode Transducer) and a demultiplexer 10 and two H-plane cross couplers. Between 31 and 32, 180-degree couplers (first and second 180-degree couplers) 51 and 52 each composed of two waveguide type magic T circuits, and between the demultiplexer 10 and the 90-degree coupler 31. Waveguides 21 and 22 made of bent waveguides, coupling waveguides 23 and 24 made of bent waveguides coupling the demultiplexer 10 and the 90-degree coupler 32, and a 90- degree coupler 31, 32 and the 180 degree couplers 51 and 52 are coupled to each other, and the waveguides 41 to 44 are formed of four rectangular waveguides.

FIG. 9 is a perspective view of the polarization splitter 10 according to the second embodiment. As shown in FIG. 9, the demultiplexer 10 includes branch waveguides 13A, 13B, and 13C that are four rectangular waveguides that extend radially outward from the central axes of the tubular conductors 11 and 12. , 13D. The outer ends of the branch waveguides 13A, 13B, 13C, and 13D form the input / output terminals 13a, 13b, 13c, and 13d of the polarization demultiplexer 10, respectively.

FIG. 10 is a schematic diagram showing a cross-sectional structure taken along the line A1-A1 of the polarization splitter 10 shown in FIG. As shown in FIG. 10, a high frequency band signal input to the input / output terminal 10p of the tubular conductor 11 propagates in the inner waveguide space of the tubular conductor 11 as a waveguide mode, and the demultiplexer It is output to the high frequency band polarization separation circuit 60 (FIG. 1) from the input / output end 10s on the back side (negative side of the Z-axis) of 10. The low-frequency band signal input to the input / output terminal 10q is distributed to the branch waveguides 13A, 13B, 13C, and 13D after propagating in the waveguide space formed between the cylindrical conductors 11 and 12. It

FIG. 11 is a perspective view showing the configuration of the waveguides 21, 22, 23, and 24 formed of the four bent waveguides of the second embodiment. As shown in FIGS. 11 and 8, the bending waveguide forming the waveguide 23 includes a 135 degree H-plane bend HBc and a 90 degree E-plane that are coupled to one end of the branching waveguide 13C of the demultiplexer 10. An inner bent portion made of the bend EBc, and a step-shaped outer bent portion (corner cut portion) 23B having a plurality of step surfaces 23Bs and 23Bs extending at an angle of 90 ° with respect to the side wall surface of the bent waveguide. have. The step surfaces 23Bs and 23Bs of the outer bent portion 23B are provided to reduce the loss due to the reflection of the signal propagating in the waveguide 23, and can be formed by machining using an end mill, for example. Here, the number of step surfaces 23Bs and 23Bs is not limited to two, and three or more step surfaces may be provided.

Similarly, the bending waveguide forming the waveguide 21 includes a 135-degree H-plane bend HBa coupled to one end of the branching waveguide 13A of the demultiplexer 10 and an inner bend portion formed of a 90-degree E-plane bend EBa. A stepwise outer bent portion (corner cut portion) 21B having a plurality of step surfaces 21Bs, 21Bs extending at an angle of 90 ° with respect to the side wall surface of the bent waveguide, The bending waveguide to be formed is a 135 ° H-plane bend HBb coupled to one end of the branching waveguide 13B of the demultiplexer 10, an inner bending portion made of a 90 ° E-plane bend EBb, and the bending waveguide of the bending waveguide. The bent waveguide forming the waveguide 24 has a stepwise outer bent portion (corner cut portion) 22B having a plurality of step surfaces 22Bs and 22Bs extending at an angle of 90 ° with respect to the side wall surface. , An inner bent portion formed of a 135 ° H-plane bend HBd coupled to one end of the branch waveguide 13D of the demultiplexer 10 and a 90 ° E-face bend EBd, and 90 ° to the side wall surface of the bent waveguide. And a stepped outer bent portion (corner cut portion) 24B having a plurality of step surfaces 24Bs and 24Bs extending at an angle of.

FIG. 12 is a perspective view of an H-plane cross coupler which constitutes the 90-degree coupler 31 of the second embodiment. The H-plane cross coupler shown in FIG. 12 has wide wall surfaces 31W arranged on the same plane, four H-plane bends, and four rectangular waveguides. The ends of the four rectangular waveguides form the input / output terminals 31a, 31b, 31e, 31f of the 90-degree coupler 31, respectively. This H-plane cross coupler includes a waveguide (waveguide conduit) extending from the input / output terminal 31a to the input / output terminal 31e and a waveguide (waveguide conduit) extending from the input / output terminal 31b to the input / output terminal 31f. ) And have a structure that intersects in a cross shape at the center. The 90-degree coupler 32 may have the same structure as the 90-degree coupler 31. A matching element (not shown) may be arranged inside the 90- degree couplers 31 and 32.

FIG. 13 is a perspective view of a waveguide type magic T circuit that constitutes the 180-degree coupler 51 of the second embodiment. The magic T circuit shown in FIG. 13 has four open ends forming four input / output terminals 51g, 51e, 51p, and 51q. The 180-degree coupler 52 may have the same structure as the 180-degree coupler 51.

As shown in FIG. 7, the 90- degree couplers 31 and 32 are biased via the 135-degree H-plane bends HBa, HBb, HBc, HBd and the 90-degree E-plane bends EBa, EBb, EBc, and EBd (FIG. 11). It is connected to the wave device 10 and is also connected to the 180-degree couplers 51 and 52 (magic T circuit) via the H-plane bend and the E-plane bend. Further, as shown in FIG. 7, the 180- degree couplers 51 and 52 are arranged so as to be displaced from each other in the Z-axis direction (pipe axis direction) so as not to physically interfere with each other. The connection length between the 180-degree coupler 51 and the 90-degree coupler 31 is the same as the connection length between the 180-degree coupler 51 and the 90-degree coupler 32, and the 180-degree coupler 52 and the 90-degree coupler 31 are the same. The connection length between them is also the same as the connection length between the 180-degree coupler 52 and the 90-degree coupler 32. As shown in FIG. 7, the input / output terminal 52q that outputs a right-handed circularly polarized wave and the input / output terminal 51q that outputs a left-handed circularly polarized wave when viewed from the upper surface direction (Z-axis direction) of the power feeding circuit 1. It is arranged at the central position of the power feeding circuit 1 and along the central axis of the polarization splitter 10. Further, as shown in FIG. 8, the input / output terminals 51p and 52p for outputting the coaxial TEM mode are arranged so as to face opposite directions.

Therefore, the power feeding circuit 1 of the present embodiment has a structure that is geometrically symmetric with respect to the central axis of the demultiplexer 10 (the central axes of the cylindrical conductors 11 and 12), and has a small circuit size. It can be seen that the realization has been realized. If the lengths of the waveguides 41 and 43 are the same and the lengths of the waveguides 42 and 44 are the same, even if the lengths of the waveguides 43 and 44 are not the same, a predetermined phase relationship is obtained. Can be obtained. Therefore, since it is not necessary to strictly adjust the positions of the 180- degree couplers 51 and 52, the power feeding circuit 1 can be easily manufactured. Further, the 90- degree couplers 31 and 32 are connected to the polarization demultiplexer 10 via the 135-degree H-plane bends HBa, HBb, HBc, and HBd of the waveguides 21, 22, 23, and 24. There is also an effect that the manufacturing is easy.

FIG. 14 is a graph showing the calculation result of the isolation characteristic of the power feeding circuit 1 shown in FIG. The horizontal axis of the graph is the normalized frequency normalized by the center frequency of the frequency band used, and the vertical axis is input / output terminals 51q and 52q when the low frequency coaxial TEM mode is input from the antenna input / output terminal 100. The output isolation amount (unit: dB) is shown. The solid line represents the pass characteristic between the input / output terminal of the demultiplexer 10 and the input / output terminal 51q of the 180 degree coupler 51, and the dotted line represents the input / output terminal of the demultiplexer 10 and the input of the 180 degree coupler 52. The pass characteristic with the output terminal 52q is shown. As shown in the graph of FIG. 14, not only the center frequency (normalized frequency “1”), but also the isolation characteristic is good not only in the frequency range deviating from the center frequency, but also in the wide band, good isolation characteristics are realized. ing.

Note that the multi-cylinder structure of the demultiplexer 10 is not limited to the double cylinder structure. FIG. 15 is a schematic cross-sectional view of a polarization demultiplexer 10A having a triple cylindrical structure. As shown in FIG. 15, the demultiplexer 10A includes a tubular conductor 12, a tubular conductor 11A coaxially arranged inside the tubular conductor 12, and a coaxial conductor inside the tubular conductor 11A. Cylindrical conductors 14 arranged in a circle, and branch waveguides (rectangular waveguides) 15B, 15D, ... Radially extending from a waveguide space formed between the cylindrical conductor 14 and the cylindrical conductor 11A. Is equipped with. The cylindrical conductor 14 and the branch waveguides 15B, 15D, ... Form a turnstile OMT.

As shown in FIG. 15, the high frequency band signal input to the input / output terminal 10pa propagates in the inner waveguide space of the tubular conductor 14 as a waveguide mode, and is transmitted to the rear side (Z It is possible to output to the high frequency band polarization separation circuit 60 (FIG. 1) from the input / output terminal 10sa on the negative side of the axis). In addition, the signal in the first low frequency band input to the input / output terminal 10q propagates through the waveguide space formed between the cylindrical conductors 11A and 12 and then enters the branch waveguides 13A, 13B, 13C and 13D. Distributed. Further, the signal in the second low frequency band input to the input / output terminal 10pb propagates through the waveguide space formed between the cylindrical conductors 11A and 14 and is then distributed to the branch waveguides 15B, 15D, .... It A circuit having the same configuration as the polarization separation circuit portion of the first and second embodiments may be coupled to the input / output terminals 15b, 15d, ... Of the branch waveguides 15B, 15D ,. In this case, the effect that the circularly polarized signal and the coaxial TEM mode can be separated in a plurality of frequency bands is obtained.

Also, a short slot coupler or a hybrid coupler may be used instead of the 90- degree couplers 31 and 32 composed of the H-plane cross coupler described above. 16 is a front view of a short slot coupler 61 that can be substituted for each of the 90- degree couplers 31 and 32, and FIG. 17 is a front view of a hybrid coupler 71 that can be substituted for each of the 90- degree couplers 31 and 32. .. As shown in FIG. 16, the short slot coupler 61 includes four input / output terminals 61a, 61b, 61c and 61d, a pair of wide wall surfaces 61f and 61g arranged on the same plane, and wide wall surfaces 61f and 61g. And a waveguide for coupling the input / output terminals 61a, 61b, 61c, 61d. The wide wall surfaces 61f and 61g face each other in the thickness direction of the short slot coupler 61.

Further, as shown in FIG. 17, the hybrid coupler 71 includes four twisted waveguides 72, 73, 74 and 75 having four input / output terminals 71a, 71b, 71c and 71d of the hybrid coupler 71 and a twisted pair. A branch-in coupler 76 coupled to the ends of the waveguides 72, 73, 74 and 75. Each of the twisted waveguides 72, 73, 74 and 75 has a structure in which a rectangular waveguide is twisted (twisted) by 90 ° about the tube axis. The branch-in coupler 76 has a waveguide that couples the twisted waveguides 72, 73, 74, and 75.

Embodiment 3.
Next, another specific structural example of the power supply circuit 1 of the above-described first embodiment will be described below as a third embodiment. The structure of the power feeding circuit 2 of the third embodiment is implemented except that the waveguides 81, 82, 83, 84 shown in FIG. 18 are replaced with the waveguides 21, 22, 23, 24 shown in FIG. This is the same as the structure of the power feeding circuit 1 of the second aspect. 19 is a top view of the polarization splitter 10 and the waveguides 81 to 84 shown in FIG.

As shown in FIGS. 18 and 19, the bent waveguide forming the waveguide 83 includes a 135-degree H-plane bend HBc and a 90-degree E-plane that are coupled to one end of the branching waveguide 13C of the demultiplexer 10. An inner bent portion made of the bend EBc and a stepped outer bent portion (corner cut portion) 83B having a plurality of step surfaces 83Bs and 83Bs extending at an inclination angle with respect to the side wall surface of the bent waveguide are provided. is doing. The step surfaces 83Bs and 83Bs of the outer bent portion 83B are provided to reduce loss due to reflection of a signal propagating in the waveguide 23, and can be formed by, for example, machining using an end mill. Here, the number of step surfaces 83Bs, 83Bs is not limited to two, and one or three or more step surfaces may be provided.

When the distance between the branch waveguide 13C and the outer bent portion 83B of the bent waveguide is short, the wavefront of the signal output from the demultiplexer 10 to the branch waveguide 13C is oblique to the tube wall. Since the light propagates to the outer bent portion 83B, good reflection characteristics may not be obtained. Therefore, the distance between the 135 ° H-plane bend HBc and the 90 ° E-plane bend EBc can be increased so that the wavefront of the signal propagating to the outer bent portion 83B is perpendicular to the tube wall. Increases the circuit size. Alternatively, an arcuate waveguide can be used instead of the 135 degree H-plane bend HBc, but this also has a problem that the circuit size becomes large. Therefore, in the present embodiment, since the angles of the step surfaces 83Bs and 83Bs with respect to the tube wall are changed according to the wavefront shape of the propagation signal, it is possible to obtain good reflection characteristics without increasing the circuit size. it can.

Similarly, the bending waveguide forming the waveguide 81 has an 135 ° H-face bend HBa coupled to one end of the branching waveguide 13A of the demultiplexer 10 and an inner bent portion made of a 90 ° E-face bend EBa. And a stepwise outer bent portion (corner cut portion) 81B having a plurality of step surfaces 81Bs and 81Bs extending at an inclination angle with respect to the side wall surface of the bent waveguide, forming a waveguide 82. The bent waveguide is composed of a 135 degree H-plane bend HBb coupled to one end of the branching waveguide 13B of the demultiplexer 10, an inner bend formed of a 90 degree E-plane bend EBb, and a side wall surface of the bent waveguide. The bent waveguide forming the waveguide 84 has a stepwise outer bent portion (corner cut portion) 82B having a plurality of step surfaces 82Bs and 82Bs extending at an inclination angle with respect to 135 degree H plane bend HBd which couple | bonds with one end of the branch waveguide 13D of the container 10, and the inside bend part which consists of 90 degree E plane bend EBd, and it extends at an inclination angle with respect to the side wall surface of the said bending waveguide. It has a stepwise outer bent portion (corner cut portion) 84B having a plurality of step surfaces 84Bs, 84Bs.

FIG. 20 is a graph showing the reflection characteristic of the power feeding circuit 1 of the second embodiment, and FIG. 21 is a graph showing the reflection characteristic of the power feeding circuit 2 of the third embodiment. The graphs of FIG. 20 and FIG. 21 respectively show the reflection characteristics of two orthogonal TE11 modes of the antenna side terminal of the demultiplexer 10 by a solid line and a dotted line. In these graphs, the horizontal axis represents the normalized frequency normalized by the center frequency of the used frequency band, and the vertical axis represents the reflection amount (unit: dB). In the normalized frequency range of 0.92 to 1.08, the worst value of the reflection amount in the case of FIG. 20 is about −18 dB, whereas the reflection amount in the case of FIG. 21 is about −20 dB. It is confirmed that the form 3 has improved reflection characteristics as compared with the form 2 of the embodiment.

The number of step surfaces in each of the outer bent portions 81B, 82B, 83B, 84B is not limited to two, and may be one or three or more. Further, in each of the outer bent portions 81B, 82B, 83B, 84B, a plurality of step surfaces may have the same inclination angle, or different step surfaces may have different inclination angles. Further, the inclination angle of the step surface in each of the outer bent portions 81B, 82B, 83B, 84B is made smaller as it goes away from the 135 degree H-plane bend, or in each of the outer bent portions 81B, 82B, 83B, 84B. The inclination angle of the step surface may be set to increase as it approaches the 135 degree H-plane bend. As a result, better reflection characteristics can be obtained.

The various embodiments according to the present invention have been described above with reference to the drawings. These embodiments are examples of the present invention, and there may be various embodiments other than these embodiments. For example, in the structure shown in FIG. 7, the input / output terminals 51p and 52p face in opposite directions, but the invention is not limited to this. The configuration of the above-described embodiment may be modified so that the input / output terminals 51p and 52p face the same direction.

In addition, in the first, second, and third embodiments, a distributor / combiner that combines the outputs of the input / output terminals 51p and 52p may be provided. In this case, it is possible to use the coaxial TEM mode of larger power, as compared with the case of using the individual outputs of the input / output terminals 51p and 52p. FIG. 22 is a diagram schematically showing a configuration of power supply circuit 1A according to the modification of the first embodiment. The configuration of power supply circuit 1A shown in FIG. 22 is the same as the configuration of power supply circuit 1 of the first embodiment except that distribution distributor 90 is additionally provided. The distributor / combiner 90 can function as a combiner that combines the outputs of the input / output terminals 51p and 52p and outputs the coaxial TEM mode from its own input / output terminal 90p. Further, it can function as a distributor that divides the signal input to the input / output terminal 90p into two signals and outputs the two signals to the input / output terminals 51p and 52p, respectively.

Note that, within the scope of the present invention, it is possible to freely combine the above-described embodiments, modify any constituent element of each embodiment, or omit any constituent element of each embodiment.

The power supply circuit according to the present invention is suitable for use in, for example, a radio telescope for astronomical observation, a satellite communication system, and a multi-frequency shared antenna in a satellite broadcasting system.

1, 2, 1A feeding circuit, 10, 10A demultiplexer, 11, 11A, 12, 14 tubular conductor, 13A-13D branch waveguide, 15B, 15D branch waveguide, 21-24 waveguide, 21B-24B Corner cut part (outer bent part), 31, 32 90 degree coupler, 41-44 waveguide, 51, 52 180 degree coupler, 60 high frequency band polarization separation circuit, 61 short slot coupler, 71 hybrid coupler, 72-75 Twisted waveguide, 76 branch-in coupler, 81-84 waveguide, 81B-84B corner cut part (outer bent part), 90 distribution combiner, 100 antenna input / output end, HBa-HBd 135 degree H-plane bend, EBa- EBd 90 degree E side bend.

Claims (12)

1. A plurality of tubular conductors arranged coaxially, and a plurality of tubular conductors are formed from a waveguide space formed between any two tubular conductors of the plurality of tubular conductors. A polarization demultiplexer having first to fourth branch waveguides that branch symmetrically with respect to the central axis of the conductor;
   Of the first to fourth branch waveguides, the first propagation mode and the second propagation mode output from the adjacent first and second branch waveguides are input, and the second propagation mode of the second propagation mode is input. A first combined signal is generated by combining a delayed wave obtained by delaying the phase by 90 degrees and the first propagation mode, and at the same time, the phase of the first propagation mode is delayed by 90 degrees. A first 90-degree coupler that generates a second combined signal by combining the obtained delayed wave and the second propagation mode,
   The third propagation mode and the fourth propagation mode output from the adjacent third and fourth branch waveguides of the first to fourth branch waveguides are input, and the fourth propagation mode of the fourth propagation mode is input. The delayed wave obtained by delaying the phase by 90 degrees and the third propagation mode are combined to generate a third combined signal, and at the same time, the phase of the third propagation mode is delayed by 90 degrees. A second 90-degree coupler that generates a fourth combined signal by combining the obtained delayed wave and the fourth propagation mode,
   The first combined signal and the third combined signal are input, and the signal components having opposite phases are combined from the combination of the signal component of the first combined signal and the signal component of the third combined signal. Therefore, a first 180-degree coupler that outputs the first circularly polarized signal from the first output terminal,
   The second combined signal and the fourth combined signal are input, and the signal components having opposite phases are combined from the combination of the signal component of the second combined signal and the signal component of the fourth combined signal. Therefore, the power feeding circuit is provided with a second 180-degree coupler that outputs a second circularly polarized signal that is orthogonal to the first circularly polarized signal from a second output terminal.
2. The power feeding circuit according to claim 1, wherein the first 180-degree coupler has a signal component that is in phase with each other in a combination of a signal component of the first combined signal and a signal component of the third combined signal. A first coaxial TEM mode is output from a third output terminal by synthesizing the above.
3. The feed circuit according to claim 1 or 2, wherein the second 180-degree coupler is a combination of the signal component of the second combined signal and the signal component of the fourth combined signal. A power feeding circuit which outputs a second coaxial TEM mode from a fourth output terminal by combining in-phase signal components.
4. The power supply circuit according to claim 1, further comprising a combiner coupled to each of the first 180 degree coupler and the second 180 degree coupler,
   The first 180-degree coupler combines the signal components of the first combined signal and the signal component of the third combined signal, which are in phase with each other, and outputs the combined signal components to the combiner,
   The second 180-degree coupler combines the signal components of the second combined signal and the signal component of the fourth combined signal, which are in phase with each other, and outputs the combined signal components to the combiner.
   The power supply circuit, wherein the combiner combines the output of the first 180-degree coupler and the output of the second 180-degree coupler.
5. The power supply circuit according to any one of claims 1 to 3, wherein the first to fourth branch waveguides extend radially from the central axis toward the outside. Characteristic power supply circuit.
6. The power supply circuit according to claim 5, wherein the first to fourth branch waveguides are rectangular waveguides.
7. The power supply circuit according to any one of claims 1 to 3,
   First and second bent waveguides respectively coupling the one ends of the first and second branch waveguides to the first 90-degree coupler,
   Further comprising third and fourth bent waveguides respectively coupling the one ends of the third and fourth branch waveguides to the second 90-degree coupler,
   Each of the first and second bent waveguides has an inner bent portion made of a 90-degree E-plane bend, and a single sloping with respect to each side wall surface of the first and second bent waveguides. Including an outer bent portion having a plurality of step surfaces,
   Each of the third and fourth bent waveguides has an inner bent portion formed of a 90-degree E-plane bend, and a single sloping with respect to each side wall surface of the third and fourth bent waveguides. An outer bent portion having a plurality of step surfaces,
   A power supply circuit characterized by the above.
8. The power supply circuit according to claim 7,
   The inclination angles of the plurality of step surfaces in each of the first and second bent waveguides are different,
   The inclination angles of the plurality of step surfaces in each of the third and fourth bent waveguides are different.
   A power supply circuit characterized by the above.
9. The power supply circuit according to any one of claims 1 to 3,
   The first 90-degree coupler comprises an H-plane cross coupler having wide wall surfaces arranged on the same plane,
   The second 90-degree coupler is an H-plane cross coupler having wide wall surfaces arranged on the same plane,
   A power supply circuit characterized by the above.
10. The power supply circuit according to any one of claims 1 to 3,
    The first 90-degree coupler comprises a short slot coupler having wide wall surfaces arranged on the same plane,
    The second 90-degree coupler comprises a short slot coupler having wide wall surfaces arranged on the same plane,
    A power supply circuit characterized by the above.
11. The power supply circuit according to any one of claims 1 to 3,
    The first 90 degree coupler includes a plurality of first twisted waveguides and a branch line coupler coupled to an end of the plurality of first twisted waveguides,
    The second 90 degree coupler includes a plurality of second twisted waveguides and a branch line coupler coupled to an end of the plurality of second twisted waveguides.
    A power supply circuit characterized by the above.
12. The power supply circuit according to any one of claims 1 to 3,
    The first 180 degree coupler comprises a magic T circuit,
    The second 180 degree coupler comprises a magic T circuit,
    A power supply circuit characterized by the above.

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