WO2020000204A1 - 相位校准方法、相关装置及设备 - Google Patents

相位校准方法、相关装置及设备 Download PDF

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Publication number
WO2020000204A1
WO2020000204A1 PCT/CN2018/092928 CN2018092928W WO2020000204A1 WO 2020000204 A1 WO2020000204 A1 WO 2020000204A1 CN 2018092928 W CN2018092928 W CN 2018092928W WO 2020000204 A1 WO2020000204 A1 WO 2020000204A1
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Prior art keywords
signal
phase
channel
synthesized
amplitude
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PCT/CN2018/092928
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English (en)
French (fr)
Inventor
李治
诸小胜
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华为技术有限公司
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Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Priority to CN202210278789.1A priority Critical patent/CN114826442A/zh
Priority to CN201880095116.4A priority patent/CN112368957B/zh
Priority to PCT/CN2018/092928 priority patent/WO2020000204A1/zh
Publication of WO2020000204A1 publication Critical patent/WO2020000204A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/20—Monitoring; Testing of receivers
    • H04B17/21—Monitoring; Testing of receivers for calibration; for correcting measurements
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas

Definitions

  • the present application relates to the technical field of antennas, and in particular, to an antenna multi-channel phase calibration method, related devices, and equipment.
  • Antenna as a necessary energy conversion device in radio system, can transmit and receive electromagnetic waves with high efficiency.
  • An array antenna is an antenna formed by two or more single antennas working at the same frequency and arranged in space according to certain requirements. Among them, each antenna corresponds to a channel, and each channel is used to transmit the signals received by the corresponding antenna. The signal or the signal to be transmitted is transmitted to the corresponding antenna.
  • Array antennas have been widely used in various communication systems and radar systems because they have the advantages of providing flexible radiation patterns, facilitating adjustment of beam width, and increasing antenna gain.
  • phase inconsistency between the array antenna channels due to factors such as component differences, circuit design and manufacturing differences, and coupling effects between channels, there is usually a problem of phase inconsistency between the array antenna channels.
  • the phase of the signal is corrected so that the phases of the signals in the channels of the array antenna are consistent.
  • the traditional array antenna phase calibration method cannot overcome the influence of the coupling effect between the channels on the phase of the signal in the channel.
  • Embodiments of the present application provide a phase calibration method, related device and equipment, which can overcome the influence of the coupling effect between channels on the phase of a signal in a channel during the phase alignment process of a conventional array antenna.
  • an embodiment of the present application provides a multi-channel phase calibration method for an array antenna.
  • the method includes:
  • Enable n channels of the array antenna to determine a first phase difference between the debug signal and the reference signal of each of the n channels, the first phase difference including a reference phase difference and a target phase difference, the reference
  • the phase difference is a phase difference between a debugging signal of a reference channel in the n channels and the reference signal
  • the target phase difference is a debugging signal of each of n-1 channels except the reference channel.
  • n channels of the array antenna are opened at the same time, and the first phase difference between the debug signal and the reference signal in each channel is first determined, and then the debug signal in the reference channel is used
  • a reference signal according to a first phase difference between a debugging signal and a reference signal in each channel, determining a second phase difference between the debugging signal and the reference signal in n-1 channels except the reference channel, Further, the phase shifter in each of the n-1 channels is adjusted according to the second phase difference between the debugging signal and the reference signal of each of the n-1 channels, and the phase shifter can be passed
  • the phase of the debug signal in each channel is calibrated to be the same as the reference signal.
  • the first phase between the debug signal and the reference signal in each channel is the result obtained in the presence of interference between the coupling effects between channels.
  • the effect of the coupling effects between channels on the phase is The registration process has been counted, so the inter-channel phase difference method can cause the mutual coupling compensation signal is to overcome the coupling effect on the signal channel in a conventional inter-channel phase channel phase array antenna calibration.
  • the k-th first phase difference is based on the phase difference between the debugging signal in the k-th channel and the intermediate synthesized signal, the amplitude of the debugging signal in the k-th channel, and the intermediate synthesis
  • the amplitude of the signal is determined, wherein the k-th channel is any one of the n channels, and the intermediate synthesized signal is a debug in the remaining n-1 channels except the k-th channel.
  • k is a positive integer less than or equal to n.
  • the k-th first phase difference is based on the phase difference between the debugging signal in the k-th channel and the intermediate synthesized signal, the amplitude of the debugging signal in the k-th channel, and the intermediate synthesis
  • the amplitude of the signal is determined in conjunction with the vector algorithm.
  • determining a phase difference between the debugging signal in the k-th channel and the intermediate synthesized signal, the amplitude of the debugging signal in the k-th channel, and the amplitude of the intermediate synthesized signal include: :
  • the amplitudes of at least three synthesized signals synthesized by the debugging signals of the n channels include:
  • the third synthesized signal Obtain the third power of the third synthesized signal, and determine the amplitude of the third synthesized signal according to the third power, where the third synthesized signal is the phase shifter of the k-th channel in the third phase state;
  • the phase difference between the debugging signal in the k-th channel and the intermediate synthesized signal, and the debugging signal in the k-th channel are determined according to the amplitudes of at least three synthesized signals in combination with the cosine theorem.
  • Amplitude and the amplitude of the intermediate composite signal including:
  • C k is the amplitude of the intermediate synthesized signal
  • a k is the amplitude of the debug signal in the k-th channel
  • ⁇ k is between the debug signal and the intermediate synthesized signal in the k-th channel
  • ⁇ 1 is the additional phase shift of the phase shifter in the first phase state
  • ⁇ 2 is the additional phase shift of the phase shifter in the second phase state
  • ⁇ 3 is the phase shifter
  • K 1 is the amplitude of the first synthesized signal
  • K 2 is the amplitude of the second synthesized signal
  • K 3 is the amplitude of the third synthesized signal.
  • the first power of the first composite signal, the second power of the second composite signal, and the third power of the third composite signal are obtained from a power meter.
  • the first phase difference between the debugging signal and the reference signal in the k-th channel is determined according to the following formula:
  • phase difference Represents a debug signal in the k-th channel
  • the first phase state is a state when an additional phase shift of the phase shifter of the k-th channel is 0;
  • the second phase state is a state of the k-th channel The state when the additional phase shift of the phase shifter is ⁇ / 2;
  • the third phase state is the state when the additional phase shift of the phase shifter of the k-th channel is ⁇ .
  • an embodiment of the present application provides a multi-channel phase calibration apparatus, characterized in that the calibration apparatus includes a determination unit and an adjustment unit:
  • the determining unit is configured to determine a first phase difference between a debugging signal and a reference signal of each of the n channels of the array antenna when the n channels of the array antenna are activated, where the first phase difference includes a reference phase And a target phase difference, the reference phase difference is a phase difference between a debug signal of the reference channel in the n channels and the reference signal, and the target phase difference is other than the reference channel the phase difference between the debugging signal and the reference signal of each of the n-1 channels, where n is a positive integer greater than or equal to 2;
  • the determining unit is further configured to determine a second phase difference between a debugging signal and a reference signal of each of the n-1 channels according to a difference between a target phase difference and a reference phase difference, the reference The signal is a debugging signal in the reference channel;
  • the adjusting unit is configured to adjust a phase shifter in each of the n-1 channels according to a second phase difference between a debugging signal and a reference signal of each of the n-1 channels, So that the phase of the debug signal in each of the n-1 channels is the same as the phase of the reference signal.
  • the k-th first phase difference is based on the phase difference between the debugging signal in the k-th channel and the intermediate synthesized signal, the amplitude of the debugging signal in the k-th channel, and the intermediate synthesis
  • the amplitude of the signal is determined, wherein the k-th channel is any one of the n channels, and the intermediate synthesized signal is a debug in the remaining n-1 channels except the k-th channel.
  • k is a positive integer less than or equal to n.
  • the k-th first phase difference is based on the phase difference between the debugging signal in the k-th channel and the intermediate synthesized signal, the amplitude of the debugging signal in the k-th channel, and the intermediate synthesis
  • the amplitude of the signal is determined in conjunction with the vector algorithm.
  • the determining unit is further configured to:
  • the apparatus further includes:
  • the apparatus further includes: a power obtaining unit, configured to obtain a first power of a first composite signal, where the first composite signal is a phase shifter of a k-th channel in a first phase A synthesized signal synthesized by the debugging signals of the n channels in the state;
  • the determining unit is further configured to determine an amplitude of the first composite signal according to the first power
  • the power obtaining unit is further configured to obtain a second power of a second synthesized signal, where the second synthesized signal is synthesized from the debugging signals of the n channels when the phase shifter of the k-th channel is in the second phase state.
  • the determining unit is further configured to determine an amplitude of the second composite signal according to the second power
  • the power obtaining unit is further configured to obtain a third power of a third synthesized signal, where the third synthesized signal is synthesized from the debugging signals of the n channels when the phase shifter of the k-th channel is in the third phase state.
  • the determining unit is further configured to:
  • C k is the amplitude of the intermediate synthesized signal
  • a k is the amplitude of the debug signal in the k-th channel
  • ⁇ k is between the debug signal and the intermediate synthesized signal in the k-th channel
  • ⁇ 1 is the additional phase shift of the phase shifter in the first phase state
  • ⁇ 2 is the additional phase shift of the phase shifter in the second phase state
  • ⁇ 3 is the phase shifter
  • K 1 is the amplitude of the first synthesized signal
  • K 2 is the amplitude of the second synthesized signal
  • K 3 is the amplitude of the third synthesized signal.
  • the power acquisition unit is a power meter.
  • the determining unit is further configured to determine an amplitude of the third composite signal according to the third power.
  • the determining unit is further configured to:
  • the first phase difference between the debug signal and the reference signal in the k-th channel is determined according to the following formula:
  • a k is the amplitude of the debug signal in the k-th channel
  • C k is the amplitude of the intermediate synthesized signal
  • ⁇ k is the phase between the debug signal and the intermediate synthesized signal in the k-th channel difference
  • the first phase state is a state when an additional phase shift of the phase shifter of the k-th channel is 0;
  • the second phase state is a state of the k-th channel The state when the additional phase shift of the phase shifter is ⁇ / 2;
  • the third phase state is the state when the additional phase shift of the phase shifter of the k-th channel is ⁇ .
  • an embodiment of the present application provides a phase calibration device, including a processor, a transceiver, a power measurement module, and a memory.
  • the processor, the transceiver, the power measurement module, and the memory are connected to each other.
  • the memory is used for For storing application program code, the processor is configured to call the program code and execute the method according to the first aspect.
  • an embodiment of the present application provides a computer-readable storage medium, where the computer-readable storage medium stores a computer program, and is characterized in that, when the computer program is executed by a processor, the implementation as described in the first aspect is implemented. method.
  • n channels of the array antenna are opened at the same time to receive or transmit signals.
  • the debugging signals in each channel are obtained after interference including mutual coupling effects. Therefore, the above method is adopted.
  • the determined second phase difference between the debug signal and the reference signal in each channel is a phase difference obtained in the presence of a mutual coupling effect, that is, a phase difference due to the mutual coupling effect exists in the second phase difference, so
  • the phase difference caused by the mutual coupling effect can be compensated to overcome the influence of the mutual coupling effect on the signal phase in the channel in the conventional array antenna phase calibration.
  • FIG. 1 is a schematic structural diagram of an array antenna according to an embodiment of the present application.
  • FIG. 2 is a schematic diagram of phase alignment of an array antenna by a vector network analyzer in the prior art.
  • FIG. 3 is a schematic flowchart of an array antenna multi-channel phase calibration method according to an embodiment of the present application.
  • FIG. 4 is a schematic flowchart of a method for determining a first phase difference according to an embodiment of the present application.
  • FIG. 5 is a schematic flowchart of a method for determining a phase difference between a debugging signal in the k-th channel and an intermediate synthesized signal, an amplitude of the debugging signal in the k-th channel, and an amplitude of the intermediate synthesized signal according to an embodiment of the present application. .
  • FIG. 6 is a schematic diagram of an array antenna multi-channel phase calibration system according to an embodiment of the present application.
  • FIG. 7 is a schematic diagram showing a relationship between a debugging signal and a reference signal by using a signal vector according to an embodiment of the present application.
  • FIG. 8 is a schematic diagram of a cosine theorem provided by an embodiment of the present application.
  • FIG. 9 is a schematic diagram of relationships among signal vectors, intermediate composite vectors, and composite vectors in four channels of an array antenna according to an embodiment of the present application.
  • FIG. 10 is an effect diagram after calibrating a signal in each channel by implementing a multi-channel phase calibration method provided in the present application.
  • FIG. 11 is a schematic diagram of another array antenna multi-channel phase calibration system according to an embodiment of the present application.
  • FIG. 12 is a schematic structural diagram of an array antenna multi-channel phase calibration device according to an embodiment of the present application.
  • FIG. 13 is a schematic structural diagram of an array antenna multi-channel phase calibration device according to an embodiment of the present application.
  • An array antenna includes multiple channels, and each channel is a radio frequency circuit, including an antenna, a feeder, an amplifier, and a phase shifter.
  • FIG. 1 is a schematic structural diagram of an array antenna provided by an embodiment of the present application. .
  • the array antenna transmits the received signal to the high-frequency amplifier and the intermediate-frequency amplifier through the feeder.
  • the signal is phase-compensated by a phase shifter to obtain a signal that meets the phase requirements.
  • the sub-network synthesizes the signals in each channel into a single signal, which is used as the signal finally received by the array antenna.
  • the signal is divided into multiple signals according to power by the power division network, and then the signals are phase-compensated by phase shifters in each channel to obtain the phase requirements.
  • the signal is finally amplified by the intermediate frequency amplifier and the high frequency amplifier, and then transmitted to the antenna through the feeder, and then transmitted by the antenna.
  • Array antennas usually use power combining technology to combine the signals transmitted or received by multiple channels of the array antenna into one signal.
  • the signals in different channels When the signals in different channels are synthesized, the signals in each channel will cause the amplitude of the synthesized signal due to inconsistent phases. Different enhancement or weakening occurs at different times (for example, after two identical channels with a period of 2 ⁇ pass through two different channels, if the signal phase is different by ⁇ , the amplitude of the synthesized signal may be zero during synthesis), so that It will seriously affect the radiation characteristics of the array antenna, such as the composite gain and pattern. Therefore, it is necessary to ensure that the signal phase in each channel of the array antenna is consistent.
  • FIG. 2 shows a schematic diagram of phase alignment of an array antenna by a vector network analyzer. Port 1 of the vector network analyzer is connected to a transmitting antenna, and port 2 is connected to an array antenna.
  • the test signal generated by the signal source in the vector network analyzer, the array antenna receives the test signal, closes the other channels except the test channel, and transmits the received test signal to the vector network analyzer through the test channel, vector network analysis
  • the instrument analyzes the test signal after passing the test channel to obtain the phase of the test signal after passing the test channel. For example, when testing the jth (j is a positive integer less than or equal to m) channel of all m (m is greater than 1 positive integer) channels of the array antenna, only the jth channel is opened and the other m-1 channels are closed.
  • the array antenna The test signal can only be received through the antenna corresponding to the j-th channel, and the received test signal is input to the vector network analyzer through the j-th channel.
  • the vector network analyzer analyzes the test signal after passing the j-th channel to obtain the passing j-th Phase of the test signal after the channel. Then use the same method, open one of the untested channels each time as the test channel, and close the remaining m-1 channels. Use a vector network analyzer to obtain the phase of the test signal after passing the test channel, and finally obtain m channels. The phase of the signal in each channel in. Finally, the signal in any one of the m channels is selected as the reference signal. According to the phase of the signals in each channel obtained by the vector network analyzer, the phase difference between the signals in the remaining m-1 channels and the reference signal is determined.
  • the phase difference between the signal in each of the m-1 channels and the reference signal adjusts the additional phase shift of the phase shifter in the corresponding channel, so that when the signal in each channel passes the phase shifter, it can pass
  • the phase shifter performs phase compensation on the passing signal, thereby calibrating the phase of the signal in each channel to the same phase as the reference signal.
  • each channel of the array antenna is often opened at the same time to receive or send signals. No matter whether each antenna in the array antenna is in the transmitting state or the receiving state, a part of the electromagnetic energy in each channel is radiated to other channels. Some or all of the channels will also receive electromagnetic energy radiated from some or all of the other channels. This mutual coupling effect caused by the electromagnetic energy exchange between the array antenna channels will cause the The signal phase is shifted to different degrees, resulting in inconsistent signal phases in each channel.
  • the traditional phase calibration method described above only opens one channel at a time and closes other channels. It is a single-channel phase calibration method, which cannot overcome the channel-to-channel The effect of mutual coupling on the phase of a signal in a channel.
  • FIG. 3 is a method The schematic diagram of the array antenna multi-channel phase calibration method, as shown in the figure, the phase calibration method includes:
  • n is a positive integer greater than or equal to 2, and the array antenna enables n channels at the same time.
  • the n channels may be part of the array antenna or all channels of the array antenna, and the debugging signal is the n
  • the test signal received by each of the channels after passing through the corresponding channel, and the data carried by the test signal received by the corresponding antenna of each channel is the same.
  • the first phase difference includes a reference phase difference and a target phase difference, where the reference phase difference is a phase difference between a debugging signal of a reference channel in the n channels and the reference signal, and the target phase difference is The phase difference between the debug signal and the reference signal of each of the n-1 channels other than the reference channel.
  • the reference channel is any one of the n channels.
  • the reference signal is a synthesized signal synthesized by the debug signals in the n channels in a first phase state of the phase shifter of each of the n channels.
  • the first phase state of the phase shifter in each channel may be a state when an additional phase shift of the phase shifter is 0 degrees, that is, before performing multi-channel phase calibration on the array antenna,
  • the additional phase shifts of the phase shifters in the n channels are all adjusted to 0 degrees; it can also be the state after the last calibration, that is, before the multi-channel phase calibration of the array antenna, the additional phase shifters in the n channels are added.
  • the phase shift is not adjusted. For example, the four channels of the array antenna are calibrated. After the last calibration, the additional phase shifts of the phase shifters in the first to fourth channels are 15 degrees, 26 degrees, 45 degrees, and 60 degrees.
  • the first phase state of the phase shifter in the first channel is the state when the additional phase shift is 15 degrees
  • the first phase state of the phase shifter in the second channel is the additional phase shift of 26
  • the first phase state of the phase shifter in the third channel is the state when the additional phase shift is 45 degrees
  • the first phase state of the phase shifter in the fourth channel is the state when the additional phase shift is 60 degrees.
  • S21 Determine a second phase difference between a debugging signal and a reference signal of each of the n-1 channels according to a difference between a target phase difference and a reference phase difference.
  • the reference signal is a debugging signal in the reference channel.
  • FIG. 4 is a schematic flowchart of a method for determining a first phase difference according to an embodiment of the present application. As shown in the figure, the method includes:
  • the intermediate synthesized signal is a synthesized signal synthesized by the debugging signals in the n-1 channels except the k-th channel.
  • the amplitude of the debugging signal in the k-th channel, and the amplitude of the intermediate synthesized signal combined with the vector algorithm, determine the The first phase difference between the debug signal and the reference signal.
  • the method of determining the phase difference between the debugging signal in the k-th channel and the intermediate synthesized signal, the amplitude of the debugging signal in the k-th channel, and the amplitude of the intermediate synthesized signal in step S201 includes:
  • S2011 Obtain a first power of a first synthesized signal, and determine an amplitude of the first synthesized signal according to the first power.
  • S2013 Acquire a third power of the third synthesized signal, and determine an amplitude of the third synthesized signal according to the third power;
  • the first synthesized signal is a synthesized signal synthesized by the debugging signals of the n channels when the phase shifter of the k-th channel is in the first phase state
  • the second synthesized signal is a phase shift of the k-th channel.
  • the synthesized signal of the n-channel debugging signals is synthesized in the second phase state
  • the third synthesized signal is the n-channel debugging signal synthesis of the k-th phase shifter in the third phase state.
  • the synthesized signal, the first phase state, the second phase state, and the third phase state are states of the phase shifter when different additional phase shifts are performed.
  • the calibration process after obtaining the first power of the first synthesized signal, determine the amplitude of the first synthesized signal according to the relationship between the signal power and the signal amplitude, and then adjust the phase shift of the k-th channel An additional phase shift of the modulator, adjusting the phase shifter of the k-th channel from a first phase state to a second phase state, acquiring a second power of the second synthesized signal and determining an amplitude of the second synthesized signal, Then continue to adjust the additional phase shift of the phase shifter of the k-th channel, adjust the phase shifter of the k-th channel from the second phase state to the third phase state, obtain the third power of the third synthesized signal, and determine An amplitude of the third synthesized signal.
  • FIG. 6 is a schematic diagram of an array antenna multi-channel phase calibration system according to an embodiment of the present application.
  • the array antenna is in a receiving mode, a signal source is connected to a transmitting antenna, and a power meter is connected to the array antenna.
  • the transmitting antenna transmits a test signal to the array antenna.
  • the array antenna simultaneously opens n channels, and transmits n debugging signals after passing through the n channels to the power division network, where the n debugging signals correspond to the n channels one by one.
  • the power division network combines n debugging signals into a composite signal and inputs it into a power meter.
  • the power meter measures the power of the composite signal and determines the amplitude of the composite signal according to the relationship between the power of the composite signal and the amplitude.
  • the relationship between power and amplitude is:
  • M is the amplitude of the composite signal
  • P is the power of the composite signal
  • Rs is the impedance of the array antenna.
  • the power meter obtains the second power of the second synthesized signal, and then determines the second amplitude of the second synthesized signal; and then adjusts the phase shifter in the kth channel to a third phase state, and the power division network changes the kth
  • the phase shifter in the channel is in the third phase state
  • the debugging signals in the n channels are synthesized into the third synthesized signal
  • the power meter obtains the third power of the third synthesized signal, and then determines the third amplitude of the third synthesized signal.
  • S2014 Determine the phase difference between the debug signal in the k-th channel and the intermediate synthesized signal according to the three amplitudes of the three synthesized signals in the three different phase states according to the phase shifter of the k-th channel, and the k-th channel.
  • the amplitude of the debug signal in the channel and the amplitude of the intermediate synthesized signal are the phase difference between the debug signal in the k-th channel and the intermediate synthesized signal according to the three amplitudes of the three synthesized signals in the three different phase states according to the phase shifter of the k-th channel, and the k-th channel.
  • n is equal to 4 as an example, and the array antenna multi-channel phase calibration method provided in this application is described in detail.
  • a signal may be a signal vector.
  • FIG. 7 is a schematic diagram showing a relationship between a debugging signal and a reference signal of each channel of an array antenna by using a signal vector. versus Respectively indicates the debugging signals in the four channels of the first channel to the fourth channel of the array antenna before being calibrated.
  • the signal vector versus Can be synthesized to obtain a synthesized vector
  • Signal vector versus Intermediate composition vector can be synthesized According to the cosine theorem shown in Figure 8, the following relationship exists in the triangle ABC shown in Figure 8:
  • the angle ⁇ is the angle between the side AC and the side BC in the triangle
  • a is the side length of the side BC
  • b is the side length of the side AC
  • c is the side length of the side AB.
  • the synthesized vector The magnitude of K can be determined by the power of the composite signal measured by a power meter, assuming a signal vector
  • the magnitude is X 4 , the middle composite vector Amplitude C, signal vector With intermediate composite vector
  • the angle is set to ⁇ , in vector Vector And vector Applying the cosine theorem to a vector triangle consisting of the following formulas:
  • Equation 2 the intermediate synthesis vector
  • Equation 3 the signal vector
  • the magnitude X 4 is equivalent to the side length b
  • the magnitude K is equivalent to the side length c.
  • the step of determining the first phase difference between the debug signal and the reference signal in the k-th channel includes:
  • FIG. 9 is a schematic diagram of the relationship among the signal vector, the intermediate composite vector, and the composite vector in the four channels of the array antenna.
  • the magnitude of K 1 may be determined by the first power of the first composite signal power was measured, assuming signal vector The amplitude is A 4 and the intermediate composite vector is Amplitude of C 4 , signal vector With intermediate composite vector Is set to ⁇ 4 , then the vector Vector And vector Applying the cosine theorem to the vector triangles, the following formula can be obtained according to formula 2:
  • the intermediate composite vector can be obtained from formula 3, formula 4, formula 5, and ⁇ 4 Amplitude C 4 and signal vector The magnitude of A 4 .
  • the signal vector can be determined according to the above formula 10 With reference vector Angle between That is the first phase difference between the debug signal and the reference signal in the fourth channel.
  • phase difference between the debug signal in the second channel and the reference limit number in the first phase state Until the first phase difference between the debug signal and the reference signal in the first channel of the phase shifter in the first phase state is obtained
  • the order of determining the phase difference between the signals in the first channel to the fourth channel and the reference signal is only an example, and cannot be understood as a specific limitation.
  • the debug signal in the first channel is the reference signal
  • the signal vector in the first channel With reference vector Angle between Is the phase difference between the reference signal and the reference signal in the first channel, that is, the reference phase difference, and the signal vectors in the other three channels
  • the angle between them can be obtained by the following formula:
  • ⁇ k1 is the angle between the signal vector of the debug signal and the signal vector of the reference signal in the k-th channel is the difference between the target phase difference and the reference phase difference of the debug signal in the k-th channel.
  • the additional phase of the phase shifter Move the angle corresponding to the original state to increase or decrease (for example, ⁇ k1 decreases when it is greater than 0, and increases when it is less than 0), and the phases of the debugging signals in the other three channels are aligned to The phases are the same.
  • FIG. 10 shows an effect diagram after calibrating the signals in each channel by implementing the multi-channel phase calibration method provided by the present application.
  • the phase shifter may directly phase-shift the received analog signals, such as phase shifting of signals in each channel using resistance-capacitance phase shifting, transformer phase shifting, and inductive voltage divider shifting. It is also possible to digitize the received analog signal first, use a digital phase shifter to perform phase shifting, and then convert the signal after the phase shifting to an analog signal, and the present application does not limit the specific manner of phase shifting the signal by the phase shifter.
  • the additional phase shift of the second phase state relative to the first phase state or the third phase state relative to the second phase state may be ⁇ / 2, or ⁇ / 8, ⁇ / 6, ⁇ / 5, ⁇ / 4, ⁇ / 3, 2 ⁇ / 3, ⁇ , 5 ⁇ / 4, 3 ⁇ / 2, 7 ⁇ / 4, etc. Be specific.
  • FIG. 11 is another array antenna provided by an embodiment of the present application.
  • Schematic diagram of the channel phase calibration system where the signal source is connected to the input end of the array antenna power division network.
  • the power division network divides the signal sent by the signal source into n signals according to the power equally or unequally.
  • the channel outputs to the n transmitting antennas of the array antenna.
  • the n transmitting antennas of the array antenna transmit n identical test signals to a single receiving antenna connected to the power meter, and the single receiving antenna receives the n test signals through space power synthesis.
  • the method synthesizes a synthesized signal, and sends the synthesized signal to a power meter.
  • a method for calibrating a signal phase in each channel of the array antenna is the same as when the array antenna is in a receiving mode, which is not described in detail in the embodiment of the present application.
  • n channels of the array antenna are opened at the same time to receive or transmit signals.
  • the debugging signals in each channel are obtained after interference including mutual coupling effects. Therefore, the above method is adopted.
  • the determined phase difference between the debug signal and the reference signal in each channel is the phase difference obtained under the condition of mutual coupling effect, that is, the phase difference exists due to the mutual coupling effect between channels. Therefore, according to the When the second phase difference obtained by the method is used to calibrate the array antenna, the phase difference of the signals between the channels caused by the mutual coupling effect can be compensated, and the influence of the mutual coupling effect on the phase of the signal in the channel can be overcome in the phase alignment of the traditional array antenna channel calibration.
  • the vector network analyzer is used for calibration in the traditional calibration scheme
  • the multimeter in the radio frequency field when the vector network analyzer is called the king of instruments is expensive.
  • a signal source can be used.
  • power meter replaces the vector network analyzer in the traditional calibration scheme, which can reduce the hardware cost during calibration.
  • the present application also provides an array antenna multi-channel phase calibration device.
  • the phase calibration device 100 includes a determination unit 101 and an adjustment unit 102.
  • the processing unit 101 is configured to determine a first phase difference between a debugging signal and a reference signal of each of the n channels of the array antenna when n channels of the array antenna are enabled, where the first phase difference Including a reference phase difference and a target phase difference, the reference phase difference is a phase difference between a debug signal of the reference channel in the n channels and the reference signal, and the target phase difference is a division of the reference channel
  • the processing unit 101 is further configured to determine a second phase difference between a debugging signal and a reference signal of each of the n-1 channels according to a difference between a target phase difference and a reference phase difference.
  • the reference signal is the debug signal in the reference channel;
  • the adjusting unit 102 is configured to adjust a phase shifter in each of the n-1 channels according to a second phase difference between a debugging signal and a reference signal of each of the n-1 channels, So that the phase of the debug signal in each of the n-1 channels is the same as the phase of the reference signal.
  • the phase calibration device further includes a power acquisition unit 103, which is configured to acquire the power of a synthesized signal synthesized by the n debugging signals in the n channels.
  • the determining unit 101 is configured to support a multi-channel phase calibration device to perform steps S20 and S21 in FIG. 2, steps S201 and S202 in FIG. 4, and step S2014 in FIG. 5.
  • step S22 in FIG. 2 is performed.
  • the power obtaining unit 103 is configured to obtain the first power of the first composite signal in step S2011, and obtain the first power of the second composite signal in step S2012.
  • the second power and the third power of the third composite signal are obtained in step S2013.
  • the determining unit 101 may be a processor or a controller, for example, a central processing unit (CPU), or a combination of a CPU and a hardware chip.
  • the above hardware chip may be an application-specific integrated circuit (ASIC), a programmable logic device (PLD), or a combination thereof.
  • the PLD may be a complex programmable logic device (CPLD), a field-programmable gate array (FPGA), a generic array logic (GAL), or any combination thereof.
  • the power acquisition unit 103 may be a device such as a power meter capable of measuring signal power.
  • the multi-channel phase calibration device includes a hardware structure and / or a software module corresponding to each function.
  • this application can be implemented in the form of hardware or a combination of hardware and computer software. Whether a certain function is performed by hardware or computer software-driven hardware depends on the specific application and design constraints of the technical solution. Professional technicians may use different methods to implement the described functions for each specific application, but such implementation should not be considered beyond the scope of this application.
  • the functional units of the multi-channel phase calibration device may be divided according to the foregoing method example.
  • each functional unit may be divided corresponding to each function, or two or more functions may be integrated into one processing unit.
  • the above integrated unit may be implemented in the form of hardware or in the form of software functional unit. It should be noted that the division of the units in the embodiments of the present application is schematic, and is only a logical function division. In actual implementation, there may be another division manner.
  • FIG. 13 is a schematic structural diagram of a phase calibration device according to an embodiment of the present application.
  • the phase calibration device 300 includes at least a processor 310, a transceiver 320, and a power measurement module 330.
  • the memory 340, the processor 310, the transceiver 320, the power measurement module 330, and the memory 340 are connected through a bus 350.
  • the processor 310 may be a central processing unit (CPU), or a combination of a CPU and a hardware chip.
  • the above hardware chip may be an application-specific integrated circuit (ASIC), a programmable logic device (PLD), or a combination thereof.
  • the PLD may be a complex programmable logic device (CPLD), a field-programmable gate array (FPGA), a generic array logic (GAL), or any combination thereof.
  • the transceiver 320 may include a receiver and a transmitter, for example, a radio frequency module.
  • the processor 310 described below receives or sends a message. Specifically, it can be understood that the processor 310 receives or sends a message through the transceiver. .
  • the power measurement module 330 may be a module capable of measuring signal power, such as a power meter.
  • the memory 340 includes, but is not limited to, Random Access Memory (RAM), Read-Only Memory (ROM), or Erasable Programmable Read-Only Memory (EPROM). Or flash memory), the memory 340 is used to store related instructions and data, and can transmit the stored data to the processor 310.
  • RAM Random Access Memory
  • ROM Read-Only Memory
  • EPROM Erasable Programmable Read-Only Memory
  • flash memory the memory 340 is used to store related instructions and data, and can transmit the stored data to the processor 310.
  • the receiver in the transceiver 320 receives the synthesized signal synthesized by the debugging signals of the n channels of the array antenna, and sends the synthesized signal to the power acquisition module 330.
  • the power acquisition module 330 measures the power of the synthesized signal and transmits the synthesized signal.
  • Power is sent to the processor 310, and the processor 310 can determine the difference between the debug signal and the reference signal in each channel of the array antenna according to the different power values of the phase shifter in each phase of the array antenna in different phase states. Phase difference.
  • phase difference For specific implementation of each operation of the phase calibration device, refer to the foregoing method embodiments, and details are not described herein again.
  • the computer program product includes one or more computer instructions.
  • the computer may be a general-purpose computer, a special-purpose computer, a computer network, or other programmable devices.
  • the computer instructions may be stored in a computer-readable storage medium, or transmitted from one computer-readable storage medium to another computer-readable storage medium, for example, the computer instructions may be from a website site, a computer, a server, or a data center.
  • the computer-readable storage medium may be any available medium that can be accessed by a computer or a data storage device such as a server, a data center, or the like that includes one or more available medium integration.
  • the usable medium may be a magnetic medium (for example, a floppy disk, a hard disk, a magnetic tape), an optical medium (for example, a DVD), or a semiconductor medium (for example, a solid state disk (Solid State Disk) (SSD)).

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Abstract

本申请实施例公开了一种相位校准方法、相关装置及设备。方法包括：启用阵列天线的n个通道，其中，n为大于或等于2的正整数，确定所述n个通道中基准通道中的调试信号与参考信号之间的基准相位差，以及除所述基准通道之外的其他n-1个通道中的调试信号与所述参考信号之间的目标相位差，基于所述n-1个通道各自的目标相位差与所述基准相位差之间的差值，调整所述n-1个通道中每个通道中的移相器，以使得所述n-1个通道中每个通道的调试信号的相位与所述基准通道的调试限号的相位相同。本申请实施例通过在启用阵列天线n个通道的情况下对阵列天线通道相位进行校准，能够克服阵列天线通道相位校准中通道间互耦效应对通道中信号相位的影响。

Description

相位校准方法、相关装置及设备 技术领域
本申请涉及天线技术领域，尤其涉及阵列天线多通道相位校准方法、相关装置及设备。
背景技术
天线作为无线电系统中一种必需的能量转化器件，它能够高效率地发射和接收电磁波。阵列天线是将工作在同一频率的两个或者两个以上的单个天线，按照一定的要求进行空间排列构成的天线，其中，每个天线对应一个通道，每个通道用于传输对应天线接收到的信号或者将待发送信号传输至对应天线。由于阵列天线具有提供灵活辐射方向图、方便调整波束宽度以及提高天线增益等优点，阵列天线已被广泛应用于各种通信系统与雷达系统中。
但是在实际应用中，由于元器件的差异、电路设计和加工制造差异、通道间的耦合效应等因素的影响，阵列天线各通道之间通常存在相位不一致的问题，因此必须对阵列天线各通道中信号的相位加以校正，以使得阵列天线各通道中信号的相位一致，但是，传统的阵列天线相位校准方法无法克服通道间耦合效应对通道中信号相位的影响。
发明内容
本申请实施例提供一种相位校准方法、相关装置及设备，能够克服传统阵列天线相位校准过程中通道间耦合效应对通道中信号相位的影响。
第一方面，本申请实施例提供一种阵列天线多通道相位校准方法，方法包括：
启用阵列天线的n个通道，确定所述n个通道中每个通道的调试信号与参考信号之间的第一相位差，所述第一相位差包括基准相位差与目标相位差，所述基准相位差为所述n个通道中的基准通道的调试信号与所述参考信号之间的相位差，所述目标相位差为除所述基准通道之外的其他n-1个通道各自的调试信号与所述参考信号之间的相位差，其中，n为大于或者等于2的正整数；
根据目标相位差与基准相位差之间的差值，确定所述n-1个通道中每个通道的调试信号与基准信号之间的第二相位差，所述基准信号为所述基准通道中的调试信号；
根据所述n-1个通道中每个通道的调试信号与基准信号之间的第二相位差，调整所述n-1个通道中每个通道中的移相器，以使得所述n-1个通道中每个通道的调试信号的相位与所述基准信号的相位相同。
由上可见，上述阵列天线通道校准方法中，同时打开阵列天线的n个通道，首先确定每个通道中的调试信号与参考信号之间的第一相位差，然后以基准通道中的调试信号作为基准信号，根据每个通道中的调试信号与参考信号之间的第一相位差，确定除基准通道之外的其余n-1个通道中的调试信号与基准信号之间的第二相位差，进而根据所述n-1个通道中每个通道的调试信号与基准信号之间的第二相位差调整所述n-1个通道中每个通道中的移相器，即可通过移相器将每个通道中调试信号的相位校准至与基准信号相同，由于该方法在校准的过程中，阵列天线的n个通道都打开，每个通道中的调试信号与参考信号之间的第一相位差以及每个通道中调试信号与基准信号之间的第二相位差都是在存在通道间耦合效应干扰下得到的结果，通道间耦合效应对相位的影响在校准过程中已被计算在内，因此该方法能够对互耦效应造成的通道间信号的相位差进行补偿，从而克服传统阵列天线通道相位校准中通道间 耦合效应对通道中信号相位的影响。
在一种可能的实施方式中，第k个第一相位差是根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值确定的，其中，所述第k个通道为所述n个通道中的任意一个通道，所述中间合成信号为除第k个通道之外的其余n-1个通道中的调试信号合成的合成信号，k为小于或者等于n的正整数。
在一种可能的实施方式中，第k个第一相位差是根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值，结合矢量运算法则确定的。
在一种可能的实施方式中，确定所述第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值，包括：
确定所述第k个通道的移相器在至少三个不同相位状态时，所述n个通道的调试信号合成的至少三个合成信号的幅值，其中，所述不同相位状态为所述移相器在不同附加相移时的状态，所述至少三个合成信号的幅值与所述至少三个不同相位状态一一对应；
根据所述至少三个合成信号的幅值，结合余弦定理确定所述第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值。
在一种可能的实施方式中，所述确定所述第k个通道的移相器在至少三个不同相位状态时，所述n个通道的调试信号合成的至少三个合成信号的幅值，包括：
获取第一合成信号的第一功率，根据所述第一功率确定所述第一合成信号的幅值，所述第一合成信号为第k个通道的移相器在第一相位状态时所述n个通道的调试信号合成的合成信号；
获取第二合成信号的第二功率，根据所述第二功率确定所述第二合成信号的幅值，所述第二合成信号为第k个通道的移相器在第二相位状态时所述n个通道的调试信号合成的合成信号；
获取第三合成信号的第三功率，根据所述第三功率确定所述第三合成信号的幅值，所述第三合成信号为第k个通道的移相器在第三相位状态时所述n个通道的调试信号合成的合成信号。
在一种可能的实施方式中，根据至少三个合成信号的幅值，结合余弦定理确定第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值，包括：
根据如下公式确定第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值：
Figure PCTCN2018092928-appb-000001
其中，C k为所述中间合成信号的幅值，A k为所述第k个通道中的调试信号的幅值，θ k为所述第k个通道中的调试信号与中间合成信号之间的相位差，γ 1为所述移相器在第一相位状态时的附加相移，γ 2为所述移相器在第二相位状态时的附加相移，γ 3为所述移相器在第三相位状态时的附加相移，K 1为所述第一合成信号的幅值，K 2为所述第二合成信号的幅值，K 3为所述第三合成信号的幅值。
在一种可能的实施方式中，所述第一合成信号的第一功率、所述第二合成信号的第二功 率以及所述第三合成信号的第三功率是从功率计获取的。
在一种可能的实施方式中，根据如下公式确定所述第k个通道中的调试信号与参考信号之间的第一相位差：
Figure PCTCN2018092928-appb-000002
其中，A k为所述第k个通道中的调试信号的幅值，C k为所述中间合成信号的幅值，θ k为所述第k个通道中调试信号与中间合成信号之间的相位差，
Figure PCTCN2018092928-appb-000003
表示所述第k通道中的调试信号，
Figure PCTCN2018092928-appb-000004
表示所述中间合成信号，
Figure PCTCN2018092928-appb-000005
为第k个通道中的调试信号与参考信号之间的第一相位差。
在一种可能的实施方式中，所述第一相位状态为所述第k个通道的移相器的附加相移为0时的状态；所述第二相位状态为所述第k个通道的移相器的附加相移为π/2时的状态；所述第三相位状态为所述第k个通道的移相器的附加相移为π时的状态。
第二方面，本申请实施例提供一种多通道相位校准装置，其特征在于，所述校准装置包括确定单元和调整单元：
所述确定单元，用于在启动阵列天线n个通道时，确定阵列天线n个通道中的每个通道的调试信号与参考信号之间的第一相位差，所述第一相位差包括基准相位差与目标相位差，所述基准相位差为所述n个通道中的基准通道的调试信号与所述参考信号之间的相位差，所述目标相位差为除所述基准通道之外的其他n-1个通道各自的调试信号与所述参考信号之间的相位差，其中，n为大于或者等于2的正整数；
所述确定单元还用于根据目标相位差与基准相位差之间的差值，确定所述n-1个通道中每个通道的调试信号与基准信号之间的第二相位差，所述基准信号为所述基准通道中的调试信号；
所述调整单元，用于根据所述n-1个通道中每个通道的调试信号与基准信号之间的第二相位差调整所述n-1个通道中每个通道中的移相器，以使得所述n-1个通道中每个通道中的调试信号的相位与所述基准信号的相位相同。
在一种可能的实施方式中，第k个第一相位差是根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值确定的，其中，所述第k个通道为所述n个通道中的任意一个通道，所述中间合成信号为除第k个通道之外的其余n-1个通道中的调试信号合成的合成信号，k为小于或者等于n的正整数。
在一种可能的实施方式中，第k个第一相位差是根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值，结合矢量运算法则确定的。
在一种可能的实施方式中，所述确定单元还用于：
确定所述第k个通道的移相器在至少三个不同相位状态时，所述n个通道的调试信号合成的至少三个合成信号的幅值，其中，所述不同相位状态为所述移相器在不同附加相移时的状态，所述至少三个合成信号的幅值与所述至少三个不同相位状态一一对应；
根据所述至少三个合成信号的幅值，结合余弦定理确定所述第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值。在一种可能的实施方式中，所述装置还包括：
在一种可能的实施方式中，所述装置还包括：功率获取单元，用于获取第一合成信号的 第一功率，所述第一合成信号为第k个通道的移相器在第一相位状态时所述n个通道的调试信号合成的合成信号；
所述确定单元还用于：根据所述第一功率确定所述第一合成信号的幅值；
所述功率获取单元还用于：获取第二合成信号的第二功率，所述第二合成信号为第k个通道的移相器在第二相位状态时所述n个通道的调试信号合成的合成信号；
所述确定单元还用于：根据所述第二功率确定所述第二合成信号的幅值；
所述功率获取单元还用于：获取第三合成信号的第三功率，所述第三合成信号为第k个通道的移相器在第三相位状态时所述n个通道的调试信号合成的合成信号；
在一种可能的实施方式中，所述确定单元还用于：
根据如下公式确定第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值：
Figure PCTCN2018092928-appb-000006
其中，C k为所述中间合成信号的幅值，A k为所述第k个通道中的调试信号的幅值，θ k为所述第k个通道中的调试信号与中间合成信号之间的相位差，γ 1为所述移相器在第一相位状态时的附加相移，γ 2为所述移相器在第二相位状态时的附加相移，γ 3为所述移相器在第三相位状态时的附加相移，K 1为所述第一合成信号的幅值，K 2为所述第二合成信号的幅值，K 3为所述第三合成信号的幅值。
在一种可能的实施方式中，所述功率获取单元为功率计。
所述确定单元还用于：根据所述第三功率确定所述第三合成信号的幅值。
在一种可能的实施方式中，所述确定单元还用于：
根据如下公式确定所述第k个通道中的调试信号与参考信号之间的第一相位差：
Figure PCTCN2018092928-appb-000007
其中，A k为所述第k个通道中调试信号的幅值，C k为所述中间合成信号的幅值，θ k为所述第k个通道中调试信号与中间合成信号之间的相位差，
Figure PCTCN2018092928-appb-000008
表示所述第k通道中的调试信号，
Figure PCTCN2018092928-appb-000009
表示所述中间合成信号，
Figure PCTCN2018092928-appb-000010
为第k个通道中调试信号与参考信号之间的第一相位差。
在一种可能的实施方式中，所述第一相位状态为所述第k个通道的移相器的附加相移为0时的状态；所述第二相位状态为所述第k个通道的移相器的附加相移为π/2时的状态；所述第三相位状态为所述第k个通道的移相器的附加相移为π时的状态。
第三方面，本申请实施例提供一种相位校准设备，包括处理器、收发器、功率测量模块和存储器，所述处理器、收发器、功率测量模块和存储器相互连接，其中，所述存储器用于存储应用程序代码，所述处理器被配置用于调用所述程序代码，执行如第一方面所述的方法。
第四方面，本申请实施例提供一种计算机可读存储介质，所述计算机可读存储介质存储有计算机程序，其特征在于，所述计算机程序被处理器执行时实现如第一方面所述的方法。
上述阵列天线多通道相位校准方法中，同时打开阵列天线的n个通道接收或者发送信号，每个通道中的调试信号都是在经过包括互耦效应在内的干扰后得到的，因此通过上述方法确定的每个通道中调试信号与基准信号之间的第二相位差是在存在互耦效应的情况下得到的相 位差，即该第二相位差中存在由于互耦效应引起的相位差，因此根据该方法得到的第二相位差对阵列天线进行校准时，能够对互耦效应造成的相位差进行补偿，克服传统阵列天线相位校准中互耦效应对通道中信号相位的影响。
附图说明
为了更清楚地说明本申请实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍。
图1是本申请实施例提供的一种阵列天线的结构示意图。
图2是现有技术通过矢量网络分析仪对阵列天线进行相位校准的示意图。
图3是本申请实施例提供的一种阵列天线多通道相位校准方法的流程示意图。
图4是本申请实施例提供的一种确定第一相位差的方法的流程示意图。
图5是本申请实施例提供的一种确定第k个通道中调试信号与中间合成信号之间的相位差、第k通道中调试信号的幅值以及中间合成信号的幅值的方法的流程示意图。
图6是本申请实施例提供的一种阵列天线多通道相位校准系统的示意图。
图7是本申请实施例提供的一种用信号矢量表示调试信号与参考信号之间关系的示意图。
图8是本申请实施例提供的一种余弦定理的示意图。
图9是本申请实施例提供的一种阵列天线四个通道中的信号矢量、中间合成矢量以及合成矢量之间的关系示意图。
图10是通过实施本申请提供的多通道相位校准方法对各通道中信号进行校准后的效果图。
图11是本申请实施例提供的另一种阵列天线多通道相位校准系统的示意图。
图12是本申请实施例提供的一种阵列天线多通道相位校准装置的结构示意图。
图13是本申请实施例提供的一种阵列天线多通道相位校准设备的结构示意图。
具体实施方式
为了便于理解，下面首先对阵列天线如何进行信号发送以及信号接收进行介绍。
阵列天线包括多个通道，每个通道都是一个射频电路，包括天线、馈线、放大器以及移相器等，如图1所示，图1是本申请实施例提供的一种阵列天线的结构示意图。在阵列天线处于接收状态时，阵列天线将接收到的信号通过馈线传输至高频放大器和中频放大器，经过放大后再通过移相器对信号进行相位补偿以得到满足相位要求的信号，最后由功分网络将各个通道中的信号合成为一路信号，作为阵列天线最终接收到的信号。在阵列天线处于发射状态时，信号经功分网络将待发送信号按照功率等分或者不等分的分成多路信号，再通过各个通道中的移相器对信号进行相位补偿以得到满足相位要求的信号，最后由中频放大器和高频放大器放大后经馈线传输至天线，进而由天线发射出去。
阵列天线通常采用功率合成技术将阵列天线多个通道发射或接收的信号合成为一路信号，在对不同通道中的信号进行合成时，各个通道中的信号会因为相位不一致而导致合成信号的幅值在不同时刻出现不同的增强或减弱(例如两个周期为2π的相同的信号在经过两个不同的通道后，若信号相位相差π，则在合成时合成信号的幅值可能为零)，从而对阵列天线的合成增益、方向图等辐射特性会造成严重影响，因此，必须保证阵列天线各个通道中信号相位 的一致。
为了克服阵列天线各通道相位不一致的问题，需要对阵列天线各通道中信号的相位进行校准，传统的阵列天线通道相位校准方法中，采用矢量网络分析仪分别测试阵列天线各个通道中信号的相位，然后将各个通道中信号的相位校准至相同。如图2所示，图2示出了通过矢量网络分析仪对阵列天线进行相位校准的示意图，其中，矢量网络分析仪的端口1接发射天线，端口2接阵列天线，发射天线用于发射由矢量网络分析仪中的信号源产生的测试信号，阵列天线接收测试信号，将除测试通道之外的其他通道关闭，并通过测试通道将接收到的测试信号传输至矢量网络分析仪，矢量网络分析仪对通过测试通道后的测试信号进行分析，得到通过测试通道后的测试信号的相位。例如测试阵列天线所有m(m为大于1正整数)个通道中的第j(j为小于或等于m的正整数)通道时，只打开第j通道而关闭其他m-1个通道，阵列天线仅能通过第j通道对应的天线接收测试信号，并将接收到的测试信号通过第j通道输入到矢量网络分析仪中，矢量网络分析仪分析通过第j通道之后的测试信号，得到通过第j通道之后的测试信号的相位。然后采用同样的方法，每次打开未测试通道中的一个通道作为测试通道，而关闭其余m-1个通道，通过矢量网络分析仪得到通过测试通道之后的测试信号的相位，最终得到m个通道中每个通道中信号的相位。最后选取m个通道中任意一个通道中的信号作为基准信号，根据矢量网络分析仪得到的各个通道中信号的相位，确定其余m-1个通道中的信号与基准信号之间的相位差，根据所述m-1个通道中每个通道中的信号与基准信号之间的相位差调整对应通道中移相器的附加相移，使每个通道中的信号在通过移相器时，能够通过移相器对通过的信号进行相位补偿，从而将每个通道中信号的相位校准至与基准信号的相位相同。
但在实际使用中，阵列天线的各个通道往往是同时打开以接收或发送信号，无论阵列天线中各天线是处于发射状态还是处于接收状态，每个通道中都会有一部分电磁能量辐射到其他通道中的部分通道或者全部通道，也会接收到来自其他通道中部分通道或者全部通道辐射的电磁能量，这种由于阵列天线通道之间的电磁能量交换引起的的互耦效应，会使各个通道中的信号相位发生不同程度的偏移而导致各个通道中信号的相位不一致，而上述传统的相位校准方法每次只打开一个通道而关闭其他通道，是一种单通道的相位校准方法，无法克服通道间互耦效应对通道中信号相位的影响。
为解决阵列天线通道之间互耦效应导致的各个通道中信号相位不一致的问题，本申请提供一种阵列天线多通道相位校准方法，请参见图3，图3是本申请实施例提供的一种阵列天线多通道相位校准方法的流程示意图，如图所示，该相位校准方法包括：
S20、启用阵列天线的n个通道，确定阵列天线n个通道中的每个通道的调试信号与参考信号之间的第一相位差。
其中，n为大于或者等于2的正整数，阵列天线同时启用n个通道，所述n个通道可以是阵列天线的部分通道，也可以是阵列天线的全部通道，所述调试信号为所述n个通道中每个通道接收到的测试信号在通过对应的通道之后的信号，每个通道对应的天线接收到的测试信号所携带的数据是相同的。所述第一相位差包括基准相位差与目标相位差，所述基准相位差为所述n个通道中的基准通道的调试信号与所述参考信号之间的相位差，所述目标相位差为除所述基准通道之外的n-1个通道各自的调试信号与所述参考信号之间的相位差。其中，所述基准通道为所述n个通道中的任意一个通道。
在一可能的实施例中，所述参考信号为所述n个通道中每个通道的移相器在第一相位状 态下，所述n个通道中的调试信号合成的合成信号。
本申请实施例中，上述各通道中移相器的第一相位状态，可以是移相器的附加相移为0度时的状态，即在对阵列天线进行多通道相位校准前，将所述n个通道中移相器的附加相移均调整为0度；也可以是上一次校准之后的状态，即在对阵列天线进行多通道相位校准前，所述n个通道中移相器的附加相移均不做调整，例如，校准阵列天线的四个通道，在上一次校准之后，第一通道至第四通道中移相器的附加相移分别为15度、26度、45度和60度，则在此次校准中，第一通道中移相器的第一相位状态为附加相移为15度时的状态，第二通道中移相器的第一相位状态为附加相移为26度时的状态，第三通道中移相器的第一相位状态为附加相移为45度时的状态，第四通道中移相器的第一相位状态为附加相移为60度时的状态。
S21、根据目标相位差与基准相位差之间的差值，确定所述n-1个通道中每个通道的调试信号与基准信号之间的第二相位差。其中，所述基准信号为所述基准通道中的调试信号。
S22、根据所述n-1个通道中每个通道的调试信号与基准信号之间的第二相位差，调整所述n-1个通道中每个通道中的移相器，以使得所述n-1个通道中每个通道中调试信号的相位与所述基准信号的相位相同。
根据上述步骤S21得到的n-1个第二相位差，调整与每个第二相位差对应的通道中的移相器的附加相移，以使所述n-1个通道中每个通道中的信号在通过移相器时，能够通过移相器对通道中的信号的相位进行补偿，从而使每个通道中的信号在通过移相器之后与基准信号的相位相同。
下面以所述n个通道中的第k(k为正整数，k＝1，2，…n)个通道为例，对上述步骤S20确定所述第一相位差的方法进行阐述，请参见图4，图4是本申请实施例提供的一种确定第一相位差的方法的流程示意图，如图所示，该方法包括：
S201、确定第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值。
其中，所述中间合成信号为除第k个通道之外的其余n-1个通道中调试信号合成的合成信号。
S202、根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中调试信号的幅值以及中间合成信号的幅值，结合矢量运算法则，确定第k个通道中的调试信号与参考信号之间的第一相位差。
请参见图5，上述步骤S201确定第k个通道中调试信号与中间合成信号之间的相位差、第k通道中调试信号的幅值以及中间合成信号的幅值的方法包括：
S2011、获取第一合成信号的第一功率，根据所述第一功率确定所述第一合成信号的幅值；
S2012、获取第二合成信号的第二功率，根据所述第二功率确定所述第二合成信号的幅值；
S2013、获取第三合成信号的第三功率，根据所述第三功率确定所述第三合成信号的幅值；
其中，所述第一合成信号为第k个通道的移相器在第一相位状态时所述n个通道的调试信号合成的合成信号；所述第二合成信号为第k个通道的移相器在第二相位状态时所述n个通道的调试信号合成的合成信号；所述第三合成信号为第k个通道的移相器在第三相位状态时所述n个通道的调试信号合成的合成信号，所述第一相位状态、所述第二相位状态与所述第三相位状态为移相器在不同附加相移时的状态。校准过程中，在获取所述第一合成信号的第一功率之后，根据信号功率与信号幅值之间的关系，确定所述第一合成信号的幅值，然后调整第k个通道的移相器的附加相移，将第k个通道的移相器由第一相位状态调整为第二相 位状态，获取所述第二合成信号的第二功率并确定所述第二合成信号的幅值，再继续调整第k个通道的移相器的附加相移，将第k个通道的移相器由第二相位状态调整为第三相位状态，获取所述第三合成信号的第三功率并确定所述第三合成信号的幅值。
在一可能的实施例中，采用信号源和功率计代替传统校准方案中的矢量网络分析仪，通过功率计分别获取上述第一合成信号、第二合成信号以及第三合成信号的功率，进而确定每个合成信号的幅值。如图6所示，图6是本申请实施例提供的一种阵列天线多通道相位校准系统的示意图，其中，阵列天线处于接收模式，信号源连接发射天线，功率计连接阵列天线，信号源通过发射天线向阵列天线发射测试信号，阵列天线同时打开n个通道，将通过所述n个通道后的n个调试信号传输至功分网络，其中，n个调试信号与n个通道一一对应，功分网络将n个调试信号合并为一个合成信号输入到功率计中，功率计通过测量合成信号的功率，根据合成信号的功率与幅值的关系确定合成信号的幅值，其中，合成信号的功率与幅值之间的关系为：
Figure PCTCN2018092928-appb-000011
其中，M为合成信号的幅值，P为合成信号的功率，Rs为阵列天线的阻抗。在确定第k个通道中调试信号与中间合成信号之间的相位差、第k个通道中调试信号的幅值以及中间合成信号的幅值时，功分网络将第k个通道中的移相器在第一相位状态时n个通道中的调试信号合成为第一合成信号后输送到功率计，功率计获取第一合成信号的第一功率，进而确定第一合成信号的第一幅值；然后将第k个通道中的移相器调整为第二相位状态，功分网络将第k个通道中的移相器在第二相位状态时n个通道中的调试信号合成为第二合成信号，功率计获取第二合成信号的第二功率，进而确定第二合成信号的第二幅值；再将第k个通道中的移相器调整为第三相位状态，功分网络将第k个通道中的移相器在第三相位状态时n个通道中的调试信号合成为第三合成信号，功率计获取第三合成信号的第三功率，进而确定第三合成信号的第三幅值。
S2014、根据第k个通道的移相器在三种不同相位状态下三个合成信号的三个幅值，结合余弦定理确定第k通道中调试信号与中间合成信号之间的相位差、第k通道中调试信号的幅值以及中间合成信号的幅值。
下面以n等于4为例，对本申请提供的阵列天线多通道相位校准方法进行详细介绍，在一具体的实施方式中，信号可以用信号矢量
Figure PCTCN2018092928-appb-000012
进行表示。如图7所示，图7为用信号矢量表示阵列天线每个通道的调试信号与参考信号之间关系的示意图，若信号矢量
Figure PCTCN2018092928-appb-000013
与
Figure PCTCN2018092928-appb-000014
分别表示未校准之前阵列天线第一通道至第四通道这四个通道中的调试信号，则根据矢量合成原理，信号矢量
Figure PCTCN2018092928-appb-000015
与
Figure PCTCN2018092928-appb-000016
可以合成得到合成矢量
Figure PCTCN2018092928-appb-000017
除第四通道中的信号矢量
Figure PCTCN2018092928-appb-000018
之外，信号矢量
Figure PCTCN2018092928-appb-000019
与
Figure PCTCN2018092928-appb-000020
可以合成中间合成矢量
Figure PCTCN2018092928-appb-000021
根据如图8所示的余弦定理，在如图8所示的三角形ABC中存在以下关系：
Figure PCTCN2018092928-appb-000022
其中，角α为三角形中边AC和边BC的夹角，a为边BC的边长，b为边AC的边长，c为边AB的边长。
则在图7中，合成矢量
Figure PCTCN2018092928-appb-000023
的幅值K可以通过功率计测得的合成信号的功率确定，假设信号矢量
Figure PCTCN2018092928-appb-000024
的幅值为X 4，中间合成矢量
Figure PCTCN2018092928-appb-000025
的幅值为C，信号矢量
Figure PCTCN2018092928-appb-000026
与中间合成矢量
Figure PCTCN2018092928-appb-000027
的夹角设为β，在矢量
Figure PCTCN2018092928-appb-000028
矢量
Figure PCTCN2018092928-appb-000029
以及矢量
Figure PCTCN2018092928-appb-000030
组成的矢量三角形中应用余弦定理，可得到如下的公式：
Figure PCTCN2018092928-appb-000031
其中，π-β相当于角α，中间合成矢量
Figure PCTCN2018092928-appb-000032
的幅值C相当于边长a，信号矢量
Figure PCTCN2018092928-appb-000033
的幅值X 4相当于边长b，合成矢量
Figure PCTCN2018092928-appb-000034
的幅值K相当于边长c。对公式1进行推导，可以得到：
Figure PCTCN2018092928-appb-000035
Figure PCTCN2018092928-appb-000036
根据上述原理，确定第k个通道中的调试信号与参考信号之间的第一相位差的步骤包括：
(1)以第四个通道为调试通道，即上述k等于4，在进行调试时，阵列天线四个通道的移相器在第一相位状态时，四个通道中的信号矢量分别为
Figure PCTCN2018092928-appb-000037
与
Figure PCTCN2018092928-appb-000038
这四个信号矢量合成得到第一合成矢量
Figure PCTCN2018092928-appb-000039
并把第一合成矢量
Figure PCTCN2018092928-appb-000040
作为参考矢量，即所述参考信号对应的矢量，除第四通道之外的三个通道中的信号矢量
Figure PCTCN2018092928-appb-000041
与
Figure PCTCN2018092928-appb-000042
合成得到中间合成矢量为
Figure PCTCN2018092928-appb-000043
如图9所示，图9为阵列天线四个通道中的信号矢量、中间合成矢量以及合成矢量之间的关系示意图，其中，第一合成矢量
Figure PCTCN2018092928-appb-000044
的幅值K 1可以通过功率计测得的第一合成信号的第一功率确定，假设信号矢量
Figure PCTCN2018092928-appb-000045
的幅值为A 4，中间合成矢量为
Figure PCTCN2018092928-appb-000046
的幅值为C 4，信号矢量
Figure PCTCN2018092928-appb-000047
与中间合成矢量
Figure PCTCN2018092928-appb-000048
的夹角设为θ 4，则在矢量
Figure PCTCN2018092928-appb-000049
矢量
Figure PCTCN2018092928-appb-000050
以及矢量
Figure PCTCN2018092928-appb-000051
组成的矢量三角形中应用余弦定理，根据公式2可以得到如下的公式：
Figure PCTCN2018092928-appb-000052
Figure PCTCN2018092928-appb-000053
(2)继续以第四个通道为调试通道，将第四个通道中移相器调整为第二相位状态，其中，第二相位状态相对于第一相位状态的附加相移为90度(即将移相器的附加相移在第一相位状态的基础上增加90度)，其他通道中的移相器的相位状态不变，阵列天线四个通道中信号矢量
Figure PCTCN2018092928-appb-000054
与
Figure PCTCN2018092928-appb-000055
可以合成得到第二合成矢量
Figure PCTCN2018092928-appb-000056
如图9所示，其中，第二合成矢量
Figure PCTCN2018092928-appb-000057
的幅值K 2可以通过功率计测得的第二合成信号的第二功率确定，信号矢量
Figure PCTCN2018092928-appb-000058
的幅值仍为A 4，如图9所示，则在矢量
Figure PCTCN2018092928-appb-000059
矢量
Figure PCTCN2018092928-appb-000060
以及矢量
Figure PCTCN2018092928-appb-000061
组成的矢量三角形中应用余弦定理，根据公式2得到如下的公式：
Figure PCTCN2018092928-appb-000062
Figure PCTCN2018092928-appb-000063
(3)继续以第四个通道为调试通道，将第四个通道中移相器调整为第三相位状态，其中，第二相位状态相对于第一相位状态的附加相移为180度(即将移相器的附加相移在第一相位状态的基础上增加180度)，其他通道中的移相器不变，阵列天线四个通道中的信号的信号矢量
Figure PCTCN2018092928-appb-000064
与
Figure PCTCN2018092928-appb-000065
可以合成得到第二合成矢量
Figure PCTCN2018092928-appb-000066
如图9所示，其中，第三合成矢量
Figure PCTCN2018092928-appb-000067
的幅值K 3可以通过功率计测得的第三合成信号的第三功率确定，信号矢量
Figure PCTCN2018092928-appb-000068
的幅值仍为A 4，则在矢量
Figure PCTCN2018092928-appb-000069
矢量
Figure PCTCN2018092928-appb-000070
以及矢量
Figure PCTCN2018092928-appb-000071
组成的矢量三角形中应用余弦定理，根据公式2得到如下的公式：
Figure PCTCN2018092928-appb-000072
将上述公式3与公式5两边分别做减法运算，可得到：
Figure PCTCN2018092928-appb-000073
Figure PCTCN2018092928-appb-000074
将上述公式3与公式4两边分别做减法运算，可得到：
Figure PCTCN2018092928-appb-000075
将公式6带入公式7，可得到：
Figure PCTCN2018092928-appb-000076
根据上述公式6以及公式8，可以得到
Figure PCTCN2018092928-appb-000077
Figure PCTCN2018092928-appb-000078
在得到信号矢量
Figure PCTCN2018092928-appb-000079
与参考矢量
Figure PCTCN2018092928-appb-000080
之间的夹角θ 4之后，即可由公式3、公式4、公式5以及θ 4得到中间合成矢量
Figure PCTCN2018092928-appb-000081
的幅值C 4以及信号矢量
Figure PCTCN2018092928-appb-000082
的幅值A 4。
(4)由步骤(3)确定信号矢量
Figure PCTCN2018092928-appb-000083
与中间合成矢量
Figure PCTCN2018092928-appb-000084
之间的夹角θ 4中间合成矢量
Figure PCTCN2018092928-appb-000085
的幅值C 4以及信号矢量
Figure PCTCN2018092928-appb-000086
的幅值A 4之后，可以将信号矢量
Figure PCTCN2018092928-appb-000087
表示为
Figure PCTCN2018092928-appb-000088
将参考矢量
Figure PCTCN2018092928-appb-000089
表示为
Figure PCTCN2018092928-appb-000090
设信号矢量
Figure PCTCN2018092928-appb-000091
与参考矢量
Figure PCTCN2018092928-appb-000092
之间的夹角为
Figure PCTCN2018092928-appb-000093
则根据向量间夹角的计算公式，可以得到：
Figure PCTCN2018092928-appb-000094
Figure PCTCN2018092928-appb-000095
根据上述公式10可以确定信号矢量
Figure PCTCN2018092928-appb-000096
与参考矢量
Figure PCTCN2018092928-appb-000097
之间的夹角
Figure PCTCN2018092928-appb-000098
即为第四个通道中的调试信号与参考信号之间的第一相位差。
在确定信号矢量
Figure PCTCN2018092928-appb-000099
与参考矢量
Figure PCTCN2018092928-appb-000100
之间的夹角
Figure PCTCN2018092928-appb-000101
之后，将第四个通道中的移相器调整为第一相位状态，再以第三通道为调试通道，根据上述步骤，在第三个通道的移相器在三种不同相位状态的情况下，确定移相器在第一相位状态下第三个通道中的调试信号与参考信号之间的第一相位差
Figure PCTCN2018092928-appb-000102
然后再将第三个通道中的移相器调整为第一相位状态，以第二个通道为调试通道，在第二个通道的移相器在三种不同相位状态的情况下，确定移相器在第一相位状态下第二个通道中的调试信号与参考限号之间的第一相位差
Figure PCTCN2018092928-appb-000103
直至求得移相器在第一相位状态下第一个通道中的调试信号与参考信号之间的第一相位差
Figure PCTCN2018092928-appb-000104
本申请实施例中，上述确定第一通道至第四通道中的信号与参考信号之间的相位差的顺序，只是一种示例，不能理解为具体限定。
在确定信号矢量
Figure PCTCN2018092928-appb-000105
至
Figure PCTCN2018092928-appb-000106
与参考矢量
Figure PCTCN2018092928-appb-000107
之间的夹角
Figure PCTCN2018092928-appb-000108
至
Figure PCTCN2018092928-appb-000109
之后，若选择以第一个通道为基准通道，则第一个通道中的调试信号为基准信号，第一个通道中信号矢量
Figure PCTCN2018092928-appb-000110
与参考矢量
Figure PCTCN2018092928-appb-000111
之间的夹角
Figure PCTCN2018092928-appb-000112
为第一个通道中的基准信号与参考信号之间的相位差，即基准相位差，另外三个通道中信号矢量与基准通道中的信号矢量
Figure PCTCN2018092928-appb-000113
之间的夹角可以通过以下公式得到：
Figure PCTCN2018092928-appb-000114
其中，
Figure PCTCN2018092928-appb-000115
为除第一个通道之外第k个通道中信号矢量与参考矢量之间的夹角，即除基准通道 之外第k通道中的调试信号与参考信号之间的目标相位差，α k1为第k个通道中调试信号的信号矢量与基准信号的信号矢量之间的夹角，即第k个通道中的调试信号的目标相位差与基准相位差之间的差值。确定另外三个通道中的目标相位差与基准相位差之间的差值之后，根据另外三个通道每个通道中目标相位差与基准相位差之间的差值，将移相器的附加相移在原来状态的基础上增加或者减小(例如α k1大于0时减小，小于0时增大)对应的角度，即可将另外三个通道中的调试信号的相位校准至与基准信号的相位相同，如图10所示，图10示出了通过实施本申请提供的多通道相位校准方法对各通道中信号进行校准后的效果图。
本申请实施例中，上述移相器可以是直接对接收到模拟信号进行移相，如采用阻容移相、变压器移相以及感应分压器移相等方法对各通道内的信号进行移相，也可以是先将接收到的模拟信号进行数字化，采用数字移相器进行移相后再将移相之后的信号转换为模拟信号，本申请不限定移相器对信号移相的具体方式。
本申请实施例中，上述确定调试信号与参考信号之间的第一相位差时，第二相位状态相对于第一相位状态或第三相位状态相对于第二相位状态的附加相移可以是π/2，也可以是π/8、π/6、π/5、π/4、π/3、2π/3、π、5π/4、3π/2、7π/4等，本申请实施例不做具体限定。
本申请另一实施例中，上述原理也可以用于阵列天线处于发射模式时的多通道之间的相位校准，如图11所示，图11是本申请实施例提供的另一种阵列天线多通道相位校准系统的示意图，其中，信号源接阵列天线功分网络的输入端，功分网络将信号源发送的信号按照功率等分或者不等分的分成n路信号，通过阵列天线的n个通道输出到阵列天线的n个发射天线，阵列天线的n个发射天线向功率计连接的单个接收天线发射n个相同的测试信号，所述单个接收天线接收所述n个测试信号通过空间功率合成方法合成的合成信号，将所述合成信号发送给功率计。在本申请实施例中，实现阵列天线各通道中信号相位校准的方法和阵列天线处于接收模式时相同，本申请实施例不再详细阐述。
上述阵列天线多通道相位校准方法中，同时打开阵列天线的n个通道接收或者发送信号，每个通道中的调试信号都是在经过包括互耦效应在内的干扰后得到的，因此通过上述方法确定的每个通道中调试信号与基准信号之间的相位差是在存在互耦效应的情况下得到的相位差，即该相位差中存在由于通道间互耦效应引起的相位差，因此根据该方法得到的第二相位差对阵列天线进行校准时，能够对互耦效应造成的通道间信号的相位差进行补偿，克服传统阵列天线通道相位校准中互耦效应对通道中信号相位的影响。进一步的，由于传统校准方案中采用矢量网络分析仪进行校准，矢量网络分析仪时射频领域的万用表，被称为仪器之王，价格昂贵，上述阵列天线多通道相位校准方法中，可以采用信号源和功率计代替传统校准方案中的矢量网络分析仪，从而能够降低校准时的硬件成本。
基于上述原理，本申请还提供一种阵列天线多通道相位校准装置，如图12所示，所述相位校准装置100包括：确定单元101以及调整单元102，
所述处理单元101用于在启用阵列天线的n个通道时，确定阵列天线n个通道中的每个通道的调试信号与参考信号之间的第一相位差，其中，所述第一相位差包括基准相位差与目标相位差，所述基准相位差为所述n个通道中的基准通道的调试信号与所述参考信号之间的相位差，所述目标相位差为除所述基准通道之外的n-1个通道各自的调试信号与所述参考信号之间的相位差，其中，所述基准通道为所述n个通道中的任意一个通道，n为大于或者等于2的正整数；
所述处理单元101还用于根据目标相位差与基准相位差之间的差值，确定所述n-1个通 道中每个通道的调试信号与基准信号之间的第二相位差，所述基准信号为基准通道中的调试信号；
所述调整单元102用于根据所述n-1个通道中每个通道的调试信号与基准信号之间的第二相位差调整所述n-1个通道中每个通道中的移相器，以使得所述n-1个通道中每个通道中的调试信号的相位与所述基准信号的相位相同。
所述相位校准装置还包括功率获取单元103，所述功率获取单元103用于获取所述n个通道中的n个调试信号合成的合成信号的功率。
具体地，所述确定单元101用于支持多通道相位校准装置执行图2中的步骤S20与S21、图4中步骤S201与S202以及图5中步骤S2014等，所述调整单元102用于在步骤S21中确定单元101确定第二相位差之后，执行图2中步骤S22，所述功率获取单元103用于步骤S2011中获取第一合成信号的第一功率、步骤S2012中获取第二合成信号的第二功率以及步骤S2013中获取第三合成信号的第三功率。
其中，确定单元101可以是处理器或控制器，例如可以是中央处理器(central processing unit，CPU)，或者CPU和硬件芯片的组合。上述硬件芯片可以是专用集成电路(application-specific integrated circuit，ASIC)，可编程逻辑器件(programmable logic device，PLD)或其组合。上述PLD可以是复杂可编程逻辑器件(complex programmable logic device，CPLD)，现场可编程逻辑门阵列(field-programmable gate array，FPGA)，通用阵列逻辑(generic array logic，GAL)或其任意组合。功率获取单元103可以是功率计等能够测量信号功率的设备。
可以理解的是，多通道相位校准装置为了实现上述功能，其包含了执行各个功能相应的硬件结构和/或软件模块。本领域技术人员应该很容易意识到，结合本文中所公开的实施例描述的各示例的单元及方法步骤，本申请能够以硬件或硬件和计算机软件的结合形式来实现。某个功能究竟以硬件还是计算机软件驱动硬件的方式来执行，取决于技术方案的特定应用和设计约束条件。专业技术人员可以对每个特定的应用使用不同方法来实现所描述的功能，但是这种实现不应认为超出本申请的范围。
本申请实施例可以根据上述方法示例对多通道相位校准装置进行功能单元的划分，例如，可以对应各个功能划分各个功能单元，也可以将两个或两个以上的功能集成在一个处理单元中。上述集成的单元既可以采用硬件的形式实现，也可以采用软件功能单元的形式实现。需要说明的是，本申请实施例中对单元的划分是示意性的，仅仅为一种逻辑功能划分，实际实现时可以有另外的划分方式。
请参见图13，图13是本申请实施例提供的一种相位校准设备的结构示意图，如图13所示，所述相位校准设备300至少包括：处理器310、收发器320、功率测量模块330以及存储器340，处理器310、收发器320、功率测量模块330以及存储器340通过总线350连接。
所述处理器310可以是中央处理器(central processing unit，CPU)，或者CPU和硬件芯片的组合。上述硬件芯片可以是专用集成电路(application-specific integrated circuit，ASIC)，可编程逻辑器件(programmable logic device，PLD)或其组合。上述PLD可以是复杂可编程逻辑器件(complex programmable logic device，CPLD)，现场可编程逻辑门阵列(field-programmable gate array，FPGA)，通用阵列逻辑(generic array logic，GAL)或其任意组合。
所述收发器320可以包括一个接收器和一个发送器，例如，无线射频模块，以下描述的处理器310接收或者发送某个消息，具体可以理解为该处理器310通过该收发器来接收或者 发送。
所述功率测量模块330可以是功率计等能够测量信号功率的模块。
所述存储器340包括但不限于是随机存取存储器(Random Access Memory，RAM)、只读存储器(Read-Only Memory，ROM)或可擦除可编程只读存储器(Erasable Programmable Read-Only Mmory，EPROM或者快闪存储器)，该存储器340用于存储相关指令及数据，并可以将存储的数据传输给处理器310。
本申请实施例中，收发器320中的接收器接收阵列天线n个通道的调试信号合成的合成信号，将合成信号发送给功率获取模块330，功率获取模块330测量合成信号的功率，将合成信号的功率发送给处理器310，处理器310根据阵列天线每个通道中移相器在不同相位状态下合成信号的不同功率值，最终可确定阵列天线每个通道中的调试信号与参考信号之间的相位差。上述相位校准设备各个操作的具体实现参照上述方法实施例中，此处不再赘述。
在上述实施例中，可以全部或部分地通过软件、硬件、固件、或者其任意组合来实现。当使用软件实现时，可以全部或部分地以计算机程序产品的形式实现。所述计算机程序产品包括一个或多个计算机指令。在计算机上加载和执行所述计算机程序指令时，全部或部分地产生按照本申请实施例所述的流程或功能。所述计算机可以是通用计算机、专用计算机、计算机网络、或者其他可编程装置。所述计算机指令可以存储在计算机可读存储介质中，或者从一个计算机可读存储介质向另一个计算机可读存储介质传输，例如，所述计算机指令可以从一个网站站点、计算机、服务器或数据中心通过有线(例如同轴电缆、光纤、数字用户线(DSL))或无线(例如红外、无线、微波等)方式向另一个网站站点、计算机、服务器或数据中心进行传输。所述计算机可读存储介质可以是计算机能够存取的任何可用介质或者是包含一个或多个可用介质集成的服务器、数据中心等数据存储设备。所述可用介质可以是磁性介质(例如软盘、硬盘、磁带)、光介质(例如，DVD)、或者半导体介质(例如固态硬盘Solid State Disk(SSD))等。
以上对本申请实施例进行了详细介绍，本文中应用了具体个例对本申请的原理及实施方式进行了阐述，以上实施例的说明只是用于帮助理解本申请的方法及其核心思想；同时，对于本领域的一般技术人员，依据本申请的思想，在具体实施方式及应用范围上均会有改变之处，综上所述，本说明书内容不应理解为对本申请的限制。

Claims (20)

  1. 一种相位校准方法，其特征在于，其中，包括：
    启用阵列天线的n个通道，n为大于或等于2的整数；
    确定所述n个通道的基准相位差，所述基准相位差为所述n个通道中的基准通道的调试信号与参考信号之间的相位差；
    确定所述n个通道中除所述基准通道之外的其他n-1个通道的各自的目标相位差，所述目标相位差为所述n-1个通道各自的调试信号与所述参考信号之间的相位差；
    基于所述n-1个通道各自的目标相位差与所述基准相位差之间的差值，调整所述n-1个通道中每个通道中的移相器。
  2. 根据权利要求1所述的方法，其特征在于，
    第k个相位差是根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值确定的，其中，所述第k个通道为所述n个通道中的任意一个通道，所述中间合成信号为除第k个通道之外的其余n-1个通道中的调试信号合成的合成信号，k为小于或者等于n的正整数。
  3. 根据权利要求2所述的方法，其特征在于，
    第k个相位差是根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值，结合矢量运算法则确定的。
  4. 根据权利要求2所述的方法，其特征在于，确定所述第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值，包括：
    确定所述第k个通道的移相器在至少三个不同相位状态时，所述n个通道的调试信号合成的至少三个合成信号的幅值，其中，所述不同相位状态为所述移相器在不同附加相移时的状态，所述至少三个合成信号的幅值与所述至少三个不同相位状态一一对应；
    根据所述至少三个合成信号的幅值，结合余弦定理确定所述第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值。
  5. 根据权利要求4所述的方法，其特征在于，所述确定所述第k个通道的移相器在至少三个不同相位状态时，所述n个通道的调试信号合成的至少三个合成信号的幅值，包括：
    获取第一合成信号的第一功率，根据所述第一功率确定所述第一合成信号的幅值，所述第一合成信号为第k个通道的移相器在第一相位状态时所述n个通道的调试信号合成的合成信号；
    获取第二合成信号的第二功率，根据所述第二功率确定所述第二合成信号的幅值，所述第二合成信号为第k个通道的移相器在第二相位状态时所述n个通道的调试信号合成的合成信号；
    获取第三合成信号的第三功率，根据所述第三功率确定所述第三合成信号的幅值，所述第三合成信号为第k个通道的移相器在第三相位状态时所述n个通道的调试信号合成的合成信号。
  6. 根据权利要求5所述的方法，其特征在于，根据至少三个合成信号的幅值，结合余弦定理确定第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值，包括：
    根据如下公式确定第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值：
    Figure PCTCN2018092928-appb-100001
    其中，C k为所述中间合成信号的幅值，A k为所述第k个通道中的调试信号的幅值，θ k为所述第k个通道中的调试信号与中间合成信号之间的相位差，γ 1为所述移相器在第一相位状态时的附加相移，γ 2为所述移相器在第二相位状态时的附加相移，γ 3为所述移相器在第三相位状态时的附加相移，K 1为所述第一合成信号的幅值，K 2为所述第二合成信号的幅值，K 3为所述第三合成信号的幅值。
  7. 根据权利要求5所述的方法，其特征在于，所述第一合成信号的第一功率、所述第二合成信号的第二功率以及所述第三合成信号的第三功率是从功率计获取的。
  8. 根据权利要求2至6任一项所述的方法，其特征在于，
    根据如下公式确定所述第k个通道中的调试信号与参考信号之间的相位差：
    Figure PCTCN2018092928-appb-100002
    其中，A k为所述第k个通道中调试信号的幅值，C k为所述中间合成信号的幅值，θ k为所述第k个通道中调试信号与中间合成信号之间的相位差，
    Figure PCTCN2018092928-appb-100003
    表示所述第k通道中的调试信号，
    Figure PCTCN2018092928-appb-100004
    表示所述中间合成信号，
    Figure PCTCN2018092928-appb-100005
    为第k个通道中的调试信号与参考信号之间的相位差。
  9. 根据权利要求5或6所述的方法，其特征在于，所述第一相位状态为所述第k个通道的移相器的附加相移为0时的状态；所述第二相位状态为所述第k个通道的移相器的附加相移为π/2时的状态；所述第三相位状态为所述第k个通道的移相器的附加相移为π时的状态。
  10. 一种相位校准装置，其特征在于，所述校准装置包括确定单元和调整单元：
    所述确定单元，用于在启用阵列天线的n个通道时，确定所述n个通道的基准相位差，所述基准相位差为所述n个通道中的基准通道的调试信号与参考信号之间的相位差，其中，n为大于或者等于2的整数；
    所述确定单元还用于确定所述n个通道中除所述基准通道之外的其他n-1个通道的各自的目标相位差，所述目标相位差为所述n-1个通道各自的调试信号与所述参考信号之间的相位差；
    所述调整单元，用于基于所述n-1个通道各自的目标相位差与所述基准相位差之间的差 值，调整所述n-1个通道中每个通道中的移相器。
  11. 根据权利要求10所示的装置，其特征在于，
    第k个相位差是根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值确定的，其中，所述第k个通道为所述n个通道中的任意一个通道，所述中间合成信号为除第k个通道之外的其余n-1个通道中的调试信号合成的合成信号，k为小于或者等于n的正整数。
  12. 根据权利要求11所述的装置，其特征在于，
    第k个相位差是根据第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值，结合矢量运算法则确定的。
  13. 根据权利要求11所述的装置，其特征在于，所述确定单元还用于：
    确定所述第k个通道的移相器在至少三个不同相位状态时，所述n个通道的调试信号合成的至少三个合成信号的幅值，其中，所述不同相位状态为所述移相器在不同附加相移时的状态，所述至少三个合成信号的幅值与所述至少三个不同相位状态一一对应；
    根据所述至少三个合成信号的幅值，结合余弦定理确定所述第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值。
  14. 根据权利要求13所述的装置，其特征在于，所述装置还包括：
    功率获取单元，用于获取第一合成信号的第一功率，所述第一合成信号为第k个通道的移相器在第一相位状态时所述n个通道的调试信号合成的合成信号；
    所述确定单元还用于：根据所述第一功率确定所述第一合成信号的幅值；
    所述功率获取单元还用于：获取第二合成信号的第二功率，所述第二合成信号为第k个通道的移相器在第二相位状态时所述n个通道的调试信号合成的合成信号；
    所述确定单元还用于：根据所述第二功率确定所述第二合成信号的幅值；
    所述功率获取单元还用于：获取第三合成信号的第三功率，所述第三合成信号为第k个通道的移相器在第三相位状态时所述n个通道的调试信号合成的合成信号；
    所述确定单元还用于：根据所述第三功率确定所述第三合成信号的幅值。
  15. 根据权利要求14所述的装置，其特征在于，所述确定单元还用于：
    根据如下公式确定第k个通道中的调试信号与中间合成信号之间的相位差、第k个通道中的调试信号的幅值以及中间合成信号的幅值：
    Figure PCTCN2018092928-appb-100006
    其中，C k为所述中间合成信号的幅值，A k为所述第k个通道中的调试信号的幅值，θ k为所述第k个通道中的调试信号与中间合成信号之间的相位差，γ 1为所述移相器在第一相位状态时的附加相移，γ 2为所述移相器在第二相位状态时的附加相移，γ 3为所述移相器在第三相位状态时的附加相移，K 1为所述第一合成信号的幅值，K 2为所述第二合成信号的幅值，K 3 为所述第三合成信号的幅值。
  16. 根据权利要求14所述的装置，其特征在于，所述功率获取单元为功率计。
  17. 根据权利要求11至15任一项所述的装置，其特征在于，所述确定单元还用于：
    根据如下公式确定所述第k个通道中的调试信号与参考信号之间的相位差：
    Figure PCTCN2018092928-appb-100007
    其中，A k为所述第k个通道中调试信号的幅值，C k为所述中间合成信号的幅值，θ k为所述第k个通道中调试信号与中间合成信号之间的相位差，
    Figure PCTCN2018092928-appb-100008
    表示所述第k通道中的调试信号，
    Figure PCTCN2018092928-appb-100009
    表示所述中间合成信号，
    Figure PCTCN2018092928-appb-100010
    为第k个通道中的调试信号与参考信号之间的相位差。
  18. 根据权利要求14或15所述的装置，其特征在于，所述第一相位状态为所述第k个通道的移相器的附加相移为0时的状态；所述第二相位状态为所述第k个通道的移相器的附加相移为π/2时的状态；所述第三相位状态为所述第k个通道的移相器的附加相移为π时的状态。
  19. 一种相位校准设备，其特征在于，包括处理器、收发器、功率测量模块和存储器，所述处理器、收发器、功率测量模块和存储器相互连接，其中，所述存储器用于存储应用程序代码，所述处理器被配置用于调用所述程序代码，执行如权利要求1至9所述的方法。
  20. 一种计算机可读存储介质，所述计算机可读存储介质存储有计算机程序，其特征在于，所述计算机程序被处理器执行时实现如权利要求1至9所述的方法。
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