WO2019148512A1 - 一种低复杂度的模拟波束赋形天线阵列 - Google Patents

一种低复杂度的模拟波束赋形天线阵列 Download PDF

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WO2019148512A1
WO2019148512A1 PCT/CN2018/075514 CN2018075514W WO2019148512A1 WO 2019148512 A1 WO2019148512 A1 WO 2019148512A1 CN 2018075514 W CN2018075514 W CN 2018075514W WO 2019148512 A1 WO2019148512 A1 WO 2019148512A1
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Prior art keywords
phase shifter
array
sub
analog beamforming
digital phase
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PCT/CN2018/075514
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English (en)
French (fr)
Inventor
吴泽海
吴永乐
庄正
李明星
吴壁群
苏振华
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广东博纬通信科技有限公司
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Priority claimed from CN201810090680.9A external-priority patent/CN108461932B/zh
Priority claimed from CN201820158322.2U external-priority patent/CN207910069U/zh
Application filed by 广东博纬通信科技有限公司 filed Critical 广东博纬通信科技有限公司
Publication of WO2019148512A1 publication Critical patent/WO2019148512A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q23/00—Antennas with active circuits or circuit elements integrated within them or attached to them

Definitions

  • the present invention relates to the field of communications technologies, and in particular, to a low complexity analog beamforming antenna array.
  • the fifth-generation mobile communication system uses large-scale multi-input and output (Massive MIMO) technology, deploying up to 64 or more antenna units on the antenna side of the base station, and arranging multiple antennas on the mobile terminal, greatly enhancing the space. Reuse capability, achieve breakthrough innovation in wireless transmission technology, and greatly improve spectrum efficiency and power efficiency.
  • Mass MIMO massive MIMO
  • Massive MIMO systems with theoretically all-digital beamforming have optimal performance, but require expensive digital-to-analog/analog-to-digital conversion modules, which have problems such as high cost, high data transmission and large processing capacity.
  • the digital combined analog hybrid beamforming method places the digital-to-analog/analog-to-digital conversion module in a common channel, which greatly reduces the number of digital-to-analog/analog-to-digital conversion modules, thereby reducing the complexity of the system.
  • Hybrid beamforming has become a research hotspot of 5G.
  • digital phase shifters have attracted more and more scholars and enterprise R&D technicians.
  • the digital phase shifter used in the existing 5G technology adopts a normalized form, that is, has the same number of bits and phase shifting amount; the more the number of phase shifters, the higher the accuracy of the beam scanning angle, but the phase shift
  • the number of bits of the digital phase shifter and its phase shifting need to be minimized.
  • the present invention provides a low-complexity analog beamforming antenna array for a problem encountered in a 5G Massive MIMO antenna array using a hybrid beamforming method; pairing different numbers of bits or different delays by a radiating element or a radiating element group
  • the digital phase shifter of the process reduces the phase shift number or delay total range of some digital phase shifters.
  • the present invention can locally simplify the phase shifter design, reduce the complexity and cost of the Massive MIMO antenna array to address or at least partially alleviate the above problems in the prior art.
  • the present invention provides a low complexity analog beamforming antenna array including one or more sub-arrays with independent analog beamforming functions, each sub-array comprising a metal reflector, an antenna radiation unit array, and a digital phase shifter coupled to a radio frequency front end component located in a common channel, the radio frequency front end component including a power amplifier (PA), a low noise amplifier (LNA), and a filter;
  • PA power amplifier
  • LNA low noise amplifier
  • the digital phase shifter is in the form of a delay device or a phase shifter, the phase shift amount of the delay device varies linearly with the operating frequency, and the phase shift amount of the phase shifter is constant within the operating frequency band;
  • the digital phase shifter is directly connected to the radiation unit or the radiation unit group in the antenna radiation unit array, and for the digital phase shifter to be a sub-array of the phase shifter, at least one digital phase shifter has a different number of bits;
  • the digital phase shifter uses a sub-array of delays with at least one digital phase shifter having a different delay total.
  • the radiating element is a dual-polarized or single-polarized antenna unit.
  • each sub-array comprises the number of digital phase shifters less than or equal to the number of radiating elements.
  • each sub-array is connected to one end of a corresponding common channel, and the other end of the common channel is connected to a digital domain beam network, the common channel comprising at least a power amplifier, a mixer and a digital-to-analog/analog-to-digital conversion module.
  • the array of antenna radiating elements of the sub-array is arranged horizontally and vertically in two dimensions, and the number of rows and the number of columns are both greater than or equal to two.
  • the array of sub-array radiation cells has a number of columns of 4 and a number of rows of two.
  • the digital phase shifter in the sub-array is in the form of a phase shifter with a constant phase offset, comprising two digital shifters of 4 bits and 3 bits, and a 4-bit digital phase shifter consisting of 0 0 /22.5 0 , 0 0 /45 0 , 0 0 /90 0 and 0 0 /180 0
  • phase shifter units are cascaded, each phase shifter unit contains two phase states; the 3-bit digital phase shifter consists of 4 bits
  • the three phase shifter units in the digital phase shifter are cascaded.
  • the 4-bit digital phase shifter wherein the 0 0 /22.5 0 phase shifter unit comprises two phase states of 0 0 and 22.5 0 , and the 0 0 /45 0 phase shifter unit comprises 0 0 and 45 0
  • Two phase states 0 0 / 90 0 phase shifter unit includes 0 0 and 90 0 phase states, 0 0 / 180 0 phase shifter unit contains 0 0 and 180 0 two phase states; each phase shifter The unit can select one of the phase shift quantities by RF switch control.
  • the radiation unit or the radiation unit group in the sub-array one part is connected to the 4-bit digital phase shifter, and the remaining part is connected to the 3-digit digital phase shifter.
  • the horizontal distance of the radiating element in the antenna radiating element array is in the range of 0.4 to 0.65 times the wavelength of the center frequency of the working frequency band; the vertical distance of the radiating element is in the range of 0.5 to 0.8 times the wavelength of the center frequency of the working frequency band.
  • the present invention provides a low complexity analog beamforming antenna array.
  • the complexity of the Massive MIMO antenna array is reduced by reducing the number of bits of the digital phase shifter or delaying the total range. , reducing power consumption and cost, providing an economical and more practical solution for large-scale deployment of 5G mobile communication systems.
  • FIG. 1 is a schematic structural diagram of a low complexity analog beamforming antenna array according to an embodiment of the present invention
  • FIG. 2 is a layout diagram of an antenna radiation unit array of a sub-array according to an embodiment of the present invention
  • Figure 3 is a block diagram of a 4-bit digital phase shifter in an embodiment of the present invention.
  • Figure 4 is a block diagram of a 3-bit digital phase shifter in one embodiment of the invention.
  • 101 denotes an antenna sub-array
  • 102 denotes a common channel
  • 103 denotes a digital domain beam network
  • 110 denotes a radiating element
  • 111 denotes a metal reflecting plate
  • 112 denotes an antenna radiating element array
  • 113 denotes a digital phase shifter
  • 114 denotes a power amplifier
  • 115 denotes Mixer
  • 116 denotes a digital-to-analog conversion module
  • 110-1 denotes a radiation unit No. 1
  • 110-2 denotes a radiation unit No. 2
  • 110-3 denotes a radiation unit No. 3
  • 110-4 denotes a radiation unit No. 4
  • 110-5 Indicates Radiation Unit No. 5
  • 110-6 denotes Radiation Unit No.
  • 110-7 denotes Radiation Unit No. 7
  • 110-8 denotes Radiation Unit No. 8
  • 113-1 denotes a 4-bit digital phase shifter
  • 113-2 denotes 3 digits Digital phase shifter
  • 201 denotes a first phase shifting unit
  • 202 denotes a second phase shifting unit
  • 203 denotes a third phase shifting unit
  • 204 denotes a fourth phase shifting unit;
  • the directional indication is only used to explain in a certain posture (as shown in the drawing)
  • the relative positional relationship between the components, the motion situation, and the like if the specific posture changes, the directional indication also changes accordingly.
  • first”, “second”, etc. in the embodiments of the present invention, the description of the "first”, “second”, etc. is used for the purpose of description only, and is not to be construed as an Its relative importance or implicit indication of the number of technical features indicated.
  • features defining “first” or “second” may include at least one of the features, either explicitly or implicitly.
  • the technical solutions between the various embodiments may be combined with each other, but must be based on the realization of those skilled in the art, and when the combination of the technical solutions is contradictory or impossible to implement, it should be considered that the combination of the technical solutions does not exist. It is also within the scope of protection required by the present invention.
  • the invention provides a low complexity analog beamforming antenna array
  • the low complexity analog beamforming antenna array includes M sub-arrays 101, M having independent analog beamforming functions.
  • each sub-array comprises a metal reflector 111, an antenna radiating element array 112 and a digital phase shifter 113; said digital phase shifter 113 is of constant phase offset
  • the phase shifter is directly disposed at the rear end of the antenna radiating element array 112.
  • the digital phase shifter 113 has a working frequency range of 3.3-5.0 GHz and a phase shift number ⁇ 3;
  • the radio frequency front end of the sub-array 101 is placed in the common channel 102 , and each radio frequency sub-channel only retains the digital phase shifter 113 and is connected to the radiating unit 110 ; the common channel 102 includes the power amplifier 114 .
  • the number of sub-arrays 106 is M ⁇ 2;
  • the number P 4, as shown in Fig. 2, in the figure, 110-1 to 110-8 respectively represent 8 radiation units, and the operating frequency band of the radiation unit is 3.3-5.0 GHz;
  • the radiating element 110 is a single-polarized antenna unit.
  • the digital phase shifter 113 is a modular phase shifter or a distributed phase shifter operating at a radio frequency.
  • the radiating unit has a horizontal distance of 0.5 times the wavelength of the center frequency of the working frequency band; and the vertical distance is 0.75 times the wavelength of the center frequency of the working frequency band.
  • the digital phase shifter comprises two types, one is a 4-bit digital phase shifter, and the other is a 3-bit digital phase shifter.
  • the 4-bit digital phase shifter 113-1 includes four phase shifting units. As shown in FIG. 3, the first phase shifting unit 201 includes two phase states of 0 0 and 22.5 0 , and the second phase shifting unit 202 includes 0 0. And 45 0 phase states, the third phase shifting unit 203 includes two phase states of 0 0 and 90 0 , and the fourth phase shifting unit 204 includes two phase states of 0 0 and 180 0 .
  • the 3-bit digital phase shifter 113-2 includes three phase shifting units, as shown in FIG. 4, including a second phase shifting unit 202, a third phase shifting unit 203, and a fourth phase shifting unit 204.
  • the single-polarized vibrators distributed on both sides of the 110-1, 110-4, 110-5, and 110-8 are connected to the three positions.
  • the digital phase shifter 113-1, and the single-polarized vibrators distributed in the middle of the numbers 110-2, 110-3, 110-6, and 110-7 are connected to the 4-bit digital phase shifter 113-2.
  • Embodiments of the present invention can reduce the complexity of the digital phase shifter while maintaining the range of scanning angles.
  • the 3-bit digital phase shifter 113-2 includes three phase shifting units, a first phase shifting unit 201, a second phase shifting unit 202, and a third phase shifting unit 203.
  • the single-polarized vibrators distributed on both sides of the 110-1, 110-4, 110-5, and 110-8 are connected to the 3-bit digital phase shifter 107- 1
  • the single-polarized vibrators distributed in the middle of 110-2, 110-3, 110-6, and 110-7 are connected to the 4-bit digital phase shifter 113-2.
  • Embodiments of the present invention can reduce the complexity of the digital phase shifter while maintaining the accuracy of the scanning angle.

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Abstract

本发明公开一种低复杂度的模拟波束赋形天线阵列，涉及通信技术领域，包含一个或者多个具备独立的模拟波束赋形功能的子阵列，每个子阵列包含金属反射板、天线辐射单元阵列和数字移相器；所述的数字移相器直接与辐射单元或者单元组相连，至少有一个数字移相器具有不同的位数或者具有不同延迟总量程，可通过降低部分移相器的移相量降低其复杂程度。根据本发明实施例的模拟波束赋形方案，通过不同位数或者不同延迟总量程的数字移相器的组合使用，降低 Massive MIMO 天线阵列的复杂程度，降低了功耗与成本，为大规模的部署 5G 移动通信系统提供了一种经济而且更加实用的解决方法。

Description

一种低复杂度的模拟波束赋形天线阵列 技术领域
本发明涉及通信技术领域，尤其涉及一种低复杂度的模拟波束赋形天线阵列。
背景技术
第五代移动通信系统(5G)使用大规模的多输入输出(Massive MIMO)技术，基站天线侧部署多达64个或以上的天线单元，同时在移动终端布置多个天线，大幅度增强了空间复用能力，在无线传输技术上实现突破性创新，大幅度提高频谱效率以及功率效率。
理论上具有全数字的波束赋形方式的Massive MIMO系统具有最优的性能，但需要昂贵的数模/模数转换模块，存在成本高、数据传输及处理量过大等难题。数字结合模拟的混合波束赋形方式将数模/模数转换模块置于公共通道，大幅度减少了数模/模数转换模块的数量，从而降低了系统的复杂程度。
混合波束赋形已成为5G的一个研究热点，数字移相器作为其核心部件，则受到越来越多的学者以及企业研发技术人员关注。现有的5G技术中所应用的数字移相器，采用归一的形式，即具有相同的位数和移相量；移相器位数越多，波束扫描角度的精度越高，但移相器本身及其控制电路也越复杂，成本和损耗随位数及移相量的增加而明显增加。对工作在射频的动态波束赋形天线，需要尽量地降低数字移相器的位数及其移相量。
发明内容
本发明针对5G Massive MIMO天线阵列使用混和波束赋形方法所遇到的问题，提供一种低复杂度的模拟波束赋形天线阵列；通过辐射单元或者辐射单元组配对不同位数或者不同延迟总量程的数字移相器，降低了部分数字移相器的相移位数或者延迟总量程。本发明可以局部地简化移相器设计，降低Massive MIMO天线阵列的复杂度以及成本，以解决或者至少部分地缓解现有技术中存在的上述问题。
为了实现上述目的，本发明提出一种低复杂度的模拟波束赋形天线阵列，包含一个或者多个具备独立模拟波束赋形功能的子阵列，每个子阵列包含金属反射板、天线辐射单元阵列和数字移相器，所述子阵列与位于公共通道的射频前端部件相连，所述射频前端部件包括功率放大器(PA)、低噪声放大器(LNA)和滤波器；
所述数字移相器为延迟器或者移相器形式，延迟器的相位偏移量随工作频率线性变化，移相器的相位偏移量在工作频带范围内恒定；
所述的数字移相器直接与天线辐射单元阵列中的辐射单元或者辐射单元组相连，对于数字移相器为移相器的子阵列，至少有一个数字移相器具有不同的位数；对于数字移相器使用延迟器的子阵列，至少有一个数字移相器具有不同的延迟总量程。
优选地，所述的辐射单元为双极化或者单极化的天线单元。
优选地，每个子阵列包含数字移相器的个数，小于或等于辐射单元的个数。
优选地，每个子阵列与对应的公共通道的一端相连接，公共通道的另一端与数字域波束网络连接，所述的公共通道至少包含功率放大器、混频器和数模/模数转换模块。
优选地，所述子阵列的天线辐射单元阵列呈水平垂直二维排列，行数和列数均大于或等于2。
优选地，所述子阵列辐射单元阵列的列数为4，行数为2。
优选地，所述子阵列中的数字移相器为恒定相位偏移的移相器形式，其包含4位和3位两种数字移相器，4位数字移相器由0 0/22.5 0、0 0/45 0、0 0/90 0和0 0/180 0四种移相器单元级联而成，每种移相器单元包含两种相位状态；3位数字移相器由4位数字移相器中的三种移相器单元级联而成。
优选地，所述的4位数字移相器，其中，0 0/22.5 0移相器单元包含0 0和22.5 0两种相位状态，0 0/45 0移相器单元包含0 0和45 0两种相位状态，0 0/90 0移相器单元包括0 0和90 0两种相位状态，0 0/180 0移相器单元包含0 0和180 0两种相位状态；每种移相器单元可通过射频开关控制选择其中一种的移相量。
优选地，子阵列中辐射单元或者辐射单元组，一部分连接4位数字移相器，其余部分连接3位数字移相器。
优选地，天线辐射单元阵列中的辐射单元水平距离介于工作频段中心频率波长的0.4～0.65倍范围内；辐射单元垂直距离介于工作频段中心频率波长的0.5～0.8倍范围内。
本发明提出一种低复杂度的模拟波束赋形天线阵列，根据本发明的模拟波束赋形方案，通过减少部分数字移相器的位数或者延迟总量程，降低Massive MIMO天线阵列的复杂程度，降低了功耗与成本，为大规模的部署5G移动通信系统提供了一种经济而且更加实用的解决方案。
附图说明
为了更清楚地说明本发明实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本发明的一 些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图示出的结构获得其他的附图。
图1为本发明一种实施例中低复杂度的模拟波束赋形天线阵列结构示意图；
图2为本发明一种实施例中子阵列的天线辐射单元阵列排布图；
图3位本发明一种实施例中4位数字移相器的框图；
图4位本发明一种实施例中3位数字移相器的框图。
标号说明：
101表示天线子阵列，102表示公共通道，103表示数字域波束网络，110表示辐射单元，111表示金属反射板，112表示天线辐射单元阵列，113表示数字移相器，114表示功率放大器，115表示混频器，116表示数模转换模块，110-1表示1号辐射单元，110-2表示2号辐射单元，110-3表示3号辐射单元，110-4表示4号辐射单元，110-5表示5号辐射单元，110-6表示6号辐射单元，110-7表示7号辐射单元，110-8表示8号辐射单元，113-1表示4位数字移相器，113-2表示3位数字移相器，201表示第一种移相单元，202表示第二种移相单元，203表示第三种移相单元，204表示第四种移相单元；
本发明目的的实现、功能特点及优点将结合实施例，参照附图做进一步说明。
具体实施方式
下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例仅仅是本发明的一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。
需要说明，若本发明实施例中有涉及方向性指示(诸如上、下、左、右、前、后……)，则该方向性指示仅用于解释在某一特定姿态(如附图所示)下各部件之间的相对位置关系、运动情况等，如果该特定姿态发生改变时，则该方向性指示也相应地随之改变。
另外，若本发明实施例中有涉及“第一”、“第二”等的描述，则该“第一”、“第二”等的描述仅用于描述目的，而不能理解为指示或暗示其相对重要性或者隐含指明所指示的技术特征的数描。由此，限定有“第一”、“第二”的特征可以明示或者隐含地包括至少一个该特征。另外，各个实施例之间的技术方案可以相互结合，但是必须是以本领域普通技术人员能够实现为基础，当技术方案的结合出现相互矛盾或无法实现时应当认为这种技术方案的结合不存在，也不在本发明要求的保护范围之内。
本发明提出一种低复杂度的模拟波束赋形天线阵列；
本发明一种优选实施例中，以基站下行链路为例，如图1所示，低复杂度的模拟波束赋 形天线阵列包含M个具备独立的模拟波束赋形功能的子阵列101，M个对应的公共通道102和数字域波束形成网络103；每个子阵列包含金属反射板111、天线辐射单元阵列112和数字移相器113；所述的数字移相器113为具有恒定相位偏移的移相器形式，直接设置于天线辐射单元阵列112的后端。
本发明一种优选实施例中，数字移相器113的工作频段范围为3.3-5.0GHz，移相位数≥3；
本发明实施例中，如图1所示，子阵列101的射频前端放置在公共通道102，各射频子通道仅保留数字移相器113，与辐射单元110连接；公共通道102包含功率放大器114，混频器115和数模转换模块116；公共通道102的一端与子阵列101相连，另外一端连接数字域波束形成网络103。
本发明一种优选实施例中，子阵列106的个数M≥2；
本发明一种优选实施例中，所述的天线辐射单元阵列112包含P行Q列的辐射单元110，其中，行数P≥2，列数Q≥2，优选的行数Q＝2，列数P＝4，如图2所示，图中，110-1至110-8分别表示8个辐射单元，辐射单元工作频段为3.3-5.0GHz；
本发明一种优选实施例中，所述的辐射单元110为单极化的天线单元。
本发明一种优选实施例中，所述的数字移相器113为工作在射频的模块式移相器或者分布式移相器。
本发明一种优选实施例中，所述的辐射单元，水平距离为工作频段中心频率波长的0.5倍；垂直距离为工作频段中心频率波长的0.75倍。
本发明一种优选实施例中，所述的数字移相器包含两种，一种是4位数字移相器的，另外一种是3位数字移相器的。4位数字移相器113-1包括四种移相单元，如图3所示，第一种移相单元201包含0 0和22.5 0两种相位状态，第二种移相单元202包含0 0和45 0两种相位状态，第三种移相单元203包含0 0和90 0两种相位状态，第四种移相单元204包括0 0和180 0两种相位状态。3位数字移相器113-2包括三种移相单元，如图4所示，包含第二种移相单元202，第三种移相单元203和第四种移相单元204。
本发明一种优选实施例中，图2所示的子阵列的辐射单元阵列中，110-1、110-4、110-5、110-8号分布在两侧的单极化振子连接3位数字移相器113-1，而110-2、110-3、110-6、110-7号分布在中间的单极化振子连接4位数字移相器113-2。本发明实施例可在维持扫描角度范围的同时降低数字移相器的复杂程度。
本发明另外一种实施例中，3位数字移相器113-2包括如下三种移相单元，第一种移相单元201，第二种移相单元202和第三种移相单元203。类似的，图2所示的子阵列的辐射单元阵列中，110-1、110-4、110-5、110-8号分布在两侧的单极化振子连接3位数字移相器107-1， 而110-2、110-3、110-6、110-7号分布在中间的单极化振子连接4位数字移相器113-2。本发明实施例可在维持扫描角度精度的同时降低数字移相器的复杂程度。
以上所述仅为本发明的优选实施例，并非因此限制本发明的专利范围，凡是在本发明的发明构思下，利用本发明说明书及附图内容所作的等效结构变换，或直接/间接运用在其他相关的技术领域均包括在本发明的专利保护范围内。

Claims (10)

  1. 一种低复杂度的模拟波束赋形天线阵列，其特征在于，包含一个或者多个具备独立模拟波束赋形功能的子阵列，每个子阵列包含金属反射板、天线辐射单元阵列和数字移相器，所述子阵列与位于公共通道的射频前端部件相连，所述射频前端部件包括PA、LNA和滤波器；
    所述数字移相器为延迟器或者移相器，延迟器的相位偏移量随工作频率线性变化，移相器的相位偏移量在工作频带范围内恒定；
    所述数字移相器直接与天线辐射单元阵列中的辐射单元或者辐射单元组相连，对于数字移相器为移相器的子阵列，至少有一个数字移相器具有不同的位数；对于数字移相器为延迟器的子阵列，至少有一个数字移相器具有不同的延迟总量程。
  2. 根据权利要求1所述的低复杂度的模拟波束赋形天线阵列，其特征在于，所述的辐射单元为双极化或者单极化的天线单元。
  3. 根据权利要求1所述的低复杂度的模拟波束赋形天线阵列，其特征在于，每个子阵列包含数字移相器的个数，小于或等于辐射单元的个数。
  4. 根据权利要求1所述的低复杂度的模拟波束赋形天线阵列，其特征在于，每个子阵列与对应的公共通道的一端相连接，公共通道的另一端与数字域波束网络连接，所述的公共通道至少包含功率放大器、混频器和数模/模数转换模块。
  5. 根据权利要求1所述的低复杂度的模拟波束赋形天线阵列，其特征在于，所述子阵列的天线辐射单元阵列呈水平垂直二维排列，行数和列数均大于或等于2。
  6. 根据权利要求5所述的低复杂度的模拟波束赋形天线阵列，其特征在于，所述子阵列的天线辐射单元阵列的列数为4，行数为2。
  7. 根据权利要求6所述的低复杂度的模拟波束赋形天线阵列，其特征在于，所述子阵列中的数字移相器为恒定相位偏移的移相器，其包含4位和3位两种数字移相器，4位数字移相器由0°/22.5°、0°/45°、0°/90°和0°/180°的四种移相器单元级联而成，每种移相器单元包含两种相位状态；3位数字移相器由4位数字移相器中的三种移相器单元级联而成。
  8. 根据权利要求7所述的低复杂度的模拟波束赋形天线阵列，其特征在于，所述的4位数字移相器，其中，0°/22.5°移相器单元包含0°和22.5°两种相位状态，0°/45°移相器单元包含0°和45°两种相位状态，0°/90°移相器单元包括0°和90°两种相位状态，0°/180°移相器单元包含0°和180°两种相位状态；每种移相器单元可通过射频开关控制选择其中一种的相位偏移量。
  9. 根据权利要求8所述的低复杂度的模拟波束赋形天线阵列，其特征在于，子阵列中 辐射单元或者辐射单元组，一部分连接4位数字移相器，其余部分连接3位数字移相器。
  10. 根据权利要求5所述的低复杂度的模拟波束赋形天线阵列，其特征在于，所述的子阵列的天线辐射单元阵列中的辐射单元水平距离介于工作频段中心频率波长的0.4～0.65倍范围内；辐射单元垂直距离介于工作频段中心频率波长的0.5～0.8倍范围内。
PCT/CN2018/075514 2018-01-30 2018-02-07 一种低复杂度的模拟波束赋形天线阵列 WO2019148512A1 (zh)

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Citations (3)

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Publication number Priority date Publication date Assignee Title
US7064710B1 (en) * 2005-02-15 2006-06-20 The Aerospace Corporation Multiple beam steered subarrays antenna system
US20090309670A1 (en) * 2006-09-12 2009-12-17 Tsufit Magrisso Switched Bands Phase Shifter
CN206412486U (zh) * 2017-01-24 2017-08-15 成都杰联祺业电子有限责任公司 毫米波相控阵结构

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7064710B1 (en) * 2005-02-15 2006-06-20 The Aerospace Corporation Multiple beam steered subarrays antenna system
US20090309670A1 (en) * 2006-09-12 2009-12-17 Tsufit Magrisso Switched Bands Phase Shifter
CN206412486U (zh) * 2017-01-24 2017-08-15 成都杰联祺业电子有限责任公司 毫米波相控阵结构

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