WO2019102646A1 - Antenna device, antenna system, and instrumentation system - Google Patents

Abstract

The purpose of the present invention is to reduce fluctuation in pass amplitude characteristics within a band, reduce fluctuation in return loss characteristics within the band due to total reflection, improve shielding performance, and achieve a good gain. The antenna device 1 is provided with: a waveguide body 5 comprising a closure member 30 and a coaxial waveguide transformation section 6 which has a hexahedron-shaped internal space 8 formed so as to penetrate between a first surface and a second surface and a connector attachment hole 22 for inserting a coaxial connector and for providing communication between the internal space and a third surface orthogonal to the first and second surfaces, the closure member 30 being for closing an opening on the second surface-side of the internal space; and a connector 50 comprising a connector body 51 attached to the connector attachment hole so as to orient outward from the internal space without an inner end part thereof protruding into the internal space, a center conductor 60 axially penetrating the center of the connector body with a tip part of the center conductor protruding into the internal space by a prescribed length from the inner end part of the connector body, and a passive radiator 54b composed of the tip part 60a of the center conductor and causing the protrusion length of the tip part to match a specific frequency band.

Description

Antenna device, antenna system, and measurement system

The present invention relates to an antenna device, an antenna system, and a measurement system suitable for measuring digital modulation equipment.

In recent years, digital modulation devices are widely used as mobile terminals such as mobile phones and smartphones, and radio waves are transmitted or received in close proximity to or in close contact with these objects to be measured, to the high frequency of the object to be measured. Coupler antennas are used to measure various characteristics.
In the coupler antenna for such an application, in order to correspond to the frequency band to be measured, a patch antenna in which a plurality of element patterns are formed on one surface of a flat dielectric substrate is employed.

For example, a horn antenna in which a horn is attached to the front of such a conventional patch antenna is known. The results of three types of measurement performed on such a horn antenna are shown in FIGS. 27 (a) to (c).
FIG. 27A is a graph showing the return loss characteristic (return loss) when the horn antenna is disposed in free space.
FIG. 27B is a graph showing coupler coupling characteristics (pass amplitude characteristics) measured when one pair of horn antennas are opposed to each other and are coupled at a coupling distance of 0 mm.
When the coupler coupling characteristic (pass amplitude characteristic) is measured, level fluctuation of, for example, −30 db or more occurs irregularly as abrupt waveform disturbance in the target frequency band (23 GHz to 29 GHz).
FIG. 27 (c) is a graph showing the return loss characteristic (return loss) in total reflection, which was measured when the entire surface of the horn antenna was covered with a metal plate.
When the return loss characteristic (return loss) is measured, abrupt waveform irregularities occur irregularly in the band due to total reflection.

Patent Document 1 is disclosed for such a patch antenna.
In Patent Document 1, a transmitting antenna and a plurality of receiving antennas are a substrate having dielectricity, a circularly polarized antenna element disposed on the main surface of the substrate, a ground layer formed on the back surface of the substrate, and an antenna A plurality of through holes are formed to extend from the strip conductor disposed on the main surface of the substrate surrounding the element and the area where the strip conductor is formed on the main surface of the substrate to the back surface of the substrate and arranged at predetermined intervals. And a plurality of connection conductors electrically connecting the ground layer and the strip conductor through the respective through holes. The configuration is disclosed in which the inner edge of the strip conductor protrudes toward the antenna element more than the inner wall of each through hole. With such a configuration, it is disclosed that generation of surface waves on the main surface of the substrate of the transmitting antenna and the receiving antenna can be suppressed, and radiation characteristics of each antenna can be made into a desired stable shape.

JP, 2006-258762, A

The conventional patch antenna has a structure in which a plurality of elements having a specific pattern matched to a target frequency are arranged on a substrate.
For this reason, the characteristic variation of each element and mutual interference of each element occur, and the irregular disturbance of the passing amplitude characteristic in the band as shown in FIG. 28 (b) or the one shown in FIG. 28 (c) There has been a problem that such irregular disturbance of the return loss characteristic in the band due to total reflection occurs.
In addition, since an element having a specific pattern is disposed on the substrate, it is difficult to exclude radio waves coming from the back surface of the substrate and the surroundings, and there is a problem that the required blocking performance is lowered.
The present invention has been made in view of the above, and as its object, it is possible to suppress the occurrence of the disturbance of the passing amplitude characteristic in the band and the disturbance of the reflection attenuation amount characteristic in the band due to total reflection. It is an object of the present invention to provide an antenna device capable of improving the blocking performance and obtaining a better EVM value.

In order to solve the above problems, the invention according to claim 1 is an internal space formed of a hexahedron made of a conductive material, which is formed to penetrate between the opposing first surface and the second surface, and the first space. A coaxial waveguide conversion unit including a surface, and a connector mounting hole for inserting a coaxial connector formed between the third surface orthogonal to the second surface and the internal space; and the internal space A waveguide main body comprising a conductive closing member closing the opening on the second surface side, and the connector mounting hole is mounted outward from the internal space, the inner end portion being in the internal space A conductive connector body which does not project in the axial direction, and a central conductor which is disposed to penetrate the central portion of the connector body in the axial direction, and which has its tip projected from the inner end of the connector body into the internal space by a predetermined length The tip of the central conductor protruding into the internal space A connector having a radiator for radiating radio waves from the central conductor in the inner space by matching the projection length of the tip to a specific frequency band. .

According to the present invention, it is possible to suppress the occurrence of the disturbance of the passing amplitude characteristic in the band and the disturbance of the reflection attenuation amount characteristic in the band due to the total reflection, and it is possible to improve the blocking performance. Good EVM values can also be obtained.

(A) is a front view showing the structure of an antenna device according to an embodiment of the present invention, (b) is a cross-sectional view taken along the line AA of (a), (c) is a right side view, (d) is a top view, (E) is a bottom view, (f) is a rear view, (g) is a cross-sectional view taken along the line BB in (a). (A) And (b) is a perspective view which shows the structure of the antenna apparatus based on one Embodiment of this invention. (A) And (b) is a disassembled perspective view which shows the structure of the antenna apparatus based on one Embodiment of this invention. (A), (b) and (c) are the bottom view of the connector based on one Embodiment of this invention, sectional drawing, and a top view. (A), (b) and (c) are a front view, a top view, and a rear view of a circular polarization type polarization part concerning one embodiment of the present invention. (A) And (b) is the front view and side view of the deflection | deviation plate which concern on one Embodiment of this invention. (A) (b) and (c) are cross-sectional views of CC, DD and EE in FIG. 5 (a), and (d) and (e) are F in FIG. 7 (b) It is a -F, GG sectional view. (A) And (b) is a front appearance side perspective view of a circular polarization type polarization part, and an appearance perspective view in the back side. (A) is an external appearance perspective view showing circular polarization type horn part 200B of the antenna device concerning other embodiments (16 mm horn) of the present invention, (b) is a front view, (c) is a side view, d) is a rear view, and (e), (f) and (g) are front and side views of a circular polarized horn unit 200B of the antenna device according to another embodiment (15 mm horn) of the present invention, And a rear view. (A)-(d) is a side view which shows the modification of the antenna apparatus based on one Embodiment of this invention. It is a figure showing the chart showing the composition of the modification of the antenna system concerning one embodiment of the present invention. (A) is a block diagram which shows the antenna system using the antenna apparatus which concerns on one Embodiment of this invention, and a measurement system, (b) is a perspective view which shows the calibration kit used for the calibration of the said measurement system. It is a flowchart which shows the calibration procedure of the measurement system shown in FIG. It is a flowchart which shows the return loss amount measurement procedure performed in the measurement system shown in FIG. (A) and (b) are graphs showing representative characteristics immediately after assembly of the linear polarization coupler and representative characteristics after adjustment. It is a flowchart which shows the measurement procedure of the coupling loss characteristic performed in the measurement system shown in FIG. (A) to (d) are graphs showing measurement results of return loss characteristics and coupling characteristics performed in the measurement system. It is a block diagram showing an antenna system concerning EVM measurement using an antenna device concerning one embodiment of the present invention, and a measurement system. It is a flowchart which shows the calibration procedure performed in the measurement system shown in FIG. It is a flowchart which shows the EVM measurement procedure performed in the measurement system shown in FIG. It is a figure showing the monitor screen which shows the EVM value measured in the measurement system shown in FIG. (A) is a graph which shows the measurement result of the return loss characteristic in the free space of the linear polarization coupler performed in the measurement system, (b) is a coupler coupling of the linear polarization coupler performed in the measurement system It is a graph which shows the measurement result of a characteristic (pass amplitude characteristic). (A) is a graph which shows the measurement result of the return loss characteristic in the total reflection of the linear polarization coupler performed in the measurement system, (b) is an EVM value of the linear polarization coupler performed in the measurement system It is a graph which shows the measurement result of. (A) is a graph which shows the measurement result of the return loss characteristic in the free space of the linear polarization high gain high isolation coupler performed in the measurement system, (b) is a linear polarization height performed in the measurement system It is a graph which shows the measurement result of the coupler coupling characteristic (pass amplitude characteristic) of a gain high isolation coupler. (A) is a graph which shows the measurement result of the return loss characteristic in total reflection of the linear polarization high gain high isolation coupler performed in the measurement system, (b) is a linear polarization height performed in the measurement system It is a graph which shows the measurement result of the EVM value of a gain high isolation coupler. (A) is a graph which shows the measurement result of the return loss characteristic in total reflection of the linear polarization high gain high isolation coupler performed in the measurement system after fine adjustment, (b) measurement after fine adjustment It is a graph which shows the measurement result of the VSWR characteristic of the linear polarization high gain high isolation coupler performed in the system, and (c) is a coupler of the linear polarization high gain high isolation coupler performed in the measurement system after fine adjustment. It is a graph which shows the measurement result of a coupling | linkage characteristic (pass amplitude characteristic). (A) is a graph showing the return loss characteristic (return loss) when the horn antenna is disposed in free space, and (b) is a case where a pair of horn antennas are opposed to each other and are coupled at a coupling distance of 0 mm (C) is a graph showing the coupler coupling characteristic (pass amplitude characteristic) measured in the case of (h), the return loss characteristic at total reflection, which was measured when the entire surface of the horn antenna was covered with a metal plate (return (Loss)).

Hereinafter, the present invention will be described in detail by embodiments shown in the drawings.
The present invention can suppress the occurrence of the disturbance of the pass amplitude characteristic in the band and the disturbance of the return loss characteristic in the band due to the total reflection, and can improve the blocking performance, and is further preferable. In order to obtain a gain, it has the following configuration.
That is, the antenna device 1 of the present invention is composed of a hexahedron made of a conductive material, and an internal space formed to penetrate between the opposing first surface and the second surface, the first surface, and the second surface A coaxial waveguide conversion unit having a coaxial connector insertion hole for coaxial connector insertion formed in communication between the orthogonal third surface and the internal space, and a conductor for closing the opening on the second surface side of the internal space And a conductive connector body which is attached to the connector mounting hole from the inner space to the outside and the inner end does not protrude into the inner space, and the connector body A central conductor axially penetrating through the central portion of the connector and having a tip projecting from the inner end of the connector body into the inner space by a predetermined length, and a tip of the central conductor projecting into the inner space To adjust the projection length of the tip to a specific frequency band Ri is a radiator for radiating the radio wave from the center conductor in the inner space, the connector and having a, comprising the.
By providing the above configuration, it is possible to suppress the occurrence of the disturbance of the pass amplitude characteristic in the band and the disturbance of the reflection attenuation amount characteristic in the band due to the total reflection, and it is possible to improve the blocking performance. Even better EVM values can be obtained.
The features of the invention described above will be explained in detail using the following figures. However, the constituent elements, types, combinations, shapes, relative arrangements, and the like described in this embodiment are not intended to limit the scope of the present invention thereto alone, as long as they are not specifically described, and are merely illustrative examples. .
The above-mentioned features of the present invention will be described in detail below with reference to the drawings.

Next, embodiments of the present invention will be described with reference to the drawings.
<Structure of Antenna Device>
1 (a) is a front view showing the structure of an antenna device according to an embodiment of the present invention, (b) is a cross-sectional view taken along the line AA of (a), (c) is a right side view, and (d) is an upper surface (E) is a bottom view, (f) is a rear view, (g) is a cross-sectional view taken along the line BB in (a). FIGS. 2A and 2B are perspective views showing the structure of an antenna device according to an embodiment of the present invention. FIGS. 3A and 3B are exploded perspective views showing the structure of an antenna device according to an embodiment of the present invention. FIGS. 4 (a), (b) and (c) are a bottom view, a sectional view and a top view of a connector according to an embodiment of the present invention.
Hereinafter, the front view shown in FIG. 1A is used as the basic coordinate system, the left direction to the right of the drawing is the x-axis direction, and the direction orthogonal to the x-axis direction is the y-axis direction in the drawing; The z-axis direction will be described as a direction perpendicular to the y-axis direction (vertical direction).

This antenna device 1 has a waveguide main body 5 provided with an internal space 8 which is formed through the central portion of two opposing first and second surfaces M1 and M2 and whose second surface side opening is closed. An internal space 8 is disposed in one end portion of a connector mounting hole 22 which is formed to penetrate from the outer peripheral surface (third surface M3) different from the surface forming the internal space 8 to the internal space 8 The connector 50 exposed inside, the linearly polarized horn unit 200A connected to the first surface M1 side (non-closed surface side) of the internal space 8 of the waveguide main body 5, and the linearly polarized horn unit 200A In place of the circular polarization type polarization unit 100 (FIG. 5), or a circular polarization type horn unit 200B connected to the non-blocking surface side of the inner space via the circular polarization type polarization unit 100; Roughly.

The waveguide main body 5 is a rectangular block-shaped coaxial waveguide conversion portion 6 having a predetermined uniform thickness, and a thin plate for closing one opening of the internal space 8 formed to penetrate the coaxial waveguide conversion portion 6. And an occlusive member 30.
Each of the coaxial waveguide conversion unit 6 and the closing member 30 is made of a conductive material such as copper, iron, aluminum, brass, a metamaterial, or plastic plated with metal.
The coaxial waveguide conversion unit 6 is made of a hexahedron made of a conductive material, and has a first surface M1 and a second surface M2 facing each other, a third surface M3 facing each other, and a fourth surface M4 and a fifth surface facing each other It has a surface M5 and a sixth surface M6.

The coaxial waveguide conversion unit 6 is detachably attached to one surface of the first waveguide member 10 provided on one surface 6 a with a recess 11 to be the internal space 8 and to one surface of the first waveguide member 10. And a second waveguide member 20 which closes the one surface side of the recess 11 to form the internal space 8.
In FIGS. 3 (a) and 3 (b), round screw holes 13 are formed on the one surface 6a of the first waveguide member 10 at positions sandwiching the recess 11 between the second waveguides. A long hole 24 extending parallel to the z-axis direction of the internal space 8 is formed at a position in alignment (correspondence) with each screw hole 13 of the member 20, and a screw 25 is screwed into each screw hole through each long hole 24. It is configured to be wearable. In a state in which each screw 25 is screwed into each screw hole 13, the second waveguide member 20 is attached to the second waveguide member 20 within the range of the longitudinal direction (z-axis direction) length of the long hole 24. Is displaceable. In this example, the central portion in the longitudinal direction of the outer side surface (third surface M3) of the rectangular second waveguide member 20 is a recess, and the connector mounting hole 22 is formed in the recess. . Each long hole 24 is formed in a convex on both sides of the recess.
The position of the second waveguide member 20 facing the one surface 6 a of the first waveguide member 10 can be finely adjustable within the length of the elongated hole 24, whereby the antenna device 1 can be mounted. Electrical characteristics can be finely adjusted. As a result, it is possible to suppress the occurrence of the disturbance of the passing amplitude characteristic in the band and the disturbance of the reflection attenuation amount characteristic in the band due to the total reflection.

The recessed portion 11 to be the internal space 8 is a groove formed of three surfaces whose inner surfaces formed at the longitudinal direction central portion of the rectangular one surface 6a of the first waveguide member 10 are orthogonal to each other. On the other hand, an elongated plate-like second waveguide member 20 is configured to be removable by a screw 25. An internal space 8 is formed by fixing the second waveguide member 20 to the one surface 6 a and closing the recess 11.
The coaxial waveguide conversion unit 6 formed by assembling the second waveguide member 20 to the first waveguide member 10 has six surfaces, ie, the first surface M1 to the first surface, as described above. It is a rectangular parallelepiped or cube formed of six faces M6.
The internal space 8 is formed to penetrate between the opposing first surface M1 and the second surface M2 of the coaxial waveguide conversion unit 6. In addition, in the third surface M3 orthogonal to the first surface and the second surface, a connector mounting hole 22 for inserting a coaxial connector communicating with the internal space 8 is formed in a penetrating manner. In the present embodiment, the connector mounting hole 22 is formed through the second waveguide member 20.
In the internal space 8, only the first surface M1 side is opened by closing (welding) the second surface side opening with a conductive closing member.
The closing member 30 is formed with holes 30a corresponding to the screw holes 10a provided on the outer surface of the first waveguide member 10, and the screws 31 are made in a state in which the screw holes 10a and the holes 30a are communicated. By inserting and screwing, the closing member 30 is closely attached to the outer surface of the first waveguide member 10 and fixed without any gap.

<Connector>
As shown in FIGS. 1 to 4, the connector 50 is mounted in the connector mounting hole 22 outward from the internal space 8, and the conductive property is exposed and arranged in a state where the inner end 56 a does not protrude into the internal space 8. And a central conductor 60 disposed so as to penetrate the central portion of the connector main body in the y-axis direction and having the tip 60a project from the inner end 56a of the connector main body into the internal space 8 by a predetermined length L And the tip portion 60a of the central conductor projecting into the internal space 8, and by matching the projecting length L (FIG. 4) of the tip portion to a specific frequency band, the radio wave from the central conductor in the internal space 8 And a radiator 54b for emitting radiation. A male screw is formed on the outer periphery of one end of the connector main body 51. The relationship between the connector body and the central conductor is integrated via an insulating material.
As described above, although it has been described that the radiator 54b radiates a radio wave, this is an operation at the time of transmission, and at the time of reception, the radiator 54b absorbs (receives) a radio wave.

As shown in FIG. 4, the connector main body 51 of the connector 50 according to this embodiment includes a hollow cylindrical connector socket 52 made of a conductor and an insulator, and a flange 53 integrated with one end of the connector socket 52. A central conductor 60 axially penetrating the inside of the connector socket 52, a central conductor support 55 for fixedly supporting an appropriate position of the central conductor 60 on the inner periphery of the connector socket 52, and a central conductor And an insulator 56 filled to fill the space between the inner periphery 60 and the inner periphery of the connector socket 52.
A connector socket contact portion 54a is provided at the outer end of the central conductor 60, and a radiator 54b which is an element is provided at the inner end of the central conductor. The radiator 54b is a portion where the tip of the central conductor 60 protrudes a predetermined length from the inner end face of the connector socket 52, and is tuned to a desired frequency band by adjusting the length L of the element.
The length L in the y-axis direction, in which the central conductor 60 of the connector 50 is protruded from the inner end 56a, is a length obtained by multiplying 1/4 of the wavelength of a specific frequency band by a predetermined reduction rate 0.79. It is. The specific frequency band is 23 GHz to 29 GHz used for the fifth generation terminal (5G).
This makes it possible to design a length L which can be tuned to be specific to a particular frequency band.
As shown in FIG. 3A, in the present embodiment, a recess 23 for fitting the flange portion 53 of the connector to the inner side surface (the opposite side surface of the third surface M3) of the second waveguide member 20 is provided. It is formed. When the flange portion 53 is fitted and seated in the recess 23 by inserting the connector socket portion 52 of the connector into the connector mounting hole 22, the end face of the flange portion 53 is the inside of the second waveguide member 20. It is dimensioned to be flush with the side.
Thus, the antenna device 1 closes the second surface side opening of the internal space 8 of the coaxial waveguide conversion unit 6 made of a conductive material with the conductive closing member 30, and the inside of the internal space 8 of the radiator 54b. Since the projection length of the tip portion 60a of the central conductor 60 protruding in the center is adapted to a specific frequency band, the pass amplitude characteristic in the band and the return loss characteristic can be tuned in the band, and the blocking performance It can be improved and even better EVM values can be obtained.

In the opening on the first surface M1 side of the internal space 8, in other words, on the non-blocking surface side, a circular polarization type polarization unit 100 that converts radio waves radiated from the radiator 54b into linear polarization or circular polarization; Alternatively, one of the linearly polarized horn units 200A for improving gain and blocking radio waves coming from the outside is connected and disposed.
As shown in FIG. 10D, the circularly polarized horn unit 200B may be connected to the internal space 8 via the circularly polarized polarizer 100.
Thereby, the circular polarization characteristic can be easily obtained by the circular polarization type polarization unit 100, or the horn unit 200 can block radio waves coming from the outside and improve the gain.

<Circular polarization type polarization part>
FIGS. 5 (a), (b) and (c) are a front view, a top view, and a rear view of a circular polarization type polarization unit according to one embodiment of the present invention; 7 (a), 7 (b) and 7 (c) are cross-sectional views taken along the lines CC, DD, and EE of FIG. 5 (a). 7 (d) and 7 (e) are cross-sectional views taken along the line FF and G-G in FIG. 7 (b). 8A and 8B are a front external perspective view of the circular polarization type polarization unit and an external perspective view on the back side.

The circular polarization type polarization unit 100 is connected to the opening on the first surface M 1 side of the internal space 8.
The circular polarization type polarization unit 100 is formed in a block 101 of a rectangular parallelepiped (or a cube) made of a conductive material such as copper, iron, aluminum, brass, metamaterial, or plastic metal plated. The waveguide space 110 is formed through. That is, the waveguide space 110 is formed to penetrate the two opposing surfaces N1 and N2 of the block 101.
In this example, a block 101 having a depth L1 of 22 mm, a height L2 of 14 mm, and a width L3 of 24 mm will be described as an example.
In the waveguide space 110, the opening on the first surface N1 side is circular, while the opening on the second surface N2 side is a horizontally long rectangle.
That is, the waveguide space 110 has a cylindrical shape with the same diameter (φ 8.24 mm) from the opening side of the first surface N1 to a portion 10 mm inside. This cylindrical waveguide space portion is referred to as a circular waveguide portion 120. In the circular waveguide portion 120, a 0.5 mm thick rectangular deflection plate 140 made of Teflon (dielectric material) or the like is obliquely fixed through a circular central portion in an oblique posture. There is. That is, the length of the deflection plate 140 corresponds to the diameter of the circular waveguide portion 120.

The waveguide space 110 is a space having a substantially square pole shape from the opening side of the second surface N2 to a portion 12 mm inside, and this waveguide space portion is referred to as a rectangular waveguide portion 130.
The inner back side opening of the circular waveguide portion 120 and the inner back side opening of the rectangular waveguide portion 130 are in communication with each other in a state in which the central axes A1 and A2 are in line.
In addition, the circular opening (peripheral part 121 a) on the inner back part side of the circular waveguide part 120 is beyond the circular opening ( peripheral parts 131 a, 132 a) on the inner back part side of the rectangular waveguide part 130. It does not extend and ends at the position of the opening on the inner side of the rectangular waveguide portion 130. Therefore, the circular opening (peripheral part 121a) on the inner back part side of the circular waveguide part 120 and the circular opening ( peripheral parts 131a, 132a) on the inner back part side of the rectangular waveguide part 130 are It has a circular shape that matches the shape.
Thus, the deflector plate 140 remains within the axial length of the circular waveguide portion 120 and does not extend beyond the inner back opening of the rectangular waveguide portion 130.

The opening on the second surface N2 (outside) of the rectangular waveguide portion 130 is rectangular, but the shape of the opening on the inner back side is the inner back opening (circular) of the circular waveguide portion 120 It is circular with the same shape and size. That is, although the two opposite short sides 131 (4.3 mm) of the outer opening of the rectangular waveguide portion 130 are straight at the outer opening, the inner back portion of the circular waveguide portion 120 at the inner back portion 131 a It has an arc shape so as to be aligned with the peripheral edge portion 121a of the side opening (circular shape: φ 8.24 mm). That is, the arc-shaped inner back portion 131 a of each short side 131 is terminated at the periphery of the inner back portion opening (circular) of the circular waveguide portion 120.
As shown in FIG. 5, FIG. 7, FIG. 8, etc., the distance L4 (8.6 mm) between the short sides 131 is slightly smaller than the diameter (.phi. 8.24 mm) of the inner back side opening of the circular waveguide portion 120. As it is larger, the distance between the short sides gradually decreases (reduces) toward the inner back part, and finally the inner back part 131a of the short side is the inner back opening (circular) of the circular waveguide portion 120 Aligned with the rim of the

On the other hand, since the distance L5 (4.3 mm) between the two opposite long sides 132 of the outer opening of the rectangular waveguide portion 130 is smaller than the diameter of the inner opening of the circular waveguide portion 120, The distance L5 between the long sides gradually increases (spreads out) toward the back part, and the inner back part 132a of the long side is finally the periphery of the inner back side opening (circular) of the circular waveguide portion 120. It is consistent with.
An inner back portion 131a of each short side 131 and an inner back portion 132a of each long side 132 are connected in a circle, thereby forming a circular shape that matches the inner back side opening of the circular waveguide portion 120. ing.
Further, the inner wall 133 on the inner side of the rectangular waveguide portion 130 excluding the rectangular outer opening is curved as shown in FIGS.
The circular polarization type polarization section 100 formed as described above is connected to the non-closing surface side (opening surface side) of the internal space 8 of the first waveguide member 10, and is radiated from the radiator 54b. Convert the radio waves into circularly polarized waves.

<Linear polarization type horn unit 200A>
The linearly polarized horn unit 200A is connected to the opening on the first surface M1 side of the internal space 8.
As shown in FIG. 1 to FIG. 3, the linearly polarized horn unit 200A is made of a plate material such as copper, iron, aluminum, brass, metamaterial, or plastic plated with metal in a horn shape as illustrated. In this example, by fixing and integrating the side edges of the four trapezoidal plate materials 201a to 201d (FIG. 3), the one end opening becomes a quadrangle having a small diameter and the other end opening is large. It is a square of diameter.
The linearly polarized horn unit 200A is linearly polarized by a truncated square pyramid horn. In addition, truncated means the state and shape which cut | disconnected the site | part of predetermined length from the top part of a square weight by the surface orthogonal to central-axis A1, A2.
As described above, by setting the horn unit 200 to be linearly polarized by the truncated square pyramid-shaped linearly polarized horn unit 200A, it is possible to easily obtain linear polarization characteristics having directivity characteristics, and It is possible to block the radio wave coming from outside the pointing direction and to improve the gain.

<Circular polarized horn unit 200B>
Fig.9 (a) is an external appearance perspective view which shows the circular polarization type horn part 200B of the antenna apparatus which concerns on other embodiment (16 mm horn) of this invention, (b) is a front view, (c) is a side view. , (D) is a rear view. FIGS. 9 (e), (f) and (g) are a front view, a side view and a rear view of a circular polarized horn unit 200B of an antenna device according to another embodiment (15 mm horn) of the present invention.
The circularly polarized horn unit 200B has a frusto-conical shape, and the circularly polarized horn unit 200B is connected to the opening in a circular shape on the first surface N1 side of the circularly polarized polarizer 100.
The small-diameter circular opening of the circular polarization type horn section 200B has the same shape as the opening on the first surface N1 side of the circular polarization type polarization section 100, and is fixed by welding or the like.
The circularly polarized horn unit 200B is circularly polarized by a truncated conical horn. In addition, truncated means the state and shape which cut | disconnected the site | part of predetermined length from the top part of a cone by the surface orthogonal to central-axis A1, A2.
As described above, the horn portion 200 can obtain circular polarization characteristics with directivity characteristics easily by making it circularly polarized by the truncated conical circular polarization type horn portion 200B, and directivity It is possible to block radio waves coming from outside the direction and to improve the gain.

<Modification of Antenna Device>
10 (a) to 10 (d) are side views showing modifications of the antenna device according to the embodiment of the present invention. FIG. 11 is a diagram showing a chart representing the configuration of a modification of the antenna device according to an embodiment of the present invention.
FIG. 10A shows the configuration of a linearly polarized light coupler 1A provided with a coaxial waveguide conversion unit 6 and a connector 50. FIG. Specifically, the coaxial waveguide conversion unit 6 includes the first waveguide member 10, the second waveguide member 20, and the closing member 30.
FIG. 10B shows the configuration of a circular polarization coupler 1B provided with a circular polarization type polarization unit 100 for converting into circular polarization, a coaxial waveguide conversion unit 6, and a connector 50.
FIG. 10C shows the configuration of a linearly polarized high gain high isolation coupler 1C provided with a linearly polarized horn unit 200A, a coaxial waveguide conversion unit 6, and a connector 50.
FIG. 10D shows a circularly polarized high gain high isolation coupler 1D including a circularly polarized horn unit 200B, a circularly polarized polarization unit 100, a coaxial waveguide conversion unit 6, and a connector 50. Shows the configuration of

<Performance of Each Modified Example of Antenna Device>
The pass amplitude characteristic, return loss characteristic, EVM value, gain, and VSWR in the respective modified examples of the antenna device are shown in the following table.

The first waveguide member 10 is a rectangular waveguide satisfying a frequency band of 21.7 GHz to 33.0 GHz, an inner diameter dimension of the inner space 8 of 8.636 mm × 4.318 mm, and an EIA standard WR-34. use.
As described above, since the linearly polarized light coupler 1A has a variation width of 5 dB or less over the specific frequency band, the passing amplitude characteristic of the radio wave emitted from the own antenna device has a good passing amplitude characteristic of the radio wave, EVM values can be obtained.
Further, the reflection attenuation amount characteristic in total reflection of radio waves radiated from each coupler (antenna apparatus) has a fluctuation range of 10 dB or less over a specific frequency band, so that a good EVM value can be obtained.

In the linear polarization high gain high isolation coupler 1C and the circular polarization high gain high isolation coupler 1D, as an actual effect, the isolation property representing shielding of radio waves coming from the outside is good, and it is an object to be measured. Even if this antenna is placed at two places on a mobile phone and tested, interference between the two antennas can be prevented.
The material of the coaxial waveguide conversion unit 6, the circular polarization type polarization unit 100, and the horn unit 200 is copper, iron, aluminum, brass, metamaterial, plastic plated metal, plastic or resin By forming the metal coating, it is possible to suppress the occurrence of the disturbance of the pass amplitude characteristic in the band and the disturbance of the return loss characteristic in the band due to the total reflection, and have the directivity characteristic. This can improve the blocking performance outside the pointing direction, and can also obtain good EVM values and gains.
In addition, CVD (chemical vapor deposition), PVD (physical vapor deposition), metal wire spraying, metal powder spraying, etc. are known as a method of applying metal coating to plastics and resins.

<Antenna system and measurement system>
Fig.12 (a) is a block diagram which shows the antenna system which used the antenna apparatus which concerns on one Embodiment of this invention, and a measurement system, FIG.12 (b) is a perspective view which shows the calibration kit used for the calibration of the said measurement system. It is.
The antenna system 300 shown in FIG. 12A is any one of a linear polarization coupler 1A, a circular polarization coupler 1B, a linear polarization high gain high isolation coupler 1C, and a circular polarization high gain high isolation coupler 1D as an antenna device. Each antenna device is provided as a first antenna device 301 and a second antenna device 303, and radio waves radiated from the first antenna device 301 are disposed to face each other in the radiation direction of the first antenna device 301. The signal is received by the second antenna device 303.

The measurement system 310 includes a network analyzer 305 and a monitor 313. The coaxial cable 307 is connected between the terminal P1 of the network analyzer 305 and the connector of the first antenna device 301, and the terminal P2 and the second antenna device 303 are connected. A coaxial cable 309 is connected between the connector and the connector.
Furthermore, a monitor cable 311 is connected between the monitor terminal 305 m of the network analyzer 305 and the terminal 313 m of the monitor 313. As the network analyzer 305, for example, MS46322B manufactured by Anritsu Corporation is used.
The antenna device is disposed close to (in close contact with) the object to be measured, and is used, for example, to measure radio waves radiated from the object to be measured. The object to be measured is a device that generates electromagnetic waves, such as a cellular phone, a mobile terminal, etc. For example, the object is a next-generation cellular phone (5G) using a frequency band of 23 GHz to 29 GHz.
The measurement system 310 is suitable for measuring the coupling characteristic between the first antenna device 301 and the second antenna device 303 provided in the antenna system 300 and the return loss characteristic.

As described above, the antenna device 1 is disposed at a desired position or in close proximity to the device under test, and receives radio waves emitted from the device under test. Since the disturbance of the pass amplitude characteristic in the band and the disturbance of the return loss characteristic in the band due to the total reflection are suppressed, it is possible to obtain a good EVM value.
In addition, the antenna device 1 is disposed at a desired position with respect to the object to be measured or used in close proximity, and radiates radio waves to the object to be measured. Since the disturbance of the passing amplitude characteristic in the band and the disturbance of the return loss characteristic in the band due to the total reflection are suppressed, it is possible to radiate a good radio wave to the object to be measured.
In addition, the radio wave radiated from the first antenna device 301 is received by the second antenna device 303 disposed opposite to the radiation direction of the first antenna device 301, so that the disturbance of the passing amplitude characteristic in the band or It is possible to suppress the occurrence of the disturbance of the return loss characteristic in the band due to the total reflection, and to obtain a good EVM value.
Furthermore, by arranging the device under test between the first antenna device 301 and the second antenna device 303, it is possible to measure the radio wave emitted from the device under test or when it is received by the device under test, The degree of influence by objects can be measured.

In a measurement system 310 shown in FIG. 12A, a calibration kit 320 shown in FIG. 12B is used for calibration.
The calibration kit 320 includes four connectors: a connector 320S (SHORT), a connector 320o (OPEN), a connector 320L (LOAD), and a connector 320T (THRU). As the calibration kit 320, for example, TOSLKF 50A-40 manufactured by Anritsu Corporation is used.

<Calibration procedure of measurement system>
FIG. 13 is a flowchart showing a calibration procedure of the measurement system shown in FIG. In detail, the calibration procedure of the measurement system 310 performed prior to the measurement of the return loss characteristic of the antenna device 1 and the coupling characteristic is shown.
In step S5, a measurement frequency (for example, 20 GHz to 30 GHz) is input to the network analyzer 305.
In step S10, the network analyzer 305 is set to the calibration CAL mode.
In step S15, the connector 320S of the calibration kit is connected to the end of the coaxial cable 307 connected to the terminal P1 of the network analyzer 305 so that the end of the coaxial cable 307 is short circuited (SHORT).
In step S20, the network analyzer 305 performs in-measuring-apparatus operation according to the user's operation.
In step S25, the connector 320o of the calibration kit is connected to the end of the coaxial cable 307 connected to the terminal P1 of the network analyzer 305, and the end of the coaxial cable 307 is opened (OPEN).
In step S30, the network analyzer 305 performs in-measuring-apparatus operation according to the user's operation.
In step S35, the connector 320L of the calibration kit is connected to the end of the coaxial cable 307 connected to the terminal P1 of the network analyzer 305, and a load (for example, 50 Ω) is connected to the end of the coaxial cable 307 Set to LOAD).
In step S40, the network analyzer 305 performs in-measuring-apparatus operation according to the user's operation.

In step S45, the connector 320S of the calibration kit is connected to the end of the coaxial cable 309 connected to the terminal P2 of the network analyzer 305 so that the end of the coaxial cable 309 is in a short circuit state (SHORT).
In step S50, the network analyzer 305 performs in-measuring-machine operation according to the user's operation.
In step S55, the connector 320o of the calibration kit is connected to the end of the coaxial cable 309 connected to the terminal P2 of the network analyzer 305, and the end of the coaxial cable 309 is opened (OPEN).
In step S60, the network analyzer 305 performs in-measuring-apparatus operation according to the user's operation.
In step S65, the connector 320L of the calibration kit is connected to the end of the coaxial cable 309 connected to the terminal P2 of the network analyzer 305, and a load (for example, 50 Ω) is connected to the end of the coaxial cable 309 Set to LOAD).
In step S70, the network analyzer 305 performs in-measuring-apparatus operation according to the user's operation.

In step S75, the connector 320T of the calibration kit is connected to the ends of the coaxial cables 307 and 309 connected to the terminals P1 and P2 of the network analyzer 305, and the ends of the coaxial cables 307 and 309 pass each other (THRU) Make it
In step S70, the network analyzer 305 performs in-measuring-apparatus operation according to the user's operation.
As a result, with respect to the measurement system including the network analyzer 305 and the coaxial cables 307 and 309, it is possible to calibrate the amplitude characteristic, the return loss characteristic, the phase characteristic and the like in a flat state in the set frequency band.

<Return loss measurement procedure>
FIG. 14 is a flowchart showing a procedure of measuring the return loss amount performed in the measurement system shown in FIG.
In step S105, the connector of the first antenna device 301 is connected to the end of the coaxial cable 307 connected to the terminal P1 of the network analyzer 305 to make it possible to perform measurement.
In step S110, the network analyzer 305 performs in-measuring-machine operation according to the user's operation, and displays the return loss on the monitor 313. At this time, the power in the sweep of the frequency band output from the terminal P1 of the network analyzer 305 is reflected by the first antenna device 301, and the power returned from the first antenna device 301 is measured.

<Typical characteristics immediately after assembly, Typical characteristics after adjustment>
FIGS. 15 (a) and 15 (b) are graphs showing representative characteristics immediately after assembly of the linear polarization coupler 1A and representative characteristics after adjustment.
In the representative characteristics immediately after assembly of the linear polarization coupler 1A shown in FIG. 15A, the return loss characteristic value is concentrated at a level near -10 dB within the frequency band of 25 GHz to 29 GHz, and around 23 GHz. A strong resonance of -35 dB or less is generated.
Therefore, the tip portion 60 a of the central conductor 60 protruding into the internal space 8 is mounted by facing the one surface 6 a of the first waveguide member 10 so as to finely adjust the position of the second waveguide member 20. You can fine-tune the position of. As a result, it is possible to suppress the occurrence of the disturbance of the passing amplitude characteristic in the band and the disturbance of the reflection attenuation amount characteristic in the band due to the total reflection.
As a result, in the representative characteristics after adjustment of the linear polarization coupler 1A shown in FIG. 15 (b), the level is improved to around -15 dB in the return loss characteristic value in the frequency band of 25 GHz to 29 GHz, The strong resonance has also been improved to a level of -30 dB.

<Measurement procedure of coupling loss characteristics>
FIG. 16 is a flowchart showing the measurement procedure of the coupling loss characteristic performed in the measurement system shown in FIG.
In step S155, the connector of the first antenna device 301 is connected to the end of the coaxial cable 307 connected to the terminal P1 of the network analyzer 305 to enable measurement.
In step S160, the network analyzer 305 performs in-measurement operation, and displays the return loss of the first antenna device 301 on the monitor 313 (FIG. 17A).
In step S165, the connector of the second antenna device 303 is connected to the end of the coaxial cable 309 connected to the terminal P2 of the network analyzer 305 to make it possible to perform measurement.
In step S170, the network analyzer 305 performs in-measurement operation, and displays the return loss of the second antenna device 303 on the monitor 313 (FIG. 17D).
In step S175, the first antenna device 301 and the second antenna device 303 face each other and approach (close).
In step S180, the network analyzer 305 performs in-measurement operation, and the coupling characteristic between the first antenna device 301 and the second antenna device 303 (FIG. 17B), and the return loss (FIG. 17C). Is displayed on the monitor 313.

<Measurement results of return loss characteristics, coupling characteristics>
FIGS. 17 (a) to 17 (d) are graphs showing the measurement results of the return loss characteristic and the coupling characteristic performed in the measurement system.
In the return loss characteristic of the first antenna device 301 shown in FIG. 17A, a level of −10 dB or less is generated in the frequency band of 23 GHz to 29 GHz.
In the return loss characteristic of the second antenna unit 303 shown in FIG. 17D, a level of −10 dB or less is generated in the frequency band of 23 GHz to 29 GHz.
On the other hand, on the first antenna device side of the coupling characteristic between the first antenna device 301 and the second antenna device 303 shown in FIG. 17B, the variation width is in the frequency band of 23 GHz to 29 GHz. The level difference is suppressed to within 3 dB, showing extremely flat coupling characteristics.
On the other hand, on the second antenna device side of the coupling characteristic between the first antenna device 301 and the second antenna device 303 shown in FIG. 17C, the fluctuation range is about 3 dB or less in the frequency band of 23 GHz to 29 GHz. It is suppressed by the level difference, and shows a very flat return loss characteristic.

<Antenna system and measurement system related to EVM measurement>
FIG. 18 is a block diagram showing an antenna system and measurement system related to EVM measurement using the antenna device according to one embodiment of the present invention.
The antenna system 300 shown in FIG. 18 includes any one of a linear polarization coupler 1A, a circular polarization coupler 1B, a linear polarization high gain high isolation coupler 1C, and a circular polarization high gain high isolation coupler 1D as an antenna device. A second antenna apparatus including a first antenna apparatus 301 and a second antenna apparatus 303; and a radio wave radiated from the first antenna apparatus 301 disposed opposite to a radiation direction of the first antenna apparatus 301; The signal is received by the antenna device 303.

The measurement system 340 includes a vector signal generator 325, a pseudo transmitter 327, a signal analyzer 329, and a personal computer PC 331, and a coaxial cable between a terminal 325a of the vector signal generator 325 and a terminal 327 a of the pseudo transmitter 327. The connection 335 is connected, and the coaxial cable 333 is connected between the terminal 325 b of the vector signal generator 325 and the terminal 327 b of the pseudo transmitter 327. For the vector signal generator 325 and the signal analyzer 329, for example, MG3710A and MS2850A manufactured by Anritsu Co., Ltd. are used, respectively.
A coaxial cable 321 is connected between the terminal 327 c of the pseudo transmitter 327 and the connector of the first antenna device 301.
A coaxial cable 323 is connected between the connector of the second antenna device 303 and the terminal 329 a of the signal analyzer 329.
Furthermore, a USB cable 137 is connected between the USB terminal 329 m of the terminal 329 b of the signal analyzer 329 and the USB terminal 331 a of the personal computer PC 331.
The antenna device is disposed close to (in close contact with) the object to be measured, and is used, for example, to measure radio waves radiated from the object to be measured. The object to be measured is a device that generates electromagnetic waves, such as a cellular phone, a mobile terminal, etc. For example, the object is a next-generation cellular phone (5G) using a frequency band of 23 GHz to 29 GHz.
The measurement system 340 is suitable for measuring EVM characteristics between the first antenna device 301 and the second antenna device 303 provided in the antenna system 300 and between the object to be measured and the second antenna device 303. ing.

<Calibration procedure of EVM measurement>
FIG. 19 is a flow chart showing a calibration procedure performed in the measurement system shown in FIG.
In step S205, the coaxial cable 321 connected to the terminal 327c of the pseudo transmitter 327 is connected to the first antenna device 301, and the coaxial cable 323 connected to the connector of the second antenna device 303 is a terminal of the signal analyzer 329. Connect to 329a.
In step S210, as the setup of the vector signal generator 325, the frequency is set to 28.5 GHz, the bandwidth to 100 MHz, and the modulation to Pre-Standard CP-OFDM Downlink.
In step S215, the output level of the vector signal generator 325 is adjusted.
In step S220, the input level of the signal analyzer 329 is adjusted.
In steps S215 and S220, adjustment is made so that the Total EVM (rms) value (FIG. 21) of the signal analyzer 329 displayed on the monitor of the personal computer PC 331 is minimized.
In the EVM measurement based on the coupling between the antenna devices, the EVM value needs to be 1% or less (the closer to 0%, the better). In fact, it is to give reliability to the measured value when measuring the EVM value of the fifth generation terminal (5G), and it becomes unreliable if it exceeds 1%.
For this reason, it is necessary to keep the waveform of the coupling characteristic between the antenna devices flat and to have an EVM value of 1% or less at the time of coupling, and to make the waveform at the time of total reflection of the antenna device free from disturbance.

<EVM measurement procedure>
FIG. 20 is a flowchart showing an EVM measurement procedure performed in the measurement system shown in FIG.
In step S255, the coaxial cable 321 connected to the terminal 327c of the pseudo transmitter 327 is connected to the first antenna device 301.
In step S260, the coaxial cable 323 connected to the connector of the second antenna device 303 is connected to the terminal 329a of the signal analyzer 329.
In step S265, the first antenna device 301 and the second antenna device 303 face each other and approach (close).
In step S270, the EVM value (FIG. 21) is displayed on the monitor of the signal analyzer 329.
Here, FIG. 21 is a diagram showing a monitor screen showing EVM values measured in the measurement system shown in FIG.
Here, EVM refers to modulation accuracy, which is calculated by calculating how much the symbol point of the actual signal deviates with respect to the ideal symbol point (not shown) and is represented by%. When multi-bit modulation is performed in digital communication, the number of symbols increases, and the requirement for modulation accuracy becomes severe. If the modulation accuracy is bad, that is, if the EVM value is bad, it means that the symbol quality (symbol 340 in FIG. 21) is disturbed and the communication quality of the digital communication is bad. In the worst case, communication becomes impossible.

<Return loss characteristics in free space of linear polarization coupler>
FIG. 22A is a graph showing measurement results of return loss characteristics in free space of the linear polarization coupler performed in the measurement system.
In the return loss characteristic in free space of the linear polarization coupler 1A shown in FIG. 22 (a), in the target frequency band of 23 GHz to 29 GHz, it becomes -10 dB or less and the execution power value becomes -15 dB or less ing.

<Coupler Coupling Characteristics of Linear Polarization Coupler>
FIG. 22 (b) is a graph showing the measurement results of the coupler coupling characteristic (pass amplitude characteristic) of the linear polarization coupler performed in the measurement system.
One pair of linear polarization couplers 1A are coupled at around -10 dB, and the pass amplitude characteristic is within the fluctuation range of about 5 dB in the target frequency band of 23 GHz to 29 GHz, as in the prior art. There is no steep waveform disturbance (FIG. 27 (b)), and it shows extremely flat coupling characteristics.

<Return loss characteristics at total reflection of linearly polarized coupler>
FIG. 23 (a) is a graph showing measurement results of return loss characteristics at total reflection of a linear polarization coupler performed in the measurement system.
When the entire surface of the opening of the linear polarization coupler 1A is covered with a metal plate, the return loss characteristic has a fluctuation range of about 10 dB in the target frequency band of 23 GHz to 29 GHz, and There is no such steep waveform disturbance (FIG. 23 (c)) and an extremely flat return loss characteristic is shown.

<EVM value of linear polarization coupler>
FIG.23 (b) is a graph which shows the measurement result of the EVM value of the linear polarization coupler performed in the measurement system.
When one pair of linear polarization couplers 1A is coupled at a coupling distance of 0 mm, for example, at a frequency of 28.5 GHz, a good EVM value of 1% or less of EVM (rms) is shown.

<Linear polarization high gain high isolation coupler return loss characteristics in free space>
FIG. 24A is a graph showing measurement results of return loss characteristics in free space of the linear polarization high gain high isolation coupler performed in the measurement system.
In the return loss characteristic of the linear polarization high gain high isolation coupler 1C shown in FIG. 24 (a) in free space, the target power value is -10 dB or less in the target frequency band of 23 GHz to 29 GHz- It is less than 13 dB.

Coupler Coupling Characteristics of Linearly Polarized High Gain High Isolation Coupler
FIG.24 (b) is a graph which shows the measurement result of the coupler coupling characteristic (pass amplitude characteristic) of the linear polarization high gain high isolation coupler performed in the measurement system.
The linear polarization high gain high isolation coupler 1C and the linear polarization high gain high isolation coupler 1C are coupled at around -10 dB, and the pass amplitude characteristic is about 5 dB in the target frequency band of 23 GHz to 29 GHz. , And there is no sharp waveform disturbance as in the prior art (FIG. 27 (b)), and it shows extremely flat coupling characteristics.

<Return Loss Attenuation on Total Reflection of Linearly Polarized High Gain High Isolation Coupler>
FIG. 25A is a graph showing measurement results of return loss characteristics at total reflection of a linearly polarized high gain high isolation coupler performed in a measurement system.
When the entire surface of the opening of the linear polarization high gain high isolation coupler 1C is covered with a metal plate, the fluctuation range of the return loss characteristic falls within the range of about 10 dB in the target frequency band of 23 GHz to 29 GHz. There is no steep waveform disturbance (FIG. 27 (c)) as in the prior art, and an extremely flat return loss characteristic is shown.

<EVM value of linear polarization high gain high isolation coupler>
FIG. 25B is a graph showing the measurement results of the EVM value of the linear polarization high gain high isolation coupler performed in the measurement system.
When one pair of linear polarization high gain high isolation couplers 1C are coupled at a coupling distance of 0 mm, for example, at a frequency of 28.5 GHz, a good EVM value of 1% or less of EVM (rms) is shown.

<Return Attenuation Characteristic of Total Polarization High Gain High Isolation Coupler after Adjustment>
FIG. 26A is a graph showing measurement results of return loss characteristics at total reflection of a linear polarization high gain high isolation coupler performed in a measurement system after fine adjustment.
When the entire opening of the linearly polarized high gain high isolation coupler 1C is covered with a metal plate, the fluctuation range of the return loss characteristic falls within the range of about 15 dB in the frequency band of 23 GHz to 43 GHz. There is no steep waveform disturbance (Fig. 27 (c)) such as, and a very flat return loss characteristic is shown.

<VSWR characteristics of linearly polarized high gain high isolation coupler after adjustment>
FIG. 26 (b) is a graph showing the measurement results of the VSWR characteristics of the linearly polarized high gain high isolation coupler measured in the measurement system after fine adjustment.
When a sweep signal of 0 dBm is input to the linearly polarized high gain high isolation coupler 1C, the VSWR characteristic falls within the range of 1.8 or less in the frequency band of 23 GHz to 43 GHz, and shows extremely good VSWR characteristic. ing.

<Coupling characteristic of linearly polarized high gain high isolation coupler after adjustment>
FIG. 26C is a graph showing the measurement results of the coupler coupling characteristic (pass amplitude characteristic) of the linear polarization high gain high isolation coupler performed in the measurement system after fine adjustment.
The linearly polarized high gain high isolation coupler 1C and the linearly polarized high gain high isolation coupler 1C are coupled at around -10 dB, and the pass amplitude characteristic is in the range of about 5 dB in the frequency band of 23 GHz to 43 GHz. In FIG. 27, there is no sharp waveform disturbance as in the prior art (FIG. 27 (b)), and it shows extremely flat coupling characteristics.

<Summary of action and effect of aspect example of this embodiment>
<First aspect>
The antenna device 1 of the present embodiment is a hexahedron made of a conductive material, and is formed between the opposing first surface M1 and the second surface M2 to form an internal space 8, a first surface M1, and a second surface M1. A coaxial waveguide conversion portion 6 having a coaxial connector insertion hole 22 for inserting a coaxial connector formed in communication (penetration) between a third surface M3 orthogonal to the surface M2 and the internal space 8; A waveguide main body 5 provided with a conductive closing member 30 for closing the opening on the second surface side of the connector, and the connector mounting hole 22 from the internal space to the outside, the inner end being the internal space 8 A conductive connector main body 51 not projecting inward and a central portion of the connector main body 51 are axially penetrated, and a tip end portion is projected from the inner end of the connector main body 51 into the internal space 8 by a predetermined length A central conductor 60 and a tip 6 of the central conductor 60 projecting into the internal space 8 and a connector 50 having a radiator 54b for radiating radio waves from the central conductor into the internal space 8 by adapting the projection length of the tip 60a to a specific frequency band. It is characterized by
According to this aspect, the second surface side opening of the internal space 8 of the coaxial waveguide conversion unit 6 made of a conductive material is closed by the conductive closing member 30, and the radiator 54b protrudes into the internal space 8. The projection length of the tip 60a of the central conductor 60 is adapted to a specific frequency band.
As a result, the disturbance of the pass amplitude characteristic in the band and the return loss characteristic can be tuned in the band, the blocking performance can be improved, and a better EVM value can also be obtained.

Second Embodiment
The antenna device 1 of this aspect is connected to the non-closed surface side (opening surface side) of the internal space 8 of the coaxial waveguide conversion unit 6 and is a circle that converts radio waves radiated from the radiator 54b into circularly polarized waves. It is connected directly to the non-blocking surface side (opening surface side) of the polarization type polarization unit 100 or the internal space 8 or via the circular polarization type polarization unit 100 to block radio waves coming from the outside. A horn unit 200 is provided.
According to this aspect, the radio wave radiated from the radiator 54 b by the circular polarization type polarization unit 100 is converted to circular polarization, or connected to the horn unit 200 via the circular polarization type polarization unit 100. By having directivity characteristics, radio waves coming from outside the directivity direction are blocked.
Thereby, the circular polarization characteristic can be easily obtained by the circular polarization type polarization unit 100, or by having the directivity characteristic by the horn unit 200, the radio wave coming from outside the directivity direction is blocked and the gain Can be improved.

Third Embodiment
The horn unit 200 of this embodiment is characterized in that it is linearly polarized by the truncated square pyramid linear polarized horn unit 200A or circular polarized by the truncated conical circular polarized horn unit 200B. Do.
According to this aspect, the linear polarization characteristic or the circular polarization characteristic is easy by making it linearly polarized by the linear polarization type horn unit 200A or circularly polarized by the circular polarization type horn unit 200B. It is possible to improve the gain while blocking the radio wave coming from the outside of the pointing direction and having the directivity characteristic.

<Fourth aspect>
The coaxial waveguide conversion unit 6 of the present embodiment is attached to and detached from the first waveguide member 10 provided with the recess 11 serving as the internal space 8 on one surface 6 a and one surface of the first waveguide member 10. And a second waveguide member 20 which closes the one surface side of the recess 11 by being freely attached to form the internal space 8, and the recess 11 is formed on one surface of the first waveguide member 10. A screw hole is formed at a position sandwiching the space between them, and a long hole 24 extending parallel to the axial direction of the internal space 8 at a position matching (correspondence) with each screw hole 13 of the second waveguide member 20. Are formed, and screws can be screwed into the respective screw holes 13 through the respective long holes 24.
According to this aspect, each screw hole 13 for each long hole 24 can be screwed in such a manner that a screw can be screwed into each screw hole 13 via each long hole 24 extending parallel to the axial direction of the internal space 8. You can fine-tune the position of. As a result, it is possible to suppress the occurrence of the disturbance of the passing amplitude characteristic in the band and the disturbance of the reflection attenuation amount characteristic in the band due to the total reflection.

<Fifth aspect>
The coaxial waveguide conversion unit 6 of this embodiment is characterized in that the position of the second waveguide member 20 is finely adjustable so as to face the one surface 6 a of the first waveguide member 10.
According to this aspect, the center conductor 60 protruding into the internal space 8 can be mounted by finely adjusting the position of the second waveguide member 20 so as to face the surface 6 a of the first waveguide member 10. The position of the tip portion 60a of can be finely adjusted. As a result, it is possible to suppress the occurrence of the disturbance of the passing amplitude characteristic in the band and the disturbance of the reflection attenuation amount characteristic in the band due to the total reflection.

<Sixth aspect>
The axial length L of the center conductor 60 of the coaxial connector according to the present embodiment protruded from the inner end 56a is 1⁄4 of the wavelength of a specific frequency band multiplied by a predetermined reduction rate of 0.79. It is characterized in that it is a length.
According to this aspect, it is possible to design a length L which can be tuned specifically to a specific frequency band.

<Seventh aspect>
The horn portion 200 of this embodiment includes a first internal space 8 having a vertical width of 4.3 mm and a horizontal width of 8.6 mm, and a second internal space 8 having a vertical width of 15 mm to 16 mm and a horizontal width of 15 mm to 16 mm. It is characterized by
According to this aspect, by providing the first internal space 8 having a vertical width of 4.3 mm and a horizontal width of 8.6 mm, and a second internal space 8 having a vertical width of 15 mm to 16 mm and a horizontal width of 15 mm to 16 mm. It is possible to create a horn portion that can obtain a good gain by specializing in a specific frequency band of 23 GHz to 29 GHz.

Eighth Embodiment
The material of the coaxial waveguide conversion part 6, the circular polarization type polarization part 100, and the horn part 200 of this embodiment is copper, iron, aluminum, brass, metamaterial, plastic plated metal, or plastic And a resin coated with a metal coating.
According to this aspect, the material of the coaxial waveguide conversion part 6, the circular polarization type polarization part 100, and the horn part 200 is metal plated on copper, iron, aluminum, brass, metamaterial, plastic By forming the metal coating on the plastic or the resin, the disturbance of the passing amplitude characteristic in the zone and the disturbance of the reflection attenuation amount characteristic in the zone can be suppressed and shut off. Performance can be improved and even better EVM values can be obtained.

<Ninth aspect>
The linearly polarized light coupler 1A (antenna apparatus) of this aspect is characterized in that the pass amplitude characteristic of the radio wave radiated from the own antenna apparatus has a fluctuation range of 5 dB or less over a specific frequency band.
According to this aspect, since the pass amplitude characteristic of the radio wave radiated from the own antenna device has a fluctuation width within 5 dB over the specific frequency band, it is possible to obtain a good pass amplitude characteristic of the radio wave.

<10th aspect>
The fluctuation range of the reflection attenuation amount characteristic in the total reflection of the radio wave radiated from the antenna device 1 of the present embodiment is characterized in that it has a gentle waveform within 10 dB over a specific frequency band.
According to this aspect, the return loss characteristic of total reflection of the radio wave emitted from the antenna device 1 is 10 dB or less over a specific frequency band and has a gentle waveform, so that the return loss of the radio wave is good. Characteristics can be obtained.

<Eleventh embodiment>
The specific frequency band of this aspect is characterized by being 23 GHz to 29 GHz.
According to this aspect, since the specific frequency band is 23 GHz to 29 GHz, the frequency band characteristic of the pass attenuation characteristic in the band or the return loss characteristic in the band due to total reflection is specialized for this frequency band. The occurrence of disturbance can be suppressed, the blocking performance can be improved, and a further favorable EVM value can be obtained.

<12th aspect>
The antenna device 1 according to this aspect is characterized in that the antenna device 1 is disposed at a desired position with respect to a device under test, and receives radio waves emitted from the device under test.
According to this aspect, the antenna device 1 is disposed at a desired position with respect to the object to be measured, and generation of disturbance of the passing amplitude characteristic in the band and generation of disturbance of the return loss characteristic in the band due to total reflection. Being suppressed, it is possible to be in close contact with the object to be measured, to reliably receive radio waves emitted from the object to be measured, and to measure with a good EVM value. And by having directivity characteristics, it is possible to improve the blocking performance from the outside of the directivity direction, and it is also possible to obtain a good gain.

<13th aspect>
The antenna device 1 according to this aspect is characterized in that the antenna device 1 is disposed at a desired position with respect to an object to be measured and emits radio waves to the object to be measured.
According to this aspect, the antenna device 1 is disposed at a desired position with respect to the object to be measured, and the disturbance of the passing amplitude characteristic in the band and the disturbance of the return loss characteristic in the band due to total reflection are generated. Therefore, good EVM values can be obtained, and radio waves can be emitted closely to the object to be measured. And by having directivity characteristics, radio waves can be emitted only in the directivity direction.

<Fourteenth aspect>
The antenna system 300 of this aspect includes one pair of the antenna devices 1 according to any one of the first to tenth aspects, wherein each of the antenna devices 1 is a first antenna device 301 and a second antenna device 303, A radio wave radiated from the one antenna device 301 is received by the second antenna device 303 disposed opposite to the radiation direction of the first antenna device 301.
According to this aspect, the disturbance of the passing amplitude characteristic in the band and the disturbance of the reflection attenuation amount characteristic in the band due to total reflection are suppressed, and the radio wave emitted from the first antenna device 301 is A favorable EVM value can be obtained by receiving by the 2nd antenna apparatus 303 arrange | positioned facing the radiation direction of the 1st antenna apparatus 301. FIG.

<Fifteenth aspect>
The measurement system 340 of this aspect is characterized in that an object to be measured is disposed between the first antenna device 301 and the second antenna device 303 provided in the antenna system 300 described in the eleventh aspect.
According to this aspect, when the object to be measured is disposed between the first antenna device 301 and the second antenna device 303, the radio wave radiated from the object to be measured or the object to be measured is received. In addition, the degree of influence of the object to be measured can be measured.

DESCRIPTION OF SYMBOLS 1 ... Antenna apparatus, 1A ... Linear polarization coupler, 1B ... Circular polarization coupler, 1C ... Linear polarization high gain high isolation coupler, 1D ... Circular polarization high gain high isolation coupler, 5 ... Waveguide main body, 6 ... Coaxial waveguide conversion unit 8 internal space 10 first waveguide member 10a screw hole 11 concave portion 13 screw hole 20 waveguide member 22 connector mounting hole Reference Signs List 23 recess, 24 long hole 25 screw 30 blocking member 30a hole 31 screw 50 connector 51 connector body 52 connector socket portion 53 flange portion 54a connector Socket contact portion 54b Radiator 55 Center conductor support portion 56 Insulator 56a Inner end portion 60 Center conductor 60a Tip portion 100 Circularly polarized wave polarization portion 110 Conductor Wave space, 120 ... circular waveguide part, 1 DESCRIPTION OF SYMBOLS 1a ... Peripheral part, 130 ... Rectangular waveguide part, 131 ... Short side, 131a ... Peripheral part, 132 ... Long side, 132a ... Inner back part, 133 ... Inner wall, 140 ... Deflection board, 200 ... Horn part, 200A ... Linear polarization type horn, 200B: circular polarization type horn, 201a ... plate material

Claims (15)

1. An internal space formed of a hexahedron made of a conductive material and penetrating between the opposing first surface and the second surface, a third surface orthogonal to the first surface, and the second surface, and the interior A coaxial waveguide conversion part provided with a connector mounting hole for inserting a coaxial connector formed in communication with the space;
   A conductive closing member closing the opening on the second surface side of the inner space;
   A waveguide body provided with
   The connector mounting hole is mounted outward from the internal space, and the inner end portion is disposed axially penetrating the conductive connector main body which does not protrude into the internal space, and the central portion of the connector main body, It consists of a center conductor whose tip is projected from the inner end of the connector main body into the internal space by a predetermined length, and the tip of the center conductor which projects into the interior space, and the projection length of the tip is specified A radiation source for radiating radio waves from the central conductor in the internal space by adapting to a frequency band of
   An antenna device comprising:
2. A polarization unit connected to the non-closed surface side of the internal space of the coaxial waveguide conversion unit to convert radio waves radiated from the radiator into circular polarization, or the non-closed surface side of the inner space 2. The antenna device according to claim 1, further comprising: a horn unit connected to the antenna unit directly or via the polarization unit to block radio waves coming from the outside.
3. The antenna device according to claim 1, wherein the horn portion is linearly polarized by a truncated square pyramidal horn, or circularly polarized by a truncated conical horn.
4. The coaxial waveguide conversion unit is detachably attached to one surface of the first waveguide member provided with the concave portion serving as the internal space on one surface and one surface of the first waveguide member. And a second waveguide member that closes the one surface side of the recessed portion to form the internal space.
   A screw hole is formed on the one surface of the first waveguide member at a location where the recess is interposed therebetween,
   An elongated hole extending in parallel with the axial direction of the inner space is formed at a position aligned with each screw hole of the second waveguide member, and a screw is inserted into each screw hole through the each elongated hole. The antenna device according to claim 1, wherein the antenna device can be screwed.
5. The coaxial waveguide conversion unit
   The antenna device according to claim 3, wherein the position of the second waveguide member is finely adjustable so as to face one surface of the first waveguide member.
6. The axial length of the central connector of the coaxial connector protruding from the inner end is a length obtained by multiplying 1/4 of the wavelength of the specific frequency band by a predetermined reduction rate. The antenna device according to claim 1, characterized in that
7. The horn portion includes a first internal space having a vertical width of 4.3 mm and a horizontal width of 8.6 mm, and a second internal space having a vertical width of 15 mm to 16 mm and a horizontal width of 15 mm to 16 mm. The antenna device according to claim 1.
8. The material of the coaxial waveguide conversion part, the polarization part, and the horn part is copper, iron, aluminum, brass, metamaterial, metal plated plastic, or metal coated plastic or resin The antenna apparatus according to any one of claims 2 to 6, comprising:
9. The antenna device according to any one of claims 1 to 7, wherein a passing amplitude characteristic of a radio wave radiated from the self antenna device is 0 to 3 db over the specific frequency band.
10. 9. The reflection attenuation amount characteristic in total reflection of radio waves radiated from a self-antenna apparatus has a fluctuation range of 10 dB or less over the specific frequency band according to any one of claims 1 to 8. Antenna device.
11. The antenna device according to any one of claims 1 to 8, wherein the specific frequency band is 23 GHz to 29 GHz.
12. The antenna device according to any one of claims 1 to 8, wherein the antenna device is disposed at a desired position with respect to an object to be measured, and receives radio waves radiated from the object to be measured.
13. The antenna device according to any one of claims 1 to 8, which is disposed at a desired position with respect to an object to be measured, and emits radio waves to the object to be measured.
14. A pair of antenna apparatuses according to any one of claims 1 to 10,
    Each antenna device is a first antenna device and a second antenna device,
    An antenna system characterized in that radio waves radiated from the first antenna device are received by the second antenna device disposed to face the radiation direction of the first antenna device.
15. A measurement system, wherein an object to be measured is disposed between the first antenna device and the second antenna device provided in the antenna system according to claim 14.

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