WO2019086114A1 - Atténuation du brouillage entre systèmes de nombres par précodage ou suppression du brouillage - Google Patents

Atténuation du brouillage entre systèmes de nombres par précodage ou suppression du brouillage Download PDF

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Publication number
WO2019086114A1
WO2019086114A1 PCT/EP2017/078071 EP2017078071W WO2019086114A1 WO 2019086114 A1 WO2019086114 A1 WO 2019086114A1 EP 2017078071 W EP2017078071 W EP 2017078071W WO 2019086114 A1 WO2019086114 A1 WO 2019086114A1
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Prior art keywords
subcarrier signal
domain data
matrix
interference
frequency domain
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PCT/EP2017/078071
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English (en)
Inventor
Wen Xu
Mohamed Ibrahim
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Huawei Technologies Duesseldorf Gmbh
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Priority to CN201780096316.7A priority Critical patent/CN111279660B/zh
Priority to PCT/EP2017/078071 priority patent/WO2019086114A1/fr
Publication of WO2019086114A1 publication Critical patent/WO2019086114A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2626—Arrangements specific to the transmitter only
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J11/00—Orthogonal multiplex systems, e.g. using WALSH codes
    • H04J11/0023—Interference mitigation or co-ordination
    • H04J11/0026—Interference mitigation or co-ordination of multi-user interference
    • H04J11/003—Interference mitigation or co-ordination of multi-user interference at the transmitter
    • H04J11/0033—Interference mitigation or co-ordination of multi-user interference at the transmitter by pre-cancellation of known interference, e.g. using a matched filter, dirty paper coder or Thomlinson-Harashima precoder
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J11/00—Orthogonal multiplex systems, e.g. using WALSH codes
    • H04J11/0023—Interference mitigation or co-ordination
    • H04J11/0026—Interference mitigation or co-ordination of multi-user interference
    • H04J11/0036—Interference mitigation or co-ordination of multi-user interference at the receiver
    • H04J11/004—Interference mitigation or co-ordination of multi-user interference at the receiver using regenerative subtractive interference cancellation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2602—Signal structure
    • H04L27/26025—Numerology, i.e. varying one or more of symbol duration, subcarrier spacing, Fourier transform size, sampling rate or down-clocking
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only

Definitions

  • the present invention relates to the field of wireless communications, and more particularly to the field of 5 th generation (5G) wireless systems.
  • the 5G of mobile networks is on the horizon and a 5G wireless system will likely have different numerologies on the same carrier frequency.
  • the numerology may be defined as a set of multicarrier parameters such as subcarrier spacing, cyclic prefix (CP) and transmission time interval (TTI) amongst others.
  • Fig. 1 shows a 3 rd generation partnership project (3GPP) standardization proposal illustrating how different mobile network services of 5G, such as enhanced mobile broadband (eMBB), massive machine type communications (mMTC), ultra-reliable and low-latency communications (uRLLC) and broadcast, are packed close to each other in the frequency domain, each service having a different subcarrier spacing, CP and TTI as depicted in Fig. 1.
  • 3GPP 3 rd generation partnership project
  • a numerology depicted by a solid line as "Numer. 2”
  • Af2 based on a subcarrier spacing Af2
  • Afl dotted line as "Numer. 1”
  • eMBB interferes with mMTC
  • uRLLC interferes with both mMTC and broadcast.
  • large subcarriers have a high out-of-band (OOB) transmit power, which needs to be suppressed to avoid any inter-numerology interference.
  • OOB out-of-band
  • the first solution is related to a time domain filtering as found in the prior art documents: Z. Ankarali, B. Pekoz and H. Arslan, "Flexible Radio Access Beyond 5G: A Future Projection on Waveform, Numerology & Frame Design Principles" in IEEE Access, vol. PP, no. 99, pp.1-16, 2017, and A. A.
  • numerologies Moreover, another problem with this approach relates to the fact that both numerologies shall filter their respective signals, although only one numerology is causing the interference as aforementioned.
  • the second solution is related to a radio frequency (RF) filtering.
  • RF radio frequency
  • the analog transmit signal is filtered using a bandpass filter, which limits the OOB emissions.
  • this solution is expensive and does not guarantee full orthogonality amongst the subcarriers.
  • the third solution is related to the use of guard bands. This is the simplest solution, which inserts a guard band between the numerologies in order to increase the distance in frequency and decrease the OOB.
  • this use of guard bands leads to a large spectral loss and a slow fall of the OOB emissions of orthogonal frequency-division multiplexing (OFDM).
  • OFDM orthogonal frequency-division multiplexing
  • the invention relates to a multicarrier waveform-based system for mitigating inter-numerology interference, wherein at least one subcarrier signal of a first numerology designated as at least one interfering subcarrier signal interferes with at least another subcarrier signal of a second numerology designated as at least one interfered subcarrier signal, the first numerology being different from the second numerology.
  • the system is configured to comprise a transmitter and a receiver, and configured to match an interference from the at least one interfering subcarrier signal to the at least one interfered subcarrier signal by matching frequency domain data symbols of the at least one interfering subcarrier signal to frequency domain data symbols of the at least one interfered subcarrier signal through a respective interference coefficient matrix with respect to the frequency domain data symbols of the at least one interfering subcarrier signal.
  • the system is configured to obtain an orthogonal space of the interference coefficient matrix by performing a singular value decomposition (SVD) of the interference coefficient matrix into a factorization to a first matrix, a diagonal matrix and a second matrix, configured to project, at a precoder of the transmitter, each frequency domain data symbol of the at least one interfering subcarrier signal onto the orthogonal space of the interference coefficient matrix through a respective precoding matrix with respect to the frequency domain data symbols of the at least one interfering subcarrier signal, as to obtain a respective precoded frequency domain data symbol, the respective precoding matrix being derived from the second matrix, and configured to decode, at a decoder of the receiver, the respective precoded frequency domain data symbols using the first matrix.
  • SVD singular value decomposition
  • the system is configured to control, using an interference control parameter generated by a data rate controller, the level of the inter- numerology interference by controlling a number of singular values of the diagonal matrix starting from the lowest singular values to the highest singular values, and configured to transmit the interference control parameter from the precoder of the transmitter to the decoder of the receiver via a control channel.
  • the system is configured to demodulate, at a demodulator of the receiver, the at least one interfering subcarrier signal, as to obtain at least one demodulated interfering subcarrier signal, configured to obtain, at an
  • interference contribution module of the receiver the respective interference of each frequency domain data symbol of the at least one interfering subcarrier signal from the at least one
  • demodulated interfering subcarrier signal configured to subtract the respective interference of each frequency domain data symbol of the at least one interfering subcarrier signal from the at least one interfered subcarrier signal.
  • the invention relates to a method for mitigating inter-numerology interference in a multicarrier waveform-based system, wherein at least one subcarrier signal of a first numerology designated as at least one interfering subcarrier signal interferes with at least another subcarrier signal of a second numerology designated as at least one interfered subcarrier signal, the first numerology being different from the second numerology.
  • the method comprises the step of matching an interference from the at least one interfering subcarrier signal to the at least one interfered subcarrier signal by matching frequency domain data symbols of the at least one interfering subcarrier signal to frequency domain data symbols of the at least one interfered subcarrier signal through a respective interference coefficient matrix with respect to the frequency domain data symbols of the at least one interfering subcarrier signal.
  • the interference coefficient matrix is derived from a first transformation at a transmitter of the multicarrier waveform-based system and a second transformation at a receiver of the multicarrier waveform-based system.
  • the first transformation at the transmitter comprises the step of matching the frequency domain data symbols of the at least one interfering subcarrier signal to point inputs of an inverse fast Fourier transform (IFFT) matrix through a matching matrix, the step of converting the matched frequency domain data symbols of the at least one interfering subcarrier signal to time domain data symbols of the at least one interfering subcarrier signal through the IFFT matrix, and the step of attaching a respective first cyclic prefix to each time domain data symbol of the at least one interfering subcarrier signal through a respective first cyclic prefix insertion matrix, as to obtain respective input time domain data symbols of the at least one interfering subcarrier signal.
  • IFFT inverse fast Fourier transform
  • the first transformation at the transmitter comprises the step of converting the frequency domain data symbols of the at least one interfered subcarrier signal to time domain data symbols of the at least one interfered subcarrier signal through the IFFT matrix, and the step of attaching a respective second cyclic prefix to each time domain data symbol of the at least one interfered subcarrier signal through a respective second cyclic prefix insertion matrix, as to obtain respective input time domain data symbols of the at least one interfered subcarrier signal.
  • the second transformation at the receiver comprises the step of discarding the respective second cyclic prefix attached to each input time domain data symbol of the at least one interfered subcarrier signal from each input time domain data symbols of the at least one interfering subcarrier signal through a respective cyclic prefix removal matrix, as to obtain respective CPb-discarded time domain data symbols of the at least one interfering subcarrier signal, the step of converting the CPb-discarded time domain data symbols of the at least one interfering subcarrier signal to frequency domain data symbols of the at least one interfering subcarrier signal through a fast Fourier transform (FFT) matrix, as to obtain respective CPb-discarded frequency domain data symbols of the at least one interfering subcarrier signal, and the step of selecting the frequency domain data symbols of the at least one interfered subcarrier signal through a selection matrix, as to obtain a respective interference contribution with respect to the frequency domain data symbols of the at least one interfering subcarrier signal.
  • FFT fast Fourier transform
  • the second transformation at the receiver comprises the step of discarding the respective second cyclic prefix attached to each input time domain data symbol of the at least one interfered subcarrier signal through a respective cyclic prefix removal matrix, as to obtain respective CPb-discarded time domain data symbols of the at least one interfered subcarrier signal, and the step of converting the CPb-discarded time domain data symbols of the at least one interfered subcarrier signal to frequency domain data symbols of the at least one interfered subcarrier signal through the fast Fourier transform (FFT) matrix as to obtain respective CPb-discarded frequency domain data symbols of the at least one interfered subcarrier signal.
  • FFT fast Fourier transform
  • the method comprises the step of obtaining an orthogonal space of the interference coefficient matrix by performing a singular value decomposition (SVD) of the interference coefficient matrix into a factorization to a first matrix, a diagonal matrix and a second matrix, the step of projecting, at a precoder of the transmitter, each frequency domain data symbol of the at least one interfering subcarrier signal onto the orthogonal space of the interference coefficient matrix through a respective precoding matrix with respect to the frequency domain data symbols of the at least one interfering subcarrier signal, as to obtain a respective precoded frequency domain data symbol, the respective precoding matrix being derived from the second matrix, and the step of decoding, at a decoder of the receiver, the respective precoded frequency domain data symbols using the first matrix.
  • SVD singular value decomposition
  • the method comprises the step of controlling, using an interference control parameter generated by a data rate controller, the level of the inter-numerology interference by controlling a number of singular values of the diagonal matrix starting from the lowest singular values to the highest singular values, and the step of transmitting the interference control parameter from the precoder of the transmitter to the decoder of the receiver via a control channel.
  • the method comprises the step of demodulating, at a demodulator of the receiver, the at least one interfering subcarrier signal, as to obtain at least one demodulated interfering subcarrier signal, the step of obtaining, at an interference contribution module of the receiver, the respective interference of each frequency domain data symbol of the at least one interfering subcarrier signal from the at least one demodulated interfering subcarrier signal, and the step of subtracting the respective interference of each frequency domain data symbol of the at least one interfering subcarrier signal from the at least one interfered subcarrier signal.
  • the invention relates to a computer program comprising a program code for performing the method according to the second aspect and/or any one of the
  • the method can be performed in an automatic and repeatable manner.
  • the computer program can be performed by the above apparatuses.
  • all the above apparatuses may be implemented based on a discrete hardware circuitry with discrete hardware components, integrated chips or arrangements of chip modules, or based on a signal processing device or chip controlled by a software routine or program stored in a memory, written on a computer-readable medium or downloaded from a network such as the Internet.
  • Fig. 1 shows a schematic view of packing different services with different numerologies according to a 3GPP standard proposal
  • Fig. 3 shows an exemplary transmitter windowing taken from: A. A. Zaidi, . Baldemair, H.
  • Fig. 4 shows a schematic view of an interference coefficient matrix (C
  • Fig. 5 shows a sequential arrangement of multiple matrices from which the interference
  • Fig. 6 shows a time domain superposition of two numerologies denoted by numerology a and numerology b wherein two frequency domain data symbols of numerology a are superimposed in terms of duration with one frequency domain data symbol of numerology b, according to an embodiment of the present invention
  • Fig. 7 shows a schematic multicarrier waveform-based system 100 using precoding and decoding according to a first embodiment of the present invention
  • Fig. 8 shows a schematic multicarrier waveform-based system 200 using successive interference cancellation (SIC) decoding according to a second embodiment of the present invention
  • Fig. 9 shows a schematic multicarrier waveform-based system 300 using precoding and SIC decoding according to a third embodiment of the present invention
  • Fig. 10 shows an interference power (dB) due to OOB emissions versus a subcarrier index for a transmit signal of different numerologies in the case where it is precoded according the present invention with different data rate reductions (PC in %), and in the case where it uses different guard bands (GB in kHz) that are inserted between the numerologies; and
  • Fig. 11 shows an average interference power (dB) due to OOB emissions versus a data rate
  • the present invention is based on an analysis of the interference caused by a set of subcarrier signals on another set of subcarriers with a different numerology.
  • the matrix has p columns corresponding to the interfering subcarrier signals causing interference, and I rows corresponding to the interfered subcarrier signals suffering from interference.
  • the interference coefficient matrix C lxp is composed of (Ixp) matrix elements, and the matrix element Ci,j will be associated to the interference caused by the k-th subcarrier on the i-th subcarrier.
  • the interference coefficient matrix C lxp may be derived from a sequential arrangement of multiple matrices, denoted by M, W and P CPa at a transmitter side and Pcpb ⁇ and S at a receiver side as depicted in Fig. 5, and may be computed as follows:
  • W is an inverse fast Fourier transform (I FFT) matrix
  • P CPa is a cyclic prefix insertion matrix for the numerology a
  • P CPb is a cyclic prefix removal matrix for the numerology b
  • W is a fast Fourier transform (FFT) matrix
  • S is a selection matrix.
  • the interference coefficients of the interference coefficient matrix C lxp may be directly computed as a function of static parameters such as subcarrier spacing and cyclic prefix (CP) amongst others, without the need of transmitting any interfering signal via the transmitter and the receiver.
  • the interference coefficients may indeed be identified for each numerology pair using, for example, a look-up table.
  • the matching matrix M distributes the p data symbols onto the N IFFT point inputs and the I subcarriers belonging to the other numerology are padded with zeros in the matching matrix M.
  • the data symbols are interleaved with zeros since the subcarrier spacing is twice the base su bcarrier spacing of the IFFT kernel.
  • the cyclic prefix removal matrix P CPb removes a CP of length 2NCP
  • the cyclic prefix insertion matrix P CPa attaches a CP of length NCP, selects N/2 time domain samples and pads the rest into zero.
  • the selection matrix S selects the subcarriers which belong to the numerology b, i.e., the numero that suffers from the interference.
  • Fig. 6 showing a time domain superposition of two numerologies (denoted by numerology a and numerology b), two frequency domain data symbols (depicted as X3, and X ) of numerology a are superimposed in terms of duration with one frequency domain data symbol (depicted as X b ) of numerology b, the larger subcarrier spacing being half the symbol duration of the smaller subcarrier spacing due to the reciprocity of time and frequency.
  • the shorter duration symbols i.e., X3, and X
  • the longer duration symbol i.e., X b
  • Ci M . W . p i pa - PcPb - W . S (2)
  • ⁇ 3 is the cyclic prefix insertion matrix for the first frequency domain data symbol of the interfering subcarrier signal of numerology a through which one CP of the numerology a is inserted
  • P ⁇ ? PA is the cyclic prefix insertion matrix for the second frequency domain data symbol of the interfering subcarrier signal of numerology a through which one CP of the numerology a is inserted
  • P CPB is the cyclic prefix removal matrix for the numerology b through which a CP of the numerology b is removed, the CP of the numerology a having a length NCP and the CP of the numerology b having a length IShcp
  • the interference coefficient matrix C lxp is a deterministic matrix which depends solely on the numerologies (e.g., numerology a and numerology b) but not on the communication channel.
  • a respective interference coefficient matrix C lxp (i.e., Ci and C 2 ), with respect to the frequency domain data symbols (i.e., X3, and X ) of the interfering subcarrier signal, allows to match the frequency domain data symbols (i.e., X3, and X ) of the interfering subcarrier signal to the frequency domain data symbols (i.e., X b ) of the interfered subcarrier signal.
  • the interference of numerology a (i.e., the interference of the higher subcarrier numerology) can be mitigated by precoding the interfering data symbols in a first embodiment or by deducting the derived interference at the receiver in a second embodiment or by using in a third embodiment a combination of the first and second embodiments.
  • Fig. 7 shows a schematic multicarrier waveform-based system 100 using precoding and decoding according to said first embodiment of the present invention.
  • the multicarrier waveform-based system 100 comprises a transmitter and a receiver communicating to each other via a transmit channel, and a data rate controller 190.
  • the transmitter (TX) comprises a precoder 110 applicable to the numerology a (i.e., the numerology causing the interference), a matching matrix 120 (also denoted as M matrix) applicable to the numerology a, an IFFT matrix 130 (also denoted as W matrix) applicable to the numerologies a and b, a cyclic prefix insertion matrix 140-A (also denoted as P CPa matrix) applicable to the numerology a and a cyclic prefix insertion matrix 140-B (also denoted as P CPb matrix) applicable to the numerology b.
  • the receiver ( X) comprises a cyclic prefix removal matrix 150 (also denoted as P CPb matrix) applicable to the numerologies a and b, a fast Fourier transform (FFT) matrix 160 (also denoted as W matrix) applicable to the numerologies a and b, a selection matrix (also denoted as S matrix) 170 applicable to the numerology a, and a decoder 180 applicable to the numerology a.
  • FFT fast Fourier transform
  • the precoder 110 receives the first frequency domain data symbol X3, and the second frequency domain data symbol X of the interfering subcarrier signal of the numerology a.
  • a respective singular value decomposition (SVDi, SVD2) of each interference coefficient matrix (Ci, C2) into a factorization (U. ⁇ .V) to a first matrix (U matrix), a diagonal matrix ( ⁇ matrix) and a second matrix (V matrix) is performed at the precoder 110 in order to obtain a respective orthogonal space of each interference coefficient matrix (Ci, C2).
  • the precoder 110 at the transmitter (TX) may extract the column vectors of the V matrix from the SVD decomposition, whereas the decoder 180 at the receiver ( X) may take its corresponding row vectors of the U matrix.
  • the column vectors are selected according to their singular values from lowest to highest in order to control the interference power. The more precoding vectors are selected, the higher is the data rate, but the interference power increases.
  • the precoder 110 projects the first and second frequency domain data symbols (X , X ) of the interfering subcarrier signal onto their respective orthogonal space through a respective precoding matrix (Ji, J2) as to obtain a respective precoded frequency domain data symbol (Ji.X g , J2.XI).
  • the precoded frequency domain data symbols (Ji.X g , J2.XI ) are guaranteed to not interfere with the frequency domain data symbol (X b ) of the interfered subcarrier signal of the other numerology (i.e., the numerology b).
  • the respective precoding matrices (Ji, J2) are derived from the respective V matrix and may be defined as follows:
  • ⁇ 3 is the cyclic prefix insertion matrix 140-A for the first time slot frequency domain data symbol of the interfering subcarrier signal of numerology a through which one CP of the numerology a is inserted
  • P ⁇ ? Pa is the cyclic prefix insertion matrix 140-B for the second time slot frequency domain data symbol of the interfering subcarrier signal of numerology a through which one CP of the numerology a is inserted
  • P CPb is the cyclic prefix removal matrix 150 applicable to the numerology b through which a CP of the numerology b is removed, the CP of the numerology a having a length NCP and the CP of the numerology b having a length IShcp
  • the data rate controller 190 is configured to generate an interference control parameter ( ⁇ ), which controls the level (or amount) of the inter-numerology interference by controlling a number of singular values of the ⁇ matrix starting from the lowest singular values to the highest singular values and configured to transmit the interference control parameter ( ⁇ ) from the precoder
  • the interference control parameter ( ⁇ ) controls the number of non-orthogonal column vectors extracted by the precoder 110, and the more non-orthogonal column vectors are selected, the higher data rate can be achieved regarding the numerology a (i.e., the numerology causing the
  • the level (or amount) of the inter-numerology interference may be controlled, for example, depending on the channel condition, the quality of service (QoS), the signal-to-noise ratio (SNR) and/or the reliability requirement amongst others.
  • QoS quality of service
  • SNR signal-to-noise ratio
  • the precoded frequency domain data symbols (Ji.X a , J2.XI) are transmitted, through the matching matrix 120 (i.e., the M matrix), towards the IFFT matrix 130 (i.e., the W matrix) in order to be converted from the frequency domain to the time domain, and a respective cyclic prefix (Pc Pa , Pcp a ) insertion applicable to the numerology a is then applied to each of the resulting time domain data symbols (W.M. Ji.X a , W.M. J2.XI) of the interfering subcarrier signal using the insertion matrix 140-A.
  • the frequency domain data symbol (X b ) of the interfered subcarrier signal of the numerology b is directly transmitted towards the IFFT matrix 130 (i.e., the W matrix) in order to be converted from the frequency domain to the time domain, and a cyclic prefix (Pcpb) insertion applicable to the numerology b is then applied to the resulting time domain data symbol (W.X b ) of the interfered subcarrier signal, using the insertion matrix 140-B.
  • the IFFT matrix 130 i.e., the W matrix
  • Pcpb cyclic prefix
  • the time domain data symbols (Pc Pa .W.M. Ji.X a , Pcp a .W.M. J2.XI) of the interfering subcarrier signal and the time domain data symbol (P CPb .W.X b ) of the interfered subcarrier signal are then multiplexed into a time domain transmit signal (X T ) given by the following relationship:
  • X PcPb-W.X ⁇ -l- Pcp a .W.M. Ji.X3, + ⁇ ? ⁇ 3 . ⁇ . ⁇ . J 2 .X
  • the time domain transmit signal (X T ) is transmitted towards the receiver ( X) over the transmit channel, and a cyclic prefix (Pcpb) removal is then applied to each member of the time domain transmit signal (X T ), namely to each time domain data symbol (Pc Pa .W.M. Ji.X a , ⁇ ? ⁇ 3 . ⁇ /. ⁇ . J2.XI) of the interfering subcarrier signal and to the time domain data symbol (P CPb .W.X b ) of the interfered subcarrier signal, using the cyclic prefix removal matrix 150.
  • the resulting time domain data symbols ( ⁇ . ⁇ . ⁇ /.3 ⁇ 4, P CPb . Pc Pa .W.M. Ji.X a , P CPb . P,? Pa .W.Iv1. J2.X ) are directly transmitted towards the FFT matrix 160 (i.e., the W matrix) in order to be converted from the time domain to the frequency domain.
  • the resulting frequency domain data symbols (W.P CPb . Pc Pa .W.M. Ji.Xi,, W.P CPb . P ⁇ Pa .W.M. i 2 .Xl) of the interfering subcarrier signal are then transmitted towards the selection matrix 170, as to obtain the frequency domain data symbols S. W.P CPb . Pc Pa .W.M. Ji.X* and S.W.P CPb .
  • Fig. 8 shows a schematic multicarrier waveform-based system 200 using successive interference cancellation (SIC) decoding according to a second embodiment of the present invention.
  • SIC successive interference cancellation
  • the multicarrier waveform-based system 200 basically differs from the multicarrier waveform-based system 100 in that there is no precoding at the transmitter (TX), so that the precoder 110 of Fig. 7 is not provided at the transmitter of Fig. 8, and in that there is no decoder 180 at the receiver (RX).
  • the receiver (RX) of the multicarrier waveform-based system 200 comprises a first demodulator 210, an interference contribution module 220 and a second demodulator 230.
  • the first demodulator 210 is configured to demodulate the interfering subcarrier signal as to obtain a demodulated interfering subcarrier signal.
  • the second demodulator 230 is configured to provide the frequency domain data symbol (i.e., X b ) of the interfered subcarrier signal.
  • the interference contribution may be fully eliminated when the first demodulator 210 demodulates without error the interfering subcarrier signal. However, if an error occurs, this error may propagate to the interfered subcarrier signal of the other numerology b.
  • this second embodiment may advantageously apply to scenarios with high SN , for which the erroneous demodulation probability is low.
  • Fig. 9 shows a schematic multicarrier waveform-based system 300 using precoding and SIC decoding according to a third embodiment of the present invention.
  • the multicarrier waveform-based system 300 is a hybrid multicarrier waveform-based system which comprises a combination of all the constituent elements of the multicarrier waveform-based system 100 and the multicarrier waveform-based system 200.
  • the precoder 110 may be a precoder with a considerable interference as the receiver (RX) would enhance its estimate by subtracting the residual interference from the interfered subcarrier signal.
  • this third embodiment advantageously allows to achieve high data rates with a high reliability since the error propagation can be minimized.
  • Fig. 10 shows an interference power (d B) due to OOB emissions versus a subcarrier index for a transmit signal of two different numerologies in the case where it is precoded according the present invention with different data rate reductions (PC in %), and in the case where it is guard banded with different guard bands (GB in kHz) that are inserted between the two numerologies.
  • the guard bands are matched to the data rate reduction of the precoded transmit signal.
  • the signal power of the guard banded signal is boosted since the transmitter focuses its power only on the inband subcarriers.
  • Fig. 10 shows the interference leakage of the interfering numerology on the subcarrier index of the other numerology.
  • Fig. 11 shows an average interference power (dB) over all the subcarriers versus the data rate reduction (%) for a transmit signal of two different numerologies in the case where it is precoded according the present invention and in the case where it is guard banded with different guard bands that are inserted between the two numerologies.
  • the number of subcarriers has been fixed at 256 subcarriers with an allocation of 128 subcarriers (i.e., a subcarrier allocation factor equal to 50%) to each numerology.
  • guard bands offer a slow reduction in the average interference power, whereas the average interference power for the precoded transmit signal drops nearly linearly with increasing the data rate reduction.
  • the price paid to suppress the inter-numerology interference is a slight reduction in data rate;
  • the precoder design has a low complexity due to the sparseness of the interference coefficient matrix. Indeed, although the precoding procedure changes from one frequency domain data symbol to the other, the precoder itself relies solely on system design parameters such as the subcarrier spacing and the CP amongst others, and not on channel parameters;
  • the present invention relates to a multicarrier waveform-based system for mitigating inter-numerology interference, wherein at least one subcarrier signal of a first numerology designated as at least one interfering subcarrier signal interferes with at least another subcarrier signal of a second numerology designated as at least one interfered subcarrier signal, the first numerology being different from the second numerology.
  • the invention is mainly based on precoding the data assigned to a certain subcarrier dedicated to a specific function.
  • Subcarriers are usually classified into different numerologies according to numerology parameters such as subcarrier spacing and cyclic prefix (CP) amongst others. Thereby, each subcarrier having a certain numerology comprises different numerology parameters.
  • a subcarrier of a certain numerology may interfere with other subcarriers of other numerologies having, for example, narrower subcarrier spacings.
  • the suggested precoding is based on the above-mentioned numerology parameters in order to eliminate the inter-numerology interference.
  • the invention is mainly based on designing a precoder at the transmitter with specific parameters which are related to the coexisting two numerologies.
  • the parameters of the precoder are shared with a decoder of the receiver through a control channel so that the receiver can decode the received message.
  • a computer program may be stored/distributed on a suitable medium, such as an optical storage medium or a solid-state medium supplied together with or as part of other hardware, but may also be distributed in other forms, such as via the Internet or other wired or wireless telecommunication systems.
  • a suitable medium such as an optical storage medium or a solid-state medium supplied together with or as part of other hardware, but may also be distributed in other forms, such as via the Internet or other wired or wireless telecommunication systems.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • Mathematical Physics (AREA)
  • Mobile Radio Communication Systems (AREA)
  • Noise Elimination (AREA)

Abstract

La présente invention concerne un système basé sur une forme d'onde multiporteuse pour atténuer le brouillage entre des systèmes de nombres, au moins un signal de sous-porteuse d'un premier système de nombres, désigné en tant qu'au moins un signal de sous-porteuse brouilleur, parasitant au moins un autre signal de sous-porteuse d'un second système de nombres désigné en tant qu'au moins un signal de sous-porteuse brouillé, le premier système de nombres étant différent du second système de nombres. Le système est configuré pour comprendre un émetteur et un récepteur communiquant par l'intermédiaire d'un canal de communication. Le système est également configuré pour mettre en correspondance le brouillage provenant du ou des signaux de sous-porteuse brouilleur(s) avec au moins un signal de sous-porteuse brouillé, par la mise en correspondance de symboles de données du domaine fréquentiel du ou des signaux de sous-porteuse brouilleur(s) avec des symboles de données du domaine fréquentiel du ou des signaux de sous-porteuse brouillé(s), par l'intermédiaire d'une matrice de coefficients de brouillage respectifs, par rapport aux symboles de données du domaine fréquentiel du ou des signaux de sous-porteuse brouilleur(s).
PCT/EP2017/078071 2017-11-02 2017-11-02 Atténuation du brouillage entre systèmes de nombres par précodage ou suppression du brouillage WO2019086114A1 (fr)

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CN201780096316.7A CN111279660B (zh) 2017-11-02 2017-11-02 用于减轻参数集间干扰的方法
PCT/EP2017/078071 WO2019086114A1 (fr) 2017-11-02 2017-11-02 Atténuation du brouillage entre systèmes de nombres par précodage ou suppression du brouillage

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CN111698185A (zh) * 2020-06-16 2020-09-22 Oppo广东移动通信有限公司 载波干扰消除方法、装置、电子设备及存储介质
WO2023129035A3 (fr) * 2021-12-30 2023-08-17 Tobb Ekonomi Ve Teknoloji Universitesi Bloqueur d'interférence inter-numérologie dans des systèmes à numérologie multiple
WO2024019341A1 (fr) * 2022-07-19 2024-01-25 삼성전자주식회사 Dispositif de réception comprenant un coupleur linéaire dans un système mimo pour prendre en charge de multiples numérologies, et procédé de fonctionnement de celui-ci

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