WO2019039650A1 - Mélangeur de doherty - Google Patents

Mélangeur de doherty Download PDF

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Publication number
WO2019039650A1
WO2019039650A1 PCT/KR2017/011732 KR2017011732W WO2019039650A1 WO 2019039650 A1 WO2019039650 A1 WO 2019039650A1 KR 2017011732 W KR2017011732 W KR 2017011732W WO 2019039650 A1 WO2019039650 A1 WO 2019039650A1
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Prior art keywords
doherty
pass
type
amplifier
resonant circuit
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PCT/KR2017/011732
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English (en)
Korean (ko)
Inventor
안달
최관순
임종식
한상민
김성민
장유나
이대웅
오준석
구서
강태훈
김지원
장익수
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순천향대학교 산학협력단
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Application filed by 순천향대학교 산학협력단 filed Critical 순천향대학교 산학협력단
Priority to US16/641,214 priority Critical patent/US11201592B2/en
Priority to CN201780094207.1A priority patent/CN111133676B/zh
Publication of WO2019039650A1 publication Critical patent/WO2019039650A1/fr

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/24—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages
    • H03F3/245—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages with semiconductor devices only
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0288—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers using a main and one or several auxiliary peaking amplifiers whereby the load is connected to the main amplifier using an impedance inverter, e.g. Doherty amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H03F1/3241—Modifications of amplifiers to reduce non-linear distortion using predistortion circuits
    • H03F1/3282—Acting on the phase and the amplitude of the input signal
    • H03F1/3288—Acting on the phase and the amplitude of the input signal to compensate phase shift as a function of the amplitude
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/42—Modifications of amplifiers to extend the bandwidth
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/56—Modifications of input or output impedances, not otherwise provided for
    • H03F1/565—Modifications of input or output impedances, not otherwise provided for using inductive elements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/189—High frequency amplifiers, e.g. radio frequency amplifiers
    • H03F3/19—High frequency amplifiers, e.g. radio frequency amplifiers with semiconductor devices only
    • H03F3/195—High frequency amplifiers, e.g. radio frequency amplifiers with semiconductor devices only in integrated circuits
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
    • H03F3/211—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only using a combination of several amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/60—Amplifiers in which coupling networks have distributed constants, e.g. with waveguide resonators
    • H03F3/602—Combinations of several amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/451—Indexing scheme relating to amplifiers the amplifier being a radio frequency amplifier
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/20—Indexing scheme relating to power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F2203/21—Indexing scheme relating to power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
    • H03F2203/211—Indexing scheme relating to power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only using a combination of several amplifiers
    • H03F2203/21106—An input signal being distributed in parallel over the inputs of a plurality of power amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/45—Indexing scheme relating to differential amplifiers
    • H03F2203/45501—Indexing scheme relating to differential amplifiers the CSC comprising a L-C parallel resonance circuit
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/45—Indexing scheme relating to differential amplifiers
    • H03F2203/45502—Indexing scheme relating to differential amplifiers the CSC comprising a L-C series resonance circuit

Definitions

  • the present invention relates to a Doherty coupler, and more particularly, to a Doherty coupler capable of improving the bandwidth of the Doherty power amplifier by adding a transmission line or a resonant circuit to an output end of at least one amplifier constituting a Doherty power amplifier will be.
  • Modern mobile communication systems use a digital modulation communication scheme that can more efficiently use a limited frequency band.
  • the digitally modulated signal is amplified to a desired transmission power using a radio frequency (RF) power amplifier.
  • RF radio frequency
  • the power amplifier In order to transmit the signal without distortion, the power amplifier must have a high linear characteristic.
  • Doherty power amplifiers have been proposed as a way to conserve power or increase efficiency, and have advantages of easy implementation and high power efficiency, but they have a disadvantage of having a narrow bandwidth. Various studies are underway to improve the narrow bandwidth of Doherty power amplifiers.
  • the Doherty power amplifier 100 includes a coupler 110, a carrier amplifier 120, a peaking amplifier 130, and a Doherty combiner 140.
  • the Doherty combiner 140 includes a 90-degree phase shift section and a matching section.
  • a Doherty power amplifier 100 In combination, and in combination with the Doherty coupler 140 in the first branch, output danin p of the peaking amplifier 130, the output danin p of the carrier amplifier 120 at two points and the Doherty coupler 140, a Doherty power amplifier 100 The power is coupled and output at point p ' 3, which is the output stage of the inverter.
  • the present invention is directed to solving the above-mentioned problems and other problems.
  • Another object of the present invention is to provide a Doherty coupler capable of improving the phase bandwidth of a Doherty power amplifier by adding one or more transmission lines to an output terminal of at least one amplifier.
  • Yet another object is to provide a Doherty combiner capable of adding one or more resonant circuits to the output stage of at least one amplifier to improve the phase bandwidth of the Doherty power amplifier.
  • a semiconductor device comprising: a phase shifter, connected to one end of a carrier amplifier, for changing a phase of an RF signal output from the carrier amplifier; A matching unit connected to an output terminal of the Doherty power amplifier for impedance matching the output of the Doherty power amplifier; And a bandwidth enhancer coupled to one end of the peaking amplifier to vary at least one of a phase bandwidth and a size bandwidth of the Doherty power amplifier.
  • the bandwidth enhancement unit includes a 180-degree phase shift line.
  • the bandwidth improving unit includes a 180 ° phase shift line connected to one end of the peaking amplifier, a first inductor connected to the 180 ° phase shift line, And a parallel resonant circuit connected in parallel.
  • the bandwidth improving unit includes a 180 ° phase shift line connected to one end of the peaking amplifier, and a short stub connected to the 180 ° phase shift line. .
  • the bandwidth improving section includes a serial resonant circuit in which an inductor L and a capacitor C are connected in series.
  • the bandwidth improving unit includes a series resonant circuit in which a first inductor and a first capacitor are connected in series, and a parallel resonant circuit in which a second inductor and a second capacitor are connected in parallel.
  • the phase shifter includes a first transmission line for coupling the output of the carrier amplifier and the peaking amplifier
  • the matching unit includes a second transmission line for impedance matching the output of the Doherty power amplifier .
  • the phase shifter includes first lumped elements that are equivalent to a transmission line for coupling the output of the carrier amplifier and the output of the picking amplifier, And a second lumped element equivalent to a transmission line for impedance matching the output of the amplifier.
  • the first lumped element is configured by any one of a Low-Pass ⁇ type LC circuit, a High-Pass ⁇ type LC circuit, a Low-Pass T type LC circuit, and a High-Pass T type LC circuit, , A low-pass ⁇ type LC circuit, a high-pass ⁇ type LC circuit, a low-pass T type LC circuit, and a high-pass T type LC circuit.
  • the second lumped element may have an L / C value different from that of the first lumped element.
  • the phase shifter includes a first lumped element and a first resonance circuit, the first lumped element being equivalent to a transmission line for coupling the output of the carrier amplifier and the peaking amplifier, and the matching unit includes an output of the Doherty power amplifier And a second concentration element and a second resonance circuit, which are equivalent to a transmission line for impedance matching.
  • the first or second resonance circuit is constituted by a parallel resonance circuit, and when the first or second lumped element is a T type structure,
  • the second resonant circuit may be composed of a series resonant circuit. Further, the second resonance circuit may have the same L / C value as the first resonance circuit.
  • the bandwidth improving unit includes a series resonance circuit in which an inductor and a capacitor are connected in series, and a short stub connected to the series resonance circuit.
  • the bandwidth improving section includes a distribution element circuit which is equivalent to the concentration element circuit corresponding to the series resonance circuit.
  • the distribution element circuit may include two transmission lines and capacitors evenly substituted through Kuroda's Identities.
  • the phase bandwidth and / or the magnitude bandwidth of the Doherty power amplifier can be improved by adding a transmission line to the output stage of the peaking amplifier.
  • the phase bandwidth and / or the size bandwidth of the Doherty power amplifier can be improved by adding one or more resonant circuits to the output stage of the picking amplifier.
  • the effect that the Doherty coupler according to the embodiments of the present invention can achieve is not limited to those described above, and other effects not mentioned can be obtained from the following description, It will be clear to those who have it.
  • 1 is a diagram showing a configuration of a Doherty power amplifier according to the related art
  • FIG. 2 is a diagram showing a configuration of a Doherty power amplifier 200 related to the present invention
  • FIG. 3 is a diagram illustrating a configuration of a Doherty power amplifier according to a first embodiment of the present invention
  • FIG. 4 shows an equivalent circuit for Doherty combiner 340 of Fig. 3; Fig.
  • Figure 5 compares the performance of a conventional Doherty combiner and a Doherty combiner of Figure 3;
  • 6A and 6B are diagrams illustrating a configuration of a Doherty power amplifier according to a second embodiment of the present invention.
  • FIG. 7A is a diagram showing a result of simulating the magnitude characteristic of the Doherty coupler of FIG. 6B; FIG.
  • FIG. 7B is a diagram showing a result of simulating the phase difference characteristic of the Doherty coupler of FIG. 6B;
  • FIG. 8 is a diagram illustrating a configuration of a Doherty power amplifier according to a third embodiment of the present invention.
  • FIG. 9 shows an equivalent circuit for Doherty combiner 840 of FIG. 8; FIG.
  • FIG. 11 is a diagram illustrating a configuration of a Doherty power amplifier according to a fourth embodiment of the present invention.
  • 13 is a diagram referred to explain Doherty couplers of various types according to the combination of the first lumped element and the second lumped element;
  • FIGS. 14 through 29 are diagrams referred to describe Doherty couplers having sixteen forms
  • 30A and 30B are diagrams showing a configuration of a Doherty power amplifier according to a fifth embodiment of the present invention.
  • FIG. 31A is a diagram showing a simulation result of the magnitude characteristic of the Doherty coupler of FIG. 30A; FIG.
  • FIG. 31B is a diagram showing a result of simulating the phase difference characteristic of the Doherty coupler of FIG. 30A; FIG.
  • FIG. 32 is a diagram showing a configuration of a Doherty power amplifier according to a sixth embodiment of the present invention.
  • 34 is a diagram referred to describe a Doherty coupler according to various combinations of a first lumped element and a second lumped element;
  • 35 is a diagram illustrating a configuration of a Doherty power amplifier according to a seventh embodiment of the present invention.
  • 36 is a diagram referred to explain the four types of lumped element and resonant circuit provided in the Doherty power amplifier of FIG. 35;
  • 37 is a diagram referred to explain a Doherty coupler according to various combinations of a first lumped element and a first resonant circuit and a second lumped element and a second resonant circuit;
  • 38 is a diagram showing an example of a Doherty coupler having a structure in which first and second resonance circuits are added to first and second lumped elements;
  • FIG. 39A is a diagram showing a simulation result of the magnitude characteristic of the Doherty coupler of FIG. 38; FIG.
  • FIG. 39B is a diagram showing a result of simulating the phase difference characteristic of the Doherty coupler of FIG. 38; FIG.
  • FIG. 40 is a diagram illustrating a configuration of a Doherty power amplifier according to an eighth embodiment of the present invention.
  • FIG. 41A is a diagram showing a configuration of a Doherty coupler obtained by converting the lumped element shown in the Doherty coupler of Fig. 40 into a dispersive element; Fig.
  • 41B is a diagram referred to illustrate a method of implementing an equivalent circuit using a Gurode formula
  • the present invention proposes a Doherty coupler capable of improving the bandwidth of the Doherty power amplifier by adding one or more transmission lines or a resonant circuit to the output terminal of at least one amplifier constituting the Doherty power amplifier.
  • FIG. 2 is a diagram showing the configuration of a Doherty power amplifier 200 related to the present invention.
  • the Doherty power amplifier 200 may include a coupler 210, a carrier amplifier 220, a peaking amplifier 230, and a Doherty combiner 240.
  • the coupler 210 couples the RF signal received from the communication modem (not shown) and outputs it to the carrier amplifier 220 and the peaking amplifier 230.
  • the carrier amplifier 220 and the peaking amplifier 230 amplify the RF signal received from the coupler 210 and output the amplified RF signal to the Doherty combiner 240.
  • the carrier amplifier 220 operates at a low output power and the two amplifiers 220 and 230 operate at a high output power.
  • the transistors of the carrier amplifier 220 may be biased to the class AB and the transistors of the peaking amplifier 230 may be biased to the class C, but the present invention is not limited thereto.
  • the Doherty combiner 240 may combine a first RF signal output from the carrier amplifier 220 and a second RF signal output from the peaking amplifier 230 and output the resultant signal in an antenna short direction.
  • the Doherty combiner 240 includes a phase shifter 241 connected to the output stage P 1 of the carrier amplifier 220, a matching unit 242 connected to the output stage P 3 of the Doherty power amplifier 200, And a bandwidth improving unit 243 connected to the output end P 2 of the peaking amplifier 230.
  • the phase shifter 241, the matching unit 242, and the bandwidth improving unit 243 may meet at a point P 2 ' .
  • the phase shifter 241 may perform a phase shift function for coupling the outputs of the carrier amplifier 220 and the peaking amplifier 230.
  • the phase shifter 241 may include a transmission line or lumped elements, but is not limited thereto.
  • the matching unit 242 may perform impedance matching on the output of the Doherty power amplifier 200. Likewise, the matching unit 242 may be composed of transmission lines or lumped elements, but is not limited thereto.
  • the bandwidth improving unit 243 may perform a function of improving the phase bandwidth and / or the size bandwidth of the Doherty power amplifier 200.
  • the bandwidth improving unit 243 may be formed of a transmission line or one or more resonant circuits, but is not limited thereto.
  • the Doherty combiner 240 can improve the phase difference between the RF signal output from the carrier amplifier 220 and the RF signal output from the peaking amplifier 230 by using the bandwidth improving unit 243. [ The Doherty combiner 240 not only improves the size bandwidth of the Doherty power amplifier 200 by adding the bandwidth improver 243 to the output P 2 of the peaking amplifier 230, 230 may be implemented with an impedance different from 50 ohms.
  • FIG. 3 is a diagram illustrating a configuration of a Doherty power amplifier according to a first embodiment of the present invention.
  • the Doherty power amplifier 300 may include a coupler 310, a carrier amplifier 320, a peaking amplifier 330, and a Doherty combiner 340 .
  • the coupler 310, the carrier amplifier 320 and the peaking amplifier 330 are the same as the coupler 210, the carrier amplifier 220 and the peaking amplifier 230 shown in FIG. 2, .
  • the Doherty combiner 340 may combine the first RF signal output from the carrier amplifier 320 and the second RF signal output from the peaking amplifier 330 and output the combined signal.
  • the Doherty combiner 340 includes a first transmission line 341 connected to the output stage P 1 of the carrier amplifier 340 and a second transmission line 341 connected to the output stage P 3 of the Doherty power amplifier 300. And a third transmission line 343 connected to the output end P 2 of the peaking amplifier 330.
  • the characteristic impedance Z 0 is equal to the output impedance of the stage of the carrier amplifier 320. (However, slight changes are possible for bandwidth expansion.)
  • the Doherty combiner 340 can improve the phase difference between the RF signal input from the carrier amplifier 320 and the RF signal input from the peaking amplifier 330 using the third transmission line 343. [ The Doherty combiner 340 can also implement the peaking amplifier 330 at an impedance lower than 50 ohms by adding the third transmission line 343 to the output P 2 of the peaking amplifier 330 .
  • an RF signal enters the ⁇ phase in the carrier amplifier 320,
  • the RF signal comes in phase.
  • the RF signals coming from the two amplifiers 320 and 330 are amplified at the center frequency f 0 ), And at a selected frequency f other than the center frequency f 0 , ).
  • the value of the characteristic impedance Z c of the third transmission line 343 added to the output terminal of the peaking amplifier 330 may be determined so as to have a phase difference of 90 ° at the selected frequency f.
  • a method of calculating the characteristic impedance Z c will be described later with reference to FIG.
  • FIG. 4 is a diagram showing an equivalent circuit relating to the Doherty power amplifier 300 of FIG.
  • the first equivalent circuit 410 is an equivalent circuit for viewing the input / output magnitude and phase from the carrier amplifier 320.
  • the p 2 point of the peaking amplifier 330 is Z 0 &lt ; / RTI >
  • the phases ⁇ and p ' 2 from the end p 1 to p' 2 of the carrier amplifier 320 and the output terminals of the doherty power amplifier 300 It sums the phase to the (p 3).
  • the second equivalent circuit 420 is an equivalent circuit for viewing the input / output magnitude and phase from the peaking amplifier 330.
  • the second equivalent circuit 420 is connected to the p 1 point of the carrier amplifier 320 Is terminated with Z 0 and is an equivalent circuit.
  • the phase from the end point p 2 of the peaking amplifier 330 to the output end p 3 of the Doherty power amplifier 300 is calculated by the following Equation 2 so as to observe the input / output phase from the peaking amplifier 330 ABCD-parameter.
  • phase identification of the Doherty combiner 340 is possible.
  • the phase of the point p 1 to p '2 points can be obtained (that is, the electrical length ⁇ of the phase shift line (341)), ABCD- obtained from the above equation (1) through the conversion of the parameters of the phase parameter p 'p 3 from the second point to the point ( ) Can be obtained.
  • the output phase from the peaking amplifier 330 Corresponds to the phase from the end p 2 of the picking amplifier 330 to the output end p 3 of the doherty power amplifier 300. Therefore, the output phase ( Can be defined by the following Equation (4) through parameter conversion of Equation (2).
  • phase difference at the center frequency (f 0 ) ( ) And the phase difference at a specific frequency (f) ) Can be obtained. That is, the phase difference at the center frequency (f 0 ) ), And the phase difference at the selected frequency f ), .
  • the phase difference between the center frequency (f 0 ) and the selected frequency (f) can be obtained as shown in Equation (6) below.
  • Equation (6) Is a value determined by the electrical length of the first transmission line 341 Lt; / RTI & Is substituted into the above Equation (6), the following Equation (7) can be obtained.
  • FIG. 5 is a graph comparing the performance of a conventional Doherty coupler and a Doherty coupler of FIG. 5 (a) is a graph showing a result of simulation of magnitude characteristics of a conventional Doherty coupler and a Doherty coupler of the present invention, and FIG. 5 (b) FIG. 5 is a graph showing a result of simulating phase difference characteristics of a Doherty coupler of the present invention.
  • FIG. 5 is a graph comparing the performance of a conventional Doherty coupler and a Doherty coupler of FIG. 5 (a) is a graph showing a result of simulation of magnitude characteristics of a conventional Doherty coupler and a Doherty coupler of the present invention
  • FIG. 5 is a graph showing a result of simulating phase difference characteristics of a Doherty coupler of the present invention.
  • the power is divided to -3.01 dB at the center frequency (3GHz) in both the conventional Doherty coupler and the Doherty coupler of the present invention.
  • Fig. 5 (b) in the case of the conventional Doherty coupler, from the center frequency (3GHz)
  • the phase bandwidth of 2.93 GHz to 3.07 GHz is 4.66%
  • the Doherty coupler of the present invention has a wide bandwidth of 2.7% to 3.3 GHz. Accordingly, in the case of the Doherty coupler according to the present invention, it can be seen that the phase bandwidth can be improved in a desired frequency region and power is appropriately distributed.
  • 6A and 6B are diagrams showing a configuration of a Doherty power amplifier according to a second embodiment of the present invention.
  • a Doherty power amplifier 600 includes a coupler 610, a carrier amplifier 620, a picking amplifier 630, and a Doherty combiner 640 can do.
  • the coupler 610, the carrier amplifier 620 and the peaking amplifier 630 are the same as the coupler 210, the carrier amplifier 220, and the peaking amplifier 230 shown in FIG. 2, .
  • a Doherty combiner 640 includes a first transmission line 641 connected to the output stage P 1 of the carrier amplifier 640, a Doherty power amplifier (not shown) 600) an output stage (P 3) and grounded at the output terminal (P 2) and a third transmission line is connected (643), P 2 'branch of the second transmission line 642, peaking amplifier 630 connected to the ( and a parallel resonant circuit 644 connected to the ground.
  • the Doherty combiner 640 includes a first transmission line 641 connected to the output stage P 1 of the carrier amplifier 620, a Doherty power amplifier (not shown) 600) an output stage (P 3) and grounded at the output terminal (P 2) and a third transmission line is connected (643), P 2 'branch of the second transmission line 642, peaking amplifier 630 connected to the ( and a fourth transmission line 645 connected to the ground.
  • the third transmission line 643 may be a 180 ° phase shift line for improving the bandwidth of the Doherty power amplifier 600.
  • the characteristic impedance value of the third transmission line 643 can be calculated using the method described in FIG.
  • the parallel resonant circuit 644 may be composed of L / C passive elements for improving the magnitude bandwidth of the Doherty power amplifier 600. [ At this time, the inductor L and the capacitor C may be connected in parallel.
  • C is the capacitor value of the parallel resonant circuit.
  • the Doherty combiner 640 shown in FIG. 6A can improve the magnitude bandwidth of the Doherty power amplifier 600 by using the third transmission line 643 and the parallel resonant circuit 644.
  • the Doherty combiner 640 also adds the third transmission line 643 and the parallel resonant circuit 644 to the output P 2 of the peaking amplifier 630 to reduce the peaking amplifier 630 to 50 ohms, And other impedances.
  • the Doherty combiner 640 shown in FIG. 6B can improve the magnitude bandwidth of the Doherty power amplifier 600 using the third and fourth transmission lines 643 and 645.
  • the Doherty combiner 640 also adds the third and fourth transmission lines 643 and 645 to the output P 2 of the peaking amplifier 630 so that the peaking amplifier 630 is different from the 50- Impedance can be implemented.
  • FIG. 7A is a graph showing a result of simulating the magnitude characteristic of the Doherty coupler of FIG. 6B
  • FIG. 7B is a graph illustrating a simulation result of the phase difference characteristic of the Doherty coupler of FIG. 6B.
  • the center frequency (2 GHz) and the phase bandwidth between 1.9 GHz and 2.1 GHz is 20%.
  • FIG. 8 is a diagram illustrating a configuration of a Doherty power amplifier according to a third embodiment of the present invention.
  • a Doherty power amplifier 800 may include a coupler 810, a carrier amplifier 820, a peaking amplifier 830, and a Doherty combiner 840 .
  • the coupler 810, the carrier amplifier 820 and the peaking amplifier 830 are the same as the coupler 210, the carrier amplifier 220 and the peaking amplifier 230 shown in FIG. 2, .
  • the Doherty combiner 840 includes a first transmission line 841 connected to the output stage P 1 of the carrier amplifier 840 and a second transmission line 842 connected to the output stage P 3 of the Doherty power amplifier 800. 2 transmission line 842 and a series resonant circuit 843 connected to the output end P 2 of the peaking amplifier 830.
  • the serial resonant circuit 843 may be composed of L / C passive elements to improve the bandwidth of the Doherty power amplifier 800.
  • the inductor L and the capacitor C may be connected in series.
  • the inductor L and the capacitor C may be implemented through a lumped element or a distributed element.
  • the Doherty combiner 840 can improve the phase difference between the RF signal coming from the carrier amplifier 820 and the RF signal coming from the peaking amplifier 830 using the series resonant circuit 843.
  • the serial resonant circuit 843 may provide a short circuit at the center frequency (f 0), and provides about a 90 ° phase difference between S 31 and S 32 in the selected frequency band out of the center frequency (f 0) .
  • the L and C values of the series resonant circuit 843 added to the output terminal of the peaking amplifier 830 can be determined so as to have a phase difference of 90 degrees at the selected frequency f other than the center frequency f 0 . A method of calculating the L and C values will be described later with reference to FIG. 9 below.
  • FIG. 9 is a diagram showing an equivalent circuit relating to the Doherty power amplifier 800 of FIG.
  • the first equivalent circuit 910 is an equivalent circuit for viewing the phase difference of S 31 , and the p 2 point of the picking amplifier 830 is terminated to Z 0 It is a configured equivalent circuit.
  • the output terminal of the carrier amplifier 820 end (p 1) from p '1 phase ⁇ and p to the point "Doherty power amplifier (800), from a point of up to (p 3) Sum the phases.
  • the second equivalent circuit 920 is an equivalent circuit for viewing the phase difference of S 32 , in which the p 1 point of the carrier amplifier 820 is terminated to Z 0 ).
  • phase difference between S 32, through ABCD- parameters, such as output-stage phase equation (10) below the to the (p 3) of the Doherty amplifier 800 from the end point (p 2) of the peaking amplifier 830 Can be obtained.
  • phase identification of the Doherty combiner 840 is possible.
  • the phase of the point p 1 to p '1 point can be obtained (that is, the electrical length ⁇ of the phase shift line (841)), ABCD- obtained from the above equation (9)
  • the output phase from p ' 1 to p 3 ( ) Can be obtained.
  • the output phase from the peaking amplifier 830 Corresponds to the phase from the end p 2 of the picking amplifier 830 to the output end p 3 of the doherty power amplifier 800. Therefore, the output phase ( Can be defined by the following Equation (12) through parameter conversion of Equation (10).
  • Equation (13) the output phase from the carrier amplifier 820 And the output phase from the peaking amplifier 830 ) Phase difference.
  • phase difference at the center frequency (f 0 ) ) Can be defined by the following equation (14), and the phase difference at the selected frequency f ) Can be defined by the following equation (15).
  • the capacitor value C of the series resonant circuit 843 is obtained by using the above-described expression (16) And the value L of the inductor can be obtained by the resonance condition.
  • FIG. 10 is a graph comparing performance of a conventional Doherty coupler and a Doherty coupler of FIG. 10 (a) is a view showing a simulation result of magnitude characteristics of a conventional Doherty coupler and a Doherty coupler of the present invention, and FIG. 10 (b) FIG. 5 is a graph showing a result of simulating phase difference characteristics of a Doherty coupler of the present invention.
  • the power is distributed at -3.01 dB from the center frequency (2 GHz) in both the conventional Doherty coupler and the Doherty coupler of the present invention.
  • Fig. 10 (b) in the case of the conventional Doherty coupler, from the center frequency (2 GHz) While the phase bandwidth between the 1.98 GHz and 2.02 GHz bandwidths is 2% narrow, in the case of the Doherty coupler according to the present invention, The phase bandwidth between 1.9 GHz and 2.09 GHz has a wide bandwidth of 9.5%. Accordingly, in the case of the Doherty coupler according to the present invention, it can be seen that the phase bandwidth can be improved in a desired frequency region and power is appropriately distributed.
  • the series resonant circuit 843 connected to the output terminal P2 of the picking amplifier 830 is implemented through a distributed element rather than a lumped element
  • the serial resonant circuit 843 The phase? Is additionally generated.
  • a phase compensation line (not shown) for compensating for the phase phi additionally generated at the output terminal P 2 of the peaking amplifier 830 is inserted into the output terminal P 1 of the carrier amplifier 820 .
  • FIG. 11 is a diagram showing a configuration of a Doherty power amplifier according to a fourth embodiment of the present invention.
  • a Doherty power amplifier 1100 may include a coupler 1110, a carrier amplifier 1120, a picking amplifier 1130, and a Doherty combiner 1140 .
  • the coupler 1110, the carrier amplifier 1120 and the peaking amplifier 1130 are the same as the coupler 210, the carrier amplifier 220 and the peaking amplifier 230 shown in FIG. 2, .
  • the Doherty combiner 1140 includes first lumped elements 1141 connected to the output stage P 1 of the carrier amplifier 1120 and an output stage P 3 of the Doherty power amplifier 1100 And a series resonant circuit 1143 connected to the output end P 2 of the peaking amplifier 1130.
  • the second loudspeaker 1142 is connected to the output terminal P 2 of the peaking amplifier 1130.
  • the Doherty combiner 1140 can realize the phase shifter 1141 as a first lumped element equivalent to the first transmission line. Also, the matching unit 1142 can be implemented as a second lumped element equivalent to the second transmission line.
  • the Doherty combiner 1140 and the Doherty power amplifier 1100 including the Doherty combiner 1140 can be downsized.
  • the Doherty combiner 1140 may have the same phase bandwidth and size bandwidth as the Doherty combiner 840 of FIG. 8, even though the first and second lumped elements are used instead of the first and second transmission lines.
  • the first lumped element 1141 may perform a phase shift function for coupling the output of the carrier amplifier 1120 and the output of the peaking amplifier 1130. 12, the first lumped element 1141 includes a low-pass? Type LC circuit 1210, a high-pass? Type LC circuit 1220, a low-pass T type LC circuit 1220 1230, and a high-pass T-type LC circuit 1240.
  • the second lumped element 1142 may perform impedance matching on the output of the Doherty power amplifier 1100. 12, the second lumped element 1142 includes a low-pass ⁇ -type LC circuit 1210, a high-pass ⁇ -type LC circuit 1220, a low-pass T-type LC circuit 1230, and a high-pass T-type LC circuit 1240.
  • the Doherty coupler 1140 has 16 types . ≪ / RTI >
  • the first and second lumped elements are of the ⁇ - ⁇ type structure, the first and second lumped elements are classified into 'Low-pass ⁇ type / Low-pass ⁇ type' Pass type, high-pass type, high-pass type, low-pass type, high-pass type, and high-pass type.
  • the first and second lumped elements are of a TT type structure
  • the first and second lumped elements are classified into a low-pass T type / low-pass T type, a low-pass T type / high- Type, high-pass T type, low-pass T type, and high-pass T type / high-pass T type.
  • the first and second lumped elements are of the ⁇ -T type structure
  • the first and second lumped elements are classified into a low-pass ⁇ type / low-pass T type, a low-pass ⁇ type / Pass T type ',' High-pass ⁇ type / Low-pass T type ', and' High-pass ⁇ type / High-pass T type '.
  • the first and second lumped elements are of T-type
  • the first and second lumped elements are classified into a low-pass T type, a low-pass type, a low-pass type, and a high- Pass ⁇ type ',' High-pass T type / Low-pass ⁇ type ', and' High-pass T type / High-pass ⁇ type '.
  • the 16 Doherty combiners will be described in detail with reference to FIGS. 14 to 29 below.
  • the series resonant circuit 1143 may be constituted by L / C passive elements for improving the bandwidth of the Doherty power amplifier 1100. At this time, the inductor L and the capacitor C may be connected in series.
  • the Doherty combiner 1140 may add a series resonant circuit 1143 to the output stage of the peaking amplifier 1130 to improve the phase difference between the RF signal coming from the carrier amplifier 1120 and the RF signal coming from the peaking amplifier 1130 have.
  • the Doherty combiner 1400 may include a first lumped element 1410, a second lumped element 1420, and a series resonant circuit 1430.
  • the first lumped element 1410 may be configured as a Low-Pass ⁇ type composed of one inductor L 1 and two capacitors C 1 and the second lumped element 1420 may be composed of one inductor L 2 And a low-pass? Type comprising two capacitors C 2 .
  • the series resonant circuit 1430 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 1410, the second lumped element 1420, and the serial resonant circuit 1430 may have different values.
  • the Doherty coupler 1500 may include a first lumped element 1510, a second lumped element 1520, and a series resonant circuit 1530.
  • the first lumped element 1510 may be configured as a Low-Pass ⁇ type composed of one inductor L 1 and two capacitors C 1 and the second lumped element 1520 may be composed of two inductors L 2 ) and it may be of a single capacitor (C 2) High-Pass ⁇ type consisting of.
  • the series resonant circuit 1530 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 1510, the second lumped element 1520, and the serial resonant circuit 1530 may have different values.
  • 16 is a diagram showing a Doherty combiner 1600 having a High-Pass ⁇ type / Low-Pass ⁇ type structure.
  • the Doherty coupler 1600 may include a first lumped element 1610, a second lumped element 1620, and a series resonant circuit 1630.
  • the first lumped element 1610 may be configured as a High-Pass ⁇ type comprising two inductors L 1 and one capacitor C 1 and the second lumped element 1620 may be composed of one inductor L 2 And a low-pass? Type comprising two capacitors C 2 .
  • the serial resonant circuit 1630 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 1610, the second lumped element 1620, and the serial resonant circuit 1630 may have different values.
  • the Doherty combiner 1700 may include a first lumped element 1710, a second lumped element 1720, and a series resonant circuit 1730.
  • the first lumped element 1710 may be configured as a High-Pass ⁇ type having two inductors L 1 and a single capacitor C 1 and the second lumped element 1720 may be composed of two inductors L 2 ) and it may be of a single capacitor (C 2) High-Pass ⁇ type consisting of.
  • the series resonant circuit 1730 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 1710, the second lumped element 1720, and the series resonant circuit 1730 may have different values.
  • the Doherty combiner 1800 is a diagram showing a Doherty combiner 1800 having a low-pass T type / low-pass T type structure. 18, the Doherty combiner 1800 may include a first lumped element 1810, a second lumped element 1820, and a series resonant circuit 1830.
  • the first lumped element 1810 may be configured as a Low-Pass T type including two inductors L 1 and one capacitor C 1 and the second lumped element 1820 may be composed of two inductors L 2 And a low-pass T type including one capacitor C 2 .
  • the series resonant circuit 1830 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 1810, the second lumped element 1820, and the serial resonant circuit 1830 may have different values.
  • 19 is a diagram showing a Doherty coupler 1900 having a low-pass T-type / high-pass T type structure.
  • the Doherty combiner 1900 may include a first lumped element 1910, a second lumped element 1920, and a series resonant circuit 1930.
  • the first lumped element 1910 may be configured as a Low-Pass T type including two inductors L 1 and one capacitor C 1 and the second lumped element 1920 may be configured as one inductor L 2 And a high-pass T type including two capacitors C 2 .
  • the series resonant circuit 1930 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 1910, the second lumped element 1920, and the series resonant circuit 1930 may have different values.
  • the Doherty coupler 2000 may include a first lumped element 2010, a second lumped element 2020, and a series resonant circuit 2030.
  • the first lumped element 2010 may be configured as a High-Pass T type including one inductor L 1 and two capacitors C 1 and the second lumped element 2020 may be composed of two inductors L 2 And a low-pass T type including one capacitor C 2 .
  • the series resonant circuit 2030 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2010, the second lumped element 2020, and the series resonant circuit 2030 may have different values.
  • 21 is a diagram showing a Doherty combiner 2100 having a high-pass T type / high-pass T type structure.
  • the Doherty combiner 2100 may include a first lumped element 2110, a second lumped element 2120, and a series resonant circuit 2130.
  • the first lumped element 2110 may be configured as a high-pass T type including one inductor L 1 and two capacitors C 1 and the second lumped element 2120 may be configured as one inductor L 2 And a high-pass T type including two capacitors C 2 .
  • the series resonant circuit 2130 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2110, the second lumped element 2120, and the series resonant circuit 2130 may have different values.
  • the Doherty coupler 2200 may include a first lumped element 2210, a second lumped element 2220, and a series resonant circuit 2230.
  • the first lumped element 2210 may be configured as a High-Pass ⁇ type composed of two inductors L 1 and one capacitor C 1 and the second lumped element 2220 may be composed of one inductor L 2 And a high-pass T type including two capacitors C 2 .
  • the series resonant circuit 2230 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2210, the second lumped element 2220, and the serial resonant circuit 2230 may have different values.
  • the Doherty coupler 2300 may include a first lumped element 2310, a second lumped element 2320, and a series resonant circuit 2330.
  • the first lumped element 2310 may be configured as a High-Pass ⁇ type composed of two inductors L 1 and one capacitor C 1 and the second lumped element 2320 may be composed of two inductors L 2 And a low-pass T type including one capacitor C 2 .
  • the serial resonant circuit 2330 may be composed of one inductor L 3 and one capacitor C 3 .
  • 24 is a diagram showing a Doherty coupler 2400 having a low-pass ⁇ type / high-pass T type structure.
  • the Doherty combiner 2400 may include a first lumped element 2410, a second lumped element 2420, and a series resonant circuit 2430.
  • the first lumped element 2410 may be configured as a Low-Pass ⁇ type comprising one inductor L 1 and two capacitors C 1 and the second lumped element 2420 may be composed of one inductor L 2 And a high-pass T type including two capacitors C 2 .
  • the series resonant circuit 2430 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2410, the second lumped element 2420 and the serial resonant circuit 2430 may have different values.
  • 25 is a diagram showing a Doherty coupler 2500 having a Low-Pass ⁇ type / Low-Pass T type structure.
  • the Doherty coupler 2500 may include a first lumped element 2510, a second lumped element 2520, and a series resonant circuit 2530.
  • the first lumped element 2510 may be configured as a Low-Pass ⁇ type composed of one inductor L 1 and two capacitors C 1 and the second lumped element 2520 may be composed of two inductors L 2 And a low-pass T type including one capacitor C 2 .
  • the serial resonant circuit 2530 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2510, the second lumped element 2520 and the serial resonant circuit 2530 may have different values.
  • 26 is a diagram showing a Doherty combiner 2600 having a high-pass T type / high-pass? Type structure. 26, the Doherty coupler 2600 may include a first lumped element 2610, a second lumped element 2620, and a series resonant circuit 2630. [
  • the first lumped element 2610 may be configured as a High-Pass T type including one inductor L 1 and two capacitors C 1 and the second lumped element 2620 may be configured as two inductors L 2 ) and it may be of a single capacitor (C 2) High-Pass ⁇ type consisting of.
  • the series resonant circuit 2630 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2610, the second lumped element 2620 and the series resonant circuit 2630 may have different values.
  • 27 is a diagram showing a Doherty combiner 2700 having a High-Pass T type / Low-Pass ⁇ type structure.
  • the Doherty combiner 2700 may include a first lumped element 2710, a second lumped element 2720, and a series resonant circuit 2730.
  • the first lumped element 2710 may be configured as a High-Pass T type including one inductor L 1 and two capacitors C 1 and the second lumped element 2720 may be constituted by one inductor L 2 And a low-pass? Type comprising two capacitors C 2 .
  • the series resonant circuit 2730 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2710, the second lumped element 2720, and the series resonant circuit 2730 may have different values.
  • the Doherty combiner 2800 may include a first lumped element 2810, a second lumped element 2820, and a series resonant circuit 2830.
  • the first lumped element 2810 may be configured as a Low-Pass T type including two inductors L 1 and one capacitor C 1 and the second lumped element 2820 may be configured as two inductors L 2 ) and it may be of a single capacitor (C 2) High-Pass ⁇ type consisting of.
  • the series resonant circuit 2830 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2810, the second lumped element 2820, and the serial resonant circuit 2830 may have different values.
  • 29 is a diagram showing a Doherty coupler 2900 having a low-pass T type / low-pass? Type structure. 29, the Doherty coupler 2900 may include a first lumped element 2910, a second lumped element 2920, and a series resonant circuit 2930. [
  • the first lumped element 2910 may be configured as a Low-Pass T type including two inductors L 1 and one capacitor C 1 and the second lumped element 2920 may be configured as one inductor L 2 And a low-pass? Type comprising two capacitors C 2 .
  • the series resonant circuit 2930 may be composed of one inductor L 3 and one capacitor C 3 .
  • the L / C values of the first lumped element 2910, the second lumped element 2920, and the serial resonant circuit 2930 may have different values.
  • 30A and 30B are views showing the configuration of a Doherty power amplifier according to a fifth embodiment of the present invention.
  • a Doherty power amplifier 3000 includes a coupler 3010, a carrier amplifier 3020, a picking amplifier 3030, and a Doherty combiner 3040 can do.
  • the coupler 3010, the carrier amplifier 3020 and the peaking amplifier 3030 are the same as the coupler 210, the carrier amplifier 220 and the peaking amplifier 230 shown in FIG. 2, .
  • a Doherty combiner 3040 includes a first transmission line 3041 connected to the output stage P 1 of the carrier amplifier 3020, a Doherty power amplifier 3000 A second transmission line 3042 connected to the output end P 3 of the peaking amplifier 3030 and a first bandwidth improving unit 3043 connected to the output end P 2 of the peaking amplifier 3030.
  • the first bandwidth improving unit 3043 may be composed of a serial resonant circuit and a parallel resonant circuit.
  • a Doherty combiner 3040 according to the present invention includes a first transmission line 3041 connected to the output stage P 1 of the carrier amplifier 3020, a Doherty power amplifier 3000 A second transmission line 3042 connected to the output terminal P 3 of the peaking amplifier 3030 and a second bandwidth improving unit 3044 connected to the output terminal P 2 of the peaking amplifier 3030.
  • the second bandwidth improving unit 3044 may include a serial resonant circuit and a third transmission line.
  • the series resonant circuit of the first bandwidth improving unit 3043 may be configured with L / C passive elements for improving the phase bandwidth of the Doherty power amplifier 3000. [ At this time, the inductor L 1 and the capacitor C 1 may be connected in series.
  • the parallel resonance circuit of the first bandwidth enhancer 3043 may be composed of L / C passive elements for improving the magnitude bandwidth of the Doherty power amplifier 3000.
  • the inductor L 2 and the capacitor C 2 may be connected in parallel.
  • the L 2 and C 2 values of the parallel resonance circuit are independent of the L 1 and C 1 values of the series resonance circuit. (However, they may have the same value.)
  • the series resonant circuit of the second bandwidth enhancement unit 3044 may be composed of L / C passive elements for improving the phase bandwidth of the Doherty power amplifier 3000. At this time, the inductor L 1 and the capacitor C 1 may be connected in series.
  • the third transmission line of the second bandwidth improving unit 3044 may be constituted by a short stub which is an equivalent circuit of the parallel resonant circuit of the first bandwidth improving unit 3043.
  • the Doherty combiner 3040 shown in Fig. 30A can improve the phase bandwidth of the Doherty power amplifier 3000 by adding a serial resonant circuit to the output stage P 2 of the peaking amplifier 3030.
  • the Doherty combiner 3040 can also improve the size bandwidth of the Doherty power amplifier 3000 by adding a parallel resonant circuit to the output stage P 2 of the peaking amplifier 3030.
  • the Doherty combiner 3040 shown in Fig. 30B can improve the phase bandwidth of the Doherty power amplifier 3000 by adding a series resonant circuit to the output stage P 2 of the peaking amplifier 3030.
  • the Doherty combiner 3040 can also improve the size bandwidth of the Doherty power amplifier 3000 by adding a short stub to the output stage P 2 of the peaking amplifier 3030.
  • FIG. 31A is a diagram showing a result of simulation of the magnitude characteristic of the Doherty coupler of FIG. 30A
  • FIG. 31B is a diagram showing a result of simulating the phase difference characteristic of the Doherty coupler of FIG. 30A.
  • the size bandwidth is increased by 760 MHz as compared with the Doherty coupler using only the serial resonant circuit.
  • the Doherty coupler according to the present invention has the same phase difference as the Doherty coupler using only the serial resonant circuit.
  • the size bandwidth of the amplifier is improved while maintaining the phase bandwidth of the Doherty power amplifier by adding the parallel resonant circuit to the series resonant circuit provided in the Doherty combiner 800 of FIG.
  • FIG. 32 is a diagram showing a configuration of a Doherty power amplifier according to a sixth embodiment of the present invention.
  • the Doherty power amplifier 3200 may include a coupler 3210, a carrier amplifier 3220, a picking amplifier 3230 and a Doherty combiner 3240 .
  • the coupler 3210, the carrier amplifier 3220 and the peaking amplifier 3230 are the same as the coupler 210, the carrier amplifier 220 and the peaking amplifier 230 shown in FIG. 2, .
  • the Doherty combiner 3240 includes first lumped elements 3241 connected to the output stage P 1 of the carrier amplifier 3240, an output stage P 3 of the Doherty power amplifier 3200, And a bandwidth improving unit 3243 connected to the output terminal P 2 of the peaking amplifier 3230.
  • the bandwidth improving unit 3243 may be composed of a serial resonant circuit and a parallel resonant circuit.
  • the phase shifter 3241 can be implemented as a first lumped element equivalent to the first transmission line.
  • the matching unit 3242 can be implemented as a second lumped element equivalent to the second transmission line.
  • the Doherty combiner 3240 and the Doherty power amplifier 3200 including the Doherty combiner 3240 can be downsized.
  • the Doherty combiner 3240 may have the same phase bandwidth and magnitude bandwidth as the Doherty combiner 3040 of FIG. 30, even though the first and second lumped elements are used instead of the first and second transmission lines. can do.
  • the first lumped element 3241 may perform a phase shift function to combine the outputs of the carrier amplifier 3220 and the peaking amplifier 3230. 33, the first lumped element 3241 includes a low-pass? Type LC circuit 3310, a high-pass? Type LC circuit 3320, a low-pass T type LC circuit 3330, and a high-pass T-type LC circuit 3340.
  • the second lumped element 3242 may perform impedance matching of the output of the Doherty power amplifier 3200.
  • the second lumped element 3242 includes a low-pass? Type LC circuit 3310, a high-pass? Type LC circuit 3320, a low-pass T type LC circuit 3330, and a high-pass T-type LC circuit 3340.
  • the Doherty coupler 3240 according to the present embodiment has 16 types As shown in FIG.
  • the first and second lumped elements are of the ⁇ - ⁇ type structure, the first and second lumped elements are classified into 'Low-pass ⁇ type / Low-pass ⁇ type' Pass type, high-pass type, high-pass type, low-pass type, high-pass type, and high-pass type.
  • the first and second lumped elements are of a TT type structure
  • the first and second lumped elements are classified into a low-pass T type / low-pass T type, a low-pass T type / high- Type, high-pass T type, low-pass T type, and high-pass T type / high-pass T type.
  • the first and second lumped elements are of the ⁇ -T type structure
  • the first and second lumped elements are classified into a low-pass ⁇ type / low-pass T type, a low-pass ⁇ type / Pass T type ',' High-pass ⁇ type / Low-pass T type ', and' High-pass ⁇ type / High-pass T type '.
  • the first and second lumped elements are of T-type
  • the first and second lumped elements are classified into a low-pass T type, a low-pass type, a low-pass type, and a high- Pass ⁇ type ',' High-pass T type / Low-pass ⁇ type ', and' High-pass T type / High-pass ⁇ type '.
  • the series resonant circuit of the bandwidth enhancement unit 3243 may be composed of L / C passive elements for improving the phase bandwidth of the Doherty power amplifier 3200. At this time, the inductor L 1 and the capacitor C 1 may be connected in series.
  • the parallel resonance circuit of the bandwidth enhancement unit 3243 may be composed of L / C passive elements for improving the magnitude bandwidth of the Doherty power amplifier 3200.
  • the inductor L 2 and the capacitor C 2 may be connected in parallel.
  • the L 2 and C 2 values of the parallel resonance circuit are independent of the L 1 and C 1 values of the series resonance circuit. (However, they may have the same value.)
  • the Doherty combiner 3240 can improve the phase bandwidth of the Doherty power amplifier 3200 by adding a series resonant circuit to the output stage P 2 of the peaking amplifier 3230.
  • the Doherty combiner 3240 can also improve the size bandwidth of the Doherty power amplifier 3200 by adding a parallel resonant circuit to the output stage P 2 of the peaking amplifier 3230.
  • 35 is a diagram showing a configuration of a Doherty power amplifier according to a seventh embodiment of the present invention.
  • a Doherty power amplifier 3500 may include a coupler 3510, a carrier amplifier 3520, a peaking amplifier 3530 and a Doherty combiner 3540 .
  • the coupler 3510, the carrier amplifier 3520 and the peaking amplifier 3530 are the same as those of the coupler 210, the carrier amplifier 220 and the peaking amplifier 230 shown in FIG. 2, .
  • the Doherty combiner 3540 includes a phase shifter 3541 connected to the output stage P 1 of the carrier amplifier 3520 and a matching stage 3541 connected to the output stage P 3 of the Doherty power amplifier 3500. And a bandwidth improving unit 3543 connected to the output terminal P 2 of the peaking amplifier 3530.
  • the phase shifter 3541 may be constituted by the first lumped element and the first resonance circuit
  • the matching section 3542 may be constituted by the second lumped element and the second resonance circuit
  • the bandwidth improving section 3543 May be composed of a series resonance circuit and a parallel resonance circuit.
  • a phase shifter 3541 is implemented by adding a first resonant circuit to the first lumped element equivalent to the first transmission line .
  • the matching unit 3542 can be realized by adding a second resonant circuit to the second lumped element equivalent to the second transmission line.
  • the Doherty coupler 3540 can be miniaturized and the magnitude balance of the Doherty coupler 3540 can be improved.
  • the Doherty combiner 3540 may have the same phase difference as the Doherty combiner 3240 of Fig. 32 even if the first and second lumped elements are added to the first and second lumped elements.
  • the signal is transmitted without any loss at the resonance frequency, and the loss occurs due to the reflection of the signal as it deviates from the center frequency.
  • the first lumped element and the first resonance circuit may perform a phase shift function for coupling the outputs of the carrier amplifier 3520 and the peaking amplifier 3530.
  • a parallel resonant circuit can be added to the lumped element.
  • T type a serial resonant circuit can be added to the lumped element have.
  • the first lumped element and the first resonance circuit include a low-pass ⁇ type LC circuit 3610, a parallel resonance circuit 3620, a high-pass ⁇ type LC circuit Pass type LC circuit 3650 and the series resonant circuit 3660 and the high-pass T-type LC circuit 3670 and the serial resonant circuit 3680, As shown in FIG. At this time, the L and C values of the first lumped element may have different values from the L and C values of the first resonant circuit.
  • the L / C value of the first resonance circuit can be obtained by using a relational expression which is determined by the resonance frequency and a relational expression which is determined by the difference of the magnitude balance at frequencies out of the center frequency .
  • the second lumped element and the second resonant circuit may perform impedance matching of the output of the Doherty power amplifier 3500.
  • the second lumped element and the second resonant circuit include a low-pass? Type LC circuit 3610, a parallel resonant circuit 3620, a high-pass? Pass type LC circuit 3650 and the series resonant circuit 3660 and the high-pass T-type LC circuit 3670 and the serial resonant circuit 3680,
  • the L and C values of the second lumped element may have different values from the L and C values of the second resonant circuit.
  • the L and C values of the second resonance circuit may have the same values as the L and C values of the first resonance circuit.
  • the Doherty combiner 3540 may be implemented in a total of 16 forms.
  • the first lumped element + the first lumped element / the second lumped element + the second resonant circuit may be a low-pass? Type + parallel resonant circuit Pass ⁇ type + Parallel resonant circuit "," Low pass ⁇ type + Parallel resonant circuit / High pass ⁇ type + Parallel resonant circuit ",” High pass ⁇ type + Parallel resonant circuit / Low pass " Type + parallel resonance circuit ',' high-pass ⁇ type + parallel resonance circuit / high-pass ⁇ type + parallel resonance circuit '.
  • the 'first lumped element + the first resonant circuit / the second lumped element + the second resonant circuit' has a structure of 'Low Pass T type + serial resonant circuit / low pass T type + serial resonant circuit High-pass T-type + serial resonant circuit / low-pass T-type + serial resonant circuit / high-pass T-type + serial resonant circuit> Pass T type + serial resonant circuit / high-pass T type + serial resonant circuit '.
  • the first lumped element + the first lumped element / the second lumped element + the second resonant circuit may be of a low pass type, a parallel resonant circuit, a low-pass T type, Pass-T type + serial resonant circuit "," High-Pass ⁇ type + parallel resonant circuit / Low-Pass T type + serial resonant circuit ",” High-pass ⁇ type + parallel resonant circuit / high-pass T type + serial resonant circuit ".
  • the first lumped element + the first lumped element / the second lumped element + the second resonant circuit is composed of a low-pass T type + serial resonant circuit / low-pass?
  • the series resonant circuit of the bandwidth enhancement unit 3543 may be composed of L / C passive elements for improving the phase bandwidth of the Doherty power amplifier 3500.
  • the parallel resonance circuit of the bandwidth improver 3543 may be composed of L / C passive elements for improving the magnitude bandwidth of the Doherty power amplifier 3500.
  • the Doherty combiner 3540 may improve the phase bandwidth of the Doherty power amplifier 3500 by adding a series resonant circuit to the output stage P 2 of the peaking amplifier 3530.
  • the Doherty combiner 3540 can also improve the size bandwidth of the Doherty power amplifier 3500 by adding a parallel resonant circuit to the output stage P 2 of the peaking amplifier 3530.
  • phase shifter 3810 of the Doherty combiner 3800 may be configured as a? -Type structure and a low-pass? Type + parallel resonant circuit.
  • the matching unit 3820 of the Doherty combiner 3800 may be a? -Type structure, and may be configured as a Low-Pass? Type + parallel resonant circuit.
  • the Doherty coupler 3800 includes a phase shifter 3810, a second lumped element 3821, and a second resonant circuit 3822 composed of a first lumped element 3811 and a first resonant circuit 3812 A serial resonant circuit 3831 and a parallel resonant circuit 3832.
  • the matching unit 3820 may include a matching unit 3820,
  • the first lumped element 3811 may be configured as a Low-Pass ⁇ type composed of two inductors L 1/2 and two capacitors C 1.
  • the first resonant circuit 3812 may be a single- L 0 and one capacitor C 0 are connected in parallel.
  • a second focusing element (3821) comprises two inductors (L 2/2) and two capacitors (C 2) Low-Pass ⁇ and type may be configured by, in the second resonance circuit (3822) comprising one of the inductors ( L 0 and one capacitor C 0 are connected in parallel.
  • the L and C values of the second resonant circuit 3822 may have the same values as the L and C values of the first resonant circuit 3812.
  • the series resonant circuit 3831 may be constructed in a structure in which one inductor L 3 and one capacitor C 3 are connected in series and the parallel resonant circuit 3832 may be formed of one inductor L 4 and one a capacitor (C 4) may be of a structure connected in parallel.
  • the Doherty coupler 3840 may be provided with first and second resonant circuits 3812 and 3822 added to the first and second lumped elements 3811 and 3821 so that the size of the coupler 3840 can be reduced In addition, the magnitude balance of the coupler 3840 can be improved.
  • FIG. 39A is a diagram showing a result of simulating the magnitude characteristic of the Doherty coupler of FIG. 38
  • FIG. 39B is a diagram showing a result of simulating the phase difference characteristic of the Doherty coupler of FIG.
  • the size bandwidth is slightly reduced but the size balance is significantly improved as compared with the Doherty coupler using only the lumped element.
  • the Doherty coupler according to the present invention has the same phase difference as the Doherty coupler using only the lumped element.
  • FIG. 40 is a diagram showing a configuration of a Doherty power amplifier according to an eighth embodiment of the present invention.
  • a Doherty power amplifier 4000 may include a coupler 4010, a carrier amplifier 4020, a picking amplifier 4030, and a Doherty combiner 4040 .
  • the coupler 4010, the carrier amplifier 4020 and the peaking amplifier 4030 are the same as the coupler 210, the carrier amplifier 220 and the peaking amplifier 230 shown in FIG. 2, .
  • the Doherty combiner 4040 includes a phase shifter 4041 connected to the output stage P 1 of the carrier amplifier 4040 and a matching stage 4041 connected to the output stage P 3 of the Doherty power amplifier 4000. And a bandwidth improving unit 4043 connected to the output terminal P 2 of the peaking amplifier 4030.
  • the phase shifting unit 4041 may be constituted by a first lumped element (not shown) equivalent to the first transmission line or the first transmission line and the matching unit 4042 may be equivalent to the second transmission line or the second transmission line (Not shown).
  • the bandwidth improving unit 4043 may be composed of a serial resonant circuit and a parallel resonant circuit (not shown).
  • the parallel resonant circuit may be implemented as a short stub, which is an equivalent circuit.
  • the series resonant circuit of the bandwidth enhancement unit 4043 may be constituted by L / C passive elements for improving the bandwidth of the Doherty power amplifier 4000.
  • the short stub of the bandwidth improving section 4043 is a characteristic impedance of Z 2 and a short stub of? ). ≪ / RTI >
  • the characteristic impedance values (Z 0 , Z 1 , Z 2 ) of the first transmission line 4041, the second transmission line 4042 and the short stubby can be determined according to the design specifications of the carrier amplifier and the peaking amplifier.
  • the Doherty coupler 4040 is also connected to the Doherty coupler 3040 And may have the same phase bandwidth and magnitude bandwidth as the < Desc / Clms Page number 7 >
  • the Doherty coupler 4040 according to the present invention distributes the power according to the impedance ratio, Size bandwidth can be improved.
  • the Doherty combiner 4040 can improve the phase bandwidth of the Doherty power amplifier 4000 by adding a series resonant circuit to the output stage P 2 of the peaking amplifier 4030.
  • the Doherty combiner 4040 can also improve the size bandwidth of the Doherty power amplifier 4000 by adding a parallel resonant circuit or short stub to the output stage P 2 of the peaking amplifier 4030.
  • FIG. 41A is a diagram showing a configuration of a Doherty coupler obtained by converting a lumped element shown in a Doherty coupler of FIG. 40 into a dispersive element
  • FIG. 41B is a diagram referred to explain a method of implementing an equivalent circuit using a Gurode formula .
  • the Doherty combiner 4140 includes a phase shifter 4141 connected to the output stage P 1 of the carrier amplifier, a matching unit 4142 connected to the output stage P 3 of the Doherty power amplifier, And a bandwidth improving unit 4143 connected to the output end (P 2 ) of the peaking amplifier.
  • the phase shifter 4141 may be composed of a first transmission line and a second transmission line to couple the outputs of the carrier amplifier and the peaking amplifier.
  • the first transmission line may have a characteristic impedance of Z 0 and an electrical length of ⁇
  • the second transmission line may have a characteristic impedance of Z 0 and an electrical length of ⁇ .
  • the matching unit 4142 may be configured as a third transmission line to match the output of the Doherty power amplifier.
  • the third transmission line may have a characteristic impedance of Z 1 and an electrical length of?.
  • the bandwidth improving unit 4143 may be configured as a fourth transmission line, a fifth transmission line, a capacitance, and a short stub in order to improve the phase bandwidth and / or the size bandwidth.
  • the fourth transmission line may have a characteristic impedance of Z 3 and an electrical length of ⁇
  • a fifth transmission line may have a characteristic impedance of Z 4 and an electrical length of ⁇ .
  • the inductor L and the additional transmission line with two transmission lines using a known Gurode formula.
  • a distributed element equivalent to a lumped element of a serial resonant circuit can be implemented at the output stage of the peaking amplifier.
  • the distribution element may include a fourth transmission line, a fifth transmission line, and a capacitor.
  • the Doherty combiner 4140 according to the present invention has the same phase bandwidth and magnitude bandwidth as the Doherty combiner 3040 of FIG. 30 described above even when the impedance of the input port is different from that of the output port. .
  • the Doherty combiner 4140 can improve the phase bandwidth of the Doherty power amplifier by adding the distributed element implemented using the Kuroda formula to the output stage P 2 of the peaking amplifier.
  • the Doherty combiner 4140 can also improve the size bandwidth of the Doherty power amplifier by adding a parallel resonant circuit or short stub to the output stage (P 2 ) of the peaking amplifier.

Abstract

La présente invention concerne un combinateur de Doherty utilisé dans un amplificateur de puissance de Doherty, le combinateur de Doherty comprenant : une section de déphasage connectée à une extrémité d'un amplificateur de porteuse de façon à modifier une phase d'un signal RF émis par l'amplificateur de porteuse; une section d'adaptation connectée à une borne de sortie de l'amplificateur de puissance de Doherty de façon être en adaptation d'impédances avec une sortie de l'amplificateur de puissance de Doherty; et une section d'amélioration de largeur de bande connectée à une extrémité d'un amplificateur de crête de façon à modifier au moins l'une d'une largeur de bande de phase et d'une largeur de bande d'amplitude de l'amplificateur de puissance de Doherty.
PCT/KR2017/011732 2017-08-23 2017-10-23 Mélangeur de doherty WO2019039650A1 (fr)

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US16/641,214 US11201592B2 (en) 2017-08-23 2017-10-23 Doherty combiner
CN201780094207.1A CN111133676B (zh) 2017-08-23 2017-10-23 多尔蒂组合器

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KR1020170106729A KR101934933B1 (ko) 2017-08-23 2017-08-23 도허티 결합기
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KR102546533B1 (ko) * 2021-05-31 2023-06-23 한밭대학교 산학협력단 쉬프만 위상 천이기를 이용한 다중 대역 도허티 증폭기
WO2023101476A1 (fr) * 2021-12-01 2023-06-08 삼성전자 주식회사 Amplificateur de puissance et dispositif électronique le comprenant
CN114915266B (zh) * 2022-05-11 2023-08-11 锐石创芯(深圳)科技股份有限公司 射频放大电路和射频前端模组
WO2023229170A1 (fr) * 2022-05-23 2023-11-30 삼성전자 주식회사 Amplificateur de puissance de doherty dans un système de communication sans fil, et dispositif électronique le comprenant
CN117595798B (zh) * 2024-01-12 2024-03-29 四川恒湾科技有限公司 一种提升宽带功率放大器效率的电路及方法

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CN111133676A (zh) 2020-05-08
KR101934933B1 (ko) 2019-01-04
US11201592B2 (en) 2021-12-14
CN111133676B (zh) 2023-03-28

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