WO2019015030A1 - 电动车、车轮及其开关磁阻电机 - Google Patents

电动车、车轮及其开关磁阻电机 Download PDF

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Publication number
WO2019015030A1
WO2019015030A1 PCT/CN2017/100279 CN2017100279W WO2019015030A1 WO 2019015030 A1 WO2019015030 A1 WO 2019015030A1 CN 2017100279 W CN2017100279 W CN 2017100279W WO 2019015030 A1 WO2019015030 A1 WO 2019015030A1
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Prior art keywords
stator
switched reluctance
reluctance motor
teeth
phase
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PCT/CN2017/100279
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English (en)
French (fr)
Inventor
李铁才
童恩东
漆亚梅
黄国辉
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深圳市配天电机技术有限公司
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Publication of WO2019015030A1 publication Critical patent/WO2019015030A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/08—Reluctance motors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K1/00—Details of the magnetic circuit
    • H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
    • H02K1/12—Stationary parts of the magnetic circuit
    • H02K1/14—Stator cores with salient poles
    • H02K1/146—Stator cores with salient poles consisting of a generally annular yoke with salient poles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K19/00—Synchronous motors or generators
    • H02K19/02—Synchronous motors
    • H02K19/10—Synchronous motors for multi-phase current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K1/00—Details of the magnetic circuit
    • H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
    • H02K1/12—Stationary parts of the magnetic circuit
    • H02K1/14—Stator cores with salient poles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K1/00—Details of the magnetic circuit
    • H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
    • H02K1/12—Stationary parts of the magnetic circuit
    • H02K1/14—Stator cores with salient poles
    • H02K1/146—Stator cores with salient poles consisting of a generally annular yoke with salient poles
    • H02K1/148—Sectional cores
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K1/00—Details of the magnetic circuit
    • H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
    • H02K1/12—Stationary parts of the magnetic circuit
    • H02K1/16—Stator cores with slots for windings
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K1/00—Details of the magnetic circuit
    • H02K1/06—Details of the magnetic circuit characterised by the shape, form or construction
    • H02K1/22—Rotating parts of the magnetic circuit
    • H02K1/24—Rotor cores with salient poles ; Variable reluctance rotors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K11/00—Structural association of dynamo-electric machines with electric components or with devices for shielding, monitoring or protection
    • H02K11/20—Structural association of dynamo-electric machines with electric components or with devices for shielding, monitoring or protection for measuring, monitoring, testing, protecting or switching
    • H02K11/21—Devices for sensing speed or position, or actuated thereby
    • H02K11/22—Optical devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K11/00—Structural association of dynamo-electric machines with electric components or with devices for shielding, monitoring or protection
    • H02K11/20—Structural association of dynamo-electric machines with electric components or with devices for shielding, monitoring or protection for measuring, monitoring, testing, protecting or switching
    • H02K11/27—Devices for sensing current, or actuated thereby
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K15/00—Methods or apparatus specially adapted for manufacturing, assembling, maintaining or repairing of dynamo-electric machines
    • H02K15/02—Methods or apparatus specially adapted for manufacturing, assembling, maintaining or repairing of dynamo-electric machines of stator or rotor bodies
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K15/00—Methods or apparatus specially adapted for manufacturing, assembling, maintaining or repairing of dynamo-electric machines
    • H02K15/02—Methods or apparatus specially adapted for manufacturing, assembling, maintaining or repairing of dynamo-electric machines of stator or rotor bodies
    • H02K15/022—Methods or apparatus specially adapted for manufacturing, assembling, maintaining or repairing of dynamo-electric machines of stator or rotor bodies with salient poles or claw-shaped poles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K16/00—Machines with more than one rotor or stator
    • H02K16/04—Machines with one rotor and two stators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K29/00—Motors or generators having non-mechanical commutating devices, e.g. discharge tubes or semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K29/00—Motors or generators having non-mechanical commutating devices, e.g. discharge tubes or semiconductor devices
    • H02K29/03—Motors or generators having non-mechanical commutating devices, e.g. discharge tubes or semiconductor devices with a magnetic circuit specially adapted for avoiding torque ripples or self-starting problems
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K29/00—Motors or generators having non-mechanical commutating devices, e.g. discharge tubes or semiconductor devices
    • H02K29/06—Motors or generators having non-mechanical commutating devices, e.g. discharge tubes or semiconductor devices with position sensing devices
    • H02K29/08—Motors or generators having non-mechanical commutating devices, e.g. discharge tubes or semiconductor devices with position sensing devices using magnetic effect devices, e.g. Hall-plates, magneto-resistors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K3/00—Details of windings
    • H02K3/04—Windings characterised by the conductor shape, form or construction, e.g. with bar conductors
    • H02K3/18—Windings for salient poles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K3/00—Details of windings
    • H02K3/04—Windings characterised by the conductor shape, form or construction, e.g. with bar conductors
    • H02K3/18—Windings for salient poles
    • H02K3/20—Windings for salient poles for auxiliary purposes, e.g. damping or commutating
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K41/00—Propulsion systems in which a rigid body is moved along a path due to dynamo-electric interaction between the body and a magnetic field travelling along the path
    • H02K41/02—Linear motors; Sectional motors
    • H02K41/03—Synchronous motors; Motors moving step by step; Reluctance motors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/08—Reluctance motors
    • H02P25/092—Converters specially adapted for controlling reluctance motors
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/08—Reluctance motors
    • H02P25/098—Arrangements for reducing torque ripple
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/10—Arrangements for controlling torque ripple, e.g. providing reduced torque ripple
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/28—Arrangements for controlling current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02K—DYNAMO-ELECTRIC MACHINES
    • H02K2213/00—Specific aspects, not otherwise provided for and not covered by codes H02K2201/00 - H02K2211/00
    • H02K2213/03—Machines characterised by numerical values, ranges, mathematical expressions or similar information
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/62—Hybrid vehicles
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/64—Electric machine technologies in electromobility

Definitions

  • the invention relates to the technical field of electric machines, and relates to an electric vehicle, a wheel and a switched reluctance motor thereof.
  • the stator component of the three-phase switched reluctance motor needs Set three-phase windings, the magnetic lines of force generated by each phase winding must span 3 poles.
  • the magnetic lines of the three-phase windings interfere with each other, and the mutual inductance between the windings is serious, resulting in large fluctuations in motor torque;
  • the output torque of the traditional switched reluctance motor is small, resulting in low efficiency of the switched reluctance motor.
  • the general winding utilization is only 0.866.
  • the present invention provides a novel switched reluctance motor, and a wheel and an electric vehicle using the same.
  • an embodiment of the present invention provides a switched reluctance motor including a stator and a rotor, wherein the stator is axially segmented with at least three stator assemblies, each of which includes an edge a plurality of stator teeth of the stator periodically arranged in a circumferential direction and spaced apart from each other by stator slots; and stator windings on the stator teeth, the stator teeth of the at least three stator assemblies are sequentially arranged along the circumference of the stator Staggering a predetermined angle, the windings in each of the stator assemblies are all the same phase winding, and the rotor includes a plurality of rotor teeth periodically disposed along a circumference of the rotor and spaced apart from each other by a rotor slot, wherein The number of rotor teeth is the same as the number of stator teeth, and the width of the rotor teeth is smaller than the width of the stator slots.
  • a width ratio of the stator slot to the stator teeth is 1:0.95-0.85, and a width ratio of the stator teeth to the rotor teeth is 1:1.05-0.95.
  • the width ratio of the stator slot to the stator teeth is 1:0.95-0.85, and the width ratio of the stator teeth to the rotor teeth is 1:1.05-0.95.
  • the number of the stator teeth is an odd number.
  • the predetermined angle is T1/N, wherein the T1 is an electrical angle period of the stator teeth, and the N is the at least three The number of stator components.
  • N is an integer multiple of 3 or 3
  • the electrical angle period T1 of the stator teeth is 2 ⁇ /M, where M is the number of stator teeth.
  • the switched reluctance motor further comprises a switch drive circuit
  • the switch drive circuit is connected to the DC power supply and the windings of the at least three stator assemblies to periodically control the DC power supply in sequence at the third
  • the driving period corresponding to each of the stator assemblies applies the driving current to the windings, wherein phases of the driving periods of the at least three stator assemblies are staggered from each other.
  • the switch drive circuit further releases electrical energy stored on the windings of the at least three stator assemblies during a subsequent freewheeling period of the drive period corresponding to the at least three stator assemblies to form a freewheeling current.
  • phase difference of the driving period corresponding to the at least three stator components is 2 ⁇ /N, wherein the N is the number of the at least three stator components.
  • the freewheeling period of each of the stator assemblies at least partially overlaps with the phase of the driving period of the next driven stator assembly.
  • phase of the freewheeling period of each of the stator assemblies overlaps with the phase of the driving period of the next stator assembly to be ⁇ /N.
  • the switch driving circuit adjusts the driving current and the freewheeling current in a pulse width modulation manner, respectively.
  • the switched reluctance motor further includes a current detecting circuit, wherein the current detecting circuit is configured to detect a sum of currents flowing through the windings of the at least three stator assemblies, and the switch driving circuit detects the current according to the current The sum of the currents detected by the circuit controls the drive current and the freewheeling current of each of the windings, respectively, such that the sum of the currents maintains a predetermined range.
  • the current detecting circuit includes a toroidal core having an opening, and the magnetic field sensor, wherein the windings of the at least three stator assemblies are further respectively disposed on the toroidal core, and the magnetic field sensor is disposed on the The opening of the toroidal core.
  • windings of each of the stator assemblies are wound on the toroidal core with the same number of turns.
  • the magnetic field sensor is a linear Hall current sensor.
  • the switched reluctance motor further includes a position sensor coupled to the switch drive circuit, the position sensor for measuring a relative position of the stator and the rotor, the position sensor comprising a magnetic encoder or optical coding Device.
  • the present invention also provides a wheel, the wheel is driven by a hub motor, and the hub motor adopts the switched reluctance motor structure according to any one of the above embodiments.
  • the present invention further provides an electric vehicle, which is a pure electric or hybrid vehicle, and the electric vehicle adopts the switched reluctance motor structure according to any one of the above embodiments.
  • the switched reluctance motor provided by the embodiment of the invention has the following advantages: at least three stator assemblies are arranged in the axial direction by the stator, and each stator assembly is provided with a plurality of stator teeth and windings.
  • the windings on the stator teeth, the stator teeth of the at least three stator assemblies are sequentially shifted by a predetermined angle in the circumferential direction of the stator, the windings in each stator assembly are all the same phase winding, and the width of the rotor teeth is smaller than the width of the stator slots;
  • the windings in each stator assembly are all the same phase windings, so the magnetic lines generated by the windings of at least three stator components do not interfere with each other, overcoming the problem of mutual inductance of the windings, thereby solving the problem of torque ripple caused by mutual inductance;
  • the windings in the stator assembly are all the same phase winding, the magnetic field generated by the winding only spans one pole distance, the magnetic resistance is greatly reduced, the maximum inductance generated by the winding is large, and the width of the rotor teeth is smaller than the width of the stator slot, so the rotor teeth When compared with the stator slot, the resulting inductance is extremely small,
  • FIG. 1 is a schematic view showing a magnetic line of a conventional switched reluctance motor
  • FIG. 2 is a perspective view of a switched reluctance motor according to a first embodiment of the present invention
  • Figure 3 is an exploded perspective view of the switched reluctance motor of Figure 2;
  • FIG. 4 is a perspective view of a three-phase switched reluctance motor of an outer stator inner rotor
  • Figure 5 is a schematic view showing the structure of the A-phase winding of Figure 2 wound around the first stator teeth;
  • FIG. 6 is a schematic structural view of the first stator tooth, the second stator tooth, and the third stator tooth of FIG. 2;
  • Figure 7 is a magnetic line diagram of the center of the rotor teeth of Figure 2 coincident with the center of the first stator teeth;
  • Figure 8 is a schematic view showing the structure of the first stator teeth aligned with the rotor slots of Figure 2;
  • Figure 9 is a schematic view showing the magnetic lines of the rotor teeth of Figure 2 offset from the position of the first stator teeth;
  • FIG. 10 is a schematic diagram of an inductance curve of the switched reluctance motor of FIG. 2 in normal operation;
  • FIG. 11 is a schematic structural view showing a chamfering of a rotor tooth of a switched reluctance motor
  • Figure 12 is a circuit diagram of a switch driving circuit
  • Figure 13 is a timing chart of the working principle of the switched reluctance motor
  • Figure 14 is a schematic structural view of a current detecting circuit
  • Figure 15 is a timing chart showing the operation principle of the switched reluctance motor of the fifth embodiment of the present invention.
  • Figure 16 is a schematic structural view of a position sensor
  • Figure 17 is a flow chart showing a method of controlling the current of the switched reluctance motor of the first embodiment of the present invention.
  • the present invention provides a switched reluctance motor of a first embodiment, the switched reluctance motor 10 comprising a stator 11 and a rotor 12, wherein the stator 11 is provided with at least three stator assemblies in an axial section.
  • Each of the stator assemblies includes a plurality of stator teeth periodically disposed in the circumferential direction of the stator 11 and spaced apart from each other by the stator slots, and windings wound around the stator teeth, that is, a plurality of stator teeth are periodically arranged along the circumference of the stator 11. And spaced apart from each other by a plurality of stator slots.
  • the switched reluctance motor of the embodiment may be a three-phase switched reluctance motor, and the three-phase switched reluctance motor may be a three-phase switched reluctance motor of an outer rotor inner stator.
  • the stator 11 is axially segmented with three stator assemblies, which are an A-phase stator assembly 111, a B-phase stator assembly 112, and Phase C stator assembly 113.
  • the switched reluctance machine can be a three-phase switched reluctance motor 30 of the outer stator inner rotor, as shown in FIG.
  • the A-phase stator assembly 111 includes a plurality of first stator teeth 131, and the plurality of first stator teeth 131 and the plurality of first stator slots 134 are spaced apart from each other. As shown in FIG. 5, the A-phase stator assembly 111 further includes an A-phase winding 137 wound around the first stator tooth 131. When the A-phase winding 137 applies a driving current, the A-phase winding 137 generates a magnetic pole to form a magnetic field. .
  • the B-phase stator assembly 112 includes a plurality of second stator teeth 132 and a B-phase winding wound around the second stator teeth 132.
  • the plurality of second stator teeth 132 and the plurality of second stator slots 135 are spaced apart from each other;
  • the C-phase stator assembly 113 includes a plurality of third stator teeth 133 and a C-phase winding wound around the third stator teeth 133, the plurality of third stator teeth 133 being spaced apart from the plurality of third stator slots 136.
  • the B-phase winding is wound around the second stator tooth 132, and the C-phase winding is wound around the third stator tooth 133 and the A-phase winding 137 is wound around the first stator tooth 131, and details are not described herein.
  • stator teeth of the at least three stator assemblies are sequentially shifted by a predetermined angle along the circumferential direction of the stator 11 to enable the rotor 12 to continuously rotate under the action of a magnetic field generated by driving currents on the windings of the at least three stator assemblies. That is, a drive current is sequentially applied to the windings of at least three stator assemblies, and the rotor 12 continuously rotates under the action of the magnetic field generated by the windings.
  • the second stator teeth 132 and the first stator teeth 131 are sequentially shifted by a predetermined angle along the circumferential direction of the stator, and the third stator teeth 133 and the second stator teeth 132 are sequentially shifted by a predetermined angle along the circumferential direction of the stator;
  • the A-phase stator assembly 111, the B-phase stator assembly 112, and the C-phase stator assembly 113 sequentially apply a drive current, the magnetic field generated by the A-phase winding 137, the magnetic field generated by the B-phase winding, and the magnetic field generated by the C-phase winding are used to rotate the rotor. 12 continuous rotation.
  • the A-phase stator assembly 111 of the present embodiment includes an A-phase winding 137 wound around a first stator tooth 131, and the B-phase stator assembly 112 includes a B-phase winding wound around a second stator tooth 132, a C-phase stator assembly 113 includes a C-phase winding wound around the third stator tooth 133, so that each stator assembly is provided with the same phase winding, and a multi-phase winding is provided with respect to the stator of the conventional switched reluctance motor, due to the turns ratio of the same phase winding Since the number of turns of the multi-phase winding is small, the number of turns of the A-phase winding, the B-phase winding, and the C-phase winding can be reduced, thereby reducing the copper loss of the switched reluctance motor 10 and reducing the cost.
  • the number and width of the stator teeth of the at least three stator assemblies are the same, specifically, the plurality of first The number of stator teeth 131, the number of the plurality of second stator teeth 132, and the number of the plurality of third stator teeth 133 are the same, and the width of the first stator teeth 131, the width of the second stator teeth 132, and the third stator teeth 133 The width is the same. Therefore, the machining processes of the A-phase stator assembly 111, the B-phase stator assembly 112, and the C-phase stator assembly 113 are the same.
  • the preset angle may be T1/N, where T1 is the electrical angular period of the stator teeth and N is the number of at least three stator assemblies.
  • the electrical angle period of the stator teeth is 2 ⁇ /M, where M is the number of stator teeth, that is, the angle at which the stator teeth of the at least three stator assemblies are sequentially displaced along the circumferential direction of the stator 11 is a mechanical angle.
  • the predetermined angle at which the second stator teeth 132 and the first stator teeth 131 are offset is T1/N, wherein the angular period T1 of the first stator teeth 131 is 2 ⁇ /M, and N is 3, so The angle between the two stator teeth 132 and the first stator teeth 131 is 2 ⁇ /3M.
  • the second stator teeth 132 and the first stator teeth 131 are offset by 1/3 pitch, which is equivalent to the second stator teeth 132 and the first stator.
  • the sub-tooth 131 is offset by an electrical angle of 120°, which may be the distance between two adjacent first stator teeth 131.
  • the predetermined angle at which the third stator teeth 133 and the second stator teeth 132 are staggered is 2 ⁇ /3M, that is, the third stator teeth 133 and the second stator teeth 132 are offset by 1/3 pitch.
  • the predetermined angle at which the first stator tooth 131 and the third stator tooth 133 are staggered is 2 ⁇ /3M, that is, the first stator tooth 131 and the third stator tooth 133 are offset by 1/3 pitch.
  • the rotor 12 includes a plurality of rotor teeth 121 periodically disposed in the circumferential direction of the rotor 12 and spaced apart from each other by the rotor slots 122, that is, a plurality of rotor teeth 121 are periodically disposed along the circumferential direction of the rotor 12, and The plurality of rotor slots 122 are spaced apart from each other.
  • the number of rotor teeth 121 is the same as the number of stator teeth, and the width of the rotor teeth 121 is smaller than the width of the stator slots.
  • the rotor 12 of the present embodiment may be integrally provided.
  • the length of the rotor 12 along the axial direction is greater than or equal to the length of the stator 11 along the axial direction.
  • the length of the stator 11 along the axial direction may be the axial direction of the A-phase stator assembly 111.
  • the length, the length of the B-phase stator assembly 112 along the axial direction, and the length of the C-phase stator assembly 113 along the axial direction to enable the rotor 12 to cover the A-phase stator assembly 111, the B-phase stator assembly 112, and the C-phase stator Component 113.
  • the rotor 12 may be arranged in segments, for example, the rotor is arranged in three segments corresponding to the A-phase stator assembly, the B-phase stator assembly, and the C-phase stator assembly, and the rotor teeth of the three-stage rotor are axially aligned.
  • the number of the rotor teeth 121 is the same as the number of the first stator teeth 131, the number of the second stator teeth 132, and the number of the third stator teeth 133, respectively, at the center of the rotor teeth 121 and the first stator teeth 131. When the centers coincide, as shown in Figure 7.
  • FIG. 7 is a view showing the magnetic lines of force of the switched reluctance motor when the 16 first stator teeth 131 and the 16 rotor teeth 121 of the switched reluctance motor are aligned, and the magnetic field of the switched reluctance motor is represented by a magnetic line of force T. Since the stator 11 is provided with the A-phase stator assembly 111, the B-phase stator assembly 112, and the C-phase stator assembly 113 in sections, the magnetic lines of the T-phase windings generated by the A-phase windings 137 and the magnetic lines generated by the C-phase windings do not interfere with each other.
  • the mutual inductance of the A-phase winding 137, the B-phase winding, and the C-phase winding is zero.
  • the magnetic field lines T generated by the A-phase windings 137 are not entangled, so that the magnetic lines of force T generated by each magnetic pole of the A-phase windings 137 are located within the pole pitch of the magnetic poles, that is, the magnetic lines of force T generated by each magnetic pole of the A-phase windings are not Crossing the center line of adjacent magnetic poles, the three-phase windings of the conventional reluctance motor have mutual inductance, the currents of the energized phases may interact with each other, the nonlinearity of the armature reaction is very serious, and the principle torque ripple that is difficult to overcome is generated, and the present invention provides Since the switched reluctance motor is independent of each stator assembly, the windings of each stator assembly are the same phase winding, so there is no mutual inductance, so the torque fluctuation caused by the mutual inductance is
  • a three-phase winding is disposed relative to a stator component of a conventional three-phase switched reluctance motor, and a magnetic line generated by each magnetic pole must span three pole pitches, that is, a magnetic line loop generated by any magnetic pole of a conventional three-phase switched reluctance motor.
  • the length of the magnetic flux loop generated by each magnetic pole of the embodiment is three times, the magnetic resistance is large, and the maximum inductance generated by the winding is small, but the magnetic flux T generated by each magnetic pole of the embodiment is constrained to the magnetic pole.
  • the magnetic resistance is small, and the inductance generated by the A-phase winding 137 is large.
  • the magnetic line circuit generated when the B-phase winding and the C-phase winding are applied with the driving current is the same as the magnetic line T circuit generated when the A-phase winding is applied with the driving current, and will not be described again.
  • the traditional three-phase switched reluctance motor can use the stator tooth number Zd and the rotor tooth number Zz full Foot: Zz/Zd can be 4/6 or 8/6; and integer multiples 8/12, 6/12, 12/18, 24/18, 16/24 and 32/24, etc., according to the above formula
  • the coefficients are all 0.866. That is, since the three phases of the conventional three-phase switched reluctance motor are distributed along the circumference by 120°, the winding coefficient is 0.866.
  • the number of stator teeth Zd and the number of teeth Zz of the switched reluctance motor 10 of the present embodiment are equal, and the winding coefficient is 1 according to the above formula.
  • the switched reluctance motor 10 of the present embodiment belongs to a full-range and integer-slot motor having a pole angle of 180°, and the winding system of the switched reluctance motor 10 is 1, compared with the conventional three-phase switched reluctance motor.
  • the winding coefficient is 0.866, and the utilization ratio of the winding of the present embodiment is increased by 1.155 times, thereby maximizing the utilization of the winding, thereby improving the efficiency of the switched reluctance motor 10 and the torque of the output.
  • the present invention provides a switched reluctance motor of a second embodiment for setting a cogging parameter of a switched reluctance motor, which is described on the basis of the switched reluctance motor of the first embodiment.
  • the ratio of the width of the stator slot to the width of the stator teeth in this embodiment is 1:0.95-0.85, and the ratio of the width of the stator teeth to the width of the rotor teeth is 1:1.05-0.95.
  • the width ratio of the width of the first stator slot 134 to the width of the first stator teeth 131 may be 1:0.95-0.85, that is, the first The width of the stator teeth 131 is smaller than the width of the first stator slot 134, thereby ensuring that the first stator slot 134 has sufficient space to provide the A-phase winding 137.
  • the ratio of the width of the first stator slot 134 to the width of the first stator teeth 131 may be 1:0.85; the ratio of the width of the first stator slot 134 to the width of the first stator teeth 131 may be 1:0.9; The ratio of the width of the first stator slot 134 to the width of the first stator teeth 131 may be 1:0.95.
  • the ratio of the width of the second stator slot 135 to the second stator teeth 132 may be 1:0.95-0.85
  • the ratio of the width of the third stator slot 136 to the third stator teeth 133 may be 1:0.95-0.85.
  • the ratio of the width of the first stator teeth 131 to the width of the rotor teeth 121 is 1:1.05-0.95.
  • the ratio of the width of the first stator teeth 131 to the width of the rotor teeth 121 may be 1:1, that is, the width of the rotor teeth 121 is the same as the width of the first stator teeth 131, and the width of the stator teeth and the width of the rotor teeth 121. the same.
  • the ratio of the width of the first stator teeth 131 to the width of the rotor teeth 121 may be 1:0.95, that is, the width of the rotor teeth 121 is smaller than the width of the first stator teeth 131; the width of the first stator teeth 131 and the width of the rotor teeth 121
  • the width ratio may be 1:1.05, that is, the width of the rotor teeth 121 is larger than the width of the first stator teeth 131, and the width of the rotor teeth 121 is smaller than The width of the first stator slot 134.
  • the ratio of the width of the second stator teeth 132 to the width of the rotor teeth 121 is 1:1.05-0.95
  • the ratio of the width of the third stator teeth to the width of the rotor teeth 121 is 1:1.05-0.95.
  • the ratio of the width of the stator slot is 1:0.95-0.85, the ratio of the width of the stator teeth to the width of the rotor teeth is 1:1.05-0.95, which can make the inductance curve of the switched reluctance motor
  • the position of the rotor teeth changes in a triangular shape as shown in Fig. 10, and the rate of change of the inductance curve is large.
  • the air gap between the rotor 12 and the stator 11 may be 0.1 mm to 3 mm, and the difference between the width of the stator slot and the width of the rotor teeth 121 is 8-12 times that of the air gap, wherein the width of the stator slot is the stator slot
  • the slot width, the width of the rotor teeth 121 is the width of the top of the rotor teeth 121. That is, the difference between the width of the first stator slot 134 and the width of the rotor teeth 121 is 8-12 times the air gap, and the difference between the width of the second stator slot 135 and the width of the rotor teeth 121 is 8-12 of the air gap.
  • the difference between the width of the third stator slot 134 and the width of the rotor teeth 121 is 8-12 times the air gap.
  • the air gap between the rotor 12 and the stator 11 is 0.15 mm to 2 mm, and the difference between the width of the stator slot and the width of the rotor teeth 121 may be 10 times that of the air gap, that is, the width of the stator slot is larger than that of the rotor teeth 121.
  • the width is 1.5mm-20mm.
  • the width of the first stator slot 134, the width of the second stator slot 135, and the width of the third stator slot 134 are both greater than the width of the rotor teeth 121 by 1.5 mm to 20 mm.
  • the air gap disclosed in the present embodiment may be 1 mm, in which case the width of the stator slot is 10 mm larger than the width of the rotor tooth 121.
  • FIG. 9 is a measurement of the magnetic lines of force of the switched reluctance motor when the positions of the 16 first stator teeth 131 and the 16 rotor teeth 121 of the switched reluctance motor are staggered.
  • the first stator slot 134 has not been
  • the rotor teeth 121 are perfectly aligned, and since the gap between the first stator slots 134 and the rotor teeth 121 is large, for example, the width of the first stator slots 134 is 10 mm larger than the width of the rotor teeth 121.
  • the magnetic lines of force T do not entangle and cross, and are subjected to the pressing action of the adjacent magnetic lines of force, the magnetic lines of force T can only form a closed loop through the gap between the current first stator slot 134 and the rotor teeth 121, and the gap is very large. Therefore, the magnetic resistance is large, resulting in a small inductance generated by the A-phase winding 137.
  • the inductance is extremely small, and the magnetic force line T cannot be detected.
  • the inductance curve of the A-phase stator assembly is as shown in FIG. 10, and the inductance curve changes in a triangular waveform.
  • the inductance generated by the A-phase winding is the smallest; at the center of the rotor tooth 121 and the center of the first stator tooth 131 Coincidence, that is, corresponding to the second electrical angle a2, the inductance of the A-phase winding is the largest, and the inductance ratio can reach 21.25, while the inductance ratio of the conventional three-phase switched reluctance motor can only reach 2.5-4.5.
  • Output torque of switched reluctance motor Inductance ratio means high Large, the output torque of the motor is large, which increases the power density of the motor.
  • the number of stator teeth of this embodiment may be an odd number, that is, the total number of first stator teeth 131 and first stator slots 134 is 2N, where N is a natural number. Therefore, the number of first stator teeth 131 and the number of first stator slots 134 can be odd, and natural resonance of the tooth harmonics can be avoided.
  • the number of first stator teeth 131 is three, and the first stator slot 134 The number is 3.
  • the switched reluctance motor of the embodiment can select the number of the first stator teeth 131 and the first stator slot 134 according to different rotational speeds and different torques. The quantity can adapt to different occasions and improve the practicability of the switched reluctance motor.
  • the present invention provides a switched reluctance motor of a third embodiment, which is described on the basis of the switched reluctance motor of the second embodiment.
  • the tooth tip of the rotor tooth 121 in this embodiment is provided with a chamfer 123, and the chamfer 123 may be an arc chamfer having a depth D of less than 0.8 mm and a length L of the chamfer 123. It is smaller than the width of the rotor tooth 121; specifically, the length L of the chamfer 123 is smaller than 1/3 of the width of the rotor tooth 121, and the noise of the motor can be greatly reduced.
  • the tip of the rotor tooth 121 can also be configured as a chamfer with a radius of chamfer less than 1 mm.
  • the tip structure of the first stator tooth 131, the second stator tooth 132, and the third stator tooth of the present embodiment is the same as the tip structure of the rotor tooth 121, and will not be described again.
  • the present invention provides a switched reluctance motor of a fourth embodiment, which is described on the basis of the switched reluctance motor of the first embodiment.
  • the switched reluctance motor further includes a switch drive circuit 21 connected to the DC power source Us and the windings of at least three stator components, that is, the switch drive circuit 21 is connected to the DC power source Us, the A phase winding, and B. Phase winding and phase C winding.
  • the switch driving circuit 21 is configured to periodically apply driving currents to the driving phase windings corresponding to the at least three stator components, and the phases of the driving periods of the at least three stator components are shifted from each other, that is, in the driving phase of the A-phase stator assembly 111.
  • the switch drive circuit 21 applies drive power to the A-phase stator assembly 111. Flow; in the drive phase of the B-phase stator assembly 112, the switch drive circuit 21 applies a drive current to the B-phase stator assembly 112; during the drive phase of the C-phase stator assembly 113, the switch drive circuit 21 applies a drive current to the C-phase stator assembly 113. Accordingly, the phases of the driving periods of the A-phase stator assembly 111, the B-phase stator assembly 112, and the C-phase stator assembly 113 are shifted from each other.
  • the switch drive circuit 21 further releases the energy stored on the windings of the at least three stator assemblies during a subsequent freewheeling period of the drive period corresponding to the at least three stator assemblies to form a freewheeling current. That is, in the freewheeling period subsequent to the driving period of the A-phase stator assembly 111, the switch driving circuit 21 is for releasing the energy stored in the A-phase winding to form a freewheeling current of the A-phase winding; after the driving period of the B-phase stator assembly 112 The freewheeling period, the switch drive circuit 21 is for releasing the energy stored on the B-phase winding to form a freewheeling current of the B-phase winding; and during the subsequent freewheeling period of the driving period of the C-phase stator assembly 113, the switch drive circuit 21 is used for The energy stored on the Phase C winding is released to form a freewheeling current of the Phase C winding.
  • the switch drive circuit 21 includes a controller 23 and at least three switch modules respectively corresponding to at least three stator assemblies, each switch module including a first switch tube, a second switch tube, a first freewheeling diode, and a second freewheeling a diode, wherein a first connection end of the first switch tube is connected to the positive pole of the power source, a second connection end of the first switch tube is connected to the first end of the winding of the corresponding stator assembly, and the first connection end of the second switch tube is connected to the corresponding a second end of the winding of the stator assembly, a second connection end of the second switch tube is connected to the negative pole of the power supply, a positive end of the first freewheeling diode is connected to a second end of the winding of the corresponding stator assembly, and a negative connection of the first freewheeling diode
  • the anode of the power source, the anode of the second freewheeling diode is connected to the cathode of the power supply, and the ca
  • the switch drive circuit 21 includes a controller 23, a first switch module 24 corresponding to the A-phase stator assembly 111, a second switch module 25 corresponding to the B-phase stator assembly 112, and a third corresponding to the C-phase stator assembly 113.
  • the first switch module 24 includes a first switch tube V1, a second switch tube V2, a first freewheeling diode D1, and a second freewheeling diode D2.
  • the second switch module 25 includes a first switch tube V3 and a second switch tube V4.
  • the first freewheeling diode D3 and the second freewheeling diode D4, the third switching module 26 includes a first switching transistor V5, a second switching transistor V6, a first freewheeling diode D5 and a second freewheeling diode D6.
  • phase difference of the driving period corresponding to the at least three stator components is 2 ⁇ /N, where N is The number of at least three stator components.
  • the phase difference between the driving period of the A-phase stator assembly 111 and the driving period of the B-phase stator assembly 112 is 2 ⁇ /3, that is, the electrical angle 120°, the driving period of the B-phase stator assembly 112 and the phase of the driving period of the C-phase stator assembly 113.
  • the difference is an electrical angle of 120°.
  • the driving period of the phase A stator assembly 111 of the present embodiment is an electrical angle of 0°-120°, and the freewheeling period of the phase A stator assembly 111 is an electrical angle of 120°-180°; the phase B stator assembly 112
  • the driving period is an electrical angle of 120°-240°
  • the freewheeling period of the B-phase stator assembly 112 is an electrical angle of 240°-300°
  • the driving period of the C-phase stator assembly 113 is an electrical angle of 240°-360°, the C-phase stator assembly.
  • the freewheeling period of 113 is an electrical angle of 360°-420°.
  • the freewheeling period of each stator assembly at least partially overlaps with the phase of the driving period of the next driven stator assembly, that is, the phase of the freewheeling period of the A-phase stator assembly 111 and the driving period of the B-phase stator assembly 112 partially overlaps 120°-180°, the freewheeling period of the B-phase stator assembly 112 partially overlaps with the phase of the driving period of the C-phase stator assembly 113 by 240°-300°.
  • the controller 23 simultaneously controls the first switching transistor and the second switching transistor to be intermittently turned on in a pulse width modulation manner, thereby adjusting the magnitude of the driving current.
  • the pulse width modulation mode may be a PWM (Pulse Width Modulation) signal.
  • the controller 23 simultaneously controls the first switching transistor V1 and the second switching transistor V2 through the PWM signal. Pass or close.
  • the controller 23 sends a PWM signal to the first switching transistor V1 and the second switching transistor V2 when the inductance generated by the A-phase winding is minimum; when the first switching transistor V1 and the second switching transistor V2 are simultaneously turned on, the DC power source Us is at A
  • the phase stator assembly 111 applies a drive current; when the first switch tube V1 and the second switch tube V2 are simultaneously turned off, the DC power source Us stops applying a drive current to the A-phase stator assembly 111, thereby avoiding excessive drive current.
  • the controller 23 stops transmitting the PWM signal to the first switching transistor V1 when the inductance generated by the A-phase winding is maximum, the first switching transistor V1 is turned off, and the A-phase stator assembly 111 enters the freewheeling period.
  • the pulse width modulation method may employ a sine wave signal.
  • the controller 23 controls the first switching tube to continuously turn off, and controls the second switching tube to be intermittently turned on in a pulse width modulation manner, thereby adjusting the magnitude of the freewheeling current.
  • the controller 23 can control the DC power supply Us to stop working, and the A-phase winding, the second switch V2, and the second freewheeling diode D2 form a loop, thereby releasing the energy stored in the A-phase winding. .
  • the controller 23 controls the second switch tube to be intermittently turned on by the PWM signal to adjust the large freewheeling current of the A phase winding. small.
  • the switched reluctance motor further includes a current detecting circuit 27 connected to the switch drive circuit 21 for detecting the sum of currents flowing through the windings of at least three stator assemblies, that is, the current detecting circuit 27 Used to detect the sum of currents flowing through the A-phase winding, the B-phase winding, and the C-phase winding.
  • the current detecting circuit 27 includes an annular core 271 having an opening and a magnetic field sensor 272, and windings of at least three stator assemblies are respectively wound around the toroidal core 271, and the magnetic field sensor 272 is disposed at the opening of the toroidal core 271.
  • the annular core 271 may be a C-shaped iron core, and the A-phase winding, the B-phase winding, and the C-phase winding are respectively wound around the toroidal core 271 to form a coil L1, a coil L2 and a coil on the toroidal core 271, respectively. L3.
  • the windings of the respective stator assemblies are wound on the toroidal core 271 in the same number of turns, that is, the number of turns of the coil L1, the number of turns of the coil L2, and the number of turns of the coil L3.
  • the magnetic field sensor 272 can be a linear Hall current sensor.
  • the switched reluctance motor of the present embodiment requires only one magnetic field sensor 272 to detect the sum of currents flowing through the A-phase winding, the B-phase winding, and the C-phase winding, thereby reducing the number of sensors and reducing the cost of the switched reluctance motor.
  • the current sensing circuit 27 can be configured to employ a magnetically balanced current sensor.
  • the switch drive circuit 21 controls the drive current and the freewheeling current of each winding according to the sum i of the currents detected by the current detecting circuit 27, so that the sum of the currents maintains the preset range. Specifically, the switch drive circuit 21 controls the drive current and the freewheeling current of the A-phase winding, the drive current and the freewheeling current of the B-phase winding, the drive current of the C-phase winding, and the freewheeling current according to the current sum i, respectively, so that The sum of currents i remains stable.
  • the controller 23 simultaneously controls the first switching transistor V3 and the second switching transistor V4 to be turned on or off according to the sum of the currents detected by the current detecting circuit 27 through the PWM signal, to the DC power source Us in the B phase.
  • the stator assembly 112 applies a drive current and the sum of currents i remains stable, as shown in FIG.
  • the switch drive circuit 21 of the present embodiment controls the drive current and the freewheeling current of each winding according to the sum i of the currents detected by the current detecting circuit 27, so that the sum of the currents maintains the preset range, so the switched reluctance motor of the present embodiment It has the characteristics of servo motor; since the output torque of the switched reluctance motor is stable, the torque ripple and noise of the switched reluctance motor are reduced.
  • the present invention provides a switched reluctance motor of a fifth embodiment, which is different from the switched reluctance motor of the fourth embodiment in that, as shown in FIG. 15, the controller 23 controls the first switch to be continuously turned on, and is pulsed.
  • the wide modulation mode controls the intermittent conduction of the second switching transistor, thereby adjusting the magnitude of the driving current. That is, during the driving period of the A-phase stator assembly 111, the controller 23 controls the first switch V1 to be continuously turned on, and controls the second switching transistor V2 to be intermittently turned on by the PWM signal.
  • the present invention provides a switched reluctance motor according to a fifth embodiment, which is described on the basis of the switched reluctance motor of the fourth embodiment: as shown in FIG. 16, the switched reluctance motor further includes a position connected to the switch drive circuit 21.
  • the sensor 28, the position sensor 28 is for measuring the relative position between the rotor 12 and the stator 11 in the switched reluctance motor 10, so that the switch drive circuit 21 changes the energization state according to the relative position between the rotor 12 and the stator 11, that is, the switch drive Circuit 21 changes the energization state based on the maximum inductance and minimum inductance of each stator assembly to drive the switched reluctance motor to operate.
  • the position sensor 28 includes a magnetic encoder or an optical encoder.
  • the present invention provides a method of controlling current of a switched reluctance motor according to an embodiment.
  • the control method of the present embodiment is described on the basis of the switched reluctance motor disclosed in the fourth embodiment. As shown in FIG. 17, the control method includes:
  • the first switch tube and the second switch tube are simultaneously controlled to be intermittently turned on by the controller 23 in a pulse width modulation manner; or the first switch tube is continuously turned on, and the second switch is controlled in a pulse width modulation manner.
  • the switch tube is intermittently turned on to adjust the driving current of the winding;
  • step S161 the driver corresponding to the at least three stator components is further controlled by the controller 23
  • the phase difference of the active period is 2 ⁇ /N, where N is the number of at least three stator components. That is, the phase difference between the driving period of the A-phase stator assembly 111 and the driving period of the B-phase stator assembly 112 is 2 ⁇ /3, that is, the electrical angle is 120°, the driving period of the B-phase stator assembly 112 and the driving period of the C-phase stator assembly 113.
  • the phase difference is an electrical angle of 120°.
  • the overlap is ⁇ /N electrical angle. That is, the phase of the freewheeling period of the A-phase stator assembly 111 and the phase of the driving period of the B-phase stator assembly 112 partially overlap to 120°-180°, and the phase of the freewheeling period of the B-phase stator assembly 112 and the driving period of the C-phase stator assembly 113 Partial overlap is 240°-300°, as shown in Figure 13.
  • the first switching transistor V1 and the second switching transistor V2 are simultaneously turned on or off by the controller 23 in a pulse width modulation manner. That is, the controller 23 sends a PWM signal to the first switching transistor V1 and the second switching transistor V2 when the inductance generated by the A-phase winding is minimum; when the first switching transistor V1 and the second switching transistor V2 are simultaneously turned on, the DC power source Us The driving current is applied to the A-phase stator assembly 111; when the first switching transistor V1 and the second switching transistor V2 are simultaneously turned off, the DC power source Us stops applying a driving current to the A-phase stator assembly 111, and the driving current can be prevented from being excessive.
  • the controller 23 stops transmitting the PWM signal to the first switching transistor V1, the first switching transistor V1 is turned off, and the A-phase stator assembly 111 enters the freewheeling period, and proceeds to step S162.
  • step S162 during the freewheeling period of the A-phase stator assembly 111, the DC power supply Us is controlled to stop by the controller 23, and the first switching transistor V1 is controlled to be continuously turned off, and the second switching transistor V2 is controlled in a pulse width modulation manner. Intermittent conduction, so that the phase A winding, the second switch V2 and the second freewheeling diode D2 form a loop, thereby releasing the energy stored in the phase A winding to adjust the magnitude of the freewheeling current of the phase A winding.
  • the first switching transistor V3 and the second switching transistor V4 of the B winding are controlled to be turned on or off by the controller 23, and the driving current is applied to the B-phase stator assembly 112 by the DC power source Us, wherein the control mode is controlled by the control mode of step S161.
  • the first switch tube V3 and the second switch tube V4 of the winding are not described herein.
  • step S163 the current sum i is obtained from the current detecting circuit 27 through the switch drive circuit 21, And the drive current and the freewheeling current are controlled according to the current sum i such that the current sum i is maintained at a preset range.
  • the method for controlling the driving current may adopt step S161
  • the method for controlling the freewheeling current may adopt step S162.
  • the pulse width modulation method of this embodiment may be square wave pulse width modulation or sine wave pulse width modulation.
  • the PWM signal of the above embodiment is square wave pulse width modulation.
  • the A-phase winding generates the smallest inductance, specifically when the rotor teeth 121 are completely aligned with the first stator slot 134; the A-phase winding generates the largest inductance, specifically the rotor teeth 121 and the first stator teeth. When 131 is fully aligned.
  • the freewheeling current of the A-phase winding starts to become smaller, the magnetic field generated by the A-phase winding becomes weaker, and the noise is small; since the current sum i maintains the preset range, The torque outputted by the switched reluctance motor is stable, and the torque ripple is small.
  • the present invention also provides a wheel that is driven by a switched reluctance motor that is a switched reluctance motor as described in the previous embodiment.
  • the wheel may comprise a hub-type switched reluctance motor, that is, driven by a hub-type switched reluctance motor, which is a motor structure of the stator in the outer rotor.
  • the present invention also provides an electric vehicle, which may be an electric vehicle, an electric motorcycle, or an electric bicycle.
  • the electric vehicle is a pure electric or hybrid vehicle, and the wheels of the electric vehicle are driven by a switched reluctance motor, which is also a switched reluctance motor as described in the previous embodiment.
  • the driving wheel of the electric vehicle can adopt the wheel structure in the above embodiment, that is, the wheel includes a hub-type switched reluctance motor, and the wheel-type switched reluctance motor drives the wheel to rotate.
  • the application scenario of the switched reluctance motor provided by the embodiment of the present invention is not limited to an electric vehicle, and can also be used as a driving motor for a ship or a large machine.

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Abstract

一种电动车、车轮及其开关磁阻电机（10），该开关磁阻电机（10）包括定子（11）以及转子（12），其中所述定子（11）沿轴向分段设置有至少三个定子组件（111、112、113），每一所述定子组件（111、112、113）分别包括沿所述定子（11）的周向周期性设置且由定子槽（134、135、136）彼此间隔的多个定子齿（131、132、133）以及绕设于所述定子齿（131、132、133）上的绕组，所述至少三个定子组件（111、112、113）的定子齿（131、132、133）沿所述定子（11）的周向依次错开预定角度，每个所述定子组件（111、112、113）中的所述绕组均为同一相绕组，所述转子（12）包括沿所述转子（12）的周向周期性设置且由转子槽（122）彼此间隔的多个转子齿（121），其中所述转子齿（121）的数量与所述定子齿（131、132、133）的数量相同，且所述转子齿（121）的宽度小于所述定子槽（134、135、136）的宽度。该开关磁阻电机（10）能够提高电机的输出转矩，进而提高开关磁阻电机（10）的效率和力矩，并且绕组利用率最大化。

Description

电动车、车轮及其开关磁阻电机 【技术领域】
本发明涉及电机的技术领域，涉及一种电动车、车轮及其开关磁阻电机。
【背景技术】
发明人在实践中发现，传统的开关磁阻电机存在多种缺陷：1、电机转矩波动大，例如在12/8三相开关磁阻电机中，三相开关磁阻电机的定子组件则需要设置三相绕组，每相绕组所产生的磁力线必须跨越3个极距，如图1所示，由于三相绕组的磁力线相互干扰，绕组之间的互感严重，导致电机转矩波动较大；2、传统的开关磁阻电机的输出转矩较小，导致开关磁阻电机的效率低；3、传统的开关磁阻电机，一般的绕组利用率仅为0.866。
【发明内容】
为了解决现有技术中的开关磁阻电机存在的上述问题，本发明提供一种新型的开关磁阻电机，以及利用该开关磁阻电机的车轮和电动车。
为解决上述问题，本发明实施例提供了一种开关磁阻电机，其包括定子以及转子，其中所述定子沿轴向分段设置有至少三个定子组件，每一所述定子组件分别包括沿所述定子的周向周期性设置且由定子槽彼此间隔的多个定子齿以及绕设于所述定子齿上的绕组，所述至少三个定子组件的定子齿沿所述定子的周向依次错开预定角度，每个所述定子组件中的所述绕组均为同一相绕组，所述转子包括沿所述转子的周向周期性设置且由转子槽彼此间隔的多个转子齿，其中所述转子齿的数量与所述定子齿的数量相同，且所述转子齿的宽度小于所述定子槽的宽度。
其中，所述定子槽与所述定子齿的宽度比为1∶0.95-0.85，所述定子齿与所述转子齿的宽度比为1∶1.05-0.95。所述定子槽与所述定子齿的宽度比为1∶0.95-0.85，所述定子齿与所述转子齿的宽度比为1∶1.05-0.95。
其中，所述定子齿的数量为奇数。
其中，所述至少三个定子组件的定子齿的数量和宽度相同，所述预定角度为T1/N，其中所述T1为所述定子齿的电角度周期，所述N为所述至少三个定子组件的数量。
其中，N为3或3的整数倍，所述定子齿的电角度周期T1为2π/M，其中M为定子齿的数量。
其中，所述开关磁阻电机进一步包括开关驱动电路，所述开关驱动电路连接直流电源和所述至少三个定子组件的所述绕组上，以周期性控制所述直流电源依次在所述至少三个定子组件所对应的驱动时段向所述绕组上施加所述驱动电流，其中所述至少三个定子组件的所述驱动时段的相位彼此错开。
其中，所述开关驱动电路进一步在所述至少三个定子组件所对应的驱动时段后续的续流时段释放所述至少三个定子组件的所述绕组上存储的电能，以形成续流电流。
其中，所述至少三个定子组件所对应的所述驱动时段的相位差为2π/N，其中所述N为所述至少三个定子组件的数量。
其中，各所述定子组件的续流时段与下一被驱动的所述定子组件的驱动时段的相位至少部分重叠。
其中，各所述定子组件的续流时段与下一所述定子组件的驱动时段的相位重叠为π/N。
其中，所述开关驱动电路分别以脉宽调制方式对所述驱动电流和所述续流电流的大小进行调节。
其中，所述开关磁阻电机进一步包括电流检测电路，其中所述电流检测电路用于检测流经所述至少三个定子组件的所述绕组的电流总和，所述开关驱动电路根据所述电流检测电路所检测的所述电流总和分别对各所述绕组的所述驱动电流和所述续流电流进行控制，以使得所述电流总和保持预设范围。
其中，所述电流检测电路包括具有一开口的环形铁芯以及磁场传感器，所述至少三个定子组件的所述绕组进一步分别绕设于所述环形铁芯上，所述磁场传感器设置于所述环形铁芯的开口处。
其中，各所述定子组件的所述绕组在所述环形铁芯上绕设的匝数相同。
其中，所述磁场传感器为线性霍尔电流传感器。
其中，所述开关磁阻电机进一步包括与所述开关驱动电路连接的位置传感器，所述位置传感器用于测量所述定子和所述转子的相对位置，所述位置传感器包括磁编码器或者光编码器。
为解决上述技术问题，本发还提供一种车轮，车轮采用轮毂电机驱动，所述轮毂电机采用上述实施例中任一项所述开关磁阻电机结构。
为解决上述技术问题，本发还提供一种电动车，所述电动车为纯电动或混合动力车，所述电动车采用上述实施例中任一项所述开关磁阻电机结构。
与现有技术相比，本发明实施例提供的该开关磁阻电机具有以下优点：通过定子沿轴向分段设置有至少三个定子组件，每个定子组件设置有多个定子齿和绕设于定子齿上的绕组，至少三个定子组件的定子齿沿定子的周向依次错开预定角度，每个定子组件中的绕组均为同一相绕组，并且转子齿的宽度小于定子槽的宽度；由于每个定子组件中的绕组均为同一相绕组，因此至少三个定子组件的绕组所产生的磁力线互不干扰，克服了绕组互感问题，进而解决了因互感造成的转矩波动问题；由于每个定子组件中的绕组均为同一相绕组，绕组产生的磁场仅跨越一个极距，磁阻大幅减小，绕组产生的最大电感较大，此外转子齿的宽度小于定子槽的宽度，因此当转子齿与定子槽相对时，产生的电感极小，即绕组产生的最小电感极小，从而提高电机的输出转矩，进而提高开关磁阻电机的效率和力矩；另外由于定子齿和转子齿的数量相同，使得绕组利用率最大化。
【附图说明】
为了更清楚地说明本发明实施例中的技术方案，下面将对实施例描述中所需要采用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本发明的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其他的附图，也属于本发明保护范畴。其中：
图1是现有的开关磁阻电机的磁力线示意图；
图2是本发明第一实施例的开关磁阻电机的立体示意图；
图3是图2中开关磁阻电机的分解示意图；
图4是外定子内转子的三相开关磁阻电机的立体示意图；
图5是图2中A相绕组绕设在第一定子齿的结构示意图；
图6是图2中第一定子齿、第二定子齿和第三定子齿的结构示意图；
图7是图2中转子齿的中心与第一定子齿的中心重合的磁力线示意图；
图8是图2中第一定子齿与转子槽对齐的结构示意图；
图9是图2中转子齿与第一定子齿位置错开的磁力线示意图；
图10是图2中开关磁阻电机正常工作的电感曲线的示意图；
图11是开关磁阻电机的转子齿设有削角的结构示意图；
图12是开关驱动电路的电路图；
图13是开关磁阻电机的工作原理的时序图；
图14是电流检测电路的结构示意图；
图15是本发明第五实施例的开关磁阻电机的工作原理的时序图；
图16是位置传感器的结构示意图；
图17是本发明第一实施例的开关磁阻电机的电流的控制方法的流程图。
【具体实施方式】
下面结合附图和实施例，对本发明作进一步的详细描述。特别指出的是，以下实施例仅用于说明本发明，但不对本发明的范围进行限定。同样的，以下实施例仅为本发明的部分实施例而非全部实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其它实施例，都属于本发明保护的范围。
本发明的说明书和权利要求书及上述附图中的术语“第一”、“第二”、“第三”“第四”等(如果存在)是用于区别类似的对象，而不必用于描述特定的顺序或先后次序。应该理解这样使用的数据在适当情况下可以互换，以便这里描述的本发明的实施例例如能够以除了在这里图示或描述的那些以外的顺序实施。此外，术语“包括”和“具有”以及他们的任何变形，意图在于覆盖不排他的包含，例如，包含了一系列步骤或单元的过程、方法、系统、产品或设备不必限于清楚地列出的那些步骤或单元，而是可包括没有清楚地列出的或对于这些过程、方法、产品或设备固有的其它步骤或单元。
如图2-3所示，本发明提供第一实施例的开关磁阻电机，该开关磁阻电机10包括定子11和转子12，其中定子11沿轴向分段设置有至少三个定子组件，每一定子组件包括沿定子11的周向周期性设置且由定子槽彼此间隔的多个定子齿以及绕设在定子齿上的绕组，即多个定子齿沿着定子11的周向周期性设置，并且与多个定子槽彼此间隔。
举例来说，本实施例的开关磁阻电机具体可为三相开关磁阻电机，该三相开关磁阻电机可为外转子内定子的三相开关磁阻电机。如图3所示，定子11沿轴向分段设置有三个定子组件，分别为A相定子组件111、B相定子组件112和 C相定子组件113。在其他实施例中，开关磁阻电机可为外定子内转子的三相开关磁阻电机30，如图4所示。
如图3所示，A相定子组件111包括多个第一定子齿131，多个第一定子齿131与多个第一定子槽134彼此间隔。如图5所示，A相定子组件111进一步包括绕设在第一定子齿131上的A相绕组137，在A相绕组137施加驱动电流时，A相绕组137会产生磁极，进而形成磁场。
B相定子组件112包括多个第二定子齿132和绕设在第二定子齿132上的B相绕组，多个第二定子齿132与多个第二定子槽135彼此间隔；C相定子组件113包括多个第三定子齿133和绕设在第三定子齿133上的C相绕组，多个第三定子齿133与多个第三定子槽136彼此间隔。其中，B相绕组绕设在第二定子齿132上和C相绕组绕设在第三定子齿133上与A相绕组137绕设在第一定子齿131上的结构相同，不再赘述。
至少三个定子组件的定子齿沿着定子11的周向依次错开预设角度，以使得转子12能够在依次施加于至少三个定子组件的绕组上驱动电流所产生的磁场的作用下连续转动，即在至少三个定子组件的绕组上依次施加驱动电流，转子12在绕组所产生的磁场的作用下连续转动。具体地，第二定子齿132和第一定子齿131沿着定子的周向依次错开预设角度，第三定子齿133和第二定子齿132沿着定子的周向依次错开预设角度；当A相定子组件111、B相定子组件112和C相定子组件113依次施加驱动电流，在A相绕组137产生的磁场、B相绕组产生的磁场和C相绕组产生的磁场的作用下，转子12连续转动。
本实施例的A相定子组件111包括绕设在第一定子齿131上的A相绕组137，B相定子组件112包括绕设在第二定子齿132上的B相绕组，C相定子组件113包括绕设在第三定子齿133上的C相绕组，因此每个定子组件均设置同一相绕组，相对于传统的开关磁阻电机的定子设置多相绕组，由于同一相绕组的匝数比多相绕组的匝数少，因此能够减少A相绕组、B相绕组和C相绕组的匝数，进而降低开关磁阻电机10的铜耗，降低成本。
其中，至少三个定子组件的定子齿的数量和宽度相同，具体地，多个第一 定子齿131的数量、多个第二定子齿132的数量和多个第三定子齿133的数量相同，并且第一定子齿131的宽度、第二定子齿132的宽度和第三定子齿133的宽度相同。因此，A相定子组件111、B相定子组件112和C相定子组件113的加工工艺相同。
预设角度可为T1/N，其中T1为定子齿的电角度周期，N为至少三个定子组件的数量。该定子齿的电角度周期为2π/M，其中M为定子齿的数量，即该至少三个定子组件的定子齿沿着定子11的周向依次错开的角度为机械角度。
如图6所示，第二定子齿132和第一定子齿131错开的预设角度为T1/N，其中第一定子齿131的角度周期T1为2π/M，N为3，因此第二定子齿132和第一定子齿131错开的角度为2π/3M。例如，第一定子齿131的数量M为6，则第二定子齿132和第一定子齿131错开的预设角度为2π/3M＝20°。由于相邻的两个第一定子齿131之间为一个角度周期，因此第二定子齿132和第一定子齿131错开1/3齿距，相当于第二定子齿132和第一定子齿131错开的电角度为120°，该齿距可为相邻两个第一定子齿131的距离。
此外，第三定子齿133和第二定子齿132错开的预设角度为2π/3M，即第三定子齿133和第二定子齿132错开1/3齿距。第一定子齿131和第三定子齿133错开的预设角度为2π/3M，即第一定子齿131和第三定子齿133错开1/3齿距。
如图3所示，转子12包括沿转子12的周向周期性设置且由转子槽122彼此间隔的多个转子齿121，即多个转子齿121沿着转子12的周向周期性设置，并且与多个转子槽122彼此间隔。转子齿121的数量与定子齿的数量相同，并且转子齿121的宽度小于定子槽的宽度。
本实施的转子12可采用一体设置，转子12沿着轴向的长度大于或者等于定子11沿着轴向的长度，该定子11沿着轴向的长度可为A相定子组件111沿着轴向的长度、B相定子组件112沿着轴向的长度以及C相定子组件113沿着轴向的长度之和，以使转子12能够覆盖A相定子组件111、B相定子组件112和C相定子组件113。
在其他实施例中，转子12可以采用分段设置，例如转子与A相定子组件、B相定子组件和C相定子组件对应设置为三段，三段转子的转子齿沿轴向对齐。
其中，转子齿121的数量分别与第一定子齿131的数量、第二定子齿132的数量和第三定子齿133的数量均相同，在转子齿121的中心与第一定子齿131的中心重合时，如图7所示。
图7是在开关磁阻电机的16个第一定子齿131和16个转子齿121对齐时测量开关磁阻电机的磁力线，该开关磁阻电机的磁场通过磁力线T来表示。由于定子11分段设置A相定子组件111、B相定子组件112和C相定子组件113，因此A相绕组137产生的磁力线T、B相绕组产生的磁力线和C相绕组产生的磁力线互不干扰，即A相绕组137、B相绕组和C相绕组的互感为零。此外，A相绕组137产生的磁力线T不会纠缠交叉，因此A相绕组137的每磁极产生的磁力线T闭合回路位于该磁极的极距内，即A相绕组的每磁极产生的磁力线T不会跨越相邻磁极的中线，传统磁阻电机三相绕组存在互感，通电相的电流会产生互相影响，电枢反应的非线性非常严重，并且产生难以克服的原理性转矩波动，而本发明提供的开关磁阻电机由于每个定子组件是独立的，每个定子组件的绕组都是同一相绕组，所以不存在互感，因此从原理上克服了因互感造成的转矩波动。请参考图7，相对于传统的三相开关磁阻电机的定子组件设置三相绕组，每磁极产生的磁力线必须跨越3个极距，即传统三相开关磁阻电机的任何磁极产生的磁力线回路的长度都是本实施例的每磁极产生的磁力线回路的长度的3倍，磁阻较大，绕组产生的最大电感较小，但本实施例的每磁极产生的磁力线T被约束在该磁极的极距之内，磁阻小，进而A相绕组137产生的电感大。B相绕组和C相绕组在施加驱动电流时所产生的磁力线回路与A相绕组在施加驱动电流时所产生的磁力线T回路相同，不再赘述。
其中，开关磁阻电机的绕组系数的计算公式为：
Figure PCTCN2017100279-appb-000001
其中，传统的三相开关磁阻电机可以采用的定子齿数Zd和转子齿数Zz满 足：Zz/Zd可以为4/6或8/6；以及整数倍8/12、6/12、12/18、24/18、16/24和32/24等等，根据上述公式可得绕组系数均为0.866。也即由于传统的三相开关磁阻电机的三相沿圆周120°分布，导致绕组系数为0.866。而本实施例的开关磁阻电机10的定子齿数Zd和转子齿数Zz相等，根据上述公式可得绕组系数为1。
因此，本实施例的开关磁阻电机10属于极距为180°电角度的整距和整数槽电机，该开关磁阻电机10的绕组系统为1，相对于传统的三相开关磁阻电机的绕组系数为0.866，本实施例的绕组的利用率提高了1.155倍，实现绕组利用率最大化，进而提高开关磁阻电机10的效率和输出的力矩。
本发明提供第二实施例的开关磁阻电机，用于设置开关磁阻电机的齿槽参数，其在第一实施例的开关磁阻电机基础上进行描述。如图8所示，本实施例定子槽的宽度与定子齿的宽度比为1∶0.95-0.85，定子齿的宽度与转子齿的宽度比为1∶1.05-0.95。
以第一定子齿131和转子齿121为例进行说明，如图8所示，第一定子槽134的宽度与第一定子齿131的宽度比可为1∶0.95-0.85，即第一定子齿131的宽度小于第一定子槽134的宽度，进而保证第一定子槽134拥有足够的空间设置A相绕组137。例如：第一定子槽134的宽度与第一定子齿131的宽度比可为1∶0.85；第一定子槽134的宽度与第一定子齿131的宽度比可为1∶0.9；第一定子槽134的宽度与第一定子齿131的宽度比可为1∶0.95。相应地，第二定子槽135的宽度与第二定子齿132的比可为1∶0.95-0.85，第三定子槽136的宽度与第三定子齿133的比可为1∶0.95-0.85。
第一定子齿131的宽度与转子齿121的宽度比为1∶1.05-0.95。其中，第一定子齿131的宽度与转子齿121的宽度比可为1∶1，即转子齿121的宽度与第一定子齿131的宽度相同，定子齿的宽度与转子齿121的宽度相同。第一定子齿131的宽度与转子齿121的宽度比可为1∶0.95，即转子齿121的宽度小于第一定子齿131的宽度；第一定子齿131的宽度与转子齿121的宽度比可为1∶1.05，即转子齿121的宽度大于第一定子齿131的宽度，并且转子齿121的宽度小于 第一定子槽134的宽度。相应地，第二定子齿132的宽度与转子齿121的宽度比为1∶1.05-0.95，第三定子齿的宽度与转子齿121的宽度比为1∶1.05-0.95。
本实施例通过设置定子槽的宽度与定子齿的宽度比为1∶0.95-0.85，定子齿的宽度与转子齿的宽度比为1∶1.05-0.95，能够使得开关磁阻电机的电感曲线随着转子齿的位置呈三角波形变化，如图10所示，并且电感曲线的变化率大。
其中，转子12与定子11之间的气隙可为0.1mm～3mm，定子槽的宽度与转子齿121的宽度的差值为气隙的8-12倍，其中定子槽的宽度为定子槽的槽口宽度，转子齿121的宽度为转子齿121顶部的宽度。即第一定子槽134的宽度与转子齿121的宽度的差值为气隙的8-12倍，第二定子槽135的宽度与转子齿121的宽度的差值为气隙的8-12倍，第三定子槽134的宽度与转子齿121的宽度的差值为气隙的8-12倍。
更进一步，转子12和定子11之间的气隙为0.15mm～2mm，定子槽的宽度与转子齿121的宽度的差值可为气隙的10倍，即定子槽的宽度比转子齿121的宽度大1.5mm-20mm。其中，第一定子槽134的宽度、第二定子槽135的宽度和第三定子槽134的宽度均比转子齿121的宽度大1.5mm-20mm。
本实施所揭示的气隙可以为1mm，此时定子槽的宽度比转子齿121的宽度大10mm。
请进一步参见图9，图9是在开关磁阻电机的16个第一定子齿131和16个转子齿121位置错开时测量开关磁阻电机的磁力线，此时第一定子槽134尚未与转子齿121完全对齐，由于第一定子槽134和转子齿121之间的间隙较大，例如第一定子槽134的宽度比转子齿121的宽度大10mm。由于磁力线T不会纠缠交叉，并且在受到相邻的磁力线的挤压作用，该磁力线T只能通过当前第一定子槽134和转子齿121之间的间隙形成闭合回路，而该间隙非常大，因此磁阻大，导致A相绕组137产生的电感小。在第一定子槽134与转子齿121完全对齐时，电感极小，无法检测到磁力线T。
本实施例的开关磁阻电机在正常工作时，A相定子组件的电感曲线如图10所示，该电感曲线呈三角波形变化。在转子齿121的中心与第一定子槽134的 中心重合，即对应于第一电角度a1时，A相绕组产生的电感最小；在转子齿121的中心与第一定子齿131的中心重合，即对应于第二电角度a2时，A相绕组产生的电感最大，电感比可以达到21.25，而传统的三相开关磁阻电机的电感比只能达到2.5-4.5左右。由于开关磁阻电机的输出转矩
Figure PCTCN2017100279-appb-000002
电感比高意味
Figure PCTCN2017100279-appb-000003
大，电机的输出转矩就大，也即提高了电机的功率密度。
本实施例的定子齿的数量可为奇数，即第一定子齿131和第一定子槽134的总数为2N，其中N为自然数。因此第一定子齿131的数量和第一定子槽134的数量均可为奇数，能够避免齿谐波的自然谐振，例如第一定子齿131的数量为3，第一定子槽134的数量为3。相对比传统开关磁阻电机的定子齿的数量为偶数个，本实施例的开关磁阻电机能够根据不同的转速和不同转矩选择第一定子齿131的数量和第一定子槽134的数量，能够适应不同的场合，提高开关磁阻电机的实用性。
本发明提供第三实施例的开关磁阻电机，其在第二实施例的开关磁阻电机的基础上进行描述。如图11所示，本实施例中的转子齿121的齿尖设置有一削角123，削角123可以为弧形削角，该削角123的深度D小于0.8mm，削角123的长度L小于转子齿121的宽度；具体地，削角123的长度L小于转子齿121的宽度的1/3，能够大幅度减小电机的噪声。在其他实施例中，转子齿121的齿尖还可以设置为倒角，其中倒角的半径小于1mm。
本实施例的第一定子齿131、第二定子齿132和第三定子齿的齿尖结构与上述转子齿121的齿尖结构相同，不再赘述。
本发明提供第四实施例的开关磁阻电机，其在第一实施例的开关磁阻电机的基础上进行描述。如图12所示，开关磁阻电机进一步包括开关驱动电路21，开关驱动电路21连接直流电源Us和至少三个定子组件的绕组上，即开关驱动电路21连接直流电源Us、A相绕组、B相绕组和C相绕组上。
开关驱动电路21用于周期性依次在至少三个定子组件所对应的驱动阶段相绕组上施加驱动电流，至少三个定子组件的驱动时段的相位彼此错开，即在A相定子组件111的驱动阶段，开关驱动电路21在A相定子组件111施加驱动电 流；在B相定子组件112的驱动阶段，开关驱动电路21在B相定子组件112施加驱动电流；在C相定子组件113的驱动阶段，开关驱动电路21在C相定子组件113施加驱动电流。相应地，A相定子组件111、B相定子组件112和C相定子组件113的驱动时段的相位彼此错开。
其中，开关驱动电路21进一步在至少三个定子组件对应的驱动时段后续的续流时段释放至少三个定子组件的绕组上存储的能量，以形成续流电流。即在A相定子组件111的驱动时段后续的续流时段，开关驱动电路21用于释放A相绕组上存储的能量，形成A相绕组的续流电流；在B相定子组件112的驱动时段后续的续流时段，开关驱动电路21用于释放B相绕组上存储的能量，形成B相绕组的续流电流；在C相定子组件113的驱动时段后续的续流时段，开关驱动电路21用于释放C相绕组上存储的能量，形成C相绕组的续流电流。
开关驱动电路21包括控制器23以及分别与至少三个定子组件对应的至少三个开关模块，每一开关模块分别包括第一开关管、第二开关管、第一续流二极管和第二续流二极管，其中第一开关管的第一连接端连接电源的正极、第一开关管的第二连接端连接对应的定子组件的绕组的第一端、第二开关管的第一连接端连接对应的定子组件的绕组的第二端，第二开关管的第二连接端连接电源的负极，第一续流二极管的正极连接对应的定子组件的绕组的第二端，第一续流二极管的负极连接电源的正极，第二续流二极管的正极连接电源的负极，第二续流二极管的负极连接对应的定子组件的绕组的第一端。
具体地，开关驱动电路21包括控制器23、与A相定子组件111对应的第一开关模块24、与B相定子组件112对应的第二开关模块25以及与C相定子组件113对应的第三开关模块26。第一开关模块24包括第一开关管V1、第二开关管V2、第一续流二极管D1和第二续流二极管D2，第二开关模块25包括第一开关管V3、第二开关管V4、第一续流二极管D3和第二续流二极管D4，第三开关模块26包括第一开关管V5、第二开关管V6、第一续流二极管D5和第二续流二极管D6。
其中，至少三个定子组件所对应的驱动时段的相位差为2π/N，其中N为 至少三个定子组件的数量。A相定子组件111的驱动时段和B相定子组件112的驱动时段的相位差为2π/3，即电角度120°，B相定子组件112的驱动时段和C相定子组件113的驱动时段的相位差为电角度120°。
如图13所示，本实施例A相定子组件111的驱动时段为电角度0°-120°，A相定子组件111的续流时段为电角度120°-180°；B相定子组件112的驱动时段为电角度120°-240°，B相定子组件112的续流时段为电角度240°-300°；C相定子组件113的驱动时段为电角度240°-360°，C相定子组件113的续流时段为电角度360°-420°。其中，各定子组件的续流时段与下一被驱动的定子组件的驱动时段的相位至少部分重叠，即A相定子组件111的续流时段与B相定子组件112的驱动时段的相位部分重叠为120°-180°，B相定子组件112的续流时段与C相定子组件113的驱动时段的相位部分重叠为240°-300°。
在驱动时段，控制器23以脉宽调制方式同时控制第一开关管和第二开关管间歇性导通，由此调节驱动电流的大小。该脉宽调制方式可为PWM(Pulse Width Modulation，脉冲宽度调制)信号，在A相定子组件111的驱动时段时，控制器23通过PWM信号同时控制第一开关管V1和第二开关管V2导通或者关闭。控制器23在A相绕组产生的电感最小时发送PWM信号至第一开关管V1和第二开关管V2；在第一开关管V1和第二开关管V2同时导通时，直流电源Us在A相定子组件111施加驱动电流；在第一开关管V1和第二开关管V2同时关闭时，直流电源Us停止在A相定子组件111施加驱动电流，能够避免驱动电流过大。控制器23在A相绕组产生的电感最大时停止发送PWM信号至第一开关管V1，第一开关管V1关闭，A相定子组件111进入续流时段。在其他实施例，脉宽调制方式可以采用正弦波信号。
在续流时段，控制器23控制第一开关管持续关闭，并以脉宽调制方式控制第二开关管间歇性导通，由此调节续流电流的大小。在A相定子组件111的续流时段时，控制器23可以控制直流电源Us停止工作，A相绕组、第二开关V2和第二续流二极管D2形成回路，进而释放A相绕组上存储的能量。控制器23通过PWM信号控制第二开关管间歇性导通，以调节A相绕组的续流电流的大 小。
如图14所示，开关磁阻电机进一步包括与开关驱动电路21连接的电流检测电路27，该电流检测电路27用于检测流经至少三个定子组件的绕组的电流总和，即电流检测电路27用于检测流经A相绕组、B相绕组以及C相绕组的电流总和，电流总和为i＝ia+ib+ic，ia为流经A相绕组的电流，ib为流经B相绕组的电流，ic为流经C相绕组的电流。
电流检测电路27包括具有一开口的环形铁芯271以及磁场传感器272，至少三个定子组件的绕组分别绕设在环形铁芯271上，磁场传感器272设置于环形铁芯271的开口处。其中，环形铁芯271可为C形铁芯，A相绕组、B相绕组以及C相绕组分别绕设在环形铁芯271上，以分别在环形铁芯271上形成线圈L1、线圈L2和线圈L3。各个定子组件的绕组在环形铁芯271上绕设的匝数相同，即线圈L1的匝数、线圈L2的匝数和线圈L3的匝数相同。其中，磁场传感器272可为线性霍尔电流传感器。本实施例的开关磁阻电机仅需要一个磁场传感器272检测流经A相绕组、B相绕组以及C相绕组的电流总和，因此减少传感器数量，降低开关磁阻电机的成本。在其他实施例中，电流检测电路27可以设置为采用磁平衡式电流传感器。
开关驱动电路21根据电流检测电路27所检测的电流总和i分别对各绕组的驱动电流和续流电流进行控制，以使得电流总和保持预设范围。具体地，开关驱动电路21根据电流总和i分别对A相绕组的驱动电流和续流电流、B相绕组的驱动电流和续流电流、C相绕组的驱动电流和续流电流进行控制，以使得电流总和i保持稳定。
在A绕组的续流时段，控制器23根据电流检测电路27所检测的电流总和i通过PWM信号同时控制第一开关管V3和第二开关管V4导通或者关闭，以直流电源Us在B相定子组件112施加驱动电流，并且电流总和i保持稳定，如图13所示。
B绕组在驱动时段和续流时段的工作原理和C绕组在驱动时段和续流时段的工作原理与A绕组在驱动时段和续流时段的工作原理相同，不再赘述。
本实施例的开关驱动电路21根据电流检测电路27所检测的电流总和i分别对各绕组的驱动电流和续流电流进行控制，以使得电流总和保持预设范围，因此本实施的开关磁阻电机具有伺服电机的特性；由于开关磁阻电机的输出转矩稳定，进而降低开关磁阻电机的转矩波动和噪音。
本发明提供第五实施例的开关磁阻电机，其于第四实施例的开关磁阻电机的不同之处在于：如图15所示，控制器23控制第一开关持续导通，并且以脉宽调制方式控制第二开关管间歇性导通，由此调节驱动电流的大小。即在A相定子组件111的驱动时段时，控制器23控制第一开关V1持续导通，通过PWM信号控制第二开关管V2间歇性导通。
本发明提供第五实施例的开关磁阻电机，其于第四实施例的开关磁阻电机的基础上进行描述：如图16所示，开关磁阻电机进一步包括与开关驱动电路21连接的位置传感器28，位置传感器28用于测量开关磁阻电机10中转子12与定子11之间的相对位置，以使得开关驱动电路21根据转子12与定子11之间的相对位置改变通电状态，即开关驱动电路21根据每一定子组件的最大电感和最小电感改变通电状态，以驱动开关磁阻电机工作。其中，位置传感器28包括磁编码器或者光编码器。
本发明提供一实施例的开关磁阻电机的电流的控制方法，本实施例的控制方法在第四实施例所揭示的开关磁阻电机的基础上进行描述。如图17所示，该控制方法包括：
S161：在驱动时段，通过控制器23以脉宽调制方式同时控制第一开关管和第二开关管间歇性导通；或者控制第一开关管持续导通，并以脉宽调制方式控制第二开关管间歇性导通，以调节绕组的驱动电流的大小；
S162：在续流时段，通过控制器23控制第一开关管持续关闭，并以脉宽调制方式控制第二开关管间歇性导通，以调节绕组的续流电流的大小；
S163：根据电流总和i控制驱动电流和续流电流，以使电流总和i保持预设范围。
在步骤S161中，进一步通过控制器23控制至少三个定子组件所对应的驱 动时段的相位差为2π/N，其中N为至少三个定子组件的数量。即A相定子组件111的驱动时段和B相定子组件112的驱动时段的相位差为2π/3，即电角度120°，B相定子组件112的驱动时段和C相定子组件113的驱动时段的相位差为电角度120°。
通过控制器23控制定子组件的续流时段与下一被驱动的定子组件的驱动时段的相位至少部分重叠，其中定子组件的续流时段与下一被驱动的定子组件的驱动时段的相位至少部分重叠为π/N电角度。即A相定子组件111的续流时段与B相定子组件112的驱动时段的相位部分重叠为120°-180°，B相定子组件112的续流时段与C相定子组件113的驱动时段的相位部分重叠为240°-300°，如图13所示。
其中，在A相定子组件111的驱动时段时，通过控制器23以脉宽调制方式同时控制第一开关管V1和第二开关管V2导通或者关闭。即通过控制器23在A相绕组产生的电感最小时发送PWM信号至第一开关管V1和第二开关管V2；在第一开关管V1和第二开关管V2同时导通时，直流电源Us在A相定子组件111施加驱动电流；在第一开关管V1和第二开关管V2同时关闭时，直流电源Us停止在A相定子组件111施加驱动电流，能够避免驱动电流过大。
通过控制器23在A相绕组产生的电感最大时停止发送PWM信号至第一开关管V1，第一开关管V1关闭，A相定子组件111进入续流时段，进入步骤S162。
在步骤S162中，在A相定子组件111的续流时段时，通过控制器23控制直流电源Us停止工作，并且控制第一开关管V1持续关闭，并以脉宽调制方式控制第二开关管V2间歇性导通，以使A相绕组、第二开关V2和第二续流二极管D2形成回路，进而释放A相绕组上存储的能量，以调节A相绕组的续流电流的大小。
同时，通过控制器23控制B绕组的第一开关管V3和第二开关管V4导通或者关闭，以直流电源Us在B相定子组件112施加驱动电流，其中，通过步骤S161的控制方式控制B绕组的第一开关管V3和第二开关管V4，在此不再赘述。
在步骤S163中，通过开关驱动电路21从电流检测电路27获取电流总和i， 并且根据电流总和i控制驱动电流和续流电流，以使电流总和i保持预设范围。其中控制驱动电流的方法可采用步骤S161，控制续流电流的方法可采用步骤S162。
本实施例的脉宽调制方式可以为方波脉宽调制或者正弦波脉宽调制。其中，上述实施例的PWM信号为方波脉宽调制。
在本发明中，A相绕组产生的电感最小，具体可为转子齿121与第一定子槽134完全对齐时；A相绕组产生的电感最大，具体可为转子齿121与第一定子齿131完全对齐时。
本实施例所揭示的A相绕组在进入续流时段时，A相绕组的续流电流开始变小，A相绕组产生的磁场变弱，进而噪声小；由于电流总和i保持预设范围，因此开关磁阻电机输出的转矩稳定，进而转矩波动小。
本发明还提供一种车轮，该车轮采用开关磁阻电机驱动，而该开关磁阻电机为如前实施例中所述的开关磁阻电机。
优选地，该车轮可以包括轮毂式开关磁阻电机，即利用轮毂式开关磁阻电机驱动，该轮毂式开关磁阻电机为外转子内定子的电机结构。
进一步地，本发明还提供一种电动车，该电动车可以为电动汽车、电动摩托车或者电动自行车等。该电动车为纯电动或混合动力车，该电动车的车轮采用开关磁阻电机驱动，该开关磁阻电机也为如前实施例中所述的开关磁阻电机。优选的，该电动车的驱动轮可采用上述实施例中的车轮结构，即车轮包括轮毂式开关磁阻电机，利用轮毂式开关磁阻电机驱动车轮转动。
需要说明的是，本发明实施例提供的开关磁阻电机的应用场景不限于电动汽车，还可以作为船舶、大型机械等驱动用电机。
需要说明的是，以上各实施例均属于同一发明构思，各实施例的描述各有侧重，在个别实施例中描述未详尽之处，可参考其他实施例中的描述。
以上对本发明实施例所提供的开关磁阻电机及电动车和车轮进行了详细介绍，本文中应用了具体个例对本发明的原理及实施方式进行了阐述，以上实施例的说明只是用于帮助理解本发明的方法及其核心思想；同时，对于本领域的 一般技术人员，依据本发明的思想，在具体实施方式及应用范围上均会有改变之处，综上所述，本说明书内容不应理解为对本发明的限制。

Claims (18)

  1. 一种开关磁阻电机，其特征在于，所述开关磁阻电机包括定子以及转子，其中所述定子沿轴向分段设置有至少三个定子组件，每一所述定子组件分别包括沿所述定子的周向周期性设置且由定子槽彼此间隔的多个定子齿以及绕设于所述定子齿上的绕组，所述至少三个定子组件的定子齿沿所述定子的周向依次错开预定角度，每个所述定子组件中的所述绕组均为同一相绕组，所述转子包括沿所述转子的周向周期性设置且由转子槽彼此间隔的多个转子齿，其中所述转子齿的数量与所述定子齿的数量相同，且所述转子齿的宽度小于所述定子槽的宽度。
  2. 根据权利要求1所述的开关磁阻电机，其特征在于，所述定子槽与所述定子齿的宽度比为1∶0.95-0.85，所述定子齿与所述转子齿的宽度比为1∶1.05-0.95。
  3. 根据权利要求2所述的开关磁阻电机，其特征在于，所述定子齿的数量为奇数。
  4. 根据权利要求2所述的开关磁阻电机，其特征在于，所述至少三个定子组件的定子齿的数量和宽度相同，所述预定角度为T1/N，其中所述T1为所述定子齿的电角度周期，所述N为所述至少三个定子组件的数量。
  5. 根据权利要求4所述的开关磁阻电机，其特征在于，N为3或3的整数倍，所述定子齿的电角度周期T1为2π/M，其中M为定子齿的数量。
  6. 根据权利要求1所述的开关磁阻电机，其特征在于，所述开关磁阻电机进一步包括开关驱动电路，所述开关驱动电路连接直流电源和所述至少三个定子组件的所述绕组上，以周期性控制所述直流电源依次在所述至少三个定子组件所对应的驱动时段向所述绕组上施加所述驱动电流，其中所述至少三个定子组件的所述驱动时段的相位彼此错开。
  7. 根据权利要求6所述的开关磁阻电机，其特征在于，所述开关驱动电路进一步在所述至少三个定子组件所对应的驱动时段后续的续流时段释放所述至少三个定子组件的所述绕组上存储的电能，以形成续流电流。
  8. 根据权利要求6所述的开关磁阻电机，其特征在于，所述至少三个定子组件所对应的所述驱动时段的相位差为2π/N，其中所述N为所述至少三个定子组件的数量。
  9. 根据权利要求7所述的开关磁阻电机，其特征在于，各所述定子组件的 续流时段与下一被驱动的所述定子组件的驱动时段的相位至少部分重叠。
  10. 根据权利要求9所述的开关磁阻电机，其特征在于，各所述定子组件的续流时段与下一所述定子组件的驱动时段的相位重叠为π/N。
  11. 根据权利要求8所述的开关磁阻电机，其特征在于，所述开关驱动电路分别以脉宽调制方式对所述驱动电流和所述续流电流的大小进行调节。
  12. 根据权利要求9所述的开关磁阻电机，其特征在于，所述开关磁阻电机进一步包括电流检测电路，其中所述电流检测电路用于检测流经所述至少三个定子组件的所述绕组的电流总和，所述开关驱动电路根据所述电流检测电路所检测的所述电流总和分别对各所述绕组的所述驱动电流和所述续流电流进行控制，以使得所述电流总和保持预设范围。
  13. 根据权利要求12所述的开关磁阻电机，其特征在于，所述电流检测电路包括具有一开口的环形铁芯以及磁场传感器，所述至少三个定子组件的所述绕组进一步分别绕设于所述环形铁芯上，所述磁场传感器设置于所述环形铁芯的开口处。
  14. 根据权利要求13所述的开关磁阻电机，其特征在于，各所述定子组件的所述绕组在所述环形铁芯上绕设的匝数相同。
  15. 根据权利要求13所述的开关磁阻电机，其特征在于，所述磁场传感器为线性霍尔电流传感器。
  16. 根据权利要求6所述的开关磁阻电机，其特征在于，所述开关磁阻电机进一步包括与所述开关驱动电路连接的位置传感器，所述位置传感器用于测量所述定子和所述转子的相对位置，所述位置传感器包括磁编码器或者光编码器。
  17. 一种车轮，其特征在于，所述车轮采用轮毂电机驱动，所述轮毂电机为权利要求1-16任一项所述的开关磁阻电机。
  18. 一种电动车，其特征在于，所述电动车为纯电动或混合动力车，所述电动车包括如权利要求1-16任一项所述的开关磁阻电机。
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CN105429416A (zh) * 2016-01-17 2016-03-23 顾志强 一种带调角凸齿的外铁芯冲片
CN105490402A (zh) * 2016-01-17 2016-04-13 顾志强 一种带调角凸齿的内铁芯冲片
CN205622456U (zh) * 2016-01-17 2016-10-05 顾志强 一种带调角凸齿的外铁芯冲片
CN105553212A (zh) * 2016-01-22 2016-05-04 顾志强 一种多级轴向布相等极结构开关磁阻电机
CN205304560U (zh) * 2016-01-22 2016-06-08 顾志强 一种多级轴向布相等极结构开关磁阻电机

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