WO2018196594A1 - 信号传输方法、相关设备及系统 - Google Patents

信号传输方法、相关设备及系统 Download PDF

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Publication number
WO2018196594A1
WO2018196594A1 PCT/CN2018/082409 CN2018082409W WO2018196594A1 WO 2018196594 A1 WO2018196594 A1 WO 2018196594A1 CN 2018082409 W CN2018082409 W CN 2018082409W WO 2018196594 A1 WO2018196594 A1 WO 2018196594A1
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Prior art keywords
sequence
zero
training
transmitted
sequences
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PCT/CN2018/082409
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English (en)
French (fr)
Inventor
唐小虎
原頔
颜敏
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华为技术有限公司
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
    • H04B7/0615—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal
    • H04B7/0617—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of weighted versions of same signal for beam forming
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes

Definitions

  • the present application relates to the field of wireless communication technologies, and in particular, to a signal transmission method, related devices, and systems.
  • Communication systems can apply beamforming techniques to improve communication performance.
  • the beamforming technology needs to know the channel state information clearly, and the receiving end needs to feed back the complete channel state information to the transmitting end.
  • the transmitting end transmits one or more beamforming training sequences to the receiving end. Then, the receiving end estimates the channel characteristics using the received training sequence, and returns the channel estimation result to the transmitting end. Finally, the transmitting end adjusts the transmit antenna configuration according to the channel estimation estimation result returned by the receiving end.
  • the Golay complementary sequence is used for channel estimation, but also the beam (antenna weight vector) training is utilized, which fully utilizes the autocorrelation complementary feature of the Golay complementary sequence, that is, receiving the training sequence and transmitting the training sequence.
  • the autocorrelation is equal to the channel impulse response.
  • 1A-1C respectively show the frame structure and TRN field definition of two Golay complementary sequences (G a 128, G b 128), Beam Refinement Packet (BRP) used in the IEEE 802.11ad standard.
  • BRP Beam Refinement Packet
  • the beam training field TRN field in IEEE 802.11ad is composed of N (N ⁇ 17, N is a positive integer) TRN-Unit, wherein each TRN-Unit is divided into a Channel Estimation (CE) field and a T/R.
  • CE Channel Estimation
  • Each T / R field contains the sequence [G a 128G b 128G a 128G b 128Ga128], can be roughly measured using the measurement channel in time domain, may be made to the channel estimation accuracy in the frequency domain.
  • the training sequence is designed only for channel measurement under a single antenna, and does not involve MIMO multi-channel parallel transmit beam training for channel measurement design, which cannot meet the MIMO parallel training scenario.
  • Channel measurement requirements Therefore, in the MIMO scenario, the channel quality of the beam used in each antenna configuration cannot be calculated, and thus the optimal antenna configuration of the transmitting antenna and the receiving antenna cannot be obtained in the parallel training process.
  • the training end transmits and transmits at least one cascading training sequence, and may selectively modulate the training sequence by using multiple schemes, and then perform cascading, and send the cascading sequence to the one or more trainees.
  • the training sequence can be as shown in FIG. 2, the cascaded training sequence including a preamble and a plurality of modulated training sequences b-seq 1 , b-seq 2 , . . . , b-seq n .
  • the disadvantage of the prior art 2 is that only the beam training problem under one-to-many conditions is solved, and it is not suitable for channel estimation in a many-to-many scenario.
  • the present application provides a signal transmission method, which can meet the requirements for accurate channel estimation by using a beamforming training sequence in different application scenarios.
  • the present application provides a signal transmission method applied to a transmitting end, the method comprising: transmitting, by N ⁇ antennas, a data packet for beam optimization, where N ⁇ is a positive integer, and the data packet transmitted by each antenna Each includes a training sequence for channel estimation transmitted by the antenna.
  • the present application provides a signal transmission method, which is applied to a receiving end, where the method includes: receiving, by the receiving end, N ⁇ data packets for beam optimization, respectively, sent by the transmitting end through N ⁇ antennas, where N ⁇ is positive An integer; wherein the data packets transmitted by each antenna comprise a training sequence transmitted by the antenna for channel estimation.
  • the receiving end may also perform channel estimation by using the training sequence in the data packet.
  • the training sequence transmitted by each antenna includes M sequence units of the same length, and M is an integer.
  • the training sequence configured for each antenna satisfies the following conditions:
  • the above condition (1) indicates that in the presence of the multipath effect, the training sequence transmitted by the antenna t has an accumulated ISI of 0 caused by multipath during transmission, which does not adversely affect channel measurement in beam training. influences.
  • the above condition (2) indicates that in the case where there is time spread, the training sequence transmitted by the antenna t has an accumulated ISI of 0 caused by the time spreading effect during transmission, and does not adversely affect channel measurement in beam training.
  • the above condition (3) indicates that the accumulated MAI between the training sequences transmitted by different antennas is 0 during transmission, which does not adversely affect the channel measurement in beam training.
  • the above condition (3) indicates that during the transmission, the accumulated MAI between the training sequences transmitted by different antennas due to the time spreading effect is 0, which does not adversely affect the channel measurement in beam training. That is, the training sequence transmitted on each antenna does not have ISI and MAI, and does not adversely affect channel measurement in beam training, which facilitates accurate channel estimation.
  • the training sequence transmitted by a single antenna may include a first sequence, a second sequence, and between the first sequence and the second sequence The first zero sequence.
  • the first sequence and the second sequence may each include H sequence units, H is a positive integer, 2*H ⁇ M.
  • the first zero sequence may include Z1 of the sequence units, Z1 being a positive integer, Z1+2*H ⁇ M. That is to say, the middle segment of the training sequence is zero, which can make the construction of the training sequence simpler and reduce the signaling overhead.
  • the first and last two segments of the training sequence transmitted by a single antenna may also be zero. That is, the training sequence transmitted by the single antenna may further include a second zero sequence and a third zero sequence, wherein the second zero sequence is inserted in front of the first sequence, and the third zero sequence is inserted in the first Behind the second sequence.
  • the first sequence and the second sequence may be obtained from an LS code, so that the LS code may be used to spread to multiple antennas, that is, each antenna is placed.
  • Different sequences implement multiple antenna (N ⁇ ⁇ 2) transmission training sequences. That is to say, the sequence unit included in the first sequence may be the sequence a or a' in the A portion, and the sequence unit included in the second sequence may be the sequence b or b' in the A portion.
  • the number H of sequence units included in the first sequence or the second sequence is related to the number of antennas N ⁇ , specifically: The specific implementation of obtaining the training sequence from the LS code is specifically described below.
  • L represents the length of the sequences a, b, a', b' in the complementary sequence pair (a, b), (a', b').
  • the first sequence when the number of transmitting antennas N ⁇ 2, in the training sequence respectively transmitted by the N ⁇ antennas, the first sequence may be taken from multiple sequences of the A part in the ith layer LS code, where the The second sequence may be taken from a plurality of sequences of Part B of the i-th layer LS code.
  • i is a positive integer
  • the number of transmitting antennas is four.
  • Four sequences may be selected from the A portion of the second layer LS code as the first sequence transmitted on the four antennas, and four sequences may be selected from the B portion of the second layer LS code as the four antennas.
  • the second sequence transmitted on Wherein the first sequence and the second sequence transmitted on the same antenna correspond to each other. That is, the first sequence and the second sequence transmitted on the same antenna may be the j-th sequence in the A part and the B part, respectively, and j is a positive integer, j ⁇ [1, 4].
  • the examples are merely illustrative of the embodiments of the invention and should not be construed as limiting.
  • the number of transmit antennas is three.
  • Three sequences may be selected from the A portion of the Layer 2 LS code as the first sequence transmitted on the three antennas, and three sequences may be selected from the B portion of the second layer LS code as the three antennas.
  • the second sequence transmitted on Wherein the first sequence and the second sequence transmitted on the same antenna correspond to each other.
  • the examples are merely illustrative of the embodiments of the invention and should not be construed as limiting.
  • a training sequence respectively transmitted by the N ⁇ antennas can be realized (shown in FIG. 8A or FIG. 8B).
  • the above conditions (1) to (4) are satisfied. That is to say, there is no ISI and MAI in the training sequence transmitted on each antenna, which will not adversely affect the channel measurement in beam training, and facilitate accurate channel estimation.
  • the first sequence and the second sequence may be the a and b sequences of the complementary sequence pair (a, b), respectively.
  • the Golay complementary sequence is used to accumulate side lobes to zero, and the Golay complementary sequence is used for channel estimation.
  • the channel estimation is simple and excellent, and the Golay complementary sequence can be selected to construct the present application.
  • Training sequence in That is to say, the complementary sequence pairs (a, b) and (a', b') of the above constructed LS code may be Golay complementary sequence pairs.
  • the length L and the maximum delay of the a and b sequences in the (a, b) of the Golay complementary sequence are extended to T m and the symbol rate is R s related: The maximum delay of the channel is extended to T m and the symbol rate is R s .
  • the present application provides a communication device comprising a plurality of functional modules for respectively performing the method provided by the first aspect, or the method provided by any one of the possible embodiments of the first aspect.
  • the present application provides a communication device comprising a plurality of functional modules for respectively performing the method provided by the second aspect, or the method provided by any one of the possible embodiments of the second aspect.
  • the communication device can include a memory and a processor, transmitter coupled to the memory, wherein: the transmitter is configured to transmit data packets for beam optimization through N ⁇ antennas, N ⁇ being a positive integer, each antenna transmitting Each of the data packets includes a training sequence for channel estimation transmitted by the antenna; the training sequence includes M sub-sequences of the same length, and M is a positive integer; wherein: each data block in the training sequence transmitted by the same antenna The sum of the autocorrelations is zero, and the sum of the cross-correlations between all two adjacent data blocks is zero; among the training sequences transmitted by any two antennas, all of the two data blocks corresponding to the same sequence number are between The sum of the cross-correlations is zero, and the sum of the cross-correlations between the two data blocks corresponding to the adjacent sequence numbers is zero.
  • the memory is for storing implementation code of the signal transmission described in the first aspect
  • the processor is
  • the communication device can include: a memory and a processor, a receiver coupled to the memory, wherein: the receiver is configured to receive N ⁇ data packets for beam optimization, the N ⁇ of the data packets being N ⁇ is a positive integer transmitted by the transmitting end through N ⁇ antennas respectively; wherein the data packet transmitted by each antenna includes a training sequence transmitted by the antenna for channel estimation; the training sequence includes M lengths The same subsequence, M is a positive integer; wherein: in the training sequence transmitted by the same antenna, the sum of the autocorrelations of each data block is zero, and the sum of the cross correlations between all two adjacent data blocks is zero; In the training sequence transmitted by the two antennas, the sum of the cross-correlations between the two data blocks corresponding to the same sequence number is zero, and the sum of the cross-correlations between the two data blocks corresponding to the adjacent sequence numbers Zero.
  • the memory is for storing implementation
  • a communication system comprising: a first communication device and a second communication device.
  • the first communication device may be the network device described in the third aspect or the fifth aspect
  • the second communication device may be the network device described in the fourth aspect or the sixth aspect.
  • a computer readable storage medium storing program code for implementing the method described in the first aspect or the second aspect, the program code comprising running the first aspect or the second aspect The execution instructions of the described method.
  • 1A is a schematic diagram of a Golay complementary sequence pair defined in the existing 802.11ad protocol
  • FIG. 1B is a schematic structural diagram of a Beam Optimization Protocol (BRP) data packet defined in the existing 802.11ad protocol;
  • BRP Beam Optimization Protocol
  • 1C is a schematic structural diagram of a beam training field (TRN-R/T field) in a Beam Optimization Protocol (BRP) packet defined in the existing 802.11ad protocol;
  • TRN-R/T field a beam training field
  • BRP Beam Optimization Protocol
  • FIG. 2 is a schematic structural diagram of a conventional training sequence
  • FIG. 3 is a schematic structural diagram of a wireless communication system according to the present application.
  • FIG. 4 is a schematic diagram of a hardware architecture of a transmitter provided by an embodiment of the present application.
  • FIG. 5 is a schematic diagram of a hardware architecture of a receiver provided by an embodiment of the present application.
  • FIG. 6 is a schematic flowchart of a signal transmission method provided by an embodiment of the present application.
  • FIG. 7 is a schematic structural diagram of a training sequence respectively transmitted by multiple antennas provided by the present application.
  • 8A-8B are schematic structural diagrams of a training sequence provided by the present application.
  • FIG. 9 is a schematic diagram of a method for constructing an LS code according to the present application.
  • FIGS. 10A-10B are schematic structural diagrams of two other training sequences provided by the present application.
  • FIGS. 11A-11F are schematic diagrams of data of Golay complementary sequence pairs of various lengths provided by the present application.
  • 12A-12C are schematic diagrams of three methods for constructing an LS code using a Golay complementary sequence pair provided by the present application.
  • FIG. 13 is a schematic structural diagram of a wireless communication system, a transmitting device, and a receiving device provided by the present application.
  • FIG. 3 illustrates a wireless communication system to which the present application relates.
  • wireless communication system 100 can include at least one transmitter 101 and at least one receiver 102.
  • one or more antennas may be installed at both ends of the transmitter 101 and the receiver 102, the number of transmitting antennas is N T , and the number of receiving antennas is N R .
  • the transmitter 101 processes the data to generate N T data streams, each of the data streams at the same time, the same frequency transmitted from different transmit antennas, after spatial channel fading, signals from different transmit antennas and The noise is superimposed on each antenna and finally sent to the receiver for processing.
  • training sequence based beamforming training can be performed on the transmitter 101.
  • the transmitter 101 can transmit a training sequence to the receiver 102.
  • the receiver 102 can perform channel estimation using the training sequence transmitted by the transmitter 101 and return the estimation result to the transmitter 101.
  • the transmitter 101 can adjust the transmit antenna array beamforming vector based on the channel estimation results returned by the receiver 102 to optimize the transmit antenna configuration.
  • training sequence based beamforming training can be performed on the receiver 102.
  • the receiver 102 can also send a training sequence to the transmitter.
  • the transmitter 101 can perform channel estimation by using the training sequence transmitted by the receiver 102, and return the estimation result to the receiver 102.
  • the receiver 102 can adjust the receiving antenna array according to the channel estimation result returned by the transmitter 101. Beamforming vectors to optimize the receive antenna configuration.
  • ISI Inter Symbol Interference
  • MAI Multiple Access Interference
  • the wireless communication system 100 can support multiple maximum delay spreads, such as 72 ns, 300 ns, and the like.
  • the wireless communication system 100 can also support multiple symbol rates, such as 1.76 Gbps, 3.52 Gbps, 5.28 Gbps, or 7.04 Gbps.
  • the wireless communication system 100 may be a MIMO system, and the Massive MIMO system may also be a SIMO system or a MISO system.
  • the wireless communication system 100 can also be a SISO system. The specific implementation of this application under these different systems will be introduced separately.
  • FIG. 4 is a schematic structural diagram of a transmitting apparatus provided by the present application.
  • the transmitting device 200 can include one or more processors 201, a memory 202, a communication interface 203, a transmitter 205, and an antenna 206. These components can be connected by bus 204 or other means, and FIG. 4 is exemplified by a bus connection. among them:
  • Antenna 206 can be used to transmit signals.
  • the antenna 206 may be an antenna array including a plurality of transmitting antennas.
  • Transmitter 205 can be used to perform transmission processing on signals output by processor 201, such as by beamforming.
  • the transmitter 205 may include a MIMO encoding module 2051, a digital to analog converter (DAC) 2051, a mixer 2053, a beamforming controller 2054, and a power amplifier (PA) 2055.
  • the MIMO encoding module 2051 can be used to improve channel characteristics by precoding, so that the transmitted signals better match channel conditions to obtain better transmission quality.
  • the digital to analog converter 2051 and the mixer 2053 can be used to convert the digital signal into an analog signal and perform mixing, and the mixed signal is output to the beamforming controller 2054.
  • Beamforming controller 2054 may be used to transmit a signal by a transmission weight vector W 1, ??, W m, the directional control signals transmitted.
  • the power amplifier 2055 can be used to power amplify the signal output by the beamforming controller 2054 and output it to the antenna 206.
  • the transmitter 2052 may also include other devices for signal transmission processing, such as filters, frequency converters, etc., which are not limited herein.
  • the transmitter 205 may be specifically configured to transmit a training sequence for beamforming training prior to data transmission.
  • the beamforming controller 2054 is configured to adjust the transmission weight vector W1, . . . , W according to the channel estimation result of the training sequence returned by the receiving end, until the optimal.
  • Communication interface 203 can be used by transmitting device 200 to communicate with other communication devices.
  • the communication interface 203 can be a wireless communication interface such as a wireless local area network (WLAN), and can support the 802.11b protocol, the 802.11a protocol, the 802.11g protocol, the 802.11e protocol, the 802.11i protocol, and the like.
  • WLAN wireless local area network
  • the communication interface 203 may also include a wired communication interface, such as a local access network (LAN) interface, etc., which is not limited herein.
  • Memory 202 is coupled to processor 201 for storing various software programs and/or sets of instructions.
  • memory 202 can include high speed random access memory, and can also include non-volatile memory, such as one or more magnetic disk storage devices, flash memory devices, or other non-volatile solid state storage devices.
  • the memory 202 can store an operating system (hereinafter referred to as a system) such as an embedded operating system such as LINUX.
  • the memory 202 can be used to store an implementation of a signal transmission method provided by one or more embodiments of the present application.
  • a signal transmission method provided by one or more embodiments of the present application, please refer to the subsequent embodiments.
  • the processor 201 can be used to read and execute computer readable instructions. Specifically, the processor 201 can be used to invoke a program stored in the memory 202, such as an implementation of the signal transmission method provided by one or more embodiments of the present application, and execute the instructions contained in the program.
  • the transmitting device 200 can be the transmitter 101 in the wireless communication system 100 shown in FIG. 3, and can be implemented as a wireless transmitter, an access point, a mobile device, a mobile station, and a mobile unit. )and many more.
  • the transmitting device 200 shown in FIG. 4 is only one implementation of the embodiment of the present application. In practical applications, the transmitting device 200 may further include more or fewer components, which are not limited herein. In some possible embodiments, the transmitting device 200 may also be implemented as a transmitting device supporting Multi-User MIMO (MU-MIMO), configured with multiple transmit antenna arrays.
  • MU-MIMO Multi-User MIMO
  • FIG. 5 is a schematic structural diagram of a receiving apparatus provided by the present application.
  • the receiving device 300 can include one or more processors 301, a memory 302, a communication interface 303, a receiver 305, and an antenna 306. These components can be connected by bus 304 or other means, and FIG. 5 is exemplified by a bus connection. among them:
  • Antenna 306 can be used to receive signals.
  • the antenna 306 may be an antenna array including a plurality of receiving antennas.
  • Receiver 305 can be used to perform receive processing on the radio frequency signals received by antenna 306, such as by beamforming.
  • the receiver 305 may include a power amplifier (PA) 3055, a beamforming controller 3054, a mixer 3053, an analog to digital converter (ADC) 3051, and a MIMO decoding module 3051.
  • the power amplifier 2055 can be used to amplify the received power, and the antenna 306 receives the RF signal and outputs it to the beamforming controller 3054.
  • the controller 3054 may be used for beam forming of the received signal by the reception weight vector W 1, ......, W m, directional receiving a control signal.
  • the mixer 2053 and the analog to digital converter 3051 can be used to mix the received signals and convert the mixed analog signals into digital signals and output to the beamforming controller 2054.
  • the MIMO decoding module 3051 can be used to decode the received signal that has been MIMO encoded to reconstruct the transmitted signal. It should be noted that the receiver 3052 may also include other devices for signal receiving processing, such as filters, frequency converters, etc., which are not limited herein.
  • reception 305 may be specifically for receiving a training sequence for beamforming training.
  • the beamforming controller 3054 is configured to perform channel estimation based on the training sequence, and return the channel estimation result to the transmitting end, so that the transmitting end adjusts the configuration of the transmitting antenna according to the returned channel estimation result until the optimal.
  • Communication interface 303 can be used by receiving device 300 to communicate with other communication devices.
  • the communication interface 303 can be a wireless communication interface such as a wireless local area network (WLAN), and can support the 802.11b protocol, the 802.11a protocol, the 802.11g protocol, the 802.11e protocol, the 802.11i protocol, and the like.
  • the communication interface 303 may also include a wired communication interface, such as a local area network (LAN) interface, etc., which is not limited herein.
  • LAN local area network
  • Memory 302 is coupled to processor 301 for storing various software programs and/or sets of instructions.
  • memory 302 may include high speed random access memory, and may also include non-volatile memory, such as one or more magnetic disk storage devices, flash memory devices, or other non-volatile solid state storage devices.
  • the memory 302 can store an operating system (hereinafter referred to as a system) such as an embedded operating system such as LINUX.
  • the memory 302 can be used to store an implementation of a signal transmission method provided by one or more embodiments of the present application.
  • a signal transmission method provided by one or more embodiments of the present application, please refer to the subsequent embodiments.
  • the processor 301 can be used to read and execute computer readable instructions. Specifically, the processor 301 can be used to invoke a program stored in the memory 302, such as an implementation of the signal transmission method provided by one or more embodiments of the present application, and execute the instructions contained in the program.
  • the receiving device 300 can be the receiver 102 in the wireless communication system 100 shown in FIG. 3, and can be implemented as a wireless receiver, an access point, a mobile device, a mobile station, and a mobile unit. )and many more.
  • the receiving device 300 shown in FIG. 5 is only one implementation of the embodiment of the present application. In an actual application, the receiving device 300 may further include more or fewer components, which are not limited herein. In some possible embodiments, the receiving device 300 may also be implemented as a receiving device supporting Multi-User MIMO (MU-MIMO), configured with multiple receiving antenna arrays.
  • MU-MIMO Multi-User MIMO
  • the transmitting device 200 shown in FIG. 4 and the receiving device 300 shown in FIG. 5 may be implemented in the same hardware device, that is, the transmitting end or the receiving end involved in the present application may be integrated with the transmitting device.
  • the present application provides a signal transmission method, which can meet the requirements for accurate channel estimation by using a beamforming training sequence in different application scenarios.
  • the main inventive principle of the present application may include: configuring a training sequence transmitted on each antenna in a beamforming training process, wherein the accumulated intersymbol interference ISI corresponding to the training sequence transmitted on the same antenna is 0, any two The accumulated multiple access interference MAI between the training sequences transmitted on the antennas is zero. In this way, the adverse effects of inter-symbol interference ISI and multiple access interference MAI on channel measurement in beam training can be avoided, and accurate channel estimation can be achieved by transmitting training sequences on the respective antennas.
  • the transmitting end may configure a training sequence corresponding to each of the N ⁇ antennas for beamforming training.
  • N ⁇ is a positive integer, and the value of N ⁇ is not limited in this application.
  • the training sequence corresponding to each antenna includes M sequence units of the same length, and M is an integer. Moreover, the training sequence configured for each antenna satisfies the following conditions:
  • Sequence unit represents the i-th sequence unit in the training sequence transmitted by antenna j.
  • the present application does not limit the length of the sequence unit, and does not limit the value of M, and can be determined according to actual needs.
  • the above four conditions can be specifically expressed by the following data expressions (R represents a correlation function):
  • the mathematical expression (1) represents the above condition (1), and ⁇ ⁇ 0 indicates that there is a multipath effect.
  • the mathematical expression (1) specifically indicates that in the presence of multipath effects, the training sequence transmitted by the antenna t has an accumulated ISI of 0 caused by multipath during transmission, which does not adversely affect channel measurement in beam training. .
  • the mathematical expression (2) represents the above condition (2), and ⁇ ⁇ 0 indicates that there is a time diffusion effect.
  • the effect of time spreading on the transmitted signal is to cause temporal overlap between adjacent symbols and also cause intersymbol interference.
  • the mathematical expression (2) specifically indicates that in the case of time-diffusion, the training sequence transmitted by the antenna t has an accumulated ISI of 0 caused by the time spreading effect during transmission, and does not adversely affect the channel measurement in beam training. .
  • the training sequence transmission process does not require high synchronization accuracy and can tolerate small out-of-synchronization.
  • the mathematical expression (3) represents the above condition (3), specifically: during the transmission, the accumulated MAI between the training sequence transmitted by the antenna t and the training sequence transmitted by the antenna q is 0, and is not in the beam training.
  • the channel measurement has an adverse effect.
  • the mathematical expression (4) represents the above condition (4), specifically: in the transmission process, the accumulated MAI between the training sequence transmitted by the antenna t and the training sequence transmitted by the antenna q due to the time spreading effect is 0, It does not adversely affect channel measurements in beam training.
  • the training sequence transmission process does not require high synchronization accuracy and can tolerate small out-of-synchronization.
  • the transmitting end transmits a data packet for beam optimization through the N ⁇ antennas, where the data packet transmitted by each antenna includes a training sequence transmitted by the antenna.
  • the data packet for beam optimization may specifically be a Beam Refinement Protocol (BRP) data packet.
  • the training sequence may be included in the beam training field TRN field in the BRP data packet, and may be specifically included in the T/R field, and may be referred to the IEEE 802.11ad protocol, which is not described here.
  • the receiving end may receive the data packet for beam optimization sent by the transmitting end, extract N ⁇ training sequences, and perform channel estimation based on the received training sequence, and estimate the channel. The result is returned to the transmitter.
  • the transmitting end can adjust the antenna configuration according to the channel estimation result returned by the receiving end.
  • a training sequence transmitted by a single antenna may include a first sequence, a second sequence, and a first zero between the first sequence and the second sequence.
  • the first sequence and the second sequence may each include H sequence units, H is a positive integer, 2*H ⁇ M.
  • the first zero sequence may include Z1 of the sequence units, Z1 being a positive integer, Z1+2*H ⁇ M. That is to say, the middle segment of the training sequence is zero, which can make the construction of the training sequence simpler and reduce the signaling overhead.
  • the first and last two segments of the training sequence transmitted by a single antenna may also be zero. That is, on the basis of FIG. 8A, the training sequence transmitted by a single antenna may further include a second zero sequence and a third zero sequence, wherein the second zero sequence is inserted in front of the first sequence, and the third A zero sequence is inserted after the second sequence.
  • the sum of the autocorrelations of the zero sequences is 0, and the zero sequences and adjacent non- The sum of the cross-correlations between the zero sequence units (contained in the first sequence or the second sequence) is also zero. That is to say, these zero sequences do not have the problem of ISI and MAI, and it is only necessary to ensure that the first sequence and the second sequence do not have ISI and MAI.
  • first sequence and the second sequence are constructed such that the first sequence and the second sequence do not have ISI and MAI.
  • the first sequence and the second sequence may be obtained from an LS code, so that an LS (Loosely Synchronized) code may be used to extend to multiple antennas, that is, each antenna is placed with a different sequence.
  • Multiple antennas (N ⁇ ⁇ 2) transmit training sequences. That is to say, the sequence unit included in the first sequence may be the sequence a or a' in the A portion, and the sequence unit included in the second sequence may be the sequence b or b' in the A portion.
  • the number H of sequence units included in the first sequence or the second sequence is related to the number of antennas N ⁇ , specifically:
  • the LS code is a code having a non-periodic mutually uncorrelated property.
  • Each codeword consists of two parts, called A and B.
  • the LS code can be constructed from a pair of complementary sequence pairs (a, b) and (a', b'), where:
  • L represents the length of the sequences a, b, a', b' in the complementary sequence pair (a, b), (a', b').
  • the LS code constructed by a pair of complementary sequence pairs (a, b) and (a', b') can be extended to multiple layers, and each layer LS code can include two parts: A part and B part. .
  • Each of the A and B sections of each layer of the LS code includes a plurality of sequences.
  • the A portion of the first layer LS code includes four sequences, specifically: (a, a'), (a, -a'), (a', a), (a', -a).
  • the B portion of the first layer LS code includes four sequences, specifically: (b, b'), (b, -b'), (b', b), (b', -b).
  • the first sequence when the number of transmitting antennas N ⁇ ⁇ 2, in the training sequence respectively transmitted by the N ⁇ antennas, the first sequence may be taken from multiple sequences of the A part in the ith layer LS code, The second sequence may be taken from a plurality of sequences of Part B of the ith layer LS code.
  • i is a positive integer
  • the number of transmitting antennas is four.
  • Four sequences may be selected from the A portion of the second layer LS code as the first sequence transmitted on the four antennas, and four sequences may be selected from the B portion of the second layer LS code as the four antennas.
  • the second sequence transmitted on Wherein the first sequence and the second sequence transmitted on the same antenna correspond to each other. That is, the first sequence and the second sequence transmitted on the same antenna may be the j-th sequence in the A part and the B part, respectively, and j is a positive integer, j ⁇ [1, 4].
  • the examples are merely illustrative of the embodiments of the invention and should not be construed as limiting.
  • the number of transmitting antennas is three.
  • Three sequences may be selected from the A portion of the Layer 2 LS code as the first sequence transmitted on the three antennas, and three sequences may be selected from the B portion of the second layer LS code as the three antennas.
  • the second sequence transmitted on Wherein the first sequence and the second sequence transmitted on the same antenna correspond to each other.
  • the examples are merely illustrative of the embodiments of the invention and should not be construed as limiting.
  • N ⁇ 4, that is, four transmit antennas.
  • the first sequence and the second sequence in the training sequence respectively transmitted by the four transmitting antennas may be respectively taken from a plurality of sequences in the A part and the B part in the second layer LS code. That is, the training sequence respectively transmitted by the four transmitting antennas can be as shown in FIG. Then, for the training sequences transmitted on the four antennas, the above four mathematical expressions can be specifically calculated as follows:
  • the training sequence transmitted on the four antennas does not have ISI and MAI, and does not adversely affect channel measurement in beam training, which facilitates accurate channel estimation. It should be noted that the above examples are merely used to explain the embodiments of the present invention and should not be construed as limiting.
  • the first sequence and the second sequence may be a, b sequences of complementary sequence pairs (a, b), respectively.
  • the accumulation of side lobes for the aperiodic autocorrelation based on the Golay complementary sequence is zero, and the channel estimation using the Golay complementary sequence has simple and excellent characteristics for channel estimation, and the Golay complementary sequence can be selected to construct the training sequence in the present application. That is to say, the complementary sequence pairs (a, b) and (a', b') of the above constructed LS code may be Golay complementary sequence pairs.
  • a Golay complementary sequence pair (a, b) of length L can be generated on Z H by: (m is a positive integer):
  • Z represents an integer ring
  • Z H represents a ring whose number of elements is H, and is a complete ring when H is a prime number.
  • ⁇ is the conversion of ⁇ 1,...,m ⁇ to itself, c i ⁇ Z H . length That is, the length and maximum delay of the a and b sequences in the (a, b) of the Golay complementary sequence are extended to T m and the symbol rate is R s correlation.
  • this application designs a Golay complementary sequence pair suitable for 802.11ay and future standards based on the Golay complementary sequence of length 128 in the 802.11ad standard for constructing training. sequence.
  • FIGS 11A-11F show Golay complementary sequence pairs of length 128, 256, 512, respectively, as provided herein.
  • two pairs of Golay complementary sequences of length 128 are represented as (Ga128 1 , Gb128 1 ), (Ga128 2 , Gb128 2 ), respectively.
  • 2 of 256 length Golay complementary sequences denoted as (Ga256 1, Gb256 1), (Ga256 2, Gb256 2).
  • Two pairs of Golay complementary sequences of length 512 are denoted as (Ga512 1 , Gb512 1 ), (Ga512 2 , Gb512 2 ), respectively.
  • Golay complementary sequences of lengths 1024 and 2048 may be constructed according to the short sequences given above, such as:
  • Ga1024 1 [Ga512 1 Gb512 1 ]
  • Gb10241 [Ga512 1 -Gb512 1 ]
  • Ga1024 2 [Ga512 2 Gb512 2 ]
  • Gb10242 [Ga512 2 -Gb512 2 ]
  • Ga2048 1 [Ga1024 1 Gb1024 1 ]
  • Gb20481 [Ga1024 1 -Gb1024 1 ]
  • Ga2048 2 [Ga1024 2 Gb10242 ]
  • Gb20482 [Ga1024 2 -Gb1024 2 ]
  • the complementary sequence pair used in the construction training sequence of the present application may be the Golay complementary sequence pair shown in FIG. 11A-11F, the Golay complementary sequence pair defined by the existing standard, or the sum of the cross correlations.
  • Other forms of Golay complementary sequence pairs of 0 are not limited here.
  • Golay complementary sequence pair which illustrates an embodiment of a training sequence for several antenna configurations provided by the present application under different channel conditions (maximum delay spread and symbol rate).
  • an LS code is constructed using two Golay complementary sequence pairs (Ga128 1 , Gb128 1 ), (Ga128 2 , Gb128 2 ) of length 128, which can be referred to FIG. 12A.
  • the training sequences transmitted by the two antennas can be as shown in Table 1:
  • the training sequences transmitted by the four antennas can be as shown in Table 2:
  • the training sequence transmitted by the eight antennas can be as shown in Table 3:
  • Golay complementary sequence of length 256 two Golay complementary sequence pairs are generated, which are specifically expressed as: (Ga256 1 , Gb256 1 ), (Ga256 2 , Gb256 2 ).
  • an LS code is constructed using two Golay complementary sequence pairs (Ga256 1 , Gb256 1 ), (Ga256 2 , Gb256 2 ) of length 256, which can be referred to FIG. 12B.
  • the training sequences transmitted by the two antennas can be as shown in Table 4:
  • the training sequences transmitted by the four antennas can be as shown in Table 5:
  • the training sequences transmitted by the eight antennas can be as shown in Table 6:
  • the first sequence and the second sequence may be Ga256 of complementary sequence pairs (Ga256 1 , Gb256 1 ), respectively. 1, Gb256 1 two parts, or a complementary sequence Ga256 2, Gb256 2 of the two portions (Ga256 2, Gb256 2) a. That is, the training sequence transmitted by the antenna can be as shown in Table 7A or 7B:
  • Golay complementary sequence of length 512 two Golay complementary sequence pairs are generated, which are specifically expressed as: (Ga512 1 , Gb512 1 ), (Ga512 2 , Gb512 2 ).
  • an LS code is constructed using two Golay complementary sequence pairs (Ga512 1 , Gb512 1 ), (Ga512 2 , Gb512 2 ) of length 512, which can be referred to FIG. 12C.
  • the training sequence transmitted by the two antennas can be as shown in Table 8:
  • the training sequences transmitted by the four antennas can be as shown in Table 9:
  • the training sequence transmitted by the eight antennas can be as shown in Table 10:
  • the first sequence and the second sequence may be Ga512 of complementary sequence pairs (Ga512 1 , Gb512 1 ), respectively. 1, Gb512 1 two parts, or a complementary sequence (Ga512 2, Gb512 2) of Ga512 2, Gb512 2 in two parts. That is, the training sequence transmitted by the antenna can be as shown in Table 11A or 11B:
  • Golay complementary sequence of length 512 two Golay complementary sequence pairs are generated, which are specifically expressed as: (Ga512 1 , Gb512 1 ), (Ga512 2 , Gb512 2 ).
  • an LS code is constructed using two Golay complementary sequence pairs (Ga512 1 , Gb512 1 ), (Ga512 2 , Gb512 2 ) of length 512, which can be referred to FIG. 12C.
  • the training sequence transmitted by the two antennas can be as shown in Table 12:
  • the training sequences transmitted by the four antennas can be as shown in Table 13:
  • the training sequences transmitted by the eight antennas can be as shown in Table 14:
  • the first sequence and the second sequence may be Ga512 of complementary sequence pairs (Ga512 1 , Gb512 1 ), respectively. 1, Gb512 1 two parts, or a complementary sequence (Ga512 2, Gb512 2) of Ga512 2, Gb512 2 in two parts. That is, the training sequence transmitted by the antenna can be as shown in Table 15A or 15B:
  • Golay complementary sequence of length 1024 two Golay complementary sequence pairs are generated, which are specifically expressed as: (Ga1024 1 , Gb1024 1 ), (Ga1024 2 , Gb1024 2 ).
  • the training sequences transmitted by the two antennas can be as shown in Table 16:
  • the training sequences transmitted by the four antennas can be as shown in Table 17:
  • the training sequence transmitted by the eight antennas can be as shown in Table 18:
  • the first sequence and the second sequence may be Ga1024 of complementary sequence pairs (Ga1024 1 , Gb1024 1 ), respectively. 1 , Gb1024 1 two parts, or Ga1024 2 , Gb1024 2 two parts of complementary sequence pairs (Ga1024 2 , Gb1024 2 ). That is, the training sequence transmitted by the antenna can be as shown in Table 19A or 19B:
  • Golay complementary sequence pairs were generated using the Golay complementary sequence of length 2048, specifically: (Ga2048 1 , Gb2048 1 ), (Ga2048 2 , Gb2048 2 ).
  • Golay complementary sequence pair 2048 (Ga2048 1, Gb2048 1), (Ga2048 2, Gb2048 2 ) Construct an LS code (not shown).
  • the training sequence transmitted by the two antennas can be as shown in Table 20:
  • the training sequences transmitted by the four antennas can be as shown in Table 21:
  • the training sequences transmitted by the eight antennas can be as shown in Table 22:
  • the first sequence and the second sequence may be Ga2048 of complementary sequence pairs (Ga2048 1 , Gb2048 1 ), respectively. 1 , Gb2048 1 two parts, or the complementary sequence pair (Ga2048 2 , Gb2048 2 ) Ga2048 2 , Gb2048 2 two parts. That is, the training sequence transmitted by the antenna can be as shown in Table 23A or 23B:
  • FIG. 13 is a schematic structural diagram of a wireless communication system and a transmitting device and a receiving device in a wireless system provided by the present application.
  • the wireless communication system 20 includes a first communication device 400 and a second communication device 500.
  • the first communication device 400 can be implemented as the transmitting device 200 shown in FIG. 4, and the second communication device 500 can be implemented as the receiving device 300 shown in FIG. 5.
  • the first communication device 400 or the second communication device 500 may be a communication device implemented by combining the transmitting device 200 shown in FIG. 4 and the receiving device 300 shown in FIG. 5. The description is expanded below.
  • the first communication device 400 can include a processing unit 403 and a transmitting unit 401. among them:
  • the processing unit 403 can be configured to configure a training sequence corresponding to each of the N ⁇ (N ⁇ is a positive integer) antennas, so that the training sequence configured for each antenna satisfies the foregoing conditions (1)-(4).
  • the training sequence corresponding to each antenna may include M sequence units of the same length, and M is an integer.
  • the processing unit 403 is further configured to encapsulate the training sequences corresponding to the respective antennas in the data packets for beam optimization corresponding to the respective antennas.
  • the data packet for beam optimization may specifically be a Beam Optimization Protocol (BRP) data packet.
  • the training sequence may be included in the beam training field TRN field in the BRP data packet, and may be specifically included in the T/R field, and may be referred to the IEEE 802.11ad protocol, which is not described here.
  • BRP Beam Optimization Protocol
  • the transmitting unit 401 can be configured to transmit the data packet for beam optimization through N ⁇ antennas.
  • the second communication device 500 can receive the data packet, obtain the training sequence therefrom, and perform channel estimation based on the training sequence.
  • the first communication device 400 may further include a receiving unit, configured to receive a channel estimation result returned by the second communication device 500. Processing unit 403 can then adjust the antenna configuration based on the channel estimation results.
  • the second communication device 500 can include a receiving unit 501 and a processing unit 503.
  • the receiving unit 501 is configured to receive the data packet for beam optimization that is transmitted by the first communications device 400 through the N ⁇ antennas, where the data packets each include a training sequence.
  • the processing unit 503 can be configured to decapsulate the data packet, acquire the training sequence, and perform channel estimation based on the training sequence.
  • the second communication device 500 may further include a transmitting unit for returning the channel estimation result to the first communication device 400. In this way, the first communication device 400 can adjust the antenna configuration according to the channel estimation result.
  • the wireless communication system 20 of the present application may be specifically implemented as the wireless communication system 100 shown in FIG. 3, the wireless communication system 20 may be a MIMO system, and the Massive MIMO system may also be a SIMO system or a MISO system. Wireless communication system 20 can also be a SISO system.
  • the embodiment of the present invention can not only avoid the ISI and MSI pair beams by configuring the training sequence transmitted by each antenna to satisfy the above conditions (1)-(4) under different channel conditions and different antenna configurations.
  • the adverse effects of channel measurement in training can meet the requirements of accurate channel estimation using beamforming training sequences in different application scenarios, and can also reduce the requirement for synchronization accuracy.
  • by inserting a zero sequence into the training sequence transmitted by each antenna it is also possible to simplify the training sequence and reduce the signaling overhead.
  • constructing the training sequence using Golay complementary sequence pairs can also simplify the channel estimation process.
  • the program can be stored in a computer readable storage medium, when the program is executed
  • the flow of the method embodiments as described above may be included.
  • the foregoing storage medium includes various media that can store program codes, such as a ROM or a random access memory RAM, a magnetic disk, or an optical disk.

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Abstract

本发明实施例公开了一种信号传输方法、相关装置及系统。所述方法可包括：通过Nτ个天线发射用于波束优化的数据包，Nτ是正整数，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零。上述方案可满足不同应用场景下利用波束成形训练序列进行准确信道估计的需求。

Description

信号传输方法、相关设备及系统 技术领域
本申请涉及无线通信技术领域，尤其涉及信号传输方法、相关设备及系统。
背景技术
通信系统可应用波束成形(Beamforming)技术提高通信性能。波束成形技术需要明确知道信道状态信息，接收端需要将完整的信道状态信息反馈给发射端。在传统的波束成形的训练过中，发射端向接收端发送一个或多个波束成形训练序列。然后，接收端利用接收到的训练序列估计信道特性，并将信道估计结果返回至发射端。最后，发射端根据接收端返回的信道估计估计结果调整发射天线配置。
从相关文献来看，就波束训练而言，大多以检测信道质量为目的，所用训练序列均用于信道估计。
1986年，Scott Foster在文献“Impulse Response Measurement using Golay Codes”,Proc.Of IEEE ICASSP,1986中提出利用二元Golay互补序列的自相关互补特性，通过简单的时域相关运算计算得到信道的时域单位冲击响应。基于Golay互补序列的时域信道估计的基本原理是利用一对Golay互补对非周期自相关累加旁瓣为零的特点，获得信道时延各径的信道响应。采用Golay互补序列的时域信道估计具有信道估计实现简单的最大优点，接收端只需要在接收到两个Golay互补序列的基础上，采用两个相关器执行相关运算后累加相关运算结果即可得到各径信道增益。
2008年，Ryota Kimura和Ryuhei Funada等在文献“Golay Sequence Aided Channel Estimation for Millimeter-wave WPAN Systems”,in Proc.Of IEEE PIMRC 2008中讨论了一种基于Golay序列的SISO信道估计方案，研究结果表明，基于Golay序列的信道估计能在毫米波段单载波通信系统中获得满意的信道估计性能，单载波传输条件下基于Golay序列的信道估计无论从性能还是硬件实现方面都优于Zadoff-Chu序列。在SISO条件下，基于Golay序列的单载波频域均衡(Single-carrier Frequency Domain Equalization，SC-FDE)性能在非视距衰落环境下与理想信道估计条件下的性能只差1.8dB，不失为一种能满足实际SISO系统应用要求的信道估计方案。
现有技术中，目前存在下面几种训练序列的设计方案。
(1)现有技术一：IEEE 802.11ad中的TRN field(波束训练字段)设计
在IEEE 802.11ad标准中，不仅使用Golay互补序列来做信道估计，而且用于进行波束(天线权重向量)训练，充分利用了Golay互补序列的自相关互补特性，即接收训练序列和发送训练序列的自相关等于信道冲激响应。
图1A-1C分别示出了IEEE802.11ad标准中采用的两个Golay互补序列(G a128、G b128)、波束优化数据帧(Beam Refinement Packet，BRP)的帧结构及TRN field的定义。
其中，IEEE 802.11ad中的波束训练字段TRN field由N(N<17，N是正整数)个TRN-Unit组成，其中每个TRN-Unit分为信道估计(Channel Estimation，CE)字段和T/R两部分，CE字段由8个长度为128的Golay互补序列(G a128、G b128)与其前后放置的循环前缀和 循环后缀组成，可以满足72ns(128*0.57ns＝72ns)时延扩展范围内多径信道估计要求。每个T/R字段包含序列[G a128-G b128G a128G b128Ga128]，利用时域测量方法可以对信道进行粗略测量，也可以在频域对信道做出准确估计。
现有技术一的缺点：IEEE 802.11ad标准中，训练序列的设计仅针对于单天线下的信道测量，并未涉及MIMO多信道并行发送波束训练进行信道测量的设计,不能满足MIMO并行训练场景下的信道测量需求。因此在MIMO场景中无法计算出每种天线配置下所用波束的信道质量，进而无法在并行训练过程中得到发送天线和接收天线的最优天线配置。
(2)现有技术二：级联训练序列(可参考中国专利CN 101682377A)
具体的，施训端传输并发送至少一个级联训练序列，可选择性的使用多个方案调制训练序列后进行级联，将该级联序列发送至该一或多个受训端。所述训练序列可如图2所示，所述级联训练序列包括前导和多个已调制训练序列b-seq 1，b-seq 2，…，b-seq n。
现有技术二的缺点：仅仅解决了一对多条件下的波束训练问题，并不适合在多对多场景下进行信道估计。
发明内容
本申请提供了一种信号传输方法，可满足不同应用场景下利用波束成形训练序列进行准确信道估计的需求。
第一方面，本申请提供了一种信号传输方法，应用于发射端，所述方法包括：通过Nτ个天线发射用于波束优化的数据包，Nτ是正整数，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列。
第二方面，本申请提供了一种信号传输方法，应用于接收端，所述方法包括：接收端接收发射端通过N τ个天线分别发送的N τ个用于波束优化的数据包，Nτ是正整数；其中，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列。所述接收端还可以利用所述数据包中的所述训练序列进行信道估计。
结合第一方面和第二方面，每一个天线发射的训练序列均包括M个长度相同的序列单元，M是整数。而且，配置给各个天线的训练序列满足下述条件：
(1)同一个天线对应的训练序列中，各个序列单元的自相关之和为零；
(2)同一个天线对应的训练序列中，全部的两个相邻序列单元之间的互相关之和为零。(3)任意2个天线分别对应的训练序列中，全部的对应相同序列号的两个序列单元之间的互相关之和为零。
(4)任意2个天线分别对应的训练序列中，全部的的对应相邻序列号的两个序列单元之间的互相关之和为零。
可以理解的，上述条件(1)表示在存在多径效应的情况下，天线t发射的训练序列在传输过程中由多径引起的累加ISI为0，不会对波束训练中的信道测量产生不利影响。上述条件(2)表示在存在时间扩散的情况下，天线t发射的训练序列在传输过程中由时间扩散效应引起的累加ISI为0，不会对波束训练中的信道测量产生不利影响。上述条件(3)表示在传输过程中，不同天线发射的训练序列之间的累加MAI为0，不会对波束训练中的信道测量产生不利影响。上述条件(3)表示在传输过程中，由于时间扩散效应引起的不同天 线发射的训练序列之间的累加MAI为0，不会对波束训练中的信道测量产生不利影响。即，各个天线上发射的训练序列不存在ISI和MAI，不会对波束训练中的信道测量产生不利影响，利于进行准确的信道估计。
结合第一方面或第二方面，在一些可选的实施例中，单个天线发射的训练序列可包括第一序列、第二序列，以及所述第一序列和所述第二序列的之间的第一零序列。其中，所述第一序列和所述第二序列均可包括H个所述序列单元，H是正整数，2*H＜M。所述第一零序列可包括Z1个所述序列单元，Z1是正整数，Z1+2*H≤M。也即是说，所述训练序列的中间片段为零，这样可以使得训练序列的构造更简单，减少信令开销。
结合第一方面或第二方面，在一些可选的实施例中，单个天线发射的训练序列的首尾两个片段还可以为零。即：单个天线发射的训练序列还可包括第二零序列和第三零序列，其中，所述第二零序列插入在所述第一序列的前面，所述第三零序列插入在所述第二序列的后面。所述第二零序列、所述第三零序列的长度分别为Z2、Z3个所述子序列，Z1+Z2+Z3+2*H＝M。这样，可以进一步的简单化训练序列，减少信令开销。
结合第一方面或第二方面，在一些可选的实施例中，可以从LS码中获取所述第一序列和所述第二序列，这样可以利用LS码扩展至多天线，即每条天线放置不同的序列，实现多天线(Nτ≥2)发射训练序列。也即是说，所述第一序列包括的序列单元可以是A部中的序列a或a'，所述第二序列包括的序列单元可以是A部中的序列b或b'。具体的，所述第一序列或所述第二序列包含的序列单元的个数H与天线数量Nτ相关，具体为：
Figure PCTCN2018082409-appb-000001
下面具体描述从LS码中获取训练序列的具体实现。
这里，LS码可由一对互补序列对(a,b)与(a',b')构造，其中：每个互补序列对满足：R a,a'(τ)+R b,b'(τ)＝0,R a,a(τ)+R b,b(τ)＝0。这两个互补序列对之间满足：R a,a'(τ)+R b,b'(τ)＝0,0≤|τ|＜L。其中，L表示互补序列对(a,b)、(a',b')中的序列a、b、a'、b'的长度。
具体的，当发射天线数量Nτ≥2时，在Nτ个天线各自发射的所述训练序列中，所述第一序列可以取自第i层LS码中的A部的多个序列，所述第二序列可以取自第i层LS码中的B部的多个序列。这里，i是正整数，
Figure PCTCN2018082409-appb-000002
例如，假设发射天线个数为4个，
Figure PCTCN2018082409-appb-000003
可以从第2层LS码中的A部选择4个序列作为这4个天线上发射的所述第一序列，可以从第2层LS码中的B部相应选择4个序列作为这4个天线上发射的所述第二序列。其中，同1个天线上发射的所述第一序列和所述第二序列是相对应的。即：同1个天线上发射的所述第一序列和所述第二序列可以分别是A部、B部中的第j个序列，j是正整数，j∈[1,4]。示例仅仅用于解释本发明实施例，不应构成限定。
例如，假设发射天线个数为3个，
Figure PCTCN2018082409-appb-000004
可以从第2层LS码中的A部选择3个序列作为这3个天线上发射的所述第一序列，可以从第2层LS码中的B部相应选择3个序列作为这3个天线上发射的所述第二序列。其中，同1个天线上发射的所述第一序列和所述第二序列是相对应的。示例仅仅用于解释本发明实施例，不应构成限定。
可以理解的，通过从LS码中获取各个天线上发射的训练序列中的所述第一序列和所述 第二序列，可实现Nτ个天线各自发射的训练序列(图8A或图8B所示)满足上述条件(1)-(4)。也即是说，各个个天线上发射的训练序列不存在ISI和MAI，不会对波束训练中的信道测量产生不利影响，利于进行准确的信道估计。
具体的，当发射天线数量Nτ＝1时，天线发射的所述训练序列中，所述第一序列和所述第二序列可以分别是互补序列对(a,b)的a、b序列。这里，互补序列对(a,b)满足：R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L，L是互补序列对(a,b)、(a',b')中的序列a、b、a'、b'的长度。
在一些可选的实施例中，基于Golay互补序列对非周期自相关累加旁瓣为零，以及利用Golay互补序列进行信道估计具有信道估计实现简单的优良特性，可以选择Golay互补序列来构造本申请中的训练序列。也即是说，上述构造LS码的互补序列对(a,b)与(a',b')可以是Golay互补序列对。这时，Golay互补序列对(a,b)中的a、b序列的长度L和最大时延扩展为T m、符号速率为R s相关：
Figure PCTCN2018082409-appb-000005
其中，信道的最大时延扩展为T m，符号速率为R s。
第三方面，本申请提供了一种通信装置，包括多个功能模块，用于相应的执行第一方面所提供的方法，或者第一方面可能的实施方式中的任意一种所提供的方法。
第四方面，本申请提供了一种通信装置，包括多个功能模块，用于相应的执行第二方面所提供的方法，或者第二方面可能的实施方式中的任意一种所提供的方法。
第五方面，提供了一种通信装置，用于执行第一方面描述的信号传输方法。所述通信装置可包括：存储器以及与所述存储器耦合的处理器、发射器，其中：所述发射器用于通过Nτ个天线发射用于波束优化的数据包，Nτ是正整数，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零。所述存储器用于存储第一方面描述的信号传输的实现代码，所述处理器用于执行所述存储器中存储的程序代码，即执行第一方面所提供的方法，或者第一方面可能的实施方式中的任意一种所提供的方法。
第六方面，提供了一种通信装置，用于执行第二方面描述的信号传输方法。所述通信装置可包括：存储器以及与所述存储器耦合的处理器、接收器，其中：所述接收器用于接收N τ个用于波束优化的数据包，所述N τ个所述数据包是由发射端通过N τ个天线分别发送的，Nτ是正整数；其中，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零。所述存储器用于存储第二方面描述的信号传输方法的实现代码，所述处理器用于执行所述存储器中存储的程序代码，即执行第二方面所提供的方法，或者第二方面可能的实施方式中的任意一种所提供的方法。
第七方面，提供了一种通信系统，所述通信系统包括：第一通信装置和第二通信装置。
在一种实现方式中，所述第一通信装置可以是第三方面或第五方面描述的网络设备，所述第二通信装置可以是第四方面或第六方面描述的网络设备。
第八方面，提供了一种计算机可读存储介质，所述可读存储介质上存储有实现第一方面或第二方面描述的方法的程序代码，该程序代码包含运行第一方面或第二方面描述的方法的执行指令。
附图说明
为了更清楚地说明本发明实施例或背景技术中的技术方案，下面将对本发明实施例或背景技术中所需要使用的附图进行说明。
图1A是现有802.11ad协议中定义的一个Golay互补序列对的示意图；
图1B是现有802.11ad协议中定义的波束优化协议(BRP)数据包的结构示意图；
图1C是现有802.11ad协议中定义的波束优化协议(BRP)数据包中波束训练字段(TRN-R/T field)的结构示意图；
图2是现有的一种训练序列的结构示意图；
图3是本申请涉及的无线通信系统的架构示意图；
图4是本申请的一个实施例提供的发射机的硬件架构示意图；
图5是本申请的一个实施例提供的接收机的硬件架构示意图；
图6是本申请的一个实施例提供的信号传输方法的流程示意图；
图7是本申请提供的多个天线各自发射的训练序列的结构示意图；
图8A-8B是本申请提供的训练序列的结构示意图；
图9是本申请的涉及的一种构造LS码的方法示意图；
图10A-10B是本申请提供的另外两种训练序列的结构示意图；；
图11A-11F是本申请提供的各种长度的Golay互补序列对的数据示意图；
图12A-12C是本申请提供的三种利用Golay互补序列对构造LS码的方法示意图；
图13是本申请提供的无线通信系统、发射装置以及接收装置的结构示意图。
具体实施方式
本发明的实施方式部分使用的术语仅用于对本发明的具体实施例进行解释，而非旨在限定本发明。
图3示出了本申请涉及的一种无线通信系统。如图3所示，无线通信系统100可包括至少一个发射机101和至少一个接收机102。其中，发射机101和接收机102两端均可安装有一根或多根天线，发射天线数目为N T，接收天线数目为N R。在数据传输过程中，发射机101对数据进行处理后产生N T路数据流，每一路数据流从不同的发射天线同时、同频发射，经过空间信道衰落后，来自不同的发射天线的信号以及噪声在每一根天线上进行叠加，最后送入接收机进行处理。
为了在传输数据前获得最优的发射端天线配置，可以对发射机101进行基于训练序列的波束成形训练。具体的，发射机101可以向接收机102发送训练序列。相应的，接收机 102可以利用发射机101发送的训练序列进行信道估计，并将估计结果返回至发射机101。这样，发射机101便可以根据接收机102返回的信道估计结果来调整发射天线阵列波束成形向量，以优化发射天线配置。
同样的，为了在传输数据前获得最优的接收端天线配置，可以对接收机102进行基于训练序列的波束成形训练。具体的，接收机102也可以向发射机发送训练序列。相应的，发射机101可以利用接收机102发送的训练序列进行信道估计，并将估计结果返回至接收机102.这样，接收机102便可以根据发射机101返回的信道估计结果来调整接收天线阵列的波束成形向量，以优化接收天线配置。
本申请中，在波束训练过程中，不仅要考虑同一个天线上由于多径效应导致的符号间干扰(Inter Symbol Interference，ISI)，还要考虑各个天线之间的多址干扰(Multi Access Interference，MAI)。为了准确的估计信道，训练序列的接收需要避免ISI和MAI。
本申请中，无线通信系统100可以支持多种最大时延扩展，例如72ns、300ns等。无线通信系统100也可以支持多种符号速率，例如1.76Gbps、3.52Gbps、5.28Gbps或7.04Gbps等。
需要说明的，无线通信系统100可以是MIMO系统，Massive MIMO系统也可以是SIMO系统、MISO系统。无线通信系统100还可以是SISO系统。后续会分别介绍本申请在这几种不同系统下的具体实施方式。
图4示出了本申请提供的一种发射装置的架构示意图。如图4所示，发射装置200可包括：一个或多个处理器201、存储器202、通信接口203、发射器205、以及天线206。这些部件可通过总线204或者其他方式连接，图4以通过总线连接为例。其中：
天线206可用于发射信号。本申请中，天线206可以是天线阵列，包括多个发射天线。
发射器205可用于对处理器201输出的信号进行发射处理，例如通过波束成形实现定向发送。具体实现中，发射器205可包括MIMO编码模块2051、数模转换器(Digital to Analog Converter，DAC)2051、混频器2053、波束成形控制器2054、功率放大器(Power Amplifier，PA)2055。其中，MIMO编码模块2051可用于通过预编码来改善信道特性，使传输的信号更好地匹配信道条件，以获得更好的传输质量。数模转换器2051和混频器2053可用于将数字信号转换成模拟信号，并进行混频，混频后的信号输出到波束成形控制器2054。波束成形控制器2054可用于对发送信号乘以发送权重向量W 1，……，W m，控制信号的定向发射。功率放大器2055可用于对波束成形控制器2054输出的信号进行功率放大，并输出至天线206。需要说明的，发射器2052还可以包括其他用于信号发射处理的器件，例如滤波器、变频器等，这里不作限制。
本申请中，在数据传输之前，发射器205可具体用于发射用于波束成形训练的训练序列。具体的，波束成形控制器2054可用于根据接收端返回的基于该训练序列的信道估计结果，来调整发送权重向量W1，……，W，直至最优。
通信接口203可用于发射装置200与其他通信设备进行通信。具体实现中，通信接口203可以是无线局域网接口(Wireless Local Access Network，WLAN)等无线通信接口，可支持802.11b协议、802.11a协议、802.11g协议、802.11e协议、802.11i协议等。需要说明的， 通信接口203还可以包括有线的通信接口，例如局域接入网(Local Access Network，LAN)接口等，这里不作限制。
存储器202与处理器201耦合，用于存储各种软件程序和/或多组指令。具体的，存储器202可包括高速随机存取的存储器，并且也可包括非易失性存储器，例如一个或多个磁盘存储设备、闪存设备或其他非易失性固态存储设备。存储器202可以存储操作系统(下述简称系统)，例如LINUX等嵌入式操作系统。
在本申请的一些实施例中，存储器202可用于存储本申请的一个或多个实施例提供的信号传输方法的实现程序。关于本申请的一个或多个实施例提供的信号传输方法的实现，请参考后续实施例。
处理器201可用于读取和执行计算机可读指令。具体的，处理器201可用于调用存储于存储器202中的程序，例如本申请的一个或多个实施例提供的信号传输方法的实现程序，并执行该程序包含的指令。
可以理解的，发射装置200可以是图3示出的无线通信系统100中的发射机101，可实施为无线发射器，接入点，移动设备，移动台(mobile station)，移动单元(mobile unit)等等。
需要说明的，图4所示的发射装置200仅仅是本申请实施例的一种实现方式，实际应用中，发射装置200还可以包括更多或更少的部件，这里不作限制。在一些可能的实施例中，发射装置200还可以实施成支持多用户MIMO(Multi-User MIMO，MU-MIMO)的发射装置，配置有多个发射天线阵列。
图5示出了本申请提供的一种接收装置的架构示意图。如图5所示，接收装置300可包括：一个或多个处理器301、存储器302、通信接口303、接收器305、以及天线306。这些部件可通过总线304或者其他方式连接，图5以通过总线连接为例。其中：
天线306可用于接收信号。本申请中，天线306可以是天线阵列，包括多个接收天线。
接收器305可用于对天线306接收的射频信号进行接收处理，例如通过波束成形实现定向接收。具体实现中，接收器305可包括功率放大器(Power Amplifier，PA)3055、波束成形控制器3054、混频器3053、模数转换器(Analog to Digital Converter，ADC)3051、MIMO解码模块3051。其中，功率放大器2055可用于放大接收功率，将天线306接收到射频信号输出至波束成形控制器3054。波束成形控制器3054可用于对接收信号乘以接收权重向量W 1，……，W m，控制信号的定向接收。混频器2053和模数转换器3051可用于将接收信号进行混频，并将混频后的模拟信号转换成数字信号，并输出到波束成形控制器2054。MIMO解码模块3051可用于对已进行MIMO编码的接收信号进行解码，重建发射信号。需要说明的，接收器3052还可以包括其他用于信号接收处理的器件，例如滤波器、变频器等，这里不作限制。
本申请中，在数据传输之前，接收305可具体用于接收用于波束成形训练的训练序列。具体的，波束成形控制器3054可用于基于该训练序列进行信道估计，并将信道估计结果返回至发射端，便于发射端根据返回的信道估计结果来调整发送天线的配置，直至最优。
通信接口303可用于接收装置300与其他通信设备进行通信。具体实现中，通信接口 303可以是无线局域网接口(WLAN)等无线通信接口，可支持802.11b协议、802.11a协议、802.11g协议、802.11e协议、802.11i协议等。需要说明的，通信接口303还可以包括有线的通信接口，例如局域接入网(LAN)接口等，这里不作限制。
存储器302与处理器301耦合，用于存储各种软件程序和/或多组指令。具体的，存储器302可包括高速随机存取的存储器，并且也可包括非易失性存储器，例如一个或多个磁盘存储设备、闪存设备或其他非易失性固态存储设备。存储器302可以存储操作系统(下述简称系统)，例如LINUX等嵌入式操作系统。
在本申请的一些实施例中，存储器302可用于存储本申请的一个或多个实施例提供的信号传输方法的实现程序。关于本申请的一个或多个实施例提供的信号传输方法的实现，请参考后续实施例。
处理器301可用于读取和执行计算机可读指令。具体的，处理器301可用于调用存储于存储器302中的程序，例如本申请的一个或多个实施例提供的信号传输方法的实现程序，并执行该程序包含的指令。
可以理解的，接收装置300可以是图3示出的无线通信系统100中的接收机102，可实施为无线接收器，接入点，移动设备，移动台(mobile station)，移动单元(mobile unit)等等。
需要说明的，图5所示的接收装置300仅仅是本申请实施例的一种实现方式，实际应用中，接收装置300还可以包括更多或更少的部件，这里不作限制。在一些可能的实施例中，接收装置300还可以实施成支持多用户MIMO(Multi-User MIMO，MU-MIMO)的接收装置，配置有多个接收天线阵列。
需要说明的，实际应用中，图4所示的发射装置200和图5所示的接收装置300可结合实施在同一硬件设备中，即本申请涉及的发射端或接收端可以为集成有发射装置200中的发射器205和接收装置300中的接收器305的通信设备。
基于前述无线通信系统100、发射装置200和接收装置300，本申请提供了一种信号传输方法，可满足不同应用场景下利用波束成形训练序列进行准确信道估计的需求。
本申请的主要发明原理可包括：在波束成形训练过程中，配置各个天线上传输的训练序列，其中，同一个天线上发射的训练序列所对应的累加的符号间干扰ISI为0，任意两个天线上分别发射的训练序列之间的累加的多址干扰MAI为0。这样，可避免符号间干扰ISI和多址干扰MAI对波束训练中信道测量的不利影响，可实现通过传输在所述各个天线上的训练序列进行准确的信道估计。
参考图6，下面介绍本申请提供的信号传输方法的总体方案。具体展开如下：
S101，发射端可以配置Nτ个天线各自对应的训练序列，用于波束成形训练。Nτ是正整数，本申请对Nτ的取值不作限制。
其中，每一个天线对应的训练序列包括M个长度相同的序列单元，M是整数。而且，配置给各个天线的训练序列满足下述条件：
(1)同一个天线对应的训练序列中，各个序列单元的自相关之和为零；
(2)同一个天线对应的训练序列中，全部的两个相邻序列单元之间的互相关之和为零。
(3)任意2个天线分别对应的训练序列中，全部的对应相同序列号的两个序列单元之间的互相关之和为零。
(4)任意2个天线分别对应的训练序列中，全部的的对应相邻序列号的两个序列单元之间的互相关之和为零。
举例来说，Nτ个天线各自对应的训练序列如图7所示。其中，序列单元
Figure PCTCN2018082409-appb-000006
表示天线j发射的训练序列中的第i个序列单元。本申请对序列单元的长短不作限制，对M的取值不作限制，可根据实际需求确定。上述4个条件具体可以通过下述几个数据表达式来表示(R表示相关函数)：
Figure PCTCN2018082409-appb-000007
这里，数学表达式(1)表示上述条件(1)，τ≠0表示存在多径效应。数学表达式(1)具体表示：在存在多径效应的情况下，天线t发射的训练序列在传输过程中由多径引起的累加ISI为0，不会对波束训练中的信道测量产生不利影响。
Figure PCTCN2018082409-appb-000008
这里，数学表达式(2)表示上述条件(2)，τ≠0表示存在时间扩散效应。时间扩散对发射信号的影响是造成相邻符号之间在时间上重叠，也会引起符号间干扰。数学表达式(2)具体表示：在存在时间扩散的情况下，天线t发射的训练序列在传输过程中由时间扩散效应引起的累加ISI为0，不会对波束训练中的信道测量产生不利影响。
应理解的，由于训练序列中的相邻码块之间的互相关之和为0，即时间扩散效应引起的累加ISI为0。因此，训练序列传输过程对同步精度的要求并不高，可以容忍较小的不同步。
Figure PCTCN2018082409-appb-000009
这里，数学表达式(3)表示上述条件(3)，具体表示：在传输过程中，天线t发射的训练序列和天线q发射的训练序列之间的累加MAI为0，不会对波束训练中的信道测量产生不利影响。
Figure PCTCN2018082409-appb-000010
这里，数学表达式(4)表示上述条件(4)，具体表示：在传输过程中，由于时间扩散效应引起的天线t发射的训练序列和天线q发射的训练序列之间的累加MAI为0，不会对波束训练中的信道测量产生不利影响。
应理解的，由于不同天线发射的训练序列之间因时间扩散效应引起的累加ISI为0。因此，训练序列传输过程对同步精度的要求并不高，可以容忍较小的不同步。
S102，发射端通过Nτ个天线发射用于波束优化的数据包，其中，每一个天线发射的所述数据包均包含所述天线发射的训练序列。这里，所述用于波束优化的数据包具体可以为波束优化协议(Beam Refinement Protocol，BRP)数据包。所述训练序列可以包含在BRP数据包中的波束训练字段TRN field中，具体可包含在T/R字段中，可参考IEEE 802.11ad协议，这里不赘述。
S103-S104，相应的，接收端可以接收到发射端发送的所述用于波束优化的数据包，并 提取出Nτ个训练序列，并可以基于接收到的训练序列进行信道估计，并将信道估计结果返回给发射端。
S105，最后，发射端可以根据接收端返回的信道估计结果调整天线配置。
下面详细描述满足上述条件(1)-(4)的训练序列的实现方式。
如图8A所示，在一些可选的实施例中，单个天线发射的训练序列可包括第一序列、第二序列，以及所述第一序列和所述第二序列的之间的第一零序列。其中，所述第一序列和所述第二序列均可包括H个所述序列单元，H是正整数，2*H＜M。所述第一零序列可包括Z1个所述序列单元，Z1是正整数，Z1+2*H≤M。也即是说，所述训练序列的中间片段为零，这样可以使得训练序列的构造更简单，减少信令开销。
如图8B所示，在一些可选的实施例中，单个天线发射的训练序列的首尾两个片段还可以为零。即：在图8A的基础上，单个天线发射的训练序列还可包括第二零序列和第三零序列，其中，所述第二零序列插入在所述第一序列的前面，所述第三零序列插入在所述第二序列的后面。所述第二零序列、所述第三零序列的长度分别为Z2、Z3个所述子序列，Z1+Z2+Z3+2*H＝M。这样，可以进一步的简单化训练序列，减少信令开销。
可以理解的，由于所述第一零序列、所述第二零序列和所述第三零序列均全为0，因此这些零序列的自相关之和为0，这些零序列与相邻的非零的序列单元(包含于所述第一序列或所述第二序列)之间的互相关之和也为0。也即是说，这些零序列不存在ISI和MAI的问题，只需确保所述第一序列和所述第二序列不存在ISI和MAI即可。
下面详细说明，如何构造所述第一序列和所述第二序列，使得所述第一序列和所述第二序列不存在ISI和MAI。
在一些可选的实施例中，可以从LS码中获取所述第一序列和所述第二序列，这样可以利用LS(Loosely Synchronized)码扩展至多天线，即每条天线放置不同的序列，实现多天线(Nτ≥2)发射训练序列。也即是说，所述第一序列包括的序列单元可以是A部中的序列a或a'，所述第二序列包括的序列单元可以是A部中的序列b或b'。具体的，所述第一序列或所述第二序列包含的序列单元的个数H与天线数量Nτ相关，具体为：
Figure PCTCN2018082409-appb-000011
应理解的，LS码是一种具有非周期互不相关性质的码。每个码字都包含两部分，分别称为A部和B部。LS码可由一对互补序列对(a,b)与(a',b')构造，其中：
每个互补序列对满足：
R a,a'(τ)+R b,b'(τ)＝0,R a,a(τ)+R b,b(τ)＝0
这两个互补序列对之间满足：
R a,a'(τ)+R b,b'(τ)＝0,0≤|τ|＜L
其中，L表示互补序列对(a,b)、(a',b')中的序列a、b、a'、b'的长度。
如图9所示，由一对互补序列对(a,b)与(a′,b′)构造的LS码可扩展至多层，每一层LS码均可包括两部分：A部和B部。每一层LS码的A部、B部均包括多个序列。例如，第1层LS码的A部包括4个序列，具体为：(a,a')、(a,-a')、(a',a)、(a',-a)。第1层LS码的B部包括4个序列，具体为：(b,b')、(b,-b')、(b',b)、(b',-b)。
本申请中，当发射天线数量Nτ≥2时，在Nτ个天线各自发射的所述训练序列中，所述 第一序列可以取自第i层LS码中的A部的多个序列，所述第二序列可以取自第i层LS码中的B部的多个序列。这里，i是正整数，
Figure PCTCN2018082409-appb-000012
例如，假设发射天线个数为4个，
Figure PCTCN2018082409-appb-000013
可以从第2层LS码中的A部选择4个序列作为这4个天线上发射的所述第一序列，可以从第2层LS码中的B部相应选择4个序列作为这4个天线上发射的所述第二序列。其中，同1个天线上发射的所述第一序列和所述第二序列是相对应的。即：同1个天线上发射的所述第一序列和所述第二序列可以分别是A部、B部中的第j个序列，j是正整数，j∈[1,4]。示例仅仅用于解释本发明实施例，不应构成限定。
又例如，假设发射天线个数为3个，
Figure PCTCN2018082409-appb-000014
可以从第2层LS码中的A部选择3个序列作为这3个天线上发射的所述第一序列，可以从第2层LS码中的B部相应选择3个序列作为这3个天线上发射的所述第二序列。其中，同1个天线上发射的所述第一序列和所述第二序列是相对应的。示例仅仅用于解释本发明实施例，不应构成限定。
可以理解的，通过从LS码中获取各个天线上发射的训练序列中的所述第一序列和所述第二序列，可实现Nτ个天线各自发射的训练序列(图8A或图8B所示)满足上述条件(1)-(4)。
举例说明，假设Nτ＝4，即4个发射天线。这4个发射天线各自发射的训练序列中的所述第一序列和所述第二序列可分别取自第2层LS码中的A部、B部中的多个序列。即，这4个发射天线各自发射的训练序列可以如图10所示。那么，针对这4个天线上发射的训练序列，前述4个数学表达式可具体运算如下：
上述数学表达式(1)具体为(以天线1为例)：
Figure PCTCN2018082409-appb-000015
上述数学表达式(2)具体为(以天线1为例)：
Figure PCTCN2018082409-appb-000016
Figure PCTCN2018082409-appb-000017
上述数学表达式(3)具体为(以天线1、2为例)：
Figure PCTCN2018082409-appb-000018
上述数学表达式(4)具体为(以天线1、2为例)：
Figure PCTCN2018082409-appb-000019
Figure PCTCN2018082409-appb-000020
结合互补序列对(a,b)与(a',b')数学特性可知，由于R a,a'(τ)+R b,b'(τ)＝0，R a,a(τ)+R b,b(τ)＝0，且R a,a'(τ)+R b,b'(τ)＝0,0≤|τ|＜L，L是互补序列对(a,b)、(a',b')中的序列a、b、a′、b′的长度。因此，上述示例中的等式结果均为0。也即是说，针对所述 4个天线上发射的训练序列满足前述条件(1)-(4)。也即是说，所述4个天线上发射的训练序列不存在ISI和MAI，不会对波束训练中的信道测量产生不利影响，利于进行准确的信道估计。需要说明的，上述示例仅仅用于解释本发明实施例，不应构成限定。
本申请中，当发射天线数量Nτ＝1时，天线发射的所述训练序列中，所述第一序列和所述第二序列可以分别是互补序列对(a,b)的a、b序列。这里，互补序列对(a,b)满足：R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L，L是互补序列对(a,b)、(a',b')中的序列a、b、a'、b'的长度。
本申请中，基于Golay互补序列对非周期自相关累加旁瓣为零，以及利用Golay互补序列进行信道估计具有信道估计实现简单的优良特性，可以选择Golay互补序列来构造本申请中的训练序列。也即是说，上述构造LS码的互补序列对(a,b)与(a′,b′)可以是Golay互补序列对。
具体的，假设待估计信道的最大时延扩展为T m，符号速率为R s。可以通过下述方式在Z H上产生长度为L的Golay互补序列对(a,b)，
Figure PCTCN2018082409-appb-000021
(m是正整数)：
Figure PCTCN2018082409-appb-000022
Figure PCTCN2018082409-appb-000023
或者
Figure PCTCN2018082409-appb-000024
其中，Z表示整数环，Z H表示元素个数为H的环，且当H为素数时为整环。π是{1,…,m}到自身的转换，c i∈Z H。长度
Figure PCTCN2018082409-appb-000025
即Golay互补序列对(a,b)中的a、b序列的长度和最大时延扩展为T m、符号速率为R s相关。
同样的，Golay互补序列对(a',b')也可以采用上述方式产生。(a,b)与(a',b')满足如下条件即可：R a,a'(τ)+R b,b'(τ)＝0。即这2个互补序列对的互相关之和为0。需要说明的，Golay互补序列对(a,b)与(a',b')的产生方式不限于上述方式，实际应用中还可以采用其他方式产生Golay互补序列对，本申请不作限制。
本申请中，为使802.11ay具有更好的兼容性，本申请以802.11ad标准中长度为128的Golay互补序列为基础，设计适用于802.11ay及未来标准的Golay互补序列对，用于构造训练序列。
图11A-11F示出了本申请提供的长度分别为128、256、512的Golay互补序列对。其中，2个长度为128的Golay互补序列对分别表示为(Ga128 1，Gb128 1)、(Ga128 2，Gb128 2)。2个长度为256的Golay互补序列对分别表示为(Ga256 1，Gb256 1)、(Ga256 2，Gb256 2)。2个长度为512的Golay互补序列对分别表示为(Ga512 1，Gb512 1)、(Ga512 2，Gb512 2)。
具体的，长度为1024和2048的Golay互补序列可以根据以上给出的短序列构成，具体如：
Ga1024 1＝[Ga512 1 Gb512 1] Gb10241＝[Ga512 1 -Gb512 1]
Ga1024 2＝[Ga512 2 Gb512 2] Gb10242＝[Ga512 2 -Gb512 2]
Ga2048 1＝[Ga1024 1 Gb1024 1] Gb20481＝[Ga1024 1 -Gb1024 1]
Ga2048 2＝[Ga1024 2 Gb10242 ] Gb20482＝[Ga1024 2 -Gb1024 2]
需要说明的，本申请构造训练序列所采用的互补序列对可以是图11A-11F示出的Golay互补序列对，也可以是现有标准定义的Golay互补序列对，还可以是满足互相关之和为0的其他形式的Golay互补序列对，这里不作限制
下面以Golay互补序列对为例，详细说明在不同信道条件(最大时延扩展和符号速率)下，本申请提供的针对几种天线配置的训练序列的实施例。
(1)第一种信道条件：信道最大时延扩展T m＝72ns，符号速率R s＝1.76Gbps。
首先，根据最大时延扩展T m和符号速率R s确定Golay互补序列的长度L为：
Figure PCTCN2018082409-appb-000026
然后，利用长度为128的Golay互补序列产生2个Golay互补序列对，具体表示为：(Ga128 1，Gb128 1)、(Ga128 2，Gb128 2)。
最后，利用长度为128的2个Golay互补序列对(Ga128 1，Gb128 1)、(Ga128 2，Gb128 2)构造出LS码，可参考图12A。
在上述第一种信道条件下，以下描述本申请提供的针对几种天线配置的训练序列的实施例。
实施例1：MIMO天线数量Nτ＝2(如2×2MIMO)
具体的，当天线数量Nτ＝2时，这2个天线分别发射的所述第一序列和所述第二序列可以分别取自第1(i＝log 2Nτ＝1)层LS码(图12A所示)的A部和B部。具体的，这2个天线发射的训练序列可如表1所示：
Figure PCTCN2018082409-appb-000027
表1
实施例2：MIMO天线数量Nτ＝4(如4×4MIMO)
具体的，当天线数量Nτ＝4时，这4个天线分别发射的所述第一序列和所述第二序列可以分别取自第2(i＝log 2Nτ＝2)层LS码(图12A所示)的A部和B部。具体的，这4个天线发射的训练序列可如表2所示：
Figure PCTCN2018082409-appb-000028
表2
实施例3：MIMO天线数量Nτ＝8(如8×8MIMO)
具体的，当天线数量Nτ＝8时，这8个天线分别发射的所述第一序列和所述第二序列可以分别取自第3(i＝log 2Nτ＝2)层LS码(图12A所示)的A部和B部。具体的，这8个天线发射的训练序列可如表3所示：
Figure PCTCN2018082409-appb-000029
表3
(2)第二种信道条件：信道最大时延扩展T m＝72ns，符号速率R s＝3.52Gbps。
首先，根据最大时延扩展T m和符号速率R s确定Golay互补序列的长度L为：
Figure PCTCN2018082409-appb-000030
然后，利用长度为256的Golay互补序列产生2个Golay互补序列对，具体表示为：(Ga256 1，Gb256 1)、(Ga256 2，Gb256 2)。
最后，利用长度为256的2个Golay互补序列对(Ga256 1，Gb256 1)、(Ga256 2，Gb256 2)构造出LS码，可参考图12B。
在上述第二种信道条件下，以下描述本申请提供的针对几种天线配置的训练序列的实施例。
实施例4：MIMO天线数量Nτ＝2(如2×2MIMO)
具体的，当天线数量Nτ＝2时，这2个天线分别发射的所述第一序列和所述第二序列可以分别取自第1(i＝log 2Nτ＝1)层LS码(图12B所示)的A部和B部。具体的，这2个天线发射的训练序列可如表4所示：
Figure PCTCN2018082409-appb-000031
表4
实施例5：MIMO天线数量Nτ＝4(如4×4MIMO)
具体的，当天线数量Nτ＝4时，这4个天线分别发射的所述第一序列和所述第二序列可以分别取自第2(i＝log2Nτ＝2)层LS码(图12B所示)的A部和B部。具体的，这4个 天线发射的训练序列可如表5所示：
Figure PCTCN2018082409-appb-000032
表5
实施例6：MIMO天线数量Nτ＝8(如8×8MIMO)
具体的，当天线数量Nτ＝8时，这8个天线分别发射的所述第一序列和所述第二序列可以分别取自第3(i＝log 2Nτ＝3)层LS码(图12B所示)的A部和B部。具体的，这8个天线发射的训练序列可如表6所示：
Figure PCTCN2018082409-appb-000033
表6
实施例7：MIMO天线数量Nτ＝1(如SISO)
参考前述内容可知，当发射天线数量Nτ＝1时，该天线发射的所述训练序列中，所述第一序列和所述第二序列可以分别是互补序列对(Ga256 1，Gb256 1)的Ga256 1,Gb256 1两部分，或者是互补序列对(Ga256 2，Gb256 2)的Ga256 2,Gb256 2两部分。即，该天线发射的训练序列可如表7A或7B所示：
Figure PCTCN2018082409-appb-000034
表7A
Figure PCTCN2018082409-appb-000035
表7B
(3)第三种信道条件：信道最大时延扩展T m＝72ns，符号速率R s＝5.28Gbps。
首先，根据最大时延扩展T m和符号速率R s确定Golay互补序列的长度L为：
Figure PCTCN2018082409-appb-000036
然后，利用长度为512的Golay互补序列产生2个Golay互补序列对，具体表示为：(Ga512 1，Gb512 1)、(Ga512 2，Gb512 2)。
最后，利用长度为512的2个Golay互补序列对(Ga512 1，Gb512 1)、(Ga512 2，Gb512 2)构造出LS码，可参考图12C。
在上述第三种信道条件下，以下描述本申请提供的针对几种天线配置的训练序列的实施例。
实施例8：MIMO天线数量Nτ＝2(如2×2MIMO)
具体的，当天线数量Nτ＝2时，这2个天线分别发射的所述第一序列和所述第二序列可以分别取自第1(i＝log 2Nτ＝1)层LS码(图12C所示)的A部和B部。具体的，这2个天线发射的训练序列可如表8所示：
Figure PCTCN2018082409-appb-000037
表8
实施例9：MIMO天线数量Nτ＝4(如4×4MIMO)
具体的，当天线数量Nτ＝4时，这4个天线分别发射的所述第一序列和所述第二序列可以分别取自第2(i＝log 2Nτ＝2)层LS码(图12C所示)的A部和B部。具体的，这4个天线发射的训练序列可如表9所示：
Figure PCTCN2018082409-appb-000038
表9
实施例10：MIMO天线数量Nτ＝8(如8×8MIMO)
具体的，当天线数量Nτ＝8时，这8个天线分别发射的所述第一序列和所述第二序列可以分别取自第3(i＝log 2Nτ＝8)层LS码(图12C所示)的A部和B部。具体的，这8个天线发射的训练序列可如表10所示：
Figure PCTCN2018082409-appb-000039
表10
实施例11：MIMO天线数量Nτ＝1(如SISO)
参考前述内容可知，当发射天线数量Nτ＝1时，该天线发射的所述训练序列中，所述第一序列和所述第二序列可以分别是互补序列对(Ga512 1，Gb512 1)的Ga512 1,Gb512 1两部分，或者是互补序列对(Ga512 2，Gb512 2)的Ga512 2,Gb512 2两部分。即，该天线发射的训练序列可如表11A或11B所示：
Figure PCTCN2018082409-appb-000040
表11A
Figure PCTCN2018082409-appb-000041
表11B
(4)第四种信道条件：信道最大时延扩展T m＝300ns，符号速率R s＝1.76Gbps。
首先，根据最大时延扩展T m和符号速率R s确定Golay互补序列的长度L为：
Figure PCTCN2018082409-appb-000042
然后，利用长度为512的Golay互补序列产生2个Golay互补序列对，具体表示为：(Ga512 1，Gb512 1)、(Ga512 2，Gb512 2)。
最后，利用长度为512的2个Golay互补序列对(Ga512 1，Gb512 1)、(Ga512 2，Gb512 2)构造出LS码，可参考图12C。
在上述第四种信道条件下，以下描述本申请提供的针对几种天线配置的训练序列的实施例。
实施例12：MIMO天线数量Nτ＝2(如2×2MIMO)
具体的，当天线数量Nτ＝2时，这2个天线分别发射的所述第一序列和所述第二序列可以分别取自第1(i＝log 2Nτ＝1)层LS码(图12C所示)的A部和B部。具体的，这2个天线发射的训练序列可如表12所示：
Figure PCTCN2018082409-appb-000043
表12
实施例13：MIMO天线数量Nτ＝4(如4×4MIMO)
具体的，当天线数量Nτ＝4时，这4个天线分别发射的所述第一序列和所述第二序列可以分别取自第2(i＝log 2Nτ＝2)层LS码(图12C所示)的A部和B部。具体的，这4个天线发射的训练序列可如表13所示：
Figure PCTCN2018082409-appb-000044
表13
实施例14：MIMO天线数量Nτ＝8(如8×8MIMO)
具体的，当天线数量Nτ＝8时，这8个天线分别发射的所述第一序列和所述第二序列可以分别取自第3(i＝log 2Nτ＝3)层LS码(图12C所示)的A部和B部。具体的，这8个天线发射的训练序列可如表14所示：
Figure PCTCN2018082409-appb-000045
表14
实施例15：MIMO天线数量Nτ＝1(如SISO)
参考前述内容可知，当发射天线数量Nτ＝1时，该天线发射的所述训练序列中，所述第一序列和所述第二序列可以分别是互补序列对(Ga512 1，Gb512 1)的Ga512 1,Gb512 1两部 分，或者是互补序列对(Ga512 2，Gb512 2)的Ga512 2,Gb512 2两部分。即，该天线发射的训练序列可如表15A或15B所示：
Figure PCTCN2018082409-appb-000046
表15A
Figure PCTCN2018082409-appb-000047
表15B
(5)第五种信道条件：信道最大时延扩展T m＝300ns，符号速率R s＝3.52Gbps。
首先，根据最大时延扩展T m和符号速率R s确定Golay互补序列的长度L为：
Figure PCTCN2018082409-appb-000048
然后，利用长度为1024的Golay互补序列产生2个Golay互补序列对，具体表示为：(Ga1024 1，Gb1024 1)、(Ga1024 2，Gb1024 2)。
最后，与利用较短的Golay互补序列对构造LS码的方式(参考图12A-12C)相同，可以利用长度为1024的2个Golay互补序列对(Ga1024 1，Gb1024 1)、(Ga1024 2，Gb1024 2)构造出LS码(未示出)。
在上述第五种信道条件下，以下描述本申请提供的针对几种天线配置的训练序列的实施例。
实施例16：MIMO天线数量Nτ＝2(如2×2MIMO)
具体的，当天线数量Nτ＝2时，这2个天线分别发射的所述第一序列和所述第二序列可以分别取自第1(i＝log 2Nτ＝1)层LS码的A部和B部。具体的，这2个天线发射的训练序列可如表16所示：
Figure PCTCN2018082409-appb-000049
表16
实施例17：MIMO天线数量Nτ＝4(如4×4MIMO)
具体的，当天线数量Nτ＝4时，这4个天线分别发射的所述第一序列和所述第二序列可以分别取自第2(i＝log 2Nτ＝2)层LS码的A部和B部。具体的，这4个天线发射的训练序列可如表17所示：
Figure PCTCN2018082409-appb-000050
表17
实施例18：MIMO天线数量Nτ＝8(如8×8MIMO)
具体的，当天线数量Nτ＝8时，这8个天线分别发射的所述第一序列和所述第二序列可以分别取自第3(i＝log 2Nτ＝3)层LS码的A部和B部。具体的，这8个天线发射的训练序列可如表18所示：
Figure PCTCN2018082409-appb-000051
表18
实施例19：MIMO天线数量Nτ＝1(如SISO)
参考前述内容可知，当发射天线数量Nτ＝1时，该天线发射的所述训练序列中，所述第一序列和所述第二序列可以分别是互补序列对(Ga1024 1，Gb1024 1)的Ga1024 1,Gb1024 1两部分，或者是互补序列对(Ga1024 2，Gb1024 2)的Ga1024 2,Gb1024 2两部分。即，该天线发射的训练序列可如表19A或19B所示：
Figure PCTCN2018082409-appb-000052
表19A
Figure PCTCN2018082409-appb-000053
表19B
(6)第六种信道条件：信道最大时延扩展T m＝300ns，符号速率R s＝5.28Gbps或7.04Gbps。
首先，根据最大时延扩展T m和符号速率R s确定Golay互补序列的长度L为：
Figure PCTCN2018082409-appb-000054
然后，利用长度为2048的Golay互补序列产生2个Golay互补序列对，具体表示为：(Ga2048 1，Gb2048 1)、(Ga2048 2，Gb2048 2)。
最后，与利用较短的Golay互补序列对构造LS码的方式(参考图12A-12C)相同，可以利用长度为2048的2个Golay互补序列对(Ga2048 1，Gb2048 1)、(Ga2048 2，Gb2048 2)构造出LS码(未示出)。
在上述第六种信道条件下，以下描述本申请提供的针对几种天线配置的训练序列的实施例。
实施例20：MIMO天线数量Nτ＝2(如2×2MIMO)
具体的，当天线数量Nτ＝2时，这2个天线分别发射的所述第一序列和所述第二序列可以分别取自第1(i＝log 2Nτ＝1)层LS码的A部和B部。具体的，这2个天线发射的训练序列可如表20所示：
Figure PCTCN2018082409-appb-000055
表20
实施例21：MIMO天线数量Nτ＝4(如4×4MIMO)
具体的，当天线数量Nτ＝4时，这4个天线分别发射的所述第一序列和所述第二序列可以分别取自第2(i＝log 2Nτ＝2)层LS码的A部和B部。具体的，这4个天线发射的训练序列可如表21所示：
Figure PCTCN2018082409-appb-000056
表21
实施例22：MIMO天线数量Nτ＝8(如8×8MIMO)
具体的，当天线数量Nτ＝8时，这8个天线分别发射的所述第一序列和所述第二序列可以分别取自第3(i＝log 2Nτ＝3)层LS码的A部和B部。具体的，这8个天线发射的训练序列可如表22所示：
Figure PCTCN2018082409-appb-000057
表22
实施例23：MIMO天线数量Nτ＝1(如SISO)
参考前述内容可知，当发射天线数量Nτ＝1时，该天线发射的所述训练序列中，所述第一序列和所述第二序列可以分别是互补序列对(Ga2048 1，Gb2048 1)的Ga2048 1,Gb2048 1两部分，或者是互补序列对(Ga2048 2，Gb2048 2)的Ga2048 2,Gb2048 2两部分。即，该天线发射的训练序列可如表23A或23B所示：
Figure PCTCN2018082409-appb-000058
表23A
Figure PCTCN2018082409-appb-000059
表23B
需要说明的，上述多个实施例详细说明了本申请在不同的信道条件、不同的天线配置下的具体实施方式。不限于上述多个实施例，本申请提供的发明原理以及图6实施例描述的总体方案还可以适用其他信道条件或其他天线配置情况，这里不作限制。
从上面内容可以看出，在不同的信道条件、不同的天线配置下，通过配置各个天线发射的训练序列使其满足上述条件(1)-(4)，不仅可以避免ISI和MSI对波束训练中的信道测量的不利影响，可满足不同应用场景下利用波束成形训练序列进行准确信道估计的需求，还可以降低对同步精度的要求。而且，通过在各个天线发射的训练序列中插入零序列，还可以简单化训练序列，减少信令开销。另外，利用Golay互补序列对来构造所述训练序列还可以简单化信道估计过程。
图13是本申请提供的无线通信系统、以及无线系统中的发射装置和接收装置的结构示意图。如图13所示，无线通信系统20包括第一通信装置400和第二通信装置500。可选的，第一通信装置400可以实现成图4所示的发射装置200，第二通信装置500可实现成图5所示的接收装置300。可选的，第一通信装置400或第二通信装置500也可以是图4所示的发 射装置200和图5所示的接收装置300结合实施得到的通信设备。下面分别展开描述。
如图13所示，第一通信装置400可包括处理单元403和发射单元401。其中：
处理单元403可用于配置Nτ(Nτ是正整数)天线各自对应的训练序列，使得配置给各个天线的训练序列满足前述条件(1)-(4)。关于前述条件(1)-(4)的具体内容可参考图6实施例，这里不再赘述。这里，每一个天线对应的训练序列均可包括M个长度相同的序列单元，M是整数。具体的，处理单元403还可用于将各个天线对应的训练序列分别封装在所述各个天线各自对应的用于波束优化的数据包中。这里，所述用于波束优化的数据包具体可以为波束优化协议(BRP)数据包。所述训练序列可以包含在BRP数据包中的波束训练字段TRN field中，具体可包含在T/R字段中，可参考IEEE 802.11ad协议，这里不赘述。
发射单元401可用于通过Nτ个天线发射所述用于波束优化的数据包。这样，第二通信装置500便可以接收到所述数据包，并从中获取到所述训练序列，基于所述训练序列进行信道估计。
进一步的，第一通信装置400还可包括接收单元，用于接收第二通信装置500返回的信道估计结果。然后，处理单元403可以根据所述信道估计结果调整天线配置。
可以理解的，关于第一通信装置400包括的各个功能单元的具体实现可参考前述方法实施例中关于所述发射端的内容，这里不再赘述。
如图13所示，第二通信装置500可包括接收单元501和处理单元503。其中：接收单元501可用于接收第一通信装置400通过Nτ个天线发射的所述用于波束优化的数据包，所述数据包均包含训练序列。处理单元503可用于解封装所述数据包，获取所述训练序列，并基于所述训练序列进行信道估计。
进一步的，第二通信装置500还可包括发射单元，用于将信道估计结果返回给第一通信装置400。这样，第一通信装置400便可以根据所述信道估计结果调整天线配置。
可以理解的，关于第二通信装置50包括的各个功能单元的具体实现可参考前述方法实施例中关于所述接收端的内容，这里不再赘述。
具体的，本申请所涉及的无线通信系统20可具体实现成图3所示的无线通信系统100，无线通信系统20可以是MIMO系统，Massive MIMO系统也可以是SIMO系统、MISO系统。无线通信系统20还可以是SISO系统。
综上，实施本发明实施例，在不同的信道条件、不同的天线配置下，通过配置各个天线发射的训练序列使其满足上述条件(1)-(4)，不仅可以避免ISI和MSI对波束训练中的信道测量的不利影响，可满足不同应用场景下利用波束成形训练序列进行准确信道估计的需求，还可以降低对同步精度的要求。而且，通过在各个天线发射的训练序列中插入零序列，还可以简单化训练序列，减少信令开销。另外，利用Golay互补序列对来构造所述训练序列还可以简单化信道估计过程。
本领域普通技术人员可以理解实现上述实施例方法中的全部或部分流程，该流程可以由计算机程序来指令相关的硬件完成，该程序可存储于计算机可读取存储介质中，该程序在执行时，可包括如上述各方法实施例的流程。而前述的存储介质包括：ROM或随机存储记忆体RAM、磁碟或者光盘等各种可存储程序代码的介质。

Claims (24)

  1. 一种信号传输方法，其特征在于，包括：
    通过Nτ个天线发射用于波束优化的数据包，Nτ是正整数，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零。
  2. 如权利要求1所述的方法，其特征在于，所述训练序列包括第一序列、第二序列，以及所述第一序列和所述第二序列的之间的第一零序列，其中，所述第一序列和所述第二序列的长度均为H个所述子序列，H是正整数，2*H＜M；所述零序列长度为Z1个所述子序列，Z1是正整数，Z1+2*H≤M。
  3. 如权利要求2所述的方法，其特征在于，当N τ≥2时，在所述N τ个天线各自发射的所述训练序列中，所述第一序列分别取自指定LS码的第i层中的A部中的多个序列，所述第二序列分别取自所述指定LS码的第i层中的B部中的多个序列；其中，
    Figure PCTCN2018082409-appb-100001
    所述指定LS码由2个互补序列对(a,b)与(a',b')构造，所述2个互补序列对满足：
    R a,a'(τ)+R b,b'(τ)＝0,0≤|τ|＜L
    R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L
    R a',a'(τ)+R b',b'(τ)＝0,0≤|τ|＜L
    其中，L是互补序列对(a,b)、(a',b')中的序列a、b、a'、b'的长度。
  4. 如权利要求2所述的方法，其特征在于，当N τ＝1时，天线发射的所述训练序列中，所述第一序列和所述第二序列分别是一对互补序列(a,b)的a、b序列，R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L，L是互补序列对(a,b)中a序列或b序列的长度。
  5. 如权利要求2-4中任一项所述的方法，其特征在于，所述M个数据块还包括第二零序列和第三零序列，其中，所述第二零序列插入在所述第一序列的前面，所述第三零序列插入在所述第二序列的后面；所述第二零序列、所述第三零序列的长度分别为Z2、Z3个所述子序列，Z1+Z2+Z3+2*H＝M。
  6. 一种信号传输方法，其特征在于，包括：
    接收N τ个用于波束优化的数据包，所述N τ个所述数据包是由发射端通过N τ个天线分别发送的，Nτ是正整数；其中，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零；
    利用所述数据包中的所述训练序列进行信道估计。
  7. 如权利要求6所述的方法，其特征在于，所述训练序列包括第一序列、第二序列，以及所述第一序列和所述第二序列的之间的第一零序列，其中，所述第一序列和所述第二序列的长度均为H个所述子序列，H是正整数，2*H＜M；所述零序列长度为Z1个所述子序列，Z1是正整数，Z1+2*H≤M。
  8. 如权利要求7所述的方法，其特征在于，当N τ≥2时，在所述N τ个天线各自发射的所述训练序列中，所述第一序列分别取自指定LS码的第i层中的A部中的多个序列，所述第二序列分别取自所述指定LS码的第i层中的B部中的多个序列；其中，
    Figure PCTCN2018082409-appb-100002
    所述指定LS码由2个互补序列对(a,b)与(a',b')构造，所述2个互补序列对满足：
    R a,a'(τ)+R b,b'(τ)＝0,0≤|τ|＜L
    R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L
    R a',a'(τ)+R b',b'(τ)＝0,0≤|τ|＜L
    其中，L是互补序列对(a,b)、(a',b')中的序列a、b、a'、b'的长度。
  9. 如权利要求7所述的方法，其特征在于，当N τ＝1时，天线发射的所述训练序列中，所述第一序列和所述第二序列分别是一对互补序列(a,b)的a、b序列，R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L，L是互补序列对(a,b)中a序列或b序列的长度。
  10. 如权利要求7-9中任一项所述的方法，其特征在于，所述M个数据块还包括第二零序列和第三零序列，其中，所述第二零序列插入在所述第一序列的前面，所述第三零序列插入在所述第二序列的后面；所述第二零序列、所述第三零序列的长度分别为Z2、Z3个所述子序列，Z1+Z2+Z3+2*H＝M。
  11. 一种通信装置，其特征在于，包括：处理单元和发射单元，其中：
    所述处理单元，用于配置Nτ个天线各自对应的用于波束优化的数据包，Nτ是正整数，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各 个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零；
    所述发射单元，用于通过所述Nτ个天线分别发射所述Nτ个天线各自对应的所述用于波束优化的数据包。
  12. 如权利要求11所述的通信装置，其特征在于，所述训练序列包括第一序列、第二序列，以及所述第一序列和所述第二序列的之间的第一零序列，其中，所述第一序列和所述第二序列的长度均为H个所述子序列，H是正整数，2*H＜M；所述零序列长度为Z1个所述子序列，Z1是正整数，Z1+2*H≤M。
  13. 如权利要求12所述的通信装置，其特征在于，当N τ≥2时，在所述N τ个天线各自发射的所述训练序列中，所述第一序列分别取自指定LS码的第i层中的A部中的多个序列，所述第二序列分别取自所述指定LS码的第i层中的B部中的多个序列；其中，
    Figure PCTCN2018082409-appb-100003
    所述指定LS码由2个互补序列对(a,b)与(a',b')构造，所述2个互补序列对满足：
    R a,a'(τ)+R b,b'(τ)＝0,0≤|τ|＜L
    R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L
    R a',a'(τ)+R b',b'(τ)＝0,0≤|τ|＜L
    其中，L是互补序列对(a,b)、(a',b')中的序列a、b、a'、b'的长度。
  14. 如权利要求12所述的通信装置，其特征在于，当N τ＝1时，天线发射的所述训练序列中，所述第一序列和所述第二序列分别是一对互补序列(a,b)的a、b序列，R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L，L是互补序列对(a,b)中a序列或b序列的长度。
  15. 如权利要求12-14中任一项所述的通信装置，其特征在于，所述M个数据块还包括第二零序列和第三零序列，其中，所述第二零序列插入在所述第一序列的前面，所述第三零序列插入在所述第二序列的后面；所述第二零序列、所述第三零序列的长度分别为Z2、Z3个所述子序列，Z1+Z2+Z3+2*H＝M。
  16. 一种通信装置，其特征在于，包括：处理单元和接收单元，其中：
    所述接收单元，用于接收N τ个用于波束优化的数据包，所述N τ个所述数据包是由发射端通过N τ个天线分别发送的，Nτ是正整数；其中，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零；
    所述处理单元，用于利用所述数据包中的所述训练序列进行信道估计。
  17. 如权利要求16所述的通信装置，其特征在于，所述训练序列包括第一序列、第二序列，以及所述第一序列和所述第二序列的之间的第一零序列，其中，所述第一序列和所述第二序列的长度均为H个所述子序列，H是正整数，2*H＜M；所述零序列长度为Z1个所述子序列，Z1是正整数，Z1+2*H≤M。
  18. 如权利要求17所述的通信装置，其特征在于，当N τ≥2时，在所述N τ个天线各自发射的所述训练序列中，所述第一序列分别取自指定LS码的第i层中的A部中的多个序列，所述第二序列分别取自所述指定LS码的第i层中的B部中的多个序列；其中，
    Figure PCTCN2018082409-appb-100004
    所述指定LS码由2个互补序列对(a,b)与(a',b')构造，所述2个互补序列对满足：
    R a,a'(τ)+R b,b'(τ)＝0,0≤|τ|＜L
    R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L
    R a',a'(τ)+R b',b'(τ)＝0,0≤|τ|＜L
    其中，L是互补序列对(a,b)、(a',b')中的序列a、b、a'、b'的长度。
  19. 如权利要求17所述的通信装置，其特征在于，当N τ＝1时，天线发射的所述训练序列中，所述第一序列和所述第二序列分别是一对互补序列(a,b)的a、b序列，R a,a(τ)+R b,b(τ)＝0,0≤|τ|＜L，L是互补序列对(a,b)中a序列或b序列的长度。
  20. 如权利要求17-19中任一项所述的通信装置，其特征在于，所述M个数据块还包括第二零序列和第三零序列，其中，所述第二零序列插入在所述第一序列的前面，所述第三零序列插入在所述第二序列的后面；所述第二零序列、所述第三零序列的长度分别为Z2、Z3个所述子序列，Z1+Z2+Z3+2*H＝M。
  21. 一种通信装置，其特征在于，包括：发射器、存储器以及耦合于所述存储器的处理器，其中：
    所述发射器用于通过Nτ个天线发射用于波束优化的数据包，Nτ是正整数，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零。
  22. 一种通信装置，其特征在于，包括：接收器、存储器以及耦合于所述存储器的处理器，其中：
    所述接收器用于接收N τ个用于波束优化的数据包，所述N τ个所述数据包是由发射端 通过N τ个天线分别发送的，Nτ是正整数；其中，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零；
    所述处理器用于利用所述数据包中的所述训练序列进行信道估计。
  23. 一种通信系统，其特征在于，包括：第一通信装置和第二通信装置，其中：所述第一通信装置用于通过Nτ个天线发射用于波束优化的数据包，每一个天线发射的所述数据包均包括所述天线发射的用于信道估计的训练序列；所述第二通信装置用于接收所述N τ个用于波束优化的数据包，并利用所述数据包中的所述训练序列进行信道估计；
    其中，Nτ是正整数；各个天线发射的所述训练序列包括M个长度相同的子序列，M是正整数；其中：同一个天线发射的训练序列中，各个数据块的自相关之和为零，全部的两个相邻数据块之间的互相关之和为零；任意2个天线分别发射的训练序列中，全部的对应相同序列号的两个数据块之间的互相关之和为零，全部的对应相邻序列号的两个数据块之间的互相关之和为零。
  24. 如权利要求23所述的通信系统，其特征在于，所述第一通信装置是权利要求12-15中任一项所述的通信装置，所述第二通信装置是权利要求17-20中任一项所述的通信装置。
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